LINER LT1351 90mhz, 2200v/î¼s 30v low power op amp Datasheet

LT6274/LT6275
90MHz, 2200V/µs
30V Low Power Op Amps
FEATURES
DESCRIPTION
2200V/μs Slew Rate
nn 90MHz –3dB Bandwidth (A = +1)
V
nn 40MHz Gain-Bandwidth Product
nn 1.6mA Supply Current per Amplifier
nn C-Load™ Op Amp Drives All Capacitive Loads
nn ±4.5V to ±16V Operating Supply Range
nn Unity-Gain Stable
nn 10nV/√Hz Input Noise Voltage
nn 400µV Maximum Input Offset Voltage
nn 500nA Maximum Input Bias Current
nn 30nA Maximum Input Offset Current
nn ±13.25V Minimum Output Swing into 1k (±15V Supply)
nn ±3.5V Minimum Output Swing into 500Ω (±5V Supply)
nn 74dB Minimum Open-Loop Gain, R = 1k
L
nn 40ns Settling Time to 1%, 10V Step
nn Specified at ±5V and ±15V
nn Single in 5-Lead TSOT-23 Package
nn Dual in 8-Lead MSOP Package
The LT®6274/LT6275 are single/dual low power, high
speed, very high slew rate operational amplifiers with
outstanding AC and DC performance. The circuit topology
is a voltage feedback amplifier with matched high impedance inputs plus the enhanced slewing performance of a
current feedback amplifier. The high slew rate and single
stage design provide excellent settling characteristics that
make the circuit an ideal choice for data acquisition systems. Each output drives a 1k load to ±13.25V with ±15V
supplies and a 500Ω load to ±3.5V on ±5V supplies. The
LT6274/LT6275 are stable with any capacitive load making them useful in buffer or cable driving applications.
nn
APPLICATIONS
The LT6274 single op amp is available in a 5-lead TSOT‑23
package, and the LT6275 dual op amp is available in an
8-lead MSOP package. They operate with guaranteed
specifications over the –40°C to 85°C and –40°C to 125°C
temperature ranges.
All registered trademarks and trademarks are the property of their respective owners. All other
trademarks are the property of their respective owners.
Wideband Large Signal Amplification
Cable Drivers
nn Buffers
nn Automated Test Equipment
nn Data Acquisition Systems
nn High Fidelity Video and Audio Amplification
nn
nn
TYPICAL APPLICATION
Undistorted Output Swing vs Frequency
30
Wideband Large Signal Amplification
+
10V
VIN
–10V
1k
10V
LT6274
VOUT
–
–10V
–15V
1k
AV = –1
FPBW = 3MHz
6275 TA01
OUTPUT VOLTAGE (VP-P)
25
15V
AV = –1
20
15
10
AV = –10
AV = +1
5 VS = ±15V
RL = 1k
1% MAX DISTORTION
0
100k
1M
10M
FREQUENCY (Hz)
100M
6275 G31
6275fa
For more information www.linear.com/LT6275
1
LT6274/LT6275
ABSOLUTE MAXIMUM RATINGS
(Note 1)
Total Supply Voltage
(V+ – V–)....................................................................34V
Differential Input Voltage
(Transient Only) (Note 2)......................................... ±10V
Input Voltage....................................................... V– to V+
Input Current
(+IN, –IN) (Note 3)................................................ ±10mA
Output Current (Note 12)................................115mARMS
Output Short-Circuit Current Duration
(Note 4)...........................................Thermally Limited
Operating Temperature Range (Note 5)
LT6274I/LT6275I...................................–40°C to 85°C
LT6274H/LT6275H.............................. –40°C to 125°C
Specified Temperature Range (Note 6)
LT6274I/LT6275I...................................–40°C to 85°C
LT6274H/LT6275H.............................. –40°C to 125°C
Maximum Junction Temperature........................... 150°C
Storage Temperature Range................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................... 300°C
PIN CONFIGURATION
TOP VIEW
–
+
OUTA
–INA
+INA
V–
+IN 3
4 –IN
–
+
8
7
6
5
V+
OUTB
–INB
+INB
MS8 PACKAGE
8-LEAD PLASTIC MSOP
TJMAX = 150°C, qJA = 163°C/W
S5 PACKAGE
5-LEAD PLASTIC TSOT-23
θJA = 215°C/W
ORDER INFORMATION
1
2
3
4
+
–
V– 2
TOP VIEW
5 V+
OUT 1
http://www.linear.com/product/LT6275#orderinfo
TUBE
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
SPECIFIED TEMPERATURE RANGE
LT6274IS5#PBF
LT6274IS5 #TRPBF
LTHCY
5-Lead Plastic TSOT-23
–40°C to 85°C
LT6274HS5#PBF
LT6274HS5 #TRPBF
LTHCY
5-Lead Plastic TSOT-23
–40°C to 125°C
LT6275IMS8#PBF
LT6275IMS8 #TRPBF
LTFYV
8-Lead Plastic MSOP
–40°C to 85°C
LT6275HMS8#PBF
LT6275HMS8 #TRPBF
LTFYV
8-Lead Plastic MSOP
–40°C to 125°C
*The temperature grade is identified by a label on the shipping container.
Consult LTC Marketing for parts specified with wider operating temperature ranges. Parts ending with PBF are RoHS and WEEE compliant.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through
designated sales channels with #TRMPBF suffix.
2
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. Unless noted otherwise, VCM = 0V, and specifications apply at both
VS = (V+ – V–) = ±5V and ±15V.
SYMBOL PARAMETER
VOS
CONDITIONS
MIN
Input Offset Voltage (Note 7)
TYP
MAX
UNITS
±0.15
±0.4
±1.2
mV
mV
±4
±10
µV/°C
±100
±500
±1000
nA
nA
±3
±30
±50
nA
nA
l
∆VOS/∆T
Input Offset Voltage Drift (Note 8)
IB
Input Bias Current
l
l
IOS
Input Offset Current
l
en
Input Voltage Noise Density
Low Frequency Integrated Voltage Noise
1/f
1/f Noise Corner Frequency
f = 1kHz
10
nV/√Hz
0.1Hz to 10Hz
1
µVP-P
Voltage Noise
Current Noise
30
70
Hz
Hz
in
Input Current Noise Density
f = 1kHz
RIN
Input Resistance
Common Mode, VCM = ±12V, VS = ±15V
Differential Mode
CIN
Input Capacitance
Common Mode
Differential Mode
VINCM
Input Voltage Range + (Note 9)
VS = ±15V
VS = ±5V
l
l
Input Voltage Range – (Note 9)
VS = ±15V
VS = ±5V
l
l
CMRR
Common Mode Rejection Ratio
VS = ±15V, VCM = ±12V
VS = ±5V, VCM = ±2.5V
l
l
90
80
110
102
PSRR
Power Supply Rejection Ratio
VS = ±4.5V to ±16V
l
90
115
VS
Supply Voltage Range (Note 10)
l
9
l
100
12
2.5
0.5
pA/√Hz
700
20
MΩ
MΩ
3
0.4
pF
pF
13.4
3.4
V
V
–13.2
–3.2
–12
–2.5
V
V
dB
dB
dB
32
V
Channel Separation
VS = ±15V, VOUT = ±1V, AV = 1, RL = 1kΩ
l
100
126
dB
AVOL
Open-Loop Voltage Gain
VS = ±15V, VOUT = ±12V, RL = 1kΩ
VS = ±5V, VOUT = ±2.5V, RL = 500Ω
l
l
74
68
90
84
dB
dB
VOUT
Maximum Output Voltage Swing
±40mV Input Overdrive
VS = ±15V, RL = 1kΩ
VS = ±5V, RL = 500Ω
l
l
±13.25
±3.5
±13.5
±3.8
V
V
IOUT
Output Current
VS = ±15V, VOUT = ±12V, VIN = ±40mV
VS = ±5V, VOUT = ±2.5V, VIN = ±40mV
l
l
±15
±12
±35
±30
mA
mA
ISC
Output Short-Circuit Current
VS = ±15V, VOUT = 0V, VIN = ±3V
VS = ±5V, VOUT = 0V, VIN = ±3V
l
l
±35
±30
±90
±80
mA
mA
IS
Supply Current
Per Amplifier, VS = ±15V
1.6
l
SR
Slew Rate (Note 11)
VS = ±15V, AV = 1
VS = ±15V, AV = –1
VS = ±15V, AV = –2
VS = ±5V, AV = –2
FPBW
Full Power Bandwidth
VS = ±15V, 10V Peak, AV = –1, <1% THD
VS = ±5V, 1V Peak, AV = –1, <1% THD
GBW
Gain-Bandwidth Product
fTEST = 200kHz
VS = ±15V
VS = ±5V
f–3dB
Unity Gain –3dB Bandwidth
VOUT = 100mVP-P, VS = ±15V
l
l
l
l
900
270
28
25
1.7
2.3
mA
mA
2200
1600
1250
400
V/µs
V/µs
V/µs
V/µs
3
8
MHz
MHz
40
36
MHz
MHz
90
MHz
6275fa
For more information www.linear.com/LT6275
3
LT6274/LT6275
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. Unless noted otherwise, VCM = 0V, and specifications apply at both
VS = (V+ – V–) = ±5V and ±15V.
SYMBOL PARAMETER
CONDITIONS
tR, tF
Small Signal Rise/Fall Time
AV = 1, 10% – 90%, 100mV Input Step
4
ns
tPD
Propagation Delay
50% VIN to 50% VOUT, 100mV Input Step
4
ns
ts
Settling Time
1% of 10V Step, AV = 1, VS = ±15V
0.1% of 10V Step, AV = 1, VS = ±15V
1% of 5V Step, AV = 1, VS = ±5V
40
185
65
ns
ns
ns
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: Differential inputs of ±10V are appropriate for transient operation
only, such as during slewing. Large, sustained differential inputs will
cause excessive power dissipation and may damage the part. See Input
Considerations in the Applications Information section of this data sheet
for more details.
Note 3: The inputs are protected by ESD protection diodes to each power
supply. The Input current should be limited to less than 10mA.
Note 4: A heat sink may be required to keep the junction temperature
below the absolute maximum rating when the output is shorted
indefinitely.
Note 5: The LT6274I/LT6275I are guaranteed functional over the
operating temperature range of –40°C to 85°C. The LT6274H/LT6275H
are guaranteed functional over the operating temperature range of
–40°C to 125°C.
4
MIN
TYP
MAX
UNITS
Note 6: The LT6274I/LT6275I are guaranteed to meet specified
performance from –40°C to 85°C. The LT6274H/LT6275H are guaranteed
to meet specified performance from –40°C to 125°C.
Note 7: Input offset voltage is pulse tested and is exclusive of warm-up drift.
Note 8: This parameter is not 100% tested.
Note 9: Input voltage range is guaranteed by common mode rejection ratio
test.
Note 10: Supply voltage range is guaranteed by power supply rejection
ratio test.
Note 11: Slew rate is measured between 20% and 80% of output step with
±6V input (at AV = –2) and ±10V input (at AV = ±1) for ±15V supplies, and
between 35% and 65% of output step with ±1.75V input (at AV = –2) for
±5V supplies.
Note 12: Current density limitations within the IC require the continuous
RMS current supplied by the output (sourcing or sinking) over the
operating lifetime of the part be limited to under 115mA (Absolute
Maximum). Proper heat sinking may be required to keep the junction
temperature below the absolute maximum rating.
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Input Offset Voltage vs Input
Common Mode Voltage
200
35
2.5
100
30
25°C
1.5
–40°C
1.0
0.5
0
25°C
–100
–200
–300
125°C
0
5
10
15
20
25
30
TOTAL SUPPLY VOLTAGE (V)
–500
–15
35
VS = ±15V
–10
–5
0
5
10
INPUT COMMON MODE VOLTAGE (V)
6275 G01
100
300
–100
25°C
–200
–300
125°C
–10
–5
0
5
10
INPUT COMMON MODE VOLTAGE (V)
0
–100
–200
15
80
75
–400
–50
–25
0
25
50
75
TEMPERATURE (°C)
100
70
–50
125
75
6275 G07
0
25
50
75
TEMPERATURE (°C)
16
VS = ±15V
90
VS = ±5V
85
80
75
70
60
125
6275 G06
100
TA = 25°C
95 VOUT = ±100mV
100
Output Voltage Swing
vs Resistive Load
65
125
–25
6275 G05
OPEN-LOOP GAIN (dB)
80
100
VS = ±15V
VOUT = ±12V
RL = 1k
85
Open-Loop Gain
vs Resistive Load
85
0
25
50
75
TEMPERATURE (°C)
10
Open-Loop Gain vs Temperature
90
100
VS = ±5V
VOUT = ±2.5V
RL = 500Ω
–25
1 2 3 4 5 6 7 8 9
INPUT OFFSET VOLTAGE DRIFT (µV/°C)
6275 G03
VS = ±15V
200
Open-Loop Gain vs Temperature
70
–50
0
95
6275 G04
90
10
–300
VS = ±15V
95
15
0
15
OPEN-LOOP GAIN (dB)
–40°C
INPUT BIAS CURRENT (nA)
INPUT BIAS CURRENT (nA)
400
–500
–15
20
Input Bias Current vs Temperature
200
–400
25
6275 G02
Input Bias Current
vs Input Common Mode Voltage
0
VS = ±15V
36 UNITS
5
–400
OUTPUT VOLTAGE SWING (±V)
0
–40°C
PERCENTAGE OF UNITS (%)
125°C
2.0
OPEN-LOOP GAIN (dB)
Typical Distribution of Input
Offset Voltage Drift
3.0
INPUT OFFSET VOLTAGE (µV)
SUPPLY CURRENT (mA)
Supply Current vs Supply Voltage
and Temperature (per Amplifier)
VS = ±15V
14 VIN = ±20mV
TA = 25°C
12
10
8
6
4
2
10
100
1k
10k
100k
LOAD RESISTANCE (Ω)
1M
6275 G08
0
10
100
1k
10k
LOAD RESISTANCE (Ω)
100k
6275 G09
6275fa
For more information www.linear.com/LT6275
5
LT6274/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Output Voltage Swing
vs Supply Voltage
V+
VS = ±5V
4.0 VIN = ±20mV
TA = 25°C
3.5
3.0
2.5
2.0
1.5
1.0
3
RL = 500Ω
2
0
–
V
100k
RL = 500Ω
–3
1
100
1k
10k
LOAD RESISTANCE (Ω)
0
5
10
15
20
25
30
TOTAL SUPPLY VOLTAGE (V)
OUTPUT SHORT-CIRCUIT CURRENT (mA)
OUTPUT VOLTAGE SWING (V)
125°C
125°C
–40°C
–40°C
2
1
SINK
100
V–
–50 –40 –30 –20 –10 0 10 20 30 40 50
OUTPUT CURRENT (mA)
90
70
–25
0
25
50
75
TEMPERATURE (°C)
1
100
1k
FREQUENCY (Hz)
10k
SOURCE
90
80
SINK
70
60
–25
0
25
50
75
TEMPERATURE (°C)
0.1
100k
125
Settling Time vs Output Step
VS = ±15V
AV = 1
RL = 2k
SETTLING TIME (ns)
200
0.1%
150
100
1%
50
TIME (1s/DIV)
100
6275 G15
250
6275 G17
0
2
4
6
8
OUTPUT STEP (V)
10
6275 G18
6275 G16
6
VS = ±5V
VIN = ±3V
50
–50
125
INPUT VOLTAGE NOISE (200nV/DIV)
INPUT VOLTAGE NOISE (nV/√Hz)
1
10
100
100
VS = ±15V
INPUT CURRENT NOISE (pA/√Hz)
10
en
1
6275 G12
6275 G14
100
in
–40°C
2
0.1Hz to 10Hz
Input Voltage Noise
100
10
VS = ±15V
VIN = ±3V
80
60
–50
Input Noise Spectral Density
VS = ±15V
–40°C
125°C
3
Output Short-Circuit Current
vs Temperature
SOURCE
6275 G13
1k
125°C
25°C
V–
–50 –40 –30 –20 –10 0 10 20 30 40 50
OUTPUT CURRENT (mA)
35
OUTPUT SHORT-CIRCUIT CURRENT (mA)
110
25°C
–2
3
–3
Output Short-Circuit Current
vs Temperature
V+
25°C
–2
6275 G11
Output Voltage Swing
vs Load Current
VS = ±5V
–1 VIN = ±20mV
25°C
1
RL = 1k
6275 G10
–3
VS = ±15V
–1 VIN = ±20mV
RL = 1k
–2
0.5
10
V+
TA = ±25°C
VIN = ±20mV
–1
OUTPUT VOLTAGE SWING (V)
OUTPUT VOLTAGE SWING (±V)
4.5
Output Voltage Swing
vs Load Current
OUTPUT VOLTAGE SWING (V)
Output Voltage Swing
vs Resistive Load
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Closed-Loop Output Impedance
vs Frequency
70
100
PHASE
60
GAIN (dB)
40
–120
GAIN
30
–150
20
10
1k
–180
–10
10k 100k
1M
FREQUENCY (Hz)
10M
–20
10k
100M
100k
1M
10M
FREQUENCY (Hz)
6275 G20
50
45
45
GAIN-BANDWIDTH PRODUCT
40
0
5
C=0
–10
10
15
20
25
30
TOTAL SUPPLY VOLTAGE (V)
35
–20
100k
30
POWER SUPPLY REJECTION RATIO (dB)
CROSSTALK (dB)
–80
–90
VS = ±5V
RL = 500Ω
VS = ±15V
RL = 1k
100k
1M
10M
FREQUENCY (Hz)
100M
6275 G26
0
25
50
75
TEMPERATURE (°C)
100
1M
10M
100M
FREQUENCY (Hz)
C = 5nF C = 1nF
C = 500pF
C = 100pF
C = 50pF
0
C=0
–10
–20
100k
1G
VS = ±15V
TA = 25°C
100
–PSRR
80
60
+PSRR
40
20
0
–20
100
1k
30
125
VS = ±5V
TA = 25°C
AV = 1
120
TA = 25°C
–60 AV = 1
VIN = 2VP–P
–70
–130
10k
–25
C = 10nF
1M
10M
100M
FREQUENCY (Hz)
10k 100k
1M
FREQUENCY (Hz)
10M
100M
6275 G27
1G
6275 G25
Power Supply Rejection Ratio
vs Frequency
–50
–120
35
GAIN-BANDWIDTH PRODUCT
VS = ±5V
6275 G24
Crosstalk vs Frequency
–110
35
40
Closed-Loop Frequency
Response vs Load Capacitance
VS = ±15V
TA = 25°C
AV = 1
6275 G23
–100
40
10
C = 50pF
0
35
35
45
6275 G22
C = 500pF
C = 10nF
50
GAIN-BANDWIDTH PRODUCT
VS = ±15V
C = 100pF
GAIN MAGNITUDE (dB)
50
30
C = 5nF C = 1nF
55
PHASE MARGIN
40
10
60
PHASE MARGIN (DEG)
GAIN-BANDWIDTH PRODUCT (MHz)
55
45
Closed-Loop Frequency
Response vs Load Capacitance
TA = 25°C
55
PHASE MARGIN
VS = ±5V
50
6275 G21
Gain-Bandwidth Product
and Phase Margin
vs Supply Voltage
60
55
30
–50
–210
1G
100M
GAIN MAGNITUDE (dB)
0.01
100
VS = ±5V
0
AV = 1
Common Mode Rejection Ratio
vs Frequency
120
COMMON MODE REJECTION RATIO (dB)
0.1 A = 10
V
60
PHASE MARGIN
VS = ±15V
PHASE MARGIN (DEG)
AV = 100
1
–90
VS = ±15V
50
10
60
–60
TA = 25°C
GAIN-BANDWIDTH PRODUCT (MHz)
80
VS = ±15V
TA = 25°C
PHASE (DEG)
OUTPUT IMPEDANCE (Ω)
1k
Gain-Bandwidth Product and
Phase Margin vs Temperature
Gain/Phase vs Frequency
VS = ±15V
TA = 25°C
100
80
60
40
20
0
100
1k
10k 100k
1M
FREQUENCY (Hz)
10M
100M
6275 G28
6275fa
For more information www.linear.com/LT6275
7
LT6274/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
2nd and 3rd Harmonic Distortion
vs Frequency (AV = 1)
–50
–60
–70
–80
3RD HARMONIC
–90
–100
–110
–120
2ND HARMONIC
1k
10k
100k
FREQUENCY (Hz)
1M
25
–50
–60
–70
–80
3RD HARMONIC
–90
–100
–110
2ND HARMONIC
–120
–140
100
10M
1k
10k
100k
FREQUENCY (Hz)
1M
Undistorted Output Swing
vs Frequency
SLEW RATE (V/µs)
OUTPUT VOLTAGE (VP-P)
TA = 25°C
AV = –1
RG = RF = 2k
2000 20%
to 80% OF STEP
AV = –10
AV = –1
4
2
10M
1M
10M
FREQUENCY (Hz)
100M
OUTPUT FALLING
VS = ±15V
1000
OUTPUT RISING
VS = ±15V
0
0
2
4
OUTPUT FALLING
VS = ±15V
±12V OUTPUT STEP
OUTPUT RISING
VS = ±15V
±12V OUTPUT STEP
1000
0
–50
6 8 10 12 14 16 18 20
INPUT LEVEL (VP-P)
VS = ±5V
±3.5V OUTPUT STEP
–25
0
25
50
75
TEMPERATURE (°C)
6275 G33
100
125
6275 G34
Step Response Overshoot
vs Capacitive Load
80
70
1000
VS = ±15V
100mV STEP
60
OVERSHOOT (%)
SLEW RATE (V/µs)
AV = –2
RG = 2k, RF = 4k
20% to 80% OF STEP
1500
VS = ±5V
10000
100
10
10p
AV = 1
40
30
20
VS = ±15V
AV = –1
RG = RF = 2k
20% to 80% of ±10V STEP
1p
50
AV = –1
RG = RF = 2k
10
100p
1n
10n 100n
LOAD CAPACITANCE (F)
1µ
0
10p
6275 G35
8
100M
500
Slew Rate vs Capacitive Load
0.1
2000
1500
6275 G32
1
AV = +1
Slew Rate vs Temperature
2500
500
VS = ±5V
RL = 1k
1% MAX DISTORTION
0
100k
10
6275 G31
2500
AV = +1
AV = –10
15
Slew Rate vs Input Level
10
6
20
6275 G30
6275 G29
8
AV = –1
5 VS = ±15V
RL = 1k
1% MAX DISTORTION
0
100k
1M
10M
FREQUENCY (Hz)
–130
–130
–140
100
30
V = ±15V
–30 VS = 10V
IN
P–P
–40 RG = RF = 1k
OUTPUT VOLTAGE (VP-P)
–40
–20
VS = ±15V
VIN = 10VP–P
RL = 1k
SLEW RATE (V/µs)
HARMONIC DISTORTION (dBc)
–30
HARMONIC DISTORTION (dBc)
–20
Undistorted Output Swing
vs Frequency
2nd and 3rd Harmonic Distortion
vs Frequency (AV = –1)
100p
1n
10n
100n
LOAD CAPACITANCE (F)
1µ
6275 G36
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Small-Signal Step Response
(AV = 1)
Small-Signal Step Response
(AV = –1)
VS = ±15V
Small-Signal Step Response
(AV = 1, CL = 10nF)
VS = ±15V
20mV/DIV
20mV/DIV
20mV/DIV
VS = ±15V
RG = RF = 2k
20ns/DIV
500ns/DIV
20ns/DIV
6275 G37
6275 G39
6275 G38
Large-Signal Step Response
(AV = 1)
Large-Signal Step Response
(AV = –1)
Large-Signal Step Response
(AV = 1, CL = 10nF)
VS = ±15V
RG = RF =2k
5V/DIV
5V/DIV
VS = ±15V
5V/DIV
VS = ±15V
50ns/DIV
50ns/DIV
6275 G40
5µs/DIV
6275 G41
6275 G42
6275fa
For more information www.linear.com/LT6275
9
LT6274/LT6275
SIMPLIFIED SCHEMATIC
(ONE AMPLIFIER SHOWN)
V+
–IN
R1
1k
+IN
RC
C
V–
10
OUT
CC
6275 SS01
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
PIN FUNCTIONS
V –: Negative Supply Voltage. Total supply voltage
(V+ – V–) ranges from 9V to 32V.
–IN: Inverting Input of Amplifier.
+IN: Noninverting Input of Amplifier.
V+: Positive Supply Voltage. Total supply voltage (V+ – V–)
ranges from 9V to 32V.
OUT: Amplifier Output.
6275fa
For more information www.linear.com/LT6275
11
LT6274/LT6275
APPLICATIONS INFORMATION
Circuit Operation
Comparison to Current Feedback Amplifiers
The LT6274/LT6275 circuit topology is a true voltage
feedback amplifier that has the slewing behavior of a current feedback amplifier. The operation of the circuit can
be understood by referring to the simplified schematic.
The inputs are buffered by complementary NPN and PNP
emitter followers that drive a 1k resistor. The input voltage
appears across the resistor generating currents that are
mirrored into the high impedance node. Complementary
followers form an output stage that buffers the gain node
from the load. The bandwidth is set by the internal input
resistor and the capacitance on the high impedance node.
The slew rate is determined by the current available to
charge the gain node capacitance. This current is the differential input voltage divided by R1, so the slew rate is
proportional to the input. This important characteristic
gives the LT6274/LT6275 superior slew performance
compared to conventional voltage feedback amplifiers in
which the slew rate is constrained by a fixed current (biasing the input transistors) available to charge the gain node
capacitance (independent of the magnitude of the differential input voltage). Therefore, in the LT6274/LT6275, highest slew rates are seen in the lowest gain configurations.
For example, a 10V output step in a gain of 10 has only a
1V input step, whereas the same output step in unity gain
has a 10 times greater input step. The curve of Slew Rate
vs Input Level illustrates this relationship. The LT6274/
LT6275 are tested in production for slew rate in a gain of
–2 so higher slew rates can be expected in gains of 1 and
–1, with lower slew rates in higher gain configurations.
The LT6274/LT6275 enjoy the high slew rates of Current
Feedback Amplifiers (CFAs) while maintaining the characteristics of a true voltage feedback amplifier. The primary differences are that the LT6274/LT6275 have two
high impedance inputs, and the closed loop bandwidth
decreases as the gain increases. CFAs have a low impedance inverting input and maintain relatively constant
bandwidth with increasing gain. The LT6274/LT6275 can
be used in all traditional op amp configurations including
integrators and applications such as photodiode amplifiers and I-to-V converters where there may be significant
capacitance on the inverting input. The frequency compensation is internal and does not depend on the value
of the external feedback resistor. For CFAs, by contrast,
the feedback resistance is fixed for a given bandwidth,
and capacitance on the inverting input can cause peaking
or oscillations. The slew rate of the LT6274/LT6275 in
noninverting gain configurations is also superior to that
of CFAs in most cases.
Special compensation across the output buffer allows the
LT6274/LT6275 to be stable with any capacitive load. The
RC network across the output stage is bootstrapped when
the amplifier is driving a light or moderate load and has
no effect under normal operation. When driving a capacitive load (or a low value resistive load) the network is
incompletely bootstrapped and adds to the compensation at the high impedance node. The added capacitance
slows down the amplifier by lowering the dominant pole
frequency, improving the phase margin. The zero created
by the RC combination adds phase to ensure that even
for very large load capacitances, the total phase lag does
not exceed 180° (zero phase margin), and the amplifier
remains stable.
12
Input Considerations
Each of the LT6274/LT6275 inputs is the base of an NPN
and a PNP transistor whose base currents are of opposite
polarity and provide first-order input bias current cancellation. Because of differences between NPN and PNP beta,
the polarity of the input bias current can be positive or
negative. The offset current does not depend on NPN/PNP
beta matching and is well controlled. The use of balanced
source resistance at each input is therefore recommended
for applications where DC accuracy must be maximized.
The inputs can withstand transient differential input voltages up to ±10V without damage and need no clamping
or source resistance for protection. Differential inputs,
however, generate large supply currents (tens of mA) as
required for high slew rates. If the device is used with
sustained differential inputs, the average supply current
will increase, excessive power dissipation will result, and
the part may be damaged. The part should not be used
as a comparator, peak detector or in other open-loop
applications with large, sustained differential inputs.
Under normal, closed-loop operation, an increase of
power dissipation is only noticeable in applications with
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
APPLICATIONS INFORMATION
large slewing outputs, and the increased power is proportional to the magnitude of the differential input voltage and
the percent of the time that the inputs are apart. Measure
the average supply current for the application in order to
calculate the power dissipation.
combination of the feedback resistor and gain setting
resistor on the inverting input combines with the total
capacitance on that node, CIN, to form a pole which can
cause peaking or oscillations. If feedback resistors greater
than 5k are used, a parallel capacitor of value
CF > RG × CIN/RF
Capacitive Loading
The LT6274/LT6275 are stable with any capacitive load.
As previously stated in the Circuit Operation section of this
data sheet, this is accomplished by dynamically sensing
the load-induced output pole and adjusting the compensation at the amplifier’s internal gain node. As the capacitive
load increases, the bandwidth will decrease. The phase
margin may increase or decrease with different capacitive loads, and so there may be peaking in the frequency
domain and overshoot in the transient response for some
capacitive loads as shown in the Typical Performance
curves. The Small-Signal Step Response curve with 10nF
load shows 30% overshoot. For large load capacitance,
the slew rate of the LT6274/LT6275 can be limited by
the output current available to charge the load capacitor
according to:
I
SR = SC
CL
The Large-Signal Step Response with 10nF load shows
the output slew rate being limited to 9V/µs by the output
short-circuit current. Coaxial cable can be driven directly,
but for best pulse fidelity the cable should be properly
terminated by placing a resistor of value equal to the characteristic impedance of the cable (e.g. 50Ω) in series with
the output. The other end of the cable should be terminated with the same value resistor to ground.
Layout and Passive Components
should be used to cancel the input pole and optimize
dynamic performance. For unity-gain applications where
a large feedback resistor is used, CF should be greater
than or equal to CIN.
Power Dissipation
The LT6274/LT6275 combine high speed and large output drive in a small package. Because of the wide supply voltage range, it is possible to exceed the maximum
junction temperature under certain conditions. Maximum
junction temperature (TJ) is calculated from the ambient
temperature (TA), the device’s power dissipation (PD),
and the thermal resistance of the device (θJA) as follows:
TJ = TA + (PD × θJA)
Worst case power dissipation occurs at the maximum
supply current and when the output voltage is at 1/2 of
either V+ or V– (on split rails), or at the maximum output swing (if less than 1/2 of the rail voltage). Therefore
PDMAX (per amplifier) is:
PDMAX = (V+ – V–)(ISMAX) + (V+/2)2/RL
Example: For an LT6274 with thermal resistance of
215°C/W, operating on ±15V supplies and driving a 1kΩ
load to 7.5V, the maximum power dissipation is calculated
to be:
PDMAX = (30V)(2.3mA) + (7.5V)2/1kΩ = 125mW
This leads to a die temperature rise above ambient of:
The LT6274/LT6275 are easy to use and tolerant of less
than ideal layouts. For maximum performance use a
ground plane, short lead lengths, and RF-quality ceramic
bypass capacitors (0.01µF to 0.1µF). For high drive current applications use low ESR bypass capacitors (1µF to
10µF ceramic or tantalum). The resistance of the parallel
TRISE = (125mW)(215°C/W) = 27°C
This implies that the maximum ambient temperature at
which the LT6274 should operate under the above conditions is:
TA = 150°C – 27°C = 123°C
6275fa
For more information www.linear.com/LT6275
13
LT6274/LT6275
TYPICAL APPLICATIONS
Noninverting Amplifier Slew Rate and Step Response
RG
RF
Figure 1 shows a noninverting amplifier with closed-loop
gain of 11V/V. The closed-loop bandwidth of this amplifier is approximately GBW/11 (GBW = Gain-Bandwidth
Product). For a step input, the output follows an exponential curve:
200
2k
⎞⎞
⎟
⎠⎟
⎟⎟
⎠
1/2 LT6275
VIN
VOUT
–15V
6275 TA06
(1)
where τ = time constant associated with the closed-loop
bandwidth.
The maximum slew rate occurs in the beginning of the
output response:
1
(2)
VOUTSRMAX = A V • VINPUSTEP •
τ
Keep in mind that the closed-loop bandwidth and the
closed-loop gain are related (τ = τo AV), so Equation (2)
is simplified to:
1
(3)
VOUTSRMAX = VINPUTSTEP •
τo
Figure 1. LT6275 Configured in a Noninverting Gain of AV = +11V/V
15
12
AV = +11
9
OUTPUT VOLTAGE (V)
⎛t
⎛
–⎜
⎜
VOUT = VINITIAL + A V • VINPUTSTEP • ⎜1– e ⎝ τ
⎜
⎝
+15V
6
3
0
–3
–6
–9
–12
–15
50ns/DIV
6275 TA07
Figure 2. Noninverting Amplifier Step Response (AV = +11V/V)
where τo = time constant associated with the LT6274/
LT6275 GBW.
capability ensures that the output response is never slew
rate limited despite the very high excursion.
Interestingly, Equation (3) reveals that the maximum slew
rate is nominally related only to the input step size and the
op amp’s inherent GBW. Closing the loop to implement
AV > 1 gain configurations slows down the response, but
increases the excursion. The resulting maximum slew rate
remains the same.
Figure 2 shows the output response to varying input step
amplitudes. Note that none of the exponential responses
is limited by the initial slew rate (which increases with
increasing amplitude).
The LT6274/LT6275 feature ample slew rate capability
with low power consumption. Because the input stage
architecture allows high slew rate with low input stage
quiescent currents, the overall power consumption when
amplifying pulses is very low; additional power is only
drawn from the supplies during the highest slew rate
moments of the exponential response.
Since GBW of the LT6274/LT6275 is 40MHz, Equation (3)
suggests that the maximum slew rate in a step response
whose output swings 25V (implying VINPUTSTEP = 25/11
= 2.27V) is 571V/µs. The LT6274/LT6275 high slew
14
As a particular example, with AV = +11V/V, 15V output
excursion, and 40 MHz GBW, Equation (3) predicts a
maximum slew rate of 343V/μs. Measurement on the corresponding curve in Figure 2 shows 390V/μs, which is in
good agreement with the prediction. As another example,
with an 18.5V output excursion, the predicted maximum
slew rate is 423V/μs; measurement shows 460V/μs.
As the peak to peak voltage of the input step changes, the
maximum initial slew rate changes. The 63% rise time
of the closed loop response, however, does not change
(as seen in Figure 2), because the closed loop bandwidth
stays constant for all input amplitudes.
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
TYPICAL APPLICATIONS
Using the LT6274/LT6275 to Create a Composite
Amplifier with High Gain, High Bandwidth and Large
Output Signal Capability
While the LT6274/LT6275 provide ample slew rate and
large output swing capability, the GBW is not so large
as to achieve high gain, high bandwidth, and high amplitude at the same time. The circuit of Figure 3 harnesses
the high slew rate capability of the LT6275 by placing it
under control of the LTC6252, an op amp with greater
than 700MHz GBW. The LTC6252 offers high bandwidth
at low supply current, but with limited slew rate and limited output swing (since it is a 5V op amp). By creating a
composite amplifier adding the LT6275 as a high-voltage,
high-slew secondary op amp, this composite amplifier
enables large output swing at high frequencies with relatively low power dissipation.
Circuit Description
R4 and R1 realize inverting gain of –11V/V from VIN to
VOUT. The LT6275 op amp drives the output based on
whatever is commanded by the middle node, VMID. The
LTC6252 is very fast relative to the LT6275. As a consequence, the LTC6252 controlling first stage can force the
LT6275 output to move quickly by providing sufficient
differential input voltage to the LT6275. With the inverting
input of the LT6275 tied to a DC bias voltage, the LTC6252
needs merely to drive the noninverting input.
Unlike the LTC6252, the LT6275 slew rate increases linearly with its differential input voltage. Hence, the LTC6252
benefits from using the LT6275 as a slew enhancer.
reduces the LTC6252 phase shift, but it also adds to the
gain burden of the LT6275.
R2 was selected to take a gain of 2V/V in the LTC6252,
implying a gain of 5.5V/V being taken in the LT6275. The
5.5V/V gain is required to translate the 5V maximum output swing of the LTC6252 to the 27.5V maximum output
swing of the LT6275 (when operated at ±15V supplies). It
may be possible to achieve even higher bandwidth in the
composite amplifier if a high speed ±5V (rather than 5V,
0V) op amp replaces the LTC6252 as the first stage, with
the resulting increased first-stage output swing lowering
the gain that has to be taken in the LT6275.
Capacitor C7 in Figure 3 is adjusted to create a favorable
looking transient response. Figure 4 shows the transient
response at the output of the LT6275 as C7 varies. C7 =
3pF was chosen.
DC Biasing
In the circuit of Figure 3, LTC6252 supplies were chosen to be 5V and 0V, which are more practical than split
±2.5V supplies. R5 and R6 form a resistive divider to
bias the noninverting input of LTC6252 and the inverting
input of LT6275 at the middle of this rail, 2.5V. Note that
this approach results in the output of LT6275 having a DC
offset of 2.5V, which reduces the potential peak to peak
output excursion of the composite amplifier since LT6275
is powered up from split ±15V supplies.
C1
1µ
VIN
R1
1k
R4
C7
Optimizing the Loop
Larger R2 increases the local gain taken by the LTC6252.
Since the total gain is fixed by the global feedback around
the composite amplifier (AV = –R4/R1 = –11V/V), raising
the gain in the LTC6252 lowers the gain requirement of
the LT6275, increasing the overall bandwidth of the composite amplifier. Care must be taken to not take too much
gain in the LTC6252, as the reduction in the LTC6252
bandwidth and the resulting additional phase shift seen
at the output of the LTC6252 can lower the stability margins of the composite amplifier. Conversely, smaller R2
R2
2k
11k
3p
+15V
5V
5V
LTC6252
1/2 LT6275
VMID
–15V
C2
1µ
VOUT
R3
10k
R5
10k
R6
10k
6275 TA08
C5
1µ
Figure 3. Composite Amplifier Using
LTC6252 and LT6275 (AV = –11V/V)
6275fa
For more information www.linear.com/LT6275
15
LT6274/LT6275
TYPICAL APPLICATIONS
Pulse Response
15
Sine Waves
9
OUTPUT VOLTAGE (V)
6
3
0
–3
–6
–9
–12
–15
200ns/DIV
6275 TA12
Figure 5. Composite Amplifier Step Response at
Various Output Step Amplitudes (AV = –11V/V)
25
225
20
180
15
135
10
90
5
45
0
0
–5
–45
–10
–90
PHASE (DEG)
The composite amplifier of Figure 3 was also tested with
sine waves. Figure 6 shows the small signal closed-loop
gain and phase response. Distortion was also evaluated
for this circuit: for a 20VP-P output signal at 1MHz, HD2/
HD3 were measured to be –55dBc/–47dBc, respectively.
These numbers are more impressive when considering the very low power dissipation of the composite
amplifier, as illustrated in Figure 7. For example, for the
20VP-P/1MHz output condition mentioned above, the 5V
rail supply current is 3.75mA, for 1/2 LT6275 the ±15V
rails supply current is 2.2mA, resulting in a total power
dissipation of 85mW.
12
GAIN (dB)
Figure 5 shows the output step response of the composite
amplifier (measured at the output of the LT6275) at many
different amplitudes. At 15V output excursion, the initial
slope is measured to be 725V/μs. This slope is faster than
the 390V/μs measured with a 15V output excursion using
the simple noninverting amplifier of Figure 1. According
to Equation (3), this improvement has been made possible because the effective bandwidth of the composite
amplifier is higher (and thus has a lower τo), as intended.
–135
–15
–20
–25
0.1
GAIN
PHASE
–180
–225
100
1
10
FREQUENCY (MHz)
6275 TA14
Figure 6. Composite Amplifier Closed-Loop
Gain/Phase vs Frequency
10
150
5
8
USING 1/2 LT6275
2
0
–2
SUPPLY CURRENT (mA)
8pF
5pF
3pF
1pF
NO CAP
4
–4
–6
250ns/DIV
6275 TA09
Figure 4. Composite Amplifier Step Response
vs LTC6252 Feedback Capacitance (AV = –11V/V)
16
120
3
90
2
60
5V SUPPLY CURRENT
±15V SUPPLY CURRENT
TOTAL POWER
1
–8
–10
4
0
30
OUTPUT = 20VP–P
0
0.5
1
1.5
FREQUENCY (MHz)
POWER (mW)
OUTPUT VOLTAGE (V)
6
2
0
6275 TA15
Figure 7. Composite Amplifier Supply
Current and Total Power Dissipation
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LT6274#packaging for the most recent package drawings.
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
0.62
MAX
0.95
REF
2.90 BSC
(NOTE 4)
1.22 REF
1.4 MIN
3.85 MAX 2.62 REF
2.80 BSC
1.50 – 1.75
(NOTE 4)
PIN ONE
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
0.95 BSC
0.80 – 0.90
0.20 BSC
0.01 – 0.10
1.00 MAX
DATUM ‘A’
0.30 – 0.50 REF
0.09 – 0.20
(NOTE 3)
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
1.90 BSC
S5 TSOT-23 0302
6275fa
For more information www.linear.com/LT6275
17
LT6274/LT6275
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LT6275#packaging for the most recent package drawings.
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev G)
0.889 ±0.127
(.035 ±.005)
5.10
(.201)
MIN
3.20 – 3.45
(.126 – .136)
3.00 ±0.102
(.118 ±.004)
(NOTE 3)
0.65
(.0256)
BSC
0.42 ± 0.038
(.0165 ±.0015)
TYP
8
7 6 5
0.52
(.0205)
REF
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
4.90 ±0.152
(.193 ±.006)
DETAIL “A”
0° – 6° TYP
GAUGE PLANE
0.53 ±0.152
(.021 ±.006)
DETAIL “A”
1
2 3
4
1.10
(.043)
MAX
0.86
(.034)
REF
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
TYP
0.65
(.0256)
BSC
0.1016 ±0.0508
(.004 ±.002)
MSOP (MS8) 0213 REV G
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
18
6275fa
For more information www.linear.com/LT6275
LT6274/LT6275
REVISION HISTORY
REV
DATE
DESCRIPTION
A
12/17
Added LT6274
Updated Power Dissipation section
PAGE NUMBER
All
13
6275fa
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog
Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications
subject to change without notice. No license
is granted
by implication
or otherwise under any patent or patent rights of Analog Devices.
For more
information
www.linear.com/LT6275
19
LT6274/LT6275
TYPICAL APPLICATION
Composite Amplifier Provides 18-Bit Precision and Fast Settling
15V
12V
IN
LTC6655-5
+
OUT
LT1012
0.1µF
10µF
–
–15V
1
14
10k 23
10k 17
25
4
19
20
21
22
VDD
ROFS
5
3
RIN
RCOM
100pF
2
REF
RFB
LDAC
IOUT1
27, 28
VOUT
1k
26
LTC2756
CLR
10k
VOSADJ
M-SPAN
S0
–
1µF
LTC2054HV
S2
9
SDI
SCK
10
11
SRO
15V
+
+
10Ω
–5V
CCOMP
1/2 LT6275
–
–5V
5pF
1µF
6275 TA13
12
SPI BUS
1k
5V
LTC6240HV
+
IOUT2 7
6, 8, 13,
15, 16, 24
GND
S1
CS/LD
5V
10k
GEADJ
–
–15V
4.02k
DAC with Composite Amplifier Output Response
(Varying Compensation Capacitance)
1k
14
12
OUTPUT RESPONSE (V)
10
8
6
4
CCOMP
2
100pF
68pF
30pF
22pF
15pF
10pF
0
–2
–4
–6
–8
–10
–2
–1
0
1
2
3
4
TIME (µs)
5
6
7
6275 TA14
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LT1351/LT1352/LT1353
Single/Dual/Quad 3MHz, 200V/µs, C-Load Amplifiers
250µA Supply Current, 600µV Max VOS, 5V to 30V Supply Operation
LT1354/LT1355/LT1356
Single/Dual/Quad 12MHz, 400V/μs, C-Load Amplifiers
1mA Supply Current, 800µV Max VOS, 5V to 30V Supply Operation
LT1357/LT1358/LT1359
Single/Dual/Quad 25MHz, 600V/μs, C-Load Amplifiers
2mA Supply Current, 600µV Max VOS, 5V to 30V Supply Operation
LT1360/LT1361/LT1362
Single/Dual/Quad 50MHz, 800V/μs, C-Load Amplifiers
4mA Supply Current, 1mV Max VOS, 5V to 30V Supply Operation
LT1363/LT1364/LT1365
Single/Dual/Quad 70MHz, 1000V/μs, C-Load Amplifiers 6.3mA Supply Current, 1.5mV Max VOS, 5V to 30V Supply Operation
LT1812/LT1813/LT1814
Single/Dual/Quad 100MHz, 750V/μs Op Amps
3mA Supply Current, 1.5mV Max VOS, 4V to 11V Supply Operation
LTC6261/LTC6262/LTC6263 Single/Dual/Quad 30MHz, 7V/µs Op Amps
240µA Supply Current, 400µV Max VOS, 1.8V to 5.25V Supply Operation
LTC6246/LTC6247/LTC6248 Single/Dual/Quad 180MHz, 90V/µs Op Amps
0.95mA Supply Current, 500µV Max VOS, 2.5V to 5.25V Supply Operation
LTC6252/LTC6253/LTC6254 Single/Dual/Quad 720MHz, 280V/µs Op Amps
3.3mA Supply Current, 350µV Max VOS, 2.5V to 5.25V Supply Operation
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6275fa
LT 1217 REV A • PRINTED IN USA
For more information www.linear.com/LT6275
www.linear.com/LT6275
 ANALOG DEVICES, INC. 2017