N CLC416 Dual Low-Power, 120MHz Op Amp General Description Features The CLC416 is a dual, wideband (120MHz) op amp. The CLC416 consumes only 39mW per channel and can source or sink an output current of 60mA. These features make the CLC416 a versatile, high-speed solution for demanding applications that are sensitive to both power and cost. ■ Utilizing National’s proven architectures, this dual current feedback amplifier surpasses the performance of alternative solutions and sets new standards for low power. This powerconserving dual op amp achieves low distortion with -80dBc and -80dBc second and third harmonics respectively. Many high source impedance applications will benefit from the CLC416’s 6MΩ input impedance. And finally, designers will have a bipolar part with an exceptionally low 100nA non-inverting bias current. ■ ■ ■ ■ ■ ■ Applications ■ ■ ■ ■ ■ ■ ■ With 0.1dB flatness to 30MHz and low differential gain and phase errors, the CLC416 is an ideal part for professional video processing and distribution. The 120MHz -3dB bandwidth (Av = +2) coupled with a 400V/µs slew rate also makes the CLC416 a perfect choice in cost-sensitive applications such as video monitors, fax machines, copiers, and CATV systems. 0.01%, 0.03° DG, Dφ Very low input bias current: 100nA High input impedance: 6MΩ 120MHz -3dB bandwidth (Av = +2) Low power High output current: 60mA Low-cost Desktop video systems Video distribution Flash A/D driver High-speed driver High-source impedance applications Professional video processing High resolution monitors CLC416 Dual Low-Power, 120MHz Op Amp September 1998 Frequency Response (Av = +2V/V) Typical Application Diagram Pinout Instrumentation Amplifier V1 DIP & SOIC + 1/2 CLC416 348Ω Vo1 348Ω 348Ω Vout = 3(V2 - V1) - 348Ω 348Ω 348Ω CLC405 + - V2 1/2 CLC416 + © 1998 National Semiconductor Corporation Printed in the U.S.A. Vinv1 Vnon-inv1 -VCC +VCC Vo2 Vinv2 Vnon-inv2 R1 348Ω http://www.national.com CLC416 Electrical Characteristics (AV = +2, Rf = 348Ω: Vcc = + 5V, RL = 100Ω unless specified) PARAMETERS Ambient Temperature CONDITIONS CLC416AJ TYP +25˚C MIN/MAX RATINGS +25˚C 0 to 70˚C -40 to 85˚C UNITS NOTES 1 FREQUENCY DOMAIN RESPONSE -3dB bandwidth Vout < 1.0Vpp Vout < 5.0Vpp ±0.1dB bandwidth Vout < 1.0Vpp gain flatness Vout < 1.0Vpp peaking DC to 200MHz rolloff <30MHz linear phase deviation <20MHz differential gain 4.43MHz, RL=150Ω differential phase 4.43MHz, RL=150Ω 120 52 30 65 40 15 45 36 45 35 MHz MHz MHz 0.1 0 0.3 0.01 0.03 0.7 0.3 0.6 0.04 0.08 0.8 0.6 0.7 0.04 0.11 1.0 0.6 0.7 0.04 0.12 dB dB deg % deg TIME DOMAIN RESPONSE rise and fall time settling time to 0.05% overshoot slew rate AV = +2 AV = -1 4.3 22 3 400 700 6.5 30 12 300 7.2 38 12 260 7.4 41 12 250 ns ns % V/µs V/µs 2V step 2V step 2V step 2V step 1V step DISTORTION AND NOISE RESPONSE 2Vpp, 1MHz 2nd harmonic distortion 3rd harmonic distortion 2Vpp, 1MHz 2nd harmonic distortion 2Vpp, 10MHz 3rd harmonic distortion 2Vpp, 10MHz equivalent input noise voltage >1MHz inverting current >1MHz non-inverting current >1MHz crosstalk, input referred 2Vpp, 10MHz STATIC DC PERFORMANCE input offset voltage average drift input bias current average drift input bias current average drift power supply rejection ratio common-mode rejection ratio supply current per channel non-inverting inverting DC DC RL= ∞ MISCELLANEOUS PERFORMANCE input resistance non-inverting input capacitance non-inverting common mode input range output voltage range RL = 100Ω output voltage range RL = ∞ output current output resistance, closed loop -80 -80 -65 -57 -55 -50 -50 -45 -47 -45 dBc dBc dBc dBc 5 12 3 72 6.3 15 3.8 66 6.6 16 4.0 66 6.7 17 4.2 66 nV/√Hz pA/√Hz pA/√Hz dB 1 30 100 3 1 17 52 50 3.9 5 47 45 4.5 7 50 1600 8 6 40 47 45 4.6 8 50 2800 11 8 45 45 43 4.9 mV µV/˚C nA nA/˚C µA nA/˚C dB dB mA 3 2 ±1.8 +3.1/-2.8 +3.9/-3.3 44 0.2 2.4 2 ±1.7 +2.9/-2.7 +3.8/-3.2 38 0.25 1 2 ±1.5 +2.4/-1.7 +3.7/-2.8 20 0.4 MΩ pF V V V mA Ω 6 1 ±2.2 +3.5,-2.9 +4.0,-3.4 60 0.06 900 5 A A A A Recommended gain range +1 to +40V/V Transistor count = 110 Min/max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Outgoing quality levels are determined from tested parameters. Absolute Maximum Ratings supply voltage Iout is short circuit protected to ground common-mode input voltage maximum junction temperature storage temperature range lead temperature (soldering 10 sec) ESD rating (human body model) Model CLC416AJP CLC416AJE Notes 1) At temps < 0˚C, spec is guaranteed for RL = 500Ω. A) J-level: spec is 100% tested at +25˚C. ±7V ±Vcc +175˚C -65˚C to +150˚C +300˚C 1000V Ordering Information Package Thermal Resistance Temperature Range Package -40˚C to +85˚C -40˚C to +85˚C http://www.national.com Description 8-pin PDIP 8-pin SOIC Plastic (AJP) Surface Mount (AJE) 2 θJC θJA 80°C/W 95°C/W 95°C/W 115°C/W CLC416 Typical Performance Characteristics (Vcc = ±5V, Av = +2, Rf = 348ΩΩ, RL = 100ΩΩ; Inverting Frequency Response 0 -90 -180 Av = 10 Rf = 100Ω -270 Av = 4 Rf = 200Ω -360 -450 1 10 Av = -2 Rf = 348Ω Av = -1 Rf = 2kΩ Av = -4 Rf = 255Ω 0 -90 Vo = 1Vpp Av = +2 -180 -270 -360 Av = -10 Rf = 200Ω RL = 100Ω RL = 1kΩ -450 RL = 50Ω RL = 1kΩ -90 RL = 100Ω -180 RL = 50Ω -270 -360 -630 10 -450 100 1 10 Frequency (MHz) Frequency (MHz) Frequency Response vs. Vout 0 -540 1 100 Frequency Response vs. RL Magnitude (1dB/div) Normalized Magnitude (1dB/div) Av = 2 Rf = 348Ω Vo = 0.5Vpp Phase (deg) Av = 1 Rf = 1.65kΩ Phase (deg) Vo = 0.5Vpp Phase (deg) Normalized Magnitude (1dB/div) Frequency Response unless specified) 100 Frequency (MHz) Open Loop Transimpedance Gain, Z(s) Frequency Response vs. CL 130 200 Vo = 1Vpp 2Vpp 5Vpp 0.2Vpp 20 log [|Vo/|i|] (dBΩ) Rs = 107Ω CL = 10pF Magnitude (1dB/div) 1Vpp Rs = 39.25Ω CL = 47pF Rs = 27.4Ω CL = 100pF Rs = 8Ω CL = 1000pF Rs 348Ω 348Ω CL 110 160 Gain 90 120 Phase 70 80 - Ii 50 1k CLC416 Vo 40 + 100Ω 30 1 10 1 100 10 Frequency (MHz) Maximum Output Voltage vs. RL Distortion Level (dBc) 80 Rs (Ω) 60 40 -2 20 0 200 300 400 500 100 2nd Harmonic Distortion vs. Pout 50Ω 10MHz -70 -75 1MHz -85 -60 -80 0.30 0.09 0.27 0.08 0.24 0.07 0.21 0.06 -5 0 5 0.18 0.05 0.15 Gain Negative Sync Phase Negative Sync 0.04 0.12 0.03 1MHz 0.09 0.02 500kHz -100 -10 10 0.06 Phase Positive Sync 0.03 Gain Positive Sync 0 -10 Output Power (dBm) -5 0 5 1 10 Small Signal Pulse Response 3 2 Output Power (dBm) 0 4 Number of 150Ω Loads Large Signal Pulse Response 0.08 PSRR and CMRR 2 60 Av = +1 Output Voltage (V) PSRR 0.04 0.02 0 -0.02 -0.04 1 Av = +2 0 -1 Av = -2 -0.06 0.1 0.01 -90 Output Voltage (V) 5MHz -70 -90 500kHz Gain (%) Distortion (dBc) 5MHz 0.06 Differential Gain & Phase 10MHz 348Ω 348Ω 10 Frequency (MHz) Po 50Ω -50 348Ω 348Ω -80 3rd, RL = 1kΩ 1 3rd Harmonic Distortion vs. Pout 50Ω -65 2nd, RL = 1kΩ -80 Phase (deg) Distortion (dBc) -60 Po 2nd, RL = 100Ω -70 1000 -40 50Ω -60 CL (pF) Load (Ω) -55 3rd, RL = 100Ω Vo = 2Vpp -50 -90 10 600 PSRR/CMRR (dB) Maximum Output Voltage (V) -40 2 -4 100M Frequency (Hz) 100 0 10M 1M 100k 2nd & 3rd Harmonic Distoration 120 100 10k Frequency (MHz) Recommended Rs vs. Capacitive Load 4 0 0 1k 100 Phase (deg) Magnitude (1dB/div) Av = +2 50 CMRR 40 30 20 Av = -1 -0.08 -2 Time (5ns/div) 10 Time (5ns/div) 10k 100k 10M 1M 100M Frequency (Hz) 3 http://www.national.com CLC416 Typical Performance Characteristics (Vcc = ±5V, Av = +2, Rf = 348ΩΩ, RL = 100ΩΩ; unless specified) Equivalent Input Noise Typical DC Errors vs. Temperature Power Derating Curves 100 6 100 1.0 -1 IBI 3 -2 2 VIO Inverting Current = 12pA/√Hz 10 10 Voltage = 5nV/√Hz Non-Inverting Current = 3pA/√Hz -3 0.8 Power (W) 4 Noise Voltage (nV/√Hz) 0 Noise Current (pA/√Hz) IBN Bias Current (µA) Offset Voltage (mV) 1 5 -50 50 0 100 AJP 0.4 AJE 0.2 1 1 1 0.6 0 100 1k 10k 100k 1M 10M 0 20 Frequency (Hz) Temperature (°C) 40 60 80 100 120 140 160 180 Ambient Temperature (°C) CLC416 OPERATION Description The CLC416 is a dual current feedback amplifier with the following features: Feedback Resistor Selection The feedback resistor, Rf, determines the loop gain and frequency response of a current feedback amplifier. Optimum performance of the CLC416, at a gain of +2V/V, is achieved with Rf equal to 348Ω. The frequency response plots in the typical performance section illustrate the recommended Rf for several gains. Within limits, Rf can be adjusted to optimize the frequency response. Differential gain and phase errors of 0.01% and 0.03° into a 150Ω load ■ Low, 3.9mA, supply current per amplifier ■ The professional video quality differential gain and phase errors and low power capabilities of the CLC416 make this product a good choice for video applications. Decrease Rf to peak frequency response and extend bandwidth ■ Increase Rf to roll off frequency response and reduce bandwidth ■ Gain The non-inverting and inverting gain equations for the CLC416 are as follows: Non-inverting Gain: 1+ Inverting Gain: − As a rule of thumb, if the recommended Rf is doubled, the bandwidth will be cut in half. Rf Rg Rf Rg Channel Matching Channel matching and crosstalk efficiency are largely dependent on board layout. The layout of National’s dual amplifier evaluation boards are designed to produce optimum channel matching and isolation. Typical channel matching for the CLC416 is shown in Figure 2. Where Rf is the feedback resistor and Rg is the gain setting resistor. Figure 1 shows the general non-inverting gain configuration including the recommended bypass capacitors. g +Vcc Channel A + 0.1µF Vo CLC416 Rin - Rf Channel B Channel A 0 Channel B -90 -180 Av = +2 RL = 100Ω Vo = 2Vpp RL Phase (deg) Vin Magnitude (0.5dB/div) 6.8µF -270 -360 -450 1 0.1µF Rg 10 100 Frequency (MHz) Figure 2: Channel Matching 6.8µF -Vcc The CLC416’s channel-to-channel isolation is better than 70dB for input frequencies of 4MHz. Input referred crosstalk vs. frequency is illustrated in Figure 3. Figure 1: Recommended Non-Inverting Gain Circuit http://www.national.com 4 evaluation boards for the CLC416 (CLC730038 - DIP, CLC730036 - SOIC) and suggests their use as a guide for high frequency layout and as an aid for device testing and characterization. -20 Crosstalk (dB) -40 -60 Supply bypassing is required for best performance. The bypass capacitors provide a low impedance return current path at the supply pins. They also provide high frequency filtering on the power supply traces. Other layout factors play a major role in high frequency performance. The following are recommended as a basis for high frequency layout: -80 -100 -120 1 10 100 Frequency (MHz) 1. Include 6.8µF tantalum and 0.1µF ceramic capacitors on both supplies. 2. Place the 6.8µF capacitors within 0.75 inches of the power pins. 3. Place the 0.1µF capacitors within 0.1 inches of the power pins. 4. Remove the ground plane under and around the part, especially near the input and output pins to reduce parasitic capacitance. 5. Minimize all trace lengths to reduce series inductances. Figure 3: Input Referred Crosstalk vs. Frequency Driving Cables and Capacitive Loads When driving cables, double termination is used to prevent reflections. For capacitive load applications, a small series resistor at the output of the CLC416 will improve stability. The Rs vs. Capacitive Load plot, in the Typical Performance section, gives the recommended series resistance value for optimum flatness at various capacitive loads. Power Dissipation The power dissipation of an amplifier can be described in two conditions: Additional information is included in the evaluation board literature. Quiescent Power Dissipation PQ (No Load Condition) ■ Total Power Dissipation PT (with Load Condition) ■ SPICE Models SPICE models provide a means to evaluate amplifier designs. Free SPICE models are available for National’s monolithic amplifiers that: The following steps can be taken to determine the power consumption for each CLC416 amplifier: Support Berkeley SPICE 2G and its many derivatives ■ Reproduce typical DC, AC, Transient, and Noise performance ■ Support room temperature simulations ■ 1. Determine the quiescent power PQ = Icc (VCC - VEE) 2. Determine the RMS power at the output stage PO = (Vcc - Vload) (Iload), where Vload and Iload are the RMS voltage and current across the external load. 3. Determine the total RMS power PT = PQ + PO The readme file that accompanies the diskette lists released models, and provides a list of modeled parameters. The application note OA-18, Simulation SPICE Models for National’s Op Amps, contains schematics and a reproduction of the readme file. Add the total RMS powers for both channels to determine the power dissipated by the dual. Applications Circuits The maximum power that the package can dissipate at a given temperature is illustrated in the Power Derating curves in the Typical Performance section. The power derating curve for any package can be derived by utilizing the following equation: Instrumentation Amplifier An instrumentation circuit is shown on the front page and reproduced in Figure 4. The DC CMRR can be fine tuned by adjusting R1. V1 + 1/2 CLC416 (175° − Tamb) P= θ JA 348Ω 348Ω 348Ω Vout = 3(V2 - V1) where: Tamb = Ambient temperature (°C) θJA = Thermal resistance, from junction to ambient, for a given package (°C/W) - 348Ω 348Ω 348Ω CLC405 + - V2 Layout Considerations A proper printed circuit layout is essential for achieving high frequency performance. National provides 1/2 CLC416 + R1 348Ω Figure 4: Instrumentation Amplifier 5 http://www.national.com C + 1/2 CLC416 R R R R 1/2 CLC416 + +Vin R Av = -1V/V R - R - R R - - 1/2 CLC416 R -Vin + R1 Vin + R 1/2 CLC416 Ro Vo = 2Vin + C Vo CLC405 Av = -1V/V - R= 1 2πfr C R1 = QR Rf Figure 5: Differential Line Receiver Figure 6: Bandpass Filter Topology Bandpass Filter Figure 6 illustrates a low-sensitivity bandpass filter and design equations. This topology utilizes the CLC416’s closely matched amplifiers to obtain low op-amp sensitivity at high frequencies. The CLC405 is used as a buffer to obtain low output impedance. The overall circuit gain is unity. For additional gain, the CLC405 can be configured as a non-inverting amplifier. 1.8dB 935kHz 0 Magnitude (dB) CLC416 Dual Low-Power, 120MHz Op Amp Differential Line Receiver Figure 5 illustrates a Differential Line Receiver. The circuit will convert differential signals to single-ended signals. To design the filter, choose C and then determine values for R and R1 based on the desired resonant frequency (fr) and Q factor. -10 -20 -30 -40 Figure 7 illustrates a bandpass filter with Q = 10 and fr = 1MHz. The component values used are listed below: R1 = 4.9kΩ R = 499Ω C = 330pF Rf = 2kΩ 1 10 Frequency (MHz) Figure 7: Bandpass Response Customer Design Applications Support National Semiconductor is committed to design excellence. For sales, literature and technical support, call the National Semiconductor Customer Response Group at 1-800-272-9959 or fax 1-800-737-7018. Life Support Policy National’s products are not authorized for use as critical components in life support devices or systems without the express written approval of the president of National Semiconductor Corporation. As used herein: 1. Life support devices or systems are devices or systems which, a) are intended for surgical implant into the body, or b) support or sustain life, and whose failure to perform, when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. N National Semiconductor Corporation National Semiconductor Europe National Semiconductor Hong Kong Ltd. National Semiconductor Japan Ltd. 1111 West Bardin Road Arlington, TX 76017 Tel: 1(800) 272-9959 Fax: 1(800) 737-7018 Fax: (+49) 0-180-530 85 86 E-mail: europe.support.nsc.com Deutsch Tel: (+49) 0-180-530 85 85 English Tel: (+49) 0-180-532 78 32 Francais Tel: (+49) 0-180-532 93 58 Italiano Tel: (+49) 0-180-534 16 80 13th Floor, Straight Block Ocean Centre, 5 Canton Road Tsimshatsui, Kowloon Hong Kong Tel: (852) 2737-1600 Fax: (852) 2736-9960 Tel: 81-043-299-2309 Fax: 81-043-299-2408 National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. http://www.national.com 6