LINER LTC2912 High voltage surge Datasheet

LT4363
High Voltage Surge
Stopper with Current Limit
FEATURES
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DESCRIPTION
Withstands Surges Over 80V with VCC Clamp
Wide Operating Voltage Range: 4V to 80V
Adjustable Output Clamp Voltage
Fast Overcurrent Limit: Less Than 5µs
Reverse Input Protection to –60V
Adjustable UV/OV Comparator Thresholds
Low 7µA Shutdown Current
Shutdown Pin Withstands –60V to 100V
Adjustable Fault Timer
Controls N-Channel MOSFET
Less Than 1% Retry Duty Cycle During Faults,
LT4363-2
Available in 12-Pin (4mm × 3mm) DFN, 12-Pin
MSOP or 16-Pin SO Packages
The LT®4363 surge stopper protects loads from high voltage
transients. It regulates the output during an overvoltage
event, such as load dump in vehicles, by controlling the
gate of an external N-channel MOSFET. The output is limited
to a safe value allowing the loads to continue functioning.
The LT4363 also monitors the voltage drop between the
SNS and OUT pins to protect against overcurrent faults.
An internal amplifier limits the voltage across the current
sense resistor to 50mV. In either fault condition, a timer is
started inversely proportional to MOSFET stress. Before the
timer expires, the FLT pin pulls low to warn of an impending power down. If the condition persists, the MOSFET is
turned off. The LT4363-1 remains off until reset whereas
the LT4363-2 restarts after a cool down period.
Two precision comparators can monitor the input supply
for overvoltage (OV) and undervoltage (UV) conditions.
When the potential is below the UV threshold, the external
MOSFET is kept off. If the input supply voltage is above the
OV threshold, the MOSFET is not allowed to turn back on.
Back-to-back MOSFETs can be used in lieu of a Schottky
diode for reverse input protection, reducing voltage drop
and power loss. A shutdown pin reduces the quiescent
current to less than 7µA during shutdown.
APPLICATIONS
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Automotive/Avionic Surge Protection
Hot Swap™/Live Insertion
High Side Switch for Battery Powered Systems
Intrinsic Safety Applications
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and
No RSENSE, ThinSOT and Hot Swap are trademarks of Linear Technology Corporation. All other
trademarks are the property of their respective owners.
TYPICAL APPLICATION
4A, 12V Overvoltage Output Regulator with 150V Surge Protection
FDB33N25
VIN
12V
10mΩ
22µF
1k
10Ω
0.1µF
127k
VCC
GATE SNS
4.99k
SHDN GND
ENOUT
GND
TMR
VCC
DC/DC
CONVERTER
LT4363-2
49.9k
OV
80V INPUT SURGE
CTMR = 6.8µF
ILOAD = 500mA
VIN
20V/DIV
OUT
SHDN
UV
OUTPUT
CLAMP
AT 16V
57.6k
FB
SMAJ58A
Overvoltage Protector Regulates
Output at 27V During Transient
FLT
4363 TA01
FAULT
12V
VOUT
20V/DIV
27V ADJUSTABLE CLAMP
12V
100ms/DIV
4363 TA01b
0.1µF
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LT4363
ABSOLUTE MAXIMUM RATINGS
(Notes 1, 2)
VCC, SHDN, UV, OV.................................... –60V to 100V
SNS, OUT.................................................. –0.3V to 100V
SNS to OUT.................................................. –30V to 30V
GATE (Note 3)...................................–0.3V to SNS + 10V
ENOUT, FLT............................................... –0.3V to 100V
FB .............................................................. –0.3V to 5.5V
TMR.......................................................................0.5mA
Operating Temperature Range
LT4363C................................................... 0°C to 70°C
LT4363I.................................................–40°C to 85°C
Storage Temperature Range
DE12................................................... –65°C to 125°C
MS, SO............................................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec)
MS, SO.............................................................. 300°C
PIN CONFIGURATION
LT4363-1
LT4363-1
LT4363-1
TOP VIEW
TOP VIEW
FB
1
12
TMR
OUT
2
11
ENOUT
10
FLT
9
GND
5
8
UV
6
7
GND
SNS
3
GATE
4
VCC
SHDN
13
GND
TOP VIEW
FB
OUT
SNS
GATE
VCC
SHDN
12
11
10
9
8
7
TMR
ENOUT
FLT
GND
UV
GND
MS PACKAGE
12-LEAD PLASTIC MSOP
TJMAX = 125°C, θJA = 135°C/W
DE PACKAGE
12-LEAD (4mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 43°C/W
EXPOSED PAD (PIN 13) IS GND, CONNECTION TO PCB
OPTIONAL
LT4363-2
1
2
3
4
5
6
OUT
1
16 FB
SNS
2
15 TMR
NC
3
14 NC
GATE
4
13 ENOUT
NC
5
12 FLT
VCC
6
11 GND
NC
7
10 UV
SHDN
8
9
S PACKAGE
16-LEAD PLASTIC SO
TJMAX = 125°C, θJA = 80°C/W
LT4363-2
LT4363-2
TOP VIEW
TOP VIEW
FB
1
12
TMR
OUT
2
11
ENOUT
10
FLT
9
GND
5
8
UV
6
7
OV
SNS
3
GATE
4
VCC
SHDN
13
GND
GND
DE PACKAGE
12-LEAD (4mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 43°C/W
EXPOSED PAD (PIN 13) IS GND, CONNECTION TO PCB
OPTIONAL
TOP VIEW
FB
OUT
SNS
GATE
VCC
SHDN
1
2
3
4
5
6
12
11
10
9
8
7
MS PACKAGE
12-LEAD PLASTIC MSOP
TJMAX = 125°C, θJA = 135°C/W
TMR
ENOUT
FLT
GND
UV
OV
OUT
1
16 FB
SNS
2
15 TMR
NC
3
14 NC
GATE
4
13 ENOUT
NC
5
12 FLT
VCC
6
11 GND
NC
7
10 UV
SHDN
8
9
OV
S PACKAGE
16-LEAD PLASTIC SO
TJMAX = 125°C, θJA = 80°C/W
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LT4363
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LT4363CDE-1#PBF
LT4363CDE-1#TRPBF
43631
12-Lead (4mm × 3mm) Plastic DFN
0°C to 70°C
LT4363IDE-1#PBF
LT4363IDE-1#TRPBF
43631
12-Lead (4mm × 3mm) Plastic DFN
–40°C to 85°C
LT4363CDE-2#PBF
LT4363CDE-2#TRPBF
43632
12-Lead (4mm × 3mm) Plastic DFN
0°C to 70°C
LT4363IDE-2#PBF
LT4363IDE-2#TRPBF
43632
12-Lead (4mm × 3mm) Plastic DFN
–40°C to 85°C
LT4363CMS-1#PBF
LT4363CMS-1#TRPBF
43631
12-Lead Plastic MSOP
0°C to 70°C
LT4363IMS-1#PBF
LT4363IMS-1#TRPBF
43631
12-Lead Plastic MSOP
–40°C to 85°C
LT4363CMS-2#PBF
LT4363CMS-2#TRPBF
43632
12-Lead Plastic MSOP
0°C to 70°C
LT4363IMS-2#PBF
LT4363IMS-2#TRPBF
43632
12-Lead Plastic MSOP
–40°C to 85°C
LT4363CS-1#PBF
LT4363CS-1#TRPBF
LT4363S-1
16-Lead Plastic SO
0°C to 70°C
LT4363IS-1#PBF
LT4363IS-1#TRPBF
LT4363S-1
16-Lead Plastic SO
–40°C to 85°C
LT4363CS-2#PBF
LT4363CS-2#TRPBF
LT4363S-2
16-Lead Plastic SO
0°C to 70°C
LT4363IS-2#PBF
LT4363IS-2#TRPBF
LT4363S-2
16-Lead Plastic SO
–40°C to 85°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
Consult LTC Marketing for information on non-standard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VCC = 12V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
VCC
Operating Voltage Range
LT4363C
LT4363I
l
l
ICC
VCC Supply Current
SHDN Open, OUT = SNS = 12V
SHDN = 0V, OUT = SNS = 0V
l
IR
Reverse Input Current
VCC = –60V, SHDN, UV, OV Open
VCC = SHDN = UV = OV = –60V
ΔVGATE
GATE Drive
ΔVGATE = (GATE – SNS);VCC = OUT
VCC = 4V; IGATE = –0.5µA, 0µA
9V ≤ VCC ≤ 80V; IGATE = –1µA, 0µA
TYP
4
4.5
UNITS
80
80
V
V
0.7
7
1.2
20
40
mA
µA
µA
–0.5
–3
–3
–10
mA
mA
l
l
l
MAX
l
l
4.5
10
13
16
V
V
–35
–40
µA
µA
IGATE(UP)
GATE Pull-Up Current
VCC = GATE = OUT = 12V
VCC = GATE = OUT = 48V
l
l
–10
–10
–20
–25
IGATE(DN)
GATE Pull-Down Current
Overvoltage: FB = 1.5V, GATE = 12V, OUT = 5V
Overcurrent: ΔVSNS = 150mV, VGATE = 10V, OUT = 0V
Shutdown/UV Mode: SHDN = 0V, GATE = 10V
UV = 1V, GATE = 10V
l
l
l
l
75
50
50
200
150
100
1000
1000
1.25
1.275
1.3
V
±0.2
±1
µA
mA
mA
µA
µA
VFB
FB Servo Voltage
GATE = 12V; OUT = 8V
l
IFB
FB Input Current
VFB = 1.275V
l
ΔVSNS
Current Limit Sense Voltage
ΔVSNS = (SNS – OUT)
VCC = 12V, OUT = 3V to 12V
VCC = 48V, OUT = 3V to 48V
l
l
43
45
50
52
58
59
mV
mV
Current Limit Foldback
VCC = 12V, OUT = 0V to 1V
VCC = 48V, OUT = 0V to 1V
l
l
15
16
25
27
35
36
mV
mV
SNS Input Current
OUT = SNS = 3V to 80V
OUT = SNS = 0V
l
l
20
–10
30
–15
µA
µA
ISNS
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LT4363
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VCC = 12V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
ITMR
TMR Pull-up Current, Overvoltage
TMR = 1V, FB = 1.5V, ΔVDS = 0.5V
TMR = 1V, FB = 1.5V, ΔVDS = 75V
l
l
–1.7
–42
–4
–50
–6
–58
µA
µA
TMR Pull-up Current, OV Warning
TMR = 1.325V, FB = 1.5V, ΔVDS = 0.5V
l
–3
–5
–7
µA
TMR Pull-up Current, Overcurrent
TMR = 1V, ΔVSNS = 100mV, ΔVDS = 0.5V
TMR = 1V, ΔVSNS = 100mV, ΔVDS = 80V
l
l
–5
–190
–9
–250
–13
–310
µA
µA
TMR Pull-up Current, Cool Down
TMR = 3V, FB = 1.5V, ΔVSNS = 0V, ΔVDS = 0V
l
–1
–2.3
–3.5
µA
TMR Pin Pull-down Current, Cool Down
VTMR = 3V, FB = 1.5V, ΔVSNS = 0V, ΔVDS = 0V
l
1
2
4
µA
VTMR(F)
VTMR(G)
VTMR(R)
TMR Fault Threshold
TMR Gate Off Threshold
TMR Restart Threshold
TMR Rising
TMR Rising
TMR Falling, LT4363-2
l
l
l
1.235
1.335
0.47
1.275
1.375
0.5
1.31
1.41
0.53
V
V
V
ΔVTMR
Early Warning Window
VTMR(G) – VTMR(F)
l
80
100
120
mV
VTMR(H)
TMR Cool Down High Threshold
VCC = 7V to 80V, TMR Rising
l
3.7
4.3
5
V
VUV
UV Input Threshold
UV Rising
l
1.24
1.275
1.31
V
VUV(HYST)
UV Input Hysteresis
VOV
OV Input Threshold
OV Rising
l
1.24
1.275
VOV(HYST)
OV Input Hysteresis
IIN
UV, OV Input Current
UV = 1.275V
UV = –60V
l
l
±0.2
–1
±1
–2
ILEAK
FLT, ENOUT Leakage Current
FLT, ENOUT = 80V
l
±0.5
±2.5
µA
VOL
FLT, ENOUT Output Low
ISINK = 0.1mA
ISINK = 2mA
l
l
300
2
800
9
mV
V
ΔVOUT(TH)
OUT High Threshold
ΔVOUT = VCC – VOUT, ENOUT From Low to High
l
0.25
0.5
0.75
V
ENOUT From High to Low
l
1.9
2.7
3.6
V
l
l
0.25
0.25
0.5
1
mA
mA
1.4
1.7
2.1
V
V
2.2
V
ΔVOUT(RST) OUT Reset Threshold
12
7.5
IOUT
OUT Input Current
VCC = OUT = 12V, SHDN Open
VCC = OUT = 12V, SHDN = 0V
VSHDN
SHDN Threshold
VCC = 4V to 80V
l
VSHDN(Z)
SHDN Open Voltage
mV
1.31
VCC = 4V to 80V
0.6
0.4
l
ISHDN
SHDN Current
SHDN = 0.4V
l
tRESET
SHDN Reset Time
SHDN ≤ 0.4V; LT4363-1
l
–1
–4
D
Retry Duty Cycle; Overvoltage
VCC = 80V, OUT = 16V, FB = 1.5V; LT4363-2
l
1
Retry Duty Cycle; Output Short
VCC = 12V, OUT = 0V, ∆VSNS = 100mV; LT4363-2
l
V
mV
µA
mA
–8
µA
100
µs
2
%
0.76
1
%
tOFF(UV)
Undervoltage Turn Off Propagation Delay UV Steps from 1.5V to 1V
l
2
5
µs
tOFF(OV)
Overvoltage Turn Off Propagation Delay
FB Steps from 0V to 1.5V; OUT = 0V
l
0.25
1
µs
tOFF(OC)
Overcurrent Turn Off Propagation Delay
∆VSNS Steps from 0V to 150mV; OUT = 0V
l
1
2.5
µs
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: All currents into device pins are positive all current out of device
pins are negative. All voltages are referenced to GND unless otherwise
specified.
Note 3: An internal clamp limits the GATE pin to a minimum of 10V above
the OUT pin. Driving this pin to voltages beyond the clamp may damage
the device.
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LT4363
TYPICAL PERFORMANCE CHARACTERISTICS
otherwise noted.
1000
Supply Current vs Supply Voltage
(ICC vs VCC)
8
Specifications are at VCC = 12V, TA = 25°C, unless
Supply Current During Shutdown
vs Temperature
(ICC(SHDN) vs Temperature)
6
OUT = SNS = 0V
7
5
4
400
ICC (µA)
5
600
4
3
2
1
1
0
10
20
30
40 50
VCC (V)
60
70
0
–50
80
SHDN = 0.4V
1.5
1.0
0.5
–25
75
0
25
50
TEMPERATURE (°C)
0
125
100
40
VCC = SNS = OUT = GATE
35
35
30
30
25
25
20
15
5
5
GATE Pull-Down Current vs
Temperature: Overcurrent
0
10
20
30
40 50
VCC (V)
60
70
175
14
150
150
12
125
10
100
75
50
SNS = OUT = 5V
25 GATE = 12V
FB = 1.5V
0
–50 –25
0
25
50
75
TEMPERATURE (°C)
125
4363 G07
∆VGATE (V)
175
IGATE(DN,OV) (mA)
16
∆VSNS = 150mV
25 OUT
= 0V
GATE = 10V
0
–50 –25
0
25
50
75
TEMPERATURE (°C)
60
70
80
4363 G03
–25
0
25
50
75
TEMPERATURE (°C)
100
125
4363 G06
200
50
40 50
VCC (V)
4363 G05
200
100
30
VCC = SNS = OUT
0
–50
80
GATE Pull-Down Current vs
Temperature: Overvoltage
75
20
15
10
4363 G04
100
10
20
10
0
125
125
0
GATE Pull-Up Current vs
Temperature
IGATE(UP) (µA)
IGATE(UP) (µA)
ICC(SHDN) (µA)
SHDN = 0V
0
–50
100
GATE Pull-Up Current vs VCC
40
2.0
0
25
50
75
TEMPERATURE (°C)
4363 G02
3.0
2.5
–25
4363 G01
SHDN Current vs Temperature
IGATE(DN,OC) (mA)
3
2
200
0
OUT = SNS = 0V
6
ICC (µA)
ICC (µA)
800
Supply Current During Shutdown
vs Supply Voltage
(ICC(SHDN) vs VCC)
Gate Drive Voltage vs Gate
Pull-Down Current ΔVGATE vs IGATE
VCC = SNS = OUT
8
6
4
2
100
125
4363 G08
0
0
2
6
4
IGATE (µA)
8
10
4363 G09
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LT4363
TYPICAL PERFORMANCE CHARACTERISTICS
Specifications are at VCC = 12V, TA = 25°C, unless
otherwise noted.
TMR High Threshold vs
Supply Voltage
5
VCC = SNS = OUT
IGATE = 0µA
4
12
11
10
IGATE = 1µA
8
VTMR (V)
IGATE = –1µA
12
Gate Drive vs Supply Voltage
(ΔVGATE vs VCC)
14
IGATE = 0µA
13
∆VGATE (V)
16
∆VGATE (V)
14
Gate Drive at Temperature
(ΔVGATE vs Temperature)
6
3
2
4
2
VCC = SNS = OUT
10
–50
75
0
25
50
TEMPERATURE (°C)
–25
100
0
125
0
4
8
12
4363 G10
260
TMR = 1V
20
10
Overcurrent TMR Current vs
(VCC – VOUT)
2.5
TMR = 1V
10
20
30 40 50
VCC – VOUT (V)
60
70
120
80
0
80
ITMR(UP,COOL) (µA)
2.0
1.6
1.2
0.8
0.4
0
–50
–25
75
0
25
50
TEMPERATURE (°C)
100
125
4363 G16
30
40 50
VCC (V)
60
70
80
4363 G12
Warning Period TMR Current
vs VCC
∆VDS = 0.5V
1.5
1.0
0
10
20
30 40 50
VCC – VOUT (V)
60
70
0
80
2.5
5
2.0
4
1.5
2
0.5
1
75
0
25
50
TEMPERATURE (°C)
20
30
100
125
4363 G17
40 50
VCC (V)
60
70
80
4363 G15
OUT = SNS = 3V
3
1.0
–25
10
Output Low Voltage vs Current
6
TMR = 3V
0
–50
0
4363 G14
TMR Pull-Up Current (Cool Down)
vs Temperature
TMR = 1V
20
0.5
4363 G13
3.0
10
2.0
40
0
0
4363 G11
160
TMR Pull-Down Current vs
Temperature
ITMR(DN) (µA)
1
80
ITMR(OV,EW) (µA)
ITMR(UP,OC) (µA)
ITMR(UP,OV) (µA)
30
2.4
70
220
40
0
60
VOL (V)
50
Overvoltage TMR Current vs
(VCC – VOUT)
16 20
VCC (V)
0
0
0.5
1.0
1.5
2.0
ISINK (mA)
2.5
3.0
4363 G18
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LT4363
TYPICAL PERFORMANCE CHARACTERISTICS
otherwise noted.
Overcurrent Turn-Off Time vs
Temperature
350
1.4
300
1.2
250
1.0
tOFF(OC) (µs)
tOFF(OV) (ns)
Overvoltage Turn-Off Time vs
Temperature
200
150
50
0.2
0
25
50
75
TEMPERATURE (°C)
100
OUT = 3V
∆VSNS = 300mV
0.6
0.4
–25
OUT = 0V
∆VSNS = 150mV
0.8
100
0
–50
Specifications are at VCC = 12V, TA = 25°C, unless
0
–50
125
–25
0
25
50
75
TEMPERATURE (°C)
100
4363 G19
4363 G20
Reverse Current vs Reverse
Voltage
–7
60
VCC = SHDN
–6
OUT = 3V
50
∆VSNS (mV)
IGND (mA)
Current Limit at Supply Voltage
(ΔVSNS vs VCC)
55
–5
–4
–3
45
40
–2
OUT = 0V
35
–1
0
125
0
–10 –20 –30 –40 –50 –60 –70 –80
VCC (V)
4363 G21
30
0
10
20
30
40 50
VCC (V)
60
70
80
4363 G22
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LT4363
PIN FUNCTIONS
ENOUT: Open Collector Enable Output. The ENOUT pin goes
high impedance when the voltage at the OUT pin is within
0.5V of VCC and 3V above GND, indicating the external
MOSFET is fully on. The state of the pin is latched until the
OUT pin voltage drops below 2V, resetting the latch. The
internal NPN is capable of sinking up to 2mA of current.
Exposed Pad (DFN Package Only): Exposed pad may be
left open or connected to device ground (GND).
FB: Voltage Regulator Feedback Input. Connect this pin to
the center tap of the resistive divider connected between
the OUT pin and ground. During an overvoltage condition,
the GATE pin is controlled to maintain a 1.275V threshold
at the FB pin. Connect to GND to disable the OV clamp.
FLT: Open Collector Fault Output. This pin pulls low after
the voltage at the TMR pin has reached the fault threshold
of 1.275V. It indicates the pass transistor is about to turn off
because either the supply voltage has stayed at an elevated
level for an extended period of time (voltage fault) or the
device is in an overcurrent condition (current fault). The
internal NPN is capable of sinking up to 2mA of current.
GATE: N-Channel MOSFET Gate Drive Output. The GATE pin
is pulled up by an internal charge pump current source and
clamped to 14V above the OUT pin. Both voltage and current amplifiers control the GATE pin to regulate the output
voltage and limit the current through the MOSFET.
GND: Device Ground.
OUT: Output Voltage Sense Input. This pin senses the
voltage at the source of the external N-channel MOSFET.
The voltage difference between VCC and OUT sets the fault
timer current. When this difference drops below 0.5V, the
EN pin goes high impedance.
OV (LT4363-2): Overvoltage Comparator Input. When OV
is above its threshold of 1.275V, the fault retry function
is inhibited even when the TMR pin voltage has reached
its retry threshold. As soon as the voltage at OV pin falls
below its lower threshold the GATE pin is allowed to turn
back on. Connect to GND if unused.
SHDN: Shutdown Control Input. The LT4363 can be
shutdown to a low current mode by pulling the SHDN pin
below the threshold of 0.4V. Pull this pin above 2.1V or
disconnect it to allow the internal current source to turn
the part back on. The leakage current to ground at the pin
should be limited to no more than 1µA if no external pull
up is used to turn the part on. The SHDN pin can be pulled
up to 100V or below GND by 60V without damage.
SNS: Current Sense Input. Connect this pin to the input of
the current sense resistor. The current limit circuit controls
the GATE pin to limit the sense voltage between SNS and
OUT pins to 50mV. This is reduced to 25mV in a severe
fault when OUT is below 2V. When in current limit mode,
a current source charges up the TMR pin. The voltage
difference with the OUT pin must be limited to less than
30V. Connect to OUT pin if unused.
TMR: Fault Timer Input. Connect a capacitor between this
pin and ground to set the times for early fault warning,
fault turn-off, and cool down periods. The current charging up this pin during fault conditions depends on the
voltage difference between the VCC and OUT pins. When
TMR reaches 1.275V, the FLT pin pulls low to indicate the
detection of a fault condition. If the condition persists, the
pass transistor turns off when TMR reaches the threshold
of 1.375V. A 2µA current source then continues to pull
the TMR up. When TMR reaches 4.3V, the 2µA current
reverses direction and starts to pull the TMR pin low.
When TMR reaches the retry threshold of 0.5V, the GATE
pin pulls high turning back on the pass transistor for the
LT4363-2 version. The GATE pin latches low after fault
time out for the LT4363-1.
UV: Undervoltage Comparator Input. When UV falls below
its threshold of 1.275V, the GATE is pulled down with a
1mA current. When UV rises above 1.275V plus the hysteresis, the pull down current disappears and the GATE
pin is pulled up by the internal charge pump. If unused,
connect to VCC.
VCC: Positive Supply Voltage Input. The positive supply
input ranges from 4V to 80V for normal operation. It can
also be pulled below ground by up to 60V during a reverse
battery condition, without damaging the part. Shutting
down the LT4363 by pulling the SHDN pin to ground will
reduce the supply current to 7µA.
4363fa
8
LT4363
BLOCK DIAGRAM
VCC
GATE
SNS
13V
OUT
CHARGE
PUMP
+
–
FB
+
+
VA
–
–
50mV/
25mV
IA
SHDN
UV
1.275V
FLT
SHDN
–
ENOUT
UV
+
CONTROL
LOGIC
1.275V
+
RETRY
–
GATEOFF
OV
(LT4363-2 ONLY)
1.375V
FLT
–
0.5V
ITMR
–
+
VCC
+
+
2µA
1.275V
–
+
4.3V
TMR
–
GND
4363 BD
4363fa
9
LT4363
OPERATION
Some power systems must cope with high voltage surges
of short duration such as those in vehicles. Load circuitry
must be protected from these transients, yet high availability
systems must continue operating during these events.
sufficient time for TMR to discharge to 0.5V and for the
MOSFET to cool before attempting to reset the part. To
reset, pull the SHDN pin low for at least 100µs, then pull
high with a slew rate of at least 10V/ms.
The LT4363 is an overvoltage protection regulator that
drives an external N-channel MOSFET as the pass transistor. It operates from a wide supply voltage range of 4V to
80V. It can also be pulled below ground potential by up
to 60V without damage. The low power supply requirement of 4V allows it to operate even during cold cranking
conditions in automotive applications. The internal charge
pump turns on the N-channel MOSFET to supply current
to the loads with very little power loss. Two MOSFETs can
be connected back to back to replace an inline Schottky
diode for reverse input protection. This improves the efficiency and increases the available supply voltage level
to the load circuitry during cold crank.
The fault timer allows the load to continue functioning
during short transient events while protecting the MOSFET
from being damaged by a long period of supply overvoltage,
such as a load dump in vehicles. The timer period varies
with the voltage across the MOSFET. A higher voltage corresponds to a shorter fault timer period, helping to keep
the MOSFET within its safe operating area (SOA).
Normally, the pass transistor is fully on, powering the loads
with very little voltage drop. When the supply voltage surges
too high, the voltage amplifier (VA) controls the gate of the
MOSFET and regulates the voltage at the OUT pin to a level
that is set by the external resistive divider from the OUT
pin to ground and the internal 1.275V reference. A current
source starts charging up the capacitor connected at the
TMR pin to ground. If the TMR voltage reaches 1.275V,
the FLT pin pulls low to indicate impending turn-off due
to the overvoltage condition. The pass transistor stays on
until TMR reaches 1.375V, at which point the GATE pin
pulls low turning off the MOSFET.
The LT4363 senses an overcurrent condition by monitoring the voltage across an optional sense resistor placed
between the SNS and OUT pins. An active current limit
circuit (IA) controls the GATE pin to limit the sense voltage to 50mV, if the OUT pin potential is above 2V. In the
case of a severe output short that brings OUT below 2V,
the servo sense voltage is reduced to 25mV to reduce
the stress on the pass transistor. During current limit, the
current charging the TMR capacitor is about 5 times the
current during an overvoltage event. The FLT pin pulls low
when the TMR voltage reaches 1.275V and the MOSFET
is turned off when it reaches 1.375V. The MOSFET turns
back on and the FLT pin returns to a high impedance state
after TMR has reached the 0.5V threshold for the LT4363‑2
version. For the latch-off version, LT4363-1, both the GATE
and FLT pins remain low even after TMR has reached
the 0.5V threshold. Reset the part in the same way as in
overvoltage time-out case.
A current continues to pull the TMR pin up until it reaches
about 4.3V, at which point the current reverses direction
and pulls the TMR pin down. For the LT4363-2 version,
when the voltage at the TMR pin reaches 0.5V the GATE
pin begins rising, turning on the MOSFET. The FLT pin will
then return to a high impedance state. For the latch-off
version, LT4363-1, both the GATE and FLT pins remain
low even after TMR has reached the 0.5V threshold. Allow
An accurate undervoltage comparator keeps the GATE
pin low until the voltage at the UV pin is above the
1.275V threshold. An overvoltage comparator prevents
the MOSFET from turning on after fault time-out while
the voltage at the OV pin is still above 1.275V for the
LT4363‑2. The SHDN pin turns off the pass transistor
and all the internal circuitry, reducing the supply current
to a mere 7µA.
4363fa
10
LT4363
APPLICATIONS INFORMATION
The LT4363 limits the voltage and current delivered to the
load during supply transient or output overload events. The
total fault timer period is set to ride through short-duration
faults, while longer events cause the output to shut off
and protect the MOSFET pass device from damage. The
MOSFET provides a low resistance path from the input to
the load during normal operation, while in fault conditions
it operates as a series regulator.
Overvoltage Fault
The LT4363 limits the voltage at the output during an
overvoltage at the input. An internal amplifier regulates
the GATE pin to maintain 1.275V at the FB pin. During
this interval the MOSFET is on and supplies current to
the load. This allows uninterrupted operation during short
overvoltage events. If the overvoltage condition persists,
the timer causes the MOSFET to turn off.
Overcurrent Fault
The LT4363 features and adjustable current limit that protects against output short circuits or excessive load current.
During an overcurrent event, the GATE pin is regulated to
limit the current sense voltage across the SNS and OUT
pins to 50mV. In the case of a severe short at the output,
where OUT is less than 2V, the current sense voltage is
reduced to 25mV to further reduce power dissipation in
the MOSFET. If the overcurrent condition persists, the
timer causes the MOSFET to turn off.
Fault Timer Overview
Overvoltage and overcurrent conditions are limited in
duration by an adjustable timer. A capacitor at the TMR pin
sets the delay time before a fault condition is reported at
the FLT pin as well as the overall delay before the MOSFET
is turned off. The same capacitor also sets the cool down
time before the MOSFET is allowed to turn back on.
When either an overvoltage or overcurrent fault condition
occurs, a current source charges the TMR pin capacitor.
The exact current level varies as a function of the type of
fault and the VDS voltage drop across the MOSFET. This
scheme takes better advantage of the MOSFET’s available
Safe Operating Area (SOA) than would a fixed timer current.
The TMR pin is biased to 0.5V under normal operating
conditions. In the presence of a fault the timer first charges
to 1.275V, and then enters the early warning phase of
operation. At this point the FLT pin pulls low and after
charging to 1.375V, the timer shuts off the MOSFET. The
warning phase is indicated by FLT low and gives time for
the load to perform house-keeping chores such as data
storage in anticipation of impending power loss. After
faulting off, the timer enters the cool down phase. At the
end of the cool down period the LT4363-1 remains off until
reset, while the LT4363-2 automatically restarts. For the
LT4363-2 retry is inhibited if the OV pin is greater than
1.275V. This prevents motorboating in the event there is
a sustained input overvoltage condition.
Fault Timer Operation in Overvoltage
In the presence of an overvoltage condition when the
LT4363 regulates the output voltage, the timer charges
from 0.5V to 1.275V with a current that varies as a function of VDS (see Figure 1). VDS is inferred from the drop
across VCC and OUT. The timer current increases linearly
from around 4µA with VDS ≤ 0.5V, to 50µA with VDS = 75V.
Because VDS is measured indirectly, clamping or filtering
at the VCC pin affects the timer current response. A graph
of Overvoltage TMR Current vs (VCC – VOUT) is shown in
the Typical Performance Characteristics.
When TMR reaches 1.275V, the FLT pin is latched low as
an early warning of impending shutdown. The timer current is cut to a fixed value of 6µA and continues to run
until TMR reaches 1.375V, producing a fixed early warning
period given by:
CTMR = t WARNING •
6µA
100mV
When TMR reaches 1.375V, the MOSFET is turned off and
allowed to cool for an extended period. The total elapsed
time between the onset of output regulation and turn-off
is given by:
 0.775V 100mV 
tREG = CTMR • 
+
6µA 
 ITMR
Because ITMR is a function of VCC – VOUT, the exact time in
regulation depends upon the input waveform and the time
required for the output voltage to come into regulation.
4363fa
11
LT4363
APPLICATIONS INFORMATION
Fault Timer Operation in Overcurrent
TMR pin behavior in overcurrent is substantially the same
as in overvoltage. In the presence of an overcurrent condition when the LT4363 regulates the output current, the
timer charges from 0.5V to 1.275V with a current that
varies as a function of VDS (see Figure 2). The current is
about 5 times the value produced in overvoltage, under
similar conditions VDS, increasing linearly from 8µA with
VDS < 0.5V to 260µA with VDS = 80V. VDS is inferred from
the drop across VCC and OUT. Because VDS is measured
indirectly, clamping or filtering at the VCC pin affects the
timer current response. A graph of Overcurrent TMR Current vs (VCC – VOUT) is shown in the Typical Performance
Characteristics.
VTMR(V)
ITMR = 6µA
ITMR = 6µA
1.375
1.275
VDS = 75V
(ITMR = 50µA)
0.50
TIME
tWARNING
= 16.67ms/µF
tFLT = 96.9ms/µF
tWARNING
= 16.67ms/µF
TOTAL FAULT TIMER = tFLT + tWARNING
CTMR = t WARNING •
ITMR
100mV
When TMR reaches 1.375V, the MOSFET is turned off and
allowed to cool for an extended period. The total elapsed
time between the onset of current limiting and turn-off
is given by:
tLIM = CTMR •
0.875V
ITMR
Because ITMR is a function of VCC – VOUT, the exact time
in current limit depends upon the input waveform and the
time required for the output current to come into regulation.
Cool Down Phase
VDS = 10V
(ITMR = 8µA)
tFLT
= 15.5ms/µF
When TMR reaches 1.275V, the FLT pin is latched low as
an early warning of impending shutdown. But unlike the
overvoltage case, the timer current is not reduced and
instead continues unabated until TMR reaches 1.375V,
producing an early warning period given by:
Cool Down behavior is the same whether initiated by
overvoltage or overcurrent. During the cool down phase,
the timer continues to charge from 1.375V to 4.3V with
2µA, and then discharges back down to 0.5V with 2µA,
for a total equivalent voltage swing of 6.725V. The cool
down time is given by:
4363 F01
tCOOL = CTMR •
Figure 1. Overvoltage Fault Timer Current
VTMR(V)
2.925V + 3.8V
2µA
Up to this point the operation of the LT4363-1 and LT4363-2
is the same. Behavior at the end of the cool down phase
and in response to the SHDN pin is entirely different.
1.375
1.275
VDS = 80V
(ITMR = 260µA)
0.50
tFLT
= 2.98ms/µF
VDS = 10V
(ITMR = 35µA)
TIME
tWARNING
= 0.38ms/µF
tFLT = 22.14ms/µF
TOTAL FAULT TIMER = tFLT + tWARNING
tWARNING
= 2.86ms/µF
Figure 2. Overcurrent Fault Timer Current
4363 F02
At the end of the cool down phase the LT4363-1 remains
latched off and FLT remains low. It may be restarted by
pulling the SHDN pin low for at least 100µs or by cycling
power. The cool down phase may be interrupted at anytime by pulling SHDN low for at least 1s/µF of CTMR; the
LT4363-1 will restart when SHDN goes high.
The LT4363-2 will automatically retry at the end of the
cool down phase. Retry is inhibited if the OV pin is above
1.275V; this prevents repetitive retries while the input is
held in a sustained overvoltage condition. Retry is auto4363fa
12
LT4363
APPLICATIONS INFORMATION
matically initiated once the OV pin falls below 1.268V. OV
has no effect on initial start-up when power is first applied
and upon exiting shutdown. The cool down phase may
be interrupted in the LT4363-2 by pulling SHDN low for
at least 1s/µF of CTMR.
For both the LT4363-1 and LT4363-2 the FLT pin goes
high in shutdown and is cleared high when power is first
applied to VCC. If FLT is set low, it can be reset during the
cool down phase by pulling SHDN low for at least 1s/µF
of CTMR.
Intermittent Fault Conditions
Brief overvoltage or overcurrent conditions interrupt the
operation of the timer. If the TMR pin has not yet reached
1.275V when the input falls below the regulation value
or drops out of current limit, the timer capacitor is discharged back to 0.5V with a 2µA current sink. If the TMR
voltage crosses 1.275V FLT is set low. If the overvoltage
or overcurrent abates before reaching 1.375V, the timer
capacitor discharges with 2µA back to 0.5V, whereupon
FLT resets high. If several short overvoltage or overcurrent
events occur in rapid succession, the timer capacitor will
integrate the charging and discharging currents.
MOSFET Selection
The LT4363 drives an N-channel MOSFET to conduct the
load current. The important features of the MOSFET are
on-resistance RDS(ON), the maximum drain-source voltage
V(BR)DSS, the threshold voltage, and the SOA.
The maximum allowable drain-source voltage must be
higher than the supply voltage. If the output is shorted
to ground or during an overvoltage event, the full supply
voltage will appear across the MOSFET.
The gate drive for the MOSFET is guaranteed to be more
than 10V and less than 16V for those applications with VCC
higher than 9V. This allows the use of standard threshold
voltage N-channel MOSFETs. For systems with VCC less
than 9V, a logic level MOSFET is required since the gate
drive can be as low as 4.5V.
The SOA of the MOSFET must encompass all fault conditions. In normal operation the pass transistor is fully on,
dissipating very little power. But during either overvoltage
or overcurrent faults, the GATE pin is controlled to regulate either the output voltage or the current through the
MOSFET. Large current and high voltage drop across the
MOSFET can coexist in these cases. The SOA curves of
the MOSFET must be considered carefully along with the
selection of the fault timer capacitor.
Transient Stress in the MOSFET
During an overvoltage event, the LT4363 drives a series
pass MOSFET to regulate the output voltage at an acceptable
level. The load circuitry may continue operating throughout
this interval, but only at the expense of dissipation in the
MOSFET pass device. MOSFET dissipation or stress is a
function of the input voltage waveform, regulation voltage
and load current. The MOSFET must be sized to survive
this stress.
Most transient event specifications use the prototypical waveshape shown in Figure 3, comprising a linear
ramp of rise time tr, reaching a peak voltage of VPK and
exponentially decaying back to VIN with a time constant
of τ. A common automotive transient specification has
constants of tr = 10µs, VPK = 80V and τ = 1ms. A surge
condition known as load dump commonly has constants
of tr = 5ms, VPK = 60V and τ = 200ms.
MOSFET stress is the result of power dissipated within
the device. For long duration surges of 100ms or more,
stress is increasingly dominated by heat transfer; this is
a matter of device packaging and mounting, and heat sink
thermal mass. This is best analyzed by simulation, using
the MOSFET thermal model.
For short duration transients of less than 100ms, MOSFET
survival is increasingly a matter of safe operating area
VPK
τ
VIN
tr
4363 F03
Figure 3. Prototypical Transient Waveform
4363fa
13
LT4363
APPLICATIONS INFORMATION
(SOA), an intrinsic property of the MOSFET. SOA quantifies the time required at any given condition of VDS and
ID to raise the junction temperature of the MOSFET to its
rated maximum. MOSFET SOA is expressed in units of
watt-squared-seconds (P2t). This figure is essentially constant for intervals of less than 100ms for any given device
type, and rises to infinity under DC operating conditions.
Destruction mechanisms other than bulk die temperature
distort the lines of an accurately drawn SOA graph so that
P2t is not the same for all combinations of ID and VDS.
In particular P2t tends to degrade as VDS approaches the
maximum rating, rendering some devices useless for
absorbing energy above a certain voltage.
When a fast input voltage step occurs, the current through
the pass transistor to supply the load and charge up the output capacitor can be high enough to trigger an overcurrent
event. The gate pulls low to 1V above the OUT pin, turning
off the MOSFET momentarily. The internal charge pump
will then start to pull the GATE pin high and turn on the
MOSFET to support the load current and charge up the
OUT pin. The fault timer may not start yet because the
current level is below the overcurrent limit threshold and
the output voltage has not reached the servo voltage. This
extra stress needs to be included in calculating the overall
stress level of the MOSFET.
a = VREG – VIN
b = VPK – VIN
(VIN = Nominal Input Voltage)
Then
P 2 t = ILOAD2 •
 1 ( b – a )3 1  2 b

+ τ  2a ln + 3a 2 +b2 − 4ab 
 tr

b
2 
a
 3

Typically VREG ≈ VIN and τ » tr simplifying the above to
1
2
P 2 t = ILOAD2 ( VPK – VREG ) τ
2
[W 2s]
For the transient conditions of VPK = 80V, VIN = 12V,
VREG = 16V, tr = 10µs and τ = 1ms, and a load current
of 3A, P2t is 18.4W2s – easily handled by a MOSFET in
a DPAK package. The P2t of other transient waveshapes
is evaluated by integrating the square of MOSFET power
over time. LTSpice can be used to simulate timer behavior
for more complex transients and cases where overvoltage
and overcurrent faults coexist.
Calculating Short-Circuit Stress
Calculating Transient Stress
To select a MOSFET suitable for any given application, the
SOA stress must be calculated for each input transient
which shall not interrupt operation. It is then a simple matter
to choose a device which has adequate SOA to survive the
maximum calculated stress. P2t for a prototypical transient
waveform is calculated as follows (Figure 4):
VPK
SOA stress must also be calculated for short-circuit conditions. Short-circuit P2t is given by:
2

ΔV 
P t =  ΔVDS • SNS  • t TMR [W 2s]
R


2
SNS
Where ΔVDS is the voltage across the MOSFET, and ΔVSNS
is the SNS pin threshold, and tTMR is the overcurrent timer
interval.
For VIN = 15V, ΔVDS = 13V (VOUT = 2V), ΔVSNS = 50mV,
RSNS = 12mΩ and CTMR = 100nF, P2t is 6.3W2s – less
than the transient SOA calculated in the previous example.
Nevertheless, to account for circuit tolerances this figure
should be doubled to 12.6W2s.
τ
VREG
VIN
Let
tr
4363 F04
Figure 4. Safe Operating Area Required to Survive Prototypical
Transient Waveform
4363fa
14
LT4363
APPLICATIONS INFORMATION
Limiting Inrush Current and GATE Pin Compensation
The LT4363 limits the inrush current to any load capacitance
by controlling the GATE pin voltage slew rate. An external
capacitor can be connected from GATE to ground to reduce
the inrush current at the expense of slower turn-off time.
The gate capacitor is set at:
C1=
IGATE(UP)
IINRUSH
• CL
threshold during a fault. The pass transistor is not allowed
to turn back on even after the cool down period has finished.
This prevents the pass transistor from cycling between ON
and OFF states when the input voltage stays at an elevated
level for a long period of time, reducing the stress on the
N-channel MOSFET. For the latch-off version, LT4363-1,
the overvoltage comparator function is not available.
Reverse Input Protection
The LT4363 does not need extra compensation components at the GATE pin for stability during an overvoltage or
overcurrent event. With transient input voltage slew rates
faster than 5V/µs, a gate capacitor, C1, to ground is needed
to prevent self enhancement of the N-channel MOSFET.
A blocking diode is commonly employed to protect the
load when reverse input is possible, such as in automotive applications. This diode causes extra power loss,
generates heat, and reduces the available supply voltage
range. During cold crank, the extra voltage drop across
the diode is particularly undesirable.
The extra gate capacitance slows down the turn off time
during fault conditions and may allow excessive current
during an output short event. An extra resistor, R1, in series
with the gate capacitor can improve the turn off time. A
diode, D1, should be placed across R1 with the cathode
connected to C1 as shown in Figure 5.
The LT4363 is designed to withstand reverse voltage without damage to itself. The VCC, SHDN, UV, and OV pins can
withstand up to 60V of DC voltage below the GND potential.
Back-to-back MOSFETs must be used to block the current
path through Q1’s body diode (Figure 6). Figure 7 shows
the approach with a P-channel MOSFET in place of Q2.
Q1
Q2
IRLR2908
VIN
12V
D1
IN4148W
D1*
SMAJ58CA
R3
Q3
2N3904
R1
RSNS
10mΩ
Q1
IRLR2908
R4 R5
10Ω 1M
VOUT
12V, 3A
CLAMPED
AT 16V
R3
10Ω
R1
57.6k
C1
GATE
D2
1N4148
R7
10k
C1
47nF
LT4363
4363 F05
5
Figure 5. External GATE network
VCC
The overvoltage comparator prevents the LT4363-2 from
restarting if the voltage at the OV pin is above the 1.275V
2
OUT
FB
1
R2
4.99k
Undervoltage/Overvoltage Comparators
The LT4363 has both undervoltage and overvoltage comparators that can be used to sense the input supply voltage. When the voltage at the UV pin is below the 1.275V
threshold, the GATE pin is held low to keep the external
MOSFET off. The supply voltage at the VCC pin should be
at least 4V for the UV comparator to function.
3
SNS
4
GATE
LT4363DE-2
6
8
7
SHDN
ENOUT
UV
OV
GND
9
*DIODES INC.
FLT
TMR
12
11
10
4363 F06
CTMR
0.1µF
Figure 6. Overvoltage Regulator with N-channel MOSFET
Reverse Input Protection
4363fa
15
LT4363
APPLICATIONS INFORMATION
VIN
12V
Q2
SI7461DP
D1*
SMAJ58CA
R7
10k
5
RSNS
10mΩ
Q1
IRLR2908
D2
1N5245
15V
C1
47nF
VOUT
12V, 3A
CLAMPED
AT 16V
R3
10Ω
4
GATE
VCC
2
OUT
FB
1
LT4363DE-2
8
7
SHDN
ENOUT
OV
GND
9
*DIODES INC.
FLT
TMR
12
11
10
4363 F07
CTMR
0.1µF
Figure 7. Overvoltage Regulator with P-channel MOSFET
Reverse Input Protection
Shutdown
The LT4363 can be shut down to a low current mode when
the voltage at the SHDN pin is pulled below the shutdown
threshold of 0.4V. The quiescent current drops down to
7µA with internal circuitry turned off.
The SHDN pin can be pulled up to 100V or below GND by
up to 60V without damage. Leaving the pin open allows
an internal current source to pull it up and turn on the part
while clamping the pin to 2.2V. The leakage current at the
pin should be limited to no more than 1µA if no pull up
device is used to help turn it on.
Supply Transient Protection
The LT4363 is tested to operate to 80V and guaranteed to
be safe from damage up to 100V. Nevertheless, voltage
transients above 100V may cause permanent damage.
During a short-circuit condition, the large change in current flowing through power supply traces and associated
wiring can cause inductive voltage transients which could
exceed 100V. To minimize the voltage transients, the power
trace parasitic inductance should be minimized by using
wide traces. A small RC filter, in Figure 8, at the VCC pin
will clamp the voltage spikes.
RSNS
10mΩ
VOUT
CL**
22µF
R3
10Ω
3
4
VCC GATE SNS
R1
100k
2
OUT
5
FB
1
R2
4.99k
D1*
SMAJ58A
6
R4
374k
UV
C1
47nF
R7
1k
C2
0.1µF
R2
4.99k
6
VIN
R1
57.6k
3
SNS
Q1
FDB33N25
R5
90.9k
R6
10k
8
SHDN
VCC
LT4363DE-2
DC/DC
CONVERTER
UV
ENOUT
7
OV
GND
9
TMR
12
FLT
11
10
SHDN
FAULT
4363 F08
CTMR
47nF
GND
*DIODES INC.
**SANYO 25CE22GA
Figure 8. Overvoltage Regulator with Input Voltage Detection
Another way to limit transients above 100V at the VCC
pin is to use a Zener diode and a resistor, D1 and R7 in
Figure 8. The Zener diode limits the voltage at the pin
while the resistor limits the current through the diode to
a safe level during the surge. However, D1 can be omitted
if the filtered voltage, due to R7 and C1, at the VCC pin
is below 100V. The inclusion of R7 in series with the VCC
pin will increase the minimum required voltage at VIN due
to the extra voltage drop across it. This voltage drop is
due to the supply current of the LT4363 and the leakage
current of D1.
A total bulk capacitance of at least 22µF low ESR electrolytic is required close to the source pin of MOSFET Q1. In
addition, the bulk capacitance should be at least 10 times
larger than the total ceramic bypassing capacitor on the
input of the DC/DC converter.
Layout Considerations
To achieve accurate current sensing, Kelvin connection
to the current sense resistor (RSNS in Figure 8) is recommended. The minimum trace width for 1 oz copper foil is
0.02" per amp to ensure the trace stays at a reasonable
temperature. 0.03" per amp or wider is recommended.
Note that 1oz copper exhibits a sheet resistance of about
530µΩ/square. Small resistances can cause large errors in
4363fa
16
LT4363
APPLICATIONS INFORMATION
high current applications. Noise immunity will be improved
significantly by locating resistive dividers close to the pins
with short VCC and GND traces.
Design Example
As a design example, take an application with the following specifications: VCC = 8V to 14V DC with a transient of
150V and decay time constant (τ) of 400ms, VOUT ≤ 27V,
current limit (ILIM) at 5A, low battery detection of 6V, input
overvoltage level at 60V, and 1ms of overvoltage early
warning (Figure 8).
Selection of SMAJ58A for D1 will limit the voltage at the
VCC pin to less than 71V during 150V surge. The minimum
required voltage at the VCC pin is 4V when VIN is at 8V;
the supply current for LT4363 is 1.5mA. The maximum
value for R7 to ensure proper operation is:
R7 =
8V – 4V
= 2.67kΩ
1.5mA
Select 1kΩ for R7 to accommodate all conditions.
The maximum current through R7 into D1 is then calculated as:
ID1 =
150V – 64V
= 86mA
1kΩ
Choose 4.99kΩ for R2.
R1=
(27V – 1.275V ) • R2 = 100.7kΩ
1.275V
The nearest standard value for R1 is 100kΩ.
Next calculate the sense resistor, RSNS, value:
RSNS =
50mV 50mV
=
= 10mΩ
ILIM
5A
CTMR is then chosen for 1ms of early warning time:
CTMR =
1ms • 6µA
= 60nF
100mV
The nearest standard value for CTMR is 47nF.
Finally, calculate R4, R5, and R6 for 6V low battery detection and 60V input overvoltage level:
6V •
R5 + R6
= 1.275V
R4 + R5 + R6
60V •
R6
= 1.275V
R4 + R5 + R6
Choose 10kΩ for R6.
60V • 10kΩ
– 10kΩ = 460.6kΩ
1.275V
which is easily handled by the SMAJ58A for more than
500ms.
R4 + R5 =
With 0.1µF of bypass capacitance, C1, along with 1k of
R7, high voltage transients up to 200V with a pulse width
less than 10µs are filtered out at the VCC pin.
R5 = 1.275V •
Next, calculate the resistive divider value to limit VOUT to
27V during an overvoltage event:
1.275V • (R1+ R2)
VREG =
= 27V
R2
Set the current through R1 and R2 during the overvoltage
condition to 250µA.
R2 =
460.6kΩ + 10kΩ
– 10kΩ = 90kΩ
6V
R4 = 460.6kΩ – 90kΩ = 370.6kΩ
Select 90.9kΩ for R5 and 374kΩ for R4.
The pass transistor, Q1, should be chosen to withstand a
short-circuit with VCC = 14V. In the case of a severe output
short where VOUT = 0V, the total overcurrent fault time is:
tOC =
47nF • 0.875V
= 0.904ms
45.5µA
1.275V
= 5kΩ
250µA
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17
LT4363
APPLICATIONS INFORMATION
The power dissipation in Q1 is:
P=
The power dissipation in Q1 is:
14V • 25mV
= 35W
10mΩ
P=
During an output overload or soft short, the voltage at the
OUT pin could stay at 2V or higher. The total overcurrent
fault time when VOUT = 2V is:
tOC =
(14V – 2V ) • 50mV = 60W
10mΩ
These conditions are well within the Safe Operating Area
of the FDB33N25.
47nF • 0.875V
= 1.028ms
40µA
TYPICAL APPLICATIONS
Overvoltage Regulator with Output Keep Alive During Shutdown
VIN
R7
1k
D1*
SMAJ58A
R9
1k, 1W
RSNS
10mΩ
Q1
IRLR2908
CL**
22µF
R3
10Ω
C1
47nF
5
VCC
3
4
GATE SNS
2
OUT
FB
R1
287k
VOUT
12V, 4A
REGULATED
AT 16V
D2
1N4746A
18V
1W
1
R2
24.9k
6
R4
147k
R5
30.1k
R6
10k
8
SHDN
LT4363DE-2
UV
ENOUT
7
OV
GND
9
FLT
TMR
12
4363 TA02
CTMR
0.1µF
11
10
UV = 6V
OV = 24V
*DIODES INC.
**SANYO 25CE22GA
4363fa
18
LT4363
TYPICAL APPLICATIONS
2.5A, 48V Hot Swap with Overvoltage Output Regulation at 72V
VIN
RSNS
15mΩ
Q1
FDB3632
R7
1k
VOUT
48V, 2.5A
CL
300µF
R3
10Ω
C1
47nF
5
D1*
SMAT70A
3
4
GATE SNS
VCC
2
OUT
FB
R1
221k
1
R2
4.02k
6
R4
604k
R5
13k
8
SHDN
LT4363DE-2
UV
ENOUT
7
OV
GND
R6
10k
FLT
TMR
9
12
11
10
UV = 35V
OV = 80V
4363 TA03
CTMR
0.1µF
*DIODES INC.
2.5A, 28V Hot Swap with Overvoltage Output Regulation at 36V
VIN
28V
Q1
IRLR2908
R7
1k
RSNS
15mΩ
VOUT
28V, 2.5A
CL
300µF
R3
10Ω
C1
47nF
5
D1*
SMAJ58A
VCC
3
4
GATE SNS
2
OUT
FB
R1
110k
1
R2
4.02k
6
R4
261k
R5
10k
R6
10k
8
SHDN
LT4363DE-2
UV
ENOUT
7
OV
GND
9
TMR
12
FLT
4363 TA04
CTMR
0.1µF
11
10
UV = 18V
OV = 36V
*DIODES INC.
4363fa
19
LT4363
TYPICAL APPLICATIONS
Overvoltage Regulator with Reverse Input Protection Up to –80V
Q2
IRLR2908
VIN
12V
Q3
2N3904
R5
1M
R1
57.6k
C1
47nF
3
4
GATE SNS
5
VCC
D1*
SMAJ58CA
D3**
1N4148
VOUT
12V, 3A
CL**
CLAMPED
22µF
AT 16V
R3
10Ω
R4
10Ω
D2
1N4148
R7
10k
RSNS
10mΩ
Q1
IRLR2908
2
OUT
FB
1
R2
4.99k
6
8
7
LT4363DE-2
SHDN
UV
ENOUT
OV
GND
*DIODES INC.
**SANYO 25CE22GA
***OPTIONAL COMPONENT
FOR REDUCED STANDBY CURRENT
FLT
TMR
9
12
11
10
4363 TA05
CTMR
0.1µF
Overvoltage Regulator with 250V Surge Protection
VIN
12V
Q1
FDB33N25
R6
49.9k
Q2
MPS-A42
D1*
SMAJ58A
C1
0.1µF
RSNS
10mΩ
CL
22µF
R3
10Ω
R1
57.6k
C1
47nF
5
VCC
R4
127k
6
8
4
3
GATE SNS
FB
R2
4.99k
ENOUT
7
1
LT4363DE-2
R5
49.9k
OV
GND
9
*DIODES INC.
2
OUT
SHDN
UV
OUTPUT
CLAMP
AT 16V
FLT
TMR
12
11
10
VCC
DC/DC
CONVERTER
SHDN GND
FAULT
4363 TA07
0.1µF
4363fa
20
LT4363
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
DE/UE Package
12-Lead Plastic DFN (4mm × 3mm)
(Reference LTC DWG # 05-08-1695 Rev D)
0.70 ±0.05
3.60 ±0.05
2.20 ±0.05
3.30 ±0.05
1.70 ± 0.05
PACKAGE OUTLINE
0.25 ± 0.05
0.50 BSC
2.50 REF
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
4.00 ±0.10
(2 SIDES)
7
R = 0.115
TYP
0.40 ± 0.10
12
R = 0.05
TYP
PIN 1
TOP MARK
(NOTE 6)
0.200 REF
3.30 ±0.10
3.00 ±0.10
(2 SIDES)
1.70 ± 0.10
0.75 ±0.05
6
0.25 ± 0.05
1
PIN 1 NOTCH
R = 0.20 OR
0.35 × 45°
CHAMFER
(UE12/DE12) DFN 0806 REV D
0.50 BSC
2.50 REF
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING PROPOSED TO BE A VARIATION OF VERSION
(WGED) IN JEDEC PACKAGE OUTLINE M0-229
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
4363fa
21
LT4363
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
MS Package
12-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1668 Rev Ø)
4.039 ± 0.102
(.159 ± .004)
(NOTE 3)
12 11 10 9 8 7
0.889 ± 0.127
(.035 ± .005)
0.254
(.010)
DETAIL “A”
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
4.90 ± 0.152
(.193 ± .006)
0° – 6° TYP
0.406 ± 0.076
(.016 ± .003)
REF
GAUGE PLANE
5.23
(.206)
MIN
3.20 – 3.45
(.126 – .136)
0.53 ± 0.152
(.021 ± .006)
DETAIL “A”
0.65
(.0256)
BSC
0.42 ± 0.038
(.0165 ± .0015)
TYP
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
TYP
RECOMMENDED SOLDER PAD LAYOUT
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
1 2 3 4 5 6
1.10
(.043)
MAX
0.86
(.034)
REF
0.1016 ± 0.0508
(.004 ± .002)
0.650
(.0256)
BSC
MSOP (MS12) 1107 REV Ø
S Package
16-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610)
.386 – .394
(9.804 – 10.008)
NOTE 3
.045 ±.005
.050 BSC
16
N
.245
MIN
13
12
11
10
9
.150 – .157
(3.810 – 3.988)
NOTE 3
.228 – .244
(5.791 – 6.197)
2
3
N/2
N/2
RECOMMENDED SOLDER PAD LAYOUT
.010 – .020
× 45°
(0.254 – 0.508)
.008 – .010
(0.203 – 0.254)
1
2
3
4
5
.053 – .069
(1.346 – 1.752)
NOTE:
1. DIMENSIONS IN
.014 – .019
(0.355 – 0.483)
TYP
INCHES
(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
6
7
8
.004 – .010
(0.101 – 0.254)
0° – 8° TYP
.016 – .050
(0.406 – 1.270)
22
14
N
.160 ±.005
1
.030 ±.005
TYP
15
.050
(1.270)
BSC
S16 0502
4363fa
LT4363
REVISION HISTORY
REV
DATE
DESCRIPTION
PAGE NUMBER
A
03/12
Add 57.6k resistor to Typical Application
24
4363fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
23
LT4363
TYPICAL APPLICATION
Overvoltage Regulator with Ideal Diode Reverse Voltage Protection
M1
FDB3632
VIN
12V
IRLR2908
10mΩ
OUTPUT
CLAMP
AT 16V
22µF
10Ω
IN
GATE
OUT
LTC4357
47nF
VDD
DCLAMP
SMAT70A
GND
D1
MMBD1205
VCC GATE SNS
FB
4.99k
SHDN
LT4363
127k
–60V TO 75V DC PROTECTION
100V TRANSIENT MAXIMUM
UV = 4.5V
57.6k
OUT
DC/DC
CONVERTER
UV
ENOUT
49.9k
GND
VCC
SHDN
FLT
TMR
FAULT
GND
4363 TA06
0.1µF
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LTC1696
Overvoltage Protection Controller
ThinSOT™ Package, 2.7V to 28V
LTC2909
Triple/Dual Inputs UV/OV Negative Monitor
Pin Selectable Input Polarity Allows Negative and OV Monitoring
LTC2912/LTC2913
Single/Dual UV/OV Voltage Monitor
Ads UV and OV Trip Values, ±1.5% Threshold Accuracy
LTC2914
Quad UV/OV Monitor
For Positive and Negative Supplies
LTC3827/LTC3827-1 Low IQ, Dual, Synchronous Controller
LTC3835/LTC3835-1 Low IQ, Synchronous Step-Down Controller
4V ≤ VIN ≤ 36V, 0.8V ≤ VOUT ≤ 10V, 80µA Quiescent Current
Single Channel LTC3827/LTC3827-1
LT3845
Low IQ, Synchronous Step-Down Controller
4V ≤ VIN ≤ 60V, 1.23V ≤ VOUT ≤ 36V, 120µA Quiescent Current
LT3850
Dual, 550kHz, 2-Phase Sychronous Step-Down
Controller
Dual 180° Phased Controllers, VIN 4V to 24V, 97% Duty Cycle, 4mm × 4mm
QFN-28, SSOP-28 Packages
LTC3890
Low IQ, Dual 2-Phase, Synchronous Step-Down
Controller
4V ≤ VIN ≤ 60V, 0.8V ≤ VOUT ≤ 24V, 50µA Quiescent Current
LT4256
Positive 48V Hot Swap Controller with
Open-Circuit Detect
Foldback Current Limiting, Open-Circuit and Overcurrent Fault Output, Up to 80V
Supply
LTC4260
Positive High Voltage Hot Swap Controller with
8-Bit ADC and I2C
Wide Operating Range 8.5V to 80V
LT4352
Ideal MOSFET ORing Diode
External N-Channel MOSFETs Replace ORing Diodes, 0V to 18V
LTC4354
Negative Voltage Diode-OR Controller
Controls Two N-Channel MOSFETs, 1µs Turn-Off, 80V Operation
LTC4355
Positive Voltage Diode-OR Controller
Controls Two N-Channel MOSFETs, 0.5µs Turn-Off, 80V Operation
LT4356
High Voltage Surge Stopper
100V Overvoltage and Overcurrent Protection, Latch-Off and Auto-Retry Options
LTC4365
Window Passer - OV, UV and Reverse Supply
Protection Controller
2.5V to 34V Operation, Protects 60V to –40V
4363fa
24 Linear Technology Corporation
LT 0312 REV A • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
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 LINEAR TECHNOLOGY CORPORATION 2011