AD AD8644 Single and quad 18 v operational amplifier Datasheet

a
FEATURES
Unity Gain Bandwidth: 5.5 MHz
Low Voltage Offset: 1.0 mV
Slew Rate: 7.5 V/␮s
Single-Supply Operation: 5 V to 18 V
High Output Current: 70 mA
Low Supply Current: 800 ␮A/Amplifier
Stable with Large Capacitive Loads
Rail-to-Rail Inputs and Outputs
APPLICATIONS
LCD Gamma and VCOM Drivers
Modems
Portable Instrumentation
Direct Access Arrangement
Single and Quad +18 V
Operational Amplifiers
AD8614/AD8644
PIN CONFIGURATIONS
5-Lead SOT-23
(RT Suffix)
OUT A 1
V2 2
They are processed using Analog Devices high voltage, high speed,
complementary bipolar process—HV XFCB. This proprietary
process includes trench isolated transistors that lower internal
parasitic capacitance which improves gain bandwidth, phase margin and capacitive load drive. The low supply current of 800 µA
(typ) per amplifier is critical for portable or densely packed designs.
In addition, the rail-to-rail output swing provides greater dynamic
range and control than standard video amplifiers provide.
AD8614
4 2IN
+IN 3
14-Lead TSSOP
(RU Suffix)
OUT A
2IN A
1IN A
V1
1IN B
2IN B
OUT B
1
14
7
8
OUT D
2IN D
1IN D
V2
1IN C
2IN C
OUT C
AD8644
GENERAL DESCRIPTION
The AD8614 (single) and AD8644 (quad) are single-supply,
5.5 MHz bandwidth, rail-to-rail amplifiers optimized for LCD
monitor applications.
5 V+
14-Lead Narrow Body SO
(R Suffix)
OUT A 1
14
OUT D
–IN A 2
13
–IN D
+IN A 3
12
+IN D
11
V–
+IN B 5
10
+IN C
–IN B 6
9
–IN C
OUT B 7
8
OUT C
V+ 4
AD8644
These products operate from supplies of 5 V to as high as
18 V. The unique combination of an output drive of 70 mA,
high slew rates, and high capacitive drive capability makes the
AD8614/AD8644 an ideal choice for LCD applications.
The AD8614 and AD8644 are specified over the temperature
range of –20°C to +85°C. They are available in 5-lead SOT-23,
14-lead TSSOP and 14-lead SOIC surface mount packages in
tape and reel.
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
World Wide Web Site: http://www.analog.com
Fax: 781/326-8703
© Analog Devices, Inc., 1999
AD8614/AD8644–SPECIFICATIONS
ELECTRICAL CHARACTERISTICS (5 V ≤ V ≤ 18 V, V
S
Parameter
Symbol
INPUT CHARACTERISTICS␣
Offset Voltage
VOS
CM
= VS/2, TA = 25ⴗC unless otherwise noted)
Conditions
Min
–20°C ≤ TA ≤ +85°C
Typ
Max
Unit
1.0
2.5
3
400
500
100
200
VS
mV
mV
nA
nA
nA
nA
V
dB
V/mV
80
Input Bias Current
IB
Input Offset Current
IOS
Input Voltage Range
Common-Mode Rejection Ratio
Voltage Gain
CMRR
AVO
VCM = 0 V to V S
VOUT = 0.5 V to VS –0.5 V, RL = 10 kΩ
OUTPUT CHARACTERISTICS␣
Output Voltage High
Output Voltage Low
Output Short Circuit Current
VOH
VOL
ISC
ILOAD = 10 mA
ILOAD = 10 mA
–20°C ≤ TA ≤ +85°C
VS –0.15
65
35
70
30
POWER SUPPLY␣
PSRR
Supply Current / Amplifier
PSRR
Isy
VS = ± 2.25 V to ± 9.25 V
80
DYNAMIC PERFORMANCE␣
Slew Rate
Gain Bandwidth Product
Phase Margin
Settling Time
SR
GBP
Φo
tS
CL = 200 pF
en
en
in
NOISE PERFORMANCE
Voltage Noise Density
Current Noise Density
–20°C ≤ TA ≤ +85°C
5
–20°C ≤ TA ≤ +85°C
0
60
10
75
150
150
110
0.8
–20°C ≤ TA ≤ +85°C
1.1
1.5
V
mV
mA
mA
dB
mA
mA
0.01%, 10 V Step
7.5
5.5
65
3
V/µs
MHz
Degrees
µs
f = 1 kHz
f = 10 kHz
f = 10 kHz
12
11
1
nV/√Hz
nV/√Hz
pA/√Hz
NOTE
All typical values are for VS = 18 V.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS
1
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VS
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range . . . . . . . . . . . –20°C to +85°C
Junction Temperature Range . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
Package Type
␪JA1
␪JC
Unit
5-Lead SOT-23 (RT)
14-Lead TSSOP (RU)
14-Lead SOIC (R)
230
180
120
140
35
56
°C/W
°C/W
°C/W
NOTE
1
θ JA is specified for worst-case conditions, i.e., θ JA is specified for device soldered
onto a circuit board for surface mount packages.
NOTES
1
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational sections
of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
ORDERING GUIDE
Model
Temperature
Range
AD8614ART1 –20°C to +85°C
AD8644ARU2 –20°C to +85°C
AD8644AR2
–20°C to +85°C
Package
Description
Package
Option
5-Lead SOT-23 RT-5
14-Lead TSSOP RU-14
14-Lead SOIC
R-14
NOTES
1
Available in 3,000 or 10,000 piece reels.
2
Available in 2,500 piece reels only.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD8614/AD8644 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper
ESD precautions are recommended to avoid performance degradation or loss of functionality.
–2–
WARNING!
ESD SENSITIVE DEVICE
REV. 0
Typical Performance Characteristics – AD8614/AD8644
12
30
25
20
15
+OS
10
2OS
5
0
10
100
1k
CAPACITANCE – pF
4
24
0.1%
0
135
180
0.01%
0
0.5
1.0
1.5
2.0
2.5
SETTLING TIME – ms
3.0
3.5
1k
10k
100k
1M
10M
FREQUENCY – Hz
100M
Figure 3. Open-Loop Gain and Phase
vs. Frequency
Figure 2. Settling Time
29
7.5
VS = 5V
RL = 2kV
CL = 200pF
AV = 1
TA = 258C
5.5
4.5
25
21
VOLTAGE – 4V/Div
6.5
VOLTAGE – 1V/Div
90
5V # VS # 18V
RL = 1MV
CL = 40pF
TA = 258C
20
28
Figure 1. Small Signal Overshoot vs.
Load Capacitance
3.5
2.5
1.5
0.5
17
VS = 18V
RL = 2kV
CL = 200pF
AV = 1
TA = 258C
13
9
5
1
VS
2
VS = 5V # VS # 18V
RL = 2kV
CL = 200pF
AV = 1
TA = 258C
23
20.5
21.5
27
22.5
211
TIME – 1ms/Div
TIME – 500ns/Div
TIME – 1ms/Div
Figure 4. Large Signal Transient
Response
Figure 6. Small Signal Transient
Response
Figure 5. Large Signal Transient
Response
1,000
SUPPLY CURRENT/AMPLIFIER – mA
5V # VS # 18V
TA = 258C
1k
100
SINK
10
1
0.001
SOURCE
0.01
0.1
1
10
LOAD CURRENT – mA
100
Figure 7. Output Voltage to Supply
Rail vs. Load Current
REV. 0
900
400
300
TA = 258C
INPUT BIAS CURRENT – nA
10k
DOUTPUT VOLTAGE – mV
40
0
212
10k
45
60
0.01%
0.1%
PHASE SHIFT – Degrees
35
80
8
VOLTAGE – 50mV/Div
40
GAIN – dB
VS = 18V
RL = 2kV
TA = 258C
45
OUTPUT SWING FROM 0 TO 6 V
SMALL SIGNAL OVERSHOOT – %
50
800
700
600
500
400
300
200
100
0
2100
2200
2300
100
0
0
VS = 62.5V
200
1
2 3
4 5
6 7 8
SUPPLY VOLTAGE – 6Volts
9
10
Figure 8. Supply Current vs. Supply
Voltage
–3–
2400
22.5
21.5
20.5
0.5
1.5
COMMON-MODE VOLTAGE – Volts
2.5
Figure 9. Input Bias Current vs.
Common-Mode Voltage
AD8614/AD8644
180
300
160
INPUT BIAS CURRENT – nA
VS = 69V
QUANTITY – Amplifiers
200
100
0
2100
2200
1.0
2.5V # VS # 9V
TA = 258C
SUPPLY CURRENT/AMPLIFIER – mA
400
140
120
100
2300
80
60
40
20
2400
29 27 25 23 21 0 1
3
5
7
COMMON-MODE VOLTAGE – Volts
0
9
Figure 10. Input Bias Current vs.
Common-Mode Voltage
22 21.5 21 20.5 0 0.5 1 1.5
INPUT OFFSET VOLTAGE – mV
0.8
0.7
VS = 5V
0.6
0.5
235
2
Figure 11. Input Offset Voltage
Distribution
3
2
12
10
8
6
180
120
60
4
1
1k
10k
100k
FREQUENCY – Hz
1M
Figure 13. Maximum Output Swing
vs. Frequency
AV = 100
0
100
10M
1k
10k
100k
FREQUENCY – Hz
1M
0
10M
20
0
1k
10k
100k
1M
10M
FREQUENCY – Hz
100M
Figure 16. Closed-Loop Gain vs.
Frequency
10k
100k
1M
FREQUENCY – Hz
10M
100
5V # VS # 18V
TA = 258C
POWER-SUPPLY REJECTION – dB
COMMON-MODE REJECTION – dB
GAIN – dB
40
120
1k
Figure 15. Closed-Loop Output
Impedance vs. Frequency
Figure 14. Maximum Output Swing
vs. Frequency
140
5V # VS # 18V
TA = 258C
AV = 1
AV = 10
2
0
100
85
240
VS = 18V
AVCL = 1
RL = 2kV
TA = 258C
14
IMPEDANCE – V
OUTPUT SWING – V p-p
OUTPUT SWING – V p-p
4
65
5V # VS # 18V
TA = 258C
16
VS = 5V
AVCL = 1
RL = 2kV
TA = 258C
5
25
45
TEMPERATURE – 8C
300
18
5
215
Figure 12. Supply Current vs.
Temperature
20
6
VS = 18V
0.9
100
80
60
40
20
0
100
1k
10k
100k
FREQUENCY – Hz
1M
10M
Figure 17. Common-Mode Rejection
vs. Frequency
–4–
VS = 18V
TA = 258C
80
60
PSRR+
40
PSRR2
20
0
100
1k
10k
100k
FREQUENCY – Hz
1M
10M
Figure 18. Power-Supply Rejection
vs. Frequency
REV. 0
AD8614/AD8644
100
8
SR+
SLEW RATE – V/ms
7
6
SR2
5
4
3
AV = 1
RL = 2kV
CL = 200pF
TA = 258C
2
1
0
10
1
0
2
4
6
8 10 12 14 16 18
SUPPLY VOLTAGE – V
20
Figure 19. Slew Rate vs. Supply
Voltage
100
VS = 5V
TA = 258C
VOLTAGE NOISE DENSITY – nV Hz
VOLTAGE NOISE DENSITY – nV Hz
9
10
100
1k
FREQUENCY – Hz
10k
Figure 20. Voltage Noise Density
vs. Frequency
APPLICATIONS SECTION
Theory of Operation
VS = 18V
TA = 258C
10
1
10
100
1k
FREQUENCY – Hz
Figure 21. Voltage Noise Density vs.
Frequency
The AD8614/AD8644 have no built-in short circuit protection.
The short circuit limit is a function of high current roll-off of the
output stage transistors and the voltage drop over the resistor
shown on the schematic at the output stage. The voltage over this
resistor is clamped to one diode during short circuit voltage events.
The AD8614/AD8644 are processed using Analog Devices’ high
voltage, high speed, complementary bipolar process—HV XFCB.
This process includes trench isolated transistors that lower parasitic
capacitance.
Output Short-Circuit Protection
Figure 22 shows a simplified schematic of the AD8614/AD8644.
The input stage is rail-to-rail, consisting of two complementary
differential pairs, one NPN pair and one PNP pair. The input stage
is protected against avalanche breakdown by two back-to-back
diodes. Each input has a 1.5 kΩ resistor that limits input current
during over-voltage events and furnishes phase reversal protection
if the inputs are exceeded. The two differential pairs are connected
to a double-folded cascode. This is the stage in the amplifier with
the most gain. The double folded cascode differentially feeds the
output stage circuitry. Two complementary common emitter transistors are used as the output stage. This allows the output to swing
to within 125 mV from each rail with a 10 mA load. The gain of the
output stage, and thus the open loop gain of the op amp, depends on
the load resistance.
To achieve a wide bandwidth and high slew rate, the output of
the AD8614/AD8644 is not short-circuit protected. Shorting
the output directly to ground or to a supply rail may destroy the
device. The typical maximum safe output current is 70 mA.
In applications where some output current protection is needed,
but not at the expense of reduced output voltage headroom, a low
value resistor in series with the output can be used. This is shown
in Figure 23. The resistor is connected within the feedback loop
of the amplifier so that if VOUT is shorted to ground and VIN
swings up to 18 V, the output current will not exceed 70 mA.
For 18 V single supply applications, resistors less than 261 Ω are
not recommended.
VCC
2 1.5kV
1.5kV +
VCC
VOUT
VCC
VEE
Figure 22. Simplified Schematic
REV. 0
10k
–5–
AD8614/AD8644
The power dissipated by the device can be calculated as:
18V
PDISS = ILOAD × (VS – VOUT)
VIN
where: ILOAD is the AD86x4 output load current;
261V
AD86x4
VOUT
VS is the AD86x4 supply voltage; and
VOUT is the AD86x4 output voltage.
Figure 24 provides a convenient way to see if the device is being
overheated. The maximum safe power dissipation can be found
graphically, based on the package type and the ambient temperature around the package. By using the previous equation, it
is a simple matter to see if PDISS exceeds the device’s power
derating curve. To ensure proper operation, it is important to
observe the recommended derating curves shown in Figure 24.
Figure 23. Output Short-Circuit Protection
Input Overvoltage Protection
As with any semiconductor device, whenever the condition exists for
the input to exceed either supply voltage, attention needs to be paid
to the input overvoltage characteristic. As an overvoltage occurs, the
amplifier could be damaged, depending on the voltage level and the
magnitude of the fault current. When the input voltage exceeds
either supply by more than 0.6 V, internal pin junctions energize,
allowing current to flow from the input to the supplies. Observing
Figure 22, the AD8614/AD8644 has 1.5 kΩ resistors in series with
each input, which helps limit the current. This input current is not
inherently damaging to the device as long as it is limited to 5 mA or
less. If the voltage is large enough to cause more than 5 mA of current to flow, an external series resistor should be added. The size of
this resistor is calculated by dividing the maximum overvoltage by
5 mA and subtracting the internal 1.5 kΩ resistor. For example, if
the input voltage could reach 100 V, the external resistor should be
(100 V/5 mA) – 1.5 kΩ = 18.5 kΩ. This resistance should be placed
in series with either or both inputs if they are subjected to the overvoltages. For more information on general overvoltage characteristics
of amplifiers refer to the 1993 System Applications Guide, available
from the Analog Devices Literature Center.
MAXIMUM POWER DISSIPATION – Watts
1.5
14-LEAD SOIC PACKAGE
uJA = 1208C/W
1.0
14-LEAD TSSOP PACKAGE
uJA = 1808C/W
0.5
5-LEAD SOT-23 PACKAGE
uJA = 2308C/W
0
–35
–15
5
25
45
AMBIENT TEMPERATURE – 8C
65
85
Figure 24. Maximum Power Dissipation vs. Temperature
for 5-Lead and 14-Lead Package Types
Output Phase Reversal
Unused Amplifiers
The AD8614/AD8644 is immune to phase reversal as long as the
input voltage is limited to within the supply rails. Although the
device’s output will not change phase, large currents due to
input overvoltage could result, damaging the device. In applications where the possibility of an input voltage exceeding the
supply voltage exists, overvoltage protection should be used, as
described in the previous section.
It is recommended that any unused amplifiers in the quad package be configured as a unity gain follower with a 1 kΩ feedback
resistor connected from the inverting input to the output, and
the noninverting input tied to the ground plane.
Capacitive Load Drive
The AD8614/AD8644 exhibits excellent capacitive load driving
capabilities. Although the device is stable with large capacitive
loads, there is a decrease in amplifier bandwidth as the capacitive
load increases.
Power Dissipation
The maximum power that can be safely dissipated by the
AD8614/AD8644 is limited by the associated rise in junction
temperature. The maximum safe junction temperature is 150°C,
and should not be exceeded or device performance could suffer.
If this maximum is momentarily exceeded, proper circuit operation will be restored as soon as the die temperature is reduced.
Leaving the device in an “overheated” condition for an extended
period can result in permanent damage to the device.
When driving heavy capacitive loads directly from the AD8614/
AD8644 output, a snubber network can be used to improve the
transient response. This network consists of a series R-C connected
from the amplifier’s output to ground, placing it in parallel with the
capacitive load. The configuration is shown in Figure 25. Although
this network will not increase the bandwidth of the amplifier, it will
significantly reduce the amount of overshoot.
To calculate the internal junction temperature of the AD86x4,
the following formula can be used:
TJ = PDISS × θJA + TA
5V
where: TJ = AD86x4 junction temperature;
PDISS = AD86x4 power dissipation;
VOUT
AD86x4
θJA = AD86x4 package thermal resistance, junction-toambient; and
VIN
RX
CL
CX
TA = Ambient temperature of the circuit.
Figure 25. Snubber Network Compensation for Capacitive
Loads
–6–
REV. 0
AD8614/AD8644
5V
The optimum values for the snubber network should be determined
empirically based on the size of the capacitive load. Table I shows a
few sample snubber network values for a given load capacitance.
5V
VDD
VDD 28
U1-A
Table I. Snubber Networks for Large Capacitive Loads
Snubber Network
(RS, CS)
0.47 nF
4.7 nF
47 nF
300 Ω, 0.1 µF
30 Ω, 1 µF
5 Ω, 1 µF
AD1881
(AC'97)
6
RIGHTOUT 36
1
R5
10kV
6.2V
ZO
600V
If gain is required from the output amplifier, four additional
resistors should be added as shown in Figure 28. The gain of
the AD8644 can be set as:
AV =
5V
VDD
A2
R11
10kV
3
A3
1
5
R14
R13
10kV 14.3kV
A1, A2 = 1/2 AD8644
A3, A4 = 1/2 AD8644
1
R1
2kV
5
A4
7
6
AD1881
(AC97)
R5
10kV
RIGHTOUT 36
C2
100mF
7
U1-B
9
8
R6
20kV
NOTE: ADDITIONAL PINS
OMITTED FOR CLARITY
RECEIVE
RxA
R2
2kV
U1 = AD8644
AV =
R6
= +6dB WITH VALUES SHOWN
R5
Figure 28. A PC-99-Compliant Headphone/Speaker
Amplifier with Gain
C2
0.1mF
Input coupling capacitors are not required for either circuit as
the reference voltage is supplied from the AD1881.
Figure 26. A Single-Supply Direct Access Arrangement for
Modems
R4 and R5 help protect the AD8644 output in case the output
jack or headphone wires are accidentally shorted to ground.
The output coupling capacitors C1 and C2 block dc current
from the headphones and create a high-pass filter with a corner
frequency of:
A One-Chip Headphone/Microphone Preamplifier Solution
Because of its high output current performance, the AD8644
makes an excellent amplifier for driving an audio output jack in
a computer application. Figure 27 shows how the AD8644 can
be interfaced with an ac codec to drive headphones or speakers
f −3dB =
1
2πC1(R4 + RL )
Where RL is the resistance of the headphones.
REV. 0
R4
20V
VSS
R8
10kV
P2
Rx GAIN
ADJUST
2kV
6
R12
10kV
U1-A
R3
20V
5
R7
10kV
R10
10kV
2
C1
100mF
10
2
R5
10kV
VREF 27
10mF
R9
10kV
5V
TRANSMIT
TxA
3
6
7
R6
R5
R6
20kV
VDD 38
5V DC
R6
10kV
R2
2kV
Figure 27. A PC-99 Compliant Headphone/Line Out Amplifier
4
6.2V
T1
MIDCOM
671-8005
R4
20V
U1 = AD8644
3
C1
R1
10kV 0.1mF
2
A1
9
NOTE: ADDITIONAL PINS
OMITTED FOR CLARITY
R2
9.09kV
2kV
R3
360V
U1-B
8
LEFTOUT 35
1:1
C2
100mF
7
VSS
Figure 26 shows a schematic for a 5 V single supply transmit/receive
telephone line interface for 600 Ω transmission systems. It allows
full duplex transmission of signals on a transformer-coupled 600 Ω
line. Amplifier A1 provides gain that can be adjusted to meet the
modem output drive requirements. Both A1 and A2 are configured
to apply the largest possible differential signal to the transformer.
The largest signal available on a single 5 V supply is approximately
4.0 V p-p into a 600 Ω transmission system. Amplifier A3 is configured as a difference amplifier to extract the receive information from
the transmission line for amplification by A4. A3 also prevents the
transmit signal from interfering with the receive signal. The gain of
A4 can be adjusted in the same manner as A1’s to meet the modem’s
input signal requirements. Standard resistor values permit the use of
SIP (Single In-Line Package) format resistor arrays. Couple this with
the AD8644 14-lead SOIC or TSSOP package and this circuit can
offer a compact solution.
TO TELEPHONE
LINE
R1
2kV
3
5
Direct Access Arrangement
P1
Tx GAIN
ADJUST
R3
20V
1
4
LEFTOUT 35
Load Capacitance
(CL)
C1
100mF
10
2
–7–
AD8614/AD8644
The remaining two amplifiers can be used as low voltage
microphone preamplifiers. A single AD8614 can be used as a
stand-alone microphone preamplifier. Figure 29 shows this
implementation.
The SPICE model for the AD8614/AD8644 amplifier is available
and can be downloaded from the Analog Devices’ web site at
http://www.analog.com. The macro-model accurately simulates
a number of AD8614/AD8644 parameters, including offset voltage, input common-mode range, and rail-to-rail output swing.
The output voltage versus output current characteristic of the
macro-model is identical to the actual AD8614/AD8644 performance, which is a critical feature with a rail-to-rail amplifier model.
The model also accurately simulates many ac effects, such as gain
bandwidth product, phase margin, input voltage noise, CMRR and
PSRR versus frequency, and transient response. Its high degree of
model accuracy makes the AD8614/AD8644 macro-model one of
the most reliable and true-to-life models available for any amplifier.
5V
2.2kV
AV = 20dB
1kV
1mF
MIC 1 IN 21
MIC 1
10kV
AD1881
(AC'97)
5V
AV = +20dB
C3735–8–10/99
10kV
SPICE Model Availability
2.2kV
1kV
1mF
MIC 2 IN 22
MIC 2
VREF 27
Figure 29. Microphone Preamplifier
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
5-Lead SOT-23
(RT Suffix)
0.1181 (3.00)
0.1102 (2.80)
0.0669 (1.70)
0.0590 (1.50)
5
1
4
2
0.1181 (3.00)
0.1024 (2.60)
3
PIN 1
0.0374 (0.95) BSC
0.0748 (1.90)
BSC
0.0512 (1.30)
0.0354 (0.90)
0.0079 (0.20)
0.0031 (0.08)
0.0571 (1.45)
0.0374 (0.95)
0.0059 (0.15)
0.0019 (0.05)
0.0197 (0.50)
0.0138 (0.35)
SEATING
PLANE
108
08
0.0217 (0.55)
0.0138 (0.35)
14-Lead Narrow SOIC
(R Suffix)
0.201 (5.10)
0.193 (4.90)
0.3444 (8.75)
0.3367 (8.55)
8
0.1574 (4.00)
0.1497 (3.80)
0.256 (6.50)
0.246 (6.25)
0.177 (4.50)
0.169 (4.30)
14
1
14
8
1
7
PIN 1
0.0098 (0.25)
0.0040 (0.10)
7
0.2440 (6.20)
0.2284 (5.80)
0.0688 (1.75)
0.0532 (1.35)
PIN 1
0.006 (0.15)
0.002 (0.05)
SEATING
PLANE
0.0433
(1.10)
MAX
0.0256
(0.65)
BSC
PRINTED IN U.S.A.
14-Lead TSSOP
(RU Suffix)
0.0118 (0.30)
0.0075 (0.19)
0.0079 (0.20)
0.0035 (0.090)
0.0500
SEATING (1.27)
PLANE BSC
88
08
0.0192 (0.49)
0.0138 (0.35)
0.0099 (0.25)
0.0075 (0.19)
0.0196 (0.50)
x 45ⴗ
0.0099 (0.25)
8ⴗ
0ⴗ 0.0500 (1.27)
0.0160 (0.41)
0.028 (0.70)
0.020 (0.50)
–8–
REV. 0