NSC LM2596T-5.0 Simple switcher power converter 150 khz 3a step-down voltage regulator Datasheet

LM2596
SIMPLE SWITCHER ® Power Converter 150 kHz
3A Step-Down Voltage Regulator
General Description
Features
The LM2596 series of regulators are monolithic integrated
circuits that provide all the active functions for a step-down
(buck) switching regulator, capable of driving a 3A load with
excellent line and load regulation. These devices are available in fixed output voltages of 3.3V, 5V, 12V, and an adjustable output version.
Requiring a minimum number of external components, these
regulators are simple to use and include internal frequency
compensation†, and a fixed-frequency oscillator.
The LM2596 series operates at a switching frequency of
150 kHz thus allowing smaller sized filter components than
what would be needed with lower frequency switching regulators. Available in a standard 5-lead TO-220 package with
several different lead bend options, and a 5-lead TO-263
surface mount package.
A standard series of inductors are available from several
different manufacturers optimized for use with the LM2596
series. This feature greatly simplifies the design of
switch-mode power supplies.
Other features include a guaranteed ± 4% tolerance on output voltage under specified input voltage and output load
conditions, and ± 15% on the oscillator frequency. External
shutdown is included, featuring typically 80 µA standby current. Self protection features include a two stage frequency
reducing current limit for the output switch and an over
temperature shutdown for complete protection under fault
conditions.
n 3.3V, 5V, 12V, and adjustable output versions
n Adjustable version output voltage range, 1.2V to 37V
± 4% max over line and load conditions
n Available in TO-220 and TO-263 packages
n Guaranteed 3A output load current
n Input voltage range up to 40V
n Requires only 4 external components
n Excellent line and load regulation specifications
n 150 kHz fixed frequency internal oscillator
n TTL shutdown capability
n Low power standby mode, IQ typically 80 µA
n High efficiency
n Uses readily available standard inductors
n Thermal shutdown and current limit protection
Typical Application
Applications
n Simple high-efficiency step-down (buck) regulator
n On-card switching regulators
n Positive to negative converter
Note: †Patent Number 5,382,918.
(Fixed Output Voltage
Versions)
01258301
SIMPLE SWITCHER ® and Switchers Made Simple ® are registered trademarks of National Semiconductor Corporation.
© 2002 National Semiconductor Corporation
DS012583
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LM2596 SIMPLE SWITCHER Power Converter 150 kHz 3A Step-Down Voltage Regulator
May 2002
LM2596
Connection Diagrams and Ordering Information
Bent and Staggered Leads, Through Hole
Package
5-Lead TO-220 (T)
Surface Mount Package
5-Lead TO-263 (S)
01258303
01258302
Order Number LM2596S-3.3, LM2596S-5.0,
LM2596S-12 or LM2596S-ADJ
See NS Package Number TS5B
Order Number LM2596T-3.3, LM2596T-5.0,
LM2596T-12 or LM2596T-ADJ
See NS Package Number T05D
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2
Human Body Model (Note 2)
(Note 1)
Lead Temperature
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Maximum Supply Voltage
ON /OFF Pin Input Voltage
2 kV
S Package
45V
Vapor Phase (60 sec.)
+215˚C
Infrared (10 sec.)
+245˚C
−0.3 ≤ V ≤ +25V
T Package (Soldering, 10 sec.)
+260˚C
−0.3 ≤ V ≤+25V
Maximum Junction Temperature
+150˚C
Feedback Pin Voltage
Output Voltage to Ground
(Steady State)
−1V
Power Dissipation
Internally limited
Storage Temperature Range
−65˚C to +150˚C
Operating Conditions
−40˚C ≤ TJ ≤ +125˚C
Temperature Range
Supply Voltage
ESD Susceptibility
4.5V to 40V
LM2596-3.3
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range
LM2596-3.3
Symbol
Parameter
Conditions
Typ
(Note 3)
Limit
(Note 4)
Units
(Limits)
SYSTEM PARAMETERS (Note 5) Test Circuit Figure 1
VOUT
η
Output Voltage
Efficiency
4.75V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
VIN = 12V, ILOAD = 3A
3.3
V
3.168/3.135
V(min)
3.432/3.465
V(max)
73
%
LM2596-5.0
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range
LM2596-5.0
Symbol
Parameter
Conditions
Typ
(Note 3)
Limit
(Note 4)
Units
(Limits)
SYSTEM PARAMETERS (Note 5) Test Circuit Figure 1
VOUT
η
Output Voltage
Efficiency
7V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
VIN = 12V, ILOAD = 3A
5.0
V
4.800/4.750
V(min)
5.200/5.250
V(max)
80
%
LM2596-12
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range
LM2596-12
Symbol
Parameter
Conditions
Typ
(Note 3)
Limit
(Note 4)
Units
(Limits)
SYSTEM PARAMETERS (Note 5) Test Circuit Figure 1
VOUT
η
Output Voltage
Efficiency
15V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
VIN = 25V, ILOAD = 3A
12.0
90
3
V
11.52/11.40
V(min)
12.48/12.60
V(max)
%
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LM2596
Absolute Maximum Ratings
LM2596
LM2596-ADJ
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range
LM2596-ADJ
Symbol
Parameter
Conditions
Typ
(Note 3)
Limit
(Note 4)
Units
(Limits)
SYSTEM PARAMETERS (Note 5) Test Circuit Figure 1
VFB
Feedback Voltage
4.5V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
1.230
V
VOUT programmed for 3V. Circuit of Figure 1
η
Efficiency
VIN = 12V, VOUT = 3V, ILOAD = 3A
1.193/1.180
V(min)
1.267/1.280
V(max)
73
%
All Output Voltage Versions
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V for the 3.3V, 5V, and Adjustable version and VIN = 24V for the 12V version. ILOAD = 500 mA
LM2596-XX
Symbol
Parameter
Conditions
Typ
(Note 3)
Limit
(Note 4)
Units
(Limits)
DEVICE PARAMETERS
Ib
fO
VSAT
DC
ICL
IL
Feedback Bias Current
Oscillator Frequency
Saturation Voltage
Adjustable Version Only, VFB = 1.3V
(Note 6)
IOUT = 3A (Notes 7, 8)
(Note 8)
100
Min Duty Cycle (OFF)
(Note 9)
0
Current Limit
Peak Current (Notes 7, 8)
127/110
kHz(min)
173/173
kHz(max)
1.4/1.5
V(max)
kHz
Quiescent Current
(Note 9)
ISTBY
Standby Quiescent Current
ON/OFF pin = 5V (OFF)
V
%
4.5
Output = 0V (Notes 7, 9)
IQ
Thermal Resistance
nA (max)
1.16
Max Duty Cycle (ON)
Output Leakage Current
nA
50/100
150
Output = −1V (Note 10)
θJC
10
A
3.6/3.4
A(min)
6.9/7.5
A(max)
50
µA(max)
30
mA(max)
2
mA
5
(Note 10)
mA
10
mA(max)
200/250
µA(max)
80
µA
TO-220 or TO-263 Package, Junction to Case
2
˚C/W
θJA
TO-220 Package, Junction to Ambient (Note 11)
50
˚C/W
θJA
TO-263 Package, Junction to Ambient (Note 12)
50
˚C/W
θJA
TO-263 Package, Junction to Ambient (Note 13)
30
˚C/W
θJA
TO-263 Package, Junction to Ambient (Note 14)
20
˚C/W
1.3
V
ON/OFF CONTROL Test Circuit Figure 1
ON /OFF Pin Logic Input
VIH
Threshold Voltage
VIL
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Low (Regulator ON)
0.6
V(max)
High (Regulator OFF)
2.0
V(min)
4
LM2596
All Output Voltage Versions
Electrical Characteristics (Continued)
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V for the 3.3V, 5V, and Adjustable version and VIN = 24V for the 12V version. ILOAD = 500 mA
LM2596-XX
Symbol
IH
Parameter
Conditions
ON /OFF Pin Input Current
IL
Typ
(Note 3)
VLOGIC = 2.5V (Regulator OFF)
Limit
(Note 4)
5
VLOGIC = 0.5V (Regulator ON)
Units
(Limits)
µA
15
µA(max)
5
µA(max)
0.02
µA
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.
Note 2: The human body model is a 100 pF capacitor discharged through a 1.5k resistor into each pin.
Note 3: Typical numbers are at 25˚C and represent the most likely norm.
Note 4: All limits guaranteed at room temperature (standard type face) and at temperature extremes (bold type face). All room temperature limits are 100%
production tested. All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Note 5: External components such as the catch diode, inductor, input and output capacitors, and voltage programming resistors can affect switching regulator
system performance. When the LM2596 is used as shown in the Figure 1 test circuit, system performance will be as shown in system parameters section of Electrical
Characteristics.
Note 6: The switching frequency is reduced when the second stage current limit is activated.
Note 7: No diode, inductor or capacitor connected to output pin.
Note 8: Feedback pin removed from output and connected to 0V to force the output transistor switch ON.
Note 9: Feedback pin removed from output and connected to 12V for the 3.3V, 5V, and the ADJ. version, and 15V for the 12V version, to force the output transistor
switch OFF.
Note 10: VIN = 40V.
Note 11: Junction to ambient thermal resistance (no external heat sink) for the TO-220 package mounted vertically, with the leads soldered to a printed circuit board
with (1 oz.) copper area of approximately 1 in2.
Note 12: Junction to ambient thermal resistance with the TO-263 package tab soldered to a single printed circuit board with 0.5 in2 of (1 oz.) copper area.
Note 13: Junction to ambient thermal resistance with the TO-263 package tab soldered to a single sided printed circuit board with 2.5 in2 of (1 oz.) copper area.
Note 14: Junction to ambient thermal resistance with the TO-263 package tab soldered to a double sided printed circuit board with 3 in2 of (1 oz.) copper area on
the LM2596S side of the board, and approximately 16 in2 of copper on the other side of the p-c board. See Application Information in this data sheet and the thermal
model in Switchers Made Simple™ version 4.3 software.
Typical Performance Characteristics
Normalized
Output Voltage
(Circuit of Figure 1)
Line Regulation
01258304
Efficiency
01258305
5
01258306
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LM2596
Typical Performance Characteristics
Switch Saturation
Voltage
(Circuit of Figure 1) (Continued)
Switch Current Limit
01258307
Operating
Quiescent Current
01258310
Minimum Operating
Supply Voltage
01258311
ON /OFF Pin
Current (Sinking)
01258313
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01258309
01258308
Shutdown
Quiescent Current
ON /OFF Threshold
Voltage
Dropout Voltage
Switching Frequency
01258314
6
01258312
01258315
LM2596
Typical Performance Characteristics
(Circuit of Figure 1) (Continued)
Feedback Pin
Bias Current
01258316
7
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LM2596
Typical Performance Characteristics
Discontinuous Mode Switching Waveforms
VIN = 20V, VOUT = 5V, ILOAD = 500 mA
L = 10 µH, COUT = 330 µF, COUT ESR = 45 mΩ
Continuous Mode Switching Waveforms
VIN = 20V, VOUT = 5V, ILOAD = 2A
L = 32 µH, COUT = 220 µF, COUT ESR = 50 mΩ
01258317
01258318
Horizontal Time Base: 2 µs/div.
Horizontal Time Base: 2 µs/div.
A: Output Pin Voltage, 10V/div.
A: Output Pin Voltage, 10V/div.
B: Inductor Current 1A/div.
B: Inductor Current 0.5A/div.
C: Output Ripple Voltage, 50 mV/div.
C: Output Ripple Voltage, 100 mV/div.
Load Transient Response for Discontinuous Mode
VIN = 20V, VOUT = 5V, ILOAD = 500 mA to 2A
L = 10 µH, COUT = 330 µF, COUT ESR = 45 mΩ
Load Transient Response for Continuous Mode
VIN = 20V, VOUT = 5V, ILOAD = 500 mA to 2A
L = 32 µH, COUT = 220 µF, COUT ESR = 50 mΩ
01258320
Horizontal Time Base: 200 µs/div.
01258319
A: Output Voltage, 100 mV/div. (AC)
Horizontal Time Base: 100 µs/div.
B: 500 mA to 2A Load Pulse
A: Output Voltage, 100 mV/div. (AC)
B: 500 mA to 2A Load Pulse
Test Circuit and Layout Guidelines
Fixed Output Voltage Versions
01258322
CIN
— 470 µF, 50V, Aluminum Electrolytic Nichicon “PL Series”
COUT
— 220 µF, 25V Aluminum Electrolytic, Nichicon “PL Series”
D1
— 5A, 40V Schottky Rectifier, 1N5825
L1
— 68 µH, L38
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LM2596
Test Circuit and Layout Guidelines
(Continued)
Adjustable Output Voltage Versions
01258323
where VREF = 1.23V
Select R1 to be approximately 1 kΩ, use a 1% resistor for best stability.
CIN — 470 µF, 50V, Aluminum Electrolytic Nichicon “PL Series”
COUT
— 220 µF, 35V Aluminum Electrolytic, Nichicon “PL Series”
D1
— 5A, 40V Schottky Rectifier, 1N5825
L1
— 68 µH, L38
R1
— 1 kΩ, 1%
CFF
— See Application Information Section
FIGURE 1. Standard Test Circuits and Layout Guides
As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring inductance can
generate voltage transients which can cause problems. For
minimal inductance and ground loops, the wires indicated by
heavy lines should be wide printed circuit traces and
should be kept as short as possible. For best results,
external components should be located as close to the
switcher lC as possible using ground plane construction or
single point grounding.
If open core inductors are used, special care must be
taken as to the location and positioning of this type of inductor. Allowing the inductor flux to intersect sensitive feedback,
lC groundpath and COUT wiring can cause problems.
When using the adjustable version, special care must be
taken as to the location of the feedback resistors and the
associated wiring. Physically locate both resistors near the
IC, and route the wiring away from the inductor, especially an
open core type of inductor. (See application section for more
information.)
9
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LM2596
LM2596 Series Buck Regulator Design Procedure (Fixed Output)
PROCEDURE (Fixed Output Voltage Version)
EXAMPLE (Fixed Output Voltage Version)
Given:
VOUT = Regulated Output Voltage (3.3V, 5V or 12V)
Given:
VOUT = 5V
VIN(max) = Maximum DC Input Voltage
ILOAD(max) = Maximum Load Current
VIN(max) = 12V
ILOAD(max) = 3A
1. Inductor Selection (L1)
A. Select the correct inductor value selection guide from Figures Figure 4, Figure 5, or Figure 6. (Output voltages of 3.3V,
5V, or 12V respectively.) For all other voltages, see the design
procedure for the adjustable version.
B. From the inductor value selection guide, identify the inductance region intersected by the Maximum Input Voltage line
and the Maximum Load Current line. Each region is identified
by an inductance value and an inductor code (LXX).
C. Select an appropriate inductor from the four manufacturer’s
part numbers listed in Figure 8.
1. Inductor Selection (L1)
A. Use the inductor selection guide for the 5V version shown
in Figure 5.
B. From the inductor value selection guide shown in Figure 5,
the inductance region intersected by the 12V horizontal line
and the 3A vertical line is 33 µH, and the inductor code is L40.
C. The inductance value required is 33 µH. From the table in
Figure 8, go to the L40 line and choose an inductor part
number from any of the four manufacturers shown. (In most
instance, both through hole and surface mount inductors are
available.)
2. Output Capacitor Selection (COUT)
A. In the majority of applications, low ESR (Equivalent Series
Resistance) electrolytic capacitors between 82 µF and 820 µF
and low ESR solid tantalum capacitors between 10 µF and
470 µF provide the best results. This capacitor should be
located close to the IC using short capacitor leads and short
copper traces. Do not use capacitors larger than 820 µF .
For additional information, see section on output capacitors in application information section.
B. To simplify the capacitor selection procedure, refer to the
quick design component selection table shown in Figure 2.
This table contains different input voltages, output voltages,
and load currents, and lists various inductors and output capacitors that will provide the best design solutions.
C. The capacitor voltage rating for electrolytic capacitors
should be at least 1.5 times greater than the output voltage,
and often much higher voltage ratings are needed to satisfy
the low ESR requirements for low output ripple voltage.
D. For computer aided design software, see Switchers Made
Simple™ version 4.3 or later.
2. Output Capacitor Selection (COUT)
A. See section on output capacitors in application information section.
B. From the quick design component selection table shown in
Figure 2, locate the 5V output voltage section. In the load
current column, choose the load current line that is closest to
the current needed in your application, for this example, use
the 3A line. In the maximum input voltage column, select the
line that covers the input voltage needed in your application, in
this example, use the 15V line. Continuing on this line are
recommended inductors and capacitors that will provide the
best overall performance.
The capacitor list contains both through hole electrolytic and
surface mount tantalum capacitors from four different capacitor manufacturers. It is recommended that both the manufacturers and the manufacturer’s series that are listed in the table
be used.
In this example aluminum electrolytic capacitors from several
different manufacturers are available with the range of ESR
numbers needed.
330 µF 35V Panasonic HFQ Series
330 µF 35V Nichicon PL Series
C. For a 5V output, a capacitor voltage rating at least 7.5V or
more is needed. But even a low ESR, switching grade, 220 µF
10V aluminum electrolytic capacitor would exhibit approximately 225 mΩ of ESR (see the curve in Figure 14 for the ESR
vs voltage rating). This amount of ESR would result in relatively high output ripple voltage. To reduce the ripple to 1% of
the output voltage, or less, a capacitor with a higher value or
with a higher voltage rating (lower ESR) should be selected. A
16V or 25V capacitor will reduce the ripple voltage by approximately half.
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PROCEDURE (Fixed Output Voltage Version)
(Continued)
EXAMPLE (Fixed Output Voltage Version)
3. Catch Diode Selection (D1)
A. The catch diode current rating must be at least 1.3 times
greater than the maximum load current. Also, if the power
supply design must withstand a continuous output short, the
diode should have a current rating equal to the maximum
current limit of the LM2596. The most stressful condition for
this diode is an overload or shorted output condition.
B. The reverse voltage rating of the diode should be at least
1.25 times the maximum input voltage.
C. This diode must be fast (short reverse recovery time) and
must be located close to the LM2596 using short leads and
short printed circuit traces. Because of their fast switching
speed and low forward voltage drop, Schottky diodes provide
the best performance and efficiency, and should be the first
choice, especially in low output voltage applications. Ultra-fast
recovery, or High-Efficiency rectifiers also provide good results. Ultra-fast recovery diodes typically have reverse recovery times of 50 ns or less. Rectifiers such as the 1N5400
series are much too slow and should not be used.
3. Catch Diode Selection (D1)
4. Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is needed
between the input pin and ground pin to prevent large voltage
transients from appearing at the input. This capacitor should
be located close to the IC using short leads. In addition, the
RMS current rating of the input capacitor should be selected to
be at least 1⁄2 the DC load current. The capacitor manufacturers data sheet must be checked to assure that this current
rating is not exceeded. The curve shown in Figure 13 shows
typical RMS current ratings for several different aluminum
electrolytic capacitor values.
For an aluminum electrolytic, the capacitor voltage rating
should be approximately 1.5 times the maximum input voltage. Caution must be exercised if solid tantalum capacitors
are used (see Application Information on input capacitor). The
tantalum capacitor voltage rating should be 2 times the maximum input voltage and it is recommended that they be surge
current tested by the manufacturer.
Use caution when using ceramic capacitors for input bypassing, because it may cause severe ringing at the VIN pin.
For additional information, see section on input capacitors in Application Information section.
4. Input Capacitor (CIN)
The important parameters for the Input capacitor are the input
voltage rating and the RMS current rating. With a nominal
input voltage of 12V, an aluminum electrolytic capacitor with a
voltage rating greater than 18V (1.5 x VIN) would be needed.
The next higher capacitor voltage rating is 25V.
The RMS current rating requirement for the input capacitor in
a buck regulator is approximately 1⁄2 the DC load current. In
this example, with a 3A load, a capacitor with a RMS current
rating of at least 1.5A is needed. The curves shown in Figure
13 can be used to select an appropriate input capacitor. From
the curves, locate the 35V line and note which capacitor
values have RMS current ratings greater than 1.5A. A 680 µF/
35V capacitor could be used.
For a through hole design, a 680 µF/35V electrolytic capacitor
(Panasonic HFQ series or Nichicon PL series or equivalent)
would be adequate. other types or other manufacturers capacitors can be used provided the RMS ripple current ratings
are adequate.
For surface mount designs, solid tantalum capacitors can be
used, but caution must be exercised with regard to the capacitor surge current rating (see Application Information on input
capacitors in this data sheet). The TPS series available from
AVX, and the 593D series from Sprague are both surge current tested.
A. Refer to the table shown in Figure 11. In this example, a 5A,
20V, 1N5823 Schottky diode will provide the best performance, and will not be overstressed even for a shorted output.
11
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LM2596
LM2596 Series Buck Regulator Design Procedure (Fixed Output)
LM2596
LM2596 Series Buck Regulator Design Procedure (Fixed Output)
Conditions
Inductor
(Continued)
Output Capacitor
Through Hole Electrolytic
Surface Mount Tantalum
Output
Load
Max Input
Inductance
Inductor
Panasonic
Nichicon
AVX TPS
Sprague
Voltage
Current
Voltage
(µH)
(#)
HFQ Series
PL Series
Series
595D Series
(V)
(A)
(V)
3.3
3
2
5
3
2
12
3
2
5
22 L41
(µF/V)
(µF/V)
(µF/V)
(µF/V)
470/25
560/16
330/6.3
390/6.3
7
22 L41
560/35
560/35
330/6.3
390/6.3
10
22 L41
680/35
680/35
330/6.3
390/6.3
40
33 L40
560/35
470/35
330/6.3
390/6.3
6
22 L33
470/25
470/35
330/6.3
390/6.3
10
33 L32
330/35
330/35
330/6.3
390/6.3
40
47 L39
330/35
270/50
220/10
330/10
8
22 L41
470/25
560/16
220/10
330/10
10
22 L41
560/25
560/25
220/10
330/10
15
33 L40
330/35
330/35
220/10
330/10
40
47 L39
330/35
270/35
220/10
330/10
9
22 L33
470/25
560/16
220/10
330/10
20
68 L38
180/35
180/35
100/10
270/10
40
68 L38
180/35
180/35
100/10
270/10
15
22 L41
470/25
470/25
100/16
180/16
18
33 L40
330/25
330/25
100/16
180/16
30
68 L44
180/25
180/25
100/16
120/20
40
68 L44
180/35
180/35
100/16
120/20
15
33 L32
330/25
330/25
100/16
180/16
20
68 L38
180/25
180/25
100/16
120/20
40
150 L42
82/25
82/25
68/20
68/25
FIGURE 2. LM2596 Fixed Voltage Quick Design Component Selection Table
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12
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
Given:
VOUT = Regulated Output Voltage
Given:
VIN(max) = Maximum Input Voltage
ILOAD(max) = Maximum Load Current
F = Switching Frequency (Fixed at a nominal 150 kHz).
VIN(max) = 28V
ILOAD(max) = 3A
F = Switching Frequency (Fixed at a nominal 150 kHz).
1. Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 1 )
1. Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 1 )
Use the following formula to select the appropriate resistor
values.
Select R1 to be 1 kΩ, 1%. Solve for R2.
VOUT = 20V
R2 = 1k (16.26 − 1) = 15.26k, closest 1% value is 15.4 kΩ.
R2 = 15.4 kΩ.
Select a value for R1 between 240Ω and 1.5 kΩ. The lower
resistor values minimize noise pickup in the sensitive feedback pin. (For the lowest temperature coefficient and the best
stability with time, use 1% metal film resistors.)
2. Inductor Selection (L1)
A. Calculate the inductor Volt • microsecond constant E • T (V
• µs), from the following formula:
2. Inductor Selection (L1)
A. Calculate the inductor Volt • microsecond constant
(E • T),
where VSAT = internal switch saturation voltage = 1.16V
and VD = diode forward voltage drop = 0.5V
B. E • T = 34.2 (V • µs)
C. ILOAD(max) = 3A
B. Use the E • T value from the previous formula and match it
with the E • T number on the vertical axis of the Inductor Value
Selection Guide shown in Figure 7.
C. on the horizontal axis, select the maximum load current.
D. Identify the inductance region intersected by the E • T value
and the Maximum Load Current value. Each region is identified by an inductance value and an inductor code (LXX).
E. Select an appropriate inductor from the four manufacturer’s
part numbers listed in Figure 8.
D. From the inductor value selection guide shown in Figure 7,
the inductance region intersected by the 34 (V • µs) horizontal
line and the 3A vertical line is 47 µH, and the inductor code is
L39.
E. From the table in Figure 8, locate line L39, and select an
inductor part number from the list of manufacturers part numbers.
13
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LM2596
LM2596 Series Buck Regulator Design Procedure (Adjustable Output)
LM2596
LM2596 Series Buck Regulator Design Procedure (Adjustable Output)
(Continued)
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
3. Output Capacitor Selection (COUT)
3. Output Capacitor SeIection (COUT)
A. In the majority of applications, low ESR electrolytic or solid
tantalum capacitors between 82 µF and 820 µF provide the
best results. This capacitor should be located close to the IC
using short capacitor leads and short copper traces. Do not
use capacitors larger than 820 µF. For additional information, see section on output capacitors in application information section.
B. To simplify the capacitor selection procedure, refer to the
quick design table shown in Figure 3. This table contains
different output voltages, and lists various output capacitors
that will provide the best design solutions.
C. The capacitor voltage rating should be at least 1.5 times
greater than the output voltage, and often much higher voltage
ratings are needed to satisfy the low ESR requirements
needed for low output ripple voltage.
A. See section on COUT in Application Information section.
B. From the quick design table shown in Figure 3, locate the
output voltage column. From that column, locate the output
voltage closest to the output voltage in your application. In this
example, select the 24V line. Under the output capacitor section, select a capacitor from the list of through hole electrolytic
or surface mount tantalum types from four different capacitor
manufacturers. It is recommended that both the manufacturers and the manufacturers series that are listed in the table be
used.
In this example, through hole aluminum electrolytic capacitors
from several different manufacturers are available.
220 µF/35V Panasonic HFQ Series
150 µF/35V Nichicon PL Series
C. For a 20V output, a capacitor rating of at least 30V or more
is needed. In this example, either a 35V or 50V capacitor
would work. A 35V rating was chosen, although a 50V rating
could also be used if a lower output ripple voltage is needed.
Other manufacturers or other types of capacitors may also be
used, provided the capacitor specifications (especially the 100
kHz ESR) closely match the types listed in the table. Refer to
the capacitor manufacturers data sheet for this information.
4. Feedforward Capacitor (CFF) (See Figure 1)
For output voltages greater than approximately 10V, an additional capacitor is required. The compensation capacitor is
typically between 100 pF and 33 nF, and is wired in parallel
with the output voltage setting resistor, R2. It provides additional stability for high output voltages, low input-output voltages, and/or very low ESR output capacitors, such as solid
tantalum capacitors.
4. Feedforward Capacitor (CFF)
The table shown in Figure 3 contains feed forward capacitor
values for various output voltages. In this example, a 560 pF
capacitor is needed.
This capacitor type can be ceramic, plastic, silver mica, etc.
(Because of the unstable characteristics of ceramic capacitors
made with Z5U material, they are not recommended.)
www.national.com
14
(Continued)
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
5. Catch Diode Selection (D1)
A. The catch diode current rating must be at least 1.3 times
greater than the maximum load current. Also, if the power
supply design must withstand a continuous output short, the
diode should have a current rating equal to the maximum
current limit of the LM2596. The most stressful condition for
this diode is an overload or shorted output condition.
B. The reverse voltage rating of the diode should be at least
1.25 times the maximum input voltage.
C. This diode must be fast (short reverse recovery time) and
must be located close to the LM2596 using short leads and
short printed circuit traces. Because of their fast switching
speed and low forward voltage drop, Schottky diodes provide
the best performance and efficiency, and should be the first
choice, especially in low output voltage applications. Ultra-fast
recovery, or High-Efficiency rectifiers are also a good choice,
but some types with an abrupt turn-off characteristic may
cause instability or EMl problems. Ultra-fast recovery diodes
typically have reverse recovery times of 50 ns or less. Rectifiers such as the 1N4001 series are much too slow and should
not be used.
5. Catch Diode Selection (D1)
6. Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is needed
between the input pin and ground to prevent large voltage
transients from appearing at the input. In addition, the RMS
current rating of the input capacitor should be selected to be at
least 1⁄2 the DC load current. The capacitor manufacturers
data sheet must be checked to assure that this current rating
is not exceeded. The curve shown in Figure 13 shows typical
RMS current ratings for several different aluminum electrolytic
capacitor values.
This capacitor should be located close to the IC using short
leads and the voltage rating should be approximately 1.5
times the maximum input voltage.
If solid tantalum input capacitors are used, it is recomended
that they be surge current tested by the manufacturer.
Use caution when using a high dielectric constant ceramic
capacitor for input bypassing, because it may cause severe
ringing at the VIN pin.
For additional information, see section on input capacitors in application information section.
6. Input Capacitor (CIN)
The important parameters for the Input capacitor are the input
voltage rating and the RMS current rating. With a nominal
input voltage of 28V, an aluminum electrolytic aluminum electrolytic capacitor with a voltage rating greater than 42V (1.5 x
VIN) would be needed. Since the the next higher capacitor
voltage rating is 50V, a 50V capacitor should be used. The
capacitor voltage rating of (1.5 x VIN) is a conservative guideline, and can be modified somewhat if desired.
The RMS current rating requirement for the input capacitor of
a buck regulator is approximately 1⁄2 the DC load current. In
this example, with a 3A load, a capacitor with a RMS current
rating of at least 1.5A is needed.
The curves shown in Figure 13 can be used to select an
appropriate input capacitor. From the curves, locate the 50V
line and note which capacitor values have RMS current ratings
greater than 1.5A. Either a 470 µF or 680 µF, 50V capacitor
could be used.
For a through hole design, a 680 µF/50V electrolytic capacitor
(Panasonic HFQ series or Nichicon PL series or equivalent)
would be adequate. Other types or other manufacturers capacitors can be used provided the RMS ripple current ratings
are adequate.
For surface mount designs, solid tantalum capacitors can be
used, but caution must be exercised with regard to the capacitor surge current rting (see Application Information or input
capacitors in this data sheet). The TPS series available from
AVX, and the 593D series from Sprague are both surge current tested.
A. Refer to the table shown in Figure 11. Schottky diodes
provide the best performance, and in this example a 5A, 40V,
1N5825 Schottky diode would be a good choice. The 5A diode
rating is more than adequate and will not be overstressed
even for a shorted output.
To further simplify the buck regulator design procedure, National Semiconductor is making available computer design
software to be used with the Simple Switcher line ot switching
regulators. Switchers Made Simple (version 4.3 or later) is
available on a 31⁄2" diskette for IBM compatible computers.
15
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LM2596
LM2596 Series Buck Regulator Design Procedure (Adjustable Output)
LM2596
LM2596 Series Buck Regulator Design Procedure (Adjustable Output)
Output
Voltage
(V)
Through Hole Output Capacitor
Surface Mount Output Capacitor
Panasonic
Nichicon PL
Feedforward
AVX TPS
Sprague
Feedforward
HFQ Series
Series
Capacitor
Series
595D Series
Capacitor
(µF/V)
(µF/V)
(µF/V)
(µF/V)
2
820/35
820/35
33 nF
330/6.3
470/4
33 nF
4
560/35
470/35
10 nF
330/6.3
390/6.3
10 nF
6
470/25
470/25
3.3 nF
220/10
330/10
3.3 nF
1.5 nF
9
330/25
330/25
1.5 nF
100/16
180/16
12
330/25
330/25
1 nF
100/16
180/16
1 nF
15
220/35
220/35
680 pF
68/20
120/20
680 pF
24
220/35
150/35
560 pF
33/25
33/25
220 pF
28
100/50
100/50
390 pF
10/35
15/50
220 pF
FIGURE 3. Output Capacitor and Feedforward Capacitor Selection Table
LM2596 Series Buck Regulator Design Procedure
INDUCTOR VALUE SELECTION GUIDES (For Continuous Mode Operation)
01258326
01258324
FIGURE 6. LM2596-12
FIGURE 4. LM2596-3.3
01258327
01258325
FIGURE 7. LM2596-ADJ
FIGURE 5. LM2596-5.0
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16
Inductance Current
(µH)
(A)
Schott
LM2596
LM2596 Series Buck Regulator Design Procedure
(Continued)
Renco
Pulse Engineering
Through
Surface
Through
Surface
Hole
Mount
Hole
Mount
Through
Hole
Coilcraft
Surface
Surface
Mount
Mount
L15
22
0.99
67148350 67148460 RL-1284-22-43 RL1500-22
PE-53815
PE-53815-S DO3308-223
L21
68
0.99
67144070 67144450 RL-5471-5
RL1500-68
PE-53821
PE-53821-S DO3316-683
L22
47
1.17
67144080 67144460 RL-5471-6
—
PE-53822
PE-53822-S DO3316-473
L23
33
1.40
67144090 67144470 RL-5471-7
—
PE-53823
PE-53823-S DO3316-333
L24
22
1.70
67148370 67148480 RL-1283-22-43
—
PE-53824
PE-53825-S DO3316-223
L25
15
2.10
67148380 67148490 RL-1283-15-43
—
PE-53825
PE-53824-S DO3316-153
L26
330
0.80
67144100 67144480 RL-5471-1
—
PE-53826
PE-53826-S
DO5022P-334
L27
220
1.00
67144110 67144490 RL-5471-2
—
PE-53827
PE-53827-S
DO5022P-224
L28
150
1.20
67144120 67144500 RL-5471-3
—
PE-53828
PE-53828-S
DO5022P-154
L29
100
1.47
67144130 67144510 RL-5471-4
—
PE-53829
PE-53829-S
DO5022P-104
L30
68
1.78
67144140 67144520 RL-5471-5
—
PE-53830
PE-53830-S
DO5022P-683
L31
47
2.20
67144150 67144530 RL-5471-6
—
PE-53831
PE-53831-S DO5022P-473
L32
33
2.50
67144160 67144540 RL-5471-7
—
PE-53932
PE-53932-S DO5022P-333
L33
22
3.10
67148390 67148500 RL-1283-22-43
—
PE-53933
PE-53933-S DO5022P-223
L34
15
3.40
67148400 67148790 RL-1283-15-43
—
PE-53934
PE-53934-S DO5022P-153
L35
220
1.70
67144170
—
RL-5473-1
—
PE-53935
PE-53935-S
—
L36
150
2.10
67144180
—
RL-5473-4
—
PE-54036
PE-54036-S
—
L37
100
2.50
67144190
—
RL-5472-1
—
PE-54037
PE-54037-S
—
L38
68
3.10
67144200
—
RL-5472-2
—
PE-54038
PE-54038-S
—
L39
47
3.50
67144210
—
RL-5472-3
—
PE-54039
PE-54039-S
—
L40
33
3.50
67144220 67148290 RL-5472-4
—
PE-54040
PE-54040-S
—
L41
22
3.50
67144230 67148300 RL-5472-5
—
PE-54041
PE-54041-S
—
L42
150
2.70
67148410
—
RL-5473-4
—
PE-54042
PE-54042-S
—
L43
100
3.40
67144240
—
RL-5473-2
—
PE-54043
—
L44
68
3.40
67144250
—
RL-5473-3
—
PE-54044
—
FIGURE 8. Inductor Manufacturers Part Numbers
Coilcraft Inc.
Coilcraft Inc., Europe
Pulse Engineering Inc.
Phone
(800) 322-2645
FAX
(708) 639-1469
Phone
+11 1236 730 595
FAX
+44 1236 730 627
Phone
(619) 674-8100
FAX
(619) 674-8262
Pulse Engineering Inc., Phone
+353 93 24 107
Europe
FAX
+353 93 24 459
Renco Electronics Inc.
Phone
(800) 645-5828
FAX
(516) 586-5562
Phone
(612) 475-1173
FAX
(612) 475-1786
Schott Corp.
FIGURE 9. Inductor Manufacturers Phone Numbers
17
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LM2596
LM2596 Series Buck Regulator Design Procedure
Nichicon Corp.
Panasonic
AVX Corp.
Sprague/Vishay
(Continued)
Phone
(708) 843-7500
FAX
(708) 843-2798
Phone
(714) 373-7857
FAX
(714) 373-7102
Phone
(803) 448-9411
FAX
(803) 448-1943
Phone
(207) 324-4140
FAX
(207) 324-7223
FIGURE 10. Capacitor Manufacturers Phone Numbers
VR
3A Diodes
Surface Mount
Schottky
Ultra Fast
4A–6A Diodes
Through Hole
Schottky
Recovery
20V
SK32
30V 30WQ03
SK33
All of
these
diodes
are
rated to
at least
50V.
40V SK34
50V SK35
or
MBRS360
More 30WQ05
SR302
MBR320
1N5821
MBR330
31DQ03
1N5822
Ultra Fast
Schottky
Recovery
All of
these
diodes
are
rated to
at least
50V.
All of
these
diodes
are
rated to
at least
50V.
50WQ03
50WQ04
30WF10
31DQ04
Through Hole
Schottky
Ultra Fast
Recovery
SR502
1N5823
SB520
SR503
1N5824
SB530
All of
these
diodes
are
rated to
at least
50V.
SR504
MBR340
MURS320
1N5825
MUR320
MURS620
SR305
SB540
50WF10
MBR350
50WQ05
31DQ05
18
MUR620
HER601
SB550
50SQ080
FIGURE 11. Diode Selection Table
www.national.com
Ultra Fast
Recovery
SR304
MBRS340
30WQ04
1N5820
Surface Mount
LM2596
Block Diagram
01258321
FIGURE 12.
relatively high RMS currents flowing in a buck regulator’s
input capacitor, this capacitor should be chosen for its RMS
current rating rather than its capacitance or voltage ratings,
although the capacitance value and voltage rating are directly related to the RMS current rating.
The RMS current rating of a capacitor could be viewed as a
capacitor’s power rating. The RMS current flowing through
the capacitors internal ESR produces power which causes
the internal temperature of the capacitor to rise. The RMS
current rating of a capacitor is determined by the amount of
current required to raise the internal temperature approximately 10˚C above an ambient temperature of 105˚C. The
ability of the capacitor to dissipate this heat to the surrounding air will determine the amount of current the capacitor can
safely sustain. Capacitors that are physically large and have
a large surface area will typically have higher RMS current
ratings. For a given capacitor value, a higher voltage electrolytic capacitor will be physically larger than a lower voltage
capacitor, and thus be able to dissipate more heat to the
surrounding air, and therefore will have a higher RMS current rating.
The consequences of operating an electrolytic capacitor
above the RMS current rating is a shortened operating life.
The higher temperature speeds up the evaporation of the
capacitor’s electrolyte, resulting in eventual failure.
Selecting an input capacitor requires consulting the manufacturers data sheet for maximum allowable RMS ripple
current. For a maximum ambient temperature of 40˚C, a
general guideline would be to select a capacitor with a ripple
current rating of approximately 50% of the DC load current.
For ambient temperatures up to 70˚C, a current rating of
75% of the DC load current would be a good choice for a
conservative design. The capacitor voltage rating must be at
least 1.25 times greater than the maximum input voltage,
and often a much higher voltage capacitor is needed to
satisfy the RMS current requirements.
Application Information
PIN FUNCTIONS
+VIN — This is the positive input supply for the IC switching
regulator. A suitable input bypass capacitor must be present
at this pin to minimize voltage transients and to supply the
switching currents needed by the regulator.
Ground — Circuit ground.
Output — Internal switch. The voltage at this pin switches
between (+VIN − VSAT) and approximately −0.5V, with a duty
cycle of approximately VOUT/VIN. To minimize coupling to
sensitive circuitry, the PC board copper area connected to
this pin should be kept to a minimum.
Feedback — Senses the regulated output voltage to complete the feedback loop.
ON /OFF — Allows the switching regulator circuit to be shut
down using logic level signals thus dropping the total input
supply current to approximately 80 µA. Pulling this pin below
a threshold voltage of approximately 1.3V turns the regulator
on, and pulling this pin above 1.3V (up to a maximum of 25V)
shuts the regulator down. If this shutdown feature is not
needed, the ON /OFF pin can be wired to the ground pin or
it can be left open, in either case the regulator will be in the
ON condition.
EXTERNAL COMPONENTS
INPUT CAPACITOR
CIN — A low ESR aluminum or tantalum bypass capacitor is
needed between the input pin and ground pin. It must be
located near the regulator using short leads. This capacitor
prevents large voltage transients from appearing at the input, and provides the instantaneous current needed each
time the switch turns on.
The important parameters for the Input capacitor are the
voltage rating and the RMS current rating. Because of the
19
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LM2596
Application Information
RMS ripple current rating, voltage rating, and capacitance
value. For the output capacitor, the ESR value is the most
important parameter.
(Continued)
A graph shown in Figure 13 shows the relationship between
an electrolytic capacitor value, its voltage rating, and the
RMS current it is rated for. These curves were obtained from
the Nichicon “PL” series of low ESR, high reliability electrolytic capacitors designed for switching regulator applications.
Other capacitor manufacturers offer similar types of capacitors, but always check the capacitor data sheet.
“Standard” electrolytic capacitors typically have much higher
ESR numbers, lower RMS current ratings and typically have
a shorter operating lifetime.
Because of their small size and excellent performance, surface mount solid tantalum capacitors are often used for input
bypassing, but several precautions must be observed. A
small percentage of solid tantalum capacitors can short if the
inrush current rating is exceeded. This can happen at turn on
when the input voltage is suddenly applied, and of course,
higher input voltages produce higher inrush currents. Several capacitor manufacturers do a 100% surge current testing on their products to minimize this potential problem. If
high turn on currents are expected, it may be necessary to
limit this current by adding either some resistance or inductance before the tantalum capacitor, or select a higher voltage capacitor. As with aluminum electrolytic capacitors, the
RMS ripple current rating must be sized to the load current.
The output capacitor requires an ESR value that has an
upper and lower limit. For low output ripple voltage, a low
ESR value is needed. This value is determined by the maximum allowable output ripple voltage, typically 1% to 2% of
the output voltage. But if the selected capacitor’s ESR is
extremely low, there is a possibility of an unstable feedback
loop, resulting in an oscillation at the output. Using the
capacitors listed in the tables, or similar types, will provide
design solutions under all conditions.
If very low output ripple voltage (less than 15 mV) is required, refer to the section on Output Voltage Ripple and
Transients for a post ripple filter.
An aluminum electrolytic capacitor’s ESR value is related to
the capacitance value and its voltage rating. In most cases,
higher voltage electrolytic capacitors have lower ESR values
(see Figure 14 ). Often, capacitors with much higher voltage
ratings may be needed to provide the low ESR values required for low output ripple voltage.
The output capacitor for many different switcher designs
often can be satisfied with only three or four different capacitor values and several different voltage ratings. See the
quick design component selection tables in Figure 2 and 4
for typical capacitor values, voltage ratings, and manufacturers capacitor types.
Electrolytic capacitors are not recommended for temperatures below −25˚C. The ESR rises dramatically at cold temperatures and typically rises 3X @ −25˚C and as much as
10X at −40˚C. See curve shown in Figure 15.
Solid tantalum capacitors have a much better ESR spec for
cold temperatures and are recommended for temperatures
below −25˚C.
FEEDFORWARD CAPACITOR
(Adjustable Output Voltage Version)
CFF — A Feedforward Capacitor CFF, shown across R2 in
Figure 1 is used when the ouput voltage is greater than 10V
or when COUT has a very low ESR. This capacitor adds lead
compensation to the feedback loop and increases the phase
margin for better loop stability. For CFF selection, see the
design procedure section.
01258329
01258328
FIGURE 14. Capacitor ESR vs Capacitor Voltage Rating
(Typical Low ESR Electrolytic Capacitor)
FIGURE 13. RMS Current Ratings for Low ESR
Electrolytic Capacitors (Typical)
CATCH DIODE
Buck regulators require a diode to provide a return path for
the inductor current when the switch turns off. This must be
a fast diode and must be located close to the LM2596 using
short leads and short printed circuit traces.
Because of their very fast switching speed and low forward
voltage drop, Schottky diodes provide the best performance,
especially in low output voltage applications (5V and lower).
Ultra-fast recovery, or High-Efficiency rectifiers are also a
OUTPUT CAPACITOR
COUT — An output capacitor is required to filter the output
and provide regulator loop stability. Low impedance or low
ESR Electrolytic or solid tantalum capacitors designed for
switching regulator applications must be used. When selecting an output capacitor, the important capacitor parameters
are; the 100 kHz Equivalent Series Resistance (ESR), the
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20
LM2596
Application Information
(Continued)
good choice, but some types with an abrupt turnoff characteristic may cause instability or EMI problems. Ultra-fast
recovery diodes typically have reverse recovery times of 50
ns or less. Rectifiers such as the 1N5400 series are much
too slow and should not be used.
01258331
FIGURE 16. (∆IIND) Peak-to-Peak Inductor
Ripple Current (as a Percentage of the Load Current)
vs Load Current
By allowing the percentage of inductor ripple current to
increase for low load currents, the inductor value and size
can be kept relatively low.
When operating in the continuous mode, the inductor current
waveform ranges from a triangular to a sawtooth type of
waveform (depending on the input voltage), with the average
value of this current waveform equal to the DC output load
current.
Inductors are available in different styles such as pot core,
toroid, E-core, bobbin core, etc., as well as different core
materials, such as ferrites and powdered iron. The least
expensive, the bobbin, rod or stick core, consists of wire
wound on a ferrite bobbin. This type of construction makes
for an inexpensive inductor, but since the magnetic flux is not
completely contained within the core, it generates more
Electro-Magnetic Interference (EMl). This magnetic flux can
induce voltages into nearby printed circuit traces, thus causing problems with both the switching regulator operation and
nearby sensitive circuitry, and can give incorrect scope readings because of induced voltages in the scope probe. Also
see section on Open Core Inductors.
When multiple switching regulators are located on the same
PC board, open core magnetics can cause interference
between two or more of the regulator circuits, especially at
high currents. A torroid or E-core inductor (closed magnetic
structure) should be used in these situations.
The inductors listed in the selection chart include ferrite
E-core construction for Schott, ferrite bobbin core for Renco
and Coilcraft, and powdered iron toroid for Pulse Engineering.
Exceeding an inductor’s maximum current rating may cause
the inductor to overheat because of the copper wire losses,
or the core may saturate. If the inductor begins to saturate,
the inductance decreases rapidly and the inductor begins to
look mainly resistive (the DC resistance of the winding). This
can cause the switch current to rise very rapidly and force
the switch into a cycle-by-cycle current limit, thus reducing
the DC output load current. This can also result in overheating of the inductor and/or the LM2596. Different inductor
types have different saturation characteristics, and this
should be kept in mind when selecting an inductor.
The inductor manufacturer’s data sheets include current and
energy limits to avoid inductor saturation.
01258330
FIGURE 15. Capacitor ESR Change vs Temperature
INDUCTOR SELECTION
All switching regulators have two basic modes of operation;
continuous and discontinuous. The difference between the
two types relates to the inductor current, whether it is flowing
continuously, or if it drops to zero for a period of time in the
normal switching cycle. Each mode has distinctively different
operating characteristics, which can affect the regulators
performance and requirements. Most switcher designs will
operate in the discontinuous mode when the load current is
low.
The LM2596 (or any of the Simple Switcher family) can be
used for both continuous or discontinuous modes of operation.
In many cases the preferred mode of operation is the continuous mode. It offers greater output power, lower peak
switch, inductor and diode currents, and can have lower
output ripple voltage. But it does require larger inductor
values to keep the inductor current flowing continuously,
especially at low output load currents and/or high input voltages.
To simplify the inductor selection process, an inductor selection guide (nomograph) was designed (see Figure 4 through
8). This guide assumes that the regulator is operating in the
continuous mode, and selects an inductor that will allow a
peak-to-peak inductor ripple current to be a certain percentage of the maximum design load current. This peak-to-peak
inductor ripple current percentage is not fixed, but is allowed
to change as different design load currents are selected.
(See Figure 16.)
21
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LM2596
Application Information
voltage, the ESR of the output capacitor must be low, however, caution must be exercised when using extremely low
ESR capacitors because they can affect the loop stability,
resulting in oscillation problems. If very low output ripple
voltage is needed (less than 20 mV), a post ripple filter is
recommended. (See Figure 1.) The inductance required is
typically between 1 µH and 5 µH, with low DC resistance, to
maintain good load regulation. A low ESR output filter capacitor is also required to assure good dynamic load response and ripple reduction. The ESR of this capacitor may
be as low as desired, because it is out of the regulator
feedback loop. The photo shown in Figure 17 shows a
typical output ripple voltage, with and without a post ripple
filter.
When observing output ripple with a scope, it is essential
that a short, low inductance scope probe ground connection
be used. Most scope probe manufacturers provide a special
probe terminator which is soldered onto the regulator board,
preferable at the output capacitor. This provides a very short
scope ground thus eliminating the problems associated with
the 3 inch ground lead normally provided with the probe, and
provides a much cleaner and more accurate picture of the
ripple voltage waveform.
The voltage spikes are caused by the fast switching action of
the output switch and the diode, and the parasitic inductance
of the output filter capacitor, and its associated wiring. To
minimize these voltage spikes, the output capacitor should
be designed for switching regulator applications, and the
lead lengths must be kept very short. Wiring inductance,
stray capacitance, as well as the scope probe used to evaluate these transients, all contribute to the amplitude of these
spikes.
When a switching regulator is operating in the continuous
mode, the inductor current waveform ranges from a triangular to a sawtooth type of waveform (depending on the input
voltage). For a given input and output voltage, the
peak-to-peak amplitude of this inductor current waveform
remains constant. As the load current increases or decreases, the entire sawtooth current waveform also rises
and falls. The average value (or the center) of this current
waveform is equal to the DC load current.
If the load current drops to a low enough level, the bottom of
the sawtooth current waveform will reach zero, and the
switcher will smoothly change from a continuous to a discontinuous mode of operation. Most switcher designs (irregardless how large the inductor value is) will be forced to run
discontinuous if the output is lightly loaded. This is a perfectly acceptable mode of operation.
(Continued)
DISCONTINUOUS MODE OPERATION
The selection guide chooses inductor values suitable for
continuous mode operation, but for low current applications
and/or high input voltages, a discontinuous mode design
may be a better choice. It would use an inductor that would
be physically smaller, and would need only one half to one
third the inductance value needed for a continuous mode
design. The peak switch and inductor currents will be higher
in a discontinuous design, but at these low load currents (1A
and below), the maximum switch current will still be less than
the switch current limit.
Discontinuous operation can have voltage waveforms that
are considerable different than a continuous design. The
output pin (switch) waveform can have some damped sinusoidal ringing present. (See Typical Performance Characteristics photo titled Discontinuous Mode Switching Waveforms) This ringing is normal for discontinuous operation,
and is not caused by feedback loop instabilities. In discontinuous operation, there is a period of time where neither the
switch or the diode are conducting, and the inductor current
has dropped to zero. During this time, a small amount of
energy can circulate between the inductor and the switch/
diode parasitic capacitance causing this characteristic ringing. Normally this ringing is not a problem, unless the amplitude becomes great enough to exceed the input voltage, and
even then, there is very little energy present to cause damage.
Different inductor types and/or core materials produce different amounts of this characteristic ringing. Ferrite core inductors have very little core loss and therefore produce the most
ringing. The higher core loss of powdered iron inductors
produce less ringing. If desired, a series RC could be placed
in parallel with the inductor to dampen the ringing. The
computer aided design software Switchers Made Simple
(version 4.3) will provide all component values for continuous and discontinuous modes of operation.
01258332
FIGURE 17. Post Ripple Filter Waveform
OUTPUT VOLTAGE RIPPLE AND TRANSIENTS
The output voltage of a switching power supply operating in
the continuous mode will contain a sawtooth ripple voltage at
the switcher frequency, and may also contain short voltage
spikes at the peaks of the sawtooth waveform.
The output ripple voltage is a function of the inductor sawtooth ripple current and the ESR of the output capacitor. A
typical output ripple voltage can range from approximately
0.5% to 3% of the output voltage. To obtain low ripple
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22
(Continued)
LM2596
Application Information
1.
Peak Inductor or peak switch current
2.
Minimum load current before the circuit becomes discontinuous
3.
Output Ripple Voltage = (∆IIND)x(ESR of COUT)
= 0.62Ax0.1Ω=62 mV p-p
4.
01258333
FIGURE 18. Peak-to-Peak Inductor
Ripple Current vs Load Current
In a switching regulator design, knowing the value of the
peak-to-peak inductor ripple current (∆IIND) can be useful for
determining a number of other circuit parameters. Parameters such as, peak inductor or peak switch current, minimum load current before the circuit becomes discontinuous,
output ripple voltage and output capacitor ESR can all be
calculated from the peak-to-peak ∆IIND. When the inductor
nomographs shown in Figure 4 through 8 are used to select
an inductor value, the peak-to-peak inductor ripple current
can immediately be determined. The curve shown in Figure
18 shows the range of (∆IIND) that can be expected for
different load currents. The curve also shows how the
peak-to-peak inductor ripple current (∆IIND) changes as you
go from the lower border to the upper border (for a given load
current) within an inductance region. The upper border represents a higher input voltage, while the lower border represents a lower input voltage (see Inductor Selection Guides).
These curves are only correct for continuous mode operation, and only if the inductor selection guides are used to
select the inductor value
Consider the following example:
VOUT = 5V, maximum load current of 2.5A
OPEN CORE INDUCTORS
Another possible source of increased output ripple voltage or
unstable operation is from an open core inductor. Ferrite
bobbin or stick inductors have magnetic lines of flux flowing
through the air from one end of the bobbin to the other end.
These magnetic lines of flux will induce a voltage into any
wire or PC board copper trace that comes within the inductor’s magnetic field. The strength of the magnetic field, the
orientation and location of the PC copper trace to the magnetic field, and the distance between the copper trace and
the inductor, determine the amount of voltage generated in
the copper trace. Another way of looking at this inductive
coupling is to consider the PC board copper trace as one
turn of a transformer (secondary) with the inductor winding
as the primary. Many millivolts can be generated in a copper
trace located near an open core inductor which can cause
stability problems or high output ripple voltage problems.
If unstable operation is seen, and an open core inductor is
used, it’s possible that the location of the inductor with
respect to other PC traces may be the problem. To determine if this is the problem, temporarily raise the inductor
away from the board by several inches and then check
circuit operation. If the circuit now operates correctly, then
the magnetic flux from the open core inductor is causing the
problem. Substituting a closed core inductor such as a torroid or E-core will correct the problem, or re-arranging the
PC layout may be necessary. Magnetic flux cutting the IC
device ground trace, feedback trace, or the positive or negative traces of the output capacitor should be minimized.
Sometimes, locating a trace directly beneath a bobbin inductor will provide good results, provided it is exactly in the
center of the inductor (because the induced voltages cancel
themselves out), but if it is off center one direction or the
other, then problems could arise. If flux problems are
present, even the direction of the inductor winding can make
a difference in some circuits.
This discussion on open core inductors is not to frighten the
user, but to alert the user on what kind of problems to watch
out for when using them. Open core bobbin or “stick” inductors are an inexpensive, simple way of making a compact
efficient inductor, and they are used by the millions in many
different applications.
VIN = 12V, nominal, varying between 10V and 16V.
The selection guide in Figure 5 shows that the vertical line
for a 2.5A load current, and the horizontal line for the 12V
input voltage intersect approximately midway between the
upper and lower borders of the 33 µH inductance region.
A 33 µH inductor will allow a peak-to-peak inductor current
(∆IIND) to flow that will be a percentage of the maximum load
current. Referring to Figure 18, follow the 2.5A line approximately midway into the inductance region, and read the
peak-to-peak inductor ripple current (∆IIND) on the left hand
axis (approximately 620 mA p-p).
As the input voltage increases to 16V, it approaches the
upper border of the inductance region, and the inductor
ripple current increases. Referring to the curve in Figure 18,
it can be seen that for a load current of 2.5A, the
peak-to-peak inductor ripple current (∆IIND) is 620 mA with
12V in, and can range from 740 mA at the upper border (16V
in) to 500 mA at the lower border (10V in).
Once the ∆IIND value is known, the following formulas can be
used to calculate additional information about the switching
regulator circuit.
23
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LM2596
Application Information
material and the DC resistance, it could either act as a heat
sink taking heat away from the board, or it could add heat to
the board.
(Continued)
THERMAL CONSIDERATIONS
The LM2596 is available in two packages, a 5-pin TO-220
(T) and a 5-pin surface mount TO-263 (S).
The TO-220 package needs a heat sink under most conditions. The size of the heatsink depends on the input voltage,
the output voltage, the load current and the ambient temperature. The curves in Figure 19 show the LM2596T junction temperature rises above ambient temperature for a 3A
load and different input and output voltages. The data for
these curves was taken with the LM2596T (TO-220 package) operating as a buck switching regulator in an ambient
temperature of 25˚C (still air). These temperature rise numbers are all approximate and there are many factors that can
affect these temperatures. Higher ambient temperatures require more heat sinking.
The TO-263 surface mount package tab is designed to be
soldered to the copper on a printed circuit board. The copper
and the board are the heat sink for this package and the
other heat producing components, such as the catch diode
and inductor. The PC board copper area that the package is
soldered to should be at least 0.4 in2, and ideally should
have 2 or more square inches of 2 oz. (0.0028) in) copper.
Additional copper area improves the thermal characteristics,
but with copper areas greater than approximately 6 in2, only
small improvements in heat dissipation are realized. If further thermal improvements are needed, double sided, multilayer PC board with large copper areas and/or airflow are
recommended.
The curves shown in Figure 20 show the LM2596S (TO-263
package) junction temperature rise above ambient temperature with a 2A load for various input and output voltages. This
data was taken with the circuit operating as a buck switching
regulator with all components mounted on a PC board to
simulate the junction temperature under actual operating
conditions. This curve can be used for a quick check for the
approximate junction temperature for various conditions, but
be aware that there are many factors that can affect the
junction temperature. When load currents higher than 2A are
used, double sided or multilayer PC boards with large copper areas and/or airflow might be needed, especially for high
ambient temperatures and high output voltages.
For the best thermal performance, wide copper traces and
generous amounts of printed circuit board copper should be
used in the board layout. (One exception to this is the output
(switch) pin, which should not have large areas of copper.)
Large areas of copper provide the best transfer of heat
(lower thermal resistance) to the surrounding air, and moving
air lowers the thermal resistance even further.
Package thermal resistance and junction temperature rise
numbers are all approximate, and there are many factors
that will affect these numbers. Some of these factors include
board size, shape, thickness, position, location, and even
board temperature. Other factors are, trace width, total
printed circuit copper area, copper thickness, single- or
double-sided, multilayer board and the amount of solder on
the board. The effectiveness of the PC board to dissipate
heat also depends on the size, quantity and spacing of other
components on the board, as well as whether the surrounding air is still or moving. Furthermore, some of these components such as the catch diode will add heat to the PC
board and the heat can vary as the input voltage changes.
For the inductor, depending on the physical size, type of core
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01258334
Circuit Data for Temperature Rise Curve
TO-220 Package (T)
Capacitors
Through hole electrolytic
Inductor
Through hole, Renco
Diode
Through hole, 5A 40V, Schottky
PC board
3 square inches single sided 2 oz. copper
(0.0028")
FIGURE 19. Junction Temperature Rise, TO-220
01258335
Circuit Data for Temperature Rise Curve
TO-263 Package (S)
Capacitors
Surface mount tantalum, molded “D” size
Inductor
Surface mount, Pulse Engineering, 68 µH
Diode
Surface mount, 5A 40V, Schottky
PC board
9 square inches single sided 2 oz. copper
(0.0028")
FIGURE 20. Junction Temperature Rise, TO-263
24
tures a constant threshold voltage for turn on and turn off
(zener voltage plus approximately one volt). If hysteresis is
needed, the circuit in Figure 24 has a turn ON voltage which
is different than the turn OFF voltage. The amount of hysteresis is approximately equal to the value of the output voltage. If zener voltages greater than 25V are used, an additional 47 kΩ resistor is needed from the ON /OFF pin to the
ground pin to stay within the 25V maximum limit of the ON
/OFF pin.
(Continued)
INVERTING REGULATOR
The circuit in Figure 25 converts a positive input voltage to a
negative output voltage with a common ground. The circuit
operates by bootstrapping the regulator’s ground pin to the
negative output voltage, then grounding the feedback pin,
the regulator senses the inverted output voltage and regulates it.
01258336
FIGURE 21. Delayed Startup
01258337
01258338
This circuit has an ON/OFF threshold of approximately 13V.
FIGURE 22. Undervoltage Lockout
for Buck Regulator
FIGURE 23. Undervoltage Lockout
for Inverting Regulator
DELAYED STARTUP
The circuit in Figure 21 uses the the ON /OFF pin to provide
a time delay between the time the input voltage is applied
and the time the output voltage comes up (only the circuitry
pertaining to the delayed start up is shown). As the input
voltage rises, the charging of capacitor C1 pulls the ON /OFF
pin high, keeping the regulator off. Once the input voltage
reaches its final value and the capacitor stops charging, and
resistor R2 pulls the ON /OFF pin low, thus allowing the
circuit to start switching. Resistor R1 is included to limit the
maximum voltage applied to the ON /OFF pin (maximum of
25V), reduces power supply noise sensitivity, and also limits
the capacitor, C1, discharge current. When high input ripple
voltage exists, avoid long delay time, because this ripple can
be coupled into the ON /OFF pin and cause problems.
This example uses the LM2596-5.0 to generate a −5V output, but other output voltages are possible by selecting other
output voltage versions, including the adjustable version.
Since this regulator topology can produce an output voltage
that is either greater than or less than the input voltage, the
maximum output current greatly depends on both the input
and output voltage. The curve shown in Figure 26 provides a
guide as to the amount of output load current possible for the
different input and output voltage conditions.
The maximum voltage appearing across the regulator is the
absolute sum of the input and output voltage, and this must
be limited to a maximum of 40V. For example, when converting +20V to −12V, the regulator would see 32V between the
input pin and ground pin. The LM2596 has a maximum input
voltage spec of 40V.
Additional diodes are required in this regulator configuration.
Diode D1 is used to isolate input voltage ripple or noise from
coupling through the CIN capacitor to the output, under light
or no load conditions. Also, this diode isolation changes the
topology to closley resemble a buck configuration thus providing good closed loop stability. A Schottky diode is recommended for low input voltages, (because of its lower voltage
drop) but for higher input voltages, a fast recovery diode
could be used.
Without diode D3, when the input voltage is first applied, the
charging current of CIN can pull the output positive by several volts for a short period of time. Adding D3 prevents the
output from going positive by more than a diode voltage.
This delayed startup feature is useful in situations where the
input power source is limited in the amount of current it can
deliver. It allows the input voltage to rise to a higher voltage
before the regulator starts operating. Buck regulators require
less input current at higher input voltages.
UNDERVOLTAGE LOCKOUT
Some applications require the regulator to remain off until
the input voltage reaches a predetermined voltage. An undervoltage lockout feature applied to a buck regulator is
shown in Figure 22, while Figure 23 and 24 applies the same
feature to an inverting circuit. The circuit in Figure 23 fea-
25
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LM2596
Application Information
LM2596
Application Information
(Continued)
01258339
This circuit has hysteresis
Regulator starts switching at VIN = 13V
Regulator stops switching at VIN = 8V
FIGURE 24. Undervoltage Lockout with Hysteresis for Inverting Regulator
01258340
CIN
— 68 µF/25V Tant. Sprague 595D
470 µF/50V Elec. Panasonic HFQ
COUT
— 47 µF/20V Tant. Sprague 595D
220 µF/25V Elec. Panasonic HFQ
FIGURE 25. Inverting −5V Regulator with Delayed Startup
be narrowed down to just a few values. Using the values
shown in Figure 25 will provide good results in the majority of
inverting designs.
This type of inverting regulator can require relatively large
amounts of input current when starting up, even with light
loads. Input currents as high as the LM2596 current limit
(approx 4.5A) are needed for at least 2 ms or more, until the
output reaches its nominal output voltage. The actual time
depends on the output voltage and the size of the output
capacitor. Input power sources that are current limited or
sources that can not deliver these currents without getting
loaded down, may not work correctly. Because of the relatively high startup currents required by the inverting topology,
the delayed startup feature (C1, R1 and R2) shown in Figure
25 is recommended. By delaying the regulator startup, the
input capacitor is allowed to charge up to a higher voltage
before the switcher begins operating. A portion of the high
input current needed for startup is now supplied by the input
capacitor (CIN). For severe start up conditions, the input
capacitor can be made much larger than normal.
01258341
FIGURE 26. Inverting Regulator Typical Load Current
Because of differences in the operation of the inverting
regulator, the standard design procedure is not used to
select the inductor value. In the majority of designs, a 33 µH,
3.5A inductor is the best choice. Capacitor selection can also
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26
OFF. With the inverting configuration, some level shifting is
required, because the ground pin of the regulator is no
longer at ground, but is now setting at the negative output
voltage level. Two different shutdown methods for inverting
regulators are shown in Figure 27 and 28.
(Continued)
INVERTING REGULATOR SHUTDOWN METHODS
To use the ON /OFF pin in a standard buck configuration is
simple, pull it below 1.3V ( @25˚C, referenced to ground) to
turn regulator ON, pull it above 1.3V to shut the regulator
01258342
FIGURE 27. Inverting Regulator Ground Referenced Shutdown
01258343
FIGURE 28. Inverting Regulator Ground Referenced Shutdown using Opto Device
27
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LM2596
Application Information
LM2596
Application Information
(Continued)
TYPICAL THROUGH HOLE PC BOARD LAYOUT, FIXED OUTPUT (1X SIZE), DOUBLE SIDED
01258344
CIN — 470 µF, 50V, Aluminum Electrolytic Panasonic, “HFQ Series”
COUT — 330 µF, 35V, Aluminum Electrolytic Panasonic, “HFQ Series”
D1 — 5A, 40V Schottky Rectifier, 1N5825
L1 — 47 µH, L39, Renco, Through Hole
Thermalloy Heat Sink #7020
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28
LM2596
Application Information
(Continued)
TYPICAL THROUGH HOLE PC BOARD LAYOUT, ADJUSTABLE OUTPUT (1X SIZE), DOUBLE SIDED
01258345
CIN — 470 µF, 50V, Aluminum Electrolytic Panasonic, “HFQ Series”
COUT — 220 µF, 35V Aluminum Electrolytic Panasonic, “HFQ Series”
D1 — 5A, 40V Schottky Rectifier, 1N5825
L1 — 47 µH, L39, Renco, Through Hole
R1 — 1 kΩ, 1%
R2 — Use formula in Design Procedure
CFF — See Figure 3.
Thermalloy Heat Sink #7020
FIGURE 29. PC Board Layout
29
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LM2596
Physical Dimensions
inches (millimeters)
unless otherwise noted
5-Lead TO-220 (T)
Order Number LM2596T-3.3, LM2596T-5.0,
LM2596T-12 or LM2596T-ADJ
NS Package Number T05D
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30
inches (millimeters) unless otherwise noted (Continued)
5-Lead TO-263 Surface Mount Package (S)
Order Number LM2596S-3.3, LM2596S-5.0,
LM2596S-12 or LM2596S-ADJ
NS Package Number TS5B
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National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
LM2596 SIMPLE SWITCHER Power Converter 150 kHz 3A Step-Down Voltage Regulator
Physical Dimensions