LINER LTC1298 Micropower sampling 12-bit a/d converters in s0-8 package Datasheet

LTC1286/LTC1298
Micropower Sampling
12-Bit A/D Converters In
S0-8 Packages
DESCRIPTION
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FEATURES
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The LTC1286/LTC1298 are micropower, 12-bit, successive approximation sampling A/D converters. They typically draw only 250µA of supply current when converting
and automatically power down to a typical supply current
of 1nA whenever they are not performing conversions.
They are packaged in 8-pin SO packages and operate on
5V to 9V supplies. These 12-bit, switched-capacitor, successive approximation ADCs include sample-and-holds.
The LTC1286 has a single differential analog input. The
LTC1298 offers a software selectable 2-channel MUX.
12-Bit Resolution
8-Pin SOIC Plastic Package
Low Cost
Low Supply Current: 250µA Typ.
Auto Shutdown to 1nA Typ.
Guaranteed ±3/4LSB Max DNL
Single Supply 5V to 9V Operation
On-Chip Sample-and-Hold
60µs Conversion Time
Sampling Rates:
12.5 ksps (LTC1286)
11.1 ksps (LTC1298)
I/O Compatible with SPI, Microwire, etc.
Differential Inputs (LTC1286)
2-Channel MUX (LTC1298)
3V Versions Available: LTC1285/LTC1288
On-chip serial ports allow efficient data transfer to a wide
range of microprocessors and microcontrollers over three
wires. This, coupled with micropower consumption, makes
remote location possible and facilitates transmitting data
through isolation barriers.
These circuits can be used in ratiometric applications or
with an external reference. The high impedance analog
inputs and the ability to operate with reduced spans (to
1.5V full scale) allow direct connection to sensors and
transducers in many applications, eliminating the need for
gain stages.
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APPLICATIONS
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Battery-Operated Systems
Remote Data Acquisition
Battery Monitoring
Handheld Terminal Interface
Temperature Measurement
Isolated Data Acquisition
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TYPICAL APPLICATIONS N
25µW, S0-8 Package, 12-Bit ADC
Samples at 200Hz and Runs Off a 5V Supply
MPU
(e.g., 8051)
1
ANALOG INPUT
0V TO 5V RANGE
2
3
4
VREF
+IN
–IN
GND
VCC
LTC1286 CLK
DOUT
CS/SHDN
8
P1.4
7
P1.3
6
5
TA = 25°C
VCC = VREF = 5V
fCLK = 200kHz
5V
SUPPLY CURRENT (µA)
4.7µF
Supply Current vs Sample Rate
1000
100
10
P1.2
SERIAL DATA LINK
LTC1286/98 • TA01
1
0.1k
1k
10k
SAMPLE FREQUENCY (Hz)
100k
LTC1286/98 • TA02
1
LTC1286/LTC1298
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ABSOLUTE MAXIMUM RATINGS
(Notes 1 and 2)
Supply Voltage (VCC) to GND ................................... 12V
Voltage
Analog and Reference ................ –0.3V to VCC + 0.3V
Digital Inputs ......................................... –0.3V to 12V
Digital Output ............................. –0.3V to VCC + 0.3V
Power Dissipation .............................................. 500mW
Operating Temperature Range
LTC1286C/LTC1298C............................. 0°C to 70°C
LTC1286I/LTC1298I ........................... –40°C to 85°C
Storage Temperature Range ................. – 65°C to 150°C
Lead Temperature (Soldering, 10 sec.)................ 300°C
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PACKAGE/ORDER INFORMATION
TOP VIEW
VREF 1
8
VCC
+IN 2
7
CLK
–IN 3
6
DOUT
GND 4
5
CS/SHDN
TOP VIEW
ORDER PART
NUMBER
LTC1286CN8
LTC1286IN8
VREF 1
8
VCC
+IN 2
7
CLK
–IN 3
6
DOUT
GND 4
5
CS/SHDN
ORDER PART
NUMBER
LTC1286CS8
LTC1286IS8
PART MARKING
S8 PACKAGE
8-LEAD PLASTIC SOIC
N8 PACKAGE
8-LEAD PLASTIC DIP
TJMAX = 150°C, θJA = 130°C/W
TOP VIEW
CS/SHDN 1
8
VCC (VREF)
CH0 2
7
CLK
CH1 3
6
DOUT
GND 4
5
DIN
1286
1286I
TJMAX = 150°C, θJA = 175°C/W
ORDER PART
NUMBER
TOP VIEW
LTC1298CN8
LTC1298IN8
CS/SHDN 1
8
VCC (VREF)
CH0 2
7
CLK
CH1 3
6
DOUT
GND 4
5
DIN
ORDER PART
NUMBER
LTC1298CS8
LTC1298IS8
PART MARKING
S8 PACKAGE
8-LEAD PLASTIC SOIC
N8 PACKAGE
8-LEAD PLASTIC DIP
1298
1298I
TJMAX = 150°C, θJA = 175°C/W
TJMAX = 150°C, θJA = 130°C/W
Consult factory for military grade parts.
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RECOM ENDED OPERATING CONDITIONS
SYMBOL
PARAMETER
CONDITIONS
MIN
MAX
UNITS
VCC
Supply Voltage (Note 3)
LTC1286
LTC1298
4.5
4.5
9.0
5.5
V
V
fCLK
Clock Frequency
VCC = 5V
(Note 4)
200
kHz
tCYC
Total Cycle Time
LTC1286, fCLK = 200kHz
LTC1298, fCLK = 200kHz
80
90
µs
µs
thDI
Hold Time, DIN After CLK↑
VCC = 5V
150
ns
tsuCS
Setup Time CS↓ Before First CLK↑ (See Operating Sequence)
LTC1286, VCC = 5V
LTC1298, VCC = 5V
2
2
µs
µs
tsuDI
Setup Time, DIN Stable Before CLK↑
VCC = 5V
400
ns
tWHCLK
CLK High Time
VCC = 5V
2
µs
tWLCLK
CLK Low Time
VCC = 5V
2
µs
tWHCS
CS High Time Between Data Transfer Cycles
VCC = 5V
2
µs
tWLCS
CS Low Time During Data Transfer
LTC1286, fCLK = 200kHz
LTC1298, fCLK = 200kHz
75
85
µs
µs
2
TYP
LTC1286/LTC1298
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CONVERTER AND MULTIPLEXER CHARACTERISTICS
PARAMETER
CONDITIONS
Resolution (No Missing Codes)
MIN
●
LTC1286
TYP
MAX
12
(Note 5)
LTC1298
TYP
MAX
MIN
12
UNITS
Bits
●
±3/4
±2
±3/4
±2
Differential Linearity Error
●
±1/4
±3/4
±1/4
±3/4
LSB
Offset Error
●
3/4
±3
3/4
±3
LSB
Gain Error
●
±2
±2
±8
LSB
Integral Linearity Error
(Note 6)
Analog Input Range
(Note 7 and 8)
REF Input Range (LTC1286)
(Notes 7, 8, and 9)
4.5 ≤ VCC ≤ 5.5V
5.5V < VCC ≤ 9V
Analog Input Leakage Current (Note 10)
●
±8
–0.05V to VCC + 0.05V
V
1.5V to VCC + 0.05V
1.5V to 5.55V
●
V
V
±1
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DIGITAL AND DC ELECTRICAL CHARACTERISTICS
LSB
±1
µA
MAX
UNITS
(Note 5)
SYMBOL
PARAMETER
CONDITIONS
VIH
High Level Input Voltage
VCC = 5.25V
●
VIL
Low Level Input Voltage
VCC = 4.75V
●
IIH
High Level Input Current
VIN = VCC
IIL
Low Level Input Current
VIN = 0V
VOH
High Level Output Voltage
VCC = 4.75V, IO = 10µA
VCC = 4.75V, IO = 360µA
●
●
VOL
Low Level Output Voltage
VCC = 4.75V, IO = 1.6mA
●
0.4
V
IOZ
Hi-Z Output Leakage
CS = High
●
±3
µA
ISOURCE
Output Source Current
VOUT = 0V
– 25
mA
ISINK
Output Sink Current
VOUT = VCC
45
mA
RREF
Reference Input Resistance
(LTC1286)
CS = VCC
CS = GND
5000
55
MΩ
kΩ
IREF
Reference Current (LTC1286)
CS = VCC
tCYC ≥ 640µs, fCLK ≤ 25kHz
tCYC = 80µs, fCLK = 200kHz
●
●
●
0.001
90
90
2.5
140
140
ICC
Supply Current
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DYNAMIC ACCURACY
MIN
TYP
2
V
0.8
V
●
2.5
µA
●
– 2.5
µA
4.0
2.4
4.64
4.62
V
V
µA
µA
µA
CS = VCC
●
0.001
±3.0
µA
LTC1286, tCYC ≥ 640µs, fCLK ≤ 25kHz
LTC1286, tCYC = 80µs, fCLK = 200kHz
●
●
220
260
460
500
µA
µA
LTC1298, tCYC ≥ 720µs, fCLK ≤ 25kHz
LTC1298, tCYC = 90µs, fCLK = 200kHz
●
●
320
360
600
640
µA
µA
TYP
MAX
UNITS
fSMPL = 12.5kHz (LTC1286), fSMPL = 11.1kHz (LTC1298) (Note 5)
SYMBOL
PARAMETER
CONDITIONS
S/(N +D)
Signal-to-Noise Plus Distortion Ratio
1kHz/7kHz Input Signal
MIN
71/68
dB
THD
Total Harmonic Distortion (Up to 5th Harmonic)
1kHz/7kHz Input Signal
– 84/–80
dB
SFDR
Spurious-Free Dynamic Range
1kHz/7kHz Input Signal
90/86
dB
Peak Harmonic or Spurious Noise
1kHz/7kHz Input Signal
– 90/–86
dB
3
LTC1286/LTC1298
AC CHARACTERISTICS
(Note 5)
SYMBOL
PARAMETER
CONDITIONS
tSMPL
Analog Input Sample Time
See Operating Sequence
MIN
TYP
MAX
1.5
●
●
UNITS
CLK Cycles
fSMPL (MAX) Maximum Sampling Frequency
LTC1286
LTC1298
12.5
11.1
kHz
kHz
tCONV
Conversion Time
See Operating Sequence
tdDO
Delay Time, CLK↓ to DOUT Data Valid
See Test Circuits
●
250
tdis
Delay Time, CS↑ to DOUT Hi-Z
See Test Circuits
●
135
300
ns
ten
Delay Time, CLK↓ to DOUT Enable
See Test Circuits
●
75
200
ns
thDO
Time Output Data Remains Valid After CLK↓
CLOAD = 100pF
tf
DOUT Fall Time
See Test Circuits
●
20
75
ns
tr
DOUT Rise Time
See Test Circuits
●
20
75
ns
CIN
Input Capacitance
Analog Inputs, On Channel
Analog Inputs, Off Channel
Digital Input
12
CLK Cycles
600
ns
230
ns
20
5
5
pF
pF
pF
Note 7: Two on-chip diodes are tied to each reference and analog input
which will conduct for reference or analog input voltages one diode drop
below GND or one diode drop above VCC. This spec allows 50mV forward
bias of either diode for 4.5V ≤ VCC ≤ 5.5V. This means that as long as the
reference or analog input does not exceed the supply voltage by more than
50mV the output code will be correct. To achieve an absolute 0V to 5V
input voltage range will therefore require a minimum supply voltage of
4.950V over initial tolerance, temperature variations and loading. For 5.5V
< VCC ≤ 9V, reference and analog input range cannot exceed 5.55V. If
reference and analog input range are greater than 5.55V, the output code
will not be guaranteed to be correct.
Note 8: The supply voltage range for the LTC1286 is from 4.5V to 9V, but
the supply voltage range for the LTC1298 is only from 4.5V to 5.5V.
Note 9: Recommended operating conditions
Note 10: Channel leakage current is measured after the channel selection.
The ● denotes specifications which apply over the full operating
temperature range.
Note 1: Absolute maximum ratings are those values beyond which the life
of a device may be impaired.
Note 2: All voltage values are with respect to GND.
Note 3: These devices are specified at 5V. For 3V specified devices, see
LTC1285 and LTC1288.
Note 4: Increased leakage currents at elevated temperatures cause the S/H
to droop, therefore it is recommended that fCLK ≥ 120kHz at 85°C, fCLK ≥
75kHz at 70° and fCLK ≥ 1kHz at 25°C.
Note 5: VCC = 5V, VREF = 5V and CLK = 200kHz unless otherwise specified.
Note 6: Linearity error is specified between the actual end points of the
A/D transfer curve.
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TYPICAL PERFORMANCE CHARACTERISTICS
Supply Current vs Sample Rate
35
450
400
100
LTC1298
LTC1286
10
TA = 25°C
VCC = VREF = 5V
fCLK = 200kHz
30
350
LTC1298 fSMPL =11.1kHz
300
LTC1286 fSMPL =12.5kHz
1k
10k
SAMPLE RATE (kHz)
100k
LT1286/98 G03
4
200
–55 –35 –15
TA = 25°C
VCC = VREF = 5V
25
20
15
10
CS = 0
(AFTER CONVERSION)
5
1
250
1
SUPPLY CURRENT (µA)
TA = 25°C
VCC = VREF = 5V
fCLK = 200kHz
SUPPLY CURRENT (µA)
SUPPLY CURRENT (µA)
1000
0.1k
Shutdown Supply Current vs Clock
Rate with CS High and CS Low
Supply Current vs Temperature
0.002
CS = VCC
0
5 25 45 65 85 105 125
TEMPERATURE (°C)
LT1286/98 G04
1 20 40 60 80 100 120 140 160 180 200
FREQUENCY (kHz)
LT1286/98 G01
LTC1286/LTC1298
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TYPICAL PERFORMANCE CHARACTERISTICS
Reference Current vs
Sample Rate (LTC1286)
100
70
60
50
40
30
20
CHANGE IN OFFSET (LSB = 1/4096 VREF)
VCC = VREF = 5V
fSMPL = 12.5kHz
fCLK = 200kHz
TA = 25°C
94.5
REFERENCE CURRENT (µA)
REFERENCE CURRENT (µA)
80
3
95
TA = 25°C
VCC = 5V
VREF = 5V
fCLK = 200kHz
90
94
93.5
93
92.5
10
0
0
2
4
8
6
10
FREQUENCY (kHz)
12
92
–55 –35 –15
14
-1
1.5
-2
VCC = VREF = 5V
fCLK = 200kHz
fSMPL = fSMPL (MAX)
65
–0.4
–8
–0.3
–.25
–0.2
–0.15
–6
–5
–4
–3
–2
–0.05
–1
1
1.5
3.5 4
2 2.5 3
REFERENCE VOLTAGE (V)
4.5
0
5
1
1.5
3.5 4
2 2.5 3
REFERENCE VOLTAGE (V)
LT1286/98 G10
1
0.5
EFFECTIVE NUMBER OF BITS (ENOBs)
DIFFERENTIAL NONLINEARITY ERROR (LBS)
1.5
0.60
0.40
0.20
0.00
–0.20
–0.40
–0.60
–0.80
–1.0
5
LT1286/98 G15
0
2048
CODE
4096
5
Effective Bits and S/(N + D)
vs Input Frequency
1.0
0.80
4.5
LT1286/98 G11
Differential Nonlinearity vs Code
TA = 25°C
VCC = 5V
fCLK = 200kHz
5
–7
–0.1
0
4.5
TA = 25°C
VCC = 5V
fCLK = 200kHz
fSMPL = 12.5kHz
–9
–0.35
85
2
ADC NOISE IN LBSs
3.5 4
2 2.5 3
REFERENCE VOLTAGE (V)
–10
Peak-to-Peak ADC Noise vs
Reference Voltage
3
4
2
REFERENCE VOLTAGE (V)
1.5
Change In Gain vs
Reference Voltage
TA = 25°C
VCC = 5V
fCLK = 200kHz
fSMPL = 12.5kHz
LT1286/98 G09
1
0.5
LT1286/98 G08
CHANGE IN GAIN (LSB)
CHANGE IN LINEARITY (LSB)
CHANGE IN OFFSET (LSB)
-0.5
45
-15
5
25
TEMPERATURE (°C)
1
1
–0.5
–0.45
-35
1.5
Change In Linearity vs
Reference Voltage
0
-3
-55
2
LT1286/98 G07
Change in Offset vs Temperature
-2.5
TA = 25°C
VCC = 5V
fCLK = 200kHz
fSMPL = 12.5kHz
2.5
0
5 25 45 65 85 105 125
TEMPERATURE (°C)
LT1286/98 G06
0
Change in Offset vs
Reference Voltage
Reference Current vs Temperature
12
11
74
68
10
9
62
56
8
50
7
44
6
38
5
4
3
TA = 25°C
VCC = 5V
fCLK = 200kHz
fSMPL = 12.5kHz
2
1
0
1
10
100
INPUT FREQUENCY (kHz)
1000
LTC 1286/98 G20
5
LTC1286/LTC1298
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TYPICAL PERFORMANCE CHARACTERISTICS
Spurious Free Dynamic Range
vs Frequency
100
0
80
90
80
70
60
50
40
30
20
TA = 25°C
VCC = VREF = 5V
fSMPL = 12.5kHz
10
0
10k
100k
INPUT FREQUENCY (Hz)
1k
TA = 25°C
VCC = VREF = 5V
fIN = 1kHz
fSMPL = 12.5kHz
70
60
20
50
40
30
20
30
40
50
60
70
80
10
TA = 25°C
VCC = VREF = 5V
fSMPL = 12.5kHz
90
100
0
–40
1M
10
ATTENUATION (%)
SIGNAL-TO-NOISE PLUS DISTORTION (dB)
SPURIOUS FREE DYNAMIC RANGE (dB)
Attenuation vs
Input Frequency
S/(N+D) vs Input Level
–30
–20
–10
INPUT LEVEL (dB)
1
0
10k
100k
1M
INPUT FREQUENCY (Hz)
LTC 1286/98 G27
LTC 1286/98 G26
LT1286/98 G25
4096 Point FFT Plot
–60
–80
–100
TA = 25°C
VCC = VREF = 5V
–20
f1 = 5kHz
f2 = 6kHz
–40 fSMPL = 12.5kHz
TA = 25°C
VCC = 5V (VRIPPLE = 20mV)
VREF = 5V
fCLK = 200kHz
FEEDTHROUGH (dB)
MAGNITUDE (dB)
–60
–80
–100
–120
–140
0
1
2
4
3
5
FREQUENCY (kHz)
6
–100
–140
7
0
1
2
4
3
5
FREQUENCY (kHz)
LTC 1286/98 G21
S&H ACQUISITION TIME (ns)
CLOCK FREQUENCY (kHz)
VIN
150
+INPUT
–INPUT
100
RSOURCE–
300
TA = 25°C
VCC = VREF = 5V
1000
RSOURCE+
VIN
+INPUT
0.1
1
SOURCE RESISTANCE (kΩ)
10
LT1286/98 G12
100
0.1
1
10
100
1000
SOURCE RESISTANCE (Ω)
290
280
270
260
–INPUT
TA = 25°C
VCC = VREF = 5V
10000
Maximum Clock Frequency vs
Supply Voltage
TA = 25°C
VCC = VREF = 5V
200
10
100
1000
RIPPLE FREQUENCY (kHz)
LTC 1286/98 G22
10000
250
6
1
7
Sample and Hold Aquisition
Time vs Source Resistance
300
0
6
LTC 1286/98 G24
Maximum Clock Frequency vs
Source Resistance
50
–50
–120
CLOCK FREQUENCY (kHz)
MAGNITUDE (dB)
–40
0
0
TA = 25°C
VCC = VREF = 5V
fIN = 5kHz
fCLK = 200kHz
fSMPL = 12.5kHz
–20
Power Supply Feedthrough
vs Ripple Frequency
Intermodulation Distortion
0
10M
10000
250
5
6
7
8
9
SUPPLY VOLTAGE (V)
LT1286/98 G16
LT1286/98 G13
LTC1286/LTC1298
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TYPICAL PERFORMANCE CHARACTERISTICS
Digital Input Logic Threshold
vs Supply Voltage
Minimum Clock Frequency
for 0.1 LSB Error vs Temperature
200
1000
150
100
50
0
–55 –35
TA = 25°C
100
LEAKAGE CURRENT (nA)
DIGITAL LOGIC THRESHOLD VOLTAGE (V)
3
VCC = VREF = 5V
CLOCK FREQUENCY (kHz)
Input Channel Leakage Current
vs Temperature
2
5
25
45
TEMPERATURE (°C)
65
85
10
ON CHANNEL
1
OFF CHANNEL
0.1
1
–15
VCC = 5V
VREF = 5V
3
4
5
6
7
SUPPLY VOLTAGE (V)
LT1286/98 • G14
8
9
0.01
– 60 –40 –20 0 20 40 60 80 100 120 140
TEMPERATURE (°C)
LTC 1286/98 G17
1196/98 G19
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PIN FUNCTIONS
LTC1286
LTC1298
VREF (Pin 1): Reference Input. The reference input defines
the span of the A/D converter.
IN + (Pin 2): Positive Analog Input.
CS/SHDN (Pin 1): Chip Select Input. A logic low on this
input enables the LTC1298. A logic high on this input
disables and powers down the LTC1298.
IN – (Pin 3): Negative Analog Input.
CH0 (Pin 2): Analog Input.
GND (Pin 4): Analog Ground. GND should be tied directly
to an analog ground plane.
CH1 (Pin 3): Analog Input.
CS/SHDN (Pin 5): Chip Select Input. A logic low on this
input enables the LTC1286. A logic high on this input
disables and powers down the LTC1286.
GND (Pin 4): Analog Ground. GND should be tied directly
to an analog ground plane.
DIN (Pin 5): Digital Data Input. The multiplexer address is
shifted into this input.
DOUT (Pin 6): Digital Data Output. The A/D conversion
result is shifted out of this output.
DOUT (Pin 6): Digital Data Output. The A/D conversion
result is shifted out of this output.
CLK (Pin 7): Shift Clock. This clock synchronizes the serial
data transfer and determines conversion speed.
CLK (Pin 7): Shift Clock. This clock synchronizes the
serial data transfer and determines conversion speed.
VCC (Pin 8): Power Supply Voltage. This pin provides
power to the A/D converter. It must be kept free of noise
and ripple by bypassing directly to the analog ground
plane.
VCC /VREF (Pin 8): Power Supply and Reference Voltage.
This pin provides power and defines the span of the A/D
converter. It must be kept free of noise and ripple by
bypassing directly to the analog ground plane.
7
LTC1286/LTC1298
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BLOCK DIAGRAM
CS/SHDN
CLK
(DIN)
VCC (VCC/ V REF)
BIAS AND
SHUTDOWN CIRCUIT
IN + (CH0)
CSAMPLE
SERIAL PORT
DOUT
–
IN – (CH1)
+
SAR
MICROPOWER
COMPARATOR
CAPACITIVE DAC
VREF
GND
PIN NAMES IN PARENTHESES
REFER TO THE LTC1298
TEST CIRCUITS
Load Circuit for tdDO, tr and tf
Voltage Waveforms for DOUT Rise and Fall Times, tr, tf
1.4V
DOUT
VOH
DOUT
3k
VOL
TEST POINT
tr
100pF
tf
LTC1286/98 • TC02
LTC1286/98 • TC01
Voltage Waveforms for DOUT Delay Times, tdDO
Load Circuit for tdis and ten
TEST POINT
CLK
VIL
tdDO
3k
VCC tdis WAVEFORM 2, ten
DOUT
DOUT
VOH
100pF
tdis WAVEFORM 1
VOL
LTC1286/98 • TC04
LTC1286/98 • TC03
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LTC1286/LTC1298
TEST CIRCUITS
Voltage Waveforms for tdis
VIH
CS
Voltage Waveforms for ten
LTC1286
DOUT
WAVEFORM 1
(SEE NOTE 1)
CS
90%
1
CLK
2
tdis
DOUT
WAVEFORM 2
(SEE NOTE 2)
10%
B11
DOUT
NOTE 1: WAVEFORM 1 IS FOR AN OUTPUT WITH INTERNAL CONDITIONS SUCH
THAT THE OUTPUT IS HIGH UNLESS DISABLED BY THE OUTPUT CONTROL.
NOTE 2: WAVEFORM 2 IS FOR AN OUTPUT WITH INTERNAL CONDITIONS SUCH
THAT THE OUTPUT IS LOW UNLESS DISABLED BY THE OUTPUT CONTROL.
VOL
ten
LTC1286/98 • TC06
LTC1286/98 • TC05
Voltage Waveforms for ten
LTC1298
CS
START
DIN
1
CLK
2
3
4
B11
DOUT
VOL
ten
LTC1286/98 • TC07
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OVERVIEW
while the LTC1298 operates from a 4.5V to 5.5V supply.
The LTC1286 and LTC1298 are micropower, 12-bit, successive approximation sampling A/D converters. The
LTC1286 typically draws 250µA of supply current when
sampling at 12.5kHz while the LTC1298 nominally consumes 350µA of supply current when sampling at
11.1 kHz. The extra 100µA of supply current on the
LTC1298 comes from the reference input which is intentionally tied to the supply. Supply current drops linearly as
the sample rate is reduced (see Supply Current vs Sample
Rate). The ADCs automatically power down when not
performing conversions, drawing only leakage current.
They are packaged in 8-pin SO and DIP packages. The
LTC1286 operates on a single supply from 4.5V to 9V,
Both the LTC1286 and the LTC1298 contain a 12-bit,
switched-capacitor ADC, a sample-and-hold, and a
serial port (see Block Diagram). Although they share
the same basic design, the LTC1286 and LTC1298
differ in some respects. The LTC1286 has a differential
input and has an external reference input pin. It can
measure signals floating on a DC common-mode voltage and can operate with reduced spans to 1V. Reducing the spans allows it to achieve 244µV resolution. The
LTC1298 has a two-channel input multiplexer and can
convert either channel with respect to ground or the
difference between the two. The reference input is tied
to the supply pin.
9
LTC1286/LTC1298
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SERIAL INTERFACE
The 2-channel LTC1298 communicates with microprocessors and other external circuitry via a synchronous,
half duplex, 4-wire serial interface. The single channel
LTC1286 uses a 3-wire interface (see Operating Sequence
in Figures 1 and 2).
Data Transfer
The CLK synchronizes the data transfer with each bit being
transmitted on the falling CLK edge and captured on the
rising CLK edge in both transmitting and receiving systems.
The LTC1286 does not require a configuration input word
and has no DIN pin. A falling CS initiates data transfer as
shown in the LTC1286 operating sequence. After CS falls
the second CLK pulse enables DOUT. After one null bit the
A/D conversion result is output on the DOUT line. Bringing
CS high resets the LTC1286 for the next data exchange.
The LTC1298 first receives input data and then transmits
back the A/D conversion result (half duplex). Because of
the half duplex operation, DIN and DOUT may be tied
together allowing transmission over just 3 wires: CS, CLK
and DATA (DIN/DOUT).
Data transfer is initiated by a falling chip select (CS) signal.
After CS falls the LTC1298 looks for a start bit. After the
start bit is received, the 3-bit input word is shifted into the
DIN input which configures the LTC1298 and starts the
conversion. After one null bit, the result of the conversion
is output on the DOUT line. At the end of the data exchange
CS should be brought high. This resets the LTC1298 in
preparation for the next data exchange.
tCYC
CS
POWER
DOWN
tsuCS
CLK
DOUT
HI-Z
NULL
BIT B11 B10 B9
B8
(MSB)
tSMPL
B7
B6
B5
B4
B3
B2
B1
tCONV
NULL
BIT B11 B10
HI-Z
B0*
B9
B8
tDATA
*AFTER COMPLETING THE DATA TRANSFER, IF FURTHER CLOCKS ARE APPLIED WITH CS LOW,
THE ADC WILL OUTPUT LSB-FIRST DATA THEN FOLLOWED WITH ZEROS INDEFINITELY.
tCYC
CS
tsuCS
POWER DOWN
CLK
DOUT
HI-Z
NULL
BIT
B11 B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
B1
B2
B3
B4
B5
B6
B7 B8
B9 B10 B11*
HI-Z
(MSB)
tSMPL
tDATA
tCONV
*AFTER COMPLETING THE DATA TRANSFER, IF FURTHER CLOCKS ARE APPLIED WITH CS LOW,
THE ADC WILL OUTPUT ZEROS INDEFINITELY.
tDATA: DURING THIS TIME, THE BIAS CIRCUIT AND THE COMPARATOR POWER DOWN AND THE REFERENCE INPUT
BECOMES A HIGH IMPEDANCE NODE, LEAVING THE CLK RUNNING TO CLOCK OUT LSB-FIRST DATA OR ZEROES.
Figure 1. LTC1286 Operating Sequence
10
LTC1286/98 • F01
LTC1286/LTC1298
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CS
DIN 1
DIN 2
DOUT 1
DOUT 2
SHIFT MUX
ADDRESS IN
1 NULL BIT
SHIFT A/D CONVERSION
RESULT OUT
LTC1096/98 • AI01
MSB-First Data (MSBF = 0)
tCYC
CS
tsuCS
POWER DOWN
CLK
ODD/
SIGN
START
DIN
DON'T CARE
MSBF
NULL
HI-Z BIT
SGL/
DIFF
DOUT
tSMPL
B11 B10 B9
(MSB)
B8
B6
B7
B5
B4
B3
B2
B1
B0 B1
B2
B3
B4
B5
B6
B7
B8
B9 B10 B11*
HI-Z
tDATA
tCONV
MSB-First Data (MSBF = 1)
tCYC
CS
POWER
DOWN
tsuCS
CLK
ODD/
SIGN
START
DIN
DON'T CARE
SGL/
DIFF
DOUT
MSBF
NULL
BIT B11 B10 B9
HI-Z
tSMPL
(MSB)
B8
B7
B6
tCONV
B5
B4
B3
B2
B1
HI-Z
B0*
tDATA
*AFTER COMPLETING THE DATA TRANSFER, IF FURTHER CLOCKS ARE APPLIED WITH CS LOW,
THE ADC WILL OUTPUT ZEROS INDEFINITELY.
tDATA: DURING THIS TIME, THE BIAS CIRCUIT AND THE COMPARATOR POWER DOWN AND THE REFERENCE INPUT
BECOMES A HIGH IMPEDANCE NODE, LEAVING THE CLK RUNNING TO CLOCK OUT LSB-FIRST DATA OR ZEROES.
LTC1286/98 • F02
Figure 2. LTC1298 Operating Sequence Example: Differential Inputs (CH+, CH–)
11
LTC1286/LTC1298
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Input Data Word
The LTC1286 requires no DIN word. It is permanently
configured to have a single differential input. The conversion result appears on the DOUT line. The data format is
MSB first followed by the LSB sequence. This provides
easy interface to MSB or LSB first serial ports. For MSB
first data the CS signal can be taken high after B0 (see
Figure 1). The LTC1298 clocks data into the DIN input on
the rising edge of the clock. The input data words are
defined as follows:
START
SGL/
DIFF
ODD/
SIGN MSBF
Start Bit
GND
–
–
LTC1096/8 • AI03
MSB First/LSB First (MSBF)
The output data of the LTC1298 is programmed for
MSB first or LSB first sequence using the MSBF bit.
When the MSBF bit is a logical one, data will appear on
the DOUT line in MSB first format. Logical zeros will be
filled in indefinitely following the last data bit. When the
1LSB =
VREF
4096
VREF
CHANNEL #
0
1
+
+
+
–
–
+
VIN
000000000000
VREF–1LSB
LTC1298 Channel Selection
000000000001
VREF–2LSB
The bits of the input word following the START bit assign
the MUX configuration for the requested conversion. For
a given channel selection, the converter will measure the
voltage between the two channels indicated by the + and
– signs in the selected row of the following tables. In
single-ended mode, all input channels are measured with
respect to GND.
•
•
•
1LSB
Multiplexer (MUX) Address
12
Transfer Curve
0V
The first “logical one” clocked into the DIN input after CS
goes low is the start bit. The start bit initiates the data
transfer. The LTC1298 will ignore all leading zeros which
precede this logical one. After the start bit is received, the
remaining bits of the input word will be clocked in. Further
inputs on the DIN pin are then ignored until the next CS
cycle.
DIFFERENTIAL
MUX MODE
The LTC1286/LTC1298 are permanently configured for
unipolar only. The input span and code assignment for
this conversion type are shown in the following figures.
111111111110
LTC1096/9 • AI02
SINGLE-ENDED
MUX MODE
Transfer Curve
111111111111
MUX MSB FIRST/
ADDRESS LSB FIRST
MUX ADDRESS
SGL/DIFF ODD/SIGN
1
0
1
1
0
0
0
1
MSBF bit is a logical zero, LSB first data will follow the
normal MSB first data on the DOUT line. (see Operating
Sequence)
LTC1286/98 • AI04
Output Code
OUTPUT CODE
INPUT VOLTAGE
INPUT VOLTAGE
(VREF = 5.000V)
11111111111111
11111111111110
•
•
•
00000000000001
00000000000000
VREF – 1LSB
VREF – 2LSB
•
•
•
1LSB
0V
4.99878V
4.99756V
•
•
•
0.00122V
0V
LTC1286/98 • AI05
Operation with DIN and DOUT Tied Together
The LTC1298 can be operated with DIN and DOUT tied
together. This eliminates one of the lines required to
communicate to the microprocessor (MPU). Data is transmitted in both directions on a single wire. The processor
pin connected to this data line should be configurable as
either an input or an output. The LTC1298 will take control
of the data line and drive it low on the 4th falling CLK edge
after the start bit is received (see Figure 3). Therefore the
processor port line must be switched to an input before
this happens to avoid a conflict.
In the Typical Applications section, there is an example of
interfacing the LTC1298 with DIN and DOUT tied together to
the Intel 8051 MPU.
LTC1286/LTC1298
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MSBF BIT LATCHED
BY LTC1298
CS
1
2
3
4
START
SGL/DIFF
ODD/SIGN
MSBF
CLK
DATA (DIN/DOUT)
MPU CONTROLS DATA LINE AND SENDS
MUX ADDRESS TO LTC1298
B11
B10
• • •
LTC1298 CONTROLS DATA LINE AND SENDS
A/D RESULT BACK TO MPU
PROCESSOR MUST RELEASE
DATA LINE AFTER 4TH RISING CLK
AND BEFORE THE 4TH FALLING CLK
LTC1298 TAKES CONTROL OF DATA LINE
ON 4TH FALLING CLK
LTC1286/98 F03
Figure 3. LTC1298 Operation with DIN and DOUT Tied Together
ACHIEVING MICROPOWER PERFORMANCE
With typical operating currents of 250µA and automatic
shutdown between conversions, the LTC1286/LTC1298
achieves extremely low power consumption over a wide
range of sample rates (see Figure 4). The auto-shutdown
allows the supply curve to drop with reduced sample rate.
Several things must be taken into account to achieve such
a low power consumption.
When the CS pin is high (= supply voltage), the converter
is in shutdown mode and draws only leakage current. The
status of the DIN and CLK input have no effect on supply
current during this time. There is no need to stop DIN and
CLK with CS = high; they can continue to run without
drawing current.
1000
SUPPLY CURRENT (µA)
input becomes high impedance at the end of each conversion leaving the CLK running to clock out the LSB first data
or zeroes (see Figures 1 and 2). If the CS is not running railto-rail, the input logic buffer will draw current. This current
may be large compared to the typical supply current. To
obtain the lowest supply current, bring the CS pin to
ground when it is low and to supply voltage when it is high.
TA = 25°C
VCC = VREF = 5V
fCLK = 200kHz
100
LTC1298
LTC1286
10
Minimize CS Low Time
1
0.1k
1k
10k
SAMPLE RATE (kHz)
100k
LT1286/98 G03
Figure 4. Automatic Power Shutdown Between Conversions
Allows Power Consumption to Drop with Sample Rate.
Shutdown
The LTC1286/LTC1298 are equipped with automatic shutdown features. They draw power when the CS pin is low
and shut down completely when that pin is high. The bias
circuit and comparator powers down and the reference
In systems that have significant time between conversions, lowest power drain will occur with the minimum CS
low time. Bringing CS low, transferring data as quickly as
possible, and then bringing it back high will result in the
lowest current drain. This minimizes the amount of time
the device draws power. After a conversion the ADC
automatically shuts down even if CS is held low (see
Figures 1 and 2). If the clock is left running to clock out
LSB-data or zero, the logic will draw a small current.
Figure 5 shows that the typical supply current with CS =
ground varies from 1µA at 1kHz to 35µA at 200kHz. When
CS = VCC, the logic is gated off and no supply current is
drawn regardless of the clock frequency.
13
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Clock Frequency
35
TA = 25°C
VCC = VREF = 5V
SUPPLY CURRENT (µA)
30
25
20
15
CS = 0
(AFTER CONVERSION)
10
5
1
0.002
The maximum recommended clock frequency is 200kHz
for the LTC1286/LTC1298 running off a 5V supply. With
the supply voltage changing, the maximum clock frequency for the devices also changes (see the typical curve
of Maximum Clock Rate vs Supply Voltage). If the maximum clock frequency is used, care must be taken to
ensure that the device converts correctly.
CS = VCC
0
1 20 40 60 80 100 120 140 160 180 200
FREQUENCY (kHz)
LT1286/98 G01
Figure 5. Shutdown current with CS high is 1nA typically,
regardless of the clock. Shutdown current with CS = ground
varies from 1µA at 1kHz to 35µA at 200kHz.
DOUT Loading
Capacitive loading on the digital output can increase power
consumption. A 100pF capacitor on the DOUT pin can add
more than 50µA to the supply current at a 200kHz clock
frequency. An extra 50µA or so of current goes into
charging and discharging the load capacitor. The same
goes for digital lines driven at a high frequency by any logic.
The C × V × f currents must be evaluated and the troublesome ones minimized.
OPERATING ON OTHER THAN 5V SUPPLIES (LTC1286)
The LTC1286 operates from 4.5V to 9V supplies and the
LTC1298 operates from a 5V supply. To operate the LTC1286
on other than 5V supplies a few things must be kept in
mind.
Mixed Supplies
It is possible to have a microprocessor running off a 5V
supply and communicate with the LTC1286 operating on
a 9V supply. The requirement to achieve this is that the
outputs of CS and CLK from the MPU have to be able to trip
the equivalent inputs of the LTC1286 and the output of
DOUT from the LTC1286 must be able to toggle the
equivalent input of the MPU (see typical curve of Digital
Input Logic Threshold vs Supply Voltage). With the
LTC1286 operating on a 9V supply, the output of DOUT may
go between 0V and 9V. The 9V output may damage the
MPU running off a 5V supply. The way to get around this
possibility is to have a resistor divider on DOUT (Figure 6)
and connect the center point to the MPU input. It should
be noted that to get full shutdown, the CS input of the
LTC1286 must be driven to the VCC voltage to keep the CS
input buffer from drawing current. An alternative is to
leave CS low after a conversion, clock data until DOUT
outputs zeros, and then stop the clock low.
9V 4.7µF
MPU
(e.g. 8051)
Input Logic Levels
5V
The input logic levels of CS, CLK and DIN are made to meet
TTL on a 5V supply. When the supply voltage varies, the
input logic levels also change. For the LTC1286 to sample
and convert correctly, the digital inputs have to be in the
proper logical low and high levels relative to the operating
supply voltage (see typical curve of Digital Input Logic
Threshold vs Supply Voltage). If achieving micropower
consumption is desirable, the digital inputs must go rail-torail between supply voltage and ground (see ACHIEVING
MICROPOWER PERFORMANCE section).
14
VREF
VCC
DIFFERENTIAL INPUTS
+IN
CLK
COMMON-MODE RANGE
0V TO 5V
–IN
DOUT
GND
CS
5V
P1.4
P1.3
50k
P1.2
50k
LTC1286
LTC1286/98 • F06
Figure 6. Interfacing a 9V Powered LTC1286 to a 5V System
LTC1286/LTC1298
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BOARD LAYOUT CONSIDERATIONS
SAMPLE-AND-HOLD
Grounding and Bypassing
Both the LTC1286 and the LTC1298 provide a built-in
sample-and-hold (S&H) function to acquire signals. The
S&H of the LTC1286 acquires input signals from “+” input
relative to “–” input during the tSMPL time (see Figure 1).
However, the S&H of the LTC1298 can sample input
signals in the single-ended mode or in the differential
inputs during the tSMPL time (see Figure 7).
The LTC1286/LTC1298 are easy to use if some care is
taken. They should be used with an analog ground plane
and single point grounding techniques. The GND pin
should be tied directly to the ground plane.
The VCC pin should be bypassed to the ground plane with
a 10µF tantalum capacitor with leads as short as possible.
If the power supply is clean, the LTC1286/LTC1298 can
also operate with smaller 1µF or less surface mount or
ceramic bypass capacitors. All analog inputs should be
referenced directly to the single point ground. Digital
inputs and outputs should be shielded from and/or routed
away from the reference and analog circuitry.
Single-Ended Inputs
The sample-and-hold of the LTC1298 allows conversion
of rapidly varying signals. The input voltage is sampled
during the tSMPL time as shown in Figure 7. The sampling
interval begins as the bit preceding the MSBF bit is shifted
in and continues until the falling CLK edge after the MSBF
bit is received. On this falling edge, the S&H goes into hold
mode and the conversion begins.
SAMPLE
HOLD
"+" INPUT MUST
SETTLE DURING
THIS TIME
CS
tSMPL
tCONV
CLK
DIN
START
SGL/DIFF
MSBF
DOUT
DON'T CARE
B11
1ST BIT TEST "–" INPUT MUST
SETTLE DURING THIS TIME
"+" INPUT
"–" INPUT
LTC1096/8 • F07
Figure 7. LTC1298 “+” and “–” Input Settling Windows
15
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Differential Inputs
With differential inputs, the ADC no longer converts just a
single voltage but rather the difference between two voltages. In this case, the voltage on the selected “+” input is
still sampled and held and therefore may be rapidly time
varying just as in single-ended mode. However, the voltage on the selected “–” input must remain constant and be
free of noise and ripple throughout the conversion time.
Otherwise, the differencing operation may not be performed accurately. The conversion time is 12 CLK cycles.
Therefore, a change in the “–” input voltage during this
interval can cause conversion errors. For a sinusoidal
voltage on the “–” input this error would be:
VERROR (MAX) = VPEAK × 2 × π × f(“–”) × 12/fCLK
Where f(“–”) is the frequency of the “–” input voltage,
VPEAK is its peak amplitude and fCLK is the frequency of the
CLK. In most cases VERROR will not be significant. For a
60Hz signal on the “–” input to generate a 1/4LSB error
(305µV) with the converter running at CLK = 200kHz, its
peak value would have to be 13.48mV.
ANALOG INPUTS
Because of the capacitive redistribution A/D conversion
techniques used, the analog inputs of the LTC1286/
LTC1298 have capacitive switching input current spikes.
These current spikes settle quickly and do not cause a
problem. However, if large source resistances are used or
if slow settling op amps drive the inputs, care must be
taken to insure that the transients caused by the current
spikes settle completely before the conversion begins.
sample time can be increased by using a slower CLK
frequency.
“–” Input Settling
At the end of the tSMPL, the input capacitor switches to the
“–” input and conversion starts (see Figures 1 and 7).
During the conversion, the “+” input voltage is effectively
“held” by the sample-and-hold and will not affect the
conversion result. However, it is critical that the “–” input
voltage settles completely during the first CLK cycle of the
conversion time and be free of noise. Minimizing RSOURCE–
and C2 will improve settling time. If a large “–” input
source resistance must be used, the time allowed for
settling can be extended by using a slower CLK frequency.
Input Op Amps
When driving the analog inputs with an op amp it is
important that the op amp settle within the allowed time
(see Figure 7). Again, the“+” and “–” input sampling times
can be extended as described above to accommodate
slower op amps. Most op amps, including the LT1006 and
LT1413 single supply op amps, can be made to settle well
even with the minimum settling windows of 6µs (“+”
input) which occur at the maximum clock rate of 200kHz.
Source Resistance
The analog inputs of the LTC1286/LTC1298 look like a
20pF capacitor (CIN) in series with a 500Ω resistor (RON)
as shown in Figure 8. CIN gets switched between the
selected “+” and “–” inputs once during each conversion
cycle. Large external source resistors and capacitances
“+” Input Settling
The input capacitor of the LTC1286 is switched onto “+”
input during the tSMPL time (see Figure 1) and samples the
input signal within that time. However, the input capacitor
of the LTC1298 is switched onto “+” input during the
sample phase (tSMPL, see Figure 7). The sample phase is
1 1/2 CLK cycles before conversion starts. The voltage on
the “+” input must settle completely within tSMPLE for the
LTC1286 and the LTC1298 respectively. Minimizing
RSOURCE+ and C1 will improve the input settling time. If a
large “+” input source resistance must be used, the
16
RSOURCE +
“+”
INPUT
LTC1286/98
VIN +
C1
RSOURCE –
“–”
INPUT
RON = 500Ω
CIN = 20pF
VIN –
C2
LTC1286/98 • F08
Figure 8. Analog Input Equivalent Circuit
LTC1286/LTC1298
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will slow the settling of the inputs. It is important that the
overall RC time constants be short enough to allow the
analog inputs to completely settle within the allowed time.
converter, the reference input should be driven by a
reference with low ROUT (ex. LT1004, LT1019 and LT1021)
or a voltage source with low ROUT.
RC Input Filtering
It is possible to filter the inputs with an RC network as
shown in Figure 9. For large values of CF (e.g., 1µF), the
capacitive input switching currents are averaged into a net
DC current. Therefore, a filter should be chosen with a
small resistor and large capacitor to prevent DC drops
across the resistor. The magnitude of the DC current is
approximately IDC = 20pF × VIN /tCYC and is roughly
proportional to VIN. When running at the minimum cycle
time of 64µs, the input current equals 1.56µA at VIN = 5V.
In this case, a filter resistor of 75Ω will cause 0.1LSB of
full-scale error. If a larger filter resistor must be used,
errors can be eliminated by increasing the cycle time.
RFILTER
IDC
“+”
VIN
CFILTER
LTC1286
“–”
LTC1286/98 • F09
Figure 9. RC Input Filtering
Input Leakage Current
Input leakage currents can also create errors if the source
resistance gets too large. For instance, the maximum
input leakage specification of 1µA (at 125°C) flowing
through a source resistance of 240Ω will cause a voltage
drop of 240µV or 0.2LSB. This error will be much reduced
at lower temperatures because leakage drops rapidly (see
typical curve of Input Channel Leakage Current vs Temperature).
REFERENCE INPUTS
The reference input of the LTC1286 is effectively a 50kΩ
resistor from the time CS goes low to the end of the
conversion. The reference input becomes a high impedence
node at any other time (see Figure 10). Since the voltage
on the reference input defines the voltage span of the A/D
REF+
1
LTC1286
ROUT
VREF
GND
4
LTC1286/98 • F10
Figure 10. Reference Input Equivalent Circuit
Reduced Reference Operation
The minimum reference voltage of the LTC1298 is limited
to 4.5V because the VCC supply and reference are internally tied together. However, the LTC1286 can operate
with reference voltages below 1V.
The effective resolution of the LTC1286 can be increased
by reducing the input span of the converter. The LTC1286
exhibits good linearity and gain over a wide range of
reference voltages (see typical curves of Change in Linearity vs Reference Voltage and Change in Gain vs Reference
Voltage). However, care must be taken when operating at
low values of VREF because of the reduced LSB step size
and the resulting higher accuracy requirement placed on
the converter. The following factors must be considered
when operating at low VREF values:
1. Offset
2. Noise
3. Conversion speed (CLK frequency)
Offset with Reduced VREF
The offset of the LTC1286 has a larger effect on the output
code. When the ADC is operated with reduced reference
voltage. The offset (which is typically a fixed voltage)
becomes a larger fraction of an LSB as the size of the LSB
is reduced. The typical curve of Change in Offset vs
Reference Voltage shows how offset in LSBs is related to
reference voltage for a typical value of VOS. For example,
a VOS of 122µV which is 0.1LSB with a 5V reference
becomes 0.5LSB with a 1V reference and 2.5LSBs with a
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Noise with Reduced VREF
The total input referred noise of the LTC1286 can be
reduced to approximately 400µV peak-to-peak using a
ground plane, good bypassing, good layout techniques
and minimizing noise on the reference inputs. This noise
is insignificant with a 5V reference but will become a larger
fraction of an LSB as the size of the LSB is reduced.
For operation with a 5V reference, the 400µV noise is
only 0.33LSB peak-to-peak. In this case, the LTC1286
noise will contribute virtually no uncertainty to the
output code. However, for reduced references the noise
may become a significant fraction of an LSB and cause
undesirable jitter in the output code. For example, with
a 2.5V reference this same 400µV noise is 0.66LSB
peak-to-peak. This will reduce the range of input voltages over which a stable output code can be achieved by
1LSB. If the reference is further reduced to 1V, the 400µV
noise becomes equal to 1.65LSBs and a stable code may
be difficult to achieve. In this case averaging multiple
readings may be necessary.
This noise data was taken in a very clean setup. Any setup
induced noise (noise or ripple on VCC, VREF or VIN) will add
to the internal noise. The lower the reference voltage to be
used the more critical it becomes to have a clean, noise free
setup.
tortion and noise at the rated throughput. By applying a low
distortion sine wave and analyzing the digital output using
an FFT algorithm, the ADC’s spectral content can be
examined for frequencies outside the fundamental. Figure
11 shows a typical LTC1286 plot.
0
TA = 25°C
VCC = VREF = 5V
fIN = 5kHz
fCLK = 200kHz
fSMPL = 12.5kHz
–20
MAGNITUDE (dB)
0.2V reference. If this offset is unacceptable, it can be
corrected digitally by the receiving system or by offsetting
the “–” input of the LTC1286.
–40
–60
–80
–100
–120
–140
0
1
2
4
3
5
FREQUENCY (kHz)
6
7
LTC 1286/98 G21
Figure 11. LTC1286 Non-Averaged, 4096 Point FFT Plot
Signal-to-Noise Ratio
The Signal-to-Noise plus Distortion Ratio (S/N + D) is the
ratio between the RMS amplitude of the fundamental
input frequency to the RMS amplitude of all other frequency components at the ADC’s output. The output is
band limited to frequencies above DC and below one half
the sampling frequency. Figure 12 shows a typical spectral content with a 12.5kHz sampling rate.
Effective Number of Bits
Conversion Speed with Reduced VREF
With reduced reference voltages, the LSB step size is
reduced and the LTC1286 internal comparator overdrive is reduced. Therefore, it may be necessary to
reduce the maximum CLK frequency when low values
of VREF are used.
DYNAMIC PERFORMANCE
The LTC1286/LTC1298 have exceptional sampling capability. Fast Fourier Transform (FFT) test techniques are
used to characterize the ADC’s frequency response, dis-
18
The Effective Number of Bits (ENOBs) is a measurement of
the resolution of an ADC and is directly related to S/(N+D)
by the equation:
ENOB = [S/(N + D) – 1.76]/6.02
where S/(N + D) is expressed in dB. At the maximum
sampling rate of 12.5kHz with a 5V supply, the LTC1286
maintains above 11 ENOBs at 10kHz input frequency.
Above 10kHz the ENOBs gradually decline, as shown in
Figure 12, due to increasing second harmonic distortion.
The noise floor remains low.
LTC1286/LTC1298
U
W
U U
EFFECTIVE NUMBER OF BITS (ENOBs)
APPLICATION INFORMATION
12
11
74
68
10
9
62
56
8
50
7
44
6
38
5
4
3
TA = 25°C
VCC = 5V
fCLK = 200kHz
fSMPL = 12.5kHz
2
1
0
1
10
100
INPUT FREQUENCY (kHz)
1000
LTC 1286/98 G20
Figure 12. Effective Bits and S/(N + D) vs Input Frequency
Total Harmonic Distortion
Total Harmonic Distortion (THD) is the ratio of the RMS
sum of all harmonics of the input signal to the fundamental
itself. The out-of-band harmonics alias into the frequency
band between DC and half of the sampling frequency. THD
is defined as:
THD = 20log
If two pure sine waves of frequencies fa and fb are applied
to the ADC input, nonlinearities in the ADC transfer function can create distortion products at sum and difference
frequencies of mfa ± nfb, where m and n = 0, 1, 2, 3, etc.
For example, the 2nd order IMD terms include (fa + fb) and
(fa – fb) while 3rd order IMD terms include (2fa + fb),
(2fa – fb), (fa + 2fb), and (fa – 2fb). If the two input sine
waves are equal in magnitudes, the value (in dB) of the 2nd
order IMD products can be expressed by the following
formula:
V22 + V32 + V42 + ... + VN2
V1
where V1 is the RMS amplitude of the fundamental frequency and V2 through VN are the amplitudes of the
second through the Nth harmonics. The typical THD specification in the Dynamic Accuracy table includes the 2nd
through 5th harmonics. With a 7kHz input signal, the
LTC1286/LTC1298 have typical THD of 80dB with VCC = 5V.
Intermodulation Distortion
If the ADC input signal consists of more than one spectral
component, the ADC transfer function nonlinearity can
produce intermodulation distortion (IMD) in addition
to THD. IMD is the change in one sinusoidal input
caused by the presence of another sinusoidal input at a
different frequency.
(
)
amplitude fa ± fb
IMD fa ± fb = 20log 
 amplitude at fa

(
)


For input frequencies of 5kHz and 6kHz, the IMD of the
LTC1286/LTC1298 is 73dB with a 5V supply.
Peak Harmonic or Spurious Noise
The peak harmonic or spurious noise is the largest spectral component excluding the input signal and DC. This
value is expressed in dBs relative to the RMS value of a fullscale input signal.
Full-Power and Full-Linear Bandwidth
The full-power bandwidth is that input frequency at which
the amplitude of the reconstructed fundamental is reduced by 3dB for a full-scale input.
The full-linear bandwidth is the input frequency at which
the effective bits rating of the ADC falls to 11 bits. Beyond
this frequency, distortion of the sampled input signal
increases. The LTC1286/LTC1298 have been designed to
optimize input bandwidth, allowing the ADCs to
undersample input signals with frequencies above the
converters’ Nyquist Frequency.
19
LTC1286/LTC1298
U
TYPICAL APPLICATIONS N
MICROPROCESSOR INTERFACES
The LTC1286/LTC1298 can interface directly without external hardware to most popular microprocessor (MPU)
synchronous serial formats (see Table 1). If an MPU
without a dedicated serial port is used, then 3 or 4 of the
MPU's parallel port lines can be programmed to form the
serial link to the LTC1286/LTC1298. Included here is one
serial interface example and one example showing a
parallel port programmed to form the serial interface.
Motorola SPI (MC68HC11)
The MC68HC11 has been chosen as an example of an MPU
with a dedicated serial port. This MPU transfers data MSB
-first and in 8-bit increments. The DIN word sent to the data
register starts with the SPI process. With three 8-bit
transfers, the A/D result is read into the MPU. The second
8-bit transfer clocks B11 through B8 of the A/D conversion
result into the processor. The third 8-bit transfer clocks
the remaining bits, B7 through B0, into the MPU. The data
is right justified into two memory locations. ANDing the
second byte with OFHEX clears the four most significant
bits. This operation was not included in the code. It can be
inserted in the data gathering loop or outside the loop
when the data is processed.
MC68HC11 Code
In this example the DIN word configures the input MUX for
a single-ended input to be applied to CHO. The conversion
result is output MSB-first.
20
Table 1. Microprocessor with Hardware Serial Interfaces
Compatible with the LTC1286/LTC1298
PART NUMBER
TYPE OF INTERFACE
Motorola
MC6805S2,S3
MC68HC11
MC68HC05
SPI
SPI
SPI
RCA
CDP68HC05
SPI
Hitachi
HD6305
HD63705
HD6301
HD63701
HD6303
HD64180
SCI Synchronous
SCI Synchronous
SCI Synchronous
SCI Synchronous
SCI Synchronous
CSI/O
National Semiconductor
COP400 Family
COP800 Family
NS8050U
HPC16000 Family
MICROWIRE †
MICROWIRE/PLUS†
MICROWIRE/PLUS†
MICROWIRE/PLUS†
Texas Instruments
TMS7002
TMS7042
TMS70C02
TMS70C42
TMS32011*
TMS32020
Serial Port
Serial Port
Serial Port
Serial Port
Serial Port
Serial Port
Intel
8051
Bit Manipulation on Parallel Port
* Requires external hardware
†
MICROWIRE and MICROWIRE/PLUS are trademarks of
National Semiconductor Corp.
LTC1286/LTC1298
U
TYPICAL APPLICATIONS N
Timing Diagram for Interface to the MC68HC11
CS
CLK
DIN
START
SGL/
DIFF
ODD/
SIGN MSBF
DON'T CARE
DOUT
MPU
TRANSMIT
WORD
0
0
0
0
0
0
0
SGL/
DIFF
1
ODD/
SIGN MSBF
?
?
?
?
?
B10
B9
B8
X
X
X
X
X
B7
X
B6
B5
B4
B3
B2
B1
B0
X
X
X
X
X
X
X
B2
B1
B0
BYTE 2
BYTE 1
MPU
RECEIVED
WORD
B11
?
?
?
?
?
0
?
BYTE 3 (DUMMY)
B11
B10
B9
B8
B7
B6
BYTE 2
BYTE 1
B5
B3
B4
BYTE 3
LTC1286/98 AI06
Hardware and Software Interface to the MC68HC11
DOUT FROM LTC1298 STORED IN MC68HC11 RAM
MSB
#62
0
0
0
0
B11
B10
B9
B8
ANALOG
INPUTS
LSB
#63
B7
B6
B5
B4
CH0
BYTE 1
B3
B2
B1
B0
CS
D0
CLK
SCK
LTC1298
DOUT
BYTE 2
CH1
DIN
MC68HC11
MISO
MOSI
LTC1286/98 AI07
LABEL MNEMONIC
LDAA
STAA
LDAA
STAA
LDAA
STAA
LDAA
STAA
LDAA
LOOP
OPERAND
#$50
$1028
#$1B
$1009
#$01
$50
#$A0
$51
#$00
STAA
LDX
$52
#$1000
BCLR
LDAA
STAA
LDAA
$08,X,#$01
$50
$102A
$1029
COMMENTS
CONFIGURATION DATA FOR SPCR
LOAD DATA INTO SPCR ($1028)
CONFIG. DATA FOR PORT D DDR
LOAD DATA INTO PORT D DDR
LOAD DIN WORD INTO ACC A
LOAD DIN DATA INTO $50
LOAD DIN WORD INTO ACC A
LOAD DIN DATA INTO $51
LOAD DUMMY DIN WORD INTO
ACC A
LOAD DUMMY DIN DATA INTO $52
LOAD INDEX REGISTER X WITH
$1000
D0 GOES LOW (CS GOES LOW)
LOAD DIN INTO ACC A FROM $50
LOAD DIN INTO SPI, START SCK
CHECK SPI STATUS REG
LABEL MNEMONIC
WAIT1 BPL
LDAA
STAA
WAIT2 LDAA
BPL
LDAA
STAA
LDAA
STAA
WAIT3 LDAA
BPL
BSET
LDAA
STAA
JMP
OPERAND
WAIT1
$51
$102A
$1029
WAIT2
$102A
$62
$52
$102A
$1029
WAIT3
$08,X#$01
$102A
$63
LOOP
COMMENTS
CHECK IF TRANSFER IS DONE
LOAD DIN INTO ACC A FROM $51
LOAD DIN INTO SPI, START SCK
CHECK SPI STATUS REG
CHECK IF TRANSFER IS DONE
LOAD LTC1291 MSBs INTO ACC A
STORE MSBs IN $62
LOAD DUMMY INTO ACC A
FROM $52
LOAD DUMMY DIN INTO SPI,
START SCK
CHECK SPI STATUS REG
CHECK IF TRANSFER IS DONE
DO GOES HIGH (CS GOES HIGH)
LOAD LTC1291 LSBs IN ACC
STORE LSBs IN $63
START NEXT CONVERSION
21
LTC1286/LTC1298
U
TYPICAL APPLICATIONS N
Interfacing to the Parallel Port of the INTEL 8051
Family
LABEL
The Intel 8051 has been chosen to demonstrate the
interface between the LTC1298 and parallel port microprocessors. Normally the CS, CLK and DIN signals would
be generated on 3 port lines and the DOUT signal read on
a 4th port line. This works very well. However, we will
demonstrate here an interface with the DIN and DOUT of the
LTC1298 tied together as described in the SERIAL INTERFACE section. This saves one wire.
LOOP 1
LOOP 2
The 8051 first sends the start bit and MUX address to the
LTC1298 over the data line connected to P1.2. Then P1.2
is reconfigured as an input (by writing to it a one) and the
8051 reads back the 12-bit A/D result over the same data
line.
CS
CLK
LTC1298
DOUT
DIN
ANALOG
INPUTS
P1.4
P1.3
P1.2
LOOP 3
8051
MUX ADDRESS
LOOP 4
A/D RESULT
LTC1286/98 TA01
MNEMONIC
OPERAND
COMMENTS
MOV
SETB
CLR
MOV
RLC
CLR
MOV
SETB
DJNZ
MOV
CLR
MOV
MOV
RLC
SETB
CLR
DJNZ
MOV
CLR
MOV
MOV
RLC
SETB
CLR
DJNZ
MOV
RRC
DJNZ
MOV
SETB
A, #FFH
P1.4
P1.4
R4, #04
A
P1.3
P1.2, C
P1.3
R4, LOOP 1
P1, #04
P1.3
R4, #09
C, P1.2
A
P1.3
P1.3
R4, LOOP 2
R2, A
A
R4, #04
C, P1.2
A
P1.3
P1.3
R4, LOOP 3
R4, #04
A
R4, LOOP 4
R3, A
P1.4
DIN word for LTC1298
Make sure CS is high
CS goes low
Load counter
Rotate DIN bit into Carry
SCLK goes low
Output DIN bit to LTC1298
SCLK goes high
Next bit
Bit 2 becomes an input
SCLK goes low
Load counter
Read data bit into Carry
Rotate data bit into Acc.
SCLK goes high
SCLK goes low
Next bit
Store MSBs in R2
Clear Acc.
Load counter
Read data bit into Carry
Rotate data bit into Acc.
SCLK goes high
SCLK goes low
Next bit
Load counter
Rotate right into Acc.
Next Rotate
Store LSBs in R3
CS goes high
DOUT FROM 1298 STORED IN 8501 RAM
MSB
R2 B11 B10 B9 B8 B7 B6 B5 B4
LSB
R3 B3 B2 B1 B0 0 0 0 0
MSBF BIT LATCHED
INTO LTC1298
CS
CLK
DATA
(DIN/DOUT)
START
SGL/
DIFF
ODD/
SIGN
8051 P1.2 OUTPUTS DATA
TO LTC1298
8051 P1.2 RECONFIGURED
AS IN INPUT AFTER THE 4TH RISING CLK
AND BEFORE THE 4TH FALLING CLK
22
MSBF
B11
B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
LTC1298 SENDS A/D RESULT
BACK TO 8051 P1.2
LTC1298 TAKES CONTROL OF DATA
LINE ON 4TH FALLING CLK
LTC1286/98 TA02
LTC1286/LTC1298
U
TYPICAL APPLICATIONS N
A “Quick Look” Circuit for the LTC1286
Users can get a quick look at the function and timing of the
LT1286 by using the following simple circuit (Figure 13).
VREF is tied to VCC. VIN is applied to the +IN input and the
–IN input is tied to the ground. CS is driven at 1/16 the
clock rate by the 74C161 and DOUT outputs the data. The
output data from the DOUT pin can be viewed on an
oscilloscope that is set up to trigger on the falling edge of
CS (Figure 14). Note the LSB data is partially clocked out
before CS goes high.
4.7µF
VREF
VIN
5V
+IN
CLK
LTC1286
–IN
DOUT
CS
GND
5V
CLR
VCC
CLK
RC
A
QA
B
QB
74C161
C
QC
D
QD
P
T
GND
LOAD
VCC
Micropower Battery Voltage Monitor
A common problem in battery systems is battery voltage
monitoring. This circuit monitors the 10 cell stack of NiCad
or NiMH batteries found in laptop computers. It draws only
67µA from the 5V supply at fSMPL = 0.1kHz and 25µA to
55µA from the battery. The 12-bits of resolution of the
LTC1286 are positioned over the desired range of 8V to
16V. This is easily accomplished by using the ADC’s
differential inputs. Tying the –input to the reference gives
an ADC input span of VREF to 2VREF (2.5V to 5V). The
resistor divider then scales the input voltage for 8V to 16V.
BATTERY MONITOR
INPUT 8V TO 16V
5V
0.1µF
200k
39k
VCC
+IN
CS
LTC1286
DOUT
–IN
CLOCK IN 250kHz
91k
1µF
CLK
VREF
GND
LT1004-2.5
3Ω
TO OSCILLOSCOPE
LTC1286/98 F13
Figure 13. “Quick Look” Circuit for the LTC1286
LTC1286/98 F15
Figure 15. Micropower Battery Voltage Monitor
NULL
BIT
MSB
(B11)
LSB
(B0)
VERTICAL: 5V/DIV
HORIZONTAL: 10µs/DIV
LTC1286/98 F14
Figure 14. Scope Trace the LTC1286 “Quick Look” Circuit
Showing A/D Output 101010101010 (AAAHEX)
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
23
LTC1286/LTC1298
U
PACKAGE DESCRIPTION
Dimensions in inches (millimeters) unless otherwise noted.
N8 Package
8-Lead Plastic DIP
0.300 – 0.320
(7.620 – 8.128)
0.045 – 0.065
(1.143 – 1.651)
0.400
(10.160)
MAX
0.130 ± 0.005
(3.302 ± 0.127)
8
0.009 – 0.015
(0.229 – 0.381)
(
+0.025
0.325 –0.015
8.255
+0.635
–0.381
)
7
6
5
0.065
(1.651)
TYP
0.045 ± 0.015
(1.143 ± 0.381)
0.100 ± 0.010
(2.540 ± 0.254)
0.125
(3.175)
MIN
0.250 ± 0.010
(6.350 ± 0.254)
0.020
(0.508)
MIN
1
2
4
3
0.018 ± 0.003
(0.457 ± 0.076)
S8 Package
8-Lead Plastic SOIC
0.189 – 0.197*
(4.801 – 5.004)
0.010 – 0.020
× 45°
(0.254 – 0.508)
0.008 – 0.010
(0.203 – 0.254)
0.053 – 0.069
(1.346 – 1.752)
0°– 8° TYP
0.016 – 0.050
0.406 – 1.270
0.014 – 0.019
(0.355 – 0.483)
8
7
6
5
0.004 – 0.010
(0.101 – 0.254)
0.050
(1.270)
BSC
0.150 – 0.157*
(3.810 – 3.988)
0.228 – 0.244
(5.791 – 6.197)
1
2
3
4
SO8 0294
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.006 INCH (0.15mm).
24
Linear Technology Corporation
sn128698 128698fs LT/GP 0394 10K • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7487
(408) 432-1900 ● FAX: (408) 434-0507 ● TELEX: 499-3977
 LINEAR TECHNOLOGY CORPORATION 1994