Richtek GRM31CR61E106K 3a, 23v, 340khz synchronous step-down converter Datasheet

RT8250
3A, 23V, 340kHz Synchronous Step-Down Converter
General Description
The RT8250 is a high-efficiency synchronous step-down
DC/DC converter that can deliver up to 3A output current
from 4.5V to 23V input supply. The RT8250's current mode
architecture and external compensation allow the transient
response to be optimized over a wide range of loads and
output capacitors. Cycle-by-cycle current limit provides
protection against shorted outputs and soft-start eliminates
input current surge during start-up. The RT8250 also
provides output under voltage protection and thermal
shutdown protection. The low current (<3μA) shutdown
mode provides output disconnection, enabling easy power
management in battery-powered systems.
Ordering Information
RT8250
Package Type
SP : SOP-8 (Exposed Pad-Option 1)
Lead Plating System
G : Green (Halogen Free and Pb Free)
Note :
Richtek products are :
`
RoHS compliant and compatible with the current requirements of IPC/JEDEC J-STD-020.
`
Suitable for use in SnPb or Pb-free soldering processes.
Marking Information
Features
4.5V to 23V Input Voltage Range
1.5% High Accuracy Feedback Voltage
3A Output Current
Integrated N-MOSFET Switches
Current Mode Control
Fixed Frequency Operation : 340kHz
Output Adjustable from 0.925V to 20V
Up to 95% Efficiency
Programmable Soft-Start
Stable with Low-ESR Ceramic Output Capacitors
Cycle-by-Cycle Over Current Protection
Input Under Voltage Lockout
Output Under Voltage Protection
Thermal Shutdown Protection
Thermally Enhanced SOP-8 (Exposed Pad) Package
RoHS Compliant and Halogen Free
Applications
Industrial and Commercial Low Power Systems
Computer Peripherals
LCD Monitors and TVs
Green Electronics/Appliances
Point of Load Regulation of High-Performance DSPs,
FPGAs and ASICs.
Pin Configurations
(TOP VIEW)
RT8250GSP : Product Number
RT8250
GSPYMDNN
YMDNN : Date Code
BOOT
VIN
2
SW
3
GND
4
GND
9
8
SS
7
EN
6
COMP
5
FB
SOP-8 (Exposed Pad)
DS8250-05 March 2011
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1
RT8250
Typical Application Circuit
2
VIN
4.75V to 23V
CIN
10µFx2
REN
100k
VIN
1
RT8250
7 EN
8 SS
CSS
0.1µF
BOOT
4,
Exposed Pad(9)
GND
SW 3
CBOOT L1
10nF 10µH
R1
26.1k
FB 5
COMP
6
CC
RC
3.9nF 6.8k
VOUT
3.3V/3A
COUT
22µFx2
R2
10k
CP
NC
Table 1. Recommended Component Selection
VOUT (V)
R1 (kΩ)
R2 (kΩ)
RC (kΩ)
CC (nF)
L (μH)
COUT (μF)
15
153
10
30
3.9
33
22 x 2
10
97.6
10
20
3.9
22
22 x 2
8
76.8
10
15
3.9
22
22 x 2
5
45.3
10
13
3.9
15
22 x 2
3.3
26.1
10
6.8
3.9
10
22 x 2
2.5
16.9
10
6.2
3.9
6.8
22 x 2
1.8
9.53
10
4.3
3.9
4.7
22 x 2
1.2
3
10
3
3.9
3.6
22 x 2
Functional Pin Description
Pin No.
Pin Name
Pin Function
Bootstrap for High Side Gate Driver. Connect a 10nF or greater ceramic capacitor
1
BOOT
2
VIN
Voltage Supply Input. The input voltage range is from 4.5V to 23V. A suitable large
capacitor must be bypassed with this pin.
3
SW
Switching Node. Connect the output LC filter between the SW pin and output load.
4,
9 (Exposed Pad)
5
GND
FB
from the BOOT pin to SW pin.
Ground. The exposed pad must be soldered to a large PCB and connected to
GND for maximum power dissipation.
Output Voltage Feedback Input. The feedback reference voltage is 0.925V
typically.
Compensation Node. This pin is used for compensating the regulation control
6
COMP
loop. A series RC network is required to be connected from COMP to GND. If it is
needed, an additional capacitor should be connected from COMP to GND.
Enable Input. A logic high enables the converter, a logic low forces the converter
7
EN
8
SS
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into shutdown mode reducing the supply current to less than 3μA. For automatic
startup, connect this pin to VIN with a 100kΩ pull up resistor.
Soft-Start Control Input. The soft-start period can be set by connecting a capacitor
from the SS to GND. A 0.1μF capacitor sets the soft-start period to 13ms typically.
DS8250-05 March 2011
RT8250
Function Block Diagram
VIN
Internal
Regulator
Shutdown
Comparator
+
1.2V
5k
VA VCC
Foldback
Control
+
Lockout
Comparator
EN
VA
BOOT
S
Q
100mΩ
SW
0.5V
+
UV
Comparator
2.5V
3V
Current Sense
Slope Comp Amplifier
+
-
Oscillator
340kHz/110kHz
+
R
Q
85mΩ
Current
Comparator
VCC
GND
7µA
SS
0.925V
+
+ EA
-
COMP
FB
Absolute Maximum Ratings
(Note 1)
Supply Voltage, VIN -----------------------------------------------------------------------------------------Switching Voltage, SW ------------------------------------------------------------------------------------<20ns ---------------------------------------------------------------------------------------------------------BOOT Voltage ------------------------------------------------------------------------------------------------The Other Pins -----------------------------------------------------------------------------------------------Power Dissipation, PD @ TA = 25°C
SOP-8 (Exposed Pad) -------------------------------------------------------------------------------------Package Thermal Resistance (Note 2)
SOP-8 (Exposed Pad), θJA --------------------------------------------------------------------------------SOP-8 (Exposed Pad), θJC -------------------------------------------------------------------------------Junction Temperature ---------------------------------------------------------------------------------------Lead Temperature (Soldering, 10 sec.) -----------------------------------------------------------------Storage Temperature Range ------------------------------------------------------------------------------ESD Susceptibility (Note 3)
HBM (Human Body Mode) --------------------------------------------------------------------------------MM (Machine Mode) -----------------------------------------------------------------------------------------
Recommended Operating Conditions
−0.3V to 24V
−0.3V to (VIN + 0.3V)
−0.3V to (VIN + 3V)
(VSW − 0.3V) to (VSW + 6V)
−0.3V to 6V
1.333W
75°C/W
15°C/W
150°C
260°C
−65°C to 150°C
2kV
200V
(Note 4)
Supply Voltage, VIN ------------------------------------------------------------------------------------------ 4.5V to 23V
Enable Voltage, VEN ----------------------------------------------------------------------------------------- 0V to 5.5V
Junction Temperature Range ------------------------------------------------------------------------------- −40°C to 125°C
Ambient Temperature Range ------------------------------------------------------------------------------- −40°C to 85°C
DS8250-05 March 2011
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RT8250
Electrical Characteristics
(VIN = 12V, TA = 25°C unless otherwise specified)
Parameter
Symbol
Test Conditions
Min
Typ
Max
Unit
Shutdown Supply Current
VEN = 0V
--
0.3
3
μA
Supply Current
VEN = 3 V, V FB = 1V
--
0.7
1.2
mA
0.911
0.925
0.939
V
--
1250
--
μA/V
Feedback Voltage
VFB
4.75V ≤ VIN ≤ 23V
Error Amplifier Transconductance
GEA
ΔIC = ±10μA
High-Side Switch On-Resistance
RDS(ON)1
--
100
--
mΩ
Low-Side Switch On-Resistance
RDS(ON)2
--
85
--
mΩ
--
0
10
μA
--
5.5
--
A
--
1.4
--
A
High-Side Switch Leakage Current
VEN = 0V, V SW = 0V
Min. Duty Cycle
VBOOT – VSW = 4.8V
From Drain to Source
Upper Switch Current Limit
Lower Switch Current Limit
COMP to Current Sense
Transconductance
Oscillation Frequency
GCS
--
5.2
--
A/V
fOSC1
300
340
380
kHz
Short Circuit Oscillation Frequency
fOSC2
VFB = 0V
--
110
--
kHz
Maximum Duty Cycle
DMAX
VFB = 0.8V
--
90
--
%
Minimum On Time
tON
--
200
--
ns
Logic-High
VIH
2.7
--
--
Logic-Low
Input Under Voltage Lockout
Threshold
Input Under Voltage Lockout
Threshold Hysterisis
Soft-Start Current
VIL
--
--
0.4
3.8
4.2
4.4
V
--
200
--
mV
VSS = 0V
--
7
--
μA
CSS = 0.1μF
--
13
--
ms
--
150
--
°C
EN Threshold
Voltage
VIN Rising
Soft-Start Period
Thermal Shutdown
T SD
V
Note 1. Stresses listed as the above "Absolute Maximum Ratings" may cause permanent damage to the device. These are for
stress ratings. Functional operation of the device at these or any other conditions beyond those indicated in the
operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended
periods may remain possibility to affect device reliability.
Note 2. θJA is measured in the natural convection at TA = 25°C on a high effective thermal conductivity four-layer test board of
JEDEC 51-7 thermal measurement standard. The case position of θJC is on the exposed pad of the package.
Note 3. Devices are ESD sensitive. Handling precaution is recommended.
Note 4. The device is not guaranteed to function outside its operating conditions.
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DS8250-05 March 2011
RT8250
Typical Operating Characteristics
Efficiency vs. Output Current
Output Voltage vs. Output Current
3.33
100
3.32
90
VIN = 23V
3.31
VIN = 12V
70
Output Voltage (V)
Efficiency (%)
80
VIN = 4.75V
60
50
40
30
3.30
VIN = 4.75V
3.29
3.28
3.27
VIN = 12V
VIN = 23V
3.26
3.25
20
10
3.24
VOUT = 3.3V
VOUT = 3.3V
3.23
0
0
0.5
1
1.5
2
2.5
0
3
0.5
1
2.5
3
Reference Voltage vs. Temperature
Reference Voltage vs. Input Voltage
0.940
0.930
0.935
Reference Voltage (V)
0.932
0.928
0.926
0.924
0.922
0.930
0.925
0.920
0.915
VIN = 6V, VOUT = 3.3V
VOUT = 3.3V, IOUT = 0A
0.920
0.910
4
6
8
10
12
14
16
18
20
22
24
-50
-25
0
Input Voltage (V)
25
50
75
100
125
Temperature (°C)
Frequency vs. Temperature
Frequency. vs. Input Voltage
350
350
345
345
340
340
Frequency (kHz)
Frequency (kHz)
2
Output Current (A)
Output Current (A)
Reference Voltage (V)
1.5
335
330
325
320
315
310
335
330
325
320
315
310
305
VOUT = 3.3V, IOUT = 0A
300
305
VIN = 12V, VOUT = 3.3V, IOUT = 0A
300
4
6
8
10
12
14
16
18
Input Voltage (V)
DS8250-05 March 2011
20
22
24
-50
-25
0
25
50
75
100
125
Temperature (°C)
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RT8250
Current Limit vs. Temperature
7.0
6.5
6.5
6.0
6.0
Current Limit (A)
Current Limit (A)
Current Limit vs. Duty Cycle
7.0
5.5
5.0
4.5
4.0
3.5
5.5
5.0
4.5
4.0
3.5
VOUT = 3.3V
3.0
VIN = 12V, VOUT = 3.3V
3.0
0
10
20
30
40
50
60
70
80
90
100
-50
-25
0
25
50
75
100
125
Temperature (°C)
Duty Cycle (%)
Power On from EN
Power Off from EN
VEN
(5V/Div)
VEN
(5V/Div)
VOUT
(2V/Div)
VOUT
(2V/Div)
IOUT
(2A/Div)
IOUT
(2A/Div)
VIN = 12V, VOUT = 3.3V, IOUT = 3A
VIN = 12V, VOUT = 3.3V, IOUT = 3A
Time (5ms/Div)
Time (1ms/Div)
Power On from VIN
Switching
VOUT
(10mV/Div)
VIN
(5V/Div)
VSW
(10V/Div)
VOUT
(2V/Div)
IL
(2A/Div)
VIN = 12V, VOUT = 3.3V, IOUT = 3A
Time (5ms/Div)
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IL
(2A/Div)
VIN = 12V, VOUT = 3.3V, IOUT = 3A
Time (1μs/Div)
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RT8250
Load Transient Response
Load Transient Response
VOUT
(200mV/Div)
VOUT
(200mV/Div)
IOUT
(2A/Div)
IOUT
(2A/Div)
VIN = 12V, VOUT = 3.3V, IOUT = 0A to 1.5A
Time (100μs/Div)
DS8250-05 March 2011
VIN = 12V, VOUT = 3.3V, IOUT = 0A to 3A
Time (100μs/Div)
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RT8250
Application Information
The RT8250 is a synchronous high voltage buck converter
that can support the input voltage range from 4.5V to 23V
and the output current can be up to 3A.
can be programed by the external capacitor between SS
pin and GND. The chip provides a 7μA charge current for
the external capacitor. If a 0.1μF capacitor is used to set
the soft-start and its period will be 13ms(typ.).
Output Voltage Setting
The resistive divider allows the FB pin to sense the output
voltage as shown in Figure 1.
V OUT
R1
FB
RT8250
R2
GND
Figure 1. Output Voltage Setting
The output voltage is set by an external resistive divider
according to the following equation :
VOUT = VFB ⎛⎜ 1+ R1 ⎞⎟
⎝ R2 ⎠
Where VFB is the feedback reference voltage (0.925V typ.).
External Bootstrap Diode
Connect a 10nF low ESR ceramic capacitor between the
BOOT pin and SW pin. This capacitor provides the gate
driver voltage for the high side MOSFET.
It is recommended to add an external bootstrap diode
between an external 5V and the BOOT pin for efficiency
improvement when input voltage is lower than 5.5V or duty
ratio is higher than 65%. The bootstrap diode can be a
low cost one such as 1N4148 or BAT54.
The external 5V can be a 5V fixed input from system or a
5V output of the RT8250. Note that the external boot
voltage must be lower than 5.5V.
5V
BOOT
RT8250
10nF
SW
Figure 2. External Bootstrap Diode
Soft-Start
The RT8250 contains an external soft-start clamp that
gradually raises the output voltage. The soft-start timming
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Inductor Selection
The inductor value and operating frequency determine the
ripple current according to a specific input and output
voltage. The ripple current ΔIL increases with higher VIN
and decreases with higher inductance.
V
V
ΔIL = ⎡⎢ OUT ⎤⎥ × ⎡⎢1− OUT ⎤⎥
VIN ⎦
⎣ f ×L ⎦ ⎣
Having a lower ripple current reduces not only the ESR
losses in the output capacitors but also the output voltage
ripple. High frequency with small ripple current can achieve
highest efficiency operation. However, it requires a large
inductor to achieve this goal.
For the ripple current selection, the value of ΔI L =
0.2375(IMAX) will be a reasonable starting point. The largest
ripple current occurs at the highest VIN. To guarantee that
the ripple current stays below the specified maximum,
the inductor value should be chosen according to the
following equation :
⎡ VOUT ⎤ ⎡
VOUT ⎤
L =⎢
× ⎢1 −
⎥
⎥
f
I
V
×
Δ
L(MAX) ⎦ ⎣
IN(MAX) ⎦
⎣
Inductor Core Selection
The inductor type must be selected once the value for L
is known. Generally speaking, high efficiency converters
can not afford the core loss found in low cost powdered
iron cores. So, the more expensive ferrite or
mollypermalloy cores will be a better choice.
The selected inductance rather than the core size for a
fixed inductor value is the key for actual core loss. As the
inductance increases, core losses decrease. Unfortunately,
increase of the inductance requires more turns of wire
and therefore the copper losses will increase.
Ferrite designs are preferred at high switching frequency
due to the characteristics of very low core losses. So,
design goals can focus on the reduction of copper loss
and the saturation prevention.
DS8250-05 March 2011
RT8250
Ferrite core material saturates “hard”, which means that
inductance collapses abruptly when the peak design
current is exceeded. The previous situation results in an
abrupt increase in inductor ripple current and consequent
output voltage ripple.
Do not allow the core to saturate!
Different core materials and shapes will change the size/
current and price/current relationship of an inductor.
Toroid or shielded pot cores in ferrite or permalloy materials
are small and do not radiate energy. However, they are
usually more expensive than the similar powdered iron
inductors. The rule for inductor choice mainly depends
on the price vs. size requirement and any radiated field/
EMI requirements.
CIN and COUT Selection
The input capacitance, C IN, is needed to filter the
trapezoidal current at the source of the high side MOSFET.
To prevent large ripple current, a low ESR input capacitor
sized for the maximum RMS current should be used. The
RMS current is given by :
V
IRMS = IOUT(MAX) OUT
VIN
VIN
−1
VOUT
This formula has a maximum at VIN = 2VOUT, where
I RMS = I OUT /2. This simple worst-case condition is
commonly used for design because even significant
deviations do not offer much relief.
Choose a capacitor rated at a higher temperature than
required. Several capacitors may also be paralleled to
meet size or height requirements in the design.
For the input capacitor, a 10μF x 2 low ESR ceramic
capacitor is recommended. For the recommended
capacitor, please refer to table 3 for more detail.
The selection of COUT is determined by the required ESR
to minimize voltage ripple.
Moreover, the amount of bulk capacitance is also a key
for COUT selection to ensure that the control loop is stable.
Loop stability can be checked by viewing the load transient
response as described in a later section.
The output ripple, ΔVOUT , is determined by :
1
⎤
ΔVOUT ≤ ΔIL ⎡⎢ESR +
8fC
OUT ⎥⎦
⎣
DS8250-05 March 2011
The output ripple will be highest at the maximum input
voltage since ΔIL increases with input voltage. Multiple
capacitors placed in parallel may be needed to meet the
ESR and RMS current handling requirement. Dry tantalum,
special polymer, aluminum electrolytic and ceramic
capacitors are all available in surface mount packages.
Special polymer capacitors offer very low ESR value.
However, it provides lower capacitance density than other
types. Although Tantalum capacitors have the highest
capacitance density, it is important to only use types that
pass the surge test for use in switching power supplies.
Aluminum electrolytic capacitors have significantly higher
ESR. However, it can be used in cost-sensitive applications
for ripple current rating and long term reliability
considerations. Ceramic capacitors have excellent low
ESR characteristics but can have a high voltage coefficient
and audible piezoelectric effects. The high Q of ceramic
capacitors with trace inductance can also lead to significant
ringing.
Higher values, lower cost ceramic capacitors are now
becoming available in smaller case sizes. Their high ripple
current, high voltage rating and low ESR make them ideal
for switching regulator applications. However, care must
be taken when these capacitors are used at input and
output. When a ceramic capacitor is used at the input
and the power is supplied by a wall adapter through long
wires, a load step at the output can induce ringing at the
input, VIN. At best, this ringing can couple to the output
and be mistaken as loop instability. At worst, a sudden
inrush of current through the long wires can potentially
cause a voltage spike at VIN large enough to damage the
part.
Checking Transient Response
The regulator loop response can be checked by looking
at the load transient response. Switching regulators take
several cycles to respond to a step in load current. When
a load step occurs, VOUT immediately shifts by an amount
equal to ΔILOAD (ESR) also begins to charge or discharge
COUT generating a feedback error signal for the regulator
to return VOUT to its steady-state value. During this recovery
time, VOUT can be monitored for overshoot or ringing that
would indicate a stability problem.
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RT8250
Thermal Considerations
Layout Consideration
For continuous operation, do not exceed the maximum
operation junction temperature 125°C. The maximum
power dissipation depends on the thermal resistance of
IC package, PCB layout, the rate of surroundings airflow
and temperature difference between junction to ambient.
The maximum power dissipation can be calculated by
following formula :
Follow the PCB layout guidelines for optimal performance
of the RT8250.
PD(MAX) = ( TJ(MAX) − TA ) / θJA
`
Keep the traces of the main current paths as short and
wide as possible.
`
Put the input capacitor as close as possible to the device
pins (VIN and GND).
`
SW node is with high frequency voltage swing and
should be kept at small area. Keep sensitive
components away from the SW node to prevent stray
capacitive noise pick-up.
`
Place the feedback components to the FB pin and
COMP pin as close as possible.
`
The GND pin and Exposed Pad should be connected to
a strong ground plane for heat sinking and noise
protection.
Where T J(MAX) is the maximum operation junction
temperature, TA is the ambient temperature and the θJA is
the junction to ambient thermal resistance.
For recommended operating conditions specification of
RT8250, the maximum junction temperature is 125°C. The
junction to ambient thermal resistance θJA is layout
dependent. For PSOP-8 package, the thermal resistance
θJA is 75°C/W on the standard JEDEC 51-7 four-layers
thermal test board. The maximum power dissipation at TA
= 25°C can be calculated by following formula :
Input capacitor must be placed
as close to the IC as possible.
SW
GND
V IN
PD(MAX) = (125°C − 25°C) / (75°C/W) = 1.333W for
PSOP-8 package
The maximum power dissipation depends on operating
ambient temperature for fixed T J(MAX) and thermal
resistance θJA. For RT8250 package, the Figure 3 of
derating curve allows the designer to see the effect of
rising ambient temperature on the maximum power
dissipation allowed.
CS
The feedback
components must be
connected as close to
the device as possible.
C IN
BOOT
V OUT
C OUT
L1
8
SS
7
EN
3
6
COMP
4
5
FB
VIN
2
SW
GND
GND
CC
CP
RC
R1
V OUT
SW should be connected to inductor by
wide and short trace. Keep sensitive
components away from this trace.
R2
GND
Maximum Power Dissipation (W)
1.6
Four-Layer PCB
Figure 4. PCB Layout Guide
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0.0
0
25
50
75
100
125
Ambient Temperature (°C)
Figure 3. Derating Curve for RT8250 Package
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DS8250-05 March 2011
RT8250
Table 2. Suggested Inductors for Typical Application Circuit
Component Supplier
Series
Dimensions (mm)
TDK
VLF10045
10 x 9.7 x 4.5
TAIYO YUDEN
NR8040
8x8x4
Table 3. Suggested Capacitors for CIN and COUT
Component Supplier
Part No.
Capacitance (μF)
Case Size
MURATA
GRM31CR61E106K
10
1206
TDK
C3225X5R1E106K
10
1206
TAIYO YUDEN
TMK316BJ106ML
10
1206
MURATA
GRM31CR60J476M
47
1206
TDK
C3225X5R0J476M
47
1210
TAIYO YUDEN
EMK325BJ476MM
47
1210
MURATA
GRM32ER71C226M
22
1210
TDK
C3225X5R1C226M
22
1210
DS8250-05 March 2011
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RT8250
Outline Dimension
H
A
M
EXPOSED THERMAL PAD
(Bottom of Package)
Y
J
X
B
F
C
I
D
Dimensions In Millimeters
Symbol
Dimensions In Inches
Min
Max
Min
Max
A
4.801
5.004
0.189
0.197
B
3.810
4.000
0.150
0.157
C
1.346
1.753
0.053
0.069
D
0.330
0.510
0.013
0.020
F
1.194
1.346
0.047
0.053
H
0.170
0.254
0.007
0.010
I
0.000
0.152
0.000
0.006
J
5.791
6.200
0.228
0.244
M
0.406
1.270
0.016
0.050
X
2.000
2.300
0.079
0.091
Y
2.000
2.300
0.079
0.091
X
2.100
2.500
0.083
0.098
Y
3.000
3.500
0.118
0.138
Option 1
Option 2
8-Lead SOP (Exposed Pad) Plastic Package
Richtek Technology Corporation
Richtek Technology Corporation
Headquarter
Taipei Office (Marketing)
5F, No. 20, Taiyuen Street, Chupei City
5F, No. 95, Minchiuan Road, Hsintien City
Hsinchu, Taiwan, R.O.C.
Taipei County, Taiwan, R.O.C.
Tel: (8863)5526789 Fax: (8863)5526611
Tel: (8862)86672399 Fax: (8862)86672377
Email: [email protected]
Information that is provided by Richtek Technology Corporation is believed to be accurate and reliable. Richtek reserves the right to make any change in circuit
design, specification or other related things if necessary without notice at any time. No third party intellectual property infringement of the applications should be
guaranteed by users when integrating Richtek products into any application. No legal responsibility for any said applications is assumed by Richtek.
www.richtek.com
12
DS8250-05 March 2011
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