AD AD7891ASZ-12 Lc2mos 8-channel, 12-bit high speed data acquisition system Datasheet

a
LC2MOS 8-Channel, 12-Bit
High Speed Data Acquisition System
AD7891
FEATURES
Fast 12-Bit ADC with 1.6 ␮s Conversion Time
8 Single-Ended Analog Input Channels
Overvoltage Protection on Each Channel
Selection of Input Ranges:
ⴞ5 V, ⴞ10 V for AD7891-1
0 to +2.5 V, 0 to +5 V, ⴞ2.5 V for AD7891-2
Parallel and Serial Interface
On-Chip Track/Hold Amplifier
On-Chip Reference
Single-Supply, Low Power Operation (100 mW Max)
Power-Down Mode (75 ␮W Typ)
APPLICATIONS
Data Acquisition Systems
Motor Control
Mobile Communication Base Stations
Instrumentation
FUNCTIONAL BLOCK DIAGRAM
VDD VDD
VIN1A
VIN1B
VIN2A
VIN2B
VIN3A
VIN3B
VIN4A
VIN4B
VIN5A
VIN5B
VIN6A
VIN6B
VIN7A
VIN7B
VIN8A
VIN8B
REF OUT/
REF IN
REF GND
2.5V
REFERENCE
STANDBY
AD7891
12-BIT
ADC
M
U
X
TRACK/HOLD
DATA/
CONTROL
LINES
ADDRESS
DECODE
CLOCK
CONTROL LOGIC
WR CS RD EOC CONVST MODE
AGND AGND DGND
GENERAL DESCRIPTION
PRODUCT HIGHLIGHTS
The AD7891 is an 8-channel, 12-bit data acquisition system
with a choice of either parallel or serial interface structure. The
part contains an input multiplexer, an on-chip track/hold amplifier, a high speed 12-bit ADC, a 2.5 V reference, and a high
speed interface. The part operates from a single 5 V supply and
accepts a variety of analog input ranges across two models, the
AD7891-1 (± 5 V and ± 10 V) and the AD7891-2 (0 V to +2.5 V,
0 V to +5 V, and ± 2.5 V).
1. The AD7891 is a complete monolithic 12-bit data acquisition
system that combines an 8-channel multiplexer, 12-bit ADC,
2.5 V reference, and track/hold amplifier on a single chip.
The AD7891 provides the option of either a parallel or serial
interface structure determined by the MODE pin. The part
has standard control inputs and fast data access times for both
the serial and parallel interfaces, ensuring easy interfacing to
modern microprocessors, microcontrollers, and digital signal
processors.
In addition to the traditional dc accuracy specifications, such as
linearity, full-scale and offset errors, the part is also specified for
dynamic performance parameters, including harmonic distortion
and signal-to-noise ratio.
2. The AD7891-2 features a conversion time of 1.6 ms and an
acquisition time of 0.4 ms. This allows a sample rate of
500 kSPS when sampling one channel and 62.5 kSPS when
channel hopping. These sample rates can be achieved using
either a software or hardware convert start. The AD7891-1
has an acquisition time of 0.6 ms when using a hardware
convert start and an acquisition time of 0.7 ms when using a
software convert start. These acquisition times allow sample
rates of 454.5 kSPS and 435 kSPS, respectively, for hardware
and software convert start.
3. Each channel on the AD7891 has overvoltage protection. This
means an overvoltage on an unselected channel does not affect
the conversion on a selected channel. The AD7891-1 can
withstand overvoltages of ± 17 V.
Power dissipation in normal mode is 82 mW typical; in
the standby mode, this is reduced to 75 mW typ. The part is
available in a 44-terminal MQFP and a 44-lead PLCC.
REV. D
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties that
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
www.analog.com
Fax: 781/326-8703
© 2004 Analog Devices, Inc. All rights reserved.
(VDD = 5 V ⴞ 5%, AGND = DGND = 0 V, REF IN = 2.5 V. All specifications TMIN to TMAX,
AD7891–SPECIFICATIONS unless otherwise noted.)
Parameter
A Version1 B Version
Y Version
Unit
DYNAMIC PERFORMANCE2
Signal-to-(Noise + Distortion) Ratio4
@ 25∞C
TMIN to TMAX
Total Harmonic Distortion4
Peak Harmonic or Spurious Noise4
Intermodulation Distortion4
Second-Order Terms
Third-Order Terms
Channel-to-Channel Isolation4
Test Conditions/Comments
Sample Rate = 454.5 kSPS3 (AD7891-1),
500 kSPS3 (AD7891-2). Any channel.
70
70
–78
–80
70
70
–78
–80
70
70
–78
–80
dB min
dB min
dB max
dB max
–80
–80
–80
–80
–80
–80
–80
–80
–80
dB typ
dB typ
dB max
12
12
12
Bits
12
±1
±1
±3
0.6
±4
0.1
±3
0.6
±4
0.2
12
± 0.75
±1
±3
0.6
±4
0.1
±3
0.6
±4
0.2
12
±1
±1
±3
0.6
±4
0.1
±3
0.6
±4
0.2
Bits
LSB max
LSB max
LSB max
LSB typ
LSB max
LSB typ
LSB max
LSB typ
LSB max
LSB typ
1.5 LSB max.
Input ranges of 0 V to 2.5 V, 0 V to 5 V.
1 LSB max.
Input ranges of ± 2.5 V, ± 5 V, ± 10 V.
1.5 LSB max.
Input ranges of ± 2.5 V, ± 5 V, ± 10 V.
1.5 LSB max.
±5
± 10
7.5
15
0 to 2.5
0 to 5
± 2.5
1.5
± 50
±5
± 10
7.5
15
0 to 2.5
0 to 5
± 2.5
1.5
± 50
±5
± 10
7.5
15
0 to 2.5
0 to 5
± 2.5
1.5
± 50
V
V
kW min
kW min
V
V
V
kW min
nA max
Input applied to both VINXA and VINXB.
Input applied to VINXA, VINXB = AGND.
Input range of ± 5 V.
Input range of ± 10 V.
Input applied to both VINXA and VINXB.
Input applied to VINXA, VINXB = AGND.
Input applied to VINXA, VINXB = REF IN6.
Input ranges of ± 2.5 V and 0 V to 5 V.
Input range of 0 V to 2.5 V.
REFERENCE INPUT/OUTPUT
REF IN Input Voltage Range
Input Impedance
Input Capacitance5
REF OUT Output Voltage
REF OUT Error @ 25∞C
TMIN to TMAX
REF OUT Temperature Coefficient
REF OUT Output Impedance
2.375/2.625
1.6
10
2.5
± 10
± 20
25
5
2.375/2.625
1.6
10
2.5
± 10
± 20
25
5
2.375/2.625
1.6
10
2.5
± 10
± 20
25
5
V min/V max
kW min
pF max
V nom
mV max
mV max
ppm/∞C typ
kW nom
2.5 V ± 5%.
Resistor connected to internal reference node.
LOGIC INPUTS
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IINH
Input Capacitance5 CIN
2.4
0.8
± 10
10
2.4
0.8
± 10
10
2.4
0.8
± 10
10
V min
V max
mA max
pF max
VDD = 5 V ± 5%.
VDD = 5 V ± 5%.
DC ACCURACY
Resolution
Minimum Resolution for which
No Missing Codes Are Guaranteed
Relative Accuracy4
Differential Nonlinearity4
Positive Full-Scale Error4
Positive Full-Scale Error Match4, 5
Unipolar Offset Error
Unipolar Offset Error Match5
Negative Full-Scale Error4
Negative Full-Scale Error Match4, 5
Bipolar Zero Error
Bipolar Zero Error Match5
fa = 9 kHz, fb = 9.5 kHz.
Any channel.
ANALOG INPUTS
AD7891-1 Input Voltage Range
AD7891-1 VINXA Input Resistance
AD7891-1 VINXA Input Resistance
AD7891-2 Input Voltage Range
AD7891-2 VINXA Input Resistance
AD7891-2 VINXA Input Current
–2–
See REF IN input impedance.
REV. D
AD7891
Parameter
LOGIC OUTPUTS
Output High Voltage, VOH
Output Low Voltage, VOL
DB11to DB0
Floating-State Leakage Current
Floating-State Capacitance5
Output Coding
A Version1
B Version
Y Version
Unit
Test Conditions/Comments
4.0
0.4
4.0
0.4
4.0
0.4
V min
V max
ISOURCE = 200 mA.
ISINK = 1.6 mA.
± 10
15
± 10
15
± 10
15
mA max
pF max
Straight (Natural) Binary
Twos Complement
CONVERSION RATE
Conversion Time
Track/Hold Acquisition Time
POWER REQUIREMENTS
VDD
IDD
Normal Mode
Standby Mode
Power Dissipation
Normal Mode
Standby Mode
Data format bit of control register = 0.
Data format bit of control register = 1.
1.6
0.6
0.7
0.4
1.6
0.6
0.7
0.4
1.6
0.6
0.7
0.4
ms max
ms max
ms max
ms max
AD7891-1 hardware conversion.
AD7891-1 software conversion.
AD7891-2.
5
5
5
V nom
± 5% for specified performance.
20
80
20
80
21
80
mA max
mA max
100
400
100
400
105
400
mW max
mW max
Logic inputs = 0 V or VDD.
VDD = 5 V.
Typically 82 mW.
Typically 75 mW.
NOTES
1
Temperature ranges for the A and B Versions: –40∞C to +85∞C. Temperature range for the Y Version: –55∞C to +105∞C.
2
The AD7891-1’s dynamic performance (THD and SNR) and the AD7891-2’s THD are measured with an input frequency of 10 kHz. The AD7891-2’s SNR is
evaluated with an input frequency of 100 kHz.
3
This throughput rate can only be achieved when the part is operated in the parallel interface mode. Maximum achievable throughput rate in the serial interface mode
is 357 kSPS.
4
See the Terminology section.
5
Sample tested during initial release and after any redesign or process change that may affect this parameter.
6
REF IN must be buffered before being applied to V INXB.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS*
(TA = 25∞C, unless otherwise noted)
VDD to AGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
VDD to DGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
Analog Input Voltage to AGND
AD7891-1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 17 V
AD7891-2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . –5 V, +10 V
Reference Input Voltage to AGND . . . . –0.3 V to VDD + 0.3 V
Digital Input Voltage to DGND . . . . . . –0.3 V to VDD + 0.3 V
Digital Output Voltage to DGND . . . . . –0.3 V to VDD + 0.3 V
Operating Temperature Range
Commercial (A, B Versions) . . . . . . . . . . . –40∞C to +85∞C
Automotive (Y Version) . . . . . . . . . . . . . . –55∞C to +105∞C
Storage Temperature Range . . . . . . . . . . . . –65∞C to +150∞C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . 150∞C
MQFP Package, Power Dissipation . . . . . . . . . . . . . . 450 mW
qJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . . 95∞C/W
Lead Temperature, Soldering
Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . . . 215∞C
Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . . 220∞C
PLCC Package, Power Dissipation . . . . . . . . . . . . . . 500 mW
qJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . . 55∞C/W
Lead Temperature, Soldering
Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . . . 215∞C
Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . . 220∞C
*Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD7891 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
REV. D
–3–
AD7891
TIMING CHARACTERISTICS1, 2
Parameter
A, B, Y Versions
Unit
Test Conditions/Comments
tCONV
1.6
ms max
Conversion Time
0
35
25
5
0
35
55
35
25
5
30
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns max
CS to RD/WR Setup Time
Write Pulse Width
Data Valid to Write Setup Time
Data Valid to Write Hold Time
CS to RD/WR Hold Time
CONVST Pulse Width
EOC Pulse Width
Read Pulse Width
Data Access Time after Falling Edge of RD
Bus Relinquish Time after Rising Edge of RD
30
20
25
25
5
15
20
0
30
0
30
20
15
10
30
ns min
ns max
ns min
ns min
ns min
ns max
ns min
ns min
ns max
ns min
ns max
ns min
ns min
ns min
ns min
RFS Low to SCLK Falling Edge Setup Time
RFS Low to Data Valid Delay
SCLK High Pulse Width
SCLK Low Pulse Width
SCLK Rising Edge to Data Valid Hold Time
SCLK Rising Edge to Data Valid Delay
RFS to SCLK Falling Edge Hold Time
Bus Relinquish Time after Rising Edge of RFS
Parallel Interface
t1
t2
t3
t4
t5
t6
t7
t8
t9 3
t104
Serial Interface
t11
t123
t13
t14
t153
t163
t17
t184
t18A4
t19
t20
t21
t22
Bus Relinquish Time after Rising Edge of SCLK
TFS Low to SCLK Falling Edge Setup Time
Data Valid to SCLK Falling Edge Setup Time
Data Valid to SCLK Falling Edge Hold Time
TFS Low to SCLK Falling Edge Hold Time
NOTES
1
Sample tested during initial release and after any redesign or process change that may affect this parameter. All input signals are measured with tr = tf = 1 ns (10% to
90% of 5 V) and timed from a voltage level of 1.6 V.
2
See Figures 2, 3, and 4.
3
Measured with the load circuit of Figure 1 and defined as the time required for an output to cross 0.8 V or 2.4 V.
4
These times are derived from the measured time taken by the data outputs to change 0.5 V when loaded with the circuit of Figure 1. The measured number is then
extrapolated back to remove the effects of charging or discharging the 50 pF capacitor. This means that the times quoted in the timing characteristics are the true bus
relinquish times of the part and as such are independent of external bus loading capacitances.
Specifications subject to change without notice.
1.6mA
TO
OUTPUT
PIN
1.6V
50pF
200␮A
Figure 1. Load Circuit for Access Time and Bus Relinquish Time
–4–
REV. D
AD7891
ORDERING GUIDE
Model
Relative
Sample Rate Accuracy
Input Range
AD7891ACHIPS-1
AD7891ACHIPS-2
AD7891AS-1
AD7891ASZ-12
AD7891AP-1
AD7891AP-1REEL
AD7891BS-1
AD7891BP-1
AD7891BP-1REEL
AD7891YS-1
AD7891YS-1REEL
AD7891YP-1
AD7891YP-1REEL
AD7891AS-2
AD7891ASZ-22
AD7891AP-2
AD7891AP-2REEL
AD7891BS-2
AD7891BP-2
AD7891BP-2REEL
AD7891YS-2
AD7891YS-2REEL
EVAL-AD7891-1CB
EVAL-AD7891-2CB
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
± 5 V or ± 10 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
0 V to +5 V, 0 V to +2.5 V, ± 2.5 V
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 0.75 LSB
± 0.75 LSB
± 0.75 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 1 LSB
± 0.75 LSB
± 0.75 LSB
± 0.75 LSB
± 1 LSB
± 1 LSB
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
454 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
500 kSPS
Temperature
Range
Package Option1
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–55∞C to +105∞C
–55∞C to +105∞C
–55∞C to +105∞C
–55∞C to +105∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–40∞C to +85∞C
–55∞C to +105∞C
–55∞C to +105∞C
DIE
DIE
S-44
S-44
P-44A
P-44A
S-44
P-44A
P-44A
S-44
S-44
P-44A
P-44A
S-44
S-44
P-44A
P-44A
S-44
P-44A
P-44A
S-44
S-44
Evaluation Board
Evaluation Board
NOTES
1
S = Plastic Quad Flatpack (MQFP); P = Plastic Leaded Chip Carrier (PLCC).
2
Z = Pb-free part.
PIN CONFIGURATIONS
PLCC
REV. D
30
35
AGND
5
34
MODE
DB11/TEST
6
DB10/TEST
8
26
DB9/TFS
9
25
DB8/RFS 10
DB7/DATA IN 11
24
EOC
NC
CONVST
CS
33
PIN 1
IDENTIFIER
32
AD7891
TOP VIEW
(Not to Scale)
7
NC = NO CONNECT
–5–
VIN6A
VIN6B
VIN7A
VIN7B
29
VIN8A
28
VIN8B
AGND
27
23
12 13 14 15 16 17 18 19 20 21 22
WR
RD
DB0/FORMAT
DB1/SWSTBY
DB3/A0
DB2/SWCON
DB4/A1
VIN5B
31
4
29
DGND
VIN5A
REF OUT/REF IN
VDD
3
VIN7B
30
DB5/A2/DATA OUT
VIN4B
VIN7A
36
31
DB6/SCLK
VDD
VIN4A
37
18 19 20 21 22 23 24 25 26 27 28
NC = NO CONNECT
VIN3B
2
32
DB9/TFS 15
DB8/RFS 16
DB7/DATA IN 17
VIN3A
1
NC
WR
RD
TOP VIEW
(Not to Scale)
VIN2B
REF GND
VIN6B
VIN8A
VIN8B
33 AGND
AD7891
VIN2A
VIN6A
38
DB0/FORMAT
AGND 11
MODE 12
DB11/TEST 13
DB10/TEST 14
39
DB2/SWCON
DB1/SWSTBY
NC 8
REF OUT/REF IN 9
VDD 10
DB4/A1
DB3/A0
PIN 1
IDENTIFIER
REF GND 7
44 43 42 41 40 39 38 37 36 35 34
DGND
DB5/A2/DATA OUT
44 43 42 41 40
1
STANDBY
VIN1A
VIN1B
VIN3B
VIN4A
2
3
DB6/SCLK
VDD
VIN2B
VIN3A
4
5
VIN5B
VIN1B
VIN2A
6
VIN4B
VIN5A
STANDBY
VIN1A
MQFP
EOC
NC
CONVST
CS
AD7891
PIN FUNCTION DESCRIPTIONS
PLCC MQFP
Pin No. Pin No. Mnemonic
Description
1–5
34–44
28–43
VINXA, VINXB
Analog Input Channels. The AD7891 contains eight pairs of analog input channels. Each
channel contains two input pins to allow a number of different input ranges to be used
with the AD7891. There are two possible input voltage ranges on the AD7891-1. The
± 5 V input range is selected by connecting the input voltage to both VINXA and VINXB,
while the ± 10 V input range is selected by applying the input voltage to VINXA and connecting VINXB to AGND. The AD7891-2 has three possible input ranges. The 0 V to
2.5 V input range is selected by connecting the analog input voltage to both VINXA and VINXB; the
0 V to 5 V input range is selected by applying the input voltage to VINXA and connecting
VINXB to AGND while the ± 2.5 V input range is selected by connecting the analog input
voltage to VINXA and connecting VINXB to REF IN (provided this REF IN voltage comes
from a low impedance source). The channel to be converted is selected by the A2, A1,
and A0 bits of the control register. In the parallel interface mode, these bits are available as
three data input lines (DB3 to DB5) in a parallel write operation. While in the serial interface mode, these three bits are accessed via the DATA IN line in a serial write operation.
The multiplexer has guaranteed break-before-make operation.
10, 19
4, 13
VDD
Positive Supply Voltage, 5 V ± 5%.
11, 33
20
6
5, 27
14
44
AGND
DGND
STANDBY
9
3
REF OUT/REF IN
7
1
REF GND
30
24
CONVST
32
26
EOC
12
6
MODE
Analog Ground. Ground reference for track/hold, comparator, and DAC.
Digital Ground. Ground reference for digital circuitry.
Standby Mode Input. TTL compatible input used to put the device into the power
save or standby mode. The STANDBY input is high for normal operation and low for
standby operation.
Voltage Reference Output/Input. The part can either be used with its own internal reference or with an external reference source. The on-chip 2.5 V reference voltage is provided at this pin. When using this internal reference as the reference source for the
part, REF OUT should be decoupled to REF GND with a 0.1 mF disc ceramic capacitor. The output impedance of the reference source is typically 2 kW. When using an
external reference source as the reference voltage for the part, the reference source
should be connected to this pin. This overdrives the internal reference and provides the
reference source for the part. The reference pin is buffered on-chip but must be able to
sink or source current through this 2 kW resistor to the output of the on-chip reference.
The nominal reference voltage for correct operation of the AD7891 is 2.5 V.
Reference Ground. Ground reference for the part’s on-chip reference buffer. The REF
OUT pin of the part should be decoupled with a 0.1 mF capacitor to this REF GND
pin. If the AD7891 is used with an external reference, the external reference should also
be decoupled to this pin. The REF GND pin should be connected to the AGND pin
or the system’s AGND plane.
Convert Start. Edge-triggered logic input. A low-to-high transition on this input puts
the track/hold into hold and initiates conversion. When changing channels on the part,
sufficient time should be given for multiplexer settling and track/hold acquisition between
the channel change and the rising edge of CONVST.
End-of-Conversion. Active low logic output indicating converter status. The end of conversion is signified by a low-going pulse on this line. The duration of this EOC pulse is
nominally 80 ns.
Interface Mode. Control input that determines the interface mode for the part. With this
pin at a logic low, the AD7891 is in its serial interface mode; with this pin at a logic high,
the device is in its parallel interface mode.
–6–
REV. D
AD7891
PARALLEL INTERFACE MODE FUNCTIONS
PLCC Pin No.
MQFP Pin No. Mnemonic
Description
8, 31
2, 25
NC
No Connect. The two NC pins on the device can be left unconnected. If they
are to be connected to a voltage, it should be to ground potential. To ensure
correct operation of the AD7891, neither of the NC pins should be connected
to a logic high potential.
29
23
CS
28
22
RD
27
21
WR
Chip Select Input. Active low logic input that is used in conjunction with to
enable the data outputs and with WR to allow input data to be written to the part.
Read Input. Active low logic input that is used in conjunction with CS low to
enable the data outputs.
Write Input. Active low logic input used in conjunction with CS to latch the multiplexer address and software control information. The rising edge of this input
also initiates an internal pulse. When using the software start facility, this pulse
delays the point at which the track/hold goes into hold and conversion is initiated.
This allows the multiplexer to settle and the acquisition time of the track/hold to
elapse when a channel address is changed. If the SWCON bit of the control register is set to 1, when this pulse times out, the track/hold then goes into hold and
conversion is initiated. If the SWCON bit of the control register is set to 0, the
track/hold and conversion sequence are unaffected by WR operation.
Data I/O Lines
There are 12 data input/output lines on the AD7891. When the part is configured for parallel mode (MODE = 1), the output data
from the part is provided at these 12 pins during a read operation. For a write operation in parallel mode, these lines provide access
to the part’s control register.
Parallel Read Operation
During a parallel read operation, the 12 lines become the 12 data bits containing the conversion result from the AD7891. These
data bits are labelled Data Bit 0 (LSB) to Data Bit 11 (MSB). They are three-state, TTL compatible outputs. Output data coding
is twos complement when the data FORMAT bit of the control register is 1, and straight binary when the data FORMAT bit of
the control register is 0.
PLCC Pin No.
MQFP Pin No. Mnemonic
13 to 18,
21 to 26
7 to 12,
15 to 20
Description
DB0 to DB11 Data Bit 0 (LSB) to Data Bit 11 (MSB). Three-state TTL compatible
outputs that are controlled by the CS and RD inputs.
Parallel Write Operation
During a parallel write operation, the following functions can be written to the control register via the 12 data input/output pins.
PLCC Pin No.
MQFP Pin No. Mnemonic
Description
23
17
A0
Address Input. The status of this input during a parallel write operation is
latched to the A0 bit of the control register (see Control Register section).
22
16
A1
Address Input. The status of this input during a parallel write operation is
latched to the A1 bit of the control register (see Control Register section).
21
15
A2
Address Input. The status of this input during a parallel write operation is
latched to the A2 bit of the control register (see Control Register section).
24
18
SWCON
Software Conversion Start. The status of this input during a parallel write
operation is latched to the SWCONV bit of the control register (see Control
Register section).
25
19
SWSTBY
Software Standby Control. The status of this input during a parallel write
operation is latched to the SWSTBY bit of the control register (see Control
Register section).
26
20
FORMAT
Data Format Selection. The status of this input during a parallel write operation is
latched to the FORMAT bit of the control register (see Control Register section).
REV. D
–7–
AD7891
SERIAL INTERFACE MODE FUNCTIONS
When the part is configured for serial mode (MODE = 0), five of the 12 data input/output lines provide serial interface functions.
These functions are outlined below.
PLCC Pin No.
MQFP Pin No. Mnemonic
Description
18
12
SCLK
Serial Clock Input. This is an externally applied serial clock that is used to
load serial data to the control register and to access data from the
output register.
15
9
TFS
Transmit Frame Synchronization Pulse. Active low logic input with serial
data expected after the falling edge of this signal.
16
10
RFS
Receive Frame Synchronization Pulse. This is an active low logic input
with RFS provided externally as a strobe or framing pulse to access serial data
from the output register. For applications that require that data be transmitted
and received at the same time, RFS and TFS should be connected together.
21
15
DATA OUT
Serial Data Output. Sixteen bits of serial data are provided with the
data FORMAT bit and the three address bits of the control register
preceding the 12 bits of conversion data. Serial data is valid on the falling
edge of SCLK for 16 edges after RFS goes low. Output conversion data
coding is twos complement when the FORMAT bit of the control register is
1 and straight binary when the FORMAT bit of the control register is 0.
17
11
DATA IN
Serial Data Input. Serial data to be loaded to the control register is provided
at this input. The first six bits of serial data are loaded to the control
register on the first six falling edges of SCLK after TFS goes low. Serial
data on subsequent SCLK edges is ignored while TFS remains low.
13, 14
7, 8
TEST
Test Pin. When the device is configured for serial mode of operation,
two of the pins which had been data inputs become test inputs. To ensure
correct operation of the device, both TEST inputs should be tied to a
logic low potential.
CONTROL REGISTER
The control register for the AD7891 contains six bits of information as described below. These six bits can be written to the control
register either in a parallel mode write operation or via a serial mode write operation. The default (power-on) condition of all bits in
the control register is 0. Six serial clock pulses must be provided to the part in order to write data to the control register. If TFS
returns high before six serial clock cycles, no data transfer takes place to the control register and the write cycle has to be restarted to
write data to the control register. However, if the SWCONV bit of the register was previously set to a Logic 1 and TFS is brought
high before six serial clock cycles, another conversion is initiated.
LSB (DB0)
A2
A1
A0
SWCONV
SWSTBY
FORMAT
A2
Address Input. This input is the most significant address input for multiplexer channel selection.
A1
Address Input. This is the second most significant address input for multiplexer channel selection.
A0
Address Input. Least significant address input for multiplexer channel selection. When the address is written to
the control register, an internal pulse is initiated to allow for the multiplexer settling time and track/hold acquisition time before the track/hold goes into hold and conversion is initiated. When the internal pulse times out, the
track/hold goes into hold and conversion is initiated. The selected channel is given by the formula
A2 ¥ 4 + A1 ¥ 2 + A0 + 1
SWCONV
Conversion Start. Writing a 1 to this bit initiates a conversion in a similar manner to the CONVST input. Continuous conversion starts do not take place when there is a 1 in this location. The internal pulse and the conversion process are initiated when a 1 is written to this bit. With a 1 in this bit, the hardware conversion start, i.e.,
the CONVST input, is disabled. Writing a 0 to this bit enables the hardware CONVST input.
SWSTBY
Standby Mode Input. Writing a 1 to this bit places the device in its standby or power-down mode. Writing a 0 to
this bit places the device in its normal operating mode.
FORMAT
Data Format. Writing a 0 to this bit sets the conversion data output format to straight (natural) binary. This
data format is generally used for unipolar input ranges. Writing a 1 to this bit sets the conversion data output
format to twos complement. This output data format is generally used for bipolar input ranges.
–8–
REV. D
AD7891
TERMINOLOGY
Signal-to-(Noise + Distortion) Ratio
Channel-to-Channel Isolation
Channel-to-channel isolation is a measure of the level of
crosstalk between channels. It is measured by applying a fullscale 20 kHz (AD7891-1) or 100 kHz (AD7891-2) sine wave
signal to one input channel and determining how much that
signal is attenuated in each of the other channels. The figure
given is the worst case across all eight channels.
This is the measured ratio of signal to (noise + distortion) at the
output of the ADC. The signal is the rms amplitude of the
fundamental. Noise is the rms sum of all nonfundamental
signals up to half the sampling frequency (fS/2), excluding dc.
The ratio is dependent upon the number of quantization levels
in the digitization process; the more levels, the smaller the quantization noise. The theoretical signal-to-(noise +distortion) ratio
for an ideal N-bit converter with a sine wave input is given by
Relative Accuracy
Relative accuracy or endpoint nonlinearity is the maximum
deviation from a straight line passing through the endpoints of
the ADC transfer function.
Signal-to-(Noise + Distortion) = (6.02N + 1.76) dB
Therefore, for a 12-bit converter, this is 74 dB.
Differential Nonlinearity
Total Harmonic Distortion (THD)
This is the difference between the measured and the ideal 1 LSB
change between any two adjacent codes in the ADC.
THD is the ratio of the rms sum of harmonics to the
fundamental. For the AD7891, it is defined as
THD (dB) = 20 log
V2 + V3 + V4 + V5 + V6
V1
2
2
2
2
Positive Full-Scale Error (AD7891-1, ⴞ10 V and ⴞ5 V;
AD7891-2, ⴞ2.5 V)
This is the deviation of the last code transition (01. . .110 to
01. . .111) from the ideal 4 ¥ REF IN – 3/2 LSB (AD7891-1
± 10 V range), 2 ¥ REF IN – 3/2 LSB (AD7891-1 ± 5 V range),
or REF IN – 3/2 LSB (AD7891-2, ± 2.5 V range), after the
bipolar zero error has been adjusted out.
2
where V1 is the rms amplitude of the fundamental and V2, V3,
V4, V5 and V6 are the rms amplitudes of the second through the
sixth harmonics.
Positive Full-Scale Error (AD7891-2, 0 V to 5 V and 0 V to 2.5 V)
This is the deviation of the last code transition (11. . .110 to
11. . .111) from the ideal 2 ¥ REF IN – 3/2 LSB (0 V to 5 V
range), or REF IN – 3/2 LSB (0 V to 2.5 V range), after the
unipolar offset error has been adjusted out.
Peak Harmonic or Spurious Noise
Peak harmonic or spurious noise is defined as the ratio of the rms
value of the next largest component in the ADC output spectrum
(up to fS/2 and excluding dc) to the rms value of the fundamental.
Normally, the value of this specification is determined by the largest harmonic in the spectrum, but for parts where the harmonics
are buried in the noise floor, it is a noise peak.
Bipolar Zero Error (AD7891-1, ⴞ10 V and ⴞ5 V; AD7891-2, ⴞ2.5 V)
This is the deviation of the midscale transition (all 0s to all 1s)
from the ideal AGND – 1/2 LSB.
Intermodulation Distortion
Unipolar Offset Error (AD7891-2, 0 V to 5 V and 0 V to 2.5 V)
With inputs consisting of sine waves at two frequencies, fa and
fb, any active device with nonlinearities creates distortion
products at sum and difference frequencies of mfa ± nfb, where
m, n = 0, 1, 2, 3, and so on. Intermodulation terms are those for
which neither m nor n are equal to zero. For example, the
second-order terms include (fa + fb) and (fa – fb), while the
third-order terms include (2fa + fb), (2fa – fb), (fa + 2fb), and
(fa – 2fb).
This is the deviation of the first code transition (00. . .000 to
00. . .001) from the ideal AGND + 1/2 LSB.
Negative Full-Scale Error (AD7891-1, ⴞ10 V and ⴞ5 V;
AD7891-2, ⴞ2.5 V)
This is the deviation of the first code transition (10. . .000 to
10. . .001) from the ideal –4 ¥ REF IN + 1/2 LSB (AD7891-1
±10 V range), –2 ¥ REF IN + 1/2 LSB (AD7891-1 ± 5 V range),
or –REF IN + 1/2 LSB (AD7891-2, ± 2.5 V range), after bipolar
zero error has been adjusted out.
The AD7891 is tested using the CCIF standard where two
input frequencies near the top end of the input bandwidth are
used. In this case, the second- and third-order terms are of
different significance. The second-order terms are usually distanced in frequency from the original sine waves while the thirdorder terms are usually at a frequency close to the input
frequencies. As a result, the second- and-third order terms are
specified separately. The calculation of the intermodulation
distortion is as per the THD specification where it is the ratio of
the rms sum of the individual distortion products to the rms
amplitude of the fundamental expressed in dBs.
REV. D
Track/Hold Acquisition Time
Track/hold acquisition time is the time required for the output of
the track/hold amplifier to reach its final value, within ± 1/2 LSB,
after the end of conversion (the point at which the track/hold
returns to track mode). It also applies to situations where a
change in the selected input channel takes place or where there
is a step input change on the input voltage applied to the selected
VIN input of the AD7891. It means the user must wait for the
duration of the track/hold acquisition time after the end of
conversion or after a channel change/step input change to VIN
before starting another conversion, to ensure the part operates
to specification.
–9–
AD7891
CONVERTER DETAILS
INTERFACE INFORMATION
The AD7891 is an 8-channel, high speed, 12-bit data acquisition system. It provides the user with signal scaling, multiplexer,
track/hold, reference, ADC, and high speed parallel and serial
interface logic functions on a single chip. The signal conditioning on the AD7891-1 allows the part to accept analog input
ranges of ± 5 V or ± 10 V when operating from a single supply.
The input circuitry on the AD7891-2 allows the part to handle
input signal ranges of 0 V to +2.5 V, 0 V to +5 V, and ±2.5 V
again while operating from a single 5 V supply. The part requires
a 2.5 V reference that can be provided from the part’s own internal
reference or from an external reference source.
The AD7891 provides two interface options, a 12-bit parallel
interface and a high speed serial interface. The required interface mode is selected via the MODE pin. The two interface
modes are discussed in the following sections.
Conversion is initiated on the AD7891 either by pulsing the
CONVST input or by writing a Logic 1 to the SWCONV bit of
the control register. When using the hardware CONVST input,
the on-chip track/hold goes from track to hold mode and the
conversion sequence is started on the rising edge of the CONVST
signal. When a software conversion start is initiated, an internal
pulse is generated, delaying the track/hold acquisition point and
the conversion start sequence until the pulse is timed out. This
internal pulse is initiated (goes from low to high) whenever a
write to the AD7891 control register takes place with a 1 in the
SWCONV bit. It then starts to discharge and the track/hold
cannot go into hold and conversion cannot be initiated until the
pulse signal goes low. The internal pulse duration is equal to the
track/hold acquisition time. This allows the user to obtain a
valid result after changing channels and initiating a conversion
in the same write operation.
The conversion clock for the part is internally generated and
conversion time for the AD7891 is 1.6 ms from the rising edge of
the hardware CONVST signal. The track/hold acquisition time
for the AD7891-1 is 600 ns, while the track/hold acquisition
time for the AD7891-2 is 400 ns. To obtain optimum performance from the part, the data read operation should not occur
during the conversion or during the 100 ns prior to the next
conversion. This allows the AD7891-1 to operate at throughput
rates up to 454.5 kSPS and the AD7891-2 to operate at throughput rates up to 500 kSPS in the parallel mode and achieve data
sheet specifications. In the serial mode, the maximum achievable
throughput rate for both the AD7891-1 and the AD7891-2 is
357 kSPS (assuming a 20 MHz serial clock).
Parallel Interface Mode
The parallel interface mode is selected by tying the MODE
input to a logic high. Figure 2 shows a timing diagram illustrating
the operational sequence of the AD7891 in parallel mode for a
hardware conversion start. The multiplexer address is written to
the AD7891 on the rising edge of the WR input. The on-chip
track/hold goes into hold mode on the rising edge of CONVST;
conversion is also initiated at this point. When the conversion is
complete, the end of conversion line (EOC) pulses low to indicate that new data is available in the AD7891’s output register.
This EOC line can be used to drive an edge-triggered interrupt
of a microprocessor. CS and RD going low accesses the 12-bit
conversion result. In systems where the part is interfaced to a
gate array or ASIC, this EOC pulse can be applied to the CS
and RD inputs to latch data out of the AD7891 and into the
gate array or ASIC. This means the gate array or ASIC does not
need any conversion status recognition logic, and it also eliminates the logic required in the gate array or ASIC to generate
the read signal for the AD7891.
CONVST (I)
t6
t7
EOC (O)
t CONV
CS (O)
t1
t5
t1
t5
t2
t8
WR (I)
RD (I)
t3
t4
DB0 TO DB11
(I/O)
All unused analog inputs should be tied to a voltage within the
nominal analog input range to avoid noise pickup. For minimum power consumption, the unused analog inputs should be
tied to AGND.
VALID DATA
INPUT
t9
t 10
VALID DATA
OUTPUT
NOTE
I = INPUT
O = OUTPUT
Figure 2. Parallel Mode Timing Diagram
–10–
REV. D
AD7891
remain low for the duration of the data transfer operation. Sixteen bits of data are transmitted in serial mode with the data
FORMAT bit first, followed by the three address bits in the
control register, followed by the 12-bit conversion result starting
with the MSB. Serial data is clocked out of the device on the
rising edge of SCLK and is valid on the falling edge of SCLK.
At the end of the read operation, the DATA OUT line is threestated by a rising edge on either the SCLK or RFS inputs, whichever occurs first.
Serial Interface Mode
The serial interface mode is selected by tying the MODE input
to a logic low. In this case, five of the data/control inputs of the
parallel mode assume serial interface functions.
The serial interface on the AD7891 is a 5-wire interface with
read and write capabilities, with data being read from the output
register via the DATA OUT line and data being written to the
control register via the DATA IN line. The part operates in a
slave or external clocking mode and requires an externally applied
serial clock to the SCLK input to access data from the data
register or write data to the control register. There are separate
framing signals for the read (RFS) and write (TFS) operations.
The serial interface on the AD7891 is designed to allow the part
to be interfaced to systems that provide a serial clock that is
synchronized to the serial data, such as the 80C51, 87C51,
68HC11, and 68HC05, and most digital signal processors.
Write Operation
Figure 4 shows a write operation to the control register of the
AD7891. The TFS input goes low to indicate to the part that a
serial write is about to occur. The AD7891 control register
requires only six bits of data. These are loaded on the first six
clock cycles of the serial clock with data on all subsequent clock
cycles being ignored. Serial data to be written to the AD7891
must be valid on the falling edge of SCLK.
When using the AD7891 in serial mode, the data lines DB11 to
DB10 should be tied to logic low, and the CS, WR, and RD
inputs should be tied to logic high. Pins DB4 to DB0 can be
tied to either logic high or logic low but must not be left floating
because this condition could cause the AD7891 to draw
large amounts of current.
Simplifying the Serial Interface
To minimize the number of interconnect lines to the AD7891
in serial mode, the user can connect the RFS and TFS lines
of the AD7891 together and read and write from the part simultaneously. In this case, a new control register data line selecting
the input channel and providing a conversion start command
should be provided on the DATA IN line, while the part provides the result from the conversion just completed on the
DATA OUT line.
Read Operation
Figure 3 shows the timing diagram for reading from the AD7891
in serial mode. RFS goes low to access data from the AD7891.
The serial clock input does not have to be continuous. The serial
data can be accessed in a number of bytes. However, RFS must
RFS (I)
t 11
t 13
t 17
SCLK (I)
DATA OUT (O)
t 18
t 18A
t 14
t 12
t 15
FORMAT
A2
A1
A0
t 16
DB11
DB10
DB0
THREE-STATE
NOTE
I = INPUT
O = OUTPUT
Figure 3. Serial Mode Read Operation
TFS (I)
t 19
t 22
SCLK (I)
t 21
t 20
DATA IN (I)
A0
A1
A0
CONV
STBY
FORMAT
DON'T
CARE
NOTE
I = INPUT
Figure 4. Serial Mode Write Operation
REV. D
–11–
DON'T
CARE
AD7891
CIRCUIT DESCRIPTION
Reference
The AD7891 contains a single reference pin labeled REF OUT/
REF IN that either provides access to the part’s own 2.5 V
internal reference or to which an external 2.5 V reference can be
connected to provide the reference source for the part. The part
is specified with a 2.5 V reference voltage. Errors in the reference
source result in gain errors in the transfer function of the AD7891
and add to the specified full-scale errors on the part. They also
result in an offset error injected into the attenuator stage.
The AD7891 contains an on-chip 2.5 V reference. To use this
reference as a reference source for the AD7891, simply connect
a 0.1 mF disc ceramic capacitor from the REF OUT/REF IN pin
to REFGND. REFGND should be connected to AGND or the
analog ground plane. The voltage that appears at the REF OUT/
REF IN pin is internally buffered before being applied to the
ADC. If this reference is required for use external to the AD7891,
it should be buffered since the part has a FET switch in series
with the reference, resulting in a source impedance for this
output of 2 kW nominal. The tolerance of the internal reference
is ± 10 mV at 25∞C with a typical temperature coefficient of
25 ppm/∞C and a maximum error over temperature of ± 20 mV.
If the application requires a reference with a tighter tolerance
or if the AD7891 needs to be used with a system reference, an
external reference can be connected to the REF OUT/REF IN
pin. The external reference overdrives the internal reference
and thus provides the reference source for the ADC. The reference input is buffered before being applied to the ADC and
the maximum input current is ± 100 mA. Suitable reference for
the AD7891 include the AD580, the AD680, the AD780, and
the REF43 precision 2.5 V references.
The input resistance for the ± 5 V range is typically 20 kW. For
the ± 10 V input range, the input resistance is typically 34.3 kW.
The resistor input stage is followed by the multiplexer, which is
followed by the high input impedance stage of the track/hold
amplifier.
The designed code transitions take place midway between successive integer LSB values (i.e., 1/2 LSB, 3/2 LSBs, 5/2 LSBs).
LSB size is given by the formula 1 LSB = FS/4096. Therefore, for
the ± 5 V range, 1 LSB = 10 V/4096 = 2.44 mV. For the ± 10 V
range, 1 LSB = 20 V/4096 = 4.88 mV. Output coding is determined by the FORMAT bit of the control register. The ideal
input/output code transitions are shown in Table I.
AD7891-2
Figure 6 shows the analog input section of the AD7891-2. Each
input can be configured for input ranges of 0 V to +5 V, 0 V to +2.5 V,
or ± 2.5 V. For the 0 V to 5 V input range, the VINXB input is
tied to AGND and the input voltage is applied to the VINXA input.
For the 0 V to 2.5 V input range, the VINXA and VINXB inputs
are tied together and the input voltage is applied to both. For
the ± 2.5 V input range, the VINXB input is tied to 2.5 V and
the input voltage is applied to the VINXA input. The 2.5 V source
must have a low output impedance. If the internal reference on
the AD7891 is used, it must be buffered before being applied to
VINXB. The VINXA and VINXB inputs are symmetrical and fully
interchangeable. Therefore, for ease of PCB layout on the 0 V to +5 V
or ±2.5 V range, the input voltage may be applied to the VINXB
input, while the VINXA input is tied to AGND or 2.5 V.
REF OUT/REF IN
Analog Input Section
VINXA
The AD7891 is offered as two part types: the AD7891-1 where
each input can be configured to have a ± 10 V or a ± 5 V input
range, and the AD7891-2 where each input can be configured
to have a 0 V to +2.5 V, 0 V to +5 V, and ± 2.5 V input range.
VINXB
REF OUT/REF IN
30k⍀
7.5k⍀
VINXA
2k⍀
VINXB
30k⍀
15k⍀
TO
MULTIPLEXER
AD7891-1
2.5V
REFERENCE
1.8k⍀
TO
MULTIPLEXER
2k⍀
2.5V
REFERENCE
AD7891-2
AD7891-1
Figure 5 shows the analog input section of the AD7891-1. Each
input can be configured for ± 5 V or ± 10 V operation. For 5 V
operation, the VINXA and VINXB inputs are tied together and the
input voltage is applied to both. For ± 10 V operation, the VINXB
input is tied to AGND and the input voltage is applied to the
VINXA input. The VINXA and VINXB inputs are symmetrical and
fully interchangeable. Therefore, for ease of PCB layout on the
± 10 V range, the input voltage may be applied to the VINXB
input while the VINXA input is tied to AGND.
TO ADC
REFERENCE CIRCUITRY
TO ADC
REFERENCE
CIRCUITRY
1.8k⍀
AGND
Figure 6. AD7891-2 Analog Input Structure
The input resistance for both the 0 V to +5 V and ± 2.5 V ranges
is typically 3.6 kW. When an input is configured for 0 V to 2.5 V
operation, the input is fed into the high impedance stage of the
track/hold amplifier via the multiplexer and the two 1.8 kW
resistors in parallel.
The designed code transitions occur midway between successive
integer LSB values (i.e., 1/2 LSB, 3/2 LSBs, 5/2 LSBs). LSB size
is given by the formula 1 LSB = FS/4096. Therefore, for the 0 V
to 5 V range, 1 LSB = 5 V/4096 = 1.22 mV, for the 0 V to 2.5 V
range, 1 LSB = 2.5 V/4096 = 0.61 mV, and for the ± 2.5 V range,
1 LSB = 5 V/4096 = 1.22 mV. Output coding is determined by
the FORMAT bit in the control register. The ideal input/output
code transitions for the ± 2.5 V range are shown in Table I. The
ideal input/output code transitions for the 0 V to 5 V range and
the 0 V to 2.5 V range are shown in Table II.
AGND
Figure 5. AD7891-1 Analog Input Structure
–12–
REV. D
AD7891
Table I. Ideal Code Transition Table for the AD7891-1, ⴞ10 V and ⴞ5 V Ranges and the AD7891-2, ⴞ2.5 V Range
Input Voltage
Digital Output Code Transition1
Twos Complement
Straight Binary
+FSR /2 – 3/2 LSB
+FSR/2 – 5/2 LSB
+FSR/2 – 7/2 LSB
(9.99268 V, 4.99634 V or 2.49817 V)4
(9.98779 V, 4.99390 V or 2.49695 V)
(9.99145 V, 4.99146 V or 2.49573 V)
011...110 to 011...111
011...101 to 011...110
011...100 to 011...101
111...110 to 111...111
111...101 to 111...110
111...100 to 111...101
AGND + 3/2 LSB
AGND + 1/2 LSB
AGND – 1/2 LSB
AGND – 3/2 LSB
(7.3242 mV, 3.6621 mV or 1.8310 mV)
(2.4414 mV, 1.2207 mV or 0.6103 mV)
(–2.4414 mV, –1.2207 mV or –0.6103 mV)
(–7.3242 mV, –3.6621 mV or –1.8310 mV)
000...001 to 000...010
000...000 to 000...001
111...111 to 000...000
111...110 to 111...111
100...001 to 100...010
100...000 to 100...001
011...111 to 100...000
011...110 to 011...111
–FSR/2 + 5/2 LSB
–FSR/2 + 3/2 LSB
–FSR/2 + 1/2 LSB
(–9.98779 V, –4.99390 V or –2.49695 V)
(–9.99268 V, –4.99634 V or –2.49817 V)
(–9.99756 V, –4.99878 V or –2.49939 V)
100...010 to 100...011
100...001 to 100...010
100...000 to 100...001
000...010 to 000...011
000...001 to 000...010
000...000 to 000...001
Analog Input
2
3
NOTES
1
Output code format is determined by the FORMAT bit in the control register.
2
FSR is full-scale range and is +20 V for the ± 10 V range, +10 V for the ± 5 V range, and +5 V for the ± 2.5 V range, with REF IN = +2.5 V.
3
1 LSB = FSR/4096 = +4.88 mV (± 10 V range), +2.44 mV (± 5 V range), and +1.22 mV (± 2.5 V range), with REF IN = +2.5 V.
4
± 10 V range, ± 5 V range, or ± 2.5 V range.
Table II. Ideal Code Transition Table for the AD7891-2, 0 V to 5 V and 0 V to 2.5 V Ranges
Input Voltage
Digital Output Code Transition1
Twos Complement
Straight Binary
+FSR – 3/2 LSB
+FSR – 5/2 LSB
+FSR – 7/2 LSB
(4.99817 V or 2.49908 V)4
(4.99695 V or 2.49847 V)
(4.99573 V or 2.49786 V)
011...110 to 011...111
011...101 to 011...110
011...100 to 011...101
111...110 to 111...111
111...101 to 111...110
111...100 to 111...101
AGND + 5/2 LSB
AGND + 3/2 LSB
AGND + 1/2 LSB
(3.0518 mV or 1.52588 mV)
(1.83105 mV or 0.9155 mV)
(0.6103 mV or 0.3052 mV)
100...010 to 000...011
100...001 to 000...010
100...000 to 000...001
000...010 to 000...011
000...001 to 000...010
000...000 to 000...001
Analog Input
2
3
NOTES
1
Output code format is determined by the FORMAT bit in the control register.
2
FSR is the full-scale range and is 5 V for the 0 to 5 V range and 2.5 V for the 0 to 2.5 V range, with REF IN = 2.5 V.
3
1 LSB = F S/4096 = 1.22 mV (0 to 5 V range) or 610 mV (0 to 2.5 V range), with REF IN = 2.5 V.
4
0 V to 5 V range or 0 V to 2.5 V range.
Transfer Function of the AD7891-1 and AD7891-2
Table III. Transfer Function M and N Values
The transfer function of the AD7891-1 and AD7891-2 can be
expressed as
Range
Input Voltage = ( M ¥ REF IN ¥ D/4096) + ( N ¥ REF IN )
D is the output data from the AD7891 and is in the range 0 to
4095 for straight binary encoding and from –2048 to +2047 for
twos complement encoding. Values for M depend upon the
input voltage range. Values for N depend upon the input voltage
range and the output data format. These values are given in
Table III. REF IN is the reference voltage applied to the AD7891.
REV. D
AD7891-1
± 10 V
± 10 V
±5 V
±5 V
AD7891-2
0 V to +5 V
0 V to +5 V
0 V to +2.5 V
0 V to +2.5 V
± 2.5 V
± 2.5 V
–13–
Output Data Format
M
N
Straight Binary
Twos Complement
Straight Binary
Twos Complement
8
8
4
4
–4
0
–2
0
Straight Binary
Twos Complement
Straight Binary
Twos Complement
Straight Binary
Twos Complement
2
2
1
1
2
2
0
1
0
0.5
–1
0
AD7891
Track/Hold Amplifier
The track/hold amplifier on the AD7891 allows the ADC to
accurately convert an input sine wave of full-scale amplitude
to 12-bit accuracy. The input bandwidth of the track/hold is
greater than the Nyquist rate of the ADC even when the ADC is
operated at its maximum throughput rate of 454 kHz (AD7891-1)
or 500 kHz (AD7891-2). In other words, the track/hold amplifier
can handle input frequencies in excess of 227 kHz (AD7891-1)
or 250 kHz (AD7891-2).
The track/hold amplifier acquires an input signal in 600 ns
(AD7891-1) or 400 ns (AD7891-2). The operation of the track/
hold is essentially transparent to the user. The track/hold amplifier
goes from its tracking mode to its hold mode on the rising edge
of CONVST. The aperture time for the track/hold (i.e., the
delay between the external CONVST signal and the track/hold
actually going into hold) is typically 15 ns. At the end of conversion,
the part returns to its tracking mode. The track/hold starts acquiring
the next signal at this point.
STANDBY Operation
The AD7891 can be put into power save or standby mode by
using the STANDBY pin or the SWSTBY bit of the control
register. Normal operation of the AD7891 takes place when the
STANDBY input is at a Logic 1 and the SWSTBY bit is at a
Logic 0. When the STANDBY pin is brought low or a 1 is written to the SWSTBY bit, the part goes into its standby mode of
operation, reducing its power consumption to typically 75 mW.
The AD7891 is returned to normal operation when the
STANDBY input is at a Logic 1 and the SWSTBY bit is a
Logic 0. The wake-up time of the AD7891 is normally determined
by the amount of time required to charge the 0.1 mF capacitor
between the REF OUT/REF IN pin and REF GND. If the
internal reference is being used as the reference source, this
capacitor is charged via a nominal 2 kW resistor. Assuming 10
time constants to charge the capacitor to 12-bit accuracy, this
implies a wake-up time of 2 ms.
If an external reference is used, this must be taken into account
when working out how long it will take to charge the capacitor.
If the external reference has remained at 2.5 V during the time
the AD7891 was in standby mode, the capacitor will already be
charged when the part is taken out of standby mode. Therefore,
the wake-up time is now the time required for the internal
circuitry of the AD7891 to settle to 12-bit accuracy. This typically takes 5 ms. If the external reference was also put into
standby then the wake-up time of the reference, combined with
the amount of time taken to recharge the reference capacitor
from the external reference, determines how much time must
elapse before conversions can begin again.
MICROPROCESSOR INTERFACING
AD7891 to 8X51 Serial Interface
A serial interface between the AD7891 and the 8X51
microcontroller is shown in Figure 7. TXD of the 8X51 drives
SCLK of the AD7891, while RXD transmits data to and
receives data from the part. The serial clock speed of the 8X51 is
slow compared to the maximum serial clock speed of the
AD7891, so maximum throughput of the AD7891 is not
achieved with this interface.
P3.4
RFS
P3.3
TFS
TXD
SCLK
RXD
DATA IN
8X51*
AD7891*
DATA OUT
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 7. AD7891 to 8X51 Interface
The 8X51 provides the LSB of its SBUF register as the first bit
in the serial data stream. The AD7891 expects the MSB of the
6-bit write first. Therefore, the data in the SBUF register must
be arranged correctly so that this is taken into account. When
data is to be transmitted to the part, P3.3 is taken low. The
8X51 transmits its data in 8-bit bytes with only eight falling
clock edges occurring in the transmit cycle. One 8-bit transfer
is needed to write data to the control register of the AD7891.
After the data has been transferred, the P3.3 line is taken high
to complete the transmission.
When reading data from the AD7891, P3.4 of the 8X51 is taken
low. Two 8-bit serial reads are performed by the 8X51, and
P3.4 is taken high to complete the transfer. Again, the 8X51
expects the LSB first, while the AD7891 transmits MSB first, so
this must be taken into account in the 8X51 software.
No provision has been made in the given interface to determine
when a conversion has ended. If the conversions are initiated by
software, the 8X51 can wait a predetermined amount of time
before reading back valid data. Alternately, the falling edge of
the EOC signal can be used to initiate an interrupt service
routine that reads the conversion result from part to part.
AD7891 to 68HC11 Serial Interface
Figure 8 shows a serial interface between the AD7891 and the
68HC11 microcontroller. SCK of the 68HC11 drives SCLK of
the AD7891, the MOSI output drives DATA IN of the
AD7891, and the MISO input receives data from DATA OUT
of the AD7891. Ports PC6 and PC7 of the 68HC11 drive the
TFS and RFS lines of the AD7891, respectively.
For correct operation of this interface, the 68HC11 should be
configured such that its CPOL bit is a 1 and its CPHA bit is a 0.
When data is to be transferred to the AD7891, PC7 is taken
low. When data is to be received from the AD7891, PC6 is
taken low. The 68HC11 transmits and receives its serial data in
8-bit bytes, MSB first. The AD7891 also transmits and receives
data MSB first. Eight falling clock edges occur in a read or write
cycle from the 68HC11. A single 8-bit write with PC7 low is
required to write to the control register. When data has been
written, PC7 is taken high. When reading from the AD7891,
PC6 is left low after the first eight bits have been read. A second
byte of data is then transmitted serially from the AD7891. When
this transfer is complete, the PC6 line is taken high.
–14–
REV. D
AD7891
As in the 8X51 circuit in Figure 7, the way the 68HC11 is
informed that a conversion is completed is not shown in the
diagram. The EOC line can be used to inform the 68HC11
that a conversion is complete by using it as an interrupt signal.
The interrupt service routine reads in the result of the conversion. If a software conversion start is used, the 68HC11 can
wait for 2.0 ms (AD7891-2) or 2.2 ms (AD7891-1) before reading from the AD7891.
PC7
RFS
PC6
TFS
SCK
SCLK
68HC11*
MOSI
MOSO
AD7891 to DSP5600x Serial Interface
Figure 10 shows a serial interface between the AD7891 and the
DSP5600x series of DSPs. When reading from the AD7891, the
DSP5600x should be set up for 16-bit data transfers, MSB first,
normal mode synchronous operation, internally generated word
frame sync, and gated clock. When writing to the AD7891, 8-bit
or 16-bit data transfers can be used. The frame sync signal from
the DSP5600x must be inverted before being applied to the
RFS and TFS inputs of the AD7891, as shown in Figure 10.
To monitor the conversion time of the AD7891, a scheme such
as those outlined in previous interfaces with EOC can be used.
This can be implemented by connecting the EOC line directly
to the IRQA input of the DSP5600x.
AD7891*
DATA IN
DSP5600x*
DATA OUT
RFS
FST (SC2)
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 8. AD7891 to 68HC11 Interface
TFS
SCLK
STD
DATA IN
SRD
DATA OUT
AD7891 to ADSP-21xx Serial Interface
An interface between the AD7891 and the ADSP-21xx is shown
in Figure 9. In the interface shown, either SPORT0 or SPORT1
can be used to transfer data to the AD7891. When reading
from the part, the SPORT must be set up with a serial word
length of 16 bits. When writing to the AD7891, a serial word
length of 6 bits or more can be used. Other setups for the
serial interface on the ADSP-21xx internal SCLK use alternate
framing mode and active low framing signal. Normally, the
EOC line from the AD7891 would be connected to the IRQ2
line of the ADSP-21xx to interrupt the DSP at the end of a
conversion (not shown in diagram).
ADSP-21xx*
RFS
RFS
TFS
TFS
SCLK
AD7891*
SCK
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 10. AD7891 to DSP5600x Serial Interface
AD7891 to TMS320xxx Serial Interface
The AD7891 can be interfaced to the serial port of TMS320xxx
DSPs, as shown in Figure 11. External timing generation circuitry
is necessary to generate the serial clock and syncs necessary for
the interface.
AD7891*
SCLK
TIMING
GENERATION
CIRCUITRY
TMS320xxx* FSR
RFS
FSX
TFS
DT
DATA IN
CLKR
DR
DATA OUT
CLKX
AD7891*
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 9. AD7891 to ADSP-21xx Serial Interface
DX
DATA IN
DR
DATA OUT
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 11. AD7891 to TMS320xxx Serial Interface
REV. D
–15–
AD7891
PARALLEL INTERFACING
The parallel port on the AD7891 allows the device to be interfaced
to microprocessors or DSP processors as a memory mapped
or I/O mapped device. The CS and RD inputs are common to
all memory peripheral interfacing. Typical interfaces to different
processors are shown in Figures 12 to 15. In all the interfaces
shown, an external timer controls the CONVST input of the
AD7891 and the EOC output interrupts the host DSP.
AD7891 to ADSP-21xx
Figure 12 shows the AD7891 interfaced to the ADSP-21xx
series of DSPs as a memory mapped device. A single wait state
may be necessary to interface the AD7891 to the ADSP-21xx
depending on the clock speed of the DSP. This wait state can
be programmed via the data memory wait state control register
of the ADSP-21xx (please see the ADSP-2100 family Users
Manual for details). The following instruction reads data
from the AD7891.
MR = DM (ADC)
ADSP-21xx*
DMS
CS
WR
WR
RD
RD
D23 TO D8
DATA BUS
where D is the memory location where the data is to be stored,
and ADC is the I/O address of the AD7891.
LDI ¥ ARn, Rx
AD7891*
EOC
IRQ2
IN D, ADC
Figure 14 shows a parallel interface between the AD7891 and
the TMS320C3x family of DSPs. The AD7891 is interfaced to
the expansion bus of the TMS320C3x. A single wait state is
required in this interface. This can be programmed using the
WTCNT bits of the expansion bus control register (see the
TMS320C3x Users Guide for details). Data from the AD7891
can be read using the following instruction:
ADDRESS BUS
ADDR
DECODE
EN
Data is read from the ADC using the following instruction:
AD7891 to TMS320C3x
where ADC is the address of the AD7891.
A13 TO A0
The parallel interface on the AD7891 is fast enough to interface
to the TMS32020 with no extra wait states. If high speed glue
logic, such as 74AS devices, are used to drive the WR and RD
lines when interfacing to the TMS320C25, then again no wait
states are necessary. However, if slower logic is used, data accesses
may be slowed sufficiently when reading from and writing to the
part to require the insertion of one wait state. In such a case,
this wait state can be generated using the single OR gate to
combine the CS and MSC signals to drive the READY line of
the TMS320C25, as shown in Figure 13. Extra wait states are
necessary when using the TMS320C5x at their fastest clock
speeds. Wait states can be programmed via the IOWSR and
CWSR registers (see the TMS320C5x User Guide for details).
DB11 TO DB0
where ARn is an auxiliary register containing the lower 16 bits
of the address of the AD7891 in the TMS320C3x memory
space, and Rx is the register into which the ADC data is loaded.
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 12. AD7891 to ADSP-21xx Parallel Interface
XA15 TO XA0
AD7891 to TMS32020, TMS320C25, and TMS320C5x
TMS320C3x*
Parallel interfaces between the AD7891 and the TMS32020,
TMS320C25, and TMS320C5x family of DSPs are shown in
Figure 13. The memory mapped address chosen for the
AD7891 should be chosen to fall in the I/O memory space of
the DSPs.
ADDRESS BUS
TMS32020/
TMS320C25/ IS
TMS320C5x*
ADDR
EN DECODE
READY
MSC
CS
AD7891*
WR
RD
EOC
INTx
EXPANSION DATA BUS
DB11 TO DB0
*ADDITIONAL PINS OMITTED FOR CLARITY
CS
Figure 14. AD7891 to TMS320C3x Parallel Interface
TMS320C25
ONLY
STRB
R/W
ADDR
DECODE
IOSTRB
XR/W
XD23 TO XD0
A15 TO A0
ADDRESS BUS
AD7891*
WR
RD
EOC
INTx
D23 TO D0
DATA BUS
DB11 TO DB0
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 13. AD7891 to TMS32020/TMS320C25/TMS320C5x
Parallel Interface
–16–
REV. D
AD7891
Digital lines running under the device should be avoided because
these couple noise onto the die. The analog ground plane should
be allowed to run under the AD7891 to avoid noise coupling.
The power supply lines of the AD7891 should use as large a
trace as possible to provide low impedance paths and reduce the
effects of glitches on the power supply line. Fast switching signals like clocks should be shielded with digital ground to avoid
radiating noise to other parts of the board and should never be
run near the analog inputs. Avoid crossover of digital and analog
signals. Traces on opposite sides of the board should run at right
angles to each other. This reduces the effects of feedthrough
through the board. A microstrip technique is by far the best
technique but is not always possible with a double-sided board.
In this technique, the component side of the board is dedicated
to ground plane while signal traces are placed on the solder side.
AD7891 to DSP5600x
Figure 15 shows a parallel interface between the AD7891 and
the DSP5600x series of DSPs. The AD7891 should be mapped
into the top 64 locations of Y data memory. If extra wait states
are needed in this interface, they can be programmed using the
Port A Bus control register (see the DSP5600x Users Manual
for details). Data can be read from the AD7891 using the following instruction:
MOVEO Y: ADC, X0
where ADC is the address in the DSP5600x address space to
which the AD7891 has been mapped.
A15 TO A0
DSP56000/
DSP56002* X/Y
DS
ADDRESS BUS
ADDR
DECODE
CS
WR
WR
RD
RD
EOC
IRQ
D23 TO D0
AD7891*
DATA BUS
DB11 TO DB0
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 15. AD7891 to DSP5600x Parallel Interface
Power Supply Bypassing and Grounding
In any circuit where accuracy is important, careful consideration
of the power supply and ground return layout helps to ensure
the specified performance. The PCB on which the AD7891 is
mounted should be designed such that the analog and digital
sections are separated and confined to certain areas of the board.
This facilitates the use of ground planes that can be separated
easily. A minimum etch technique is generally best for ground
planes because it gives the best shielding. Digital and analog
ground planes should be joined at only one place. If the AD7891
is the only device requiring an AGND to DGND connection,
then the ground planes should be connected at the AGND and
DGND pins of the AD7891. If the AD7891 is in a system where
multiple devices require an AGND to DGND connection, the
connection should still be made at one point only, a star ground
point established as close as possible to the AD7891.
The AD7891 should have ample supply bypassing located as close
to the package as possible, ideally right up against the device.
One of the VDD pins (Pin 10 of the PLCC package and Pin 4
on the MQFP package) mainly drives the analog circuitry on
the chip. This pin should be decoupled to the analog ground
plane with a 10 mF tantalum bead capacitor in parallel with a
0.1 mF capacitor. The other VDD pin (Pin 19 on the PLCC
package and Pin 13 on the MQFP package) mainly drives
digital circuitry on the chip. This pin should be decoupled to the
digital ground plane with a 0.1 mF capacitor. The 0.1 mF
capacitors should have low effective series resistance (ESR) and
effective series inductance (ESI), such as the common ceramic
types or surface mount types, which provide a low impedance
path to ground at high frequencies to handle transient currents
due to internal logic switching. Figure 16 shows the
recommended decoupling scheme.
AD7891
10␮F
0.1␮F
VDD (PIN 10, PLCC
PIN 4, MQFP)
AGND
AGND
0.1␮F
VDD (PIN 19, PLCC
PIN 13, MQFP)
DGND
Figure 16. Recommended Decoupling Scheme for
the AD7891
REV. D
–17–
AD7891
AD7891 PERFORMANCE
Linearity
Dynamic Performance
The AD7891 contains an on-chip track/hold amplifier, allowing
the part to sample input signals of up to 250 kHz on any of its
input channels. Many of the AD7891’s applications require it to
sequence through low frequency input signals across its eight
channels. There may be some applications, however, for which
the dynamic performance of the converter on signals of up to
250 kHz input frequency is of interest. It is recommended for
these wider bandwidth signals that the hardware conversion
start method of sampling is used.
Noise
In an ADC, noise exhibits itself as code uncertainty in dc applications and as the noise floor (in an FFT for example) in ac
applications. In a sampling ADC, such as the AD7891, all
information about the analog input appears in the baseband from
dc to half the sampling frequency. The input bandwidth of the
track/hold amplifier exceeds the Nyquist bandwidth and,
therefore, an antialiasing filter should be used to remove
unwanted signals above fS/2 in the input signal in applications
where such signals exist.
Figure 17 shows a histogram plot for 16384 conversions of a dc
input signal using the AD7891-1. The analog input was set at
the center of a code transition in the following way. An initial dc
input level was selected and a number of conversions were
made. The resulting histogram was noted and the applied level
was adjusted so that only two codes were generated with an
equal number of occurrences. This indicated that the transition
point between the two codes had been found. The voltage level
at which this occurred was recorded. The other edge of one of
these two codes was then found in a similar manner. The dc
level for the center of code could then be calculated as the
average of the two transition levels. The AD7891-1 inputs
were configured for the ± 5 V input range and the data was read
from the part in parallel mode after conversion. Similar results
have been found with the AD7891-1 on the ± 10 V range and on
all input ranges of the AD7891-2. The same performance is
achieved in serial mode, again with the data read from the
AD7891-1 after conversion. All the codes, except for 3, appear
in one output bin, indicating excellent noise performance from
the ADC.
These applications require information on the spectral content
of the input signal. Signal-to-(noise + distortion), total
harmonic distortion, peak harmonic or spurious tone, and
intermodulation distortion are all specified. Figure 18 shows a
typical FFT plot of a 10 kHz, ± 10 V input after being digitized
by the AD7891-1 operating at 500 kHz, with the input connected
for ± 10 V operation. The signal-to-(noise + distortion) ratio is
72.2 dB and the total harmonic distortion is –87 dB. Figure 19
shows a typical FFT plot of a 100 kHz, 0 V to 5 V input after
being digitized by the AD7891-2 operating at 500 kHz, with the
input connected for 0 V to 5 V operation. The signal-to-(noise +
distortion) ratio is 71.17 dB and the total harmonic distortion
is –82.3 dB. It should be noted that reading from the part
during conversion does have a significant impact on dynamic
performance. Therefore, for sampling applications, it is
recommended not to read during conversion.
0
2048 POINT FFT
–30
SNR = 72.2dB
–60
dB
The linearity of the AD7891 is primarily determined by the
on-chip 12-bit DAC. This is a segmented DAC that is laser
trimmed for 12-bit integral linearity and differential linearity.
Typical INL for the AD7891 is ± 0.25 LSB while typical DNL
is ± 0.5 LSB.
–90
–120
18000
16381 CODES
–150
NUMBER OF OCCURRENCES
16000
FS /2
Figure 18. Typical AD7891-1 FFT Plot
14000
12000
0
10000
2048 POINT FFT
8000
–30
6000
SNR = 71.17dB
4000
0
1 CODE
2148
dB
–60
2000
2 CODES
2149
OUTPUT CODE
2150
–90
Figure 17. Typical Histogram Plot (AD7891-1)
–120
–150
FS /2
Figure 19. Typical AD7891-2 FFT Plot
–18–
REV. D
AD7891
Effective Number of Bits
12.0
The formula for signal-to-(noise + distortion) ratio (see Terminology
section) is related to the resolution or number of bits of the
converter. Rewriting the formula gives a measure of performance
expressed in effective number of bits (ENOB).
EFFECTIVE NUMBER OF BITS
11.9
ENOB = (SNR - 1.76) / 6.02
where SNR is the signal-to-(noise + distortion) ratio.
The effective number of bits for a device can be calculated from
its measured SNR. Figure 20 shows a typical plot of effective
number of bits versus frequency for the AD7891-1 and the
AD7891-2 from dc to 200 kHz. The sampling frequency is
500 kHz. The AD7891-1 inputs were configured for ± 10 V
operation. The AD7891-2 inputs were configured for 0 to 5 V
operation. The AD7891-1 plot only goes to 100 kHz as a
± 10 V sine wave of sufficient quality was unavailable at higher
frequencies.
11.8
11.7
11.6
AD7891-2 ENOB
11.5
11.4
11.3
11.2
AD7891-1 ENOB
11.1
11.0
0
20
40
60
100 120 140
80
FREQUENCY – kHz
OUTLINE DIMENSIONS
44-Lead Plastic Leaded Chip Carrier [PLCC]
(P-44A)
Dimensions shown in inches and (millimeters)
0.180 (4.57)
0.165 (4.19)
0.056 (1.42)
0.042 (1.07)
6
0.048 (1.22)
0.042 (1.07)
7
PIN 1
IDENTIFIER
0.021 (0.53)
0.013 (0.33)
0.630 (16.00)
0.590 (14.99)
0.050
(1.27)
BSC
TOP VIEW
17
0.020 (0.51)
MIN
40
39
(PINS DOWN)
0.032 (0.81)
0.026 (0.66)
29
28
18
0.656 (16.66)
SQ
0.650 (16.51)
0.120 (3.05)
0.090 (2.29)
0.040 (1.01)
R
0.025 (0.64)
0.695 (17.65)
SQ
0.685 (17.40)
COMPLIANT TO JEDEC STANDARDS MO-047AC
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
REV. D
180
200
Figure 20. Effective Number of Bits vs. Frequency
Figure 20 shows that the AD7891-1 converts an input sine wave of
100 kHz to an effective number of bits of 11 which equates to a
signal-to-(noise + distortion) level of 68.02 dBs. The AD7891-2
converts an input sine wave of 200 kHz to an effective number
of bits of 11.07, which equates to a signal-to-(noise + distortion)
level of 68.4 dBs.
0.048 (1.22)
0.042 (1.07)
160
–19–
BOTTOM VIEW
(PINS UP)
AD7891
OUTLINE DIMENSIONS
44-Lead Metric Quad Flat Package [MQFP]
(S-44-2)
Dimensions shown in millimeters
13.90
BSC SQ
2.45
MAX
33
23
34
SEATING
PLANE
C01358–0–4/04(D)
1.03
0.88
0.73
22
10.00
BSC SQ
TOP VIEW
(PINS DOWN)
2.10
2.00
1.95
7ⴗ
0ⴗ
VIEW A
PIN 1
44
0.25 MIN
COPLANARITY
0.10
VIEW A
ROTATED 90ⴗ CCW
12
1
11
0.80
BSC
0.45
0.30
COMPLIANT TO JEDEC STANDARDS MO-112-AA-1
Revision History
Location
Page
4/04—Data Sheet changed from REV. C to REV. D.
Changes to SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
Changes to PIN FUNCTION DESCRIPTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6
Changes to PARALLEL INTERFACE MODE FUNCTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Changes to SERIAL INTERFACE MODE FUNCTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Changes to CONTROL REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Changes to AD7891 to 8X51 Serial Interface section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Changes to Figure 10 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
Changes to Figure 11 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
Changes to Power Supply Bypassing and Grounding . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
Changes to Figure 16 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
01/02—Data Sheet changed from REV. B to REV. C.
Changed page 7 to page 6 and moved page 6 to page 9 to keep Pin Configurations together with Pin Function descriptions.
Edits to CONTROL REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
Text added to CONVERTER DETAILS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Edits to Figure 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
02/01—Data Sheet changed from REV. A to REV. B.
PQFP designation changed to MQFP throughout.
Edit to FEATURES, Single Supply Low Power Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to mW (90 to 82) in last paragraph of left hand column . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to POWER REQUIREMENTS section of Specifications table . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
–20–
REV. D