Exar CLC2601 Dual, triple, and quad 550mhz amplifier Datasheet

Data Sheet
Comlinear CLC2601, CLC3601, CLC4601
®
Dual, Triple, and Quad 550MHz Amplifiers
The Comlinear CLC2601 (dual), CLC3601 (triple), and CLC4601 (quad) are
high-performance, current feedback amplifiers. These amplifiers provide
550MHz unity gain bandwidth, ±0.1dB gain flatness to 120MHz, and 1,500V/μs
slew rate, exceeding the requirements of high-definition television (HDTV)
and other multimedia applications. These Comlinear high-performance amplifiers also provide ample output current to drive multiple video loads.
The Comlinear CLC2601, CLC3601, and CLC4601 are designed to operate
from ±5V supplies. They consume only 5.2mA of supply current per channel.
The combination of high-speed, low-power, and excellent video performance
make these amplifiers well suited for use in many general purpose, highspeed applications including standard definition and high definition video.
APPLICATIONS
n Video line drivers
n S-Video driver
n Video switchers and routers
n ADC buffer
n Active filters
n Cable drivers
n Twisted pair driver/receiver
Typical Application - Driving Dual Video Loads
+Vs
75Ω
Cable
Input
75Ω
75Ω
Cable
Output A
75Ω
75Ω
Rf
Rg
75Ω
75Ω
Cable
Output B
75Ω
-Vs
Ordering Information
Package
Pb-Free
RoHS Compliant
Operating Temperature Range
Packaging Method
CLC2601ISO8X
SOIC-8
Yes
Yes
-40°C to +85°C
Reel
CLC3601ISO14X
SOIC-14
Yes
Yes
-40°C to +85°C
Reel
CLC4601ISO14X
SOIC-14
Yes
Yes
-40°C to +85°C
Reel
Moisture sensitivity level for all parts is MSL-1.
Exar Corporation
48720 Kato Road, Fremont CA 94538, USA
www.exar.com
Tel. +1 510 668-7000 - Fax. +1 510 668-7001
Rev 1E
Part Number
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
General Description
FEATURES
n 0.1dB gain flatness to 120MHz
n 0.01%/0.06˚ differential gain/
phase error
n 335MHz -3dB bandwidth at G = 2
n 550MHz -3dB bandwidth at G = 1
n 1,500V/μs slew rate
n 52mA output current (sufficient for
driving two video loads)
n 5.2mA supply current
n Fully specified at ±5V supplies
n CLC2601: Pb-free SOIC-8
n CLC3601, CLC4601: Pb-free SOIC-14
Data Sheet
CLC2601 Pin Assignments
CLC2601 Pin Configuration
Pin Name
1
OUT1
Output, channel 1
OUT2
2
-IN1
Negative input, channel 1
6
-IN2
3
+IN1
Positive input, channel 1
5
+IN2
1
8
+VS
-IN1
2
7
+IN1
3
-V S
4
NC
1
14
OUT2
NC
2
13
-IN2
NC
3
12
+IN2
+VS
4
11
-VS
+IN1
5
10
+IN3
-IN1
6
9
-IN3
7
8
OUT3
CLC4601 Pin Configuration
OUT1
Negative supply
Positive input, channel 2
6
-IN2
Negative input, channel 2
7
OUT2
Output, channel 2
8
+VS
Positive supply
Pin No.
Pin Name
Description
1
NC
No Connect
2
NC
No Connect
3
NC
No Connect
4
+VS
Positive supply
5
+IN1
Positive input, channel 1
6
-IN1
Negative input, channel 1
7
OUT1
Output, channel 1
8
OUT3
Output, channel 3
9
-IN3
Negative input, channel 3
10
+IN3
Positive input, channel 3
11
-VS
12
+IN2
Positive input, channel 2
13
-IN2
Negative input, channel 2
14
OUT2
Output, channel 2
Negative supply
OUT1
Output, channel 1
-IN4
2
-IN1
Negative input, channel 1
+IN4
3
+IN1
Positive input, channel 1
4
+VS
Positive supply
5
+IN2
Positive input, channel 2
+IN3
6
-IN2
Negative input, channel 2
-IN3
7
OUT2
Output, channel 2
8
OUT3
Output, channel 3
9
-IN3
Negative input, channel 3
10
+IN3
Positive input, channel 3
11
-VS
12
+IN4
Positive input, channel 4
13
-IN4
Negative input, channel 4
14
OUT4
Output, channel 4
-IN1
2
13
+IN1
3
12
+VS
4
11
-VS
+IN2
5
10
-IN2
6
9
OUT3
©2007-2013 Exar Corporation 2/15
Description
Rev 1E
Pin Name
1
OUT4
8
+IN2
Pin No.
14
7
-VS
5
CLC4601 Pin Assignments
1
OUT2
4
CLC3601 Pin Assignments
CLC3601 Pin Configuration
OUT1
Description
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Pin No.
OUT1
Negative supply
Rev 1E
Data Sheet
Absolute Maximum Ratings
The safety of the device is not guaranteed when it is operated above the “Absolute Maximum Ratings”. The device should
not be operated at these “absolute” limits. Adhere to the “Recommended Operating Conditions” for proper device function. The information contained in the Electrical Characteristics tables and Typical Performance plots reflect the operating
conditions noted on the tables and plots.
Supply Voltage
Input Voltage Range
Min
Max
Unit
0
-Vs -0.5V
+14 or ±7
+Vs +0.5V
V
V
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Parameter
Reliability Information
Parameter
Junction Temperature
Storage Temperature Range
Lead Temperature (Soldering, 10s)
Package Thermal Resistance
8-Lead SOIC
14-Lead SOIC
Min
Typ
-65
Max
Unit
150
150
260
°C
°C
°C
100
88
°C/W
°C/W
Notes:
Package thermal resistance (qJA), JDEC standard, multi-layer test boards, still air.
ESD Protection
Product
Human Body Model (HBM)
Charged Device Model (CDM)
SOIC-8
SOIC-14
2.5kV
2kV
2.5kV
2kV
Recommended Operating Conditions
Parameter
Min
Operating Temperature Range
Supply Voltage Range
-40
±4
Typ
Max
Unit
+85
±6
°C
V
Rev 1E
©2007-2013 Exar Corporation 3/15
Rev 1E
Data Sheet
Electrical Characteristics
TA = 25°C, Vs = ±5V, Rf = 510Ω, RL = 100Ω to GND, G = 2; unless otherwise noted.
Symbol
Parameter
Conditions
Min
Typ
Max
Units
Frequency Domain Response
-3dB Bandwidth
G = +1, VOUT = 0.2Vpp, Rf = 1kΩ
550
MHz
BWSS
BWLS
-3dB Bandwidth
G = +2, VOUT = 0.2Vpp
335
MHz
Large Signal Bandwidth
G = +2, VOUT = 4Vpp
200
MHz
BW0.1dBSS
0.1dB Gain Flatness
G = +2, VOUT = 0.2Vpp
(Rf=453Ω for CLC4601)
120
MHz
BW0.1dBLS
0.1dB Gain Flatness
G = +2, VOUT = 4Vpp
55
MHz
Time Domain Response
tR, tF
Rise and Fall Time
VOUT = 2V step; (10% to 90%)
1.4
ns
tS
Settling Time to 0.1%
VOUT = 2V step
20
ns
OS
Overshoot
VOUT = 0.2V step
1.5
%
SR
Slew Rate
VOUT = 4V step
1500
V/µs
Distortion/Noise Response
HD2
2nd Harmonic Distortion
2Vpp, 1MHz
-82
dBc
HD3
3rd Harmonic Distortion
2Vpp, 1MHz
-83
dBc
THD
Total Harmonic Distortion
2Vpp, 1MHz
-80
dB
DG
Differential Gain
NTSC (3.58MHz), DC-coupled, RL = 150Ω
0.01
%
DP
Differential Phase
NTSC (3.58MHz), DC-coupled, RL = 150Ω
0.06
°
en
Input Voltage Noise
> 1MHz
7
nV/√Hz
in+
Input Current Noise (+)
> 1MHz
1.3
pA/√Hz
in-
Input Current Noise (-)
> 1MHz
11
pA/√Hz
XTALK
Crosstalk
Channel-to-channel 5MHz
-56
dB
DC Performance
VIO
dVIO
Ibn
dIbn
Ibi
dIbni
Input Offset Voltage(1)
-7.5
Average Drift
2.7
+7.5
15
Input Bias Current Non-inverting(1)
-7.0
2.6
-30
7.4
Average Drift
7.0
6
Input Bias Current Inverting(1)
Average Drift
µA
nA/°C
30
15
µA
nA/°C
PSRR
Power Supply Rejection Ratio(1)
DC
61
dB
ZOL
Open-Loop Transimpedance
VOUT = VS / 2
420
kΩ
CLC2601 Total
10.4
14
mA
CLC3601 Total
20.8
28
mA
CLC4601 Total
20.8
28
mA
Non-inverting
8
MΩ
1
pF
IS
Supply
Current(1)
57
mV
µV/°C
Input Characteristics
RIN
Input Resistance
CIN
Input Capacitance
CMIR
Common Mode Input Range
CMRR
Common Mode Rejection Ratio(1)
DC
V
50
54
dB
-2.6
±2.95
Output Characteristics
RO
Output Resistance
VOUT
Output Voltage Swing
IOUT
Output Current
ISC
Short-Circuit Output Current
Closed Loop, DC
RL = 100Ω (1)
RL = 1kΩ
VOUT = VS / 2
90
mΩ
2.6
V
±3.35
V
52
mA
65
mA
Notes:
1. 100% tested at 25°C
©2007-2013 Exar Corporation 4/15
Rev 1E
Rev 1E
±2.3
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
UGBW
Data Sheet
Typical Performance Characteristics
TA = 25°C, Vs = ±5V, Rf = 510Ω, RL = 100Ω, G = 2; unless otherwise noted.
Inverting Frequency Response
1
0
0
-1
-1
-2
Normalized Gain (dB)
1
G = 10
-3
G=5
-4
G=2
-5
-6
G=1
Rf = 1kΩ
VOUT = 0.2Vpp
G = -10
-2
G = -5
-3
-4
G = -2
-5
-6
-7
VOUT = 0.2Vpp
G = -1
-7
0.1
1
10
100
1000
0.1
1
Frequency (MHz)
1
2
0
1
CL = 1000pF
Rs = 5Ω
CL = 500pF
Rs = 7Ω
-2
-3
CL = 100pF
Rs = 15Ω
-4
CL = 50pF
Rs = 20Ω
-5
-6
1000
100
1000
RL = 2.5KΩ
0
-1
RL = 1KΩ
-2
-3
RL = 150Ω
-4
-5
CL = 10pF
Rs = 40Ω
VOUT = 0.2Vpp
VOUT = 0.2Vpp
RL = 50Ω
-6
-7
0.1
1
10
100
0.1
1000
1
Frequency Response vs. VOUT
Frequency Response vs. Temperature
1
0
0
-1
-1
Normalized Gain (dB)
1
-2
VOUT = 4Vpp
-3
-4
VOUT = 2Vpp
-5
VOUT = 1Vpp
-2
-3
+ 25degC
-4
- 40degC
-5
+ 85degC
-6
VOUT = 2Vpp
Rev 1E
-6
10
Frequency (MHz)
Frequency (MHz)
Normalized Gain (dB)
100
Frequency Response vs. RL
Normalized Gain (dB)
Normalized Gain (dB)
Frequency Response vs. CL
-1
10
Frequency (MHz)
-7
-7
0.1
1
10
100
0.1
1000
©2007-2013 Exar Corporation 1
10
100
1000
Frequency (MHz)
Frequency (MHz)
5/15
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Normalized Gain (dB)
Non-Inverting Frequency Response
Rev 1E
Data Sheet
Typical Performance Characteristics - Continued
TA = 25°C, Vs = ±5V, Rf = 510Ω, RL = 100Ω, G = 2; unless otherwise noted.
Frequency Response vs. Rf at G=1
Frequency Response vs. Rf at G=2
Rf = 510Ω
Normalized Gain (dB)
Normalized Gain (dB)
Rf = 750Ω
1
0
-1
Rf = 1.kΩ
-2
-3
Rf = 1.24kΩ
G=1
Rf = 250Ω
1
2
0
Rf = 510Ω
-1
-2
Rf = 1kΩ
-3
-4
Rf = 1.24kΩ
-5
G=2
-6
-4
0.1
1
10
100
0.1
1000
1
10
Frequency Response vs. Rf at G=5
0.1
Rf = 200Ω
-1
0
Normalized Gain (dB)
0
Normalized Gain (dB)
1000
Gain Flatness
1
Rf = 510Ω
-2
-3
Rf = 100Ω
-4
-5
-6
-0.1
-0.2
-0.3
-0.4
G=5
-7
VOUT = 0.2Vpp
-0.5
0.1
1
10
100
1000
0.1
1
Frequency (MHz)
0
-40
Phase
-60
Gain
-80
10k
-100
1k
-120
-140
100
-160
10
-200
1M
10M
100M
80
70
60
50
40
30
20
10
0
1G
0.001
Frequency (Hz)
©2007-2013 Exar Corporation 90
Rev 1E
-180
100k
1000
100
Transimpedance Phase (°)
-20
10k
100
Input Voltage Noise
Input Voltage Noise (nV/√Hz)
1M
100k
10
Frequency (MHz)
Open Loop Transimpendance Gain/Phase vs. Frequency
Transimpedance Gain (Ω)
100
Frequency (MHz)
Frequency (MHz)
0.001
0.01
0.1
1
10
100
Frequency (MHz)
6/15
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
2
3
Rev 1E
Data Sheet
Typical Performance Characteristics - Continued
TA = 25°C, Vs = ±5V, Rf = 510Ω, RL = 100Ω, G = 2; unless otherwise noted.
2nd Harmonic Distortion vs. RL
3rd Harmonic Distortion vs. RL
-55
-60
RL = 100Ω
-70
-75
-80
RL = 1kΩ
-85
-90
RL = 100Ω
-60
Distortion (dBc)
Distortion (dBc)
-65
-65
-70
RL = 1kΩ
-75
-80
-85
VOUT = 2Vpp
-95
VOUT = 2Vpp
-90
0
5
10
15
20
0
5
10
Frequency (MHz)
15
20
Frequency (MHz)
2nd Harmonic Distortion vs. VOUT
3rd Harmonic Distortion vs. VOUT
-45
-55
-50
20MHz
-60
-55
Distortion (dBc)
Distortion (dBc)
-65
-70
-75
5MHz
-80
20MHz
-60
-65
5MHz
-70
-75
-80
-85
1MHz
-85
1MHz
-90
-90
0.5
0.75
1
1.25
1.5
1.75
2
2.25
2.5
0.5
0.75
1
Output Amplitude (Vpp)
1.5
1.75
2
2.25
2.5
PSRR vs. Frequency
0
-20
-10
-30
-20
-40
PSRR (dB)
CMRR (dB)
1.25
Output Amplitude (Vpp)
CMRR vs. Frequency
-30
-40
-50
-50
-60
-70
Rev 1E
-60
-80
10k
100k
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
-50
-55
1M
10M
100M
10k
©2007-2013 Exar Corporation 100k
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
7/15
Rev 1E
Data Sheet
Typical Performance Characteristics - Continued
TA = 25°C, Vs = ±5V, Rf = 510Ω, RL = 100Ω, G = 2; unless otherwise noted.
Large Signal Pulse Response
2.5
0.100
2.0
0.075
1.5
0.050
1.0
0.025
0.5
Voltage (V)
0.125
0.000
-0.025
0.0
-0.5
-0.050
-1.0
-0.075
-1.5
-0.100
-2.0
-0.125
-2.5
0
20
40
60
80
100
120
140
160
180
200
0
20
40
60
Time (ns)
80
100
120
140
160
180
200
Time (ns)
Crosstalk vs. Frequency
Closed Loop Output Impedance vs. Frequency
-30
10
-35
Output Impedance (Ω)
-40
-45
Crosstalk (dB)
-50
-55
-60
-65
-70
-75
-80
-85
1
VOUT = 2Vpp
-90
0.1
-95
0.1
1
10
100
10k
Frequency (MHz)
1M
10M
100M
Frequency (Hz)
Differential Gain & Phase AC Coupled Output
Differential Gain & Phase DC Coupled Output
0.04
0.02
RL = 150Ω
AC coupled into 220µF
0.02
0.01
DG
0
-0.01
-0.02
DP
-0.03
RL = 150Ω
DC coupled
0.01
Diff Gain (%) / Diff Phase (°)
0.03
Diff Gain (%) / Diff Phase (°)
100k
DG
0
-0.01
-0.02
-0.03
DP
-0.04
-0.05
-0.04
Rev 1E
-0.06
-0.07
-0.7
-0.5
-0.3
-0.1
0.1
Input Voltage (V)
0.3
0.5
©2007-2013 Exar Corporation 0.7
-0.7
-0.5
-0.3
-0.1
0.1
0.3
0.5
0.7
Input Voltage (V)
8/15
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Voltage (V)
Small Signal Pulse Response
Rev 1E
Data Sheet
General Information - Current Feedback
Technology
Advantages of CFB Technology
Ierr
When designing with CFB amplifiers always abide by these
basic rules:
• Use the recommended feedback resistor value
• Do not use reactive (capacitors, diodes, inductors, etc.)
elements in the direct feedback path
• Avoid stray or parasitic capacitance across feedback resistors
• Follow general high-speed amplifier layout guidelines
• Ensure proper precautions have been made for driving
capacitive loads
VIN
Ierr
x1
Zo*Ierr
VOUT
Rf
RL
Rg
VIN
= 1+
Rf
Rg
+
1+
1
Rf
Eq. 1
Zo(jω)
Figure 1. Non-Inverting Gain Configuration with First
Order Transfer Function
©2007-2013 Exar Corporation Rg
VOUT
VIN
VOUT
Rf
= −
Rf
Rg
+
1+
1
Rf
RL
Eq. 2
Zo(jω)
Figure 2. Inverting Gain Configuration with First Order
Transfer Function
CFB Technology - Theory of Operation
Figure 1 shows a simple representation of a current feedback amplifier that is configured in the traditional noninverting gain configuration.
Instead of having two high-impedance inputs similar to a
VFB amplifier, the inputs of a CFB amplifier are connected
across a unity gain buffer. This buffer has a high impedance input and a low impedance output. It can source or
sink current (Ierr) as needed to force the non-inverting
input to track the value of Vin. The CFB architecture employs a high gain trans-impedance stage that senses Ierr
and drives the output to a value of (Zo(jω) * Ierr) volts.
With the application of negative feedback, the amplifier
will drive the output to a voltage in a manner which tries
to drive Ierr to zero. In practice, primarily due to limitations on the value of Zo(jω), Ierr remains a small but
finite value.
A closer look at the closed loop transfer function (Eq.1)
shows the effect of the trans-impedance, Zo(jω) on the
gain of the circuit. At low frequencies where Zo(jω) is very
large with respect to Rf, the second term of the equation
approaches unity, allowing Rf and Rg to set the gain. At
higher frequencies, the value of Zo(jω) will roll off, and
the effect of the secondary term will begin to dominate.
The -3dB small signal parameter specifies the frequency
where the value Zo(jω) equals the value of Rf causing the
gain to drop by 0.707 of the value at DC.
For more information regarding current feedback amplifiers, visit www.exar.com for detailed application notes,
such as AN-3: The Ins and Outs of Current Feedback Amplifiers.
9/15
Rev 1E
Rev 1E
VOUT
VIN
Zo*Ierr
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
The CLCx601 Family of amplifiers utilize current feedback
(CFB) technology to achieve superior performance. The
primary advantage of CFB technology is higher slew rate
performance when compared to voltage feedback (VFB)
architecture. High slew rate contributes directly to better
large signal pulse response, full power bandwidth, and
distortion.
CFB also alleviates the traditional trade-off between
closed loop gain and usable bandwidth that is seen with
a VFB amplifier. With CFB, the bandwidth is primarily determined by the value of the feedback resistor, Rf. By using optimum feedback resistor values, the bandwidth of a
CFB amplifier remains nearly constant with different gain
configurations.
x1
Data Sheet
Application Information
Basic Operation
+Vs
Input
Feedback Resistor Selection
6.8μF
0.1μF
+
Output
-
RL
0.1μF
Rg
Rf
6.8μF
G = 1 + (Rf/Rg)
-Vs
Figure 3. Typical Non-Inverting Gain Circuit
+Vs
R1
Input
0.1μF
+
Rg
6.8μF
One of the key design considerations when using a CFB
amplifier is the selection of the feedback resistor, Rf. Rf is
used in conjunction with Rg to set the gain in the traditional non-inverting and inverting circuit configurations.
Refer to figures 3 and 4. As discussed in the Current Feedback Technology section, the value of the feedback resistor has a pronounced effect on the frequency response of
the circuit.
Table 1, provides recommended Rf and associated Rg values for various gain settings. These values produce the
optimum frequency response, maximum bandwidth with
minimum peaking. Adjust these values to optimize performance for a specific application. The typical performance
characteristics section includes plots that illustrate how
the bandwidth is directly affected by the value of Rf at
various gain settings.
Output
-
RL
0.1μF
Rf
6.8μF
G = - (Rf/Rg)
-Vs
For optimum input offset
voltage set R1 = Rf || Rg
Figure 4. Typical Inverting Gain Circuit
+Vs
Input
6.8μF
0.1μF
+
Output
0.1μF
6.8μF
-Vs
RL
Rf
G=1
Rf is required for CFB amplifiers
Figure 5. Typical Unity Gain (G=1) Circuit
©2007-2013 Exar Corporation Rf (Ω)
Rg (Ω)
±0.1dB BW
(MHz)
-3dB BW
(MHz)
1
1120
-
165
520
2
510
510
120
335
5
200
50
40
230
Table 1: Recommended Rf vs. Gain
In general, lowering the value of Rf from the recommended value will extend the bandwidth at the expense
of additional high frequency gain peaking. This will cause
increased overshoot and ringing in the pulse response
characteristics. Reducing Rf too much will eventually
cause oscillatory behavior.
Increasing the value of Rf will lower the bandwidth. Lowering the bandwidth creates a flatter frequency response
and improves 0.1dB bandwidth performance. This is important in applications such as video. Further increase in
Rf will cause premature gain rolloff and adversely affect
gain flatness.
10/15
Rev 1E
Rev 1E
-
Gain
(V/V
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Figures 3, 4, and 5 illustrate typical circuit configurations for
non-inverting, inverting, and unity gain topologies for dual
supply applications. They show the recommended bypass
capacitor values and overall closed loop gain equations.
CFB amplifiers can be used in unity gain configurations.
Do not use the traditional voltage follower circuit, where
the output is tied directly to the inverting input. With a
CFB amplifier, a feedback resistor of appropriate value
must be used to prevent unstable behavior. Refer to figure 5 and Table 1. Although this seems cumbersome, it
does allow a degree of freedom to adjust the passband
characteristics.
Data Sheet
Driving Capacitive Loads
Input
+
Rs
-
Output
CL
Rf
RL
Rg
Overdrive Recovery
An overdrive condition is defined as the point when either
one of the inputs or the output exceed their specified voltage range. Overdrive recovery is the time needed for the
amplifier to return to its normal or linear operating point.
The recovery time varies, based on whether the input or
output is overdriven and by how much the range is exceeded. The CLCx601 Family will typically recover in less
than 20ns from an overdrive condition. Figure 7 shows the
CLC2601 in an overdriven condition.
Figure 6. Addition of RS for Driving
Capacitive Loads
CL (pF)
RS (Ω)
-3dB BW (MHz)
10
40
350
50
20
200
100
15
140
VIN = 1.5Vpp
G=5
0.75
Input Voltage (V)
0.50
4
3
2
Input
0.25
1
Output
0.00
0
-0.25
-1
-0.50
-2
-0.75
-3
-1.00
Output Voltage (V)
Table 2 provides the recommended RS for various capacitive loads. The recommended RS values result in <=0.5dB
peaking in the frequency response. The Frequency Response vs. CL plot, on page 5, illustrates the response of
the CLCx601 Family.
1.00
-4
0
20
40
60
80
100
120
140
160
180
200
Time (ns)
Figure 7. Overdrive Recovery
Table 1: Recommended RS vs. CL
For a given load capacitance, adjust RS to optimize the
tradeoff between settling time and bandwidth. In general,
reducing RS will increase bandwidth at the expense of additional overshoot and ringing.
Parasitic Capacitance on the Inverting Input
Physical connections between components create unintentional or parasitic resistive, capacitive, and inductive
elements.
In general, avoid adding any additional parasitic capacitance at this node. In addition, stray capacitance across
the Rf resistor can induce peaking and high frequency
©2007-2013 Exar Corporation Power dissipation should not be a factor when operating
under the stated 1000 ohm load condition. However, applications with low impedance, DC coupled loads should
be analyzed to ensure that maximum allowed junction
temperature is not exceeded. Guidelines listed below can
be used to verify that the particular application will not
cause the device to operate beyond it’s intended operating range.
Maximum power levels are set by the absolute maximum
junction rating of 150°C. To calculate the junction temperature, the package thermal resistance value ThetaJA
(ӨJA) is used along with the total die power dissipation.
TJunction = TAmbient + (ӨJA × PD)
Where TAmbient is the temperature of the working environment.
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Parasitic capacitance at the inverting input can be especially troublesome with high frequency amplifiers. A parasitic capacitance on this node will be in parallel with the
gain setting resistor Rg. At high frequencies, its impedance can begin to raise the system gain by making Rg
appear smaller.
Power Dissipation
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Increased phase delay at the output due to capacitive loading can cause ringing, peaking in the frequency response,
and possible unstable behavior. Use a series resistance,
RS, between the amplifier and the load to help improve
stability and settling performance. Refer to Figure 6.
ringing. Refer to the Layout Considerations section for
additional information regarding high speed layout techniques.
Data Sheet
PD = Psupply - Pload
Psupply = Vsupply × IRMS supply
Vsupply = VS+ - VSPower delivered to a purely resistive load is:
SOIC-14
2
1.5
SOIC-8
1
0.5
0
-40
Pload = ((VLOAD)RMS2)/Rloadeff
-20
0
20
40
60
80
Ambient Temperature (°C)
The effective load resistor (Rloadeff) will need to include
the effect of the feedback network. For instance,
Figure 8. Maximum Power Derating
Rloadeff in figure 3 would be calculated as:
RL || (Rf + Rg)
These measurements are basic and are relatively easy to
perform with standard lab equipment. For design purposes
however, prior knowledge of actual signal levels and load
impedance is needed to determine the dissipated power.
Here, PD can be found from
PD = PQuiescent + PDynamic - PLoad
Quiescent power can be derived from the specified IS values along with known supply voltage, VSupply. Load power
can be calculated as above with the desired signal amplitudes using:
(VLOAD)RMS = VPEAK / √2
( ILOAD)RMS = ( VLOAD)RMS / Rloadeff
The dynamic power is focused primarily within the output
stage driving the load. This value can be calculated as:
PDYNAMIC = (VS+ - VLOAD)RMS × ( ILOAD)RMS
Better thermal ratings can be achieved by maximizing PC
board metallization at the package pins. However, be careful of stray capacitance on the input pins.
In addition, increased airflow across the package can also
help to reduce the effective ӨJA of the package.
In the event the outputs are momentarily shorted to a low
impedance path, internal circuitry and output metallization
are set to limit and handle up to 65mA of output current.
However, extended duration under these conditions may
not guarantee that the maximum junction temperature
(+150°C) is not exceeded.
Layout Considerations
General layout and supply bypassing play major roles in
high frequency performance. Exar has evaluation boards
to use as a guide for high frequency layout and as aid in
device testing and characterization. Follow the steps below
as a basis for high frequency layout:
Assuming the load is referenced in the middle of the power
rails or Vsupply/2.
• Include 6.8µF and 0.1µF ceramic capacitors for power
supply decoupling
Figure 8 shows the maximum safe power dissipation in the
package vs. the ambient temperature for the 8 and 14 lead
SOIC packages.
• Place the 6.8µF capacitor within 0.75 inches of the power pin
• Place the 0.01µF capacitor within 0.1 inches of the power pin
• Minimize all trace lengths to reduce series inductances
Refer to the evaluation board layouts below for more information.
©2007-2013 Exar Corporation 12/15
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• Remove the ground plane under and around the part,
especially near the input and output pins to reduce parasitic capacitance
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Supply power is calculated by the standard power equation.
2.5
Maximum Power Dissipation (W)
In order to determine PD, the power dissipated in the load
needs to be subtracted from the total power delivered by
the supplies.
Data Sheet
Evaluation Board Information
The following evaluation boards are available to aid in the
testing and layout of these devices:
Products
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Evaluation Board #
CEB006
CEB018
CLC2601
CLC3601, CLC4601
Evalutaion Board Schematics
Evaluation board schematics and layouts are shown in Figures 9-14. These evaluation boards are built for dual- supply operation. Follow these steps to use the board in a
single-supply application:
Figure 10. CEB006 Top View
1. Short -Vs to ground.
2. Use C3 and C4, if the -VS pin of the amplifier is not
directly connected to the ground plane.
Figure 11. CEB006 Bottom View
Figure 9. CEB006 Schematic
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Data Sheet
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
Figure 14. CEB018 Bottom View
Figure 12. CEB018 Schematic
©2007-2013 Exar Corporation Rev 1E
Figure 13. CEB018 Top View
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Data Sheet
Mechanical Dimensions
SOIC-8 Package
Comlinear CLC2601, CLC3601, CLC4601 Dual, Triple, and Quad 550MHz Amplifiers
SOIC-14 Package
For Further Assistance:
Rev 1E
Exar Corporation Headquarters and Sales Offices
48720 Kato Road
Tel.: +1 (510) 668-7000
Fremont, CA 94538 - USA
Fax: +1 (510) 668-7001
www.exar.com
NOTICE
EXAR Corporation reserves the right to make changes to the products contained in this publication in order to improve design, performance or reliability. EXAR Corporation assumes no responsibility for the use of any
circuits described herein, conveys no license under any patent or other right, and makes no representation that the circuits are free of patent infringement. Charts and schedules contained here in are only for illustration
purposes and may vary depending upon a user’s specific application. While the information in this publication has been carefully checked; no responsibility, however, is assumed for inaccuracies.
EXAR Corporation does not recommend the use of any of its products in life support applications where the failure or malfunction of the product can reasonably be expected to cause failure of the life support system or
to significantly affect its safety or effectiveness. Products are not authorized for use in such applications unless EXAR Corporation receives, in writing, assurances to its satisfaction that: (a) the risk of injury or damage
has been minimized; (b) the user assumes all such risks; (c) potential liability of EXAR Corporation is adequately protected under the circumstances.
Reproduction, in part or whole, without the prior written consent of EXAR Corporation is prohibited.
©2007-2013 Exar Corporation 15/15
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