LINER LTC2977 Triple output 5a/5a/4a step-down dc/dc î¼moduleâ® regulator Datasheet

LTM4634
Triple Output 5A/5A/4A
Step-Down DC/DC
µModule® Regulator
Features
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Description
Three Independent High Efficiency Regulator
Channels
IOUT1,2 = 5A, IOUT3 = 4A
Input Voltage Range: 4.75V to 28V
Independent VIN for Each Channel
VOUT1,2 Voltage Range: 0.8V to 5.5V
VOUT3 Voltage Range: 0.8V to 13.5V
±1.5% Maximum Total DC Output Error
Current Mode Control/Fast Transient Response
Frequency Synchronization
Output Overvoltage and Overcurrent Protection
PolyPhase® Operation with Current Sharing
General Purpose Temperature Monitors
Soft-Start/Voltage Tracking
Power Good Monitors
SnPb or RoHS Compliant Finish
15mm × 15mm × 5.01mm BGA Package
The LTM®4634 integrates three complete 5A/5A/4A high
efficiency switching mode DC/DC converters into one small
package. Switching controllers, power FETs, inductors, and
most support components are included. Operating over an
input voltage range of 4.75V to 28V, the LTM4634 provides
three independent output voltages. VOUT1 and VOUT2 are
adjustable from 0.8V to 5.5V, while VOUT3 is adjustable
from 0.8V to 13.5V. Each output voltage is set by a single
external resistor.
High switching frequency and a current mode architecture
enable a very fast transient response to line and load
changes without sacrificing stability. The device supports
frequency synchronization, multiphase parallel operation, soft-start and output voltage tracking for supply rail
sequencing.
Fault protection features include overvoltage protection,
overcurrent protection and temperature monitoring. The
power module is offered in a space saving, thermally
enhanced 15mm × 15mm × 5.01mm BGA package. The
LTM4634 is available with SnPb (BGA) or RoHS compliant
terminal finish.
Applications
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Telecom, Networking and Industrial Equipment
High Density Point of Load Voltage Regulation
L, LT, LTC, LTM, µModule, PolyPhase, Burst Mode, Linear Technology and the Linear logo
are registered trademarks and PowerPath, LTpowerCAD and UltraFast are trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
Protected by U.S. Patents, including 5481178, 5705919, 5929620, 6100678, 6144194,
6177787, 6304066, 6580258 and 8163643. Other patents pending.
Typical Application
24V Input to 3.3V, 5V and 12V Output Regulator
24V Input Efficiency
100
5V
2Ω
40k
VIN1
VIN2 VIN3
EXTVCC
INTVCC FREQ/PLLLPF
CNTL_PWR
PGOOD12
PGOOD3
VOUT1
RUN1
1µF
RUN2
RUN3
TK/SS1
VFB1
LTM4634
VOUT2
TK/SS2
VFB2
TK/SS3
VOUT3
MODE/PLLIN GND SGND
VFB3
10k
19.1k
11.5k
4.32k
95
4.7µF
6.3V
10k
3.3V
5V
90
EFFICIENCY (%)
24VIN
85
80
75
VEXTVCC = 5V
24V to 3.3V EFF (750kHz) CH1
24V to 5V EFF (750kHz) CH2
24V to 12V EFF (750kHz) CH3
70
12V
4634 TA01a
65
60
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 TA01b
4634f
For more information www.linear.com/LTM4634
1
LTM4634
Absolute Maximum Ratings
Pin Configuration
(Note 1)
CNTL_PWR................................................ –0.3V to 30V
VIN1, VIN2, VIN3............................................ –0.3V to 30V
VOUT1, VOUT2............................................ –0.3V to 5.75V
VOUT3.......................................................... –0.3V to 14V
Switch Voltage (SW1, SW2 and SW3)............–1V to 30V
MODE/PLLIN, TK/SS1, TK/SS2, TK/SS3,
FREQ/PLLLPF........................................ –0.3V to INTVCC
COMP1, COMP2, COMP3, VFB1, VFB2, VFB3
(Note 3).................................................. –0.3V to INTVCC
RUN1, RUN2, RUN3, INTVCC, EXTVCC,
PGOOD12, PGOOD3...................................... –0.3V to 6V
TEMP1, TEMP2.......................................... –0.3V to 0.8V
INTVCC Peak Output Current.................................100mA
Operating Junction Temperature Range
(Note 2)................................................... –40°C to 125°C
Storage Temperature Range................... –55°C to 125°C
Peak Solder Reflow Body Temperature.................. 245°C
TOP VIEW
PGOOD12 M
PGOOD3
L
EXTVCC
K
G
MODE/PLLIN
RUN1
RUN2
RUN3
COMP2 VFB2
COMP3 VFB3 SGND
GND
J
H
FREQ/PLLLPF
TKSS2
TK/SS1
TK/SS3
VFB1 GND
COMP1
GND
INTVCC
CNTL_PWR
VIN2
VIN3
GND
VIN1
GND
F
SW3
SW1
E
D
C
TEMP2
SW2
GND
VOUT2
B
TEMP1
VOUT1
VOUT3
A
1
2
3
4
GND
5
6
7
8
9
GND
10
11
12
BGA PACKAGE 144 LEAD (15mm × 15mm × 5.01mm)
TJMAX = 125°C, θJA = 7.5°C/W, θJCbottom = 4°C/W, θJCtop = 5°C/W
θJA DERIVED FROM 95mm × 76mm PCB WITH 4-LAYER, WEIGHT = 3.2g
θ VALUES DETERMINED PER JESD51-12
Order Information
PART MARKING*
PART NUMBER
PAD OR BALL FINISH
DEVICE
FINISH CODE
PACKAGE
TYPE
MSL
RATING
TEMPERATURE RANGE
(See Note 2)
LTM4634EY#PBF
SAC305 (RoHS)
LTM4634Y
e1
BGA
4
–40°C to 125°C
LTM4634IY#PBF
SAC305 (RoHS)
LTM4634Y
e1
BGA
4
–40°C to 125°C
LTM4634IY
SnPb (63/37)
LTM4634Y
e0
BGA
4
–40°C to 125°C
Consult Marketing for parts specified with wider operating temperature
ranges. *Device temperature grade is indicated by a label on the shipping
container. Pad or ball finish code is per IPC/JEDEC J-STD-609.
• Recommended LGA and BGA PCB Assembly and Manufacturing
Procedures:
www.linear.com/umodule/pcbassembly
• Terminal Finish Part Markings:
www.linear.com/leadfree
• LGA and BGA Package and Tray Drawings:
www.linear.com/packaging
2
4634f
For more information www.linear.com/LTM4634
LTM4634
Electrical Characteristics
The l denotes the specifications which apply over the specified internal
operating temperature range (Note 2), otherwise specifications are at TA = 25°C. VIN = 24V, per the typical application for each regulator
channel.
SYMBOL
PARAMETER
CONDITIONS
VIN
Input DC Voltage
CNTL_PWR Powered Tied to Input Supply
VOUT(RANGE)
Output Voltage Range VOUT1, VOUT2
Output Voltage Range VOUT3
VOUT(DC)
Output Voltage, Total Variation with Line
and Load, VOUT1, VOUT2, VOUT3
MIN
CIN = 22µF × 3, COUT = 100µF Ceramic × 3,
RFB = 11.5k, MODE/PLLIN = 0V, VIN = 5.5V to 28V,
IOUT1,2 = 0A to 5A, IOUT3 = 0A to 4A (Note 4)
TYP
MAX
UNITS
l
4.75
28
V
l
l
0.8
0.8
5.5
13.5
V
V
l
4.925
5.0
5.075
V
1.15
1.3
1.4
V
Input Specifications
VRUN
RUN1, RUN2, RUN3 Pin ON Threshold
VRUN(HYS)
RUN Pin Hysteresis
IQ(VIN)
Input Supply Bias Current Each Channel
IS(VIN)
Input Supply Current Each Channel
VRUN Rising
175
mV
VOUT = 5V, Burst Mode Operation, IOUT = 0A
VOUT = 5V, Pulse-Skipping Mode, IOUT = 0A
VOUT = 5V, Switching Continuous, IOUT = 0A
Shutdown, RUN = 0V, VIN = 24V
0.5
1.6
45
10
mA
mA
mA
µA
VIN = 12V, EXTVCC = 5VOUT
VOUT1,2 = 5V, VOUT3 = 5V
IOUT1,2 = 5A
2.21
A
IOUT3 = 4A
1.76
A
Output Specifications (Note 4)
IOUT(DC)
Output Continuous Current Range Each
Channel
VOUT1,2 = 5V
VOUT3 = 5V
∆VOUT(LINE)
VOUT
Line Regulation Accuracy per Channel
VOUT1 = VIN from 5.5V to 28V
IOUT = 0A, CNTL_PWR Tie to VIN
l
0.015
0.02
%/V
∆VOUT(LOAD)
VOUT
Load Regulation Accuracy per Channel
VOUT = 5V, IOUT1,2 = 0A to 5A
Ch1, Ch2, IOUT3 = 0A to 4A
l
0.3
0.5
%
VOUT(AC)
Output Ripple Voltage per Channel
IOUT = 0A, COUT = 100µF Ceramic × 3,
VIN = 24V, VOUT = 5V
75
mV
∆VOUT(START)
Turn-On Overshoot per Channel
COUT = 100µF Ceramic × 3, VOUT = 5V,
IOUT = 0A, TK/SS = 0.01µF
50
mV
tSTART
Turn-On Time per Channel
COUT = 100µF Ceramic × 3, VOUT = 5V,
IOUT = 0A, TK/SS = 0.01µF
6
ms
VOUTLS
Peak Deviation for Dynamic Load per
Channel
Load: 0% to 50% to 0% of Full Load,
COUT = 100µF Ceramic × 3,
VOUT = 5V Typical Bench Data
200
mV
tSETTLE
Settling Time for Dynamic Load Step per Load: 0% to 50% to 0% of Full Load,
Channel
COUT = 100µF Ceramic × 3,
VOUT = 5V Typical Bench Data
50
µs
IOUT(PK)
Output Current Limit per Channel
8
A
0
0
VOUT = 5V
5
4
A
A
Control Specifications
VFB
Voltage at VFB Pin per Channel
IOUT = 0A, VOUT = 5V
l
0.794
0.792
0.80
0.80
l
0.84
1.1
1.5
(Note 3)
0.806
0.808
V
V
–10
–50
nA
0.86
0.88
V
1.9
µA
IFB
Current at VFB Pin per Channel
VOVL
Feedback Overvoltage Lockout per
Channel
ITK/SS
Track Pin Soft-Start Pull-Up Current per
Channel
TK/SS = 0V
tON(MIN)
Minimum On-Time
(Note 3)
90
ns
Max DC
Maximum Duty Cycle
5.5V to 5V at 5A (Note 5)
95
%
RFBHI
Resistor Between VOUT and VFB Pins
60.0
60.4
60.8
kΩ
4634f
For more information www.linear.com/LTM4634
3
LTM4634
Electrical Characteristics
The l denotes the specifications which apply over the specified internal
operating temperature range (Note 2), otherwise specifications are at TA = 25°C. VIN = 24V, per the typical application for each regulator
channel.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
VPGOOD
PGOOD Trip Level
PGOOD12
PGOOD3
VFB With Respect to Set Output
VFB Ramping Negative
VFB Ramping Positive
–7.5
7.5
VPGL
PGOOD Voltage Low
IPGOOD = 2mA
0.1
0.3
5
5.2
UNITS
%
%
V
INTVCC Linear Regulator
VINTVCC
Internal VCC Voltage
6V < VIN < 28V, ICC = 0mA
VLDOINT
INTVCC Load Regulation
ICC = 0mA to 100mA
VEXTVCC
EXTVCC Switchover Voltage
VLDOEXT
EXTVCC Voltage Drop
VLDOHYS
EXTVCC Hysteresis
Float
MODE/PLLIN
EXTVCC Ramping Positive
4.8
1
l
4.5
ICC = 20mA, VEXTVCC = 5V
V
%
4.7
30
V
75
200
mV
mV
Oscillator and Phase-Locked Loop
fSYNC
SYNC Capture Range
Clock Input Duty Cycle = 50%
250
fS
Switching Frequency
VFREQ/PLLLPF = INTVCC
700
RMODE/PLLIN
MODE/PLLIN Input Resistance
750
kHz
825
kHz
250
VIH(MODE/PLLIN) Clock Input Level High
kΩ
2.0
V
VIL(MODE/PLLIN) Clock Input Level Low
0.8
Clock Phase
VOUT2 to VOUT1 Phase
VOUT3 to VOUT2 Phase
VOUT1 to VOUT3 Phase
VFREQ/PLLLPF = 1.2V (Note 3)
VTEMP1,2
Temperature Diode Forward Voltage
ITEMP = 100µA
TC VTEMP
Temperature Coefficient
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The LTM4634 is tested under pulsed load conditions such that
TJ ≈ TA. The LTM4634E is guaranteed to meet performance specifications
over the 0°C to 125°C internal operating temperature range. Specifications
over the –40°C to 125°C internal operating temperature range are assured
by design, characterization and correlation with statistical process
controls. The LTM4634I is guaranteed to meet specifications over the
–40°C to 125°C internal operating temperature range. Note that the
maximum ambient temperature consistent with these specifications is
determined by specific operating conditions in conjunction with board
layout, the rated package thermal resistance and other environmental
factors.
4
750
120
120
120
V
Deg
Deg
Deg
0.598
V
–2.0
mV/°C
Note 3: 100% tested at wafer level.
Note 4: See output current derating curves for different VIN, VOUT and TA.
Note 5: High duty designs need to be validated based on maximum
temperature rise and derating in ambient conditions.
4634f
For more information www.linear.com/LTM4634
LTM4634
Typical Performance Characteristics
5V Input Efficiency (Ch3)
5V Input Efficiency (Ch1 and Ch2)
12V Input Efficiency (Ch1 and Ch2)
100
95
100
95
90
90
90
85
85
80
85
70
65
5V TO 1.0V EFF (250kHz)
5V TO 1.2V EFF (250kHz)
5V TO 1.5V EFF (250kHz)
5V TO 1.8V EFF (250kHz)
5V TO 2.5V EFF (250kHz)
5V TO 3.3V EFF (250kHz)
60
55
50
45
40
0
95
75
70
65
5V TO 1.OV EFF (250kHz)
5V TO 1.2V EFF (250kHz)
5V TO 1.5V EFF (250kHz)
5V TO 1.8V EFF (250kHz)
5V TO 2.5V EFF (250kHz)
5V TO 3.3V EFF (250kHz)
60
55
50
45
40
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
0
0.5
1.0
1.5 2.0 2.5 3.0
LOAD CURRENT (A)
3.5
4634 G01
80
75
70
12V Input Efficiency (Ch3)
60
55
50
45
40
4.0
24V Input Efficiency (Ch1 and Ch2)
24V Input Efficiency (Ch3)
95
85
80
65
60
55
50
45
40
0
0.5
1.0
1.5 2.0 2.5 3.0
LOAD CURRENT (A)
3.5
4.0
80
75
70
VEXTVCC = 5V
24V TO 1.0V EFF (250kHz)
24V TO 1.2V EFF (250kHz)
24V TO 1.5V EFF (300kHz)
24V TO 1.8V EFF (350kHz)
24V TO 2.5V EFF (350kHz)
24V TO 3.3V EFF (600kHz)
24V TO 5.0V EFF (750kHz)
65
60
55
50
45
40
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 G04
EFFICIENCY (%)
90
85
EFFICIENCY (%)
90
85
80
VEXTVCC = 5V
12V TO 1.0V EFF (250kHz)
12V TO 1.2V EFF (250kHz)
12V TO 1.5V EFF (250kHz)
12V TO 1.8V EFF (250kHz)
12V TO 2.5V EFF (250kHz)
12V TO 3.3V EFF (250kHz)
12V TO 5.0V EFF (250kHz)
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
100
95
90
70
0
4634 G03
100
75
VEXTVCC = 5V
12V TO 1.0V EFF (250kHz)
12V TO 1.2V EFF (250kHz)
12V TO 1.5V EFF (250kHz)
12V TO 1.8V EFF (250kHz)
12V TO 2.5V EFF (250kHz)
12V TO 3.3V EFF (250kHz)
12V TO 5.0V EFF (250kHz)
65
4634 G02
100
95
EFFICIENCY (%)
EFFICIENCY (%)
80
75
EFFICIENCY (%)
EFFICIENCY (%)
100
75
VEXTVCC = 5V
24 TO 1.0V EFF (250kHz)
24 TO 1.2V EFF (250kHz)
24 TO 1.5V EFF (250kHz)
24 TO 1.8V EFF (300kHz)
24 TO 2.5V EFF (300kHz)
24 TO 3.3V EFF (350kHz)
24 TO 5.0V EFF (500kHz)
24 TO 12V EFF (750kHz)
70
65
60
55
50
45
40
0
1.0
1.5 2.0 2.5 3.0
LOAD CURRENT (A)
4.0
3.5
4634 G06
4634 G05
24V Input Continuous, PulseSkipping and Burst Mode Operation
0.5
24V to 5V Load Step Response
24V to 3.3V Load Step Response
100
95
90
EFFICIENCY (%)
85
80
75
70
OUTPUT
100mV/DIV
OUTPUT
100mV/DIV
LOAD
STEP
1A/DIV
LOAD
STEP
1A/DIV
65
60
55
5.0VOUT (750kHz) BURST
5.0VOUT (750kHz) PULSE
5.0VOUT (750kHz) CONT
50
45
40
0
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
4634 G08
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
4634 G09
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 G07
4634f
For more information www.linear.com/LTM4634
5
LTM4634
Typical Performance Characteristics
24V to 12V Load Step Response
12V to 1.2V Load Step Response
12V to 1V Load Step Response
OUTPUT
100mV/DIV
OUTPUT
50mV/DIV
OUTPUT
50mV/DIV
LOAD
STEP
1A/DIV
LOAD
STEP
1A/DIV
LOAD
STEP
1A/DIV
4634 G10
100µs/DIV
0A TO 2A, 2A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
AND 100µF 16V 16TQC100MYF POS CAPACITOR
4634 G11
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
AND 470µF 2V 2TPE470MAJB POS CAPACITOR
12V to 1.5V Load Step Response
12V to 1.8V Load Step Response
OUTPUT
50mV/DIV
LOAD
STEP
1A/DIV
4634 G12
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
AND 470µF 2V 2TPE470MAJB POS CAPACITOR
12V to 2.5V Load Step Response
OUTPUT
50mV/DIV
OUTPUT
50mV/DIV
LOAD
STEP
1A/DIV
LOAD
STEP
1A/DIV
4634 G13
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
AND 470µF 2V 2TPE470MAJB POS CAPACITOR
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
24V to 5V No Load Start-Up
24V to 5V Full Load Start-Up
100µs/DIV
0A TO 2.5A, 2.5A/µs LOAD STEP
COUT = 2 × 100µF CERAMIC CAPACITOR
4634 G14
24V to 5V No Load Short
VOUT
1V/DIV
VOUT
1V/DIV
VOUT
2V/DIV
IOUT
1A/DIV
IOUT
1A/DIV
IIN
1A/DIV
20ms/DIV
VIN = 24V
VOUT = 5V
IOUT = 0A
COUT = 2 × 100µF X5R 1210
6
4634 G16
20ms/DIV
VIN = 24V
VOUT = 5V
IOUT = 5A
COUT = 2 × 100µF X5R 1210
4634 G15
4634 G17
20µs/DIV
VIN = 24V
VOUT = 5V
IOUT = 0A
COUT = 2 × 100µF X5R 1210
4634 G18
4634f
For more information www.linear.com/LTM4634
LTM4634
Typical Performance Characteristics
24V to 5V Full Load Short
Start-Up into Pre-Bias
RUN
5V/DIV
VOUT
2V/DIV
VOUT
RIPPLE
10mV/DIV
VOUT1
1V/DIV
IIN
1A/DIV
SW NODE
5V/DIV
SW
10V/DIV
20µs/DIV
VIN = 24V
VOUT = 5V
IOUT = 5A
COUT = 2 × 100µF X5R 1210
4634 G19
Steady-State Output Ripple
4634 G20
20ms/DIV
PREBIAS 1.5V OUTPUT STARTING AT 0.5V BIAS
12V INPUT
2µs/DIV
12V TO 3.3V AT 5A LOAD
4634 G21
Pin Functions
PACKAGE ROW AND COLUMN LABELING MAY VARY
AMONG µModule PRODUCTS. REVIEW EACH PACKAGE
LAYOUT CAREFULLY.
GND (A4, A8-A9, D1- D12, E1-E12, F4, F8, F12, G3-G4,
G7-G8, G11-G12, H3-H4, H7-H8, H11-H12, J1-J5, J7,
J9-J12, K1-K3, K8-K10, K12,L1-L2,L12, M1, M6-M8,
M12): Ground Pins for Both Input and Output Returns.
All ground pins need to connect with large copper areas
underneath the unit.
VOUT1, VOUT2, VOUT3 (A10-A12, B9-B12, and C10-C12);
(A5-A7, B5-B8, C6-C8); (A1-A3, B1-B4, C1-C4): Power
Output Pins. Apply output load between these pins and
the GND pins. Recommend placing output decoupling
capacitance directly between these pins and the GND
pins. See Table 4.
TEMP1 AND TEMP2 (C9, C5): Two Onboard Temperature
Diodes for Monitoring the VBE Junction Voltage Change
with Temperature. Each of these two temperature diode
connected PNP transistors is placed in the middle of
channel 1 and channel 2, and in the middle of channel 2
and channel 3. See the Applications Information section
and an example in Figure 25. Leave floating if not used.
VIN1,VIN2,VIN3 (F9-F10,G9-G10,H9-H10);(F5-F6,G5G6,H5-H6);(F1-F2,G1-G2,H1-H2): Power Input Pins.
Apply input voltage between these pins and the GND pins.
Recommend placing input decoupling capacitance directly
between the VIN pins and the GND pins. The VIN paths
can be all combined from one power source, or powered
from independent power sources. See the Applications
Information section.
SW1 (F11), SW2 (F7), SW3 (F3): The internal switch
node for each of the regulator channels for monitoring
the switching waveform. An R-C snubber circuit can be
placed on these pins to ground to eliminate switch node
ringing noise.
CNTL_PWR (J6): Input Supply to an Internal Bias LDO to
Power the Internal Controller and MOSFET Drivers. The
operating voltage range is 4.75V to 28V under all conditions. If the voltage at CNTL_PWR is ≤5.8V, the INTVCC
pin should be tied to CNTL_PWR for optimum efficiency.
If the voltage at CNTL_PWR is >5.8V, leave INTVCC floating with the recommended decoupling capacitor. To
eliminate power loss in the onboard linear regulator and
improve efficiency connect a 5V supply at EXTVCC. Ensure
CNTL_PWR > EXTVCC at all times to avoid reverse polarity
on the internal bias LDO.
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7
LTM4634
Pin Functions
INTVCC (J8): Output of the Internal Bias LDO for Powering
Internal Control Circuitry. Connect a 4.7µF ceramic capacitor to ground for decoupling. If the voltage at CNTL_PWR
is ≤5.8V, tie the INTVCC pin to CNTL_PWR for optimum
efficiency. If the voltage at CNTL_PWR is >5.8V, leave
INTVCC floating. See the Applications Information section.
SGND (K6-K7, L6-L7): Signal Ground Connections. The
signal ground connection in the module is separated from
normal power ground (GND) by an internal 2.2Ω resistor.
This allows the designer to connect the signal ground pin
close to GND near the external output capacitors on the
regulator channel’s outputs. The entire internal small-signal
feedback circuitry is referenced to SGND, thus allowing
for better output regulation. See the recommended layout
in the Applications Information section.
EXTVCC (L3): External Bias Power Input. The internal bias
LDO is bypassed whenever the voltage at EXTVCC is above
4.7V. Never exceed 6V at this pin and ensure CNTL_PWR >
EXTVCC at all times to avoid reverse polarity on the internal
bias LDO. Connect a 1µF capacitor to ground when used
otherwise leave floating. Use a 5V bias or 5V output to
power this pin to improve efficiency.
FREQ/PLLLPF (L8): Frequency Set and PLL Lowpass Filter
Pin. This pin is driven with a DC voltage to set the operating frequency. The recommended operating frequency
will be supplied in the efficiency graphs for optimal performance. A specific frequency can be chosen as long as
the minimum on-time is not violated, and inductor ripple
current is optimized. When an external clock is used, then
the FREQ/PLLLPF pin must not be connected to any DC
voltage. The pin must be floating and will have the proper
internal compensation for the internal loop filter. See the
Applications Information section.
MODE/PLLIN (L9): Forced Continuous Mode, Burst Mode,
or Pulse-Skipping Mode Selection Pin and External Synchronization Input to Phase Detector Pin. Connect this pin
to SGND to force all channels into the continuous mode
of operation. Connect to INTVCC to enable pulse-skipping
mode of operation. Leave floating to enable Burst Mode
operation. A clock on the pin will force the controller into
continuous mode of operation and synchronize the internal
oscillator. See the Applications Information section.
8
RUN1, RUN2, RUN3 (L10, L11, K11): Run Control Inputs.
A voltage above 1.3V on any RUN pin turns on that particular channel. However, forcing any of these RUN pins
below 1.15V causes that channel to shut down. Each of
the RUN pins has an internal 10k resistor to ground. This
resistor can be used with an external pull-up resistor to
the input voltage to set a UVLO for that channel, or simply
to turn on the channel. The RUN pins have a maximum
voltage of 6V. See the Applications Information section.
PGOOD12, PGOOD3 (M2, M3): Output Voltage Power
Good Indicator for VOUT1 and VOUT2 Combined, and VOUT3
Separate. The open-drain logic output is pulled to ground
when the output voltage is not within ±7.5% of the regulation point.
COMP1, COMP2, COMP3 (M4, L4, K4): Current Control
Threshold and Error Amplifier Compensation Point. The
current comparator threshold increases with this control
voltage. The LTM4634 regulator channels are all internally
compensated for proper stability. COMP1 and COMP2 can
be tied together for PolyPhase 10A parallel operation. See
the Applications Information section.
VFB1, VFB2, VFB3 (M5, L5, K5): The Negative Input of the
Error Amplifier for Each of the Three Channels. Internally,
each of these pins is connected to their respective output
with a 60.4k precision resistor. Different output voltages
can be programmed with an additional resistor between
each individual VFB pin and ground. In PolyPhase operation,
tying the VFB1 and VFB2 pins together allows for parallel
operation up to 10A. See the Applications Information
section for details.
TK/SS1, TK/SS2, TK/SS3 (M9, M10, M11): Output Voltage
Tracking and Soft-Start Inputs. When one particular channel
is configured to be the master, a capacitor to ground at
this pin sets the ramp rate for the master channel’s output
voltage. When the channel is configured to be the slave,
the VFB voltage of the master channel is reproduced by a
resistor divider and applied to this pin. Internal soft-start
currents of 1.5μA are charging the soft-start capacitors.
In dual output (2 + 1) mode, TK/SS1 and TK/SS2 need to
be shorted externally.
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LTM4634
Block Diagram
INTERNAL BLOCK DIAGRAM
MODE/PLLIN
INTVCC
1µF
R1
150k
MTOP1
RRUN1
10k
MBOT1
0.1µF
COMP1
RFBHI1
60.4k
+
VFB1
COUT1
SGND
VFB1
RFB1
19.1k
LOCATED NEAR POWER STAGES
SGND
SGND
VOUT1
3.3V
5A
GND
INTERNAL
COMP
SGND
GND
VOUT1
TK/SS1
SS
CAP1
24V
CIN1
4.7µF
50V
SW1
1.5µH
RUN1 SGND
1µF
50V
2Ω
VIN1
FREQ/PLLLPF
INTERNAL
FILTER
24V
VIN(UVLO) =
(R1 + 10k)1.3V
10k
CNTL_PWR
SGND
TEMP1
PNP
INTVCC
R4
10k
VIN2
PGOOD12
1µF
INTVCC
MTOP2
4.7µF
5V
24V
MBOT2
R2
150k
100µF
50V
VOUT2
5V
5A
VOUT2
0.1µF
3-CHANNEL
POWER CONTROL
RUN2
+
SW2
1.5µH
EXTVCC
CIN3
4.7µF
50V
GND
RFBHI2
60.4k
GND
RRUN2
10k
+
COUT2
SGND
TK/SS2
SS
CAP2
SGND INTVCC
R5
10k
TEMP2
PNP
VFB2
LOCATED NEAR
POWER STAGES
PGOOD3
COMP2
VIN3
INTERNAL
COMP
1µF
24V
MTOP3
R3
150k
SGND
RUN3
MBOT3
0.1µF
RFBHI3
60.4k
GND
VFB3
COMP3
INTERNAL
COMP
CIN5
4.7µF
50V
GND
VOUT3
12V
4A
VOUT3
TK/SS3
SGND
SGND
SW3
3.3µH
RRUN3
10k
SS
CAP3
VFB2
RFB2
11.5k
SGND
2.2Ω
SGND
+
COUT3
SGND
VFB3
RFB3
4.32k
SGND
4634 F01
Figure 1. Simplified LTM4634 Block Diagram
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9
LTM4634
Operation
Power Module Description
The LTM4634 µModule regulator is a high performance
triple output nonisolated switching mode DC/DC power
supply. It can provide 5A/5A/4A outputs with a few external input and output capacitors. This module provides
precisely regulated output voltages programmable via
external resistors from 0.8V DC to 5.5V DC (VOUT1 and
VOUT2), and 0.8V DC to 13.5V DC (VOUT3). When applying control bias in the range from 4.75V to 5.8V, then
connect the bias to CNTL_PWR and INTVCC, otherwise
if >5.8V only the CNTL_PWR pin needs to be biased. The
typical application schematic is shown in Figure 22.
The LTM4634 has three integrated constant-frequency current mode regulators, power MOSFETs, power inductors,
and other supporting discrete components. The typical
switching frequency is 750kHz. For switching noisesensitive applications, it can be externally synchronized
from 250kHz to 750kHz. Operating frequency range will
be dependent upon specific VIN and VOUT requirements
as they pertain to minimum on-time and inductor ripple
current of less than 60% of the load current. See the Applications Information section.
With current mode control and internal feedback loop
compensation, the LTM4634 module has sufficient stability margins and good transient performance with a wide
range of output capacitors, even with all ceramic output
capacitors.
Current mode control provides cycle-by-cycle fast current
limit in an overcurrent condition. An internal overvoltage
monitor protects the output voltages in the event of an
overvoltage >10%. The top MOSFET is turned off and the
bottom MOSFET is turned on until the output overvoltage
10
is cleared. There are two temperatures monitors in the
LTM4634. TEMP1 monitors the close relative temperature of channels 1 and 2, and TEMP2 monitors the close
relative temperature of channels 2 and 3. The two diode
connected PNP transistors are grounded in the module
and can be used as general purpose temperature monitors
using a device that is designed to monitor the single-ended
connection.
Pulling any of the RUN pins below 1.15V forces that
regulator channel into a shutdown state. The TK/SS pins
are used for programming the output voltage ramp and
voltage tracking during start-up for each of the channels.
See the Applications Information section.
The LTM4634 is internally compensated to be stable over all
operating conditions. Table 4 provides a guideline for input
and output capacitances for several operating conditions.
The LTpowerCAD™ software tool is provided for transient
and stability analysis. The VFB pin is used to program the
output voltage with a single external resistor to ground.
Each of the channels, operate 120° phase shift for multiphase operation. VOUT1 and VOUT2 can be combined to
provide a single 10A output. The two channels will not be
operating 180° phase shift, but 120° phase when combined
for a 10A design. So the input RMS current may be higher
than a 180° phase shifted design. See the Applications
Information section for details.
High efficiency at light loads can be accomplished with
selectable Burst Mode operation using the MODE/PLLIN
pin. These light load features will accommodate battery
operation. Efficiency graphs are provided for light load operation in the Typical Performance Characteristics section.
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LTM4634
Applications Information
The typical LTM4634 application circuit is shown in Figure 22. External component selection is primarily determined by the maximum load current and output voltage.
Refer to Table 4 for specific external capacitor requirements
for particular applications.
VIN to VOUT Step-Down Ratios
There are restrictions in the VIN to VOUT step-down ratio
that can be achieved for a given input voltage. The VIN to
VOUT minimum dropout is a function of load current and
at very low input voltage and high duty cycle applications
output power may be limited as the internal top power
MOSFET is not rated for 5A operation at higher ambient
temperatures. At very low duty cycles the minimum 100ns
on-time must be maintained. See the Frequency Adjustment section and temperature derating curves.
Output Voltage Programming
The PWM controller has an internal 0.8V ±1% reference
voltage. As shown in the Block Diagram, a 60.4k precision internal feedback resistor connects the VOUT and VFB
pins together.
The output voltage will default to 0.8V with no feedback
resistor. Adding a resistor RFB from VFB to ground programs the output voltage:
 60.4k +RFB 
48.32k
VOUT = 0.8V • 
or RFB =

RFB
VOUT – 0.8


Table 1. VFB Resistor Table vs Various Output Voltages
VOUT(V)
0.8
1.0
1.2
1.5
1.8
2.5
3.3
5.0
12.0
RFB (kΩ) Open 243
121
69.8
48.7
28.7
19.1
11.5
4.32
In the parallel operation the following pins should be tied
together, VFB1 and VFB2 pins, COMP1 and COMP2 pins,
TK/SS1 and TK/SS2, and RUN1 and RUN2.
For parallel operation of VOUT1 and VOUT2, connect VFB1
and VFB2 together with a single resistor to ground whose
value is determined by:
60.4k
2
RFB =
VOUT
–1
0.8
Input Capacitors
The LTM4634 module should be connected to a low AC
impedance DC source. Additional input capacitors are
needed for the RMS input ripple current rating. The ICIN(RMS)
equation which follows can be used to calculate the input
capacitor requirement for each channel. Typically 4.7µF
to 10µF X7R ceramics are a good choice with RMS ripple
current ratings of ~2A each. A 47µF to 100µF surface mount
aluminum electrolytic capacitor can be used for more input
bulk capacitance. This bulk input capacitor is only needed
if the input source impedance is compromised by long
inductive leads, traces or not enough source capacitance.
If low impedance power planes are used, then this bulk
capacitor is not needed.
For a buck converter, the switching duty cycle can be
estimated as:
D=
VOUT
VIN
Without considering the inductor ripple current, for each
output, the RMS current of the input capacitor can be
estimated as:
ICIN(RMS) =
IOUT(MAX)
η%
• D• (1–D)
(1)
In the previous equation, η% is the estimated efficiency
of the power module in decimal form (0.nn) for a given
VOUT-to-VIN ratio.
The selection of CIN is simplified by the 3-phase architecture and its impact on the worst-case RMS current draw
occurs when only one channel is operating. This is true
when the three channels are powered from a common
VIN. The channel with the highest duty cycle D peaking at
0.5 and maximum load current needs to be used in the
above formula. This will give the maximum RMS capacitor
current requirement. Increasing the output current drawn
from the other channels will actually decrease the input
RMS ripple current from its maximum value. The out-ofphase technique typically reduces the input capacitor’s
RMS ripple current by a factor of 50% when compared to
a single phase power supply solution. If the three channels
are powered from independent input sources, then each
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11
LTM4634
Applications Information
of the input RMS current ratings will need to be calculated
specific to that channel.
Output Capacitors
The LTM4634 is designed for low output voltage ripple
noise. The bulk output capacitors defined as COUT are
chosen with low enough effective series resistance (ESR)
to meet the output voltage ripple and transient requirements. COUT can be a low ESR tantalum capacitor, low
ESR Polymer capacitor or ceramic capacitor. The typical
output capacitance range is from 200µF to 470µF. Additional
output filtering may be required by the system designer
if further reduction of output ripple or dynamic transient
spikes is required. Table 4 shows a matrix of different output
voltages and output capacitors to minimize the voltage
droop and overshoot during a 5A/µs transient. The table
optimizes total equivalent ESR and total bulk capacitance
to optimize the transient performance. Stability criteria
are considered in the Table 4 matrix, and LTpowerCAD is
available for stability analysis. LTpowerCAD can calculate
the output ripple reduction as the number of implemented
phases increases by N times.
Burst Mode Operation
The LTM4634 is capable of Burst Mode operation in
which the power MOSFETs operate intermittently based
on load demand, thus saving quiescent current. For applications where maximizing the efficiency at very light
loads is a high priority, Burst Mode operation should be
applied. To enable Burst Mode operation, simply float
the MODE/PLLIN pin. During Burst Mode operation, the
peak current of the inductor is set to approximately 30%
of the maximum peak current value in normal operation
even though the voltage at the COMP pin indicates a
lower value. The voltage at the COMP pin drops when
the inductor’s average current is greater than the load
requirement. As the COMP voltage drops below 0.5V, the
burst comparator trips, causing the internal sleep line to
go high and turn off both power MOSFETs.
In sleep mode, the internal circuitry is partially turned
off, reducing the quiescent current. The load current is
now being supplied from the output capacitors. When the
output voltage drops, causing COMP to rise, the internal
12
sleep line goes low, and the LTM4634 resumes normal
operation. The next oscillator cycle will turn on the top
power MOSFET and the switching cycle repeats.
Pulse-Skipping Mode Operation
In applications where low output ripple and high efficiency
at intermediate currents are desired, pulse-skipping
mode should be used. Pulse-skipping operation allows
the LTM4634 to skip cycles at low output loads, thus
increasing efficiency by reducing switching loss. Tying
the MODE/PLLINpin to INTVCC enables pulse-skipping
operation. With pulse-skipping mode at light load, the
internal current comparator may remain tripped for several
cycles, thus skipping operation cycles. This mode has
lower ripple than Burst Mode operation and maintains a
higher frequency operation than Burst Mode operation.
Forced Continuous Operation
In applications where fixed frequency operation is more
critical than low current efficiency, and where the lowest
output ripple is desired, forced continuous operation
should be used. Forced continuous operation can be
enabled by tying the MODE/PLLIN pin to ground. In this
mode, inductor current is allowed to reverse during low
output loads, the COMP voltage is in control of the current
comparator threshold throughout, and the top MOSFET
always turns on with each oscillator pulse. During start-up,
forced continuous mode is disabled and inductor current
is prevented from reversing until the LTM4634 output
voltage is in regulation.
Frequency Synchronization
The LTM4634 device operates up to 750kHz. It can also be
synchronized with an input clock that has a high level above
2V and a low level below 0.8V at the MODE/PLLIN pin. The
FREQ/PLLLPF pin must be floating when synchronized to
an incoming clock. Once the LTM4634 is synchronized to
an external clock frequency, it will always be running in
forced continuous operation. The synchronizing range is
from 250kHz to 750kHz. For VOUT1,2,3 ≤ 1.5V use 250kHz
to 300kHz, 1.5V ≤ VOUT1,2,3 ≤ 2.5V use 400kHz, 2.5V ≤
VOUT1,2,3 ≤ 5V use 600kHz. If VOUT3 is greater than 5V
up to 12V set the operating frequency to 750kHz. These
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LTM4634
Applications Information
24V input applications that convert to output voltages equal
to 5V (VOUT1,2) and up to 12V (VOUT3) will be required to
set the LTM4634 switching frequency to 750kHz. This is
required to maintain less than 60% inductor ripple current
at the higher output voltages. The 750kHz requirement
for these higher output conversions from 24V will limit
output voltages on other channels to be no lower than 1.5V
due to minimum on-time considerations. There is a way
around this issue by taking one of these outputs, either
5V or 12V, and using it as the source for the 0.8V to 1.5V
output. An example circuit is shown in Figure 26. 5V and
12V input conversions on all three channels can be operated at lower frequencies across the output ranges so that
minimum on-time is not an issue at low output voltages.
The minimum on-time equation on the next page can be
used to verify that no switching frequency is violating this
parameter. The equations for checking IRIPPLE %:
( VIN – VOUT ) VOUT = FREQ,
L •IRIPPLE • VIN
IRIPPLE
=I
%
CH#MaxLoad RIPPLE
This verifies that the operating frequencies are selected to
limit inductor ripple currents to be below 60% of maximum
load, where FREQ is selected frequency in Hertz, IRIPPLE
and maximum load current in amps, and L is inductance
in Henrys. Ch1, Ch2 L = 1.5µH, and Ch3 L = 3.3µH. Maximum load current IOUT1,2 = 5A, and IOUT3 = 4A, therefore
IRIPPLE should try to stay below 2.5A for Ch1, Ch2, and
2A for Ch3, except for 12V output. The efficiency curves
will show the recommended optimal operating frequency
for the different conversions
A DC voltage should be applied to the FREQ/PLLLPF pin
to set the operating frequency when clock synchronization is not used. Figure 2 shows the frequency selection
as a function of the applied DC voltage. This can be done
with a voltage divider from the INTVCC (5V) pin to SGND.
A 10k resistor can be selected as the bottom resistor. The
top resistor, RFREQ, can be determined by using equation:
RFREQ =
5V •10k
– 10k
FREQV
where FREQV is the voltage at the FREQ/PLLLPF pin in
Figure 2 that corresponds to a particular frequency. See
Figure 25 for an example.
800
700
FREQUENCY (kHz)
frequencies optimize efficiency, eliminate minimum ontime issues for less than 1V output, and control the inductor
ripple currents over the input and output voltage ranges.
600
500
400
300
200
0.5
1
1.5
2
FREQ/PLLLPF PIN VOLTAGE (V)
0
2.5
4634 F02
Figure 2. Relationship Between Oscillator Frequency
and Voltage at the FREQ/PLLLPF Pin
Parallel Channel Operation
For outputs that demand more than 5A of load current,
the LTM4634 device can parallel VOUT1 and VOUT2 to supply 10A of load current. The two channels will operate at
120° of phase shift. The input RMS ripple current can be
calculated using Equation 1. For example, 12V to 1.2V at
10A equates to duty cycle D = 0.1.
ICIN(RMS) =
10A
• 0.1• (1– 0.1)
0.85
ICIN(RMS) = 3.5ARMS, use 2 × 22µF 16V X5R or X7R ceramic
capacitors rated at 2ARMS each.
The LTM4634 regulators are inherently current mode
controlled devices, so the paralleling of VOUT1 and VOUT2
channels will have good current sharing. This will balance
the thermals in the design. Tie the COMP, VFB, TK/SS
and RUN pins together for these two channels to share
the current evenly. Figure 24 shows a schematic of the
parallel design.
Minimum On-Time
Minimum on-time, tON, is the smallest time duration that
any of the three regulator channels is capable of turning on
the top MOSFET. It is determined by internal timing delays,
and the gate charge required to turn on the top MOSFET.
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LTM4634
Applications Information
Low duty cycle applications may approach this minimum
on-time limit and care should be taken to ensure that:
VOUT
>t
VIN •FREQ ON(MIN)
If the duty cycle falls below what can be accommodated
by the minimum on-time, the controller will begin to skip
cycles. The output voltage will continue to be regulated, but
the output ripple and inductor ripple current will increase.
The minimum on-time can be increased by lowering the
switching frequency. A good rule of thumb is to use a
100ns on-time.
Output Voltage Tracking
Output voltage tracking can be programmed externally
using the TK/SS pins. The output can be tracked up and
down with another regulator. The master regulator’s output
is divided down with an external resistor divider that is the
same as the slave regulator’s feedback divider to implement coincident tracking. The LTM4634 uses an accurate
60.4k resistor internally for the top feedback resistor for
each channel. Figure 3 shows an example of coincident
tracking for VOUT1 and VOUT2. VOUT1 is the master and
VOUT2 is the slave:
 60.4k 
VSLAVE =  1+
V
R TA  TRACK

VTRACK is the track ramp applied to the slave’s track pin.
VTRACK has a control range of 0V to 0.8V, or the internal
reference voltage. When the master’s output is divided
down with the same resistor values used to set the slave’s
output, then the slave will coincident track with the master
until it reaches its final value. The master will continue to
its final value from the slave’s regulation point. Voltage
tracking is disabled when VTRACK is more than 0.8V. RTA in
Figure 3 will be equal to the RFB2 for coincident tracking.
The TK/SS pin of the master can be controlled by a capacitor placed on the master regulator TK/SS pin to ground. A
1.5µA current source will charge the TK/SS pin up to the
5.5V TO 16V
CIN4
22µF
16V
CIN3
22µF
16V
CIN2
22µF
16V
CIN1
22µF
16V
4.7µF
6.3V
VIN1
UVLO SET AT 4.7V ON RUN PINS.
RUN PINS CAN BE SEQUENCED OR
ENABLED FROM LOGIC CONTROL
SW1
VIN2
SW2
7.87k
FREQ/PLLLPF
COMP1
RUN1
COMP2
VOUT3
RTB 60.4k
RTA
121k
TK/SS1
PGOOD3
TK/SS2
TEMP1
VOUT1
TEMP2
VFB1
VFB1
COUT, SEE TABLE 5
SOFT-START MASTER
RAMP SET BY CSS3 OR
EXTERNAL RAMP
47pF
VFB1
1.5V
10k
PGOOD12
TK/SS3
CSS3
0.1µF
10k
COMP3
LTM4634
RUN3
60.4k
69.8k
SW3 INTVCC EXTVCC
MODE/PLLIN
RUN2
VOUT3
VIN3
CNTL_PWR
COUT1
220µF
VOUT2
VFB2
RFB1
69.8k
COUT4
220µF
1.2V
COUT2
220µF
VFB2
VOUT3
VFB3
RFB2
121k
GND SGND
4633 F03
RFB3
19.1k
47pF
COUT7
100µF
COUT5 VFB3
220pF 220µF
VFB2
VFB3
3.3V
MASTER
COUT8
100µF
Figure 3. Triple Outputs (1.5V and 1.2V) with Tracking and 3.3V
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LTM4634
Applications Information
reference voltage and then proceed up to INTVCC. After the
0.8V ramp, the TK/SS pin will no longer be in control, and
the internal voltage reference will control output regulation from the feedback divider. Foldback current limit is
disabled during this sequence of turn-on during tracking
or soft-starting. The TK/SS pins are pulled low when the
RUN pin is below 1.15V or INTVCC drops below 3.5V. The
total soft-start time can be calculated as:
 0.8V •CSS 
tSS = 
 1.5µA 
Regardless of the mode selected by the MODE/PLLIN pin,
the regulator channels will always start in pulse-skipping
mode up to TK/SS = 0.64V. Between TK/SS = 0.64V and
0.74V, it will operate in forced continuous mode and revert
to the selected mode once TK/SS > 0.74V. The output ripple
is minimized during the 100mV forced continuous mode
window ensuring a clean PGOOD signal.
When the channel is configured to track another supply,
the feedback voltage of the other supply is duplicated by
a resistor divider and applied to the TK/SS pin. Therefore,
the voltage ramp rate on this pin is determined by the ramp
rate of the other supply’s voltage. Note that the small softstart capacitor charging current is always flowing, producing a small offset error. To minimize this error, select the
tracking resistive divider value to be small enough to make
this error negligible. In order to track down another channel
or supply after the soft-start phase expires, the LTM4634 is
forced into continuous mode of operation as soon as VFB
is below the undervoltage threshold of 0.74V regardless of
the setting of the MODE/PLLIN pin. However, the LTM4634
should always be set in forced continuous mode tracking
down when there is no load. After TK/SS drops below 0.1V,
its channel will operate in discontinuous mode.
The master’s TK/SS pin slew rate is directly equal to the
master’s output slew rate in Volts/Time. The equation:
 MR 
R TB = 
• 60.4k
 SR 
where MR is the master’s output slew rate and SR is the
slave’s output slew rate in Volts/Time. When coincident
tracking is desired, then MR and SR are equal, thus RTB
is equal the 60.4k. RTA is derived from equation:
R TA =
0.8V
V
VFB
V
+ FB – TRACK
60.4k RFB
R TB
where VFB is the feedback voltage reference of the regulator, and VTRACK is 0.8V. Since RTB is equal to the 60.4k top
feedback resistor of the slave regulator in equal slew rate
or coincident tracking, then RTA is equal to RFB with VFB =
VTRACK. Therefore RTB = 60.4k, and RTA = 60.4k in Figure 3.
In ratiometric tracking, a different slew rate maybe desired
for the slave regulator. RTB can be solved for when SR is
slower than MR. Make sure that the slave supply slew
rate is chosen to be fast enough so that the slave output
voltage will reach it final value before the master output.
Power Good
The PGOOD12 pin is an open-drain pin that can be used
to monitor valid output voltage regulation for VOUT1 and
VOUT2, and PGOOD3 for monitoring VOUT3. These pins
monitor a ±7.5% window around the 0.8V feedback voltage on either VFB1,2,3 from the output regulation point. A
resistor can be pulled up to a particular supply voltage
no greater than 6V maximum for monitoring. Any of the
PGOOD pins are pulled low when the RUN pin of the corresponding channel is pulled low.
Overcurrent and Overvoltage Protection
Each of the regulator channels senses the peak inductor
current on a cycle-by-cycle basis in current mode operation. When current limit is reached the output voltage will
begin to fall and the internal current limit threshold will
begin fold back as the output voltage falls below 50% of
its value. Foldback current limit is disabled during startup or track-up. Under short-circuit condition at low duty
cycle operation, each of the regulator channels will begin
to skip cycles to limit the short-circuit current.
Overvoltage protection is implemented by monitoring
each one of the regulator’s VFB pins. When the VFB voltage exceeds ~7.5% of the 0.8V reference value, then an
4634f
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15
LTM4634
Applications Information
internal comparator monitor will turn off the top power
switch, and turn on the bottom power switch to protect the
load. If the top power switch faults as a short, then a fuse
or circuit breaker would be recommended to protect the
system. This is due to the top switch being shorted while
the bottom switch is turning on to protect the output from
over voltage. High currents will flow and could damage
the bottom switch.
switched current path. Usually a series R-C combination
is used called a snubber circuit. The resistor will dampen
the resonance and the capacitor is chosen to only affect
the high frequency ringing across the resistor.
Stability Compensation
If the stray inductance or capacitance can be measured
or approximated then a somewhat analytical technique
can be used to select the snubber values. The inductance
is usually easier to predict. It combines the PowerPath™
board inductance in combination with the MOSFET interconnect inductance.
The module has already been internally compensated for
all output voltages. Table 4 is provided for most application requirements with verified stability. LTpowerCAD is
available for other control loop optimization.
First the SW pin can be monitored with a wide bandwidth
scope with a high frequency scope probe. The ring frequency can be measured for its value. The impedance, Z,
can be calculated:
Z(L) = 2π • f • L
Run Enable
The RUN 1, 2, 3 pins have an enable threshold of 1.4V
maximum, typically 1.3V with 175mV of hysteresis. They
control the turn-on of their respective channel. There is
a 10k resistor on each pin to ground. The RUN pins can
be pulled up to VIN for 5V operation, or a resistor can be
placed on the pins and connected to VIN for higher than 5V
input. This resistor can be set along with the onboard 10k
resistor such that an undervoltage lockout (UVLO) level
can be programmed to shut down a particular regulator
channel if VIN falls below a set value. Use the equation:
R=
10k (UVLO – 1.3V )
1.3V
where R is the resistor from the RUN pin to VIN to set the
UVLO trip point. For example, if the UVLO point is to be
6.25V while operating at 12V input:
R=
10k ( 6.25V – 1.3V )
≈ 38k
1.3V
See the Block Diagram in Figure 1. The RUN pins must
never exceed 6V maximum voltage. The RUN pins have
to be pulled up to enable the regulators.
SW Pins
The SW pins are generally for testing purposes by monitoring the pin. The SW pin can also be used to dampen
out switch node ringing caused by LC parasitics in the
16
where f is the resonant frequency of the ring, and L is the
total parasitic inductance in the switch path. If a resistor
is selected that is equal to Z, then the ringing should be
dampened. The snubber capacitor value is chosen so that
its impedance is equal to the resistor at the ring frequency.
Calculated by:
Z(C) =
1
2π • f •C
these values are a good place to start with. Modification to
these components should be made to attenuate the ringing without lowering the regulator’s conversion efficiency.
INTVCC and EXTVCC
The LTM4634 has an onboard linear regulator fed by
CNTL_PWR which delivers a roughly 5V output at INTVCC
to power the internal controller and MOSFET drivers for all
three regulator channels. Apply a 4.7µF ceramic capacitor
between INTVCC and ground for decoupling. CNTL_PWR
requires a voltage between 4.75V to 28V. If the voltage
supplied to CNTL_PWR is ≤ 5.8V, connect INTVCC to
CNTL_PWR. Otherwise, INTVCC should be left floating.
To eliminate power loss in the onboard linear regulator
and improve efficiency connect a supply from 4.7V to 6V
at EXTVCC. Biasing EXTVCC at 5V will reduce the power
loss in the internal LDO by (VCNTL_PWR – 5V) • 90mA
and is recommended for VCNTRL_POWER ≥ 12V when all
three channels are operating. If EXTVCC is used add a 1µF
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LTM4634
Applications Information
ceramic capacitor to ground at EXTVCC and ensure the
voltage at CNTL_PWR is always greater than the voltage
at EXTVCC at all times during start-up and shutdown.
Connecting VOUT3 to EXTVCC may present a convenient
way to meet the sequencing requirement. Otherwise float
EXTVCC if not used.
Thermal Considerations and Output Current Derating
The thermal resistances reported in the Pin Configuration
section of the data sheet are consistent with those parameters defined by JESD51-12 and are intended for use with
finite element analysis (FEA) software modeling tools that
leverage the outcome of thermal modeling, simulation,
and correlation to hardware evaluation performed on a
µModule package mounted to a hardware test board.
The motivation for providing these thermal coefficients is
found in JESD51-12 (“Guidelines for Reporting and Using
Electronic Package Thermal Information”).
Many designers may opt to use laboratory equipment
and a test vehicle such as the demo board to predict the
µModule regulator’s thermal performance in their application at various electrical and environmental operating
conditions to compliment any FEA activities. Without FEA
software, the thermal resistances reported in the Pin Configuration section are, in and of themselves, not relevant
to providing guidance of thermal performance; instead,
the derating curves provided in the data sheet can be used
in a manner that yields insight and guidance pertaining to
one’s application usage, and can be adapted to correlate
thermal performance to one’s own application.
The Pin Configuration section gives four thermal coefficients explicitly defined in JESD51-12. These coefficients
are quoted or paraphrased as follows:
1. θJA: The thermal resistance from junction to ambient, is
the natural convection junction-to-ambient air thermal
resistance measured in a one cubic foot sealed enclosure. This environment is sometimes referred to as
“still air” although natural convection causes the air to
move. This value is determined with the part mounted
to a 95mm × 76mm PCB with four layers.
2. θJCbottom: The thermal resistance from the junction to
the bottom of the product case, is determined with all
of the internal power dissipation flowing through the
bottom of the package. In a typical µModule regulator,
the bulk of the heat flows out the bottom of the package, but there is always heat flow out into the ambient
environment. As a result, this thermal resistance value
may be useful for comparing packages but the test
conditions don’t generally match the user’s application.
3. θJCtop: The thermal resistance from junction to top of
the product case, is determined with nearly all of the
component power dissipation flowing through the top of
the package. As the electrical connections of the typical
µModule regulator are on the bottom of the package, it
is rare for an application to operate such that most of
the heat flows from the junction to the top of the part.
As in the case of θJCbottom, this value may be useful
for comparing packages but the test conditions don’t
generally match the user’s application.
4. θJB: The thermal resistance from junction to the printed
circuit board, is the junction-to-board thermal resistance
where almost all of the heat flows through the bottom
of the µModule package and into the board, and is really
the sum of the θJCbottom and the thermal resistance of
the bottom of the part through the solder joints and
through a portion of the board. The board temperature
is measured at a specified distance from the package.
A graphical representation of the aforementioned thermal resistances is given in Figure 4; blue resistances are
contained within the μModule regulator, whereas green
resistances are external to the µModule package.
As a practical matter, it should be clear to the reader that
no individual or sub-group of the four thermal resistance
parameters defined by JESD51-12 or provided in the Pin
Configuration section replicates or conveys normal operating conditions of a μModule regulator. For example, in
normal board-mounted applications, never does 100%
of the device’s total power loss (heat) thermally conduct exclusively through the top or exclusively through
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17
LTM4634
Applications Information
JUNCTION-TO-AMBIENT RESISTANCE COMPONENTS
CASE (TOP)-TO-AMBIENT
RESISTANCE
JUNCTION-TO-CASE (TOP)
RESISTANCE
JUNCTION
JUNCTION-TO-BOARD RESISTANCE
AMBIENT
JUNCTION-TO-CASE
CASE (BOTTOM)-TO-BOARD
(BOTTOM) RESISTANCE
RESISTANCE
BOARD-TO-AMBIENT
RESISTANCE
4633 F04
µMODULE DEVICE
Figure 4. Graphical Representations of JESD51-12 Thermal Coefficients
bottom of the µModule package—as the standard defines
for θJCtop and θJCbottom, respectively. In practice, power
loss is thermally dissipated in both directions away from
the package—granted, in the absence of a heat sink and
airflow; a majority of the heat flow is into the board.
Within the LTM4634, be aware there are multiple power
devices and components dissipating power, with a consequence that the thermal resistances relative to different
junctions of components or die are not exactly linear with
respect to total package power loss. To reconcile this
complication without sacrificing modeling simplicity—
but also, not ignoring practical realities—an approach
has been taken using FEA software modeling along with
laboratory testing in a controlled environment chamber
to reasonably define and correlate the thermal resistance
values supplied in this data sheet: (1) Initially, FEA software
is used to accurately build the mechanical geometry of
the LTM4634 and the specified PCB with all of the correct material coefficients along with accurate power loss
source definitions; (2) this model simulates a softwaredefined JEDEC environment consistent with JESD51-12
to predict power loss heat flow and temperature readings
at different interfaces that enable the calculation of the
JEDEC-defined thermal resistance values; (3) the model
and FEA software is used to evaluate the LTM4634 with heat
sink and airflow; (4) having solved for and analyzed these
thermal resistance values and simulated various operating
18
conditions in the software model, a thorough laboratory
evaluation replicates the simulated conditions with thermocouples within a controlled environment chamber while
operating the device at the same power loss as that which
was simulated. The outcome of this process and due
diligence yields the set of derating curves shown in this
data sheet.
After these laboratory tests have been performed and correlated to the LTM4634 model, then the θJB and θBA are
summed together to correlate quite well with the device
model conditions of no airflow or heat sinking in a properly
define chamber. This θJB + θBA value should accurately
equal the θJA value because approximately 100% of power
loss flows from the junction through the board into ambient with no air-flow or top mounted heat sink.
LTM4634 Thermal Considerations and Output Current
Derating
The power loss curves at 5V input, 12V input, and 24V input
are shown in Figures 8 to 13. These power loss curves
can be used in coordination with the load current derating
curves in Figures 14 to 21 for calculating an approximate
θJA thermal resistance for the LTM4634 with various heat
sinking and airflow conditions. The power loss curves
are taken at room temperature, and are increased with a
multiplicative factor of 1.4 at 120°C junction.
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LTM4634
Applications Information
The derating curves are plotted with the output current
starting at 15A (5A/CH) and the ambient temperature at
~40°C. The 15A comes from each of the three channels
operating at 5A each. This simplifies the loading for this
thermal testing. The output voltages are 3.3V, and 5V
when all three channels are loaded together in parallel.
Channel 1 and Channel 2 are designed to operate with
outputs up to 5V, and Channel 3 is designed for 12V. The
power loss curve values at a particular output voltage and
output current for each output are taken and multiplied by
1.4 for increased power loss at 120°C junction. Thermal
models are derived from several temperature measurements in a controlled temperature chamber along with
thermal modeling analysis. The junction temperatures
are monitored while ambient temperature is increased
with and without airflow. The power loss increase with
ambient temperature change is factored into the derating
curves. The junctions are maintained at 120°C maximum
while lowering output current or power with increasing
ambient temperature. The decreased output current will
decrease the internal module loss as ambient temperature is increased. The monitored junction temperature of
120°C minus the ambient operating temperature specifies
how much module temperature rise can be allowed. As
an example, in Figure 17 the 5.0V load current is derated
to ~12.6A at ~71°C with no air and with no heat sink. In
Figure 10, the 12V to 5.0V power loss at 4.2A per channel is 1.25W. The total loss would be 3 times 1.25W for
3.75W total power loss. The 3.75W is then multiplied by
the 1.4 multiplier for 120°C junction. This 5.25W value is
used with the total temperature rise of 120°C minus the
71°C ambient to calculate θJA thermal resistance. If the
71°C ambient temperature is subtracted from the 120°C
junction temperature, then the difference of 49°C divided
5.25W equals a 9.3°C/W θJA thermal resistance. Table 2
specifies a 9.0°C/W value which is very close. Tables 2
and 3 provide equivalent thermal resistances for 3.3V and
5V outputs with and without air flow and heat sinking. The
derived thermal resistances in Tables 2 and 3 for the various
conditions can be multiplied by the calculated power loss
as a function of the 120°C maximum junction temperature to determine if the temperature rise plus ambient is
below the 120°C maximum junction temperature. Thermal
measurements or infrared analysis should be performed
to validate the values. Ambient temperature power loss
can be derived from the power loss curves in Figures 8 to
13 and adjusted with the 1.4 multiplier. The printed circuit
board is a 1.6mm thick four-layer board with two ounce
copper for the two outer layers and 1 ounce copper for
the two inner layers. The PCB dimensions are 95mm ×
76mm. The BGA heat sinks are listed in Table 3.
Temperature Monitoring (TEMP1 and TEMP2)
Diode connected PNP transistors are used for the TEMP1,
TEMP2 monitoring function since the diode forward voltage
varies with temperature. The temperature dependence of
the diodes can be understood in the equation:
I 
VD = nVT ln  D 
 IS 
where VT is the thermal voltage (kT/q), and n, the ideality
factor, is 1 for the two diode connected PNPs being used
in the LTM4634. IS is expressed by the typical empirical
equation:
 –V 
IS =I0 exp  G0 
 VT 
where I0 is a process and geometry-dependent current (I0
is typically around 20 orders of magnitude larger than IS
at room temperature), and VG0 is the band gap voltage of
1.2V extrapolated to absolute zero or –273°C.
If we take the IS equation and substitute into the VD equation, then we get:
kT
 kT   I 
VD = VG0 –   ln  0  , VT =
 q   ID 
q
The expression shows that the diode voltage decreases
(linearly if I0 were constant) with increasing temperature
and constant diode current. Figure 5 shows a plot of VD
vs Temperature over the operating temperature range of
the LTM4634.
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19
LTM4634
Applications Information
If we take this equation and differentiate it with respect to
temperature T, then:
0.8
ID = 100µA
This dVD/dT term is the temperature coefficient equal to
about –2mV/K or –2mV/°C. The equation is simplified for
the first order derivation.
Solving for T, T = –(VG0 – VD)/(dVD/dT) provides the
temperature.
1st Example: Figure 5 for 27°C, or 300K the diode
voltage is 0.598V, thus, 300K = –(1200mV – 598mV)/
–2.0 mV/K)
DIODE VOLTAGE (V)
0.7
V –V
dVD
= – G0 D
dT
T
0.6
0.5
0.4
0.3
–50
–25
50
25
0
75
TEMPERATURE (°C)
100
125
4634 F05
Figure 5. Diode Voltage VD vs Temperature T(°C)
2nd Example: Figure 5 for 75°C, or 350K the diode
voltage is 0.50V, thus, 350K = –(1200mV – 500mV)/
–2.0mV/K)
Converting the Kelvin scale to Celsius is simply taking the
Kelvin temp and subtracting 273 from it.
A typical forward voltage is given in the electrical characteristics section of the data sheet, and Figure 5 is the plot
of this forward voltage. Measure this forward voltage at
27°C to establish a reference point. Then using the above
expression while measuring the forward voltage over
temperature will provide a general temperature monitor.
Connect resistors between TEMP1, TEMP2 and VIN to set
the currents to 100µA each. See Figure 25 for an example.
Safety Considerations
The LTM4634 module does not provide galvanic isolation
from VIN to any of the three VOUTs. There is no internal
fuse. If required, a slow blow fuse with a rating higher
than the maximum input current can be used to protect
the unit in case of a catastrophic failure. An inline circuit
breaker function can also be used instead of a fuse.
The fuse or circuit breaker should be selected to limit the
current to the regulator during overvoltage in case of an
internal top MOSFET fault. If the internal top MOSFET fails,
then turning it off will not resolve the overvoltage, thus
20
Figure 6. Thermal Plot 24V to 3.3V at 5A, 5V at 5A, and 12V
at 4A, Airflow = 200LFM, Ambient = 25°C
the internal bottom MOSFET will turn on indefinitely trying
to protect the load. Under this fault condition, the input
voltage will source very large currents to ground through
the failed internal top MOSFET and enabled internal bottom MOSFET. This can cause excessive heat and board
damage depending on how much power the input voltage
can deliver to this system. A fuse or circuit breaker can
be used as a secondary fault protector in this situation.
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LTM4634
Applications Information
Layout Checklist/Example
Place a dedicated power ground layer underneath the unit.
To minimize the via conduction loss and reduce module
thermal stress, use multiple vias for interconnection between top layer and other power layers.
The high integration of LTM4634 makes the PCB board
layout very simple and easy. However, to optimize its electrical and thermal performance, some layout considerations
are still necessary.
Do not put vias directly on the pads, unless they are capped
or plated over. Use a separated SGND ground copper area
for components connected to signal pins. Connect the
SGND to GND underneath the unit. Bring out test points
on the signal pins for monitoring. Figure 7 gives a good
example of the recommended layout.
Use large PCB copper areas for high current paths, including VIN, GND, VOUT1, VOUT2, and VOUT3. It helps to
minimize the PCB conduction loss and thermal stress.
Place high frequency ceramic input and output capacitors
next to the VIN, GND and the VOUT pins to minimize high
frequency noise.
CONTROL
RFB1
M
GND
CIN3
FARSIDE COMPONENTS
RFB1, RFB2, RFB3
CONTROL
GND
RFB2
L
CINTVCC
K
J
FARSIDE COMPONENTS
CIN1, CIN2
CIN2
H
VIN3
GND
RFB3
CIN1
G
COUT6
GND
F
COUT4
E
GND
FARSIDE COMPONENTS
COUT4, COUT5, COUT6
D
C
B
COUT1
A
VOUT3
2
3
4
5
6
7
8
9
GND
VOUT2
10
11
12
VOUT1
COUT5
1
“A1” INDICATOR
COUT2
VOUT3
COUT3
GND
VOUT1
4634 F07
LTM4634Y BGA TOP VIEW
Figure 7. Recommended PCB Layout
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21
LTM4634
1.4
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
5V TO 3.3V POWER
LOSS CURVE
5V TO 2.5V POWER
LOSS CURVE
5V TO 1.8V POWER
LOSS CURVE
5V TO 1.5V POWER
LOSS CURVE
5V TO 1.2V POWER
LOSS CURVE
5V TO 1V POWER
LOSS CURVE
POWER LOSS (W)
POWER LOSS (W)
Applications Information
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
1.4
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
5V TO 3.3V POWER
LOSS CURVE
5V TO 2.5V POWER
LOSS CURVE
5V TO 1.8V POWER
LOSS CURVE
5V TO 1.5V POWER
LOSS CURVE
5V TO 1.2V POWER
LOSS CURVE
5V TO 1V POWER
LOSS CURVE
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 F09
4634 F08
1.6
1.5
1.4
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
Figure 9. 5V Input Power Loss (Ch3)
12V TO 5V POWER
LOSS CURVE
12V TO 3.3V POWER
LOSS CURVE
12V TO 2.5V POWER
LOSS CURVE
12V TO 1.8V POWER
LOSS CURVE
12V TO 1.5V POWER
LOSS CURVE
12V TO 1.2V POWER
LOSS CURVE
12V TO 1V POWER
LOSS CURVE
POWER LOSS (W)
POWER LOSS (W)
Figure 8. 5V Input Power Loss
(Ch1 and Ch2)
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
1.8
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
12V TO 5V POWER
LOSS CURVE
12V TO 3.3V POWER
LOSS CURVE
12V TO 2.5V POWER
LOSS CURVE
12V TO 1.8V POWER
LOSS CURVE
12V TO 1.5V POWER
LOSS CURVE
12V TO 1.2V POWER
LOSS CURVE
12V TO 1V POWER
LOSS CURVE
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 F11
4634 F10
Figure 11. 12V Power Loss (Ch3)
Figure 10. 12V Input Power Loss
(Ch1 and Ch2)
2.4
2.4
24V TO 5V POWER
LOSS CURVE
24V TO 3.3V POWER
LOSS CURVE
24V TO 2.5V POWER
LOSS CURVE
24V TO 1.8V POWER
LOSS CURVE
24V TO 1.5V POWER
LOSS CURVE
24V TO 1.2V POWER
LOSS CURVE
24V TO 1V POWER
LOSS CURVE
POWER LOSS (W)
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
24V TO 12V POWER
LOSS CURVE
24V TO 5V POWER
LOSS CURVE
24V TO 3.3V POWER
LOSS CURVE
24V TO 2.5V POWER
LOSS CURVE
24V TO 1.8V POWER
LOSS CURVE
24V TO 1.5V POWER
LOSS CURVE
24V TO 1.2V POWER
LOSS CURVE
24V TO 1V POWER
LOSS CURVE
2.2
2.0
POWER LOSS (W)
2.2
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
LOAD CURRENT (A)
4634 F12
4634 F12
Figure 12. 24V Power Loss
(Ch1 and Ch2)
22
Figure 13. 24V Power Loss (Ch3)
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LTM4634
16
16
14
14
14
12
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
2
0
0
20
40
60
12
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
2
80
100
0
120
TOTAL OUTPUT CURRENT (A)
16
TOTAL OUTPUT CURRENT (A)
TOTAL OUTPUT CURRENT (A)
Applications Information
0
40
20
TEMPERATURE (°C)
60
10
8
6
4
80
100
0
120
14
12
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
60
12
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
2
80
100
0
120
TOTAL OUTPUT CURRENT (A)
14
TOTAL OUTPUT CURRENT (A)
14
40
0
20
TEMPERATURE (°C)
40
60
80
100
14
TOTAL OUTPUT CURRENT (A)
TOTAL OUTPUT CURRENT (A)
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
0
20
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
40
40
60
4634 F18
14
20
6
0
120
60
100
120
120
12
10
8
6
4
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
0
0
20
TEMPERATURE (°C)
40
60
80
100
120
TEMPERATURE (°C)
4634 F20
Figure 20. 24VIN, 5V, with Heat
Sink, All Channels at 5A Each
100
Figure 19. 24VIN, 3.3V, without
Heat Sink, All Channels at 5A Each
2
80
80
4634 F19
Figure 18. 24VIN, 3.3V, with Heat
Sink, All Channels at 5A Each
16
0
8
TEMPERATURE (°C)
16
0
10
2
4634 F17
12
120
12
TEMPERATURE (°C)
Figure 17. 12VIN, 5V, without Heat
Sink, All Channels at 5A Each
2
100
4634 F16
16
20
80
Figure 16. 12VIN, 5V, with Heat
Sink, All Channels at 5A Each
16
0
60
4634 F15
Figure 15. 12VIN, 3.3VOUT, without
Heat Sink, All Channels at 5A Each
16
0
40
20
0
TEMPERATURE (°C)
4634 F14
2
0 LFM AIR FLOW
200 LFM AIR FLOW
400 LFM AIR FLOW
2
TEMPERATURE (°C)
Figure 14. 12VIN, 3.3VOUT, with Heat
Sink, All Channels at 5A Each
TOTAL OUTPUT CURRENT (A)
12
4634 F21
Figure 21. 24VIN, 5V, without Heat
Sink, All Channels at 5A Each
4634f
For more information www.linear.com/LTM4634
23
LTM4634
Applications Information
Table 2. 3.3V Output
DERATING CURVE
VIN (V)
POWER LOSS CURVE
AIR FLOW (LFM)
HEAT SINK
Figures 15, 19
Figures 15, 19
Figures 15, 19
Figures 14, 18
Figures 14, 18
Figures 14, 18
12, 24
12, 24
12, 24
12, 24
12, 24
12, 24
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
0
200
400
0
200
400
None
None
None
BGA Heat Sink
BGA Heat Sink
BGA Heat Sink
DERATING CURVE
VIN (V)
POWER LOSS CURVE
AIR FLOW (LFM)
HEAT SINK
Figures 17, 20
Figures 17, 20
Figures 17, 20
Figures 16, 21
Figures 16, 21
Figures 16, 21
12, 24
12, 24
12, 24
12, 24
12, 24
12, 24
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
Figures 8 to 13
0
200
400
0
200
400
None
None
None
BGA Heat Sink
BGA Heat Sink
BGA Heat Sink
θJA (°C/W)
9.0
7.5
6.5
9.0
6.5
6.0
Table 3. 5V Output
θJA (°C/W)
9.0
7.5
6.5
9.0
6.5
6.0
Heat Sink Manufacturer Part Number Website
Aavid Thermalloy
375424B00034G
www.aavid.com
Cool Innovations
4-050503P to
4-050508P
www.coolinnovations.com
24
4634f
For more information www.linear.com/LTM4634
LTM4634
Applications Information
Table 4. Output Voltage Response Versus Component Matrix
(Refer to Figure 26) 0 to 2.5A Load Step Typical Measured Values
COUT CERAMIC
VENDORS
VALUE
PART NUMBER
Murata
220µF, 4V, X5R 1206 Case Size
GRM31CR60G277M
TDK
100µF, 6.3V, X5R 1210 Case Size C3225X5R0J107M
Murata
22µF, 25V, X7R, 1210 Case Size
GRM32ER71E226K
Panasonic
Poscap
100µF, 16V, D2 Case Size
16TQC100M
150µF, 16V, D3L Case Size
16TQC100M
Murata
4.7µF, 50V
GRU55ER71H475K
10µF, 50V
GRM32ER71H06KA12L
VOUT1,
CIN
CIN
COUT1
COUT2
VOUT2 (CERAMIC) (BULK)* (CERAMIC) (BULK)
CFF
CBOT CCOMP VIN
PEAK-TO-PEAK
DEVIATION AT RECOVERY
DROP 2.5A LOAD STEP
TIME
LOAD
STEP
RFB
FREQ
1V
22µF × 3
150µF
100µF × 2
None
47pF None None
12V
50mV
100mV
90µs
2.5A/µs
243kΩ
500kHz
1V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V
40mV
80mV
90µs
2.5A/µs
243kΩ
500kHz
1.2V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V
48mV
96mV
90µs
2.5A/µs
121kΩ
500kHz
1.5V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V
50mV
100mV
100µs
2.5A/µs 69.8kΩ
500kHz
1.8V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V
50mV
100mV
100µs
2.5A/µs 48.7kΩ
500kHz
2.5V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V
75mV
150mV
100µs
2.5A/µs 28.7kΩ
500kHz
2.5V
22µF × 3
150µF
220µF × 3
None
47pF None None
12V
70mV
140mV
100µs
2.5A/µs 28.7kΩ
500kHz
3.3V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V 100mV
200mV
120µs
2.5A/µs 19.1kΩ
500kHz
3.3V
22µF × 3
150µF
220µF × 2
None
47pF None None
12V 100mV
200mV
120µs
2.5A/µs 19.1kΩ
750kHz
3.3V
22µF × 3
150µF
220µF × 3
None
47pF None None
12V
90mV
180mV
120µs
2.5A/µs 19.1kΩ
500kHz
3.3V
22µF × 3
150µF
100µF × 2
None
47pF None None
12V 100mV
200mV
120µs
2.5A/µs 19.1kΩ
750kHz
5V
22µF × 3
150µF
100µF × 2
None
47pF None None
12V 170mV
340mV
100µs
2.5A/µs 11.5kΩ
750kHz
5V
22µF × 3
150µF
100µF × 3
None
47pF None None
12V 140mV
280mV
100µs
2.5A/µs 11.5kΩ
750kHz
CIN**
CIN
COUT1
COUT2
VOUT3 (CERAMIC) (BULK)* (CERAMIC) (BULK)
5
None
4.7µF × 3 150µF 100µF × 2
CFF
CBOT CCOMP VIN
PEAK-TO-PEAK
DEVIATION AT RECOVERY
DROP 2.5A LOAD STEP
TIME
LOAD
STEP
RFB
FREQ
47pF None None
24V 170mV
340mV
120µs
2.5A/µs 11.5kΩ
600kHz
47pF None None
24V 140mV
280mV
120µs
2.5A/µs 11.5kΩ
600kHz
150µF
100µF × 1 100µF × 1 47pF None None
24V 120mV
240mV
120µs
2.5A/µs 11.5kΩ
600kHz
150µF
22µF × 1 100µF × 1 47pF None None
24V 120mV
240mV
120µs
2.5A/µs 11.5kΩ
600kHz
5
4.7µF × 3
150µF
100µF × 3
5
4.7µF × 3
5
4.7µF × 3
None
5
4.7µF × 3
150µF
22µF × 2 100µF × 1 47pF None None
24V 120mV
240mV
120µs
2.5A/µs 11.5kΩ
600kHz
5
4.7µF × 3
150µF
22µF × 1 100µF × 1 47pF None None
24V 110mV
220mV
120µs
2.5A/µs 11.5kΩ
600kHz
24V 110mV
220mV
120µs
2.5A/µs 11.5kΩ
600kHz
24V 300mV
600mV
200µs
2.5A/µs 4.32kΩ
600kHz
5
4.7µF × 3
150µF
22µF × 2 100µF × 1 47pF None None
12
4.7µF × 3
150µF
22µF × 2
None
47pF None None
12
None
4.7µF × 3
150µF
22µF × 3
47pF None None
24V 300mV
600mV
200µs
2.5A/µs 4.32kΩ
600kHz
12
4.7µF × 3
150µF
22µF × 1 100µF × 1 47pF None None
24V 250mV
500mV
200µs
2.5A/µs 4.32kΩ
600kHz
12
4.7µF × 3
150µF
22µF × 2 100µF × 1 47pF None None
24V 240mV
480mV
200µs
2.5A/µs 4.32kΩ
600kHz
12
4.7µF × 3
150µF
22µF × 1 100µF × 1 47pF None None
24V 230mV
460mV
200µs
2.5A/µs 4.32kΩ
600kHz
12
4.7µF × 3
150µF
22µF × 2 100µF × 1 47pF None None
24V 220mV
440mV
200µs
2.5A/µs 4.32kΩ
600kHz
*Bulk capacitor is optional if VIN has very low input impedance. Slew rate: 2.5A/µs. **50V
For more information www.linear.com/LTM4634
4634f
25
LTM4634
Typical Applications
100µF
50V
+
5V
24V INPUT
CIN4
4.7µF
50V
CIN1
4.7µF
50V
CIN2
4.7µF
50V
CIN3
4.7µF
50V
4.7µF
6.3V
VIN1
2Ω
VIN2
SW3 INTVCC EXTVCC
VIN3
FREQ/PLLLPF
MODE/PLLIN
COMP1
RUN1
COMP2
RUN2
50k
TK/SS1
PGOOD3
TK/SS2
TEMP1
VOUT1
TEMP2
VFB1
VOUT2
VFB2
VFB1
47pF
COUT2
100µF
6.3V
VOUT3
47pF
VFB2
COUT4
100µF
6.3V
COUT3
100µF
6.3V
GND SGND
4634 F22
VFB3
RFB2
11.5k
COUT9
22µF
16V
47pF
VFB3
5V
3.3V
VFB3
VFB2
RFB1
19.1k
FOR COUT, RFB, COMP AND CFF
SEE TABLE 4
VFB1
10k
PGOOD12
TK/SS3
CSS3
0.1µF
10k
COMP3
LTM4634
RUN3
CSS2
0.1µF
SW2
CNTL_PWR
1µF
CSS1
0.1µF
SW1
RFB3
4.32k
COUT7
22µF
16V
12V
COUT5
22µF
6.3V
COUT8
22µF
16V
Figure 22. LTM4634 Typical 24V Input to 3.3V at 5A, 5V at 5A, 12V at 4A
26
4634f
For more information www.linear.com/LTM4634
LTM4634
Typical Applications
24V
CIN1
4.7µF
50V
+
CIN2
4.7µF
50V
56µF
50V
12V
CIN5
22µF
16V
CIN6
22µF
16V
5V
CIN8
22µF
6.3V
CIN9
22µF
6.3V
VIN1
SW1
VIN2
SW2
SW3 INTVCC EXTVCC
VIN3
FREQ/PLLLPF
CNTL_PWR
5V INPUT
120k
CSS1
0.1µF
50k
12V INPUT
CSS2
0.1µF
MODE/PLLIN
COMP1
RUN1
COMP2
RUN2
CSS3
0.1µF
PGOOD3
TK/SS2
TEMP1
TEMP2
TK/SS3
VFB1
VOUT2
VFB2
VFB1
COUT2
220µF
4V
VFB2
GND SGND
4634 F23
VFB3
RFB3
19.1k
COUT4
220µF
4V
2.5V
VFB3
RFB2
69.8k
COUT1
220µF
4V
47pF
VOUT3
VFB2
RFB1
28.7k
VFB1
4.7µF
6.3V
PGOOD12
TK/SS1
VOUT1
10k
COMP3
LTM4634
RUN3
10k
COUT7
100µF
6.3V
1.5V
3.3V
COUT5
220µF
47pF
4V
COUT8
100µF
47pF 6.3V
VFB3
Figure 23. LTM4634 Triple Input and Triple Output (2.5V, 1.5V and 3.3V) at 5A, 5A and 4A
4634f
For more information www.linear.com/LTM4634
27
LTM4634
Typical Applications
24V INPUT
CIN6
4.7µF
50V
12VOUT AT 1.2A
CIN4
22µF
16V
24V
5V BIAS
VIN1
CSS1
0.22µF
SW1
120k
SW2
VIN3
FREQ/PLLLPF
COMP1
RUN1
RUN2
COMP2
PGOOD3
TK/SS2
TEMP1
TEMP2
TK/SS3
VFB1
VFB1
47pF
COUT1
100µF
6.3V
1V
10k
PGOOD12
TK/SS1
COUT, SEE TABLE 4
RFB1 = (60.4k/2)/(VOUT/0.8) – 1
10k
COMP3
LTM4634
VOUT1
4.7µF
SW3 INTVCC EXTVCC
MODE/PLLIN
RUN3
CSS3
0.1µF
VFB1
VIN2
CNTL_PWR
1µF
24V
56µF
50V
CIN3
22µF
16V
2Ω
10k
+
CIN7
4.7µF
50V
VOUT2
RFB1
121k
COUT2
100µF
6.3V
VFB2
VOUT3
VFB3
VFB3
COUT4
100µF
6.3V
COUT7
22µF
16V
COUT5
100µF
6.3V
COUT8
22µF
16V
47pF
GND SGND
4634 F24
RFB3
4.32k
VFB3
COUT3
100µF
6.3V
COUT6
100µF
6.3V
12VOUT
1V AT 10A
12V AT 2.8A
FOR OTHER CIRCUITS
Figure 24. 24V to 12V at 2.8A, Then 12V to 1V at 10A
28
4634f
For more information www.linear.com/LTM4634
LTM4634
Typical Applications
7V TO 28V INPUT
+
56µF
50V
CIN3
4.7µF
50V
CIN1
4.7µF
50V
CIN2
4.7µF
50V
5V BIAS
2Ω
VIN1
3.3V
6.04k
6.98k
3.3V
SW2
FREQ/PLLLPF
COMP1
RUN1
COMP2
PGOOD3
TK/SS2
TEMP1
TK/SS3
TEMP2
VFB1
COUT1
100µF
6.3V
REDUCED TRACKING FEEDBACK
DIVIDER BY A FACTOR OF 10 TO
REDUCE TK/SS CURRENT ERROR
VOUT2
RFB1
69.8k
VFB2
COUT2
100µF
6.3V
RFB2
48.7k
10k
VOUT3
VFB3
COUT3
3.3V 100µF
6.3V
VIN
RT
GND SGND
RFB3
19.1k
TO ADC
VIN
RT
4634 F25
1.5V
COUT4
100µF
6.3V
1.8V
COUT6
100µF
6.3V
10k
PGOOD12
TK/SS1
VOUT1
10k
COMP3
LTM4634
RUN3
CSS3
0.22µF
35.7k
(400kHz)
SW3 INTVCC EXTVCC
VIN3
MODE/PLLIN
RUN2
6.04k
4.87k
VIN2
CNTL_PWR
1µF
13.3k
SW1
4.7µF
6.3V
COUT7
100µF
6.3V
RT =
TO ADC
VIN
100µA
Figure 25. 7V to 28V Input, 1.5V, 1.8V and 3.3V at 5A,5A, 4A with Tracking
4634f
For more information www.linear.com/LTM4634
29
LTM4634
Package Description
LTM4634 Component BGA Pinout
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
A1
VOUT3
B1
VOUT3
C1
VOUT3
D1
GND
E1
GND
F1
VIN3
A2
VOUT3
B2
VOUT3
C2
VOUT3
D2
GND
E2
GND
F2
VIN3
A3
VOUT3
B3
VOUT3
C3
VOUT3
D3
GND
E3
GND
F3
SW3
A4
GND
B4
VOUT3
C4
VOUT3
D4
GND
E4
GND
F4
GND
A5
VOUT2
B5
VOUT2
C5
TEMP2
D5
GND
E5
GND
F5
VIN2
A6
VOUT2
B6
VOUT2
C6
VOUT2
D6
GND
E6
GND
F6
VIN2
A7
VOUT2
B7
VOUT2
C7
VOUT2
D7
GND
E7
GND
F7
SW2
A8
GND
B8
VOUT2
C8
VOUT2
D8
GND
E8
GND
F8
GND
A9
GND
B9
VOUT1
C9
TEMP1
D9
GND
E9
GND
F9
VIN1
A10
VOUT1
B10
VOUT1
C10
VOUT1
D10
GND
E10
GND
F10
VIN1
A11
VOUT1
B11
VOUT1
C11
VOUT1
D11
GND
E11
GND
F11
SW1
A12
VOUT1
B12
VOUT1
C12
VOUT1
D12
GND
E12
GND
F12
GND
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
PIN ID
FUNCTION
G1
VIN3
H1
VIN3
J1
GND
K1
GND
L1
GND
M1
GND
G2
VIN3
H2
VIN3
J2
GND
K2
GND
L2
GND
M2
PGOOD12
G3
GND
H3
GND
J3
GND
K3
GND
L3
EXTVCC
M3
PGOOD3
G4
GND
H4
GND
J4
GND
K4
COMP3
L4
COMP2
M4
COMP1
G5
VIN2
H5
VIN2
J5
GND
K5
VFB3
L5
VFB2
M5
VFB1
G6
VIN2
H6
VIN2
J6
CNTL_PWR
K6
SGND
L6
SGND
M6
GND
G7
GND
H7
GND
J7
GND
K7
SGND
L7
SGND
M7
GND
G8
GND
H8
GND
J8
INTVCC
K8
GND
L8
FREQ/PLLLPF
M8
GND
G9
VIN1
H9
VIN1
J9
GND
K9
GND
L9
MODE/PLLIN
M9
TK/SS1
G10
VIN1
H10
VIN1
J10
GND
K10
GND
L10
RUN1
M10
TK/SS2
G11
GND
H11
GND
J11
GND
K11
RUN3
L11
RUN2
M11
TK/SS3
G12
GND
H12
GND
J12
GND
K12
GND
L12
GND
M12
GND
Package Photo
30
4634f
For more information www.linear.com/LTM4634
aaa Z
0.630 ±0.025 Ø 144x
E
PACKAGE TOP VIEW
3.1750
3.1750
SUGGESTED PCB LAYOUT
TOP VIEW
1.9050
0.0
0.6350
0.0000
0.6350
4
1.9050
PIN “A1”
CORNER
6.9850
5.7150
4.4450
4.4450
5.7150
6.9850
Y
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection
of its circuits
as described
herein will not infringe on existing patent rights.
For more
information
www.linear.com/LTM4634
6.9850
5.7150
4.4450
3.1750
1.9050
0.6350
0.0000
0.6350
1.9050
3.1750
4.4450
5.7150
6.9850
X
D
aaa Z
// bbb Z
SYMBOL
A
A1
A2
b
b1
D
E
e
F
G
H1
H2
aaa
bbb
ccc
ddd
eee
H1
SUBSTRATE
A1
NOM
5.01
0.60
4.41
0.75
0.63
15.00
15.00
1.27
13.97
13.97
0.41
4.00
A
MAX
5.21
0.70
4.51
0.90
0.66
NOTES
DETAIL B
PACKAGE SIDE VIEW
A2
0.46
4.05
0.15
0.10
0.20
0.30
0.15
TOTAL NUMBER OF BALLS: 144
0.36
3.95
MIN
4.81
0.50
4.31
0.60
0.60
b1
DIMENSIONS
ddd M Z X Y
eee M Z
DETAIL A
Øb (144 PLACES)
DETAIL B
H2
MOLD
CAP
ccc Z
Z
(Reference LTC DWG # 05-08-1908 Rev Ø)
BGA Package
144-Lead (15mm × 15mm × 5.01mm)
Z
e
12
11
10
9
7
6
5
PACKAGE BOTTOM VIEW
8
4
b
3
2
1
DETAIL A
DETAILS OF PIN #1 IDENTIFIER ARE OPTIONAL,
BUT MUST BE LOCATED WITHIN THE ZONE INDICATED.
THE PIN #1 IDENTIFIER MAY BE EITHER A MOLD OR
MARKED FEATURE
4
7
TRAY PIN 1
BEVEL
!
PACKAGE IN TRAY LOADING ORIENTATION
µModule
LTMXXXXXX
A
B
C
D
E
F
G
H
J
K
L
M
7
SEE NOTES
PIN 1
BGA 144 0613 REV Ø
PACKAGE ROW AND COLUMN LABELING MAY VARY
AMONG µModule PRODUCTS. REVIEW EACH PACKAGE
LAYOUT CAREFULLY
6. SOLDER BALL COMPOSITION IS 96.5% Sn/3.0% Ag/0.5% Cu
5. PRIMARY DATUM -Z- IS SEATING PLANE
BALL DESIGNATION PER JESD MS-028 AND JEP95
3
2. ALL DIMENSIONS ARE IN MILLIMETERS
NOTES:
1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M-1994
COMPONENT
PIN “A1”
3
SEE NOTES
F
b
e
G
LTM4634
Package Description
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
4634f
31
LTM4634
Typical Application
24V INPUT
CIN6
4.7µF
50V
5VOUT AT 3A
24V
CIN3
22µF
6.3V
5VOUT
VIN1
2Ω
CSS1
0.1µF
SW1
VIN2
SW2
VIN3
120k
MODE/PLLIN
COMP1
RUN1
RUN2
COMP2
PGOOD3
TEMP1
10k
10k
RUN3
PGOOD12
TK/SS2
TEMP2
TK/SS3
VFB1
VOUT2
VFB2
VOUT3
VFB3
VFB1
COUT
SEE TABLE 4
10k
COMP3
LTM4634
TK/SS1
VOUT1
30k
FREQ/PLLLPF
RUN3
CSS3
0.1µF
4.7µF
SW3 INTVCC EXTVCC
CNTL_PWR
1µF
24V
56µF
50V
COUT1
220µF
4V
RFB1
60.4k
COUT2
220µF
4V
COUT7
100µF
6.3V
COUT4
220µF
4V
GND SGND
4634 F26
VFB3
RFB3
11.5k
+
CIN4
22µF
6.3V
+
CIN7
4.7µF
50V
COUT5
220µF
4V
COUT8
22µF
6.3V
1.2V
47pF
47pF
VFB1
VFB3
5VOUT
5V AT 1A
FOR OTHER CIRCUITS
Figure 26. 24V to 5V at 1A, Then 5V Output to 1.2V at 10A
Related Parts
PART NUMBER DESCRIPTION
COMMENTS
LTM4633
Triple 10A, 16VIN Step-Down DC/DC µModule 4.7V ≤ VIN ≤ 16V, 0.8V ≤ VOUT1,2 ≤ 1.8V, 0.8V ≤ VOUT3 ≤ 5.5V, PLL Input, VOUT Soft-Start
Regulator
and Tracking, PGOOD, Internal Temperature Monitor, 15mm × 15mm × 5.01mm BGA
LTM4630
Dual 15VIN, 18A or Single 36A Step-Down
µModule Regulator with VOUT Up to 1.8V
LTM4644
Quad 4A, 14V Step-Down µModule Regulator 4V ≤ VIN ≤ 14V, 0.6V ≤ VOUT ≤ 5.5V, CLK Input and Output, VOUT Tracking, PGOOD,
9mm × 15mm × 5.01mm BGA
with Configurable Output Array
LTM4676
Dual 13A or Single 26A µModule Regulator
with Digital Power System Management
4.5V ≤ VIN ≤ 26V, 0.5V ≤ VOUT0 ≤ 4.0V, 0.5V ≤ VOUT1 ≤ 5.4V, Digital I/F for Control and
Monitoring, Integrated 16-Bit ADC, PMBus Compliant I2C Interface, Remote Sense
Amplifiers, 16mm × 16mm × 5.01mm BGA
LTM8028
36VIN, UltraFast™, Low Output Noise 5A
µModule Regulator
6V ≤ VIN ≤ 36V, 0.8V ≤ VOUT ≤ 1.8V Set Via 3-Pin Three-State Interface, <1mV VOUT
Ripple, 10% Accurate Current Limit, PGOOD, 15mm × 15mm × 4.9mm BGA
LTM4637
20VIN, 20A DC/DC µModule Step-Down
Regulator
4.5V ≤ VIN ≤ 20V, 0.6V ≤ VOUT ≤ 5.5V, PLL Input, VOUT Tracking, Remote Sense Amplifier,
PGOOD, 15mm × 15mm × 4.32mm LGA and 15mm × 15mm × 4.92mm BGA
LTM8045
Inverting or SEPIC _Module DC/DC Converter 2.8V ≤ VIN ≤ 18V, ±2.5V ≤ VOUT ≤ ±15V, Synchronizable, No Derating or Logic-Level Shift
for Control Inputs When Inverting, 6.25mm × 11.25mm × 4.92mm BGA
with Up to 700mA Output Current
LTC2977
8-Channel PMBus Power System Manager
0.25% TUE 16-Bit ADC, Voltage/Temperature Monitoring and Supervision
LTC2974
4-Channel PMBus Power System Manager
0.25% TUE 16-Bit ADC, Voltage/Current/Temperature Monitoring and Supervision
32
4.5V ≤ VIN ≤ 15V, 0.6V ≤ VOUT ≤ 1.8V, PLL Input, Remote Sense Amplifier, VOUT Tracking,
PGOOD, CLKOUT, Internal Temperature Monitor, 16mm × 16mm × 4.41mm LGA
4634f
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
For more information www.linear.com/LTM4634
(408) 432-1900 ● FAX: (408) 434-0507
●
www.linear.com/LTM4634
LT 0814 • PRINTED IN USA
 LINEAR TECHNOLOGY CORPORATION 2014
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