AD ADP1173 Micropower dc-dc converter Datasheet

Micropower
DC-DC Converter
ADP1173
a
FEATURES
Operates From 2.0 V to 30 V Input Voltages
Only 110 mA Supply Current (Typical)
Step-Up or Step-Down Mode Operation
Very Few External Components Required
Low Battery Detector On-Chip
User-Adjustable Current Limit
Internal 1 A Power Switch
Fixed or Adjustable Output Voltage Versions
8-Pin DIP or SO-8 Package
FUNCTIONAL BLOCK DIAGRAMS
SET
ADP1173
VIN
The ADP1173 is part of a family of step-up/step-down switching
regulators that operates from an input supply voltage of as little as
2 V to 12 V in step-up mode and to 30 V in step-down mode.
The ADP1173 consumes as little as 110 µA in standby mode,
making it ideal for applications that need low quiescent current.
An auxiliary gain amplifier can serve as a low battery detector,
linear regulator (under voltage lockout) or error amplifier.
GAIN BLOCK/
ERROR AMP
ILIM
SW1
1.245V
REFERENCE
A1
OSCILLATOR
DRIVER
COMPARATOR
APPLICATIONS
Notebook and Palmtop Computers
Cellular Telephones
Flash Memory Vpp Generators
3 V to 5 V, 5 V to 12 V Converters
9 V to 5 V, 12 V to 5 V Converters
Portable Instruments
LCD Bias Generators
GENERAL DESCRIPTION
AO
A2
GND
SW2
FB
SET
ADP1173-3.3
ADP1173-5
ADP1173-12
AO
A2
VIN
GAIN BLOCK/
ERROR AMP
1.245V
REFERENCE
R1
SW1
A1
OSCILLATOR
COMPARATOR
DRIVER
SW2
ADP1173-3.3: R1 = 456kΩ
ADP1173-5: R1 = 250kΩ
ADP1173-12: R1 = 87.4kΩ
R2
753kΩ
GND
ILIM
SENSE
The ADP1173 can deliver 80 mA at 5 V from a 3 V input in
step-up configuration or 100 mA at 5 V from a 12 V input in
step-down configuration. For input voltages of less than 2 V use
the ADP1073.
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
World Wide Web Site: http://www.analog.com
Fax: 617/326-8703
© Analog Devices, Inc., 1997
ADP1173–SPECIFICATIONS (@ T = 08C to +708C, V
A
Model
Symbol
Conditions
QUIESCENT CURRENT
IQ
IN
= 3 V unless otherwise noted)
Typ
Max
Units
Switch Off
110
150
µA
QUIESCENT CURRENT, BOOST MODE IQ
CONFIGURATION
No Load, TA = +25°C
ADP1173-3.3
ADP1173-5
ADP1173-12
135
135
250
INPUT VOLTAGE
Step-Up Mode
Step-Down Mode
2.0
ADP11731
1.20
ADP1173-3.32
ADP1173-52
ADP1173-122
3.14
4.75
11.4
VIN
COMPARATOR TRIP POINT VOLTAGE
OUTPUT SENSE VOLTAGE
VOUT
Min
µA
µA
µA
12.6
30
V
V
1.245
1.30
V
3.30
5.00
12.0
3.46
5.25
12.6
V
V
V
COMPARATOR HYSTERESIS
ADP1173
5
12
mV
OUTPUT HYSTERESIS
ADP1173-3.3
ADP1173-5
ADP1173-12
13
20
50
35
55
100
mV
mV
mV
16
24
32
kHz
Full Load
43
55
63
%
ILIM Tied to VIN
15
23
32
µs
OSCILLATOR FREQUENCY
fOSC
DUTY CYCLE
SWITCH ON TIME
tON
FEEDBACK PIN BIAS CURRENT
ADP1173, VFB = 0 V
60
290
nA
SET PIN BIAS CURRENT
VSET = VREF
70
150
nA
ISINK = 100 µA, VSET = 1.00 V
0.15
0.4
V
2.0 V ≤ VIN ≤ 5 V
5 V ≤ VIN ≤ 30 V
0.2
0.02
0.4
0.075
%/V
%/V
VIN = 3.0 V, ISW = 650 mA
VIN = 5.0 V, ISW = 1 A,
TA = +25°C
VIN = 5.0 V, ISW = 1 A
0.5
0.85
V
0.8
1.0
1.4
V
V
1.1
1.5
1.7
V
V
GAIN BLOCK OUTPUT LOW
VOL
REFERENCE LINE REGULATION
SWSAT VOLTAGE, STEP-UP MODE
SWSAT VOLTAGE, STEP-DOWN MODE
GAIN BLOCK GAIN
VSAT
VSAT
AV
VIN = 12 V, TA = +25°C,
ISW = 650 mA
VIN = 12 V, ISW = 650 mA
RL = 100 kΩ3
220 Ω from ILIM to VIN
TA = +25°C
CURRENT LIMIT
CURRENT LIMIT TEMPERATURE
COEFFICIENT
SWITCH-OFF LEAKAGE CURRENT
MAXIMUM EXCURSION BELOW GND
VSW2
400
1000
V/V
400
mA
–0.3
%/°C
Measured at SW1 Pin
TA = +25°C
1
10
µA
ISW1 ≤ 10 µA, Switch Off
TA = +25°C
–400
–350
mV
NOTES
1
This specification guarantees that both the high and low trip points of the comparator fall within the 1.20 V to 1.30 V range.
2
The output voltage waveform will exhibit a sawtooth shape due to the comparator hysteresis. The output voltage on the fixed output versions will always be within
the specified range.
3
100 kΩ resistor connected between a 5 V source and the AO pin.
Specifications subject to change without notice.
–2–
REV. 0
ADP1173
ABSOLUTE MAXIMUM RATINGS*
PIN CONFIGURATIONS
Supply Voltage (VIN) . . . . . . . . . . . . . . . . . . . . . . . . . . . . 36 V
SW1 Pin Voltage (VSW1) . . . . . . . . . . . . . . . . . . . . . . . . . 50 V
SW2 Pin Voltage (VSW2) . . . . . . . . . . . . . . . . . . –0.5 V to VIN
Feedback Pin Voltage (ADP1173) . . . . . . . . . . . . . . . . . . . 5 V
Sense Pin Voltage (ADP1173, –3.3, –5, –12) . . . . . . . . . 36 V
Maximum Power Dissipation . . . . . . . . . . . . . . . . . . 500 mW
Maximum Switch Current . . . . . . . . . . . . . . . . . . . . . . . .1.5 A
Operating Temperature Range . . . . . . . . . . . . . 0°C to +70°C
Storage Temperature Range . . . . . . . . . . . . . –65°C to 150°C
Lead Temperature, (Soldering, 10 sec) . . . . . . . . . . . . +300°C
*Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum
ratings for extended periods of time may affect device reliability.
N-8
8-Lead Plastic DIP
ILIM
1
VIN
2
ADP1173
Output
Voltage
Package
Options*
ADP1173AN
ADP1173AR
ADP1173AN-3.3
ADP1173AR-3.3
ADP1173AN-5
ADP1173AR-5
ADP1173AN-12
ADP1173AR-12
ADJ
ADJ
3.3 V
3.3 V
5V
5V
12 V
12 V
N-8
SO-8
N-8
SO-8
N-8
SO-8
N-8
SO-8
+
+5V
OUTPUT
AT 100mA
56Ω
470µF
4X NICAD
OR
ALKALINE
CELLS
1
2
ILIM
VIN
470kΩ
SET
GND
5
+
AO 6
+
470µF
2
ADP1173 7 SET
SW1
3
TOP VIEW
(Not to Scale)
4
5 GND
*FIXED VERSIONS
8 FB (SENSE)*
6 AO
5 GND
SW2 4
*FIXED VERSIONS
PIN FUNCTION DESCRIPTIONS
Mnemonic
Function
ILIM
For normal conditions this pin is connected to
VIN. When lower current is required, a resistor
should be connected between ILIM and VIN.
Limiting the switch current to 400 mA is
achieved by connecting a 220 Ω resistor.
VIN
Input Voltage.
SW1
Collector Node of Power Transistor.
For step-down configuration, connect to VIN;
for step-up configuration, connect to an
inductor/diode.
SW2
Emitter Node of Power Transistor. For stepdown configuration, connect to inductor/
diode; for step-up configuration, connect to
ground. Do not allow this pin to drop more
than a diode drop below ground.
GND
Ground.
AO
Auxiliary Gain (GB) Output. The open
collector can sink 100 µA.
SET
Gain Amplifier Input. The amplifier has
positive input connected to the SET pin and
negative input is connected to 1.245 V
reference.
FB/SENSE
On the ADP1173 (adjustable) version this pin
is connected to the comparator input. On the
ADP1173-3.3, ADP1173-5 and ADP1173-12,
the pin goes directly to the internal application
resistor that sets the output voltage.
470µF
SW2 FB 8
4
1
VIN
SW2
75kΩ
SW1 3
ADP1173
7
IRF7203
ILIM
7 SET
TOP VIEW
3 (Not to Scale) 6 AO
*N = Plastic DIP, SO = Small Outline Package.
L1*
100µH
8 FB (SENSE)*
SW1
ORDERING GUIDE
Model
SO-8
8-Lead Plastic SO
240Ω
24kΩ
*L1 = COILTRONICS CTX100-4
Figure 1. Step-Up or Step-Down Converter
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the ADP1173 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
REV. 0
–3–
WARNING!
ESD SENSITIVE DEVICE
ADP1173 –Typical Performance Characteristics
1.2
1.6
VIN = 3V
0.6
VIN = 5V
0.4
0.2
900
SWITCH CURRENT – mA
VIN = 2V
0.8
1000
VCE(SAT)
1.2
SWITCH ON VOLTAGE – V
VCE (SAT) – V
1.0
1100
1.4
1.0
0.8
0.6
0.4
700
600
500
400
300
0.2
0
0.4
0.6
0.8
1.0
SWITCH CURRENT – A
1.2
Figure 2. Saturation Voltage vs.
Switch Current in Step-Up Mode
VIN =24V WITH L = 500µH @ VOUT = 5V
120
110
500
400
300
VIN =12V WITH L = 250µH @ VOUT = 5V
100
70
60
50
30
20
0
1000
RLIM – Ω
Figure 5. Maximum Switch Current
vs. RLIM in Step-Down Mode
25.5
80
25
70
24.5
24
23.5
23
OSCILLATOR FREQUENCY
22.5
22
3
5
20
25
10
15
INPUT VOLTAGE – Volts
30
Figure 8. Oscillator Frequency vs.
Input Voltage
0
QUIESCENT CURRENT
100
90
80
70
60
40
–40
100 200 300 400 500 600 700 800 900
SWITCH CURRENT – mA
0
25
70
85
TEMPERATURE – °C
Figure 7. Quiescent Current vs.
Temperature
450
60
VIN = 3V
50
40
30
20
10
–40
1000
50
Figure 6. Supply Current vs.
Switch Current
SET PIN BIAS CURRENT – nA
OSCILLATOR FREQUENCY – kHz
VIN = 2V
10
0
100
21.5
VIN = 5V
40
FEEDBACK PIN BIAS CURRENT – nA
200
80
100
RLIM – Ω
Figure 4. Maximum Switch Current
vs. RLIM in Step-Up Mode
90
SUPPLY CURRENT – mA
SWITCH CURRENT – mA
600
100
10
0.75
100
800
700
0.15 0.25 0.35 0.45 0.55 0.65
SWITCH CURRENT – A
Figure 3. Switch ON Voltage vs.
Switch Current in Step-Down Mode
1000
900
200
0.0
0.05
QUIESCENT CURRENT – µA
0.2
2V < VIN < 5V
800
0
25
70
85
TEMPERATURE – °C
Figure 9. Set Pin Bias Current vs.
Temperature
–4–
400
350
300
250
200
VIN = 3V
150
100
50
0
–40
0
25
70
85
TEMPERATURE – °C
Figure 10. Feedback Pin Bias Current
vs. Temperature
REV. 0
ADP1173
APPLICATIONS
Theory of Operation
COMPONENT SELECTION
General Notes on Inductor Selection
The ADP1173 is a flexible, low power switch mode power
supply (SMPS) controller. The regulated output voltage can be
greater than the input voltage (boost or step-up mode) or less
than the input (buck or step-down mode). This device uses a
gated-oscillator technique to provide very high performance
with low quiescent current.
When the ADP1173 internal power switch turns on, current
begins to flow in the inductor. Energy is stored in the inductor
core while the switch is on, and this stored energy is then
transferred to the load when the switch turns off. Both the
collector and the emitter of the switch transistor are accessible
on the ADP1173, so the output voltage can be higher, lower or
of opposite polarity than the input voltage.
A functional block diagram of the ADP1173 is shown on the
front page. The internal 1.245 V reference is connected to one
input of the comparator, while the other input is externally
connected (via the FB pin) to a feedback network connected to
the regulated output. When the voltage at the FB pin falls below
1.245 V, the 24 kHz oscillator turns on. A driver amplifier provides base drive to the internal power switch, and the switching
action raises the output voltage. When the voltage at the FB pin
exceeds 1.245 V, the oscillator is shut off. While the oscillator is
off, the ADP1173 quiescent current is only 110 µA. The comparator includes a small amount of hysteresis, which ensures
loop stability without requiring external components for frequency compensation.
The maximum current in the internal power switch can be set
by connecting a resistor between VIN and the ILIM pin. When the
maximum current is exceeded, the switch is turned OFF. The
current limit circuitry has a time delay of about 2 µs. If an
external resistor is not used, connect ILIM to VIN. Further
information on ILIM is included in the Limiting the Switch
Current section of this data sheet.
The ADP1173 internal oscillator provides 23 µs ON and 19 µs
OFF times, which is ideal for applications where the ratio
between VIN and VOUT is roughly a factor of two (such as
converting +3 V to + 5 V). However, wider range conversions
(such as generating +12 V from a +5 V supply) can easily be
accomplished.
An uncommitted gain block on the ADP1173 can be connected
as a low battery detector. The inverting input of the gain block
is internally connected to the 1.245 V reference. The noninverting input is available at the SET pin. A resistor divider, connected between VIN and GND with the junction connected to
the SET pin, causes the AO output to go LOW when the low
battery set point is exceeded. The AO output is an open
collector NPN transistor which can sink 100 µA.
The ADP1173 provides external connections for both the
collector and emitter of its internal power switch, which permits
both step-up and step-down modes of operation. For the stepup mode, the emitter (pin SW2) is connected to GND and the
collector (pin SW1) drives the inductor. For step-down mode,
the emitter drives the inductor while the collector is connected
to VIN.
The output voltage of the ADP1173 is set with two external
resistors. Three fixed-voltage models are also available:
ADP1173-3.3 (+3.3 V), ADP1173-5 (+5 V) and ADP1173-12
(+12 V). The fixed-voltage models are identical to the ADP1173,
except that laser-trimmed voltage-setting resistors are included
on the chip. On the fixed-voltage models of the ADP1173,
simply connect the feedback pin (Pin 8) directly to the output
voltage.
REV. 0
To specify an inductor for the ADP1173, the proper values of
inductance, saturation current and dc resistance must be
determined. This process is not difficult, and specific equations
for each circuit configuration are provided in this data sheet. In
general terms, however, the inductance value must be low
enough to store the required amount of energy (when both
input voltage and switch ON time are at a minimum) but high
enough that the inductor will not saturate when both VIN and
switch ON time are at their maximum values. The inductor
must also store enough energy to supply the load without
saturating. Finally, the dc resistance of the inductor should be
low, so that excessive power will not be wasted by heating the
windings. For most ADP1173 applications, an inductor of
47 µH to 470 µH, with a saturation current rating of 300 mA to
1 A and dc resistance <1 Ω is suitable. Ferrite core inductors
which meet these specifications are available in small, surfacemount packages.
To minimize Electro-Magnetic Interference (EMI), a toroid or
pot core type inductor is recommended. Rod core inductors are
a lower cost alternative if EMI is not a problem.
CALCULATING THE INDUCTOR VALUE
Selecting the proper inductor value is a simple three-step
process:
1. Define the operating parameters: minimum input voltage,
maximum input voltage, output voltage and output current.
2. Select the appropriate conversion topology (step-up, stepdown, or inverting).
3. Calculate the inductor value, using the equations in the
following sections.
Inductor Selection—Step-Up Converter
In a step-up, or boost, converter (Figure 14), the inductor must
store enough power to make up the difference between the
input voltage and the output voltage. The power that must be
stored is calculated from the equation:
P L = (V OUT +V D –V IN(MIN ) ) × ( IOUT )
(1)
where VD is the diode forward voltage (≈ 0.5 V for a 1N5818
Schottky). Energy is only stored in the inductor while the
ADP1173 switch is ON, so the energy stored in the inductor on
each switching cycle must be must be equal to or greater than:
PL
f OSC
in order for the ADP1173 to regulate the output voltage.
–5–
(2)
ADP1173
When the internal power switch turns ON, current flow in the
inductor increases at the rate of:
I L (t) =
–R′t 
V IN 
1– e L 

R′ 

When selecting an inductor, the peak current must not exceed
the maximum switch current of 1.5 A. If the equations shown
above result in peak currents > 1.5 A, the ADP1073 should be
considered. This device has a 72% duty cycle, so more energy is
stored in the inductor on each cycle. This results in greater
output power.
(3)
where L is in henrys and R' is the sum of the switch equivalent
resistance (typically 0.8 Ω at +25°C) and the dc resistance of
the inductor. In most applications, where the voltage drop across
the switch is small compared to VIN , a simpler equation can be
used:
I L (t) =
V IN
t
L
The peak current must be evaluated for both minimum and
maximum values of input voltage. If the switch current is high
when VIN is at its minimum, then the 1.5 A limit may be exceeded at the maximum value of VIN. In this case, the ADP1173’s
current limit feature can be used to limit switch current. Simply
select a resistor (using Figure 4) that will limit the maximum
switch current to the IPEAK value calculated for the minimum
value of VIN. This will improve efficiency by producing a constant IPEAK as VIN increases. See the Limiting the Switch Current
section of this data sheet for more information.
(4)
Replacing “t” in the above equation with the ON time of the
ADP1173 (23 µs, typical) will define the peak current for a
given inductor value and input voltage. At this point, the
inductor energy can be calculated as follows:
1
E L = LI 2 PEAK
2
Note that the switch current limit feature does not protect the
circuit if the output is shorted to ground. In this case, current is
only limited by the dc resistance of the inductor and the forward
voltage of the diode.
(5)
As previously mentioned, EL must be greater than PL/fOSC so the
ADP1173 can deliver the necessary power to the load. For best
efficiency, peak current should be limited to 1 A or less. Higher
switch currents will reduce efficiency, because of increased
saturation voltage in the switch. High peak current also increases
output ripple. As a general rule, keep peak current as low as possible to minimize losses in the switch, inductor and diode.
Inductor Selection—Step-Down Converter
The step-down mode of operation is shown in Figure 15. Unlike
the step-up mode, the ADP1173’s power switch does not
saturate when operating in the step-down mode. Therefore,
switch current should be limited to 650 mA in this mode. If the
input voltage will vary over a wide range, the ILIM pin can be
used to limit the maximum switch current. If higher output
current is required, the ADP1111 should be considered.
In practice, the inductor value is easily selected using the equations above. For example, consider a supply that will generate
9 V at 50 mA from a 3 V source. The inductor power required
is, from Equation 1:
The first step in selecting the step-down inductor is to calculate
the peak switch current as follows:
P L = (9V + 0.5V – 3V )×(50 mA) = 325 mW
I PEAK =
On each switching cycle, the inductor must supply:
PL
f OSC
325 mW
=
=13.5 µJ
24 kHz
VSW = voltage drop across the switch
VD = diode drop (0.5 V for a 1N5818)
IOUT = output current
VOUT = the output voltage
VIN = the minimum input voltage
V IN
3V
t=
23 µs =138 µH
I L(MAX ) 500 mA
As previously mentioned, the switch voltage is higher in stepdown mode than step-up mode. VSW is a function of switch
current and is therefore a function of VIN, L, time and VOUT.
For most applications, a VSW value of 1.5 V is recommended.
Substituting a standard inductor value of 100 µH, with 0.2 Ω dc
resistance, will produce a peak switch current of:
I PEAK =
(6)
where DC = duty cycle (0.55 for the ADP1173)
The required inductor power is fairly low in this example, so the
peak current can also be low. Assuming a peak current of 500 mA
as a starting point, Equation 4 can be rearranged to recommend
an inductor value:
L=
2IOUT  V OUT +V D 
DC V IN –V SW +V D 
The inductor value can now be calculated:
–1.0 Ω × 23 µs 
3V 
1– e 100 µH  = 616 mA

1.0 Ω 

L=
Once the peak current is known, the inductor energy can be
calculated from Equation 5:
V IN(MIN ) –V SW –V OUT
× tON
I PEAK
(7)
where tON = switch ON time (23 µs)
If the input voltage will vary (such as an application that must
operate from a 12 V to 24 V source) an RLIM resistor should be
selected from Figure 5. The RLIM resistor will keep switch current constant as the input voltage rises. Note that there are separate
RLIM values for step-up and step-down modes of operation.
1
E L = (100 µH )× (616 mA)2 =19 µJ
2
The inductor energy of 19 µJ is greater than the PL/fOSC requirement of 13.5 µJ, so the 100 µH inductor will work in this
application. By substituting other inductor values into the same
equations, the optimum inductor value can be selected.
–6–
REV. 0
ADP1173
For example, assume that +5 V at 300 mA is required from a
12 V to +24 V input. Deriving the peak current from Equation 6
yields:
I PEAK
I PEAK =
2 × 300 mA  5 + 0.5 
=
12 – 1.5 + 0.5 = 545 mA
0.55


The peak current can then be inserted into Equation 7 to calculate the inductor value:
L=
To avoid exceeding the maximum switch current when the
input voltage is at +24 V, an RLIM resistor should be specified.
Using the step-down curve of Figure 5, a value of 180 Ω will
limit the switch current to 600 mA.
Inductor Selection—Positive-to-Negative Converter
The configuration for a positive-to-negative converter using the
ADP1173 is shown in Figure 17. As with the step-up converter,
all of the output power for the inverting circuit must be supplied
by the inductor. The required inductor power is derived from
the formula:
P L = (|V OUT|+V D ) × ( IOUT )
(8)
The ADP1173 power switch does not saturate in positive-tonegative mode. The voltage drop across the switch can be
modeled as a 0.75 V base-emitter diode in series with a 0.65 Ω
resistor. When the switch turns on, inductor current will rise at
a rate determined by:
_R't 
VL 
1– e L 

R' 

where R' = 0.65 Ω + RL(DC)
where VL = VIN – 0.75 V
For example, assume that a –5 V output at 50 mA is to be
generated from a +4.5 V to +5.5 V source. The power in the
inductor is calculated from Equation 8:
P L = (|−5V|+ 0.5V ) × (50 mA) = 275 mW
During each switching cycle, the inductor must supply the
following energy:
P L 275 mW
=
=11.5 µJ
f OSC 24 kHz
–0.85 Ω × 23 µs 
4.5V – 0.75V 
220 µH
1–
e
 = 375 mA
0.65 Ω + 0.2 Ω 

Once the peak current is known, the inductor energy can be
calculated from Equation 5:
1
E L = (220 µH ) × (375 mA)2 =15.5 µJ
2
12 –1.5 – 5
× 23 µs = 232 µH
545 mA
Since 232 µH is not a standard value, the next lower standard
value of 220 µH would be specified.
I L (t) =
Using a standard inductor value of 220 µH, with 0.2 Ω dc
resistance, will produce a peak switch current of:
(9)
The inductor energy of 15.5 µJ is greater than the PL/fOSC
requirement of 11.5 µJ, so the 220 µH inductor will work in
this application.
The input voltage only varies between 4.5 V and 5.5 V in this
example. Therefore, the peak current will not change enough to
require an RLIM resistor and the ILIM pin can be connected
directly to VIN. Care should be taken to ensure that the peak
current does not exceed 650 mA.
CAPACITOR SELECTION
For optimum performance, the ADP1173’s output capacitor
must be carefully selected. Choosing an inappropriate capacitor
can result in low efficiency and/or high output ripple.
Ordinary aluminum electrolytic capacitors are inexpensive, but
often have poor Equivalent Series Resistance (ESR) and
Equivalent Series Inductance (ESL). Low ESR aluminum capacitors, specifically designed for switch mode converter applications, are also available, and these are a better choice than
general purpose devices. Even better performance can be
achieved with tantalum capacitors, although their cost is higher.
Very low values of ESR can be achieved by using OS-CON*
capacitors (Sanyo Corporation, San Diego, CA). These devices
are fairly small, available with tape-and-reel packaging, and have
very low ESR.
The effects of capacitor selection on output ripple are demonstrated in Figures 11, 12, and 13. These figures show the output
of the same ADP1173 converter, which was evaluated with
three different output capacitors. In each case, the peak switch
current is 500 mA and the capacitor value is 100 µF. Figure 11
shows a Panasonic HF-series* radial aluminum electrolytic.
When the switch turns off, the output voltage jumps by about
90 mV and then decays as the inductor discharges into the
capacitor. The rise in voltage indicates an ESR of about
0.18 Ω. In Figure 12, the aluminum electrolytic has been
replaced by a Sprague 593D-series* tantalum device. In this
case the output jumps about 35 mV, which indicates an ESR of
0.07 Ω. Figure 13 shows an OS-CON SA series capacitor in the
same circuit, and ESR is only 0.02 Ω.
*All trademarks are properties of their respective holders.
REV. 0
–7–
ADP1173
DIODE SELECTION
In specifying a diode, consideration must be given to speed,
forward voltage drop and reverse leakage current. When the
ADP1173 switch turns off, the diode must turn on rapidly if
high efficiency is to be maintained. Schottky rectifiers, as well as
fast signal diodes such as the 1N4148, are appropriate. The
forward voltage of the diode represents power that is not delivered to the load, so VF must also be minimized. Again, Schottky
diodes are recommended. Leakage current is especially important in low current applications, where the leakage can be a
significant percentage of the total quiescent current.
For most circuits, the 1N5818 is a suitable companion to the
ADP1173. This diode has a VF of 0.5 V at 1 A, 4 µA to 10 µA
leakage, and fast turn-on and turn-off times. A surface mount
version, the MBRS130T3, is also available. For applications
where the ADP1173 is “off” most of the time, such as when the
load is intermittent, a silicon diode may provide higher overall
efficiency due to lower leakage. For example, the 1N4933 has a
1 A capability, but with a leakage current of less than 1 µA. The
higher forward voltage of the 1N4933 reduces efficiency when
the ADP1173 delivers power, but the lower leakage may outweigh
the reduction in efficiency.
Figure 11. Aluminum Electrolytic
For switch currents of 100 mA or less, a Schottky diode such as
the BAT85 provides a VF of 0.8 V at 100 mA and leakage less
than 1 µA. A similar device, the BAT54, is available in a SOT23
package. Even lower leakage, in the 1 nA to 5 nA range, can be
obtained with a 1N4148 signal diode.
General purpose rectifiers, such as the 1N4001, are not suitable
for ADP1173 circuits. These devices, which have turn-on times
of 10 µs or more, are too slow for switching power supply
applications. Using such a diode “just to get started” will result
in wasted time and effort. Even if an ADP1173 circuit appears
to function with a 1N4001, the resulting performance will not
be indicative of the circuit performance when the correct diode
is used.
Figure 12. Tantalum Electrolytic
CIRCUIT OPERATION, STEP-UP (BOOST) MODE
In boost mode, the ADP1173 produces an output voltage that
is higher than the input voltage. For example, +12 V can be
generated from a +5 V logic power supply or +5 V can be
derived from two alkaline cells (+3 V).
Figure 16 shows an ADP1173 configured for step-up operation.
The collector of the internal power switch is connected to the
output side of the inductor, while the emitter is connected to
GND. When the switch turns on, pin SW1 is pulled near ground.
This action forces a voltage across L1 equal to VIN–VCE(SAT),
and current begins to flow through L1. This current reaches a
final value (ignoring second-order effects) of:
Figure 13. OS-CON Capacitor
If low output ripple is important, the user should consider the
ADP3000. This device switches at 400 kHz, and the higher
switching frequency simplifies the design of the output filter.
Consult the ADP3000 data sheet for additional details.
All potential current paths must be considered when analyzing
very low power applications, and this includes capacitor leakage
current. OS-CON capacitors have leakage in the 5 µA to 10 µA
range, which will reduce efficiency when the load is also in the
microampere range. Tantalum capacitors, with typical leakage
in the 1 µA to 5 µA range, are recommended for very low power
applications.
I PEAK ≅
V IN –V CE(SAT )
× 23 µs
L
where 23 µs is the ADP1173 switch’s “on” time.
–8–
REV. 0
ADP1173
L1
D1
VOUT
VIN
R3*
R1
1
2
ILIM
VIN
SW1 3
+
ADP1173
GND
SW2
5
4
FB
C1
8
R2
* = OPTIONAL
Figure 14. Step-Up Mode Operation
When the switch turns off, the magnetic field collapses. The
polarity across the inductor changes, current begins to flow
through D1 into the load and the output voltage is driven above
the input voltage.
The output voltage is fed back to the ADP1173 via resistors R1
and R2. When the voltage at pin FB falls below 1.245 V, SW1
turns “on” again and the cycle repeats. The output voltage is
therefore set by the formula:
 R1
V OUT =1.245 V × 1+ 
 R2
The circuit of Figure 14 shows a direct current path from VIN to
VOUT, via the inductor and D1. Therefore, the boost converter
is not protected if the output is short circuited to ground.
When the switch turns off, the magnetic field collapses. The
polarity across the inductor changes and the switch side of the
inductor is driven below ground. Schottky diode D1 then turns
on and current flows into the load. Notice that the Absolute
Maximum Rating for the ADP1173’s SW2 pin is 0.5 V below
ground. To avoid exceeding this limit, D1 must be a Schottky
diode. Using a silicon diode in this application will generate
forward voltages above 0.5 V, which will cause potentially
damaging power dissipation within the ADP1173.
The output voltage of the buck regulator is fed back to the
ADP1173’s FB pin by resistors R1 and R2. When the voltage at
pin FB falls below 1.245 V, the internal power switch turns
“on” again and the cycle repeats. The output voltage is set by
the formula:
 R1
V OUT =1.245 V × 1+ 
 R2
When operating the ADP1173 in step-down mode, the output
voltage is impressed across the internal power switch’s emitterbase junction when the switch is off. To protect the switch, the
output voltage should be limited to 6.2 V or less. If a higher
output voltage is required, a Schottky diode should be placed in
series with SW2, as shown in Figure 16.
If high output current is required in a step-down converter, the
ADP1111 or ADP3000 should be considered. These devices
offer higher frequency operation, which reduces inductor size,
and an external pass transistor can be added to reduce RON of
the switch.
CIRCUIT OPERATION, STEP-DOWN (BUCK) MODE
VIN
RLIM
100Ω
The ADP1173’s step-down mode is used to produce an output
voltage lower than the input voltage. For example, the output of
four NiCd cells (+4.8 V) can be converted to a +3.3 V logic
supply.
C2
I PEAK
VIN
R3
100Ω
C2
1
2
3
ILIM VIN SW1
FB
8
ADP1173
GND
SW2 4
VOUT
+
D1
1N5818
FB 8
ADP1173
GND
1N5818
L1
SW2 4
VOUT
+
5
D1
1N5818
C1
R1
R2
Figure 16. Step-Down Mode, VOUT > 6.2 V
C1
R1
R2
The ADP1173 can convert a positive input voltage to a negative
output voltage, as shown in Figure 17. This circuit is essentially
identical to the step-down application of Figure 15, except that
the “output” side of the inductor is connected to power ground.
When the ADP1173’s internal power switch turns off, current
flowing in the inductor forces the output (–VOUT) to a negative
potential. The ADP1173 will continue to turn the switch on
Figure 15. Step-Down Mode Operation
REV. 0
3
POSITIVE-TO-NEGATIVE CONVERSION
L1
5
2
If the input voltage to the ADP1173 varies over a wide range, a
current limiting resistor at Pin 1 may be required. If a particular
circuit requires high peak inductor current with minimum input
supply voltage, the peak current may exceed the switch maximum rating and/or saturate the inductor when the supply
voltage is at the maximum value. See the Limiting the Switch
Current section of this data sheet for specific recommendations.
where 23 µs is the ADP1173 switch’s “on” time.
+
1
ILIM VIN SW1
A typical configuration for step-down operation of the ADP1173
is shown in Figure 15. In this case, the collector of the internal
power switch is connected to VIN and the emitter drives the
inductor. When the switch turns on, SW2 is pulled up toward
VIN. This forces a voltage across L1 equal to (VIN–VCE) – VOUT,
and causes current to flow in L1. This current reaches a final
value of:
V –V CE –V OUT
≅ IN
× 23 µs
L
+
–9–
ADP1173
until its FB pin is 1.245 V above its GND pin, so the output
voltage is determined by the formula:
LIMITING THE SWITCH CURRENT
The ADP1173’s RLIM pin permits the switch current to be limited with a single resistor. This current limiting action occurs on
a pulse by pulse basis. This feature allows the input voltage to
vary over a wide range, without saturating the inductor or exceeding the maximum switch rating. For example, a particular
design may require peak switch current of 800 mA with a 2.0 V
input. If VIN rises to 4 V, however, the switch current will exceed
1.6 A. The ADP1173 limits switch current to 1.5 A and thereby
protects the switch, but increases the output ripple. Selecting
the proper resistor will limit the switch current to 800 mA, even
if VIN increases. The relationship between RLIM and maximum
switch current is shown in Figures 4 and 5.
 R1
=1.245 V × 1+ 
 R2
–V OUT
+VIN
R3
C2
+
2
1
3
ILIM VIN SW1
FB 8
ADP1173
L1
SW2 4
GND
+
5
R1
C1
D1
1N5818
The ILIM feature is also valuable for controlling inductor current
when the ADP1173 goes into continuous-conduction mode. This
occurs in the step-up mode when the following condition is met:
R2
–VOUT
V OUT +V DIODE
1
<
V IN –V SW
1– DC
Figure 17. A Positive-to-Negative Converter
The design criteria for the step-down application also apply to
the positive-to-negative converter. The output voltage should be
limited to |6.2 V|, unless a diode is inserted in series with the
SW2 Pin (see Figure 16). Also, D1 must again be a Schottky
diode to prevent excessive power dissipation in the ADP1173.
NEGATIVE-TO-POSITIVE CONVERSION
The circuit of Figure 18 converts a negative input voltage to a
positive output voltage. Operation of this circuit configuration is
similar to the step-up topology of Figure 14, except that the current
through feedback resistor R1 is level-shifted below ground by a
PNP transistor. The voltage across R1 is (VOUT –VBEQ1). However, diode D2 level-shifts the base of Q1 about 0.6 V below
ground, thereby cancelling the VBE of Q1. The addition of D2
also reduces the circuit’s output voltage sensitivity to temperature, which otherwise would be dominated by the –2 mV/°C VBE
contribution of Q1. The output voltage for this circuit is determined by the formula:
where DC is the ADP1173’s duty cycle. When this relationship
exists, the inductor current does not go all the way to zero during the time the switch is OFF. When the switch turns on for
the next cycle, the inductor current begins to ramp up from the
residual level. If the switch ON time remains constant, the inductor current will increase to a high level (see Figure 19). This
increases output ripple, and can require a larger inductor and
capacitor. By controlling switch current with the ILIM resistor,
output ripple current can be maintained at the design values.
Figure 20 illustrates the action of the ILIM circuit.
 R1 
V OUT = 1.245 V ×  
 R2 
Unlike the positive step-up converter, the negative-to-positive
converter’s output voltage can be either higher or lower than the
input voltage.
L1
+
RLIM
C2
+
1N5818
D1
R1
1
2
ILIM
VIN
SW1 3
Q1
2N3906
ADP1173
NEGATIVE
INPUT
7
5
4
CL
1N4148
D2
10kΩ
FB 8
AO SET GND SW2
6
Figure 19. (ILIM Operation, RLIM = 0 Ω)
POSITIVE
OUTPUT
R2
NC NC
Figure 18. A Negative-to-Positive Converter
Figure 20. (ILIM Operation, RLIM = 240 Ω)
–10–
REV. 0
ADP1173
The internal structure of the ILIM circuit is shown in Figure 21.
Q1 is the ADP1173’s internal power switch, which is paralleled
by sense transistor Q2. The relative sizes of Q1 and Q2 are
scaled so that IQ2 is 0.5% of IQ1. Current flows to Q2 through an
internal 80 Ω resistor and through the RLIM resistor. These two
resistors parallel the base-emitter junction of the oscillatordisable transistor, Q3. When the voltage across R1 and RLIM
exceeds 0.6 V, Q3 turns on and terminates the output pulse. If
only the 80 Ω internal resistor is used (i.e., the ILIM pin is connected directly to VIN), the maximum switch current will be
1.5 A. Figures 4 and 5 gives RLIM values for lower current-limit
values.
RLIM
(EXTERNAL)
VIN
80Ω
(INTERNAL)
SW1
Q3
VBAT
OSCILLATOR
7
100kΩ
VIN
1.245V
REF
SET
AO
TO
PROCESSOR
6
GND
R2
5
R1 =
VLB –1.245V
12.5µA
VLB = BATTERY TRIP POINT
R2 = 100kΩ
Figure 22. Setting the Low Battery Detector Trip Point
R1 =
DRIVER
Q2
ADP1173
R1
Figure 22 shows the gain block configured as a low battery
monitor. Resistors R1 and R2 should be set to high values to
reduce quiescent current, but not so high that bias current in the
SET input causes large errors. A value of 100 kΩ for R2 is a
good compromise. The value for R1 is then calculated from the
formula:
ILIM
R1
+5V
2
Q1
SW2
Figure 21. Current Limit Operation
V LOBATT − 1.245 V
1.245 V
R2
where VLOBATT is the desired low battery trip point. Since the
gain block output is an open-collector NPN, a pull-up resistor
should be connected to the positive logic power supply.
The delay through the current limiting circuit is approximately
2 µs. If the switch ON time is reduced to less than 4 µs, accuracy of the current trip-point is reduced. Attempting to program
a switch ON time of 2 µs or less will produce spurious responses
in the switch ON time. However, the ADP1173 will still provide
a properly regulated output voltage.
5V
2
ADP1173
R1
VBAT
7
47kΩ
VIN
1.245mV
REF
SET
AO
6
TO
PROCESSOR
GND
R2
5
PROGRAMMING THE GAIN BLOCK
The gain block of the ADP1173 can be used as a low-battery
detector, error amplifier or linear post regulator. The gain block
consists of an op amp with PNP inputs and an open-collector
NPN output. The inverting input is internally connected to the
ADP1173’s 1.245 V reference, while the noninverting input is
available at the SET pin. The NPN output transistor will sink
about 100 µA.
REV. 0
R3
1.6MΩ
Figure 23. Adding Hysteresis to the Low Battery Detector
–11–
ADP1173
Typical Circuit Applications
L1*
68µH
100Ω
1N4148
R1
100Ω
ILIM
2 x 1.5V
CELLS
2.21MΩ
1%
2
1
9V
BATTERY
VIN SW1 3
ADP1173
1N5818
1N5818
4
118kΩ
1%
22µF
*L1 = GOWANDA GA10-682K
COILTRONICS CTX68-4
FOR 5V INPUT CHANGE R1 TO 47Ω
CONVERTER WILL DELIVER –22V AT 40mA
SW1 3
SENSE 8
SW2
5
GND SW2
4
VIN
GND
FB 8
5
2
ILIM
ADP1173-5
0.1µF
4.7µF
1
1N5818
220kΩ
–22V OUTPUT
7mA AT 2.0V INPUT
70% EFFICIENCY
L1*
47µH
100µF
+
5V OUTPUT
150mA AT 9V INPUT
50mA AT 6.5V INPUT
*L1 = GOWANDA GA10-472K
COILTRONICS CTX50-1
FOR HIGHER OUTPUT CURRENTS SEE ADP1073 DATASHEET
Figure 27. 9 V to 5 V Converter
Figure 24. 3 V–22 V LCD Bias Generator
+VIN
12V-28V
L1*
82µH
ILIM
2 x 1.5V
CELLS
VIN
SW1 3
SW2
5
4
1N5818
SENSE
8
+
5
5V OUTPUT
150mA AT 3V INPUT
60mA AT 2V INPUT
SW1 3
SENSE 8
SW2
4
1N5818
100µF
L1*
220µH
100µF
+
5V OUTPUT
300mA
*L1 = GOWANDA GA10-223K
*L1 = GOWANDA GA10-822K
Figure 28. +20 V to 5 V Step-Down Converter
Figure 25. 3 V to 5 V Step-Up Converter
+VIN
5V INPUT
2
VIN
GND
ADP1173-5
GND
1
ILIM
ADP1173-5
2
1
100Ω
+
22µF
100Ω
1
2
ILIM
VIN
SW1 3
ADP1173-5
GND
5
SENSE 8
SW2
4
L1*
100µH
+
1N5818
100µF
*L1 = GOWANDA GA10-103K
COILTRONICS CTX100-1
–5V OUTPUT
75mA
Figure 26. +5 V to –5 V Converter
–12–
REV. 0
ADP1173
44mH
L1*
500µH
~
+
48V DC
44mH
MUR110
+
~
47µF
100V
+
3.6MΩ
–
10kΩ
2N5400
VN2222L
12V
IRF530
15V
10nF
*L1 = CTX110077
IQ = 120µA
220µF
10V
100Ω
VIN
ILIM
1N965B
1N4148
2
1
10µF
16V
+
+5V
100mA
390kΩ
SW1 3
ADP1173
GND
SW2
5
4
FB 8
110kΩ
Figure 29. Telecom Supply
L1*
100µH
1N5818
SI9405DY
VOUT = 5V AT 100mA
AT VIN = 2.6V
56Ω
+
470µF
4 x NICAD
OR
ALKALINE
CELLS
7
1
2
ILIM
VIN
SET
470kΩ
ADP1173
GND
SW2
5
4
75k
SW1 3
+
AO 6
470µF
FB 8
470µF
+
240Ω
24kΩ
*L1 = GOWANDA GA20-103K
COILTRONICS CTX100-4
VIN = 2.6V TO 7.2V
Figure 30. 5 V to 5 V Step-Up or Step-Down Converter
L1*
20µH, 5A
100kΩ
47kΩ
100kΩ
470µF
+
2N3906
6
AO
7
SET
2.2MΩ
2 x NICAD
1
2
ILIM
VIN
1N5820
220Ω
100Ω
2N4403
SW1 3
ADP1173
+5V OUTPUT
200mA
LOCKOUT AT
1.85V INPUT
301kن
FB 8
GND
SW2
5
4
5Ω
100kΩ
+
MJE200
100kن
470µF
47Ω
*L1 = COILTRONICS CTX-20-5-52
†1% METAL FILM
Figure 31. 2 V to 5 V at 200 mA Step-Up Converter with Undervoltage Lockout
REV. 0
–13–
ADP1173
0.22Ω
VIN
7V-24V
1N5818
18V
1W
1N5820
2kΩ
2N3904
2
1
ILIM
L1*
25µH, 2A
MTM20P08
+
51Ω
470µF
VIN SW1 3
100Ω
1/2W
ADP1173
GND
SW2
5
4
1N4148
VIN
200kΩ
–VOUT = –5.13*VC
39kΩ
VC (0V TO +5V)
OP196
FB 8
*L1 = GOWANDA GT10-100
EFFICIENCY ≥ 80% FOR 10mA ≤ ILOAD ≤ 500mA
STANDBY IQ ≤ 150µA
Figure 32. Voltage Controlled Positive-to-Negative Converter
0.22Ω
VIN
7V-24V
MTM20P08
1N5818
18V
1W
ILIM
1N5820
2kΩ
2N3904
2
1
L1*
25µH, 2A
5V
500mA
+
470µF
51Ω
VIN SW1 3
100Ω
1/2W
ADP1173
GND
SW2
5
4
1N4148
121kΩ
FB 8
OPERATE STANDBY
40.2kΩ
*L1 = GOWANDA GT10-100
EFFICIENCY ≥ 80% FOR 10mA ≤ ILOAD ≤ 500mA
STANDBY IQ ≤ 150µA
Figure 33. High Power, Low Quiescent Current Step-Down Converter
–14–
REV. 0
ADP1173
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Plastic DIP
(N-8)
0.430 (10.92)
0.348 (8.84)
8
5
0.280 (7.11)
0.240 (6.10)
1
4
0.060 (1.52)
0.015 (0.38)
PIN 1
0.210 (5.33)
MAX
0.325 (8.25)
0.300 (7.62)
0.195 (4.95)
0.115 (2.93)
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
0.022 (0.558) 0.100 0.070 (1.77)
0.014 (0.356) (2.54) 0.045 (1.15)
BSC
0.015 (0.381)
0.008 (0.204)
SEATING
PLANE
8-Lead Small Outline Package
(SO-8)
0.1968 (5.00)
0.1890 (4.80)
0.1574 (4.00)
0.1497 (3.80)
PIN 1
0.0098 (0.25)
0.0040 (0.10)
SEATING
PLANE
REV. 0
8
5
1
4
0.2440 (6.20)
0.2284 (5.80)
0.0688 (1.75)
0.0532 (1.35)
0.0500 0.0192 (0.49)
(1.27) 0.0138 (0.35)
BSC
0.0196 (0.50)
x 45°
0.0099 (0.25)
0.0098 (0.25)
0.0075 (0.19)
–15–
8°
0°
0.0500 (1.27)
0.0160 (0.41)
–16–
PRINTED IN U.S.A.
C2965–12–1/97