AD AD8278ARZ-R7 Low power, wide supply range, low cost difference amplifiers, Datasheet

Low Power, Wide Supply Range,
Low Cost Difference Amplifiers, G = ½, 2
AD8278/AD8279
FEATURES
FUNCTIONAL BLOCK DIAGRAMS
+VS
Wide input range beyond supplies
Rugged input overvoltage protection
Low supply current: 200 μA maximum (per amplifier)
Low power dissipation: 0.5 mW at VS = 2.5 V
Bandwidth: 1 MHz (G = ½)
CMRR: 80 dB minimum, dc to 20 kHz (G = ½, B Grade)
Low offset voltage drift: ±1 μV/°C maximum (B Grade)
Low gain drift: 1 ppm/°C maximum (B Grade)
Enhanced slew rate: 1.4 V/μs
Wide power supply range
Single supply: 2 V to 36 V
Dual supplies: ±2 V to ±18 V
8-lead SOIC, 14-lead SOIC, and 8-lead MSOP packages
7
AD8278
+IN 3
20kΩ
40kΩ
20kΩ
The AD8278 and AD8279 operate on single supplies (2.0 V to 36 V)
or dual supplies (±2 V to ±18 V). The maximum quiescent supply
current is 200 μA, which is ideal for battery-operated and portable
systems. For unity-gain difference amplifiers with similar
performance, refer to the AD8276 and AD8277 data sheets.
OUT
1
REF
Figure 1. AD8278
+VS
11
–INA
+INA 3
–INB 6
40kΩ
20kΩ
40kΩ
20kΩ
40kΩ
20kΩ
+INB 5
40kΩ
20kΩ
12
SENSEA
13
OUTA
14
REFA
10
SENSEB
9
OUTB
8
REFB
4
–VS
08308-058
AD8279
2
GENERAL DESCRIPTION
The AD8278 and AD8279 can be used as difference amplifiers with
G = ½ or G = 2. They can also be connected in a high precision,
single-ended configuration for non inverting and inverting gains of
−½, −2, +3, +2, +1½, +1, or +½. The AD8278 and AD8279
provide an integrated precision solution that has a smaller size,
lower cost, and better performance than a discrete alternative.
6
4
Voltage measurement and monitoring
Current measurement and monitoring
Instrumentation amplifier building block
Portable, battery-powered equipment
Test and measurement
The common-mode range of the amplifier extends to almost
triple the supply voltage (for G = ½), making the amplifer ideal
for single-supply applications that require a high commonmode voltage range. The internal resistors and ESD circuitry at
the inputs also provide overvoltage protection to the op amp.
SENSE
–VS
APPLICATIONS
The AD8278 and AD8279 are general-purpose difference
amplifiers intended for precision signal conditioning in power
critical applications that require both high performance and low
power. The AD8278 and AD8279 provide exceptional commonmode rejection ratio (80 dB) and high bandwidth while amplifying
input signals that are well beyond the supply rails. The on-chip
resistors are laser trimmed for excellent gain accuracy and high
CMRR. They also have extremely low gain drift vs. temperature.
5
08308-001
–IN 2
40kΩ
Figure 2. AD8279
Table 1. Difference Amplifiers by Category
Low
Distortion
AD8270
AD8271
AD8273
AD8274
AMP03
High Voltage
AD628
AD629
Current Sensing1
AD8202 (U)
AD8203 (U)
AD8205 (B)
AD8206 (B)
AD8216 (B)
Low Power
AD8276
AD8277
1
U = unidirectional, B = bidirectional.
The AD8278 is available in the space-saving 8-lead MSOP and
SOIC packages, and the AD8279 is offered in a 14-lead SOIC
package. Both are specified for performance over the industrial
temperature range of −40°C to +85°C and are fully RoHS
compliant.
Rev. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113 ©2009–2011 Analog Devices, Inc. All rights reserved.
AD8278/AD8279
TABLE OF CONTENTS
Features .............................................................................................. 1
Typical Performance Characteristics ..............................................9
Applications....................................................................................... 1
Theory of Operation ...................................................................... 16
General Description ......................................................................... 1
Circuit Information.................................................................... 16
Functional Block Diagrams............................................................. 1
Driving the AD8278 and AD8279 ........................................... 16
Revision History ............................................................................... 2
Input Voltage Range................................................................... 16
Specifications..................................................................................... 3
Power Supplies ............................................................................ 17
Absolute Maximum Ratings............................................................ 7
Applications Information .............................................................. 18
Thermal Resistance ...................................................................... 7
Configurations............................................................................ 18
Maximum Power Dissipation ..................................................... 7
Differential Output .................................................................... 19
Short-Circuit Current .................................................................. 7
Instrumentation Amplifier........................................................ 19
ESD Caution.................................................................................. 7
Outline Dimensions ....................................................................... 20
Pin Configurations and Function Descriptions ........................... 8
Ordering Guide .......................................................................... 21
REVISION HISTORY
1/11—Rev. B to Rev. C
Change to Impedance/Differential Parameter, Table 3 ............... 4
Change to Impedance/Differential Parameter, Table 5 ............... 6
4/10—Rev. A to Rev. B
Changed Supply Current Parameters to AD8278 Supply Current
Parameter and AD8279 Supply Current Parameter, Table 5 ...... 6
Updated Outline Dimensions ....................................................... 20
10/09—Rev. 0 to Rev. A
Added AD8279 and 14-Lead SOIC Model .....................Universal
Changes to Features.......................................................................... 1
Changes to General Description .................................................... 1
Change to Table 2 ............................................................................. 3
Change to Table 3 ..............................................................................4
Change to Table 4 ..............................................................................5
Change to Table 5 ..............................................................................6
Added Figure 6 and Table 9 .............................................................8
Changes to Figure 31 and Figure 32............................................. 13
Changes to Figure 40, Figure 41, and Figure 42 ......................... 14
Added Figure 47; Renumbered Sequentially .............................. 15
Changes to Figure 51 to Figure 57................................................ 18
Added Differential Output Section.............................................. 19
Changes to Figure 59...................................................................... 19
Updated Outline Dimensions....................................................... 21
Changes to Ordering Guide .......................................................... 21
7/09—Revision 0: Initial Version
Rev. C | Page 2 of 24
AD8278/AD8279
SPECIFICATIONS
VS = ±5 V to ±15 V, VREF = 0 V, TA = 25°C, RL = 10 kΩ connected to ground, G = ½ difference amplifier configuration, unless
otherwise noted.
Table 2.
G=½
Parameter
INPUT CHARACTERISTICS
System Offset 1
Over Temperature
vs. Power Supply
Average Temperature
Coefficient
Common-Mode Rejection
Ratio (RTI)
Input Voltage Range 2
Impedance 3
Differential
Common Mode
DYNAMIC PERFORMANCE
Bandwidth
Slew Rate
Channel Separation
Settling Time to 0.01%
Settling Time to 0.001%
GAIN
Gain Error
Gain Drift
Gain Nonlinearity
OUTPUT CHARACTERISTICS
Output Voltage Swing 4
Short-Circuit Current Limit
Capacitive Load Drive
NOISE 5
Output Voltage Noise
POWER SUPPLY 6
AD8278 Supply Current
Over Temperature
AD8279 Supply Current
Over Temperature
Operating Voltage Range 7
TEMPERATURE RANGE
Operating Range
Conditions
Grade B
Typ
Max
Min
250
250
5
μV
μV
μV/V
0.3
1
2
5
μV/°C
+3 (VS − 1.5)
dB
V
+3 (VS − 1.5)
1
1.4
130
74
−3 (VS + 0.1)
1.1
120
30
kΩ
kΩ
1
1.4
130
MHz
V/μs
dB
9
10
0.005
TA = −40°C to +85°C
VOUT = 20 V p-p
VS = ±15 V, RL = 10 kΩ
TA = −40°C to +85°C
−VS + 0.2
0.02
1
7
+VS − 0.2
0.01
−VS + 0.2
±15
200
f = 0.1 Hz to 10 Hz
f = 1 kHz
Unit
50
120
30
f = 1 kHz
10 V step on output,
CL = 100 pF
Max
100
100
2.5
80
−3 (VS + 0.1)
1.1
Grade A
Typ
50
TA = −40°C to +85°C
VS = ±5 V to ±18 V
TA = −40°C to +85°C
VS = ±15 V, VCM = ±27 V,
RS = 0 Ω
Min
1.4
47
9
10
μs
μs
0.05
5
12
%
ppm/°C
ppm
+VS − 0.2
V
mA
pF
±15
200
1.4
47
50
50
μV p-p
nV/√Hz
μA
μA
μA
μA
V
°C
±2
200
250
350
400
±18
±2
200
250
350
400
±18
−40
+125
−40
+125
TA = −40°C to +85°C
300
TA = −40°C to +85°C
1
300
Includes input bias and offset current errors, RTO (referred to output).
The input voltage range may also be limited by absolute maximum input voltage or by the output swing. See the Input Voltage Range for details.
Internal resistors are trimmed to be ratio matched and have ±20% absolute accuracy.
4
Output voltage swing varies with supply voltage and temperature. See Figure 22 through Figure 25 for details.
5
Includes amplifier voltage and current noise, as well as noise from internal resistors.
6
Supply current varies with supply voltage and temperature. See Figure 26 and Figure 28 for details.
7
Unbalanced dual supplies can be used, such as −VS = −0.5 V and +VS = +2 V. The positive supply rail must be at least 2 V above the negative supply and reference
voltage.
2
3
Rev. C | Page 3 of 24
AD8278/AD8279
VS = ±5 V to ±15 V, VREF = 0 V, TA = 25°C, RL = 10 kΩ connected to ground, G = 2 difference amplifier configuration, unless
otherwise noted.
Table 3.
G=2
Parameter
INPUT CHARACTERISTICS
System Offset 1
Over Temperature
vs. Power Supply
Average Temperature
Coefficient
Common-Mode
Rejection Ratio (RTI)
Input Voltage Range 2
Impedance 3
Differential
Common Mode
DYNAMIC PERFORMANCE
Bandwidth
Slew Rate
Channel Separation
Settling Time to 0.01%
Settling Time to 0.001%
GAIN
Gain Error
Gain Drift
Gain Nonlinearity
OUTPUT CHARACTERISTICS
Output Voltage Swing 4
Short-Circuit Current
Limit
Capacitive Load Drive
NOISE 5
Output Voltage Noise
POWER SUPPLY 6
AD8278 Supply Current
Over Temperature
AD8279 Supply Current
Over Temperature
Operating Voltage Range 7
TEMPERATURE RANGE
Operating Range
Conditions
Grade B
Typ
Max
Min
100
500
500
10
μV
μV
μV/V
0.6
2
2
5
μV/°C
+1.5 (VS − 1.5)
dB
V
80
+1.5 (VS − 1.5) −1.5 (VS + 0.1)
30
30
550
1.4
130
f = 1 kHz
10 V step on output,
CL = 100 pF
1.1
30
30
kΩ
kΩ
550
1.4
130
kHz
V/μs
dB
10
11
0.005
TA = −40°C to +85°C
VOUT = 20 V p-p
VS = ±15 V, RL = 10 kΩ,
TA = −40°C to +85°C
−VS + 0.2
0.02
1
7
+VS − 0.2
0.01
−VS + 0.2
±15
350
f = 0.1 Hz to 10 Hz
f = 1 kHz
2.8
90
10
11
μs
μs
0.05
5
12
%
ppm/°C
ppm
+VS − 0.2
V
±15
350
2.8
90
95
mA
pF
95
μV p-p
nV/√Hz
μA
μA
μA
μA
V
°C
±2
200
250
350
400
±18
±2
200
250
350
400
±18
−40
+125
−40
+125
TA = −40°C to +85°C
300
TA = −40°C to +85°C
Unit
200
200
5
86
−1.5 (VS + 0.1)
1.1
Grade A
Typ
Max
100
TA = −40°C to +85°C
VS = ±5 V to ±18 V
TA = −40°C to +85°C
VS = ±15 V, VCM = ±27 V,
RS = 0 Ω
Min
1
300
Includes input bias and offset current errors, RTO (referred to output).
The input voltage range may also be limited by absolute maximum input voltage or by the output swing. See the Input Voltage Range section for details.
3
Internal resistors are trimmed to be ratio matched and have ±20% absolute accuracy.
4
Output voltage swing varies with supply voltage and temperature. See Figure 22 through Figure 25 for details.
5
Includes amplifier voltage and current noise, as well as noise from internal resistors.
6
Supply current varies with supply voltage and temperature. See Figure 26 and Figure 28 for details.
7
Unbalanced dual supplies can be used, such as −VS = −0.5 V and +VS = +2 V. The positive supply rail must be at least 2 V above the negative supply and reference
voltage.
2
Rev. C | Page 4 of 24
AD8278/AD8279
VS = +2.7 V to <±5 V, VREF = midsupply, TA = 25°C, RL = 10 kΩ connected to midsupply, G = ½ difference amplifier configuration, unless
otherwise noted.
Table 4.
G=½
Parameter
INPUT CHARACTERISTICS
System Offset 1
Over Temperature
vs. Power Supply
Average Temperature
Coefficient
Common-Mode Rejection
Ratio (RTI)
Input Voltage Range 2
Impedance 3
Differential
Common Mode
DYNAMIC PERFORMANCE
Bandwidth
Slew Rate
Channel Separation
Settling Time to 0.01%
GAIN
Gain Error
Gain Drift
OUTPUT CHARACTERISTICS
Output Swing 4
Short-Circuit Current Limit
Capacitive Load Drive
NOISE 5
Output Voltage Noise
POWER SUPPLY 6
AD8278 Supply Current
AD8279 Supply Current
Operating Voltage Range
TEMPERATURE RANGE
Operating Range
Conditions
Grade B
Typ
Max
Min
250
250
5
μV
μV
μV/V
0.3
1
2
5
μV/°C
74
+3 (VS − 1.5)
dB
74
−3 (VS + 0.1)
+3 (VS − 1.5)
dB
V
120
30
120
30
kΩ
kΩ
870
1.3
130
870
1.3
130
kHz
V/μs
dB
7
7
μs
0.005
TA = −40°C to +85°C
−VS + 0.1
0.02
1
+VS − 0.15
0.01
−VS + 0.1
±10
200
1.4
47
TA = −40°C to +85°C
TA = −40°C to +85°C
Unit
75
80
−3 (VS + 0.1)
f = 0.1 Hz to 10 Hz
f = 1 kHz
Max
150
150
2.5
80
f = 1 kHz
2 V step on output,
CL = 100 pF, VS = 2.7 V
RL = 10 kΩ,
TA = −40°C to +85°C
Grade A
Typ
75
TA = −40°C to +85°C
VS = ±5 V to ±18 V
TA = −40°C to +85°C
VS = 2.7 V, VCM = 0 V to
2.4 V, RS = 0 Ω
VS = ±5 V, VCM = −10 V
to +7 V, RS = 0 Ω
Min
0.05
5
%
ppm/°C
+VS − 0.15
V
mA
pF
±10
200
1.4
47
50
50
μV p-p
nV/√Hz
μA
μA
V
°C
2.0
200
375
36
2.0
200
375
36
−40
+125
−40
+125
1
Includes input bias and offset current errors, RTO (referred to output).
The input voltage range may also be limited by absolute maximum input voltage or by the output swing. See the Input Voltage Range section for details.
3
Internal resistors are trimmed to be ratio matched and have ±20% absolute accuracy.
4
Output voltage swing varies with supply voltage and temperature. See Figure 22 through Figure 25 for details.
5
Includes amplifier voltage and current noise, as well as noise from internal resistors.
6
Supply current varies with supply voltage and temperature. See Figure 27 and Figure 28 for details.
2
Rev. C | Page 5 of 24
AD8278/AD8279
VS = +2.7 V to <±5 V, VREF = midsupply, TA = 25°C, RL = 10 kΩ connected to midsupply, G = 2 difference amplifier configuration, unless
otherwise noted.
Table 5.
G=2
Parameter
INPUT CHARACTERISTICS
System Offset 1
Over Temperature
vs. Power Supply
Average Temperature
Coefficient
Common-Mode Rejection
Ratio (RTI)
Input Voltage Range 2
Impedance 3
Differential
Common Mode
DYNAMIC PERFORMANCE
Bandwidth
Slew Rate
Channel Separation
Settling Time to 0.01%
GAIN
Gain Error
Gain Drift
OUTPUT CHARACTERISTICS
Output Swing 4
Short-Circuit Current Limit
Capacitive Load Drive
NOISE 5
Output Voltage Noise
POWER SUPPLY 6
AD8278 Supply Current
AD8279 Supply Current
Operating Voltage Range
TEMPERATURE RANGE
Operating Range
Conditions
Grade B
Typ
Max
Min
150
500
500
10
μV
μV
μV/V
0.6
2
3
5
μV/°C
80
86
−1.5 (VS + 0.1)
+1.5 (VS − 1.5)
dB
80
−1.5 (VS + 0.1)
+1.5 (VS − 1.5)
dB
V
30
30
30
30
kΩ
kΩ
450
1.3
130
450
1.3
130
kHz
V/μs
dB
9
9
μs
0.005
TA = −40°C to +85°C
−VS + 0.1
0.02
1
+VS − 0.15
0.01
−VS + 0.1
±10
200
f = 0.1 Hz to 10 Hz
f = 1 kHz
Unit
300
300
5
86
f = 1 kHz
2 V step on output,
CL = 100 pF, VS = 2.7 V
RL = 10 kΩ,
TA = −40°C to +85°C
Grade A
Typ Max
150
TA = −40°C to +85°C
VS = ±5 V to ±18 V
TA = −40°C to +85°C
VS = 2.7 V, VCM = 0 V
to 2.4 V, RS = 0 Ω
VS = ±5 V, VCM = −10 V
to +7 V, RS = 0 Ω
Min
2.8
94
TA = −40°C to +85°C
TA = −40°C to +85°C
0.05
5
%
ppm/°C
+VS − 0.15
V
mA
pF
±10
200
2.8
94
100
100
μV p-p
nV/√Hz
μA
μA
V
°C
2.0
200
375
36
2.0
200
375
36
−40
+125
−40
+125
1
Includes input bias and offset current errors, RTO (referred to output).
The input voltage range may also be limited by absolute maximum input voltage or by the output swing. See the Input Voltage Range section for details.
3
Internal resistors are trimmed to be ratio matched and have ±20% absolute accuracy.
4
Output voltage swing varies with supply voltage and temperature. See Figure 22 through Figure 25 for details.
5
Includes amplifier voltage and current noise, as well as noise from internal resistors.
6
Supply current varies with supply voltage and temperature. See Figure 27 and Figure 28 for details.
2
Rev. C | Page 6 of 24
AD8278/AD8279
ABSOLUTE MAXIMUM RATINGS
2.0
Table 6.
THERMAL RESISTANCE
SOIC
θJA = 121°C/W
1.2
0.8
MSOP
θJA = 135°C/W
0.4
0
–50
–25
0
25
50
75
100
125
AMBIENT TEMERATURE (°C)
Figure 3. Maximum Power Dissipation vs. Ambient Temperature
SHORT-CIRCUIT CURRENT
The AD8278 and AD8279 have built-in, short-circuit protection
that limits the output current (see Figure 29 for more information).
While the short-circuit condition itself does not damage the
part, the heat generated by the condition can cause the part to
exceed its maximum junction temperature, with corresponding
negative effects on reliability. Figure 3 and Figure 29, combined
with knowledge of the supply voltages and ambient temperature of
the part, can be used to determine whether a short circuit will
cause the part to exceed its maximum junction temperature.
The θJA values in Table 7 assume a 4-layer JEDEC standard
board with zero airflow.
Table 7. Thermal Resistance
θJA
135
121
105
1.6
08308-002
Rating
±18 V
−VS + 40 V
+VS − 40 V
−65°C to +150°C
−40°C to +85°C
150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Package Type
8-Lead MSOP
8-Lead SOIC
14-Lead SOIC
MAXIMUM POWER DISSIPATION (W)
TJ MAX = 150°C
Parameter
Supply Voltage
Maximum Voltage at Any Input Pin
Minimum Voltage at Any Input Pin
Storage Temperature Range
Specified Temperature Range
Package Glass Transition Temperature (TG)
Unit
°C/W
°C/W
°C/W
MAXIMUM POWER DISSIPATION
ESD CAUTION
The maximum safe power dissipation for the AD8278 and
AD8279 are limited by the associated rise in junction temperature (TJ) on the die. At approximately 150°C, which is the glass
transition temperature, the properties of the plastic change.
Even temporarily exceeding this temperature limit may change
the stresses that the package exerts on the die, permanently shifting
the parametric performance of the amplifiers. Exceeding a
temperature of 150°C for an extended period may result in a
loss of functionality.
Rev. C | Page 7 of 24
AD8278/AD8279
8
NC
REF 1
AD8278
7
–IN 2
TOP VIEW
(Not to Scale)
+VS
6
OUT
5
SENSE
–IN 2
+IN 3
–VS 4
NC = NO CONNECT
Description
Reference Voltage Input.
Inverting Input.
Noninverting Input.
Negative Supply.
Sense Terminal.
Output.
Positive Supply.
No Connect.
NC 1
14 REFA
–INA 2
+INA 3
13 OUTA
AD8279
12 SENSEA
–VS 4
11 +VS
TOP VIEW 10
SENSEB
(Not to Scale)
9 OUTB
–INB 6
NC 7
8
REFB
NC = NO CONNECT
08308-059
+INB 5
Figure 6. 14-Lead SOIC Pin Configuration
Table 9. AD8279 Pin Function Descriptions
Pin No.
1
2
3
4
5
6
7
8
9
10
11
12
13
14
Mnemonic
NC
−INA
+INA
−VS
+INB
−INB
NC
REFB
OUTB
SENSEB
+VS
SENSEA
OUTA
REFA
NC
7
+VS
6
OUT
5
SENSE
Figure 5. SOIC Pin Configuration
Table 8. AD8278 Pin Function Descriptions
Mnemonic
REF
−IN
+IN
−VS
SENSE
OUT
+VS
NC
8
NC = NO CONNECT
Figure 4. MSOP Pin Configuration
Pin No.
1
2
3
4
5
6
7
8
AD8278
TOP VIEW
+IN 3 (Not to Scale)
–VS 4
08308-003
REF 1
08308-004
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
Description
No Connect.
Channel A Inverting Input.
Channel A Noninverting Input.
Negative Supply.
Channel B Noninverting Input.
Channel B Inverting Input.
No Connect.
Channel B Reference Voltage Input.
Channel B Output.
Channel B Sense Terminal.
Positive Supply.
Channel A Sense Terminal.
Channel A Output.
Channel A Reference Voltage Input.
Rev. C | Page 8 of 24
AD8278/AD8279
TYPICAL PERFORMANCE CHARACTERISTICS
VS = ±15 V, TA = 25°C, RL = 10 kΩ connected to ground, G = ½ difference amplifier configuration, unless otherwise noted.
600
80
N = 3840
MEAN = –16.8
SD = 41.7673
60
500
SYSTEM OFFSET (µV)
NUMBER OF HITS
40
400
300
200
20
0
–20
–40
–60
100
–150
–100
–50
0
50
100
REPRESENTATIVE DATA
–100
–50
–35
–20
–5
10
08308-005
0
150
SYSTEM OFFSET VOLTAGE (µV)
Figure 7. Distribution of Typical System Offset Voltage, G = 2
800
40
55
70
85
Figure 10. System Offset vs. Temperature, Normalized at 25°, G = ½
20
N = 3837
MEAN = 7.78
SD = 13.569
700
25
TEMPERATURE (°C)
08308-008
–80
15
10
GAIN ERROR (µV/V)
NUMBER OF HITS
600
500
400
300
5
0
–5
–10
–15
200
–20
100
–20
0
20
40
60
REPRESENTATIVE DATA
–30
–50
–35
–20
–5
10
CMRR (µV/V)
Figure 8. Distribution of Typical Common-Mode Rejection, G = 2
40
55
70
85
Figure 11. Gain Error vs. Temperature, Normalized at 25°C, G = ½
30
5
20
COMMON-MODE VOLTAGE (V)
10
0
–5
–10
–15
VS = ±15V
10
0
VS = ±5V
–10
–20
REPRESENTATIVE DATA
–20
–50
–35
–20
–5
10
25
40
55
70
85
TEMPERATURE (°C)
–30
–20
08308-007
CMRR (µV/V)
25
TEMPERATURE (°C)
–15
–10
–5
0
5
10
15
20
OUTPUT VOLTAGE (V)
Figure 9. CMRR vs. Temperature, Normalized at 25°C, G = ½
Figure 12. Input Common-Mode Voltage vs. Output Voltage,
±15 V and ±5 V Supplies, G = ½
Rev. C | Page 9 of 24
08308-010
–40
08308-006
–60
08308-009
–25
0
AD8278/AD8279
10
5
VREF = MIDSUPPLY
VS = 5V
VS = 5V
6
4
2
0
VS = 2.7V
–2
–4
–6
2.5
3.5
4.5
5.5
1
12
–1
1.5
2.5
3.5
4.5
5.5
Figure 16. Input Common-Mode Voltage vs. Output Voltage,
5 V and 2.7 V Supplies, VREF = Midsupply, G = 2
6
VREF = 0V
VS = 5V
5
COMMON-MODE VOLTAGE (V)
VS = 5V
8
6
4
2
VS = 2.7V
0
0.5
OUTPUT VOLTAGE (V)
VREF = 0V
10
–2
4
3
2
1
VS = 2.7V
0
1.5
2.5
3.5
4.5
5.5
OUTPUT VOLTAGE (V)
–2
–0.5
08308-012
0.5
0.5
1.5
2.5
3.5
4.5
5.5
OUTPUT VOLTAGE (V)
Figure 14. Input Common-Mode Voltage vs. Output Voltage,
5 V and 2.7 V Supplies, VREF = 0 V, G = ½
Figure 17. Input Common-Mode Voltage vs. Output Voltage,
5 V and 2.7 V Supplies, VREF = 0 V, G = 2
30
18
VS = ±15V
08308-015
–1
–4
12
20
6
GAIN = 2
0
0
GAIN (dB)
10
VS = ±5V
–10
–6
GAIN = ½
–12
–18
–24
–20
–30
–20
–15
–10
–5
0
5
10
15
20
OUTPUT VOLTAGE (V)
Figure 15. Input Common-Mode Voltage vs. Output Voltage,
±15 V and ±5 V Supplies, G = 2
–36
100
1k
10k
100k
1M
FREQUENCY (Hz)
Figure 18. Gain vs. Frequency, ±15 V Supplies
Rev. C | Page 10 of 24
10M
08308-016
–30
08308-013
COMMON-MODE VOLTAGE (V)
VS = 2.7V
0
–3
–0.5
Figure 13. Input Common-Mode Voltage vs. Output Voltage,
5 V and 2.7 V Supplies, VREF = Midsupply, G = ½
COMMON-MODE VOLTAGE (V)
2
08308-014
1.5
08308-011
0.5
OUTPUT VOLTAGE (V)
–6
–0.5
3
–2
–8
–10
–0.5
VREF = MIDSUPPLY
4
COMMON-MODE VOLTAGE (V)
COMMON-MODE VOLTAGE (V)
8
AD8278/AD8279
18
+VS
–0.1
OUTPUT VOLTAGE SWING (V)
REFERRED TO SUPPLY VOLTAGES
12
GAIN = 2
6
GAIN = ½
–6
–12
–18
–24
–30
TA = –40°C
TA = +25°C
TA = +85°C
TA = +125°C
+0.4
+0.3
+0.2
100k
1M
10M
–VS
2
4
6
8
10
12
14
18
16
SUPPLY VOLTAGE (±VS)
08308-020
10k
08308-017
1k
FREQUENCY (Hz)
Figure 22. Output Voltage Swing vs. Supply Voltage and Temperature,
RL = 10 kΩ
Figure 19. Gain vs. Frequency, +2.7 V Single Supply
120
+VS
–0.2
100
GAIN = ½
80
60
40
0
1
10
100
1k
10k
100k
1M
FREQUENCY (Hz)
–0.6
–0.8
–1.0
TA = –40°C
TA = +25°C
TA = +85°C
TA = +125°C
–1.2
+1.2
+1.0
+0.8
+0.6
+0.4
+0.2
–VS
08308-018
20
–0.4
2
4
6
8
10
12
14
16
18
SUPPLY VOLTAGE (±VS)
08308-021
OUTPUT VOLTAGE SWING (V)
REFERRED TO SUPPLY VOLTAGES
GAIN = 2
CMRR (dB)
–0.4
+0.1
–36
100
Figure 23. Output Voltage Swing vs. Supply Voltage and Temperature,
RL = 2 kΩ
Figure 20. CMRR vs. Frequency
+VS
OUTPUT VOLTAGE SWING (V)
REFERRED TO SUPPLY VOLTAGES
120
100
–PSRR
80
60
+PSRR
40
20
0
1
10
100
1k
10k
FREQUENCY (Hz)
Figure 21. PSRR vs. Frequency
100k
1M
–4
–8
TA = –40°C
TA = +25°C
TA = +85°C
TA = +125°C
+8
+4
–VS
1k
08308-019
PSRR (dB)
–0.3
10k
100k
LOAD RESISTANCE (Ω)
Figure 24. Output Voltage Swing vs. RL and Temperature, VS = ±15 V
Rev. C | Page 11 of 24
08308-022
GAIN (dB)
0
–0.2
AD8278/AD8279
+VS
250
VREF = MIDSUPPLY
200
–1.0
SUPPLY CURRENT (µA)
OUTPUT VOLTAGE SWING (V)
REFERRED TO SUPPLY VOLTAGES
–0.5
–1.5
–2.0
TA = –40°C
TA = +25°C
TA = +85°C
TA = +125°C
+2.0
+1.5
150
VS = ±15V
100
VS = +2.7V
50
+1.0
0
1
2
3
4
5
6
7
8
9
10
OUTPUT CURRENT (mA)
0
–50
08308-023
–VS
–30
–10
10
30
50
70
90
110
130
TEMPERATURE (°C)
Figure 25. Output Voltage Swing vs. IOUT and Temperature, VS = ±15 V
08308-026
+0.5
Figure 28. Supply Current per Channel vs. Temperature
180
30
25
SHORT-CIRCUIT CURRENT (mA)
SUPPLY CURRENT (µA)
170
160
150
140
130
20
15
ISHORT+
10
5
0
–5
–10
ISHORT–
0
2
4
6
8
10
12
14
16
18
SUPPLY VOLTAGE (±V)
–20
–50
08308-024
120
–30
–10
10
Figure 26. Supply Current per Channel vs. Dual-Supply Voltage, VIN = 0 V
50
70
90
110
130
Figure 29. Short-Circuit Current per Channel vs. Temperature
180
2.0
–SLEW RATE
1.8
170
1.6
160
SLEW RATE (V/µs)
SUPPLY CURRENT (µA)
30
TEMPERATURE (°C)
08308-027
–15
150
140
1.4
+SLEW RATE
1.2
1.0
0.8
0.6
0.4
130
5
10
15
20
25
SUPPLY VOLTAGE (V)
30
35
40
Figure 27. Supply Current per Channel vs. Single-Supply Voltage, VIN = 0 V,
VREF = 0 V
Rev. C | Page 12 of 24
0
–50
–30
–10
10
30
50
70
90
110
130
TEMPERATURE (°C)
Figure 30. Slew Rate vs. Temperature, VIN = 20 V p-p, 1 kHz
08308-028
0
08308-025
0.2
120
AD8278/AD8279
10
8
NONLINEARITY (2ppm/DIV)
6
4
1V/DIV
2
3.64µs TO 0.01%
4.12µs TO 0.001%
0
–2
0.002%/DIV
–4
–8
4µs/DIV
–4
–3
–2
–1
0
1
2
3
4
5
OUTPUT VOLTAGE (V)
TIME (µs)
08308-029
–10
–5
Figure 31. Gain Nonlinearity, VS = ±15 V, RL ≥ 2 kΩ, G = ½
08308-032
–6
Figure 34. Large Signal Pulse Response and Settling Time, 2 V Step,
VS = 2.7 V, G = ½
20
16
NONLINEARITY (2ppm/DIV)
12
8
5V/DIV
4
7.6µs TO 0.01%
9.68µs TO 0.001%
0
–4
0.002%/DIV
–8
–16
40µs/DIV
–3
–2
–1
0
1
2
3
4
5
OUTPUT VOLTAGE (V)
TIME (µs)
Figure 35. Large Signal Pulse Response and Settling Time, 10 V Step,
VS = ±15 V, G = 2
Figure 32. Gain Nonlinearity, VS = ±15 V, RL ≥ 2 kΩ, G = 2
1V/DIV
5V/DIV
4.34µs TO 0.01%
5.12µs TO 0.001%
6.24µs TO 0.01%
7.92µs TO 0.001%
0.002%/DIV
0.002%/DIV
TIME (µs)
4µs/DIV
08308-031
40µs/DIV
TIME (µs)
08308-034
–4
08308-030
–20
–5
08308-033
–12
Figure 36. Large Signal Pulse Response and Settling Time, 2 V Step,
VS = 2.7 V
Figure 33. Large Signal Pulse Response and Settling Time, 10 V Step,
VS = ±15 V, G = ½
Rev. C | Page 13 of 24
AD8278/AD8279
5.0
4.5
VS = 5V
2V/DIV
OUTPUT VOLTAGE (V p-p)
4.0
3.5
3.0
VS = 2.7V
2.5
2.0
1.5
1.0
10µs/DIV
0
100
1k
10k
100k
1M
FREQUENCY (Hz)
08308-038
08308-035
0.5
Figure 40. Maximum Output Voltage vs. Frequency, VS = 5 V, 2.7 V
5V/DIV
20mV/DIV
Figure 37. Large Signal Step Response, G = ½
08308-036
CL = 100pF
CL = 147pF
CL = 247pF
10µs/DIV
40µs/DIV
Figure 38. Large Signal Step Response, G = 2
08308-039
NO LOAD
Figure 41. Small Signal Step Response for Various Capacitive Loads, G = ½
30
VS = ±15V
20
20mV/DIV
15
10
VS = ±5V
CL = 100pF
CL = 200pF
5
CL = 247pF
CL = 347pF
1k
10k
FREQUENCY (Hz)
100k
1M
40µs/DIV
08308-037
0
100
Figure 39. Maximum Output Voltage vs. Frequency, VS = ±15 V, ±5 V
08308-040
OUTPUT VOLTAGE (V p-p)
25
Figure 42. Small Signal Step Response for Various Capacitive Loads, G = 2
Rev. C | Page 14 of 24
AD8278/AD8279
50
GAIN = 2
45
40
±2V
±5V
30
1µV/DIV
OVERSHOOT (%)
35
25
±15V
20
GAIN = ½
±18V
15
10
0
50
100
150
200
250
CAPACITIVE LOAD (pF)
1s/DIV
08308-041
0
Figure 46. 0.1 Hz to 10 Hz Voltage Noise
Figure 43. Small Signal Overshoot vs. Capacitive Load, RL ≥ 2 kΩ, G = ½
160
35
140
CHANNEL SEPARATION (dB)
30
±2V
20
15
±5V
±15V
10
±18V
5
2kΩ LOAD
120
100
80
60
40
0
0
50
100
150
200
250
300
350
CAPACITIVE LOAD (pF)
08308-042
20
Figure 44. Small Signal Overshoot vs. Capacitive Load, RL ≥ 2 kΩ, G = 2
1k
GAIN = 2
100
10
0.1
1
10
100
1k
10k
FREQUENCY (Hz)
100k
08308-043
GAIN = ½
Figure 45. Voltage Noise Density vs. Frequency
Rev. C | Page 15 of 24
0
10
100
1k
10k
FREQUENCY (Hz)
Figure 47. Channel Separation
100k
08308-060
OVERSHOOT (%)
25
NOISE (nV/ Hz)
08308-044
5
AD8278/AD8279
THEORY OF OPERATION
CIRCUIT INFORMATION
AC Performance
Each channel of the AD8278 and AD8279 consists of a low power,
low noise op amp and four laser-trimmed on-chip resistors.
These resistors can be externally connected to make a variety
of amplifier configurations, including difference, noninverting,
and inverting configurations. Taking advantage of the integrated
resistors of the AD8278 and AD8279 provides the designer with
several benefits over a discrete design, including smaller size,
lower cost, and better ac and dc performance.
Component sizes and trace lengths are much smaller in an IC
than on a PCB; therefore, the corresponding parasitic elements
are also smaller. This results in better ac performance of the
AD8278 and AD8279. For example, the positive and negative
input terminals of the AD8278 and AD8279 op amps are
intentionally not pinned out. By not connecting these nodes
to the traces on the PCB, their capacitance remains low and
balanced, resulting in improved loop stability and excellent
common-mode rejection over frequency.
+VS
7
DRIVING THE AD8278 AND AD8279
AD8278
20kΩ
40kΩ
5
SENSE
6
OUT
1
REF
4
–VS
Care should be taken to drive the AD8278 and AD8279 with a
low impedance source, for example, another amplifier. Source
resistance of even a few kilohms (kΩ) can unbalance the resistor
ratios and, therefore, significantly degrade the gain accuracy and
common-mode rejection of the AD8278 and AD8279. Because all
configurations present several kilohms (kΩ) of input resistance,
the AD8278 and AD8279 do not require a high current drive
from the source and are easy to drive.
Figure 48. Functional Block Diagram
INPUT VOLTAGE RANGE
DC Performance
Much of the dc performance of op amp circuits depends on the
accuracy of the surrounding resistors. Using superposition to
analyze a typical difference amplifier circuit, as is shown in
Figure 49, the output voltage is found to be
⎛ R2 ⎞⎛
⎟ 1 + R4 ⎞⎟ − V IN − ⎛⎜ R4 ⎞⎟
VOUT = V IN + ⎜
⎜ R1 + R2 ⎟⎜⎝
R3 ⎠
⎝ R3 ⎠
⎠
⎝
This equation demonstrates that the gain accuracy and commonmode rejection ratio of the AD8278 and AD8279 is determined
primarily by the matching of resistor ratios. Even a 0.1%
mismatch in one resistor degrades the CMRR to 69 dB for a
G = 2 difference amplifier.
The AD8278 and AD8279 are able to measure input voltages
beyond the supply rails. The internal resistors divide down
the voltage before it reaches the internal op amp and provide
protection to the op amp inputs. Figure 49 shows an example
of how the voltage division works in a difference amplifier
configuration. For the AD8278 and AD8279 to measure correctly,
the input voltages at the input nodes of the internal op amp
must stay below 1.5 V of the positive supply rail and can exceed
the negative supply rail by 0.1 V. Refer to the Power Supplies
section for more details.
R2 (V )
R1 + R2 IN+
R4
VIN–
The difference amplifier output voltage equation can be reduced to
VOUT =
VIN+
R4
(VIN + − VIN − )
R3
R3
R1
R2
as long as the following ratio of the resistors is tightly matched:
R2 R4
=
R1 R3
The resistors on the AD8278 and AD8279 are laser trimmed to
match accurately. As a result, the AD8278 and AD8279 provide
superior performance over a discrete solution, enabling better
CMRR, gain accuracy, and gain drift, even over a wide temperature range.
R2 (V )
R1 + R2 IN+
08308-062
+IN 3
20kΩ
08308-045
–IN 2
40kΩ
Figure 49. Voltage Division in the Difference Amplifier Configuration
The AD8278 and AD8279 have integrated ESD diodes at the inputs
that provide overvoltage protection. This feature simplifies
system design by eliminating the need for additional external
protection circuitry and enables a more robust system.
The voltages at any of the inputs of the parts can safely range
from +VS − 40 V up to −VS + 40 V. For example, on ±10 V
supplies, input voltages can go as high as ±30 V. Care should be
taken to not exceed the +VS − 40 V to −VS + 40 V input limits
to avoid damaging the parts.
Rev. C | Page 16 of 24
AD8278/AD8279
The AD8278 and AD8279 are typically specified at single and
dual supplies, but they can be used with unbalanced supplies as
well; for example, −VS = −5 V, +VS = +20 V. The difference between
the two supplies must be kept below 36 V. The positive supply
rail must be at least 2 V above the negative supply.
The AD8278 and AD8279 operate extremely well over a very
wide range of supply voltages. They can operate on a single
supply as low as 2 V and as high as 36 V, under appropriate
setup conditions.
R1 (V
)
R1 + R2 REF
For best performance, the user should ensure that the internal
op amp is biased correctly. The internal input terminals of the
op amp must have sufficient voltage headroom to operate
properly. Proper operation of the part requires at least 1.5 V
between the positive supply rail and the op amp input terminals.
This relationship is expressed in the following equation:
R4
R3
R1
R2
VREF
R1 (V
)
R1 + R2 REF
R1
V REF < + VS − 1.5 V
R1 + R2
08308-046
POWER SUPPLIES
Figure 50. Ensure Sufficient Voltage Headroom on the Internal Op Amp
Inputs
For example, when operating on a +VS= 2 V single supply and
VREF = 0 V, it can be seen from Figure 50 that the op amp input
terminals are biased at 0 V, allowing more than the required 1.5 V
headroom. However, if VREF = 1 V under the same conditions, the
input terminals of the op amp are biased at 0.66 V (G = ½). Now
the op amp does not have the required 1.5 V headroom and
cannot function. Therefore, the user must increase the supply
voltage or decrease VREF to restore proper operation.
Use a stable dc voltage to power the AD8278 and AD8279. Noise
on the supply pins can adversely affect performance. Place a
bypass capacitor of 0.1 μF between each supply pin and ground,
as close as possible to each supply pin. Use a tantalum capacitor
of 10 μF between each supply and ground. It can be farther
away from the supply pins and, typically, it can be shared by
other precision integrated circuits.
Rev. C | Page 17 of 24
AD8278/AD8279
APPLICATIONS INFORMATION
–IN
The AD8278 and AD8279 can be configured in several ways
(see Figure 51 to Figure 57). These configurations have excellent
gain accuracy and gain drift because they rely on the internal
matched resistors. Note that Figure 53 shows the AD8278 and
AD8279 as difference amplifiers with a midsupply reference
voltage at the noninverting input. This allows the AD8278 and
AD8279 to be used as a level shifter, which is appropriate in
single-supply applications that are referenced to midsupply.
Table 10 lists several single-ended amplifier configurations
that are not illustrated.
5 20kΩ
+IN
1 20kΩ
3 40kΩ
20kΩ
AD8278
IN
2 40kΩ
5
OUT
6
20kΩ
AD8278
VOUT = –½VIN
Figure 55. Inverting Amplifier, Gain = −½
1
08308-047
2 40kΩ
5
OUT
1 20kΩ
IN
2
3 40kΩ
AD8278
OUT
6
20kΩ
6
Figure 51. Difference Amplifier, Gain = ½
40kΩ
20kΩ
3 40kΩ
AD8278
5 20kΩ
VREF = MIDSUPPLY
Figure 54. Difference Amplifier, Gain = 2, Referenced to Midsupply
OUT
VOUT = ½ (VIN+ − VIN−)
–IN
3
VOUT = 2 (VIN+ − VIN−) + VREF
5
6
+IN
40kΩ
08308-051
20kΩ
OUT
08308-052
2 40kΩ
2
6
1
–IN
40kΩ
08308-050
CONFIGURATIONS
VOUT = 1.5VIN
Figure 56. Noninverting Amplifier, Gain = 1.5
40kΩ
3
5 20kΩ
AD8278
40kΩ
08308-048
+IN
1 20kΩ
VOUT = 2(VIN+ − VIN−)
2
6
OUT
Figure 52. Difference Amplifier, Gain = 2
2 40kΩ
20kΩ
IN
5
6
OUT
1 20kΩ
40kΩ
3
AD8278
VOUT = 2VIN
08308-053
–IN
Figure 57. Noninverting Amplifier, Gain = 2
3 40kΩ
20kΩ
AD8278
VOUT = ½ (VIN+ − VIN−) + VREF
1
VREF = MIDSUPPLY
08308-049
+IN
Figure 53. Difference Amplifier, Gain = ½, Referenced to Midsupply
Table 10. AD8278 Difference and Single-Ended Amplifier Configurations
Amplifier Configuration
Difference Amplifier
Difference Amplifier
Single-Ended Inverting Amplifier
Single-Ended Inverting Amplifier
Single-Ended Noninverting Amplifier
Single-Ended Noninverting Amplifier
Single-Ended Noninverting Amplifier
Single-Ended Noninverting Amplifier
Single-Ended Noninverting Amplifier
Single-Ended Noninverting Amplifier
Signal Gain
+½
+2
−½
−2
+3⁄2
+3
+½
+1
+1
+2
Pin 1 (REF)
GND
IN+
GND
GND
IN
IN
GND
IN
GND
IN
Rev. C | Page 18 of 24
Pin 2 (VIN−)
IN−
OUT
IN
OUT
GND
OUT
GND
GND
OUT
OUT
Pin 3 (VIN+)
IN+
GND
GND
GND
IN
IN
IN
GND
IN
GND
Pin 5 (SENSE)
OUT
IN−
OUT
IN
OUT
GND
OUT
OUT
GND
GND
AD8278/AD8279
The reference must be driven with a low impedance source to
maintain the internal resistor ratio. An example using the low
power, low noise OP1177 as a reference is shown in Figure 58.
INCORRECT
CORRECT
AD8278
AD8278
REF
REF
V
INSTRUMENTATION AMPLIFIER
The AD8278 and AD8279 can be used as building blocks for a
low power, low cost instrumentation amplifier. An instrumentation
amplifier provides high impedance inputs and delivers high
common-mode rejection. Combining the AD8278 with an Analog
Devices, Inc., low power amplifier (see Table 11) creates a precise,
power efficient voltage measurement solution suitable for power
critical systems.
V
–IN
A1
+
20kΩ
RG
Figure 58. Driving the Reference Pin
RF
DIFFERENTIAL OUTPUT
A2
VDIFF_OUT = V+OUT − V−OUT = 2 × GAD8279 × (VIN+ – VIN−)
If the AD8279 amplifiers are each configured for G = ½, the
differential gain is 1×; if the AD8279 amplifiers are each
configured for G = 2, the differential gain is 4×.
+VS
11
AD8279
12
20kΩ
40kΩ
2
13
+IN
14
10
20kΩ
40kΩ
20kΩ
40kΩ
REF
Figure 60. Low Power Precision Instrumentation Amplifier
Table 11. Low Power Op Amps
Op Amp (A1, A2)
AD8506
AD8607
AD8617
AD8667
It is preferable to use dual op amps for the high impedance inputs
because they have better matched performance and track each
other over temperature. The AD8278 and AD8279 difference
amplifiers cancel out common-mode errors from the input op
amps, if they track each other. The differential gain accuracy of
the in-amp is proportional to how well the input feedback
resistors (RF) match each other. The CMRR of the in-amp
increases as the differential gain is increased (1 + 2RF/RG), but a
higher gain also reduces the common-mode voltage range.
6
20kΩ
40kΩ
4
–VS
Features
Dual micropower op amp
Precision dual micropower op amp
Low cost CMOS micropower op amp
Dual precision CMOS micropower op amp
Refer to A Designer’s Guide to Instrumentation Amplifiers for
more design ideas and considerations at www.analog.com,
under Technical Documentation.
3
9
8
+OUT
AD8278/
AD8279
VOUT = (1 + 2RF/RG) (VIN+ – VIN–) × 2
–OUT
5
08308-061
–IN
40kΩ
+IN
The two difference amplifiers of the AD8279 can be configured
to provide a differential output, as shown in Figure 59. This
differential output configuration is suitable for various applications,
such as strain gage excitation and single-ended-to-differential
conversion. The differential output voltage has a gain twice that
of a single AD8279 channel, as shown in the following equation:
VOUT
20kΩ
08308-056
08308-054
–
40kΩ
RF
OP1177
Figure 59. AD8279 Differential Output G = 4 Configuration
Rev. C | Page 19 of 24
AD8278/AD8279
OUTLINE DIMENSIONS
5.00 (0.1968)
4.80 (0.1890)
8
4.00 (0.1574)
3.80 (0.1497)
5
1
4
1.27 (0.0500)
BSC
0.25 (0.0098)
0.10 (0.0040)
6.20 (0.2441)
5.80 (0.2284)
1.75 (0.0688)
1.35 (0.0532)
0.51 (0.0201)
0.31 (0.0122)
COPLANARITY
0.10
SEATING
PLANE
0.50 (0.0196)
0.25 (0.0099)
45°
8°
0°
0.25 (0.0098)
0.17 (0.0067)
1.27 (0.0500)
0.40 (0.0157)
012407-A
COMPLIANT TO JEDEC STANDARDS MS-012-AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
Figure 61. 8-Lead Standard Small Outline Package [SOIC_N]
Narrow Body (R-8)
Dimensions shown in millimeters and (inches)
3.20
3.00
2.80
3.20
3.00
2.80
8
1
5.15
4.90
4.65
5
4
PIN 1
IDENTIFIER
0.65 BSC
0.95
0.85
0.75
15° MAX
1.10 MAX
0.40
0.25
6°
0°
0.23
0.09
COMPLIANT TO JEDEC STANDARDS MO-187-AA
Figure 62. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
Rev. C | Page 20 of 24
0.80
0.55
0.40
10-07-2009-B
0.15
0.05
COPLANARITY
0.10
AD8278/AD8279
8.75 (0.3445)
8.55 (0.3366)
8
14
1
7
1.27 (0.0500)
BSC
0.25 (0.0098)
0.10 (0.0039)
COPLANARITY
0.10
0.51 (0.0201)
0.31 (0.0122)
6.20 (0.2441)
5.80 (0.2283)
0.50 (0.0197)
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
SEATING
PLANE
45°
8°
0°
0.25 (0.0098)
0.17 (0.0067)
1.27 (0.0500)
0.40 (0.0157)
COMPLIANT TO JEDEC STANDARDS MS-012-AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
060606-A
4.00 (0.1575)
3.80 (0.1496)
Figure 63. 14-Lead Standard Small Outline Package [SOIC_N]
Narrow Body (R-14)
Dimensions shown in millimeters and (inches)
ORDERING GUIDE
Model 1
AD8278ARZ
AD8278ARZ-R7
AD8278ARZ-RL
AD8278BRZ
AD8278BRZ-R7
AD8278BRZ-RL
AD8278ARMZ
AD8278ARMZ-R7
AD8278ARMZ-RL
AD8278BRMZ
AD8278BRMZ-R7
AD8278BRMZ-RL
AD8279ARZ
AD8279ARZ-R7
AD8279ARZ-RL
AD8279BRZ
AD8279BRZ-R7
AD8279BRZ-RL
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
8-Lead SOIC_N
8-Lead SOIC_N, 7" Tape and Reel
8-Lead SOIC_N, 13" Tape and Reel
8-Lead SOIC_N
8-Lead SOIC_N, 7" Tape and Reel
8-Lead SOIC_N, 13" Tape and Reel
8-Lead MSOP
8-Lead MSOP, 7" Tape and Reel
8-Lead MSOP, 13" Tape and Reel
8-Lead MSOP
8-Lead MSOP, 7" Tape and Reel
8-Lead MSOP, 13" Tape and Reel
14-Lead SOIC_N
14-Lead SOIC_N, 7" Tape and Reel
14-Lead SOIC_N, 13" Tape and Reel
14-Lead SOIC_N
14-Lead SOIC_N, 7" Tape and Reel
14-Lead SOIC_N, 13" Tape and Reel
Z = RoHS Compliant Part.
Rev. C | Page 21 of 24
Package Option
R-8
R-8
R-8
R-8
R-8
R-8
RM-8
RM-8
RM-8
RM-8
RM-8
RM-8
R-14
R-14
R-14
R-14
R-14
R-14
Branding
Y21
Y21
Y21
Y22
Y22
Y22
AD8278/AD8279
NOTES
Rev. C | Page 22 of 24
AD8278/AD8279
NOTES
Rev. C | Page 23 of 24
AD8278/AD8279
NOTES
©2009–2011 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D08308-0-1/11(C)
Rev. C | Page 24 of 24