Intersil EL2227CYZ Dual very low noise amplifier Datasheet

EL2227
®
Data Sheet
May 1, 2007
Dual Very Low Noise Amplifier
Features
The EL2227 is a dual, low-noise amplifier, ideally suited to
line receiving applications in ADSL and HDSLII designs.
With low noise specification of just 1.9nV/√Hz and
1.2pA/√Hz, the EL2227 is perfect for the detection of very
low amplitude signals.
• Voltage noise of only 1.9nV/√Hz
The EL2227 features a -3dB bandwidth of 115MHz and is
gain-of-2 stable. The EL2227 also affords minimal power
dissipation with a supply current of just 4.8mA per amplifier.
The amplifier can be powered from supplies ranging from
±2.5V to ±12V.
• Just 4.8mA per amplifier
FN7058.3
• Current noise of only 1.2pA/√Hz
• Bandwidth (-3dB) of 115MHz @AV = +2
• Gain-of-2 stable
• 8 Ld MSOP package
• ±2.5V to ±12V operation
• Pb-free plus anneal available (RoHS compliant)
The EL2227 is available in a space-saving 8 Ld MSOP
package as well as the industry-standard 8 Ld SOIC. It can
operate over the -40°C to +85°C temperature range.
Applications
Pinout
• HDSLII receivers
• ADSL receivers
• Ultrasound input amplifiers
EL2227
(8 LD SOIC, 8 LD MSOP)
TOP VIEW
• Wideband instrumentation
• Communications equipment
VOUTA
1
VINA-
2
VINA+
3
-
8
VS+
7
VOUTB
6
VINB-
5
VINB+
• AGC and PLL active filters
• Wideband sensors
+
+
VS-
4
.
Ordering Information
PART
MARKING
PART NUMBER
EL2227CY
L
TEMP RANGE
(°C)
TAPE AND REEL
-40 to +85
-
PACKAGE
8 Ld MSOP (3.0mm)
PKG. DWG.#
MDP0043
EL2227CY-T13
L
-40 to +85
13”
8 Ld MSOP (3.0mm)
MDP0043
EL2227CY-T7
L
-40 to +85
7”
8 Ld MSOP (3.0mm)
MDP0043
EL2227CYZ (Note)
BASAA
-40 to +85
-
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL2227CYZ-T13 (Note)
BASAA
-40 to +85
13”
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL2227CYZ-T7 (Note)
BASAA
-40 to +85
7”
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL2227CS
2227CS
-40 to +85
-
8 Ld SOIC (150 mil)
MDP0027
EL2227CS-T13
2227CS
-40 to +85
13”
8 Ld SOIC (150 mil)
MDP0027
EL2227CS-T7
2227CS
-40 to +85
7”
8 Ld SOIC (150 mil)
MDP0027
EL2227CSZ (Note)
2227CSZ
-40 to +85
-
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
EL2227CSZ-T13 (Note)
2227CSZ
-40 to +85
13”
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
EL2227CSZ-T7 (Note)
2227CSZ
-40 to +85
7”
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate
termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL
classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2004, 2005, 2007. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL2227
Absolute Maximum Ratings
Thermal Information
Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . .28V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . VS- - 0.3V, VS +0.3V
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 40mA
Maximum Die Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
ESD Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2kV
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Pb-free reflow profile . . . . . . . . . . . . . . . . . . . . . . . . . .see link below
http://www.intersil.com/pbfree/Pb-FreeReflow.asp
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
VS+ = +12V, VS- = -12V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C Unless Otherwise
Specified.
PARAMETER
DESCRIPTION
CONDITION
MIN
TYP
MAX
UNIT
-0.2
3
mV
INPUT CHARACTERISTICS
VOS
Input Offset Voltage
TCVOS
Average Offset Voltage Drift
IB
Input Bias Current
RIN
VCM = 0V
-0.6
µV/°C
-3.4
µA
Input Impedance
7.3
MΩ
CIN
Input Capacitance
1.6
pF
CMIR
Common-Mode Input Range
CMRR
Common-Mode Rejection Ratio
for VIN from -11.8V to 10.4V
60
94
dB
AVOL
Open-Loop Gain
-5V ≤ VOUT ≤ 5V
70
87
dB
eN
Voltage Noise
f = 100kHz
1.9
nV/√Hz
iN
Current Noise
f = 100kHz
1.2
pA/√Hz
RL = 500Ω
-10.4
-10
V
RL = 250Ω
-9.8
-9
V
VCM = 0V
-9
-11.8
+10.4
V
OUTPUT CHARACTERISTICS
VOL
Output Swing Low
VOH
Output Swing High
RL = 500Ω
RL = 250Ω
9.5
10
V
ISC
Short Circuit Current
RL = 10Ω
140
180
mA
65
95
dB
10
10.4
V
POWER SUPPLY PERFORMANCE
PSRR
Power Supply Rejection Ratio
VS is moved from ±2.25V to ±12V
IS
Supply Current (Per Amplifier)
No Load
VS
Operating Range
4.8
±2.5
6.5
mA
±12
V
DYNAMIC PERFORMANCE
SR
Slew Rate (Note 2)
±2.5V square wave, measured 25% to 75%
50
V/µS
tS
Settling to 0.1% (AV = +2)
(AV = +2), VO = ±1V
65
ns
BW
-3dB Bandwidth
RF = 358Ω
115
MHz
HD2
2nd Harmonic Distortion
f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω
93
dBc
f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω
83
dBc
f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω
94
dBc
f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω
76
dBc
HD3
3rd Harmonic Distortion
2
40
FN7058.3
May 1, 2007
EL2227
Electrical Specifications
VS+ = +12V, VS- = -12V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C Unless Otherwise
Specified.
PARAMETER
DESCRIPTION
CONDITION
MIN
TYP
MAX
UNIT
0.2
3
mV
INPUT CHARACTERISTICS
VOS
Input Offset Voltage
TCVOS
Average Offset Voltage Drift
IB
Input Bias Current
RIN
VCM = 0V
-0.6
µV/°C
-3.7
µA
Input Impedance
7.3
MΩ
CIN
Input Capacitance
1.6
pF
CMIR
Common-Mode Input Range
CMRR
Common-Mode Rejection Ratio
for VIN from -4.8V to 3.4V
60
97
dB
AVOL
Open-Loop Gain
-5V ≤ VOUT ≤ 5V
70
84
dB
eN
Voltage Noise
f = 100kHz
1.9
nV/√Hz
iN
Current Noise
f = 100kHz
1.2
pA/√Hz
RL = 500Ω
-3.8
-3.5
V
RL = 250Ω
-3.7
-3.5
V
VCM = 0V
-9
-4.8
3.4
V
OUTPUT CHARACTERISTICS
VOL
VOH
ISC
Output Swing Low
Output Swing High
Short Circuit Current
RL = 500Ω
3.5
3.7
V
RL = 250Ω
3.5
3.6
V
RL = 10Ω
60
100
mA
65
95
dB
POWER SUPPLY PERFORMANCE
PSRR
Power Supply Rejection Ratio
VS is moved from ±2.25V to ±12V
IS
Supply Current (Per Amplifier)
No Load
VS
Operating Range
4.5
±2.5
5.5
mA
±12
V
DYNAMIC PERFORMANCE
SR
Slew Rate
±2.5V square wave, measured 25%-75%
tS
Settling to 0.1% (AV = +2)
BW
HD2
HD3
45
V/µS
(AV = +2), VO = ±1V
77
ns
-3dB Bandwidth
RF = 358Ω
90
MHz
2nd Harmonic Distortion
f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω
98
dBc
f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω
90
dBc
f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω
94
dBc
f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω
79
dBc
3rd Harmonic Distortion
3
35
FN7058.3
May 1, 2007
EL2227
4
4
3
3
2
2
RF = 1kΩ
1
RF = 620Ω
0
-1
RF = 100Ω
-2
RF = 350Ω
-3
-4
-5
VS = ±12V
AV = +2
RL = 500Ω
-6
1M
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
Typical Performance Curves
0
-1
RF = 420Ω
-2
RF = 620Ω
-3
-4
-6
1M
100M 200M
RF = 350Ω
1
-5
10M
RF = 100Ω
RF = 1kΩ
VS = ±12V
AV = -1
RL = 500Ω
10M
FIGURE 2. INVERTING FREQUENCY RESPONSE FOR
VARIOUS RF
4
4
3
3
2
AV = 2
0
-1
AV = 10
AV = 5
-2
-3
-4
-5
-6
1M
VS = ±12V
RF = 350Ω
RL = 500Ω
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
FIGURE 1. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS RF
1
2
AV = -10
-2
AV = -5
-3
-4
VS = ±12V
RF = 420Ω
RL = 500Ω
10M
FREQUENCY (Hz)
135
90
90
45
AV = 5
-45
AV = 10
-135
-270
-315
1M
-45
AV = -10
-90
AV = -2
AV = -5
-135
-180
-180
-225
AV = -1
0
AV = 2
PHASE (°)
PHASE (°)
FIGURE 4. INVERTING FREQUENCY RESPONSE (GAIN)
135
-90
100M 200M
FREQUENCY (Hz)
FIGURE 3. NON-INVERTING FREQUENCY RESPONSE
(GAIN)
0
AV = -1
0
-1
-6
1M
100M 200M
AV = -2
1
-5
10M
45
100M 200M
FREQUENCY (Hz)
FREQUENCY (Hz)
-225
VS = ±12
RF = 350Ω
RL = 500Ω
-270
10M
100M 200M
FREQUENCY (Hz)
FIGURE 5. NON-INVERTING FREQUENCY RESPONSE
(PHASE)
4
-315
1M
VS = ±12V
RF = 420Ω
RL = 500Ω
10M
100M 200M
FREQUENCY (Hz)
FIGURE 6. INVERTING FREQUENCY RESPONSE (PHASE)
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
NORMALIZED GAIN (dB)
3
2
1
4
VS = ±12V
RF = 350Ω
AV = +2
RL = 500Ω
3
VIN = 100mVPP
VIN = 20mVPP
0
-1
VIN = 500mVPP
-2
VIN = 1VPP
-3
-4
VIN = 2VPP
-5
-6
100k
NORMALIZED GAIN (dB)
4
2
VIN = 1.4VPP
1
0
-1
VIN = 2.8VPP
-2
VIN = 280mVPP
-3
-4
-5
1M
10M
-6
1M
100M
VS ±12V
RF = 420Ω
RL = 500Ω
AV = -1
10M
FREQUENCY (Hz)
FIGURE 8. INVERTING FREQUENCY RESPONSE FOR
VARIOUS INPUT SIGNAL LEVELS
5
4
3
CL = 12pF
2
1
0
CL = 2pF
-1
-4
-5
1M
CL = 30pF
3
CL = 30pF
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
4
-3
VVSS=±12
= ±12V
VRF = 620Ω
R
RFL=620
= 500Ω
Ω
AV = +2
2
CL = 12pF
1
0
-1
CL = 2pF
-2
-3
VS ± 12V
R F= 420Ω
RL = 500Ω
AV = -1
-4
-5
10M
-6
1M
100M 200M
10M
FREQUENCY (Hz)
FIGURE 10. INVERTING FREQUENCY RESPONSE FOR
VARIOUS CL
4
4
RL = 500Ω
1
0
RL = 50Ω
-1
-2
-5
-6
1M
VS = ±12V
RF = 620Ω
CL = 15pF
AV = +2
NORMALIZED GAIN (dB)
NorMalized GAIN (dB)
2
-4
VO = +10V
3
3
RL = 100Ω
100M 200M
FREQUENCY (Hz)
FIGURE 11. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS RL
5
VO = -10V
2
VO = +5V
1
0
-1
VO = 0V
-2
-3
-4
-5
10M
100M 200M
FREQUENCY (Hz)
FIGURE 9. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS CL
-3
100M 200M
FREQUENCY (Hz)
FIGURE 7. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS INPUT SIGNAL LEVELS
-2
VIN = 20mVPP
VO = -5V
VS = ±12V
RF = 620Ω
RL = 500Ω
AV = +2
-6
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS OUTPUT
DC LEVELS
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
140
AV = +2
RF = 620Ω
RL = 500Ω
AV = -1
AV = +2
80
A V= -2
60
40 A = +5
V
AV = -5
AV = +10
AV = +2
RF = 620Ω
RL = 500Ω
AV = -1
2.5
2
AV = +10
AV = -10
1.5
1
20
0
AV = +2
3
100
PEAKING (dB)
3dB BANDWIDTH (MHz)
120
4
3.5
AV = +5
0.5
AV = -10
2
4
6
8
10
12
0
2
SUPPLY VOLTAGE (±V)
4
6
AV = -2
AV = -5
8
10
12
SUPPLY VOLTAGE (±V)
FIGURE 13. 3dB BANDWIDTH vs SUPPLY VOLTAGE
FIGURE 14. PEAKING vs SUPPLY VOLTAGE
RF = 620Ω
AV = 2
RL = 500Ω
0.5V/DIV
RF = 620Ω
AV = 2
RL = 500Ω
0.5V/DIV
100ns/DIV
100ns/DIV
FIGURE 15. LARGE SIGNAL STEP RESPONSE (VS = ±12V)
FIGURE 16. LARGE SIGNAL STEP RESPONSE (VS = ±2.5V)
RF = 620Ω
AV = 2
RL = 500Ω
20mV/DIV
RF = 620Ω
AV = 2
RL = 500Ω
20mV/DIV
100ns/DIV
FIGURE 17. SMALL SIGNAL STEP RESPONSE (VS = ±12V)
6
100ns/DIV
FIGURE 18. SMALL SIGNAL STEP RESPONSE (VS = ±2.5V)
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
10
0.1
8
GROUP DELAY (ns)
0.08
AV = 5V
6
2
dG (%) OR dP (°)
4
AV = 2V
0
-2
-4
VS = ±12V
RF = 620Ω
RL = 500Ω
PIN = -20dBm into 50Ω
-6
-8
-10
1M
0.04
AV = 2
RF = 620Ω
RL = 150Ω
fO = 3.58MHz
dP
0.02
0
-0.02
-1
100M
10M
0.06
dG
-0.5
FREQUENCY (Hz)
FIGURE 19. GROUP DELAY vs FREQUENCY
OUTPUT IMPEDANCE (Ω)
SUPPLY CURRENT (mA)
1
100
1.2/DIV
6
1.2/DIV
0
6
10
1
0.1
0.01
10k
12
1M
100k
10M
100M
FREQUENCY (Hz)
SUPPLY VOLTAGE (±V)
FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE
FIGURE 22. CLOSED LOOP OUTPUT IMPEDANCE vs
FREQUENCY
110
0
90
20
PSRR (dB)
-CMRR (dB)
0.5
FIGURE 20. DIFFERENTIAL GAIN/PHASE vs DC INPUT
VOLTAGE AT 3.58MHz
12
0
0
DC INPUT VOLTAGE (V)
70
50
30
40
VS-
60
VS+
80
VS = ±12
10
10
100
1k
10k
100k
1M
10M
100M
100
1k
10k
100k
1M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 23. CMRR
FIGURE 24. PSRR
7
10M
100M
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
-40
2nd H
-60
-70
3rd H
-80
-70
2nd H
-80
3rd H
-90
-90
-100
AV = 2
RF = 358Ω
RL = 500Ω
-60
DISTORTION (dBc)
-50
DISTORTION (dBc)
-50
AV = 2
RF = 620Ω
RL = 500Ω
0
4
8
12
16
-100
20
0
OUTPUT SWING (VPP)
-60
-70
-70
THD (dBc)
THD (dBc)
-100
RL = 500
10
RL = 50
RL = 500
-100
-110
100
1000
1
10
100
1000
FREQUENCY (kHz)
FREQUENCY (kHz)
FIGURE 27. TOTAL HARMONIC DISTORTION vs FREQUENCY
@ 2VPP VS = ±12V
FIGURE 28. TOTAL HARMONIC DISTORTION vs FREQUENCY
@ 2VPP VS = ±2.5V
10
0
9
8
7
-20
A→B
IN
GAIN (dB)
VOLTAGE NOISE (nV/√Hz), CURRENT
NOISE (pA/√Hz)
2.5
-90
-120
1
2
-80
RL = 50
-90
-120
1.5
FIGURE 26. 1MHz 2nd and 3rd HARMONIC DISTORTION vs
OUTPUT SWING FOR VS = ±2.5V
-60
-110
1
OUTPUT SWING (VPP)
FIGURE 25. 1MHz 2nd and 3rd HARMONIC DISTORTION vs
OUTPUT SWING FOR VS = ±12V
-80
0.5
6
5
4
3
EN
B→A
-60
-80
2
1
10
-40
100
1k
10k
100k
FREQUENCY (Hz)
FIGURE 29. VOLTAGE AND CURRENT NOISE vs FREQUENCY
8
-100
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 30. CHANNEL TO CHANNEL ISOLATION vs
FREQUENCY
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
150
10
130
9.5
120
IS (mA)
-3dB BANDWIDTH (MHz)
140
110
9
100
90
80
-40
-20
0
20
40
60
80
8.5
-50
100 120 140
DIE TEMPERATURE (°C)
0
50
100
150
DIE TEMPERATURE (°C)
FIGURE 31. -3dB BANDWIDTH vs TEMPERATURE
FIGURE 32. SUPPLY CURRENT vs TEMPERATURE
-2
2
-3
VOS (mV)
IBIAS (µA)
0
-4
-2
-5
-4
-50
0
50
100
-6
-50
150
55
150
160
140
SETTLING TIME (ns)
53
SLEW RATE (V/µs)
100
50
FIGURE 34. INPUT BIAS CURRENT vs TEMPERATURE
FIGURE 33. VOS vs TEMPERATURE
51
49
47
120
0
50
100
150
DIE TEMPERATURE (°C)
FIGURE 35. SLEW RATE vs TEMPERATURE
9
VS = ±2.5V
VO = 2VPP
VS = ±12V
VO = 5VPP
100
80
60
40
20
45
-50
0
DIE TEMPERATURE (°C)
DIE TEMPERATURE (°C)
0
0.01
VS = ±12V
VO = 2VPP
0.1
1
ACCURACY (%)
FIGURE 36. SETTLING TIME vs ACCURACY
FN7058.3
May 1, 2007
EL2227
Typical Performance Curves (Continued)
0.9
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
781mW
POWER DISSIPATION (W)
0.8
0.7
θ
JA
=
607mW
0.6
0.5
θJ
0.4
A=
0.3
MS
OP
8
+2
06
°C
/W
SO
8
+1
60
°C
/W
0.2
0.1
0
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 37. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
Pin Descriptions
EL2227CY
8-PIN MSOP
EL2227CS
8-PIN SO
PIN NAME
PIN
FUNCTION
1
1
VOUTA
Output
EQUIVALENT CIRCUIT
VS+
VOUT
Circuit 1
2
2
VINA-
Input
VS+
VIN+
VIN-
VS-
Circuit 2
3
3
VINA+
Input
4
4
VS-
Supply
5
5
VINB+
Input
6
6
VINB-
Input
Reference Circuit 2
7
7
VOUTB
Output
Reference Circuit 1
8
8
VS+
Supply
10
Reference Circuit 2
FN7058.3
May 1, 2007
EL2227
Applications Information
+12V
Product Description
1k
The EL2227 is a dual voltage feedback operational amplifier
designed especially for DMT ADSL and other applications
requiring very low voltage and current noise. It also features
low distortion while drawing moderately low supply current
and is built on Elantec's proprietary high-speed
complementary bipolar process. The EL2227 use a classical
voltage-feedback topology which allows them to be used in a
variety of applications where current-feedback amplifiers are
not appropriate because of restrictions placed upon the
feedback element used with the amplifier. The conventional
topology of the EL2227 allows, for example, a capacitor to
be placed in the feedback path, making it an excellent choice
for applications such as active filters, sample-and-holds, or
integrators.
ADSL CPE Applications
The low noise EL2227 amplifier is specifically designed for
the dual differential receiver amplifier function with ADSL
transceiver hybrids as well as other low-noise amplifier
applications. A typical ADSL CPE line interface circuit is
shown in Figure 38. The EL2227 is used in receiving DMT
down stream signal. With careful transceiver hybrid design
and the EL2227 1.9nV/√Hz voltage noise and 1.2pA/√Hz
current noise performance, -140dBm/Hz system background
noise performance can be easily achieved.
DRIVER
INPUT
+
-
ROUT
LINE +
RF
RG
ZLINE
RF
ROUT
+
LINE RF
RECEIVE
OUT +
RECEIVE
AMPLIFIERS
RECEIVE
OUT -
+
+
RF
1µF
10k
10k
1k
+
-
1µF
4.7µF
1k
75k
FIGURE 39.
Power Dissipation
With the wide power supply range and large output drive
capability of the EL2227, it is possible to exceed the +150°C
maximum junction temperatures under certain load and
power-supply conditions. It is therefore important to calculate
the maximum junction temperature (TJMAX) for all
applications to determine if power supply voltages, load
conditions, or package type need to be modified for the
EL2227 to remain in the safe operating area. These
parameters are related as follows:
T JMAX = T MAX + ( θ JA × PD MAXTOTAL )
(EQ. 1)
where:
PDMAXTOTAL is the sum of the maximum power
dissipation of each amplifier in the package (PDMAX)
PDMAX for each amplifier can be calculated as follows:
V OUTMAX
PD MAX = 2 × V S × I SMAX + ( V S – V OUTMAX ) × ---------------------------RL
(EQ. 2)
R
RIN
where:
TMAX = Maximum Ambient Temperature
R
RIN
FIGURE 38. TYPICAL LINE INTERFACE CONNECTION
θJA = Thermal Resistance of the Package
PDMAX = Maximum Power Dissipation of 1 Amplifier
VS = Supply Voltage
Disable Function
The EL2227 is in the standard dual amplifier package
without the enable/disable function. A simple way to
implement the enable/disable function is depicted below.
When disabled, both the positive and negative supply
voltages are disconnected (see Figure 39)
IMAX = Maximum Supply Current of 1 Amplifier
VOUTMAX = Maximum Output Voltage Swing of the
Application
RL = Load Resistance
To serve as a guide for the user, we can calculate maximum
allowable supply voltages for the example of the video
cable-driver below since we know that TJMAX = +150°C,
TMAX = +75°C, ISMAX = 9.5mA, and the package θJAs are
shown in Table 1. If we assume (for this example) that we
are driving a back-terminated video cable, then the
11
FN7058.3
May 1, 2007
EL2227
maximum average value (over duty-cycle) of VOUTMAX is
1.4V, and RL = 150Ω, giving the results seen in Table 1.
TABLE 1.
θJA
MAX PDISS @
TMAX
PART
PACKAGE
EL2227CS
SO8
160°C/W 0.406W @ +85°C
EL2227CY
MSOP8
206°C/W 0.315W @ +85°C
MAX VS
Single-Supply Operation
The EL2227 have been designed to have a wide input and
output voltage range. This design also makes the EL2227 an
excellent choice for single-supply operation. Using a single
positive supply, the lower input voltage range is within
200mV of ground (RL = 500Ω), and the lower output voltage
range is within 875mV of ground. Upper input voltage range
reaches 3.6V, and output voltage range reaches 3.8V with a
5V supply and RL = 500Ω. This results in a 2.625V output
swing on a single 5V supply. This wide output voltage range
also allows single-supply operation with a supply voltage as
high as 28V.
Printed-Circuit Layout
The EL2227 are well behaved, and easy to apply in most
applications. However, a few simple techniques will help
assure rapid, high quality results. As with any high-frequency
device, good PCB layout is necessary for optimum
performance. Ground-plane construction is highly
recommended, as is good power supply bypassing. A 0.1µF
ceramic capacitor is recommended for bypassing both
supplies. Lead lengths should be as short as possible, and
bypass capacitors should be as close to the device pins as
possible. For good AC performance, parasitic capacitances
should be kept to a minimum at both inputs and at the
output. Resistor values should be kept under 5kW because
of the RC time constants associated with the parasitic
capacitance. Metal-film and carbon resistors are both
acceptable, use of wire-wound resistors is not recommended
because of their parasitic inductance. Similarly, capacitors
should be low-inductance for best performance.
Gain-Bandwidth Product and the -3dB Bandwidth
The EL2227 have a gain-bandwidth product of 137MHz
while using only 5mA of supply current per amplifier. For
gains greater than 2, their closed-loop -3dB bandwidth is
approximately equal to the gain-bandwidth product divided
by the noise gain of the circuit. For gains less than 2, higherorder poles in the amplifiers' transfer function contribute to
even higher closed loop bandwidths. For example, the
EL2227 have a -3dB bandwidth of 115MHz at a gain of +2,
dropping to 28MHz at a gain of +5. It is important to note that
the EL2227 have been designed so that this “extra”
bandwidth in low-gain applications does not come at the
expense of stability. As seen in the typical performance
curves, the EL2227 in a gain of +2 only exhibit 0.5dB of
peaking with a 1000Ω load.
Output Drive Capability
The EL2227 have been designed to drive low impedance
loads. They can easily drive 6VP-P into a 500Ω load. This
high output drive capability makes the EL2227 an ideal
choice for RF, IF and video applications.
12
FN7058.3
May 1, 2007
EL2227
Small Outline Package Family (SO)
A
D
h X 45°
(N/2)+1
N
A
PIN #1
I.D. MARK
E1
E
c
SEE DETAIL “X”
1
(N/2)
B
L1
0.010 M C A B
e
H
C
A2
GAUGE
PLANE
SEATING
PLANE
A1
0.004 C
0.010 M C A B
L
b
0.010
4° ±4°
DETAIL X
MDP0027
SMALL OUTLINE PACKAGE FAMILY (SO)
INCHES
SYMBOL
SO-14
SO16 (0.300”)
(SOL-16)
SO20
(SOL-20)
SO24
(SOL-24)
SO28
(SOL-28)
TOLERANCE
NOTES
A
0.068
0.068
0.068
0.104
0.104
0.104
0.104
MAX
-
A1
0.006
0.006
0.006
0.007
0.007
0.007
0.007
±0.003
-
A2
0.057
0.057
0.057
0.092
0.092
0.092
0.092
±0.002
-
b
0.017
0.017
0.017
0.017
0.017
0.017
0.017
±0.003
-
c
0.009
0.009
0.009
0.011
0.011
0.011
0.011
±0.001
-
D
0.193
0.341
0.390
0.406
0.504
0.606
0.704
±0.004
1, 3
E
0.236
0.236
0.236
0.406
0.406
0.406
0.406
±0.008
-
E1
0.154
0.154
0.154
0.295
0.295
0.295
0.295
±0.004
2, 3
e
0.050
0.050
0.050
0.050
0.050
0.050
0.050
Basic
-
L
0.025
0.025
0.025
0.030
0.030
0.030
0.030
±0.009
-
L1
0.041
0.041
0.041
0.056
0.056
0.056
0.056
Basic
-
h
0.013
0.013
0.013
0.020
0.020
0.020
0.020
Reference
-
16
20
24
28
Reference
-
N
SO-8
SO16
(0.150”)
8
14
16
Rev. M 2/07
NOTES:
1. Plastic or metal protrusions of 0.006” maximum per side are not included.
2. Plastic interlead protrusions of 0.010” maximum per side are not included.
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994
13
FN7058.3
May 1, 2007
EL2227
Mini SO Package Family (MSOP)
0.25 M C A B
D
MINI SO PACKAGE FAMILY
(N/2)+1
N
E
MDP0043
A
E1
MILLIMETERS
PIN #1
I.D.
1
B
(N/2)
e
H
C
SEATING
PLANE
0.10 C
N LEADS
SYMBOL
MSOP8
MSOP10
TOLERANCE
NOTES
A
1.10
1.10
Max.
-
A1
0.10
0.10
±0.05
-
A2
0.86
0.86
±0.09
-
b
0.33
0.23
+0.07/-0.08
-
c
0.18
0.18
±0.05
-
D
3.00
3.00
±0.10
1, 3
E
4.90
4.90
±0.15
-
E1
3.00
3.00
±0.10
2, 3
e
0.65
0.50
Basic
-
L
0.55
0.55
±0.15
-
L1
0.95
0.95
Basic
-
N
8
10
Reference
-
0.08 M C A B
b
Rev. D 2/07
NOTES:
1. Plastic or metal protrusions of 0.15mm maximum per side are not
included.
L1
2. Plastic interlead protrusions of 0.25mm maximum per side are
not included.
A
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994.
c
SEE DETAIL "X"
A2
GAUGE
PLANE
L
A1
0.25
3° ±3°
DETAIL X
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
14
FN7058.3
May 1, 2007