ON MC44603AP Mixed frequency mode greenline pwm controller Datasheet

Order this document by MC44603A/D
 Fixed Frequency, Variable Frequency,
Standby Mode
The MC44603A is an enhanced high performance controller that is
specifically designed for off–line and dc–to–dc converter applications. This
device has the unique ability of automatically changing operating modes if
the converter output is overloaded, unloaded, or shorted, offering the
designer additional protection for increased system reliability. The
MC44603A has several distinguishing features when compared to
conventional SMPS controllers. These features consist of a foldback facility
for overload protection, a standby mode when the converter output is slightly
loaded, a demagnetization detection for reduced switching stresses on
transistor and diodes, and a high current totem pole output ideally suited for
driving a power MOSFET. It can also be used for driving a bipolar transistor
in low power converters (< 150 W). It is optimized to operate in
discontinuous mode but can also operate in continuous mode. Its advanced
design allows use in current mode or voltage mode control applications.
Current or Voltage Mode Controller
• Operation up to 250 kHz Output Switching Frequency
•
•
•
MIXED FREQUENCY MODE
GREENLINE PWM*
CONTROLLER:
VARIABLE FREQUENCY,
FIXED FREQUENCY,
STANDBY MODE
* PWM = Pulse Width Modulation
16
1
P SUFFIX
PLASTIC PACKAGE
CASE 648
Inherent Feed Forward Compensation
16
Latching PWM for Cycle–by–Cycle Current Limiting
1
Oscillator with Precise Frequency Control
DW SUFFIX
PLASTIC PACKAGE
CASE 751G
(SOP–16L)
High Flexibility
• Externally Programmable Reference Current
•
•
•
•
Secondary or Primary Sensing
Synchronization Facility
High Current Totem Pole Output
PIN CONNECTIONS
Undervoltage Lockout with Hysteresis
Safety/Protection Features
• Overvoltage Protection Against Open Current and Open Voltage Loop
•
•
•
•
•
•
•
VCC
1
VC
2
Output
3
Gnd
4
13 Error Amp Output
Foldback Input
5
Overvoltage
Protection (OVP)
6
12 RPower Standby
Soft–Start/Dmax/
11
Voltage Mode
Current Sense Input
7
10 CT
Demag Detection
8
9
Protection Against Short Circuit on Oscillator Pin
Fully Programmable Foldback
Soft–Start Feature
Accurate Maximum Duty Cycle Setting
Demagnetization (Zero Current Detection) Protection
Internally Trimmed Reference
Enhanced Output Drive
GreenLine Controller: Low Power Consumption in Standby Mode
• Low Startup and Operating Current
•
•
•
16 Rref
R
15 Frequency
Standby
Voltage Feedback
14
Input
Sync Input
(Top View)
Fully Programmable Standby Mode
Controlled Frequency Reduction in Standby Mode
ORDERING INFORMATION
Low dV/dT for Low EMI Radiations
Device
GreenLine is a trademark of Motorola, Inc.
Operating
Temperature Range
MC44603AP
MC44603ADW
Plastic DIP–16
TA = –25° to +85°C
 Motorola, Inc. 1999
MOTOROLA ANALOG IC DEVICE DATA
Package
SOP–16L
Rev 1
1
MC44603A
MAXIMUM RATINGS
Rating
Symbol
Value
Unit
(ICC + IZ)
30
mA
VC
VCC
18
V
IO(Source)
IO(Sink)
–750
750
Output Energy (Capacitive Load per Cycle)
W
5.0
µJ
RF Stby, CT, Soft–Start, Rref, RP Stby Inputs
Vin
–0.3 to 5.5
V
Foldback Input, Current Sense Input,
E/A Output, Voltage Feedback Input,
Overvoltage Protection, Synchronization Input
Vin
Total Power Supply and Zener Current
Supply Voltage with Respect to Ground (Pin 4)
Output Current (Note 1)
Source
Sink
mA
V
–0.3 to
VCC + 0.3
Synchronization Input
High State Voltage
Low State Reverse Current
VIH
VIL
VCC + 0.3
–20
Idemag–ib (Source)
Idemag–ib (Sink)
–4.0
10
IE/A (Sink)
20
mA
PD
RθJA
0.6
100
W
°C/W
PD
RθJA
0.45
145
W
°C/W
Operating Junction Temperature
TJ
150
°C
Operating Ambient Temperature
TA
–25 to +85
°C
Demagnetization Detection Input Current
Source
Sink
V
mA
mA
Error Amplifier Output Sink Current
Power Dissipation and Thermal Characteristics
P Suffix, Dual–In–Line, Case 648
Maximum Power Dissipation at TA = 85°C
Thermal Resistance, Junction–to–Air
DW Suffix, Surface Mount, Case 751G
Maximum Power Dissipation at TA = 85°C
Thermal Resistance, Junction–to–Air
NOTES: 1. Maximum package power dissipation limits must be observed.
2. ESD data available upon request.
ELECTRICAL CHARACTERISTICS (VCC and VC = 12 V, [Note 3], Rref = 10 kΩ, CT = 820 pF, for typical values TA = 25°C,
for min/max values TA = –25° to +85°C [Note 4], unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
VOL
–
–
–
–
1.0
1.4
1.5
2.0
1.2
2.0
2.0
2.7
–
–
–
–
01
0.1
01
0.1
1.0
10
1.0
10
1.0
Unit
OUTPUT SECTION
Output Voltage (Note 5)
Low State (ISink = 100 mA)
Low State (ISink = 500 mA)
High State (ISource = 200 mA)
High State (ISource = 500 mA)
Output
p Voltage
g During
g Initialization Phase
VCC = 0 to 1.0 V, ISink = 10 µA
VCC = 1
1.0
0 to 5
5.0
0V
V, ISi
Sink
k = 100 µA
VCC = 5
5.0
0 to 13 V,
V ISink = 1
1.0
0 mA
V
VOH
VOL
V
Output Voltage Rising Edge Slew–Rate (CL = 1.0 nF, TJ = 25°C)
dVo/dT
–
300
–
V/µs
Output Voltage Falling Edge Slew–Rate (CL = 1.0 nF, TJ = 25°C)
dVo/dT
–
–300
–
V/µs
VFB
2.42
2.5
2.58
V
Input Bias Current (VFB = 2.5 V)
IFB–ib
–2.0
–0.6
–
µA
Open Loop Voltage Gain (VE/A out = 2.0 to 4.0 V)
AVOL
65
70
–
dB
ERROR AMPLIFIER SECTION
Voltage Feedback Input (VE/A out = 2.5 V)
NOTES: 3. Adjust VCC above the startup threshold before setting to 12 V.
4. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
5. VC must be greater than 5.0 V.
2
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (VCC and VC = 12 V, [Note 3], Rref = 10 kΩ, CT = 820 pF, for typical values TA = 25°C,
for min/max values TA = –25° to +85°C [Note 4], unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
–
–
4.0
–
–
5.5
VFBline–reg
–10
–
10
ISink
2.0
12
–
ISource
–2.0
–
–0.2
VOH
VOL
5.5
–
6.5
1.0
7.5
1.1
Reference Output Voltage (VCC = 10 to 15 V)
Vref
2.4
2.5
2.6
V
Reference Current Range (Iref = Vref/Rref, R = 5.0 k to 25 kΩ)
Iref
–500
–
–100
µA
∆Vref
–40
–
40
mV
44.5
44
48
–
51.5
52
–
0.05
–
%/V
ERROR AMPLIFIER SECTION (continued)
Unity Gain Bandwidth
TJ = 25°C
TJ = –25° to +85°C
Voltage Feedback Input Line Regulation (VCC = 10 to 15 V)
Output Current
Sink (VE/A out = 1.5 V, VFB = 2.7 V)
TA = –25° to +85°C
Source (VE/A out = 5.0 V, VFB = 2.3 V)
TA = –25° to +85°C
Output Voltage Swing
High State (IE/A out (source) = 0.5 mA, VFB = 2.3 V)
Low State (IE/A out (sink) = 0.33 mA, VFB = 2.7 V)
BW
MHz
mV
mA
V
REFERENCE SECTION
Reference Voltage Over Iref Range
OSCILLATOR AND SYNCHRONIZATION SECTION
Frequency
TA = 0° to +70°C
TA = –25° to +85°C
Frequency Change with Voltage (VCC = 10 to 15 V)
fOSC
∆fOSC/∆V
kHz
Frequency Change with Temperature (TA = –25° to +85°C)
∆fOSC/∆T
–
0.05
–
%/°C
Oscillator Voltage Swing (Peak–to–Peak)
VOSC(pp)
1.65
1.8
1.95
V
Ratio Charge Current/Reference Current
TA = 0° to +70°C (VCT = 2.0 V)
TA = –25° to +85°C
Icharge/Iref
0.375
0.37
0.4
–
0.425
0.43
78
80
82
0.46
0.43
0.53
–
0.6
0.63
VR F Stby
2.4
2.5
2.6
V
FStby
18
21
24
kHz
IR F Stby
–200
–
–50
µA
VinthH
VinthL
3.2
0.45
3.7
0.7
4.3
0.9
V
ISync–in
–5.0
–
0
µA
tSync
–
–
0.5
µs
Startup Threshold
Vstup–th
13.6
14.5
15.4
V
Output Disable Voltage After Threshold Turn–On (UVLO 1)
TA = 0° to +70°C
TA = –25° to +85°C
Vdisable1
8.6
8.3
9.0
–
9.4
9.6
Reference Disable Voltage After Threshold Turn–On (UVLO 2)
Vdisable2
7.0
7.5
8.0
Fixed Maximum Duty Cycle = Idischarge/(Idischarge + Icharge)
Ratio Standby Discharge Current versus IR F Stby (Note 6)
TA = 0° to +70°C
TA = –25° to +85°C (Note 8)
VR F Stby (IR F Stby = 100 µA)
Frequency in Standby Mode (RF Stby (Pin 15) = 25 kΩ)
Current Range
Synchronization Input Threshold Voltage (Note 7)
Synchronization Input Current
Minimum Synchronization Pulse Width (Note 8)
D
Idisch–Stby/
IR F Stby
–
%
–
UNDERVOLTAGE LOCKOUT SECTION
V
V
NOTES: 13. Adjust VCC above the startup threshold before setting to 12 V.
14. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
16. Standby is disabled for VR P Stby < 25 mV typical.
17. If not used, Synchronization input must be connected to Ground.
18. Synchronization Pulse Width must be shorter than tOSC = 1/fOSC.
MOTOROLA ANALOG IC DEVICE DATA
3
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (VCC and VC = 12 V, [Note 3], Rref = 10 kΩ, CT = 820 pF, for typical values TA = 25°C,
for min/max values TA = –25° to +85°C [Note 4], unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
Vdemag–th
–
Idemag–lb
50
–
–0.5
65
0.25
–
80
–
–
mV
µs
µA
Negative Clamp Level (Idemag = –2.0 mA)
CL(neg)
–
–0.38
–
V
Positive Clamp Level (Idemag = 2.0 mA)
CL(pos)
–
0.72
–
V
0.37
0.36
0.4
–
0.43
0.44
DEMAGNETIZATION DETECTION SECTION (Note 9)
Demagnetization Detect Input
Demagnetization Comparator Threshold (VPin 9 Decreasing)
Propagation Delay (Input to Output, Low to High)
Input Bias Current (Vdemag = 65 mV)
SOFT–START SECTION (Note 11)
Ratio Charge Current/Iref
TA = 0° to +70°C
TA = –25° to +85°C
Iss(ch)/Iref
Discharge Current (Vsoft–start = 1.0 V)
Idischarge
1.5
5.0
–
mA
Vss(CL)
2.2
2.4
2.6
V
Dsoft–start 12k
Dsoft–start
36
–
42
–
49
0
%
VOVP–th
2.42
2.5
2.58
V
1.0
–
3.0
µs
16.1
15.9
17
–
17.9
18.1
1.5
1.4
2.0
–
3.0
3.4
VCS–th
0.86
0.89
0.9
V
Ifoldback–lb
–6.0
–2.0
–
µA
0.37
0.36
0.4
–
0.43
0.44
Clamp Level
Duty Cycle (Rsoft–start = 12 kΩ)
Duty Cycle (Vsoft–start (Pin 11) = 0.1 V)
–
OVERVOLTAGE SECTION
Protection Threshold Level on VOVP
Propagation Delay (VOVP > 2.58 V to Vout Low)
Protection Level on VCC
TA = 0° to +70°C
TA = –25° to +85°C
Input Resistance
TA = 0° to +70°C
TA = –25° to +85°C
VCC prot
V
–
kΩ
FOLDBACK SECTION (Note 10)
Current Sense Voltage Threshold (Vfoldback (Pin 5) = 0.9 V)
Foldback Input Bias Current (Vfoldback (Pin 5) = 0 V)
STANDBY SECTION
Ratio IR P Stby/Iref
TA = 0° to +70°C
TA = –25° to +85°C
IR P Stby/Iref
Ratio Hysteresis (Vh Required to Return to Normal Operation from Standby
Operation)
TA = 0° to +70°C
TA = –25° to +85°C
Vh/VR P Stby
–
–
1.42
1.4
1.5
–
1.58
1.6
VCS–Stby
0.28
0.31
0.34
V
Maximum Current Sense Input Threshold
(Vfeedback (Pin 14) = 2.3 V and Vfoldback (Pin 6) = 1.2 V)
VCS–th
0.96
1.0
1.04
V
Input Bias Current
ICS–ib
–10
–2.0
–
µA
–
–
120
200
ns
–
13
0.3
17
0.45
20
Current Sense Voltage Threshold (VR P Stby (Pin 12) = 1.0 V)
CURRENT SENSE SECTION
Propagation Delay (Current Sense Input to Output at VTH of
MOS transistor = 3.0 V)
TOTAL DEVICE
Power Supply Current
Startup (VCC = 13 V with VCC Increasing)
Operating TA = –25° to +85°C (Note 3)
ICC
Power Supply Zener Voltage (ICC = 25 mA)
VZ
18.5
–
–
V
–
–
155
–
°C
Thermal Shutdown
mA
NOTES: 13. Adjust VCC above the startup threshold before setting to 12 V.
14. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
19. This function can be inhibited by connecting Pin 8 to Gnd. This allows a continuous current mode operation.
10. This function can be inhibited by connecting Pin 5 to VCC.
11. The MC44603A can be shut down by connecting the Soft–Start pin (Pin 11) to Ground.
4
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Representative Block Diagram
RF Stby
Rref
RF Stby 15 16 Vref
Negative
Active
Clamp
Demag
Detect
8
R
Q
S
UVLO2
VCC
+
65 mV
VDemag Out
+
3.7 V
Sync
Input
9
Vref
Vref
VOSC prot
Iref
Vaux
VCC
Reference
Block
Synchro
+
0.7 V
0.4 Iref
18.0 V
+
1
14.5 V/7.5 V
To Power
Transformer
IF Stby
1.0 V
R
VC
Q
1.6 V
CT
10
S
R
2
Q
S
+
CT
VOSC
3.6 V
Output
S
3
Q
R
0.4 Iref
Vref Vref
0.4 Iref
Vref
0.6 Iref
0.8 Iref
RPwr Stby
12
Compen–
sation
13
5
Foldback
Input
IDischarge
Vref
Vref
0.25
IF Stby
0.2 Iref
IDischarge/2
2R
+
2.5 V
Vref
VOVP
Out
Vref
4
Gnd
VCC
Vref
0.4 Iref
11.6 k
5.0 µs
Delay
OVP
2.0 k
VCC
1.0 mA
Feed–
back
14
2.0 µs
Delay
Thermal
Shutdown
+
Current Mirror X2
6
ROVP
+ 2.5 V
1.6 V
Error Amplifier
Current
Sense Input
7
R
1.0 V
UVLO1
2.4 V
5.0 mA
VCC
+
9.0 V
11 SS/Dmax/VM
= Sink only
= Positive True Logic
RSS
CSS
This device contains 243 active transistors.
MOTOROLA ANALOG IC DEVICE DATA
5
MC44603A
Figure 1. Timing Resistor versus
Oscillator Frequency
10000
CT = 100 pF
VCC = 16 V
TA = 25°C
CT = 500 pF
VCC = 16 V
TA = 25°C
Rref = 10 k
C T, TIMING CAPACITOR (pF)
Rref , TIMING RESISTANCE (k Ω )
100
Figure 2. Standby Mode Timing Capacitor
versus Oscillator Frequency
CT = 1000 pF
10
RF Stby = 2.0 k
RF Stby = 5.0 k
1000
RF Stby = 27 k
RF Stby = 100 k
CT = 2200 pF
3.0
10 k
100 k
300
10 k
1.0 M
100 k
fOSC, Oscillator Frequency (Hz)
Figure 3. Oscillator Frequency
versus Temperature
Figure 4. Ratio Charge Current/Reference
Current versus Temperature
Icharge/Iref = RATIO CHARGE CURRENT/
REFERENCE CURRENT
f OSC, OSCILLATOR FREQUENCY (kHz)
52
51
50
49
48
47
46
VCC = 12 V
Rref = 10 k
CT = 820 pF
45
44
–50
–25
0
25
50
75
100
0.43
0.42
0.41
0.40
0.39
VCC = 12 V
Rref = 10 k
CT = 820 pF
0.38
0.37
–50
–25
0
TA, AMBIENT TEMPERATURE (°C)
50
0
40
–200
30
–400
20
Voltage
–600
10
–800
0
–10
–1000
1.0 µs/Div
6
VO , OUTPUT DRIVE VOLTAGE (V)
Current
60
70
VO , OUTPUT DRIVE VOLTAGE (V)
I O , OUTPUT CURRENT (mA)
200
50
75
100
Figure 6. Output Cross Conduction
70
VCC = 12 V
CL = 2200 pF
TA = 25°C
25
TA, AMBIENT TEMPERATURE (°C)
Figure 5. Output Waveform
600
400
1.0 M
fOSC, Oscillator Frequency (Hz)
60
50
300
VCC = 12 V
CL = 2200 pF
TA = 25°C
200
100
Current
40
0
30
–100
20
10
–200
VO
–300
Voltage
0
–10
–400
ICC
–500
1.0 µs/Div
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
VOH , SOURCE OUTPUT SATURATION VOLTAGE (V)
Figure 7. Oscillator Discharge Current
versus Temperature
475
450
425
400
375
VCC = 12 V
Rref = 10 k
CT = 820 pF
350
325
300
–50
–25
0
25
50
75
100
2.5
2.0
1.5
VCC = 12 V
Rref = 10 k
CT = 820 pF
TA = 25°C
1.0
0
100
Figure 9. Sink Output Saturation Voltage
versus Sink Current
Sink Saturation
(Load to VCC)
40
20
TA = 25°C
VCC = 12 V
80 µs Pulsed Load
120 Hz Rate
0.4
500
200
300
400
50
500
100
101
Figure 11. Voltage Feedback Input
versus Temperature
VFB, VOLTAGE FEEDBACK INPUT (V)
2.60
VCC = 12 V
G = 10
VO = 2.0 to 4.0 V
RL = 100 k
2.50
2.45
–25
0
25
50
TA, AMBIENT TEMPERATURE (°C)
MOTOROLA ANALOG IC DEVICE DATA
10 2
–40
104
103
f, FREQUENCY (kHz)
75
100
Vdemag–th, DEMAG COMPARATOR THRESHOLD (mV)
Isink, SINK OUTPUT CURRENT (mA)
2.55
140
0
–20
100
VCC = 12 V
G = 10
Vin = 30 mV
VO = 2.0 to 4.0 V
RL = 100 k
TA = 25°C
60
0.8
2.40
–50
400
80
1.2
0
0
300
Figure 10. Error Amplifier Gain and Phase
versus Frequency
2.0
1.6
200
Isource, OUTPUT SOURCE CURRENT (mA)
GAIN (dB)
VOL , SINK OUTPUT SATURATION VOLTAGE (V)
TA, AMBIENT TEMPERATURE (°C)
PHASE (DEGREES)
Idisch , DISCHARGE CURRENT (µA)
500
Figure 8. Source Output Saturation Voltage
versus Load Current
Figure 12. Demag Comparator Threshold
versus Temperature
80
VCC = 12 V
75
70
65
60
55
50
–50
–25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
7
100
A VCS, CURRENT SENSE GAIN
3.2
3.1
3.0
VCC = 12 V
Rref = 10 k
CT = 820 pF
2.9
2.8
–50
Figure 14. Thermal Resistance and Maximum
Power Dissipation versus P.C.B. Copper Length
–25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
80
L
PD(max) for TA = 70°C
20
3.0
1.0
0
50
0
0
10
20
30
L, LENGTH OF COPPER (mm)
40
Figure 16. Startup Current versus VCC
0.35
0.30
STARTUP CURRENT (mA)
PROPAGATION DELAY (ns)
4.0
2.0
40
140
120
100
VCC = 12 V
Rref = 10 k
CT = 820 pF
80
–50
0.25
0.20
0.15
0.10
Rref = 10 k
CT = 820 pF
0.05
0
–25
0
25
50
75
100
0
2.0
4.0
8.0
6.0
10
12
TA, AMBIENT TEMPERATURE (°C)
VCC, SUPPLY VOLTAGE (V)
Figure 17. Supply Current versus
Supply Voltage
Figure 18. Power Supply Zener Voltage
versus Temperature
14
21.5
16
14
VZ, ZENER VOLTAGE (V)
ICC , SUPPLY CURRENT (mA)
2.0 oz
Copper
L
3.0 mm
Graphs represent symmetrical layout
RθJA
60
Figure 15. Propagation Delay Current Sense
Input to Output versus Temperature
12
10
8.0
6.0
4.0
2.0
0
2.0
TA = 25°C
Rref = 10 k
CT = 820 pF
VFB = 0 V
VCS = 0 V
4.0
6.0
8.0
10
12
VCC, SUPPLY VOLTAGE (V)
8
ÉÉÉ
ÉÉ
ÉÉÉÉÉ
5.0
Printed circuit board heatsink example
P D, MAXIMUM POWER DISSIPATION (W)
Figure 13. Current Sense Gain
versus Temperature
R θ JA , THERMAL RESISTANCE JUNCTION–TO–AIR (° C/W)
MC44603A
14
16
21.0
20.5
20.0
19.5
19.0
–50
ICC = 25 mA
–25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
MOTOROLA ANALOG IC DEVICE DATA
Figure 19. Startup Threshold Voltage
versus Temperature
Figure 20. Disable Voltage After Threshold
Turn–On (UVLO1) versus Temperature
9.50
15.0
9.25
Vdisable1 , UVLO1 (V)
15.5
14.5
VCC Increasing
14.0
13.5
–50
–25
0
25
50
75
Vdisable2 , UVLO2 (V)
25
50
75
Figure 22. Protection Threshold Level on
VOVP versus Temperature
7.4
VCC Decreasing
7.2
7.0
–25
0
25
50
75
100
2.55
2.50
2.45
VCC = 12 V
2.40
2.35
2.30
–50
–25
0
25
50
75
TA, AMBIENT TEMPERATURE (°C)
Figure 23. Protection Level on VCC
versus Temperature
Figure 24. Propagation Delay (VOVP > 2.58 V
to Vout Low) versus Temperature
3.0
PROPAGATION DELAY (µs)
Rref = 10 k
CT = 820 pF
Pin 6 Open
17
16.5
–25
0
25
50
TA, AMBIENT TEMPERATURE (°C)
MOTOROLA ANALOG IC DEVICE DATA
75
100
100
2.60
TA, AMBIENT TEMPERATURE (°C)
18
VCC prot , PROTECTION LEVEL (V)
0
Figure 21. Disable Voltage After Threshold
Turn–On (UVLO2) versus Temperature
7.6
16
–50
–25
TA, AMBIENT TEMPERATURE (°C)
7.8
17.5
VCC Decreasing
8.55
TA, AMBIENT TEMPERATURE (°C)
8.0
6.8
–50
9.00
8.50
–50
100
VOVP–th, PROTECTION THRESHOLD LEVEL (V)
Vstup–th , STARTUP THRESHOLD VOLTAGE (V)
MC44603A
100
2.5
2.0
VCC = 12 V
Rref = 10 k
CT = 820 pF
1.5
1.0
–50
–25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
9
Figure 25. Standby Reference Current
versus Temperature
Figure 26. Current Sense Voltage Threshold
Standby Mode versus Temperature
270
VCS–stby , CURRENT SENSE THRESHOLD
STANDBY MODE (V)
I R P Stby , STANDBY REFERENCE CURRENT (µA)
MC44603A
265
260
255
250
VR P Stdby (Pin 12)
Voltage Increasing
245
240
235
230
–50
–25
0
25
50
75
100
0.33
0.32
VCC = 12 V
Rref = 10 k
CT = 820 pF
Pin 12 Clamped
at 1.0 V
0.31
0.30
–50
–25
0
TA, AMBIENT TEMPERATURE (°C)
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
PIN FUNCTION DESCRIPTION
Pin
10
Name
Description
1
VCC
This pin is the positive supply of the IC. The operating voltage range after startup is 9.0 to 14.5 V.
2
VC
The output high state (VOH) is set by the voltage applied to this pin. With a separate connection to the
power source, it can reduce the effects of switching noise on the control circuitry.
3
Output
Peak currents up to 750 mA can be sourced or sunk, suitable for driving either MOSFET or Bipolar
transistors. This output pin must be shunted by a Schottky diode, 1N5819 or equivalent.
4
Gnd
The ground pin is a single return, typically connected back to the power source; it is used as control and
power ground.
5
Foldback Input
The foldback function provides overload protection. Feeding the foldback input with a portion of the VCC
voltage (1.0 V max) establishes on the system control loop a foldback characteristic allowing a smoother
startup and sharper overload protection. Above 1.0 V the foldback input is inactive.
6
Overvoltage
Protection
When the overvoltage protection pin receives a voltage greater than 17 V, the device is disabled and
requires a complete restart sequence. The overvoltage level is programmable.
7
Current Sense
Input
A voltage proportional to the current flowing into the power switch is connected to this input. The PWM
latch uses this information to terminate the conduction of the output buffer when working in a current
mode of operation. A maximum level of 1.0 V allows either current or voltage mode operation.
8
Demagnetization
Detection
A voltage delivered by an auxiliary transformer winding provides to the demagnetization pin an indication
of the magnetization state of the flyback transformer. A zero voltage detection corresponds to complete
core saturation. The demagnetization detection ensures a discontinuous mode of operation. This
function can be inhibited by connecting Pin 8 to Gnd.
9
Synchronization
Input
The synchronization input pin can be activated with either a negative pulse going from a level between
0.7 V and 3.7 V to Gnd or a positive pulse going from a level between 0.7 V and 3.7 V up to a level
higher than 3.7 V. The oscillator runs free when Pin 9 is connected to Gnd.
10
CT
The normal mode oscillator frequency is programmed by the capacitor CT choice together with the Rref
resistance value. CT, connected between Pin 10 and Gnd, generates the oscillator sawtooth.
11
Soft–Start/Dmax/
Voltage–Mode
A capacitor, resistor or a voltage source connected to this pin limits the switching duty–cycle. This pin
can be used as a voltage mode control input. By connecting Pin 11 to Ground, the MC44603A can be
shut down.
12
RP Standby
A voltage level applied to the RP Standby pin determines the output power level at which the oscillator will
turn into the reduced frequency mode of operation (i.e. standby mode). An internal hysteresis
comparator allows to return in the normal mode at a higher output power level.
13
E/A Out
The error amplifier output is made available for loop compensation.
14
Voltage Feedback
This is the inverting input of the Error Amplifier. It can be connected to the switching power supply output
through an optical (or other) feedback loop.
15
RF Standby
The reduced frequency or standby frequency programming is made by the RF Standby resistance choice.
16
Rref
Rref sets the internal reference current. The internal reference current ranges from 100 µA to 500 µA.
This requires that 5.0 kΩ ≤ Rref ≤ 25 kΩ.
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 27. Starting Behavior and Overvoltage Management
No–Take Over
Startup
VCC
VCC prot
Vstup–th
Loop Failure
Restart
>2.0 µs
Normal Mode
Vdisable1
Vdisable2
Vref
UVLO1
VPin 11
(Soft–Start)
VOVP Out
ÏÏ
ÏÏÏÏÏÏÏÏ
ÏÏÏ
ÏÏ
ÏÏÏÏÏÏÏÏ
ÏÏÏ
ÏÏ ÏÏÏÏÏÏÏÏ ÏÏÏ
Output
ICC
17 mA
0.3 mA
Figure 28. Demagnetization
VDemag In
Output
(Pin 3)
VDemag Out
VDemag In
Demagnetization
Management
VDemag Out
Oscillator
Buffer
MOTOROLA ANALOG IC DEVICE DATA
Output
11
MC44603A
Figure 29. Switching Off Behavior
VCC
Vstup–th
Vdisable1
Vdisable2
Vref
UVLO1
VPin 11
(Soft–Start)
ÏÏÏ
ÏÏÏ
Output
(Pin 3)
ICC
17 mA
0.3 mA
Figure 30. Oscillator
3.6 V
VCT
1.0 V
1.6 V
VStby
VDemag Out
VOSC
VOSC prot
VDemag Out
Synchronization
Input
VOSC prot
Oscillator
VOSC
CT
VStby
12
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 31. Soft–Start & Dmax
Vref
VCSS + 1.6 V
Internal Clamp
Soft–Start
External Clamp
VCT 3.6 V
VCT low 1.6 V
VOSC
Output
(Pin 3)
OPERATING DESCRIPTION
Error Amplifier
A fully compensated Error Amplifier with access to the
inverting input and output is provided. It features a typical dc
voltage gain of 70 dB. The noninverting input is internally
biased at 2.5 V and is not pinned out. The converter output
voltage is typically divided down and monitored by the
inverting input. The maximum input bias current with the
inverting input at 2.5 V is –2.0 µA. This can cause an output
voltage error that is equal to the product of the input bias
current and the equivalent input divider source resistance.
The Error Amp output (Pin 13) is provided for external loop
compensation. The output voltage is offset by two diode
drops (≈ 1.4 V) and divided by three before it connects to the
inverting input of the Current Sense Comparator. This
guarantees that no drive pulses appear at the Output (Pin 3)
when Pin 13 is at its lowest state (VOL). The Error Amp
minimum feedback resistance is limited by the amplifier’s
minimum source current (0.2 mA) and the required output
voltage (VOH) to reach the current sense comparator’s 1.0 V
clamp level:
Rf(min)
[ 3.0 (1.00.2V)mA) 1.4 V + 22 kW
MOTOROLA ANALOG IC DEVICE DATA
Figure 32. Error Amplifier Compensation
+
1.0 mA
Compensation
RFB
Cf
Error
Amplifier
13
Rf
14 2.5 V
R
Voltage
Feedback
Input
Current Sense
Comparator
1.0 V
5
Foldback
Input
R1
R2
2R
Gnd
4
From Power Supply Output
Current Sense Comparator and PWM Latch
The MC44603A can operate as a current mode controller
or as a voltage mode controller. In current mode operation,
the MC44603A uses the current sense comparator. The
output switch conduction is initiated by the oscillator and
terminated when the peak inductor current reaches the
13
MC44603A
threshold level established by the Error Amplifier output (Pin
13). Thus, the error signal controls the peak inductor current
on a cycle–by–cycle basis. The Current Sense Comparator
PWM Latch ensures that only a single pulse appears at the
Source Output during the appropriate oscillator cycle.
The inductor current is converted to a voltage by inserting
the ground referenced sense resistor RS in series with the
power switch Q1.
This voltage is monitored by the Current Sense Input
(Pin 7) and compared to a level derived from the Error Amp
output. The peak inductor current under normal operating
conditions is controlled by the voltage at Pin 13 where:
Figure 34. Oscillator
Vref
0.4 Iref
CVOS prot
1.0 V
VOSC prot
VOSC
COSC Low
CT < 1.6 V
Discharge
R Q
COSC High
Disch
S
1.6 V
10
CT
R Q
LOSC
S
Synchro
3.6 V
[
VDemag
Out
COSC Regul
V(Pin 13) – 1.4 V
Ipk
3 RS
The Current Sense Comparator threshold is internally
clamped to 1.0 V. Therefore, the maximum peak switch
current is:
1.0 V
Ipk(max)
RS
0
1
1
0
IRegul
[
IDischarge
Figure 35. Simplified Block Oscillator
Figure 33. Output Totem Pole
Vin
Vref
VC
UVLO
14
ICharge
0.4 Iref
VOSC prot
10
R2
VDemag Out
Thermal
Protection
Q1
3
S
R Q
R
PWM
Latch
Current Sense
Comparator
0
D
1N5819
R3
CT
1
0: Discharge Phase
1: Charge Phase
IDischarge
Current
Substrate Sense
7
IRegul
R
C
RS
Series gate resistor, R2, will dampen any high frequency oscillations caused by
the MOSFET input capacitance and any series wiring inductance in the
gate–source circuit. Diode D is required if the negative current into the output
drive pin exceeds 15 mA.
Oscillator
The oscillator is a very accurate sawtooth generator that
can work either in free mode or in synchronization mode. In
this second mode, the oscillator stops in the low state and
waits for a demagnetization or a synchronization pulse to
start a new charging cycle.
• The Sawtooth Generation:
In the steady state, the oscillator voltage varies between
about 1.6 V and 3.6 V.
The sawtooth is obtained by charging and discharging an
external capacitor CT (Pin 10), using two distinct current
sources = Icharge and Idischarge. In fact, CT is permanently
connected to the charging current source (0.4 Iref) and so,
the discharge current source has to be higher than the
charge current to be able to decrease the CT voltage (refer
to Figure 35).
This condition is performed, its value being (2.0 Iref) in
normal working and (0.4 Iref + 0.5 IF Stby in standby mode).
14
COSC Regul
1.6 V
Two comparators are used to generate the sawtooth. They
compare the CT voltage to the oscillator valley (1.6 V) and
peak reference (3.6 V) values. A latch (Ldisch) memorizes the
oscillator state.
In addition to the charge and discharge cycles, a third
state can exist. This phase can be produced when, at the end
of the discharge phase, the oscillator has to wait for a
synchronization or demagnetization pulse before restarting.
During this delay, the CT voltage must remain equal to the
oscillator valley value ( 1.6 V). So, a third regulated current
source IRegul controlled by COSC Regul, is connected to CT in
order to perfectly compensate the (0.4 Iref) current source
that permanently supplies CT.
The maximum duty cycle is 80%. Indeed, the on–time is
allowed only during the oscillator capacitor charge.
]
Consequently:
Tcharge = CT x ∆V/Icharge
Tdischarge = CT x ∆V/Idischarge
where:
Tcharge is the oscillator charge time
∆V is the oscillator peak–to–peak value
Icharge is the oscillator charge current
and
Tdischarge is the oscillator discharge time
Idischarge is the oscillator discharge current
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
So, as fS = 1 /(Tcharge + Tdischarge) when the Regul
arrangement is not activated, the operating frequency can be
obtained from the graph in Figure 1.
NOTE: The output is disabled by the signal VOSC prot when
VCT is lower than 1.0 V (refer to Figure 30).
Synchronization and Demagnetization Blocks
To enable the output, the LOSC latch complementary
output must be low. Reset is activated by the Ldisch output
during the discharge phase. To restart, the LOSC has to be set
(refer to Figure 34). To perform this, the demagnetization
signal and the synchronization must be low.
• Synchronization:
The synchronization block consists of two comparators
that compare the synchronization signal (external) to 0.7 and
3.7 V (typical values). The comparators’ outputs are
connected to the input of an AND gate so that the final output
of the block should be :
– high when 0.7 < SYNC < 3.7 V
– low in the other cases.
A diode D has been incorporated to clamp the positive
applied voltages while an active clamping system limits the
negative voltages to typically –0.33 V. This negative clamp
level is sufficient to avoid the substrate diode switching on.
In addition to the comparator, a latch system has been
incorporated in order to keep the demagnetization block
output level low as soon as a voltage lower than 65 mV is
detected and as long as a new restart is produced (high level
on the output) (refer to Figure 38). This process prevents
ringing on the signal at Pin 8 from disrupting the
demagnetization detection. This results in a very accurate
demagnetization detection.
The demagnetization block output is also directly
connected to the output, disabling it during the
demagnetization phase (refer to Figure 33).
NOTE: The demagnetization detection can be inhibited by
connecting Pin 8 to the ground.
Figure 38. Demagnetization Block
Oscillator
Output
R Q
Demag
S
Buffer
As a low level is necessary to enable the output,
synchronized low level pulses have to be generated on the
output of the synchronization block. If synchronization is not
required, the Pin 9 must be connected to the ground.
VCC
Figure 36. Synchronization
Negative Active
Clamping System
VDemag Out
3.7 V
8
C Dem
Oscillator
65 mV
Sync
D
9
Standby
Output Buffer
0.7 V
• Power Losses in a Classical Flyback Structure
• Demagnetization:
In flyback applications, a good means to detect magnetic
saturation of the transformer core, or demagnetization,
consists in using the auxiliary winding voltage. This voltage is:
– negative during the on–time,
– positive during the off–time,
– equal to zero for the dead–time with generally some
– ringing (refer to Figure 37).
That is why, the MC44603A demagnetization detection
consists of a comparator that can compare the auxiliary
winding voltage to a reference that is typically equal to
65 mV.
Figure 39. Power Losses in a Classical
Flyback Structure
RICL
AC Line
Clamping
Network
Vin
+
+
Rstartup
VCC
MC44603A
RS
Figure 37. Demagnetization Detection
Snubber
Zero Current
Detection
VPin 8
0.75 V
65 mV
–0.33 V
In a classical flyback (as depicted in Figure 39), the
standby losses mainly consist of the energy waste due to:
– the startup resistor Rstartup
– the consumption of the IC and
– the power switch control
– the inrush current limitation resistor RICL
– the switching losses in the power switch
– the snubber and clamping network
Pstartup
Pcontrol
PICL
PSW
PSN–CLN
Pstartup is nearly constant and is equal to:
On–Time
Off–Time
Dead–Time
MOTOROLA ANALOG IC DEVICE DATA
ǒ(Vin–VCC)2ńRstartupǓ
15
MC44603A
PICL only depends on the current drawn from the mains.
Losses can be considered constant. This waste of energy
decreases when the standby losses are reduced.
Pcontrol increases when the oscillator frequency is
increased (each switching requires some energy to turn on
the power switch).
PSW and PSN–CLN are proportional to the switching
frequency.
Consequently, standby losses can be minimized by
decreasing the switching frequency as much as possible.
The MC44603A was designed to operate at a standby
frequency lower than the normal working one.
• Standby Power Calculations with MC44603A
During a switching period, the energy drawn by the
transformer during the on–time to be transferred to the output
during the off–time, is equal to:
1 x L x I 2
E
pk
2
where:
+
– L is the transformer primary inductor,
– lpk is the inductor peak current.
Input power is labelled Pin:
Pin
+ 0.5 x L x Ipk2 x fS
Ipk
ǒ
+
And as:
Ǔ
+ RP Stby x 0.4 x Iref
+ RR P Stby x 0.4 x RVref
ref
VR P Stby
+ 10.6 x VRrefS x Rref
RP Stby
x
Ǹ
PthL
L x fS
Thus, when the power drawn by the converter decreases,
VCS decreases and when VCS becomes lower than [VCS–th
x (VR P Stby)/3], the standby mode is activated. This results in
an oscillator discharge current reduction in order to increase
the oscillator period and to diminish the switching frequency.
As it is represented in Figure 40, the (0.8 x Iref) current
source is disconnected and is replaced by a lower value one
(0.25 x IF Stby).
Where: IF Stby = Vref/RF Stby
where fS is the normal working switching frequency.
Also,
The V CS threshold level is typically equal to
[(VR P Stby)/3] and if the corresponding power threshold is
labelled PthL:
VR P Stby 2
PthL
0.5 x L x
x fS
3.0 RS
+ VRCS
S
where RS is the resistor used to measure the power switch
current.
Thus, the input power is proportional to VCS2 (VCS being
the internal current sense comparator input).
That is why the standby detection is performed by creating
a VCS threshold. An internal current source (0.4 x Iref) sets
the threshold level by connecting a resistor to Pin 12.
As depicted in Figure 40, the standby comparator
noninverting input voltage is typically equal to (3.0 x VCS + VF)
while the inverter input value is (VR P Stby + VF).
In order to prevent undesired mode switching when power
is close to the threshold value, a hysteresis that is
proportional to VR P Stby is incorporated creating a second
VCS threshold level that is equal to [2.5 x (VR P Stby)/3]. When
the standby comparator output is high, a second current
source (0.6 x Iref) is connected to Pin 12.
Finally, the standby mode function can be shown
graphically in Figure 41.
Figure 41. Dynamic Mode Change
Pin
fS
Figure 40. Standby
Vref Vref
0.6 Iref
0.4 Iref
RP Stby
12
0
0.8 Iref
1
CStby
13
ERAmpOut
Oscillator
Discharge
Current
Vref Vref
1
Vref
0.25
IF Stby
0.2 Iref
0
1R
IDischarge
C. S. Comparator
Current Mirror X2
fStby
PthH
Standby
PthL
[(VR P Stby)/3]
IDischarge/2
2R
Normal
Working
VCS
2.5 x [(VR P Stby)/3] 1
This curve shows that there are two power threshold
levels:
– the low one:
PthL fixed by VR P Stby
– the high one:
+ (2.5)2 x PthL x fStby
fS
fStby
PthH + 6.25 x PthL x
fS
PthH
16
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Maximum Duty Cycle and Soft–Start Control
Maximum duty cycle can be limited to values less than
80% by utilizing the Dmax and soft–start control. As depicted
in Figure 42, the Pin 11 voltage is compared to the oscillator
sawtooth.
Figure 42. Dmax and Soft–Start
Vref
VO
Nominal
New Startup
Sequence Initiated
11
Soft–Start
Capacitor
Ipk max
Vout
Output
Control
0.4 Iref
DZ
Figure 45. Foldback Characteristic
2.4 V CDmax
Dmax
VCC
Vdisable2
Output
Drive
Iout
Overload
VOSC
NOTE: Foldback is disabled by connecting Pin 5 to VCC.
Oscillator
Figure 43. Maximum Duty Cycle Control
Pin 11
Voltage
VCT
(Pin 10)
Overvoltage Protection
The overvoltage arrangement consists of a comparator
that compares the Pin 6 voltage to Vref (2.5 V) (refer to
Figure 46).
If no external component is connected to Pin 6, the
comparator noninverting input voltage is nearly equal to:
ǒ
Dmax
ǒ
2.0 kW
11.6 kW 2.0 kW
)
Ǔ
Ǔ
x VCC
The comparator output is high when:
Using the internal current source (0.4 Iref), the Pin 11
voltage can easily be set by connecting a resistor to this pin.
If a capacitor is connected to Pin 11, the voltage increases
from 0 to its maximum value progressively (refer to Figure
44), thereby, implementing a soft–start. The soft–start
capacitor is discharged internally when the VCC (Pin 1)
voltage drops below 9.0 V.
Figure 44. Different Possible Uses of Pin 11
Pin 11
RI
R Connected to Pin 11
I = 0.4 Iref
VZ
C
C // R
VZ
RI
τ = RC
If no external component is connected to Pin 11, an
internal zener diode clamps the Pin 11 voltage to a value VZ
that is higher than the oscillator peak value, disabling
soft–start and maximum duty cycle limitation.
Foldback
As depicted in Figures 32 and 48, the foldback input (Pin
5) can be used to reduce the maximum VCS value, providing
foldback protection. The foldback arrangement is a
programmable peak current limitation.
If the output load is increased, the required converter peak
current becomes higher and VCS increases until it reaches its
maximum value (normally, VCS max = 1.0 V).
Then, if the output load keeps on increasing, the system is
unable to supply enough energy to maintain the output
voltages in regulation. Consequently, the decreasing output
can be applied to Pin 5, in order to limit the maximum peak
current. In this way, the well known foldback characteristic
can be obtained (refer to Figure 45).
MOTOROLA ANALOG IC DEVICE DATA
2.0 kW
11.6 kW 2.0 kW
x VCC w 2.5 V
)
à VCC w 17 V
A delay latch (2.0 µs) is incorporated in order to sense
overvoltages that last at least 2.0 µs.
If this condition is achieved, VOVP out, the delay latch
output, becomes high. As this level is brought back to the
input through an OR gate, VOVP out remains high (disabling
the IC output) until Vref is disabled.
Consequently, when an overvoltage longer than 2.0 µs is
detected, the output is disabled until VCC is removed and
then re–applied.
The VCC is connected after Vref has reached steady state
in order to limit the circuit startup consumption.
The overvoltage section is enabled 5.0 µs after the
regulator has started to allow the reference Vref to stabilize.
By connecting an external resistor to Pin 6, the threshold
VCC level can be changed.
Figure 46. Overvoltage Protection
Vref
VCC
Out
Delay
T
0
VOVP
External
Resistor
6
τ
5.0 µs
In
2.5 V
11.6 k Enable
2.0 k
COVLO
2.5 V
(Vref)
In
τ
VOVP out
Out
Delay
2.0 µs
(If VOVP out = 1.0,
the Output is Disabled)
17
MC44603A
Undervoltage Lockout Section
Figure 47. VCC Management
RF Stby
Pin 15
Vref enable
VCC
Pin 16
Cstartup
1
1
1
0
Vdisable2
7.5 V
CUVLO1
Vdisable1
9.0 V
18
Rref
0
Reference Block:
Voltage and Current
Sources Generator
(Vref, Iref, ...)
Startup
14.5 V
UVLO1
(to Soft–Start)
As depicted in Figure 47, an undervoltage lockout has
been incorporated to garantee that the IC is fully functional
before allowing system operation.
This block particularly, produces Vref (Pin 16 voltage) and
Iref that is determined by the resistor Rref connected between
Pin 16 and the ground:
Vref
Iref
where Vref
2.5 V (typically)
Rref
Another resistor is connected to the Reference Block:
RF Stby that is used to fix the standby frequency.
In addition to this, VCC is compared to a second threshold
level that is nearly equal to 9.0 V (Vdisable1). UVLO1 is
generated to reset the maximum duty cycle and soft–start
block disabling the output stage as soon as VCC becomes
lower than Vdisable1. In this way, the circuit is reset and made
ready for the next startup, before the reference block is
disabled (refer to Figure 29). Finally, the upper limit for the
minimum normal operating voltage is 9.4 V (maximum value
of Vdisable1) and so the minimum hysteresis is 4.2 V.
((Vstup–th) min = 13.6 V).
The large hysteresis and the low startup current of the
MC44603A make it ideally suited for off–line converter
applications where efficient bootstrap startup techniques are
required.
+
+
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Figure 48. 250 W Input Power Off–Line Flyback Converter with MOSFET Switch
185 Vac
to
270 Vac
RFI
Filter
R1
1.0/5.0 W
C3
1.0 nF/1.0 kV
C4 ... C7
1.0 nF/1000 V
R3
4.7 M
D1 ... D4
1N4007
C1
220 µF
C2
220 µF
Sync
C16
100 pF
9
R12
27 k
8
C9 1.0 nF
10
7
11
6
12
R15
5.6 k
C11
1.0 nF
R15
22 k
13
MC44603AP
C10 1.0 µF
5
R9 1.0 k
C15
1.0 nF
D8
MR856 C30
100 µF
D7
M856
L1
1.0 µH
3
15
2
D6
1N4148
R5
1.2 k
Laux
D9
MR852
Lp
C27
1000 µF
14 V/2.0 A
R6
150
R8
15 k
D10
MR852
MTP6N60E
R26
1.0 k
C18
2.2 nF
D12
MR856
C25
1000 µF
16
7.0 V/2.0 A
1
R12 22
R18
27 k
R19
10 k
C13
100 nF
C24
0.1 µF
C23 220 pF
R11 39
R17
22 k
C28
0.1 µF
C26 220 pF
R7 180 k
R10 10
C31
0.1 µF
C29 220 pF
4
14
C33
100 µF
150 V/0.6 A
30 V/2.0 A
C14
4.7 nF
*D15 1N5819
L2
22.5 µH
C32 220 pF
C17
47 nF
D5
1N4934
R2
68 k/2.0 W
C8 2.2 nF
R20
22 k
5.0 W
R14
0.2
D11
MR852
R13
1.0 k
C22
0.1 µF
C21
1000 µF
R24
270
R23
147.5 k
MOC8101
R21
10 k
C19
100 nF
D14
1N4733
C20
33 nF
R25
1.0 k
C12
6.8 nF
TL431
R22
2.5 k
* Diode D15 is required if the negative current into the output pin exceeds 15 mA.
MOTOROLA ANALOG IC DEVICE DATA
19
MC44603A
250 W Input Power Fly–Back Converter
185 V – 270 V Mains Range
MC44603AP & MTP6N60E
Tests
Line Regulation
Conditions
Vin = 185 Vac to 270 Vac
Fmains = 50 Hz
Iout = 0.6 A
Iout = 2.0 A
Iout = 2.0 A
Iout = 2.0 A
10 mV
10 mV
10 mV
20 mV
Load Regulation
150 V
Vin = 220 Vac
Iout = 0.3 A to 0.6 A
50 mV
Cross Regulation
Vin = 220 Vac
Iout (150 V) = 0.6 A
Iout (30 V) = 0 A to 2.0 A
Iout (14 V) = 2.0 A
Iout (7.0 V) = 2.0 A
150 V
130 V
114 V
7.0 V
150 V
< 1.0 mV
Efficiency
Vin = 220 Vac, Pin = 250 W
81%
Standby Mode
P input
Vin = 220 Vac, Pout = 0 W
3.3 W
Switching Frequency
20
Results
20 kHz fully stable
Output Short Circuit
Pout (max) = 270 W
Safe on all outputs
Startup
Pin = 250 W
Vac = 160 V
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
OUTLINE DIMENSIONS
P SUFFIX
PLASTIC PACKAGE
CASE 648–08
ISSUE R
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEADS WHEN
FORMED PARALLEL.
4. DIMENSION B DOES NOT INCLUDE MOLD FLASH.
5. ROUNDED CORNERS OPTIONAL.
–A–
16
9
1
8
B
F
C
L
S
–T–
SEATING
PLANE
K
H
G
D
J
16 PL
0.25 (0.010)
M
MOTOROLA ANALOG IC DEVICE DATA
T A
M
M
DIM
A
B
C
D
F
G
H
J
K
L
M
S
INCHES
MIN
MAX
0.740
0.770
0.250
0.270
0.145
0.175
0.015
0.021
0.040
0.70
0.100 BSC
0.050 BSC
0.008
0.015
0.110
0.130
0.295
0.305
0_
10 _
0.020
0.040
MILLIMETERS
MIN
MAX
18.80
19.55
6.35
6.85
3.69
4.44
0.39
0.53
1.02
1.77
2.54 BSC
1.27 BSC
0.21
0.38
2.80
3.30
7.50
7.74
0_
10 _
0.51
1.01
21
MC44603A
OUTLINE DIMENSIONS
DW SUFFIX
PLASTIC PACKAGE
CASE 751G–02
(SOP–16L)
ISSUE A
–A–
16
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSIONS A AND B DO NOT INCLUDE MOLD
PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER
SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN
EXCESS OF D DIMENSION AT MAXIMUM
MATERIAL CONDITION.
9
–B–
8X
P
0.010 (0.25)
1
M
B
M
8
16X
J
D
0.010 (0.25)
M
T A
S
B
S
F
R X 45 _
C
–T–
14X
22
G
K
SEATING
PLANE
M
DIM
A
B
C
D
F
G
J
K
M
P
R
MILLIMETERS
MIN
MAX
10.15
10.45
7.40
7.60
2.35
2.65
0.35
0.49
0.50
0.90
1.27 BSC
0.25
0.32
0.10
0.25
0_
7_
10.05
10.55
0.25
0.75
INCHES
MIN
MAX
0.400
0.411
0.292
0.299
0.093
0.104
0.014
0.019
0.020
0.035
0.050 BSC
0.010
0.012
0.004
0.009
0_
7_
0.395
0.415
0.010
0.029
MOTOROLA ANALOG IC DEVICE DATA
MC44603A
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and
are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.
MOTOROLA ANALOG IC DEVICE DATA
23
MC44603A
Mfax is a trademark of Motorola, Inc.
How to reach us:
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852–26629298
HOME PAGE: http://motorola.com/sps/
24
◊
MC44603A/D
MOTOROLA ANALOG IC DEVICE
DATA