NSC LM2599 Simple switcherâ® power converter 150 khz 3a step-down voltage regulator, with feature Datasheet

LM2599
SIMPLE SWITCHER ® Power Converter 150 kHz 3A
Step-Down Voltage Regulator, with Features
General Description
The LM2599 series of regulators are monolithic integrated
circuits that provide all the active functions for a step-down
(buck) switching regulator, capable of driving a 3A load with
excellent line and load regulation. These devices are available in fixed output voltages of 3.3V, 5V, 12V, and an adjustable output version.
This series of switching regulators is similar to the LM2596
series, with additional supervisory and performance features
added.
Requiring a minimum number of external components, these
regulators are simple to use and include internal frequency
compensation†, improved line and load specifications,
fixed-frequency oscillator, Shutdown/Soft-start, error flag delay and error flag output.
The LM2599 series operates at a switching frequency of 150
kHz thus allowing smaller sized filter components than what
would be needed with lower frequency switching regulators.
Available in a standard 7-lead TO-220 package with several
different lead bend options, and a 7-lead TO-263 Surface
mount package.
A standard series of inductors (both through hole and surface mount types) are available from several different manufacturers optimized for use with the LM2599 series. This
feature greatly simplifies the design of switch-mode power
supplies.
Other features include a guaranteed ± 4% tolerance on output voltage under all conditions of input voltage and output
load conditions, and ± 15% on the oscillator frequency. External shutdown is included, featuring typically 80 µA
Typical Application
standby current. Self protection features include a two stage
current limit for the output switch and an over temperature
shutdown for complete protection under fault conditions.
Features
n 3.3V, 5V, 12V, and adjustable output versions
n Adjustable version output voltage range, 1.2V to 37V
± 4% max over line and load conditions
n Guaranteed 3A output current
n Available in 7-pin TO-220 and TO-263 (surface mount)
Package
n Input voltage range up to 40V
n 150 kHz fixed frequency internal oscillator
n Shutdown/Soft-start
n Out of regulation error flag
n Error output delay
n Low power standby mode, IQ typically 80 µA
n High Efficiency
n Uses readily available standard inductors
n Thermal shutdown and current limit protection
Applications
n
n
n
n
Simple high-efficiency step-down (buck) regulator
Efficient pre-regulator for linear regulators
On-card switching regulators
Positive to Negative converter
Note: † Patent Number 5,382,918.
(Fixed Output Voltage Versions)
DS012582-1
SIMPLE SWITCHER ® and Switchers Made Simple ® are registered trademarks of National Semiconductor Corporation.
© 2001 National Semiconductor Corporation
DS012582
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LM2599 SIMPLE SWITCHER Power Converter 150 kHz 3A Step-Down Voltage Regulator, with
Features
December 2000
LM2599
Absolute Maximum Ratings (Note 1)
ESD Susceptibility
Human Body Model (Note 3)
Lead Temperature
S Package
Vapor Phase (60 sec.)
Infrared (10 sec.)
T Package (Soldering, 10 sec.)
Maximum Junction Temperature
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Maximum Supply Voltage (VIN)
SD /SS Pin Input Voltage (Note 2)
Delay Pin Voltage (Note 2)
Flag Pin Voltage
Feedback Pin Voltage
Output Voltage to Ground
(Steady State)
Power Dissipation
Storage Temperature Range
45V
6V
1.5V
−0.3 ≤ V ≤45V
−0.3 ≤ V ≤+25V
2 kV
+215˚C
+245˚C
+260˚C
+150˚C
Operating Conditions
−1V
Internally limited
−65˚C to +150˚C
−40˚C ≤ TJ ≤ +125˚C
4.5V to 40V
Temperature Range
Supply Voltage
LM2599-3.3
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range.
Symbol
Parameter
Conditions
LM2599-3.3
Typ
Limit
(Note 4)
(Note 5)
Units
(Limits)
SYSTEM PARAMETERS (Note 6) Test Circuit Figure 1
VOUT
η
Output Voltage
Efficiency
4.75V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
VIN = 12V, ILOAD = 3A
3.3
V
3.168/3.135
V(min)
3.432/3.465
V(max)
73
%
LM2599-5.0
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range.
Symbol
Parameter
Conditions
LM2599-5.0
Typ
Limit
(Note 4)
(Note 5)
Units
(Limits)
SYSTEM PARAMETERS (Note 6) Test Circuit Figure 1
VOUT
η
Output Voltage
Efficiency
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7V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
VIN = 12V, ILOAD = 3A
5
80
2
V
4.800/4.750
V(min)
5.200/5.250
V(max)
%
LM2599
LM2599-12
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range.
Symbol
Parameter
Conditions
LM2599-12
Units
(Limits)
Typ
Limit
(Note 4)
(Note 5)
SYSTEM PARAMETERS (Note 6) Test Circuit Figure 1
VOUT
η
15V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
Output Voltage
Efficiency
12
VIN = 25V, ILOAD = 3A
V
11.52/11.40
V(min)
12.48/12.60
V(max)
90
%
LM2599-ADJ
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range.
Symbol
Parameter
Conditions
LM2599-ADJ
Units
(Limits)
Typ
Limit
(Note 4)
(Note 5)
SYSTEM PARAMETERS (Note 6) Test Circuit Figure 1
VFB
Feedback Voltage
4.5V ≤ VIN ≤ 40V, 0.2A ≤ ILOAD ≤ 3A
1.230
V
VOUT programmed for 3V. Circuit of Figure 1.
η
Efficiency
VIN = 12V, VOUT = 3V, ILOAD = 3A
1.193/1.180
V(min)
1.267/1.280
V(max)
73
%
All Output Voltage Versions
Electrical Characteristics
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V for the 3.3V, 5V, and Adjustable version and VIN = 24V for the 12V version. ILOAD = 500 mA
Symbol
Parameter
Conditions
LM2599-XX
Units
(Limits)
Typ
Limit
(Note
4)
(Note 5)
DEVICE PARAMETERS
Ib
Feedback Bias Current
Adjustable Version Only, VFB = 1.3V
10
fO
Oscillator Frequency
(Note 7)
150
VSAT
Saturation Voltage
IOUT = 3A (Note 8) (Note 9)
DC
Max Duty Cycle (ON)
Min Duty Cycle (OFF)
(Note 10)
ICL
Current Limit
Peak Current, (Note 8) (Note 9)
nA
50/100
nA (max)
127/110
kHz(min)
173/173
kHz(max)
1.4/1.5
V(max)
kHz
1.16
(Note 9)
V
100
%
0
4.5
A
3.6/3.4
IL
Output Leakage Current
(Note 8) (Note 10) (Note 11)
Output = 0V
Output = −1V
3
A(min)
6.9/7.5
A(max)
50
µA(max)
30
mA(max)
2
mA
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LM2599
All Output Voltage Versions
Electrical Characteristics (Continued)
Specifications with standard type face are for TJ = 25˚C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V for the 3.3V, 5V, and Adjustable version and VIN = 24V for the 12V version. ILOAD = 500 mA
Symbol
Parameter
Conditions
LM2599-XX
Typ
Limit
(Note
4)
(Note 5)
Units
(Limits)
DEVICE PARAMETERS
IQ
Operating Quiescent
SD /SS Pin Open (Note 10)
5
Current
ISTBY
Standby Quiescent
θJC
Thermal Resistance
mA
10
SD /SS pin = 0V
(Note 11)
80
Current
mA(max)
µA
200/250
µA(max)
TO220 or TO263 Package, Junction to Case
2
˚C/W
θJA
TO220 Package, Juncton to Ambient (Note 12)
50
˚C/W
θJA
TO263 Package, Juncton to Ambient (Note 13)
50
˚C/W
θJA
TO263 Package, Juncton to Ambient (Note 14)
30
˚C/W
θJA
TO263 Package, Juncton to Ambient (Note 15)
20
˚C/W
SHUTDOWN/SOFT-START CONTROL Test Circuit of Figure 1
VSD
Shutdown Threshold
Voltage
VSS
ISD
ISS
Soft-start Voltage
Shutdown Current
Soft-start Current
1.3
V
Low, (Shutdown Mode)
0.6
V(max)
High, (Soft-start Mode)
2
V(min)
VOUT = 20% of Nominal Output Voltage
2
VOUT = 100% of Nominal Output Voltage
3
VSHUTDOWN = 0.5V
5
VSoft-start = 2.5V
V
µA
10
µA(max)
5
µA(max)
92
%(min)
98
%(max)
1.6
µA
FLAG/DELAY CONTROL Test Circuit of Figure 1
Regulator Dropout Detector
Low (Flag ON)
96
Threshold Voltage
VFSAT
Flag Output Saturation
ISINK = 3 mA
Voltage
VDELAY = 0.5V
IFL
Flag Output Leakage Current
VFLAG = 40V
0.3
V
0.7/1.0
Delay Pin Threshold
Voltage
%
V(max)
0.3
µA
1.25
V
Low (Flag ON)
1.21
V(min)
High (Flag OFF) and VOUT Regulated
1.29
V(max)
Delay Pin Source Current
VDELAY = 0.5V
3
Delay Pin Saturation
Low (Flag ON)
55
µA
6
µA(max)
350/400
mV(max)
mV
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.
Note 2: Voltage internally clamped. If clamp voltage is exceeded, limit current to a maximum of 1 mA.
Note 3: The human body model is a 100 pF capacitor discharged through a 1.5k resistor into each pin.
Note 4: Typical numbers are at 25˚C and represent the most likely norm.
Note 5: All limits guaranteed at room temperature (standard type face) and at temperature extremes (bold type face). All room temperature limits are 100%
production tested. All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. All limits are used
to calculate Average Outgoing Quality Level (AOQL).
Note 6: External components such as the catch diode, inductor, input and output capacitors can affect switching regulator system performance. When the LM2599
is used as shown in the Figure 1 test circuit, system performance will be as shown in system parameters section of Electrical Characteristics.
Note 7: The switching frequency is reduced when the second stage current limit is activated. The amount of reduction is determined by the severity of current
overload.
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4
LM2599
All Output Voltage Versions
Electrical Characteristics (Continued)
Note 8: No diode, inductor or capacitor connected to output pin.
Note 9: Feedback pin removed from output and connected to 0V to force the output transistor switch ON.
Note 10: Feedback pin removed from output and connected to 12V for the 3.3V, 5V, and the ADJ. version, and 15V for the 12V version, to force the output transistor
switch OFF.
Note 11: VIN = 40V.
Note 12: Junction to ambient thermal resistance (no external heat sink) for the package mounted TO-220 package mounted vertically, with the leads soldered to
a printed circuit board with (1 oz.) copper area of approximately 1 in2.
Note 13: Junction to ambient thermal resistance with the TO-263 package tab soldered to a single sided printed circuit board with 0.5 in2 of (1 oz.) copper area.
Note 14: Junction to ambient thermal resistance with the TO-263 package tab soldered to a single sided printed circuit board with 2.5 in2 of (1 oz.) copper area.
Note 15: Junction to ambient thermal resistance with the TO-263 package tab soldered to a double sided printed circuit board with 3 in2 of (1 oz.) copper area on
the LM2599S side of the board, and approximately 16 in2 of copper on the other side of the p-c board. See application hints in this data sheet and the thermal model
in Switchers Made Simple version 4.2.1 (or later) software.
Typical Performance Characteristics
Normalized
Output Voltage
(Circuit of Figure 1)
Efficiency
Line Regulation
DS012582-4
DS012582-3
DS012582-2
Switch Saturation
Voltage
Dropout Voltage
Switch Current Limit
DS012582-7
DS012582-6
DS012582-5
Operating
Quiescent Current
Shutdown
Quiescent Current
DS012582-8
Minimum Operating
Supply Voltage
DS012582-9
5
DS012582-10
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LM2599
Typical Performance Characteristics
Feedback Pin
Bias Current
(Circuit of Figure 1) (Continued)
Flag Saturation
Voltage
Switching Frequency
DS012582-13
DS012582-11
Soft-start
DS012582-12
Shutdown /Soft-start
Current
Daisy Pin Current
DS012582-14
DS012582-16
DS012582-15
Soft-start Response
Shutdown/Soft-start
Threshold Voltage
DS012582-18
DS012582-53
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Continuous Mode Switching Waveforms
VIN = 20V, VOUT = 5V, ILOAD = 2A
L = 32 µH, COUT = 220 µF, COUT ESR = 50 mΩ
LM2599
Typical Performance Characteristics
(Circuit of Figure 1) (Continued)
Discontinuous Mode Switching Waveforms
VIN = 20V, VOUT = 5V, ILOAD = 500 mA
L = 10 µH, COUT = 330 µF, COUT ESR = 45 mΩ
DS012582-20
A: Output Pin Voltage, 10V/div.
B: Inductor Current 1A/div.
C: Output Ripple Voltage, 50 mV/div.
DS012582-19
A: Output Pin Voltage, 10V/div.
B: Inductor Current 0.5A/div.
C: Output Ripple Voltage, 100 mV/div.
Horizontal Time Base: 2 µs/div.
Horizontal Time Base: 2 µs/div.
Load Transient Response for Continuous Mode
VIN = 20V, VOUT = 5V, ILOAD = 500 mA to 2A
L = 32 µH, COUT = 220 µF, COUT ESR = 50 mΩ
Load Transient Response for Discontinuous Mode
VIN = 20V, VOUT = 5V, ILOAD = 500 mA to 2A
L = 10 µH, COUT = 330 µF, COUT ESR = 45 mΩ
DS012582-22
DS012582-21
A: Output Voltage, 100 mV/div. (AC)
B: 500 mA to 2A Load Pulse
A: Output Voltage, 100 mV/div. (AC)
B: 500 mA to 2A Load Pulse
Horizontal Time Base: 200 µs/div.
Horizontal Time Base: 50 µs/div.
Connection Diagrams and Order Information
Bent and Staggered Leads, Through Hole Package
7-Lead TO-220 (T)
Surface Mount Package
7-Lead TO-263 (S)
DS012582-50
DS012582-23
Order Number LM2599T-3.3, LM2599T-5.0,
LM2599T-12 or LM2599T-ADJ
See NS Package Number TA07B
Order Number LM2599S-3.3, LM2599S-5.0,
LM2599S-12 or LM2599S-ADJ
See NS Package Number TS7B
7
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LM2599
Test Circuit and Layout Guidelines
Fixed Output Voltage Versions
DS012582-24
Component Values shown are for VIN = 15V,
VOUT = 5V, ILOAD = 3A.
CIN — 470 µF, 50V, Aluminum Electrolytic Nichicon “PL Series”
COUT — 220 µF, 25V Aluminum Electrolytic, Nichicon “PL Series”
D1 — 5A, 40V Schottky Rectifier, 1N5825
L1 — 68 µH, L38
Typical Values
CSS — 0.1 µF
CDELAY — 0.1 µF
RPull Up — 4.7k
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8
LM2599
Test Circuit and Layout Guidelines
(Continued)
Adjustable Output Voltage Versions
DS012582-25
where VREF = 1.23V
Select R1 to be approximately 1 kΩ, use a 1% resistor for best stability.
Component Values shown are for VIN = 20V,
VOUT = 10V, ILOAD = 3A.
CIN: — 470 µF, 35V, Aluminum Electrolytic Nichicon “PL Series”
COUT: — 220 µF, 35V Aluminum Electrolytic, Nichicon “PL Series”
D1 — 5A, 30V Schottky Rectifier, 1N5824
L1 — 68 µH, L38
R1 — 1 kΩ, 1%
R2 — 7.15k, 1%
CFF — 3.3 nF, See Application Information Section
RFF — 3 kΩ, See Application Information Section
Typical Values
CSS — 0.1 µF
CDELAY — 0.1 µF
RPULL UP — 4.7k
FIGURE 1. Standard Test Circuits and Layout Guides
As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring inductance can
generate voltage transients which can cause problems. For
minimal inductance and ground loops, the wires indicated by
heavy lines should be wide printed circuit traces and
should be kept as short as possible. For best results,
external components should be located as close to the
switcher lC as possible using ground plane construction or
single point grounding.
If open core inductors are used, special care must be
taken as to the location and positioning of this type of inductor. Allowing the inductor flux to intersect sensitive feedback,
lC groundpath and COUT wiring can cause problems.
When using the adjustable version, special care must be
taken as to the location of the feedback resistors and the
associated wiring. Physically locate both resistors near the
IC, and route the wiring away from the inductor, especially an
open core type of inductor. (See application section for more
information.)
9
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LM2599
LM2599 Series Buck Regulator Design Procedure (Fixed Output)
PROCEDURE (Fixed Output Voltage Version)
EXAMPLE (Fixed Output Voltage Version)
Given:
VOUT = Regulated Output Voltage (3.3V, 5V or 12V)
Given:
VOUT = 5V
VIN(max) = Maximum DC Input Voltage
VIN(max) = 12V
ILOAD(max) = Maximum Load Current
ILOAD(max) = 3A
1. Inductor Selection (L1)
A. Select the correct inductor value selection guide from
Figure 4, Figure 5, or 6. (Output voltages of 3.3V, 5V, or 12V
respectively.) For all other voltages, see the design procedure for the adjustable version.
B. From the inductor value selection guide, identify the inductance region intersected by the Maximum Input Voltage
line and the Maximum Load Current line. Each region is
identified by an inductance value and an inductor code
(LXX).
C. Select an appropriate inductor from the four manufacturer’s part numbers listed in Figure 8.
1. Inductor Selection (L1)
A. Use the inductor selection guide for the 5V version shown
in Figure 5.
B. From the inductor value selection guide shown in Figure 5,
the inductance region intersected by the 12V horizontal line
and the 3A vertical line is 33 µH, and the inductor code is
L40.
C. The inductance value required is 33 µH. From the table in
Figure 8, go to the L40 line and choose an inductor part
number from any of the four manufacturers shown. (In most
instance, both through hole and surface mount inductors are
available.)
2. Output Capacitor Selection (COUT)
A. In the majority of applications, low ESR (Equivalent Series
Resistance) electrolytic capacitors between 82 µF and 820
µF and low ESR solid tantalum capacitors between 10 µF
and 470 µF provide the best results. This capacitor should be
located close to the IC using short capacitor leads and short
copper traces. Do not use capacitors larger than 820 µF.
For additional information, see section on output capacitors in application information section.
B. To simplify the capacitor selection procedure, refer to the
quick design component selection table shown in Figure 2.
This table contains different input voltages, output voltages,
and load currents, and lists various inductors and output
capacitors that will provide the best design solutions.
C. The capacitor voltage rating for electrolytic capacitors
should be at least 1.5 times greater than the output voltage,
and often much higher voltage ratings are needed to satisfy
the low ESR requirements for low output ripple voltage.
D. For computer aided design software, see Switchers
Made Simple (version 4.2.1 or later).
2. Output Capacitor Selection (COUT)
A. See section on output capacitors in application information section.
B. From the quick design component selection table shown
in Figure 2, locate the 5V output voltage section. In the load
current column, choose the load current line that is closest to
the current needed in your application, for this example, use
the 3A line. In the maximum input voltage column, select the
line that covers the input voltage needed in your application,
in this example, use the 15V line. Continuing on this line are
recommended inductors and capacitors that will provide the
best overall performance.
The capacitor list contains both through hole electrolytic and
surface mount tantalum capacitors from four different capacitor manufacturers. It is recommended that both the manufacturers and the manufacturer’s series that are listed in the
table be used.
In this example aluminum electrolytic capacitors from several
different manufacturers are available with the range of ESR
numbers needed.
330 µF 35V Panasonic HFQ Series
330 µF 35V Nichicon PL Series
C. For a 5V output, a capacitor voltage rating at least 7.5V or
more is needed. But even a low ESR, switching grade, 220
µF 10V aluminum electrolytic capacitor would exhibit approximately 225 mΩ of ESR (see the curve in Figure 17 for
the ESR vs voltage rating). This amount of ESR would result
in relatively high output ripple voltage. To reduce the ripple to
1% of the output voltage, or less, a capacitor with a higher
value or with a higher voltage rating (lower ESR) should be
selected. A 16V or 25V capacitor will reduce the ripple voltage by approximately half.
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PROCEDURE (Fixed Output Voltage Version)
(Continued)
EXAMPLE (Fixed Output Voltage Version)
3. Catch Diode Selection (D1)
A. The catch diode current rating must be at least 1.3 times
greater than the maximum load current. Also, if the power
supply design must withstand a continuous output short, the
diode should have a current rating equal to the maximum
current limit of the LM2599. The most stressful condition for
this diode is an overload or shorted output condition.
B. The reverse voltage rating of the diode should be at least
1.25 times the maximum input voltage.
C. This diode must be fast (short reverse recovery time) and
must be located close to the LM2599 using short leads and
short printed circuit traces. Because of their fast switching
speed and low forward voltage drop, Schottky diodes provide
the best performance and efficiency, and should be the first
choice, especially in low output voltage applications.
Ultra-fast recovery, or High-Efficiency rectifiers also provide
good results. Ultra-fast recovery diodes typically have reverse recovery times of 50 ns or less. Rectifiers such as the
IN5400 series are much too slow and should not be used.
3. Catch Diode Selection (D1)
4. Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is needed
between the input pin and ground to prevent large voltage
transients from appearing at the input. In addition, the RMS
current rating of the input capacitor should be selected to be
at least 1⁄2 the DC load current. The capacitor manufacturers
data sheet must be checked to assure that this current rating
is not exceeded. The curve shown in Figure 16 shows typical
RMS current ratings for several different aluminum electrolytic capacitor values.
This capacitor should be located close to the IC using short
leads and the voltage rating should be approximately 1.5
times the maximum input voltage.
If solid tantalum input capacitors are used, it is recomended
that they be surge current tested by the manufacturer.
Use caution when using ceramic capacitors for input bypassing, because it may cause severe ringing at the VIN pin.
For additional information, see section on input capacitors in Application Information section.
4. Input Capacitor (CIN)
The important parameters for the Input capacitor are the
input voltage rating and the RMS current rating. With a
nominal input voltage of 12V, an aluminum electrolytic capacitor with a voltage rating greater than 18V (1.5 x VIN)
would be needed. The next higher capacitor voltage rating is
25V.
The RMS current rating requirement for the input capacitor in
a buck regulator is approximately 1⁄2 the DC load current. In
this example, with a 3A load, a capacitor with a RMS current
rating of at least 1.5A is needed. The curves shown in Figure
16 can be used to select an appropriate input capacitor.
From the curves, locate the 35V line and note which capacitor values have RMS current ratings greater than 1.5A. A
680 µF, 35V capacitor could be used.
For a through hole design, a 680 µF/35V electrolytic capacitor (Panasonic HFQ series or Nichicon PL series or equivalent) would be adequate. other types or other manufacturers
capacitors can be used provided the RMS ripple current
ratings are adequate.
For surface mount designs, solid tantalum capacitors are
recommended. The TPS series available from AVX, and the
593D series from Sprague are both surge current tested.
A. Refer to the table shown in Figure 11. In this example, a
5A, 20V, 1N5823 Schottky diode will provide the best performance, and will not be overstressed even for a shorted
output.
11
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LM2599
LM2599 Series Buck Regulator Design Procedure (Fixed Output)
LM2599
LM2599 Series Buck Regulator Design Procedure (Fixed Output)
Conditions
Inductor
(Continued)
Output Capacitor
Through Hole Electrolytic
Surface Mount Tantalum
Output
Load
Max Input
Inductance
Inductor
Panasonic
Nichicon
AVX TPS
Sprague
Voltage
Current
Voltage
(µH)
(#)
HFQ Series
PL Series
Series
595D Series
(V)
(A)
(V)
(µF/V)
(µF/V)
(µF/V)
(µF/V)
5
22
L41
470/25
560/16
330/6.3
390/6.3
7
22
L41
560/35
560/35
330/6.3
390/6.3
10
22
L41
680/35
680/35
330/6.3
390/6.3
40
33
L40
560/35
470/35
330/6.3
390/6.3
6
22
L33
470/25
470/35
330/6.3
390/6.3
10
33
L32
330/35
330/35
330/6.3
390/6.3
40
47
L39
330/35
270/50
220/10
330/10
8
22
L41
470/25
560/16
220/10
330/10
10
22
L41
560/25
560/25
220/10
330/10
15
33
L40
330/35
330/35
220/10
330/10
40
47
L39
330/35
270/35
220/10
330/10
9
22
L33
470/25
560/16
220/10
330/10
3
3.3
2
3
5
2
3
12
2
20
68
L38
180/35
180/35
100/10
270/10
40
68
L38
180/35
180/35
100/10
270/10
15
22
L41
470/25
470/25
100/16
180/16
18
33
L40
330/25
330/25
100/16
180/16
30
68
L44
180/25
180/25
100/16
120/20
40
68
L44
180/35
180/35
100/16
120/20
15
33
L32
330/25
330/25
100/16
180/16
20
68
L38
180/25
180/25
100/16
120/20
40
150
L42
82/25
82/25
68/20
68/25
FIGURE 2. LM2599 Fixed Voltage Quick Design Component Selection Table
LM2599 Series Buck Regulator Design Procedure (Adjustable Output)
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
Given:
VOUT = Regulated Output Voltage
VIN(max) = Maximum Input Voltage
Given:
VOUT = 20V
VIN(max) = 28V
ILOAD(max) = Maximum Load Current
F = Switching Frequency (Fixed at a nominal 150 kHz).
ILOAD(max) = 3A
F = Switching Frequency (Fixed at a nominal 150 kHz).
1. Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 1)
1. Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 1)
Use the following formula to select the appropriate resistor
values.
Select R1 to be 1 kΩ, 1%. Solve for R2.
R2 = 1k (16.26 − 1) = 15.26k, closest 1% value is 15.4 kΩ.
R2 = 15.4 kΩ.
Select a value for R1 between 240Ω and 1.5 kΩ. The lower
resistor values minimize noise pickup in the sensitive feedback pin. (For the lowest temperature coefficient and the best
stability with time, use 1% metal film resistors.)
www.national.com
12
(Continued)
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
2. Inductor Selection (L1)
A. Calculate the inductor Volt • microsecond constant E • T
(V • µs), from the following formula:
2. Inductor Selection (L1)
A. Calculate the inductor Volt • microsecond constant (E •
T),
where VSAT = internal switch saturation voltage = 1.16V and
VD = diode forward voltage drop = 0.5V
B. Use the E • T value from the previous formula and match
it with the E • T number on the vertical axis of the Inductor
Value Selection Guide shown in Figure 7.
C. on the horizontal axis, select the maximum load current.
D. Identify the inductance region intersected by the E • T
value and the Maximum Load Current value. Each region is
identified by an inductance value and an inductor code
(LXX).
E. Select an appropriate inductor from the four manufacturer’s part numbers listed in Figure 8.
B. E • T = 34.2 (V • µs)
C. ILOAD(max) = 3A
D. From the inductor value selection guide shown in Figure 7,
the inductance region intersected by the 34 (V • µs) horizontal line and the 3A vertical line is 47 µH, and the inductor
code is L39.
E. From the table in Figure 8, locate line L39, and select an
inductor part number from the list of manufacturers part
numbers.
3. Output Capacitor Selection (COUT)
A. In the majority of applications, low ESR electrolytic or solid
tantalum capacitors between 82 µF and 820 µF provide the
best results. This capacitor should be located close to the IC
using short capacitor leads and short copper traces. Do not
use capacitors larger than 820 µF. For additional information, see section on output capacitors in application
information section.
B. To simplify the capacitor selection procedure, refer to the
quick design table shown in Figure 3. This table contains
different output voltages, and lists various output capacitors
that will provide the best design solutions.
C. The capacitor voltage rating should be at least 1.5 times
greater than the output voltage, and often much higher voltage ratings are needed to satisfy the low ESR requirements
needed for low output ripple voltage.
3. Output Capacitor SeIection (COUT)
4. Feedforward Capacitor (CFF) (See Figure 1)
For output voltages greater than approximately 10V, an additional capacitor is required. The compensation capacitor is
typically between 100 pF and 33 nF, and is wired in parallel
with the output voltage setting resistor, R2. It provides additional stability for high output voltages, low input-output voltages, and/or very low ESR output capacitors, such as solid
tantalum capacitors.
4. Feedforward Capacitor (CFF)
The table shown in Figure 3 contains feed forward capacitor
values for various output voltages. In this example, a 560 pF
capacitor is needed.
A. See section on COUT in Application Information section.
B. From the quick design table shown in Figure 3, locate the
output voltage column. From that column, locate the output
voltage closest to the output voltage in your application. In
this example, select the 24V line. Under the output capacitor
section, select a capacitor from the list of through hole electrolytic or surface mount tantalum types from four different
capacitor manufacturers. It is recommended that both the
manufacturers and the manufacturers series that are listed in
the table be used.
In this example, through hole aluminum electrolytic capacitors from several different manufacturers are available.
220/35 Panasonic HFQ Series
150/35 Nichicon PL Series
C. For a 20V output, a capacitor rating of at least 30V or
more is needed. In this example, either a 35V or 50V capacitor would work. A 50V rating was chosen because it has a
lower ESR which provides a lower output ripple voltage.
Other manufacturers or other types of capacitors may also
be used, provided the capacitor specifications (especially the
100 kHz ESR) closely match the types listed in the table.
Refer to the capacitor manufacturers data sheet for this
information.
This capacitor type can be ceramic, plastic, silver mica, etc.
(Because of the unstable characteristics of ceramic capacitors made with Z5U material, they are not recommended.)
13
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LM2599
LM2599 Series Buck Regulator Design Procedure (Adjustable Output)
LM2599
LM2599 Series Buck Regulator Design Procedure (Adjustable Output)
(Continued)
PROCEDURE (Adjustable Output Voltage Version)
EXAMPLE (Adjustable Output Voltage Version)
5. Catch Diode Selection (D1)
A. The catch diode current rating must be at least 1.3 times
greater than the maximum load current. Also, if the power
supply design must withstand a continuous output short, the
diode should have a current rating equal to the maximum
current limit of the LM2599. The most stressful condition for
this diode is an overload or shorted output condition.
B. The reverse voltage rating of the diode should be at least
1.25 times the maximum input voltage.
C. This diode must be fast (short reverse recovery time) and
must be located close to the LM2599 using short leads and
short printed circuit traces. Because of their fast switching
speed and low forward voltage drop, Schottky diodes provide
the best performance and efficiency, and should be the first
choice, especially in low output voltage applications.
Ultra-fast recovery, or High-Efficiency rectifiers are also a
good choice, but some types with an abrupt turn-off characteristic may cause instability or EMl problems. Ultra-fast recovery diodes typically have reverse recovery times of 50 ns
or less. Rectifiers such as the 1N4001 series are much too
slow and should not be used.
5. Catch Diode Selection (D1)
6. Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is needed
between the input pin and ground to prevent large voltage
transients from appearing at the input. In addition, the RMS
current rating of the input capacitor should be selected to be
at least 1⁄2 the DC load current. The capacitor manufacturers
data sheet must be checked to assure that this current rating
is not exceeded. The curve shown in Figure 16 shows typical
RMS current ratings for several different aluminum electrolytic capacitor values.
This capacitor should be located close to the IC using short
leads and the voltage rating should be approximately 1.5
times the maximum input voltage.
If solid tantalum input capacitors are used, it is recomended
that they be surge current tested by the manufacturer.
Use caution when using a high dielectric constant ceramic
capacitor for input bypassing, because it may cause severe
ringing at the VIN pin.
For additional information, see section on input capacitor in application information section.
6. Input Capacitor (CIN)
The important parameters for the Input capacitor are the
input voltage rating and the RMS current rating. With a
nominal input voltage of 28V, an aluminum electrolytic aluminum electrolytic capacitor with a voltage rating greater than
42V (1.5 x VIN) would be needed. Since the the next higher
capacitor voltage rating is 50V, a 50V capacitor should be
used. The capacitor voltage rating of (1.5 x VIN) is a conservative guideline, and can be modified somewhat if desired.
The RMS current rating requirement for the input capacitor of
a buck regulator is approximately 1⁄2 the DC load current. In
this example, with a 3A load, a capacitor with a RMS current
rating of at least 1.5A is needed.
The curves shown in Figure 16 can be used to select an
appropriate input capacitor. From the curves, locate the 50V
line and note which capacitor values have RMS current
ratings greater than 1.5A. Either a 470 µF or 680 µF, 50V
capacitor could be used.
For a through hole design, a 680 µF/50V electrolytic capacitor (Panasonic HFQ series or Nichicon PL series or equivalent) would be adequate. Other types or other manufacturers
capacitors can be used provided the RMS ripple current
ratings are adequate.
For surface mount designs, solid tantalum capacitors can be
used, but caution must be exercised with regard to the
capacitor sure current rating (see Application Information or
input capacitors in this data sheet). The TPS series available
from AVX, and the 593D series from Sprague are both surge
current tested.
A. Refer to the table shown in Figure 11. Schottky diodes
provide the best performance, and in this example a 3A, 40V,
1N5825 Schottky diode would be a good choice. The 3A
diode rating is more than adequate and will not be overstressed even for a shorted output.
To further simplify the buck regulator design procedure, National Semiconductor is making available computer design
software to be used with the Simple Switcher line ot switching regulators. Switchers Made Simple (version 4.2.1 or
later) is available on a 31⁄2" diskette for IBM compatible
computers.
www.national.com
14
(Continued)
Output
Voltage
(V)
Through Hole Output Capacitor
Surface Mount Output Capacitor
Panasonic
Nichicon PL
Feedforward
AVX TPS
Sprague
Feedforward
HFQ Series
Series
Capacitor
Series
595D Series
Capacitor
(µF/V)
(µF/V)
(µF/V)
(µF/V)
2
820/35
820/35
33 nF
330/6.3
470/4
4
560/35
470/35
10 nF
330/6.3
390/6.3
10 nF
6
470/25
470/25
3.3 nF
220/10
330/10
3.3 nF
1.5 nF
33 nF
9
330/25
330/25
1.5 nF
100/16
180/16
12
330/25
330/25
1 nF
100/16
180/16
1 nF
15
220/35
220/35
680 pF
68/20
120/20
680 pF
24
220/35
150/35
560 pF
33/25
33/25
220 pF
28
100/50
100/50
390 pF
10/35
15/50
220 pF
FIGURE 3. Output Capacitor and Feedforward Capacitor Selection Table
LM2599 Series Buck Regulator Design Procedure
INDUCTOR VALUE SELECTION GUIDES (For Continuous Mode Operation)
DS012582-28
DS012582-26
FIGURE 6. LM2599-12
FIGURE 4. LM2599-3.3
DS012582-29
DS012582-27
FIGURE 7. LM2599-ADJ
FIGURE 5. LM2599-5.0
15
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LM2599
LM2599 Series Buck Regulator Design Procedure (Adjustable Output)
LM2599
LM2599 Series Buck Regulator Design Procedure
Inductance
(µH)
Current
(A)
Schott
(Continued)
Renco
Pulse Engineering
Through
Surface
Through
Surface
Through
Surface
Hole
Mount
Hole
Mount
Hole
Mount
PE-53815
PE-53815-S
Coilcraft
Surface
Mount
L15
22
0.99
67148350
67148460
RL-1284-22-43
RL1500-22
L21
68
0.99
67144070
67144450
RL-5471-5
RL1500-68
PE-53821
PE-53821-S
DO3316-683
L22
47
1.17
67144080
67144460
RL-5471-6
—
PE-53822
PE-53822-S
DO3316-473
L23
33
1.40
67144090
67144470
RL-5471-7
—
PE-53823
PE-53823-S
DO3316-333
L24
22
1.70
67148370
67148480
RL-1283-22-43
—
PE-53824
PE-53825-S
DO3316-223
L25
15
2.1
67148380
67148490
RL-1283-15-43
—
PE-53825
PE-53824-S
DO3316-153
L26
330
0.80
67144100
67144480
RL-5471-1
—
PE-53826
PE-53826-S
DOS022P-334
L27
220
1.00
67144110
67144490
RL-5471-2
—
PE-53827
PE-53827-S
DOS022P-224
L28
150
1.20
67144120
67144500
RL-5471-3
—
PE-53828
PE-53828-S
DOS022P-154
L29
100
1.47
67144130
67144510
RL-5471-4
—
PE-53829
PE-53829-S
DOS022P-104
L30
68
1.78
67144140
67144520
RL-5471-5
—
PE-53830
PE-53830-S
DOS022P-683
L31
47
2.2
67144150
67144530
RL-5471-6
—
PE-53831
PE-53831-S
DOS022P-473
L32
33
2.5
67144160
67144540
RL-5471-7
—
PE-53932
PE-53932-S
DOS022P-333
L33
22
3.1
67148390
67148500
RL-1283-22-43
—
PE-53933
PE-53933-S
DOS022P-223
L34
15
3.4
67148400
67148790
RL-1283-15-43
—
PE-53934
PE-53934-S
DOS022P-153
L35
220
1.70
67144170
—
RL-5473-1
—
PE-53935
PE-53935-S
—
L36
150
2.1
67144180
—
RL-5473-4
—
PE-54036
PE-54036-S
—
L37
100
2.5
67144190
—
RL-5472-1
—
PE-54037
PE-54037-S
—
L38
68
3.1
67144200
—
RL-5472-2
—
PE-54038
PE-54038-S
—
L39
47
3.5
67144210
—
RL-5472-3
—
PE-54039
PE-54039-S
—
L40
33
3.5
67144220
67148290
RL-5472-4
—
PE-54040
PE-54040-S
—
L41
22
3.5
67144230
67148300
RL-5472-5
—
PE-54041
PE-54041-S
—
L42
150
2.7
67148410
—
RL-5473-4
—
PE-54042
PE-54042-S
—
L43
100
3.4
67144240
—
RL-5473-2
—
PE-54043
—
—
L44
68
3.4
67144250
—
RL-5473-3
—
PE-54044
—
—
FIGURE 8. Inductor Manufacturers Part Numbers
Coilcraft Inc.
Coilcraft Inc., Europe
Pulse Engineering Inc.
Phone
(800) 322-2645
FAX
(708) 639-1469
Phone
+11 1236 730 595
FAX
+44 1236 730 627
Phone
(619) 674-8100
FAX
(619) 674-8262
Pulse Engineering Inc.,
Phone
+353 93 24 107
Europe
FAX
+353 93 24 459
Renco Electronics Inc.
Phone
(800) 645-5828
FAX
(516) 586-5562
Phone
(612) 475-1173
FAX
(612) 475-1786
Schott Corp.
FIGURE 9. Inductor Manufacturers Phone Numbers
www.national.com
16
DO3308-223
Nichicon Corp.
Panasonic
AVX Corp.
Sprague/Vishay
Phone
LM2599
LM2599 Series Buck Regulator Design Procedure
(Continued)
(708) 843-7500
FAX
(708) 843-2798
Phone
(714) 373-7857
FAX
(714) 373-7102
Phone
(803) 448-9411
FAX
(803) 448-1943
Phone
(207) 324-4140
FAX
(207) 324-7223
FIGURE 10. Capacitor Manufacturers Phone Numbers
3 Amp Diodes
Surface Mount
VR
Schottky
Ultra Fast
Through Hole
Schottky
Recovery
All of
20V
SK32
30WQ03
30V
40V
50V
or
more
SK33
4 to 6 Amp Diodes
1N5820
Surface Mount
Ultra Fast
Schottky
Ultra Fast
Through Hole
Schottky
Recovery
Recovery
All of
All of
SR502
Ultra Fast
Recovery
All of
these
SR302
these
these
1N5823
these
diodes
MBR320
diodes
diodes
SB520
diodes
are rated
1N5821
are rated
are rated
to at
MBR330
to at
to at
SR503
to at
least
31DQ03
least
least
1N5824
least
50V.
1N5822
50V.
50V.
SB530
50V.
SK34
SR304
MBRS340
MBR340
30WQ04
MURS320
31DQ04
SK35
30WF10
SR305
MBRS360
MBR350
30WQ05
31DQ05
50WQ03
are rated
50WQ04
SR504
1N5825
MUR320
MURS620
SB540
50WF10
50WQ05
MUR620
HER601
SB550
50SQ080
FIGURE 11. Diode Selection Table
17
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LM2599
Block Diagram
DS012582-30
FIGURE 12.
Special Note If any of the above three features (Shutdown
/Soft-start, Error Flag, or Delay) are not used, the respective
pins should be left open.
Application Information
PIN FUNCTIONS
+VIN (Pin 1) — This is the positive input supply for the IC
switching regulator. A suitable input bypass capacitor must
be present at this pin to minimize voltage transients and to
supply the switching currents needed by the regulator.
Ground (Pin 4) — Circuit ground.
Output (Pin 2) — Internal switch. The voltage at this pin
switches between approximately (+VIN − VSAT) and approximately −0.5V, with a duty cycle of VOUT/VIN. To minimize
coupling to sensitive circuitry, the PC board copper area
connected to this pin should be kept to a minimum.
Feedback (Pin 6) — Senses the regulated output voltage to
complete the feedback loop.
Shutdown /Soft-start (Pin 7) — This dual function pin provides the following features: (a) Allows the switching regulator circuit to be shut down using logic level signals thus
dropping the total input supply current to approximately
80 µA. (b) Adding a capacitor to this pin provides a soft-start
feature which minimizes startup current and provides a controlled ramp up of the output voltage.
Error Flag (Pin 3) — Open collector output that provides a
low signal (flag transistor ON) when the regulated output
voltage drops more than 5% from the nominal output voltage. On start up, Error Flag is low until VOUT reaches 95% of
the nominal output voltage and a delay time determined by
the Delay pin capacitor. This signal can be used as a reset to
a microprocessor on power-up.
Delay (Pin 5) — At power-up, this pin can be used to provide
a time delay between the time the regulated output voltage
reaches 95% of the nominal output voltage, and the time the
error flag output goes high.
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EXTERNAL COMPONENTS
SOFT-START CAPACITOR
CSS — A capacitor on this pin provides the regulator with a
Soft-start feature (slow start-up). When the DC input voltage
is first applied to the regulator, or when the Shutdown
/Soft-start pin is allowed to go high, a constant current
(approximately 5 µA begins charging this capacitor). As the
capacitor voltage rises, the regulator goes through four operating regions (See the bottom curve in Figure 13).
1. Regulator in Shutdown. When the SD /SS pin voltage is
between 0V and 1.3V, the regulator is in shutdown, the
output voltage is zero, and the IC quiescent current is approximately 85 µA.
2. Regulator ON, but the output voltage is zero. With the
SD /SS pin voltage between approximately 1.3V and 1.8V,
the internal regulator circuitry is operating, the quiescent
current rises to approximately 5 mA, but the output voltage is
still zero. Also, as the 1.3V threshold is exceeded, the
Soft-start capacitor charging current decreases from 5 µA
down to approximately 1.6 µA. This decreases the slope of
capacitor voltage ramp.
3. Soft-start Region. When the SD /SS pin voltage is between 1.8V and 2.8V (@ 25˚C), the regulator is in a Soft-start
condition. The switch (Pin 2) duty cycle initially starts out
very low, with narrow pulses and gradually get wider as the
capacitor SD /SS pin ramps up towards 2.8V. As the duty
cycle increases, the output voltage also increases at a controlled ramp up. See the center curve in Figure 13. The input
supply current requirement also starts out at a low level for
18
LM2599
Application Information
(Continued)
the narrow pulses and ramp up in a controlled manner. This
is a very useful feature in some switcher topologies that
require large startup currents (such as the inverting configuration) which can load down the input power supply.
Note: The lower curve shown in Figure 13 shows the Soft-start region from
0% to 100%. This is not the duty cycle percentage, but the output
voltage percentage. Also, the Soft-start voltage range has a negative
temperature coefficient associated with it. See the Soft-start curve in
the electrical characteristics section.
4. Normal operation. Above 2.8V, the circuit operates as a
standard Pulse Width Modulated switching regulator. The
capacitor will continue to charge up until it reaches the
internal clamp voltage of approximately 7V. If this pin is
driven from a voltage source, the current must be limited to
about 1 mA.
If the part is operated with an input voltage at or below the
internal soft-start clamp voltage of approximately 7V, the
voltage on the SD/SS pin tracks the input voltage and can be
disturbed by a step in the voltage. To maintain proper function under these conditions, it is strongly recommended that
the SD/SS pin be clamped externally between the 3V maximum soft-start threshold and the 4.5V minimum input voltage. Figure 15 is an example of an external 3.7V (approx.)
clamp that prevents a line-step related glitch but does not
interfere with the soft-start behavior of the device.
DS012582-31
FIGURE 13. Soft-start, Delay, Error, Output
DS012582-32
FIGURE 14. Timing Diagram for 5V Output
19
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LM2599
Application Information
(Continued)
DS012582-65
FIGURE 15. External 3.7V Soft-Start Clamp
DELAY CAPACITOR
CDELAY — Provides delay for the error flag output. See the
upper curve in Figure 13, and also refer to timing diagrams in
Figure 14. A capacitor on this pin provides a time delay
between the time the regulated output voltage (when it is
increasing in value) reaches 95% of the nominal output
voltage, and the time the error flag output goes high. A 3 µA
constant current from the delay pin charges the delay capacitor resulting in a voltage ramp. When this voltage
reaches a threshold of approximately 1.3V, the open collector error flag output (or power OK) goes high. This signal can
be used to indicate that the regulated output has reached the
correct voltage and has stabilized.
If, for any reason, the regulated output voltage drops by 5%
or more, the error output flag (Pin 3) immediately goes low
(internal transistor turns on). The delay capacitor provides
very little delay if the regulated output is dropping out of
regulation. The delay time for an output that is decreasing is
approximately a 1000 times less than the delay for the rising
output. For a 0.1 µF delay capacitor, the delay time would be
approximately 50 ms when the output is rising and passes
through the 95% threshold, but the delay for the output
dropping would only be approximately 50 µs.
RPull Up — The error flag output, (or power OK) is the collector of a NPN transistor, with the emitter internally
grounded. To use the error flag, a pullup resistor to a positive
voltage is needed. The error flag transistor is rated up to a
maximum of 45V and can sink approximately 3 mA. If the
error flag is not used, it can be left open.
INPUT CAPACITOR
CIN — A low ESR aluminum or tantalum bypass capacitor is
needed between the input pin and ground pin. It must be
located near the regulator using short leads. This capacitor
prevents large voltage transients from appearing at the input, and provides the instantaneous current needed each
time the switch turns on.
The important parameters for the Input capacitor are the
voltage rating and the RMS current rating. Because of the
relatively high RMS currents flowing in a buck regulator’s
input capacitor, this capacitor should be chosen for its RMS
current rating rather than its capacitance or voltage ratings,
although the capacitance value and voltage rating are directly related to the RMS current rating.
The RMS current rating of a capacitor could be viewed as a
capacitor’s power rating. The RMS current flowing through
the capacitors internal ESR produces power which causes
the internal temperature of the capacitor to rise. The RMS
current rating of a capacitor is determined by the amount of
current required to raise the internal temperature approximately 10˚C above an ambient temperature of 105˚C. The
ability of the capacitor to dissipate this heat to the surrounding air will determine the amount of current the capacitor can
safely sustain. Capacitors that are physically large and have
a large surface area will typically have higher RMS current
ratings. For a given capacitor value, a higher voltage electrolytic capacitor will be physically larger than a lower voltage
capacitor, and thus be able to dissipate more heat to the
surrounding air, and therefore will have a higher RMS current rating.
FEEDFORWARD CAPACITOR
(Adjustable Output Voltage Version)
CFF - A Feedforward Capacitor CFF, shown across R2 in
Figure 1 is used when the output voltage is greater than 10V
or when COUT has a very low ESR. This capacitor adds lead
compensation to the feedback loop and increases the phase
margin for better loop stability. For CFF selection, see the
design procedure section.
If the output ripple is large ( > 5% of the nominal output
voltage), this ripple can be coupled to the feedback pin
through the feedforward capacitor and cause the error comparator to trigger the error flag. In this situation, adding a
resistor, RFF, in series with the feedforward capacitor, approximately 3 times R1, will attenuate the ripple voltage at
the feedback pin.
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20
bypassing, but several precautions must be observed. A
small percentage of solid tantalum capacitors can short if the
inrush current rating is exceeded. This can happen at turn on
when the input voltage is suddenly applied, and of course,
higher input voltages produce higher inrush currents. Several capacitor manufacturers do a 100% surge current testing on their products to minimize this potential problem. If
high turn on currents are expected, it may be necessary to
limit this current by adding either some resistance or inductance before the tantalum capacitor, or select a higher voltage capacitor. As with aluminum electrolytic capacitors, the
RMS ripple current rating must be sized to the load current.
(Continued)
OUTPUT CAPACITOR
COUT — An output capacitor is required to filter the output
and provide regulator loop stability. Low impedance or low
ESR Electrolytic or solid tantalum capacitors designed for
switching regulator applications must be used. When selecting an output capacitor, the important capacitor parameters
are; the 100 kHz Equivalent Series Resistance (ESR), the
RMS ripple current rating, voltage rating, and capacitance
value. For the output capacitor, the ESR value is the most
important parameter.
DS012582-33
FIGURE 16. RMS Current Ratings for Low
ESR Electrolytic Capacitors (Typical)
The output capacitor requires an ESR value that has an
upper and lower limit. For low output ripple voltage, a low
ESR value is needed. This value is determined by the maximum allowable output ripple voltage, typically 1% to 2% of
the output voltage. But if the selected capacitor’s ESR is
extremely low, there is a possibility of an unstable feedback
loop, resulting in an oscillation at the output. Using the
capacitors listed in the tables, or similar types, will provide
design solutions under all conditions.
If very low output ripple voltage (less than 15 mV) is required, refer to the section on Output Voltage Ripple and
Transients for a post ripple filter.
An aluminum electrolytic capacitor’s ESR value is related to
the capacitance value and its voltage rating. In most cases,
higher voltage electrolytic capacitors have lower ESR values
(see Figure 17). Often, capacitors with much higher voltage
ratings may be needed to provide the low ESR values required for low output ripple voltage.
The output capacitor for many different switcher designs
often can be satisfied with only three or four different capacitor values and several different voltage ratings. See the
quick design component selection tables in Figure 2 and 3
for typical capacitor values, voltage ratings, and manufacturers capacitor types.
Electrolytic capacitors are not recommended for temperatures below −25˚C. The ESR rises dramatically at cold temperatures and typically rises 3X @ −25˚C and as much as
10X at −40˚C. See curve shown in Figure 18.
Solid tantalum capacitors have a much better ESR spec for
cold temperatures and are recommended for temperatures
below −25˚C.
DS012582-34
FIGURE 17. Capacitor ESR vs Capacitor Voltage Rating
(Typical Low ESR Electrolytic Capacitor)
The consequences of operating an electrolytic capacitor
above the RMS current rating is a shortened operating life.
The higher temperature speeds up the evaporation of the
capacitor’s electrolyte, resulting in eventual failure.
Selecting an input capacitor requires consulting the manufacturers data sheet for maximum allowable RMS ripple
current. For a maximum ambient temperature of 40˚C, a
general guideline would be to select a capacitor with a ripple
current rating of approximately 50% of the DC load current.
For ambient temperatures up to 70˚C, a current rating of
75% of the DC load current would be a good choice for a
conservative design. The capacitor voltage rating must be at
least 1.25 times greater than the maximum input voltage,
and often a much higher voltage capacitor is needed to
satisfy the RMS current requirements.
A graph shown in Figure 16 shows the relationship between
an electrolytic capacitor value, its voltage rating, and the
RMS current it is rated for. These curves were obtained from
the Nichicon “PL” series of low ESR, high reliability electrolytic capacitors designed for switching regulator applications.
Other capacitor manufacturers offer similar types of capacitors, but always check the capacitor data sheet.
“Standard” electrolytic capacitors typically have much higher
ESR numbers, lower RMS current ratings and typically have
a shorter operating lifetime.
Because of their small size and excellent performance, surface mount solid tantalum capacitors are often used for input
CATCH DIODE
Buck regulators require a diode to provide a return path for
the inductor current when the switch turns off. This must be
a fast diode and must be located close to the LM2599 using
short leads and short printed circuit traces.
Because of their very fast switching speed and low forward
voltage drop, Schottky diodes provide the best performance,
especially in low output voltage applications (5V and lower).
Ultra-fast recovery, or High-Efficiency rectifiers are also a
good choice, but some types with an abrupt turnoff charac21
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LM2599
Application Information
LM2599
Application Information
(Continued)
teristic may cause instability or EMI problems. Ultra-fast
recovery diodes typically have reverse recovery times of 50
ns or less. Rectifiers such as the IN5400 series are much too
slow and should not be used.
DS012582-36
FIGURE 19. (∆IIND) Peak-to-Peak Inductor Ripple
Current (as a Percentage of the
Load Current) vs Load Current
By allowing the percentage of inductor ripple current to
increase for low load currents, the inductor value and size
can be kept relatively low.
When operating in the continuous mode, the inductor current
waveform ranges from a triangular to a sawtooth type of
waveform (depending on the input voltage), with the average
value of this current waveform equal to the DC output load
current.
Inductors are available in different styles such as pot core,
toroid, E-core, bobbin core, etc., as well as different core
materials, such as ferrites and powdered iron. The least
expensive, the bobbin, rod or stick core, consists of wire
wound on a ferrite bobbin. This type of construction makes
for an inexpensive inductor, but since the magnetic flux is not
completely contained within the core, it generates more
Electro-Magnetic Interference (EMl). This magnetic flux can
induce voltages into nearby printed circuit traces, thus causing problems with both the switching regulator operation and
nearby sensitive circuitry, and can give incorrect scope readings because of induced voltages in the scope probe. Also
see section on Open Core Inductors.
When multiple switching regulators are located on the same
PC board, open core magnetics can cause interference
between two or more of the regulator circuits, especially at
high currents. A torroid or E-core inductor (closed magnetic
structure) should be used in these situations.
The inductors listed in the selection chart include ferrite
E-core construction for Schott, ferrite bobbin core for Renco
and Coilcraft, and powdered iron toroid for Pulse Engineering.
Exceeding an inductor’s maximum current rating may cause
the inductor to overheat because of the copper wire losses,
or the core may saturate. If the inductor begins to saturate,
the inductance decreases rapidly and the inductor begins to
look mainly resistive (the DC resistance of the winding). This
can cause the switch current to rise very rapidly and force
the switch into a cycle-by-cycle current limit, thus reducing
the DC output load current. This can also result in overheating of the inductor and/or the LM2599. Different inductor
types have different saturation characteristics, and this
should be kept in mind when selecting an inductor.
The inductor manufacturer’s data sheets include current and
energy limits to avoid inductor saturation.
DS012582-35
FIGURE 18. Capacitor ESR Change vs Temperature
INDUCTOR SELECTION
All switching regulators have two basic modes of operation;
continuous and discontinuous. The difference between the
two types relates to the inductor current, whether it is flowing
continuously, or if it drops to zero for a period of time in the
normal switching cycle. Each mode has distinctively different
operating characteristics, which can affect the regulators
performance and requirements. Most switcher designs will
operate in the discontinuous mode when the load current is
low.
The LM2599 (or any of the Simple Switcher family) can be
used for both continuous or discontinuous modes of operation.
In many cases the preferred mode of operation is the continuous mode. It offers greater output power, lower peak
switch, inductor and diode currents, and can have lower
output ripple voltage. But it does require larger inductor
values to keep the inductor current flowing continuously,
especially at low output load currents and/or high input voltages.
To simplify the inductor selection process, an inductor selection guide (nomograph) was designed (see Figure 4 through
7). This guide assumes that the regulator is operating in the
continuous mode, and selects an inductor that will allow a
peak-to-peak inductor ripple current to be a certain percentage of the maximum design load current. This peak-to-peak
inductor ripple current percentage is not fixed, but is allowed
to change as different design load currents are selected.
(See Figure 19).
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22
ESR capacitors because they can affect the loop stability,
resulting in oscillation problems. If very low output ripple
voltage is needed (less than 20 mV), a post ripple filter is
recommended (See Figure 1). The inductance required is
typically between 1 µH and 5 µH, with low DC resistance, to
maintain good load regulation. A low ESR output filter capacitor is also required to assure good dynamic load response and ripple reduction. The ESR of this capacitor may
be as low as desired, because it is out of the regulator
feedback loop. The photo shown in Figure 20 shows a
typical output ripple voltage, with and without a post ripple
filter.
When observing output ripple with a scope, it is essential
that a short, low inductance scope probe ground connection
be used. Most scope probe manufacturers provide a special
probe terminator which is soldered onto the regulator board,
preferable at the output capacitor. This provides a very short
scope ground thus eliminating the problems associated with
the 3 inch ground lead normally provided with the probe, and
provides a much cleaner and more accurate picture of the
ripple voltage waveform.
The voltage spikes are caused by the fast switching action of
the output switch, the diode, and the parasitic inductance of
the output filter capacitor, and its associated wiring. To minimize these voltage spikes, the output capacitor should be
designed for switching regulator applications, and the lead
lengths must be kept very short. Wiring inductance, stray
capacitance, as well as the scope probe used to evaluate
these transients, all contribute to the amplitude of these
spikes.
(Continued)
DISCONTINUOUS MODE OPERATION
The selection guide chooses inductor values suitable for
continuous mode operation, but for low current applications
and/or high input voltages, a discontinuous mode design
may be a better choice. It would use an inductor that would
be physically smaller, and would need only one half to one
third the inductance value needed for a continuous mode
design. The peak switch and inductor currents will be higher
in a discontinuous design, but at these low load currents (1A
and below), the maximum switch current will still be less than
the switch current limit.
Discontinuous operation can have voltage waveforms that
are considerable different than a continuous design. The
output pin (switch) waveform can have some damped sinusoidal ringing present. (See Typical Performance Characteristics photo titled Discontinuous Mode Switching Waveforms) This ringing is normal for discontinuous operation,
and is not caused by feedback loop instabilities. In discontinuous operation, there is a period of time where neither the
switch or the diode are conducting, and the inductor current
has dropped to zero. During this time, a small amount of
energy can circulate between the inductor and the switch/
diode parasitic capacitance causing this characteristic ringing. Normally this ringing is not a problem, unless the amplitude becomes great enough to exceed the input voltage, and
even then, there is very little energy present to cause damage.
Different inductor types and/or core materials produce different amounts of this characteristic ringing. Ferrite core inductors have very little core loss and therefore produce the most
ringing. The higher core loss of powdered iron inductors
produce less ringing. If desired, a series RC could be placed
in parallel with the inductor to dampen the ringing. The
computer aided design software Switchers Made Simple
(version 4.3) will provide all component values for continuous and discontinuous modes of operation.
DS012582-49
FIGURE 21. Peak-to-Peak Inductor
Ripple Current vs Load Current
When a switching regulator is operating in the continuous
mode, the inductor current waveform ranges from a triangular to a sawtooth type of waveform (depending on the input
voltage). For a given input and output voltage, the
peak-to-peak amplitude of this inductor current waveform
remains constant. As the load current increases or decreases, the entire sawtooth current waveform also rises
and falls. The average value (or the center) of this current
waveform is equal to the DC load current.
If the load current drops to a low enough level, the bottom of
the sawtooth current waveform will reach zero, and the
switcher will smoothly change from a continuous to a discontinuous mode of operation. Most switcher designs (irregardless how large the inductor value is) will be forced to run
discontinuous if the output is lightly loaded. This is a perfectly acceptable mode of operation.
In a switching regulator design, knowing the value of the
peak-to-peak inductor ripple current (∆IIND) can be useful for
DS012582-37
FIGURE 20. Post Ripple Filter Waveform
OUTPUT VOLTAGE RIPPLE AND TRANSIENTS
The output voltage of a switching power supply operating in
the continuous mode will contain a sawtooth ripple voltage at
the switcher frequency, and may also contain short voltage
spikes at the peaks of the sawtooth waveform.
The output ripple voltage is a function of the inductor sawtooth ripple current and the ESR of the output capacitor. A
typical output ripple voltage can range from approximately
0.5% to 3% of the output voltage. To obtain low ripple
voltage, the ESR of the output capacitor must be low, however, caution must be exercised when using extremely low
23
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LM2599
Application Information
LM2599
Application Information
OPEN CORE INDUCTORS
(Continued)
Another possible source of increased output ripple voltage or
unstable operation is from an open core inductor. Ferrite
bobbin or stick inductors have magnetic lines of flux flowing
through the air from one end of the bobbin to the other end.
These magnetic lines of flux will induce a voltage into any
wire or PC board copper trace that comes within the inductor’s magnetic field. The strength of the magnetic field, the
orientation and location of the PC copper trace to the magnetic field, and the distance between the copper trace and
the inductor, determine the amount of voltage generated in
the copper trace. Another way of looking at this inductive
coupling is to consider the PC board copper trace as one
turn of a transformer (secondary) with the inductor winding
as the primary. Many millivolts can be generated in a copper
trace located near an open core inductor which can cause
stability problems or high output ripple voltage problems.
If unstable operation is seen, and an open core inductor is
used, it’s possible that the location of the inductor with
respect to other PC traces may be the problem. To determine if this is the problem, temporarily raise the inductor
away from the board by several inches and then check
circuit operation. If the circuit now operates correctly, then
the magnetic flux from the open core inductor is causing the
problem. Substituting a closed core inductor such as a torroid or E-core will correct the problem, or re-arranging the
PC layout may be necessary. Magnetic flux cutting the IC
device ground trace, feedback trace, or the positive or negative traces of the output capacitor should be minimized.
Sometimes, locating a trace directly beneath a bobbin inductor will provide good results, provided it is exactly in the
center of the inductor (because the induced voltages cancel
themselves out), but if it is off center one direction or the
other, then problems could arise. If flux problems are
present, even the direction of the inductor winding can make
a difference in some circuits.
This discussion on open core inductors is not to frighten the
user, but to alert the user on what kind of problems to watch
out for when using them. Open core bobbin or “stick” inductors are an inexpensive, simple way of making a compact
efficient inductor, and they are used by the millions in many
different applications.
determining a number of other circuit parameters. Parameters such as, peak inductor or peak switch current, minimum load current before the circuit becomes discontinuous,
output ripple voltage and output capacitor ESR can all be
calculated from the peak-to-peak ∆IIND. When the inductor
nomographs shown in Figure 4 through 7 are used to select
an inductor value, the peak-to-peak inductor ripple current
can immediately be determined. The curve shown in Figure
21 shows the range of (∆IIND) that can be expected for
different load currents. The curve also shows how the
peak-to-peak inductor ripple current (∆IIND) changes as you
go from the lower border to the upper border (for a given load
current) within an inductance region. The upper border represents a higher input voltage, while the lower border represents a lower input voltage (see Inductor Selection Guides).
These curves are only correct for continuous mode operation, and only if the inductor selection guides are used to
select the inductor value
Consider the following example:
VOUT = 5V, maximum load current of 2.5A
VIN = 12V, nominal, varying between 10V and 16V.
The selection guide in Figure 5 shows that the vertical line
for a 2.5A load current, and the horizontal line for the 12V
input voltage intersect approximately midway between the
upper and lower borders of the 33 µH inductance region. A
33 µH inductor will allow a peak-to-peak inductor current
(∆IIND) to flow that will be a percentage of the maximum load
current. Referring to Figure 21, follow the 2.5A line approximately midway into the inductance region, and read the
peak-to-peak inductor ripple current (∆IIND) on the left hand
axis (approximately 620 mA p-p).
As the input voltage increases to 16V, it approaches the
upper border of the inductance region, and the inductor
ripple current increases. Referring to the curve in Figure 21,
it can be seen that for a load current of 2.5A, the
peak-to-peak inductor ripple current (∆IIND) is 620 mA with
12V in, and can range from 740 mA at the upper border (16V
in) to 500 mA at the lower border (10V in).
Once the ∆IIND value is known, the following formulas can be
used to calculate additional information about the switching
regulator circuit.
1. Peak Inductor or peak switch current
2.
Minimum load current before the circuit becomes discontinuous
3.
Output Ripple Voltage = (∆IIND)x(ESR of COUT)
= 0.62Ax0.1Ω=62 mV p-p
THERMAL CONSIDERATIONS
The LM2599 is available in two packages, a 7-pin TO-220
(T) and a 7-pin surface mount TO-263 (S).
The TO-220 package needs a heat sink under most conditions. The size of the heat sink depends on the input voltage,
the output voltage, the load current and the ambient temperature. The curves in Figure 22 show the LM2599T junction temperature rises above ambient temperature for a 3A
load and different input and output voltages. The data for
these curves was taken with the LM2599T (TO-220 package) operating as a buck switching regulator in an ambient
temperature of 25˚C (still air). These temperature rise numbers are all approximate and there are many factors that can
affect these temperatures. Higher ambient temperatures require more heat sinking.
The TO-263 surface mount package tab is designed to be
soldered to the copper on a printed circuit board. The copper
and the board are the heat sink for this package and the
other heat producing components, such as the catch diode
and inductor. The pc board copper area that the package is
soldered to should be at least 0.4 in2, and ideally should
have 2 or more square inches of 2 oz. (0.0028 in) copper.
Additional copper area improves the thermal characteristics,
4.
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LM2599
Application Information
(Continued)
but with copper areas greater than approximately 6 in2, only
small improvements in heat dissipation are realized. If further thermal improvements are needed, double sided, multilayer pc-board with large copper areas and/or airflow are
recommended.
The curves shown in Figure 23 show the LM2599S (TO-263
package) junction temperature rise above ambient temperature with a 2A load for various input and output voltages. This
data was taken with the circuit operating as a buck switching
regulator with all components mounted on a pc board to
simulate the junction temperature under actual operating
conditions. This curve can be used for a quick check for the
approximate junction temperature for various conditions, but
be aware that there are many factors that can affect the
junction temperature. When load currents higher than 2A are
used, double sided or multilayer pc-boards with large copper
areas and/or airflow might be needed, especially for high
ambient temperatures and high output voltages.
DS012582-39
Circuit Data for Temperature Rise Curve TO-263
Package (S)
Capacitors
Surface mount tantalum, molded “D” size
Inductor
Surface mount, Pulse engineering, 68 µH
Diode
Surface mount, 5A 40V, Schottky
PC board
9 square inches single sided 2 oz. copper
(0.0028")
FIGURE 23. Junction Temperature Rise, TO-263
For the best thermal performance, wide copper traces and
generous amounts of printed circuit board copper should be
used in the board layout. (One exception to this is the output
(switch) pin, which should not have large areas of copper.)
Large areas of copper provide the best transfer of heat
(lower thermal resistance) to the surrounding air, and moving
air lowers the thermal resistance even further.
Package thermal resistance and junction temperature rise
numbers are all approximate, and there are many factors
that will affect these numbers. Some of these factors include
board size, shape, thickness, position, location, and even
board temperature. Other factors are, trace width, total
printed circuit copper area, copper thickness, single- or
double-sided, multilayer board and the amount of solder on
the board. The effectiveness of the pc board to dissipate
heat also depends on the size, quantity and spacing of other
components on the board, as well as whether the surrounding air is still or moving. Furthermore, some of these components such as the catch diode will add heat to the pc
board and the heat can vary as the input voltage changes.
For the inductor, depending on the physical size, type of core
material and the DC resistance, it could either act as a heat
sink taking heat away from the board, or it could add heat to
the board.
DS012582-38
Circuit Data for Temperature Rise Curve TO-220
Package (T)
Capacitors
Through hole electrolytic
Inductor
Through hole Renco
Diode
Through hole, 5A 40V, Schottky
PC board
3 square inches single sided 2 oz. copper
(0.0028")
FIGURE 22. Junction Temperature Rise, TO-220
SHUTDOWN /SOFT-START
The circuit shown in Figure 26 is a standard buck regulator
with 20V in, 12V out, 1A load, and using a 0.068 µF Soft-start
capacitor. The photo in Figure 24 Figure 25 show the effects
of Soft-start on the output voltage, the input current, with,
and without a Soft-start capacitor. The reduced input current
required at startup is very evident when comparing the two
photos. The Soft-start feature reduces the startup current
from 2.6A down to 650 mA, and delays and slows down the
output voltage rise time.
25
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LM2599
Application Information
(Continued)
DS012582-41
FIGURE 25. Output Voltage, Input Current,
at Start-Up, WITHOUT Soft-start
DS012582-40
FIGURE 24. Output Voltage, Input Current,
at Start-Up, WITH Soft-start
This reduction in start up current is useful in situations where
the input power source is limited in the amount of current it
can deliver. In some applications Soft-start can be used to
replace undervoltage lockout or delayed startup functions.
If a very slow output voltage ramp is desired, the Soft-start
capacitor can be made much larger. Many seconds or even
minutes are possible.
If only the shutdown feature is needed, the Soft-start capacitor can be eliminated.
DS012582-42
FIGURE 26. Typical Circuit Using Shutdown /Soft-start and Error Flag Features
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LM2599
Application Information
(Continued)
DS012582-43
FIGURE 27. Inverting −5V Regulator With Shutdown and Soft-start
lNVERTING REGULATOR
The circuit in Figure 27 converts a positive input voltage to a
negative output voltage with a common ground. The circuit
operates by bootstrapping the regulator’s ground pin to the
negative output voltage, then grounding the feedback pin,
the regulator senses the inverted output voltage and regulates it.
This example uses the LM2599-5 to generate a −5V output,
but other output voltages are possible by selecting other
output voltage versions, including the adjustable version.
Since this regulator topology can produce an output voltage
that is either greater than or less than the input voltage, the
maximum output current greatly depends on both the input
and output voltage. The curve shown in Figure 28 provides a
guide as to the amount of output load current possible for the
different input and output voltage conditions.
The maximum voltage appearing across the regulator is the
absolute sum of the input and output voltage, and this must
be limited to a maximum of 40V. In this example, when
converting +20V to −5V, the regulator would see 25V between the input pin and ground pin. The LM2599 has a
maximum input voltage rating of 40V.
An additional diode is required in this regulator configuration.
Diode D1 is used to isolate input voltage ripple or noise from
coupling through the CIN capacitor to the output, under light
or no load conditions. Also, this diode isolation changes the
topology to closely resemble a buck configuration thus providing good closed loop stability. A Schottky diode is recommended for low input voltages, (because of its lower voltage
drop) but for higher input voltages, a IN5400 diode could be
used.
Because of differences in the operation of the inverting
regulator, the standard design procedure is not used to
select the inductor value. In the majority of designs, a 33 µH,
3.5A inductor is the best choice. Capacitor selection can also
be narrowed down to just a few values. Using the values
shown in Figure 27 will provide good results in the majority of
inverting designs.
This type of inverting regulator can require relatively large
amounts of input current when starting up, even with light
loads. Input currents as high as the LM2599 current limit
(approximately 4.5A) are needed for 2 ms or more, until the
output reaches its nominal output voltage. The actual time
depends on the output voltage and the size of the output
capacitor. Input power sources that are current limited or
sources that can not deliver these currents without getting
loaded down, may not work correctly. Because of the relatively high startup currents required by the inverting topology,
the Soft-start feature shown in Figure 27 is recommended.
Also shown in Figure 27 are several shutdown methods for
the inverting configuration. With the inverting configuration,
some level shifting is required, because the ground pin of the
regulator is no longer at ground, but is now at the negative
output voltage. The shutdown methods shown accept
ground referenced shutdown signals.
Inverting Regulator
UNDERVOLTAGE LOCKOUT
Some applications require the regulator to remain off until
the input voltage reaches a predetermined voltage. Figure
29 contains a undervoltage lockout circuit for a buck configuration, while Figure 30 and 30 are for the inverting types
(only the circuitry pertaining to the undervoltage lockout is
DS012582-44
FIGURE 28. Maximum Load Current for
Inverting Regulator Circuit
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LM2599
Application Information
(Continued)
shown). Figure 29 uses a zener diode to establish the
threshold voltage when the switcher begins operating. When
the input voltage is less than the zener voltage, resistors R1
and R2 hold the Shutdown /Soft-start pin low, keeping the
regulator in the shutdown mode. As the input voltage exceeds the zener voltage, the zener conducts, pulling the
Shutdown /Soft-start pin high, allowing the regulator to begin
switching. The threshold voltage for the undervoltage lockout
feature is approximately 1.5V greater than the zener voltage.
DS012582-47
FIGURE 30. Undervoltage Lockout Without
Hysteresis for an Inverting Regulator
DS012582-45
FIGURE 29. Undervoltage Lockout for a Buck
Regulator
Figure 30 and 30 apply the same feature to an inverting
circuit. Figure 30 features a constant threshold voltage for
turn on and turn off (zener voltage plus approximately one
volt). If hysteresis is needed, the circuit in Figure 31 has a
turn ON voltage which is different than the turn OFF voltage.
The amount of hysteresis is approximately equal to the value
of the output voltage. Since the SD /SS pin has an internal
7V zener clamp, R2 is needed to limit the current into this pin
to approximately 1 mA when Q1 is on.
DS012582-46
FIGURE 31. Undervoltage Lockout With
Hysteresis for an Inverting Regulator
NEGATIVE VOLTAGE CHARGE PUMP
Occasionally a low current negative voltage is needed for
biasing parts of a circuit. A simple method of generating a
negative voltage using a charge pump technique and the
switching waveform present at the OUT pin, is shown in
Figure 32. This unregulated negative voltage is approximately equal to the positive input voltage (minus a few volts),
and can supply up to a 600 mA of output current. There is a
requirement however, that there be a minimum load of 1.2A
on the regulated positive output for the charge pump to work
correctly. Also, resistor R1 is required to limit the charging
current of C1 to some value less than the LM2599 current
limit (typically 4.5A).
This method of generating a negative output voltage without
an additional inductor can be used with other members of
the Simple Switcher Family, using either the buck or boost
topology.
DS012582-48
FIGURE 32. Charge Pump for Generating a
Low Current, Negative Output Voltage
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LM2599
Application Information
(Continued)
TYPICAL THROUGH HOLE PC BOARD LAYOUT, FIXED OUTPUT (1X SIZE), DOUBLE SIDED
DS012582-51
CIN:
— 470 µF, 50V, Aluminum Electrolytic Panasonic, “HFQ Series”
COUT: — 330 µF, 35V, Aluminum Electrolytic Panasonic, “HFQ Series”
D1: — 5A, 40V Schottky Rectifier, 1N5825
L1: — 47 µH, L39, Renco, Through Hole
RPULL UP: — 10k
CDELAY: — 0.1 µF
CSD/SS: — 0.1 µF
Thermalloy Heat Sink #7020
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LM2599
Application Information
(Continued)
TYPICAL THROUGH HOLE PC BOARD LAYOUT, ADJUSTABLE OUTPUT (1X SIZE), DOUBLE SIDED
DS012582-52
CIN:
— 470 µF, 50V, Aluminum Electrolytic Panasonic, “HFQ Series”
COUT: — 220 µF, 35V Aluminum Electrolytic Panasonic, “HFQ Series”
D1: — 5A, 40V Schottky Rectifier, 1N5825
L1: — 47 µH, L39, Renco, Through Hole
R1: — 1 kΩ, 1%
R2: — Use formula in Design Procedure
CFF: — See Figure 4.
RFF: — See Application Information Section (CFF Section)
RPULL UP: — 10k
CDELAY: — 0.1 µF
CSD/SS: — 0.1 µF
Thermalloy Heat Sink #7020
FIGURE 33. PC Board Layout
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30
LM2599
Physical Dimensions
inches (millimeters) unless otherwise noted
7-Lead TO-220 Bent and Staggered Package
Order Number LM2599T-3.3, LM2599T-5.0,
LM2599T-12 or LM2599T-ADJ
NS Package Number TA07B
31
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LM2599 SIMPLE SWITCHER Power Converter 150 kHz 3A Step-Down Voltage Regulator, with
Features
Physical Dimensions
inches (millimeters) unless otherwise noted (Continued)
7-Lead TO-263 Bent and Formed Package
Order Number LM2599S-3.3, LM2599S-5.0, LM2599S-12 or LM2599S-ADJ
NS Package Number TS7B
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