AD OP296HRU Micropower, rail-to-rail input and output operational amplifier Datasheet

a
Micropower, Rail-to-Rail Input and Output
Operational Amplifiers
OP196/OP296/OP496
FEATURES
Rail-to-Rail Input and Output Swing
Low Power: 60 ␮A/Amplifier
Gain Bandwidth Product: 450 kHz
Single-Supply Operation: 3 V to 12 V
Low Offset Voltage: 300 ␮V max
High Open-Loop Gain: 500 V/mV
Unity-Gain Stable
No Phase Reversal
PIN CONFIGURATIONS
8-Lead Narrow-Body SO
NULL 1
8 NC
–IN A 2
7 V+
6 OUT A
+IN A 3
OP196
V– 4
5 NULL
8-Lead TSSOP
1
OUT A
–IN A
+IN A
V–
The OP196/OP296/OP496 are specified over the HOT extended
industrial (–40°C to +125°C) temperature range. 3 V operation
is specified over the 0°C to 125°C temperature range.
The single OP196 and the dual OP296 are available in 8-lead
SO-8 surface mount packages. The dual OP296 is available in
8-lead PDIP. The quad OP496 is available in 14-lead plastic
DIP and narrow SO-14 surface-mount packages.
–IN A 2
+IN A 3
8 V+
OP296
V– 4
7 OUT B
6 –IN B
5 +IN B
V+
OUT B
–IN B
+IN B
OP296
4
5
14-Lead Narrow-Body SO
OUT A 1
–IN A 2
+IN A 3
V+ 4
8-Lead Plastic DIP
8
The OP196 family of CBCMOS operational amplifiers features
micropower operation and rail-to-rail input and output ranges.
The extremely low power requirements and guaranteed operation from 3 V to 12 V make these amplifiers perfectly suited to
monitor battery usage and to control battery charging. Their
dynamic performance, including 26 nV/√Hz voltage noise
density, recommends them for battery-powered audio applications. Capacitive loads to 200 pF are handled without oscillation.
OUT A 1
NC = NO CONNECT
APPLICATIONS
Battery Monitoring
Sensor Conditioners
Portable Power Supply Control
Portable Instrumentation
GENERAL DESCRIPTION
8-Lead Narrow-Body SO
OP496
+IN B 5
–IN B 6
14 OUT D
13 –IN D
12 +IN D
11 V–
10 +IN C
9 –IN C
OUT B 7
8 OUT C
OUT A 1
OP296
8
V+
–IN A 2
7 OUT B
+IN A 3
6 –IN B
V– 4
5 +IN B
14-Lead Plastic DIP
OUT A 1
14 OUT D
–IN A 2
13 –IN D
+IN A 3
12 +IN D
V+ 4
OP496
11 V–
+IN B 5
10 +IN C
–IN B 6
9 –IN C
OUT B 7
8 OUT C
14-Lead TSSOP
(RU Suffix)
1
OUT A
–IN A
+IN A
V+
+IN B
–IN B
OUT B
14
OUT D
–IN D
+IN D
V–
+IN C
–IN C
OUT C
OP496
7
8
REV. C
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties that
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
www.analog.com
Fax: 781/326-8703
© Analog Devices, Inc., 2002
OP196/OP296/OP496–SPECIFICATIONS
ELECTRICAL SPECIFICATIONS (@ V = 5.0 V, V
S
CM
= 2.5 V, TA = 25ⴗC, unless otherwise noted.)
Parameter
Symbol
Conditions
INPUT CHARACTERISTICS
Offset Voltage
VOS
OP196G, OP296G, OP496G
–40°C ≤ TA ≤ +125°C
OP296H, OP496H
–40°C ≤ TA ≤ +125°C
–40°C ≤ TA ≤ +125°C
Input Bias Current
Input Offset Current
IB
IOS
Input Voltage Range
VCM
Common-Mode Rejection Ratio
CMRR
Large Signal Voltage Gain
AVO
Long-Term Offset Voltage
VOS
Offset Voltage Drift
∆VOS/∆T
OUTPUT CHARACTERISTICS
Output Voltage Swing High
VOH
Output Voltage Swing Low
VOL
Output Current
IOUT
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current per Amplifier
PSRR
ISY
Min
Typ
Max
Unit
35
300
650
800
1.2
± 50
±8
± 20
µV
µV
µV
mV
nA
nA
nA
5.0
V
± 10
± 1.5
–40°C ≤ TA ≤ +125°C
0
0 V ≤ VCM ≤ 5.0 V,
–40°C ≤ TA ≤ +125°C
RL = 100 kΩ,
0.30 V ≤ VOUT ≤ 4.7 V,
–40°C ≤ TA ≤ +125°C
G Grade, Note 1
H Grade, Note 1
G Grade, Note 2
H Grade, Note 2
IL = –100 µA
IL = 1 mA
IL = 2 mA
IL = –1 mA
IL = –1 mA
IL = –2 mA
± 2.5 V ≤ VS ≤ ± 6 V,
–40°C ≤ TA ≤ +125°C
VOUT = 2.5 V, RL = ∞
–40°C ≤ TA ≤ +125°C
65
150
dB
200
1.5
2
V/mV
µV
mV
µV/°C
µV/°C
4.92
4.56
4.1
36
350
750
±4
V
V
V
mV
mV
mV
mA
550
1
4.85
4.30
70
550
85
45
60
80
dB
µA
µA
DYNAMIC PERFORMANCE
Slew Rate
Gain Bandwidth Product
Phase Margin
SR
GBP
øm
RL = 100 kΩ
0.3
350
47
V/µs
kHz
Degrees
NOISE PERFORMANCE
Voltage Noise
Voltage Noise Density
Current Noise Density
en p-p
en
in
0.1 Hz to 10 Hz
f = 1 kHz
f = 1 kHz
0.8
26
0.19
µV p-p
nV/√Hz
pA/√Hz
NOTES
1
Long-term offset voltage is guaranteed by a 1,000 hour life test performed on three independent lots at 12 5°C, with an LTPD of 1.3.
2
Offset voltage drift is the average of the –40°C to +25°C delta and the +25°C to +125°C delta.
Specifications subject to change without notice.
–2–
REV. C
OP196/OP296/OP496
ELECTRICAL SPECIFICATIONS
(@ VS = 3.0 V, VCM = 1.5 V, TA = 25ⴗC, unless otherwise noted.)
Parameter
Symbol
Conditions
INPUT CHARACTERISTICS
Offset Voltage
VOS
OP196G, OP296G, OP496G
0°C ≤ TA ≤ 125°C
OP296H, OP496H
0°C ≤ TA ≤ 125°C
Input Bias Current
Input Offset Current
IB
IOS
Input Voltage Range
VCM
Common-Mode Rejection Ratio
CMRR
Large Signal Voltage Gain
Long-Term Offset Voltage
AVO
VOS
Offset Voltage Drift
∆VOS/∆T
Min
Typ
Max
Unit
35
300
650
800
1.2
± 50
±8
µV
µV
µV
mV
nA
nA
3.0
V
550
1
dB
V/mV
µV
mV
µV/°C
µV/°C
± 10
±1
0
0 V ≤ VCM ≤ 3.0 V,
0°C ≤ TA ≤ 125°C
RL = 100 kΩ
G Grade, Note 1
H Grade, Note 1
G Grade, Note 2
H Grade, Note 2
60
80
200
1.5
2
OUTPUT CHARACTERISTICS
Output Voltage Swing High
Output Voltage Swing Low
VOH
VOL
IL = 100 µA
IL = –100 µA
POWER SUPPLY
Supply Current per Amplifier
ISY
VOUT = 1.5 V, RL = ∞
0°C ≤ TA ≤ 125°C
DYNAMIC PERFORMANCE
Slew Rate
Gain Bandwidth Product
Phase Margin
SR
GBP
øm
RL = 100 kΩ
0.25
350
45
V/µs
kHz
Degrees
NOISE PERFORMANCE
Voltage Noise
Voltage Noise Density
Current Noise Density
en p-p
en
in
0.1 Hz to 10 Hz
f = 1 kHz
f = 1 kHz
0.8
26
0.19
µV p-p
nV/√Hz
pA/√Hz
2.85
40
NOTES
1
Long-term offset voltage is guaranteed by a 1,000 hour life test performed on three independent lots at 12 5°C, with an LTPD of 1.3.
2
Offset voltage drift is the average of the 0°C to 25°C delta and the 25°C to 125°C delta.
Specifications subject to change without notice.
REV. C
–3–
70
V
mV
60
80
µA
µA
OP196/OP296/OP496
ELECTRICAL SPECIFICATIONS (@ V = 12.0 V, V
S
CM
= 6 V, TA = 25ⴗC, unless otherwise noted.)
Parameter
Symbol
Conditions
INPUT CHARACTERISTICS
Offset Voltage
VOS
OP196G, OP296G, OP496G
0°C ≤ TA ≤ 125°C
OP296H, OP496H
0°C ≤ TA ≤ 125°C
–40°C ≤ TA ≤ +125°C
Input Bias Current
Input Offset Current
IB
IOS
Input Voltage Range
VCM
Common-Mode Rejection Ratio
CMRR
Large Signal Voltage Gain
Long-Term Offset Voltage
AVO
VOS
Offset Voltage Drift
∆VOS/∆T
OUTPUT CHARACTERISTICS
Output Voltage Swing High
VOH
Output Voltage Swing Low
VOL
Output Current
IOUT
POWER SUPPLY
Supply Current per Amplifier
Supply Voltage Range
ISY
Min
Typ
Max
Unit
35
300
650
800
1.2
± 50
±8
± 15
µV
µV
µV
mV
nA
nA
nA
12
V
550
1
1.5
2
dB
V/mV
µV
mV
µV/°C
µV/°C
±4
V
V
mV
mV
mA
± 10
±1
–40°C ≤ TA ≤ +125°C
0
0 V ≤ VCM ≤ 12 V,
–40°C ≤ TA ≤ +125°C
RL = 100 kΩ
G Grade, Note 1
H Grade, Note 1
G Grade, Note 2
H Grade, Note 2
IL = 100 µA
IL = 1 mA
IL = –1 mA
IL = –1 mA
65
300
1000
11.85
11.30
70
550
VOUT = 6 V, RL = ∞
–40°C ≤ TA ≤ +125°C
VS
60
80
12
3
µA
µA
V
DYNAMIC PERFORMANCE
Slew Rate
Gain Bandwidth Product
Phase Margin
SR
GBP
øm
RL = 100 kΩ
0.3
450
50
V/µs
kHz
Degrees
NOISE PERFORMANCE
Voltage Noise
Voltage Noise Density
Current Noise Density
en p-p
en
in
0.1 Hz to 10 Hz
f = 1 kHz
f = 1 kHz
0.8
26
0.19
µV p-p
nV/√Hz
pA/√Hz
NOTES
1
Long-term offset voltage is guaranteed by a 1,000 hour life test performed on three independent lots at 12 5°C, with an LTPD of 1.3.
2
Offset voltage drift is the average of the –40°C to +25°C delta and the +25°C to +125°C delta.
Specifications subject to change without notice.
–4–
REV. C
OP196/OP296/OP496
ABSOLUTE MAXIMUM RATINGS 1
ORDERING GUIDE
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 V
Input Voltage2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 V
Differential Input Voltage2 . . . . . . . . . . . . . . . . . . . . . . . . 15 V
Output Short Circuit Duration . . . . . . . . . . . . . . . . . Indefinite
Storage Temperature Range
P, S, RU Package . . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
OP196G, OP296G, OP496G, H . . . . . . . –40°C to +125°C
Junction Temperature Range
P, S, RU Package . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
Package Type
␪JA3
␪JC
Unit
8-Lead Plastic DIP
8-Lead SOIC
8-Lead TSSOP
14-Lead Plastic DIP
14-Lead SOIC
14-Lead TSSOP
103
158
240
83
120
180
43
43
43
39
36
35
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
Model
Temperature
Range
Package
Description
Package
Option
OP196GS
–40°C to +125°C
8-Lead SOIC
SO-8
OP296GP* –40°C to +125°C
OP296GS
–40°C to +125°C
OP296HRU –40°C to +125°C
8-Lead Plastic DIP
8-Lead SOIC
8-Lead TSSOP
N-8
SO-8
RU-8
OP496GP* –40°C to +125°C
OP496GS
–40°C to +125°C
OP496HRU –40°C to +125°C
14-Lead Plastic DIP N-14
14-Lead SOIC
SO-14
14-Lead TSSOP
RU-14
*Not for new design, obsolete April 2002.
NOTES
1
Absolute maximum ratings apply to both DICE and packaged parts, unless
otherwise noted.
2
For supply voltages less than 15 V, the absolute maximum input voltage is
equal to the supply voltage.
3
θJA is specified for the worst case conditions, i.e., θJA is specified for device in
socket for P-DIP package; θJA is specified for device soldered in circuit board
for SOIC and TSSOP packages.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the OP196/OP296/OP496 feature proprietary ESD protection circuitry, permanent
damage may occur on devices subjected to high-energy electrostatic discharges. Therefore,
proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
REV. C
–5–
WARNING!
ESD SENSITIVE DEVICE
OP196/OP296/OP496–Typical Performance Characteristics
25
250
150
100
0
–250 –200 –150 –100 –50
0
50
100 150
INPUT OFFSET VOLTAGE – ␮V
200
1.0
25
VS = 5V
TA = 25ⴗC
COUNT = 400
VS = 12V
VCM = 6V
TA = –40ⴗC TO ⴙ125ⴗC
20
QUANTITY – Amplifiers
QUANTITY – Amplifiers
–3.0 –2.5 –2.0 –1.5 –1.0 –0.5 0
0.5
INPUT OFFSET DRIFT, TCVOS – ␮V/ⴗC
TPC 4. Input Offset Voltage Distribution (TCVOS)
250
150
100
15
10
5
50
0
–250 –200 –150 –100 –50
0
50
100 150
INPUT OFFSET VOLTAGE – ␮V
200
0
–4.0 –3.5 –3.0 –2.5 –2.0 –1.5 –1.0 –0.5 0 0.5
INPUT OFFSET DRIFT, TCVOS – ␮V/ⴗC
250
TPC 2. Input Offset Voltage Distribution
1.0
1.5
TPC 5. Input Offset Voltage Distribution (TCVOS)
250
600
VS = 12V
TA = 25ⴗC
COUNT = 400
3V
INPUT OFFSET VOLTAGE – ␮V
QUANTITY – Amplifiers
10
0
–4.0 –3.5
250
TPC 1. Input Offset Voltage Distribution
200
15
5
50
200
VS = 5V
VCM = 2.5V
TA = –40ⴗC TO ⴙ125ⴗC
20
QUANTITY – Amplifiers
QUANTITY – Amplifiers
200
VS = 3V
TA = 25ⴗC
COUNT = 400
150
100
50
0
–250 –200 –150 –100 –50
0
50
100 150
INPUT OFFSET VOLTAGE – ␮V
400
VS 12V
VS
2
VCM =
200
0
–200
200
–400
–75
250
TPC 3. Input Offset Voltage Distribution
–50
–25
0
25
50
75
TEMPERATURE – ⴗC
100
125
150
TPC 6. Input Offset Voltage vs. Temperature
–6–
REV. C
OP196/OP296/OP496
25
1000
VS = 5V
VCM = 2.5V
VS = ⴞ1.5V
OUTPUT VOLTAGE – mV
INPUT BAIS CURRENT – nA
20
15
10
–50
–25
0
25
50
75
TEMPERATURE – ⴗC
100
125
SINK
10
1
0.001
150
TPC 7. Input Bias Current vs. Temperature
0.01
10
0.1
1
LOAD CURRENT – mA
TPC 10. Output Voltage to Supply Rail vs. Load Current
1000
16
VS = ⴞ2.5V
OUTPUT VOLTAGE – mV
INPUT BIAS CURRENT – nA
SOURCE
5
0
–75
12
8
4
2
3
12
5
SUPPLY VOLTAGE – V
SOURCE
SINK
10
0.01
10
0.1
1
LOAD CURRENT – mA
TPC 11. Output Voltage to Supply Rail vs. Load Current
40
30
100
1
0.001
14
TPC 8. Input Bias Current vs. Supply Voltage
1000
VS = ⴞ2.5V
TA = 25ⴗC
VS = ⴞ6V
20
OUTPUT VOLTAGE – mV
INPUT BIAS CURRENT – nA
100
10
0
–10
–20
100
SOURCE
SINK
10
–30
–40
–2.5 –2.0 –1.5 –1.0 –0.5
0
0.5
1.0 1.5
COMMON-MODE VOLTAGE – V
2.0
1
0.001
2.5
TPC 9. Input Bias Current vs. Common-Mode Voltage
REV. C
0.01
0.1
1
LOAD CURRENT – mA
10
TPC 12. Output Voltage to Supply Rail vs. Load Current
–7–
OP196/OP296/OP496
4.95
90
I L = 100␮A
VS = ⴞ2.5V
TA = –40ⴗC
80
70
4.45
I L = 2mA
4.2
VS = 5V
60
GAIN
50
–50
–25
0
25
50
75
TEMPERATURE – ⴗC
100
125
135
0
180
1k
10k
FREQUENCY – Hz
100
225
1M
100k
90
VS = ⴞ2.5V
TA = 125ⴗC
80
0.60
70
0.50
0.30
0.10
60
GAIN
50
40
0
30
45
90
20
PHASE
135
10
–50
–25
0
25
50
75
TEMPERATURE – ⴗC
180
0
I L = –100␮A
100
125
–10
10
150
TPC 14. Output Voltage Swing vs. Temperature
1k
10k
FREQUENCY – Hz
100
PHASE SHIFT – ⴗC
I L = –1mA
OPEN-LOOP GAIN – dB
VOL OUTPUT VOLTAGE – V
10
TPC 16. Open-Loop Gain and Phase vs. Frequency
(No Load)
VS = 5V
225
1M
100k
TPC 17. Open-Loop Gain and Phase vs. Frequency
(No Load)
90
950
VS = ⴞ2.5V
TA = 25ⴗC
80
VS = 5V
0.3V < VO < 4.7V
RL = 100k⍀
800
70
OPEN-LOOP GAIN – V/mV
60
GAIN
50
40
0
30
45
20
90
PHASE
10
135
0
180
100
1k
10k
FREQUENCY – Hz
100k
PHASE SHIFT – ⴗC
OPEN-LOOP GAIN – dB
90
PHASE
0.80
–10
10
45
–10
10
150
TPC 13. Output Voltage Swing vs. Temperature
–75
0
30
20
3.85
3.7
–75
40
PHASE SHIFT – ⴗC
I L = 1mA
OPEN-LOOP GAIN – dB
VOH OUTPUT VOLTAGE – V
4.70
225
1M
650
500
350
200
–75
–50
–25
0
25
50
75
TEMPERATURE – ⴗC
100
125
150
TPC 18. Open-Loop Gain vs. Temperature
TPC 15. Open-Loop Gain and Phase vs. Frequency
(No Load)
–8–
REV. C
OP196/OP296/OP496
160
600
VS = ⴞ2.5V
TA = 25ⴗC
ALL CHANNELS
140
VS = 5V
OPEN-LOOP GAIN – V/mV
500
120
TA = 25ⴗC
100
80
CMRR – dB
400
300
60
40
200
20
0
100
–20
0
150
100
50
10
LOAD – k⍀
2
–40
100
1
TPC 19. Open-Loop Gain vs. Resistive Load
10k
100k
FREQUENCY – Hz
10M
160
VS = ⴞ2.5V
RL = 10k⍀
TA = 25ⴗC
60
50
VS = 5V
TA = 25ⴗC
140
120
40
PSRR – dB
100
30
20
10
80
+PSRR
60
40
–PSRR
0
20
–10
0
–20
–20
–30
10
100
1k
10k
FREQUENCY – Hz
100k
–40
10
1M
100
1k
10k
100k
FREQUENCY – Hz
10M
6
1000
VS = ⴞ2.5V
VIN = 5V p-p
AV = 1
RL = 100k⍀
900
5
VS = ⴞ2.5V
TA = 25ⴗC
MAXIMUM OUTPUT SWING – V
800
1M
TPC 23. PSRR vs. Frequency
TPC 20. Closed-Loop Gain vs. Frequency
OUTPUT IMPEDANCE – ⍀
1M
TPC 22. CMRR vs. Frequency
70
CLOSED-LOOP GAIN – dB
1k
700
600
ACL = 10
500
400
ACL = 1
300
200
4
3
2
1
100
0
100
1k
10k
FREQUENCY – Hz
100k
0
1k
1M
TPC 21. Output Impedance vs. Frequency
REV. C
10k
100k
FREQUENCY – Hz
1M
TPC 24. Maximum Output Swing vs. Frequency
–9–
OP196/OP296/OP496
90
0.6
CURRENT NOISE DENSITY – pA/ Hz
ISY/AMPLIFIER – ␮A
80
70
VS = 12V
60
50
VS = 5V
40
VS = 3V
30
20
–75 –50
–40 –25
0
25 50
75
85
TEMPERATURE – ⴗC
VS = ⴞ2.5V
TA = 25ⴗC
VCM = 0V
0.5
0.4
0.3
0.2
0.1
0
1
100 125 150
TPC 25. Supply Current/Amplifier vs. Temperature
10
1k
100
FREQUENCY – Hz
TPC 28. Input Bias Current Noise Density vs. Frequency
10
55
TA = 25ⴗC
8
VS = ⴞ6V
6
TA = 25ⴗC
TO 0.1%
50
ⴙOUTPUT SWING
INPUT STEP – V
ISY/AMPLIFIER – ␮A
4
45
2
0
–2
–4
– OUTPUT SWING
40
–6
–8
35
1
3
5
7
9
11
SUPPLY VOLTAGE – V
12
–10
0
13
5
10
15
20
SETTLING TIME – ␮s
25
30
TPC 29. Settling Time to 0.1% vs. Step Size
TPC 26. Supply Current/Amplifier vs. Supply Voltage
VOLTAGE NOISE DENSITY – nV/ Hz
80
VS = ⴞ2.5V
TA = 25ⴗC
VCM = 0V
70
2mV
1s
100
90
60
50
40
30
10
0%
20
VS = ⴞ2.5V
AV = 10k
en = 0.8␮V p-p
10
0
1
10
100
FREQUENCY – Hz
1k
TPC 30. 0.1 Hz to 10 Hz Noise
TPC 27. Voltage Noise Density vs. Frequency
–10–
REV. C
OP196/OP296/OP496
100mV
100
90
VS = 2.5V
AV = 1
RL = 10k⍀
CL = 100pF
TA = 25ⴗC
10
0V
0%
20mV
10
0%
2␮s
TPC 33. Large Signal Transient Response
VS = ⴞ2.5V
RL = 100k⍀
100
90
100
90
VS = ⴞ2.5V
AV = 1
RL = 100k⍀
CL = 100pF
TA = 25ⴗC
10
0V
10␮s
1V
TPC 31. Small Signal Transient Response
100mV
VS = ⴞ2.5V
RL = 10k⍀
100
90
0%
20mV
10
0%
10␮s
1V
2␮s
TPC 32. Small Signal Transient Response
TPC 34. Large Signal Transient Response
CH A: 40.0␮V FS
MKR: 36.8␮V/ Hz
5.00␮V/DIV
10Hz
0Hz
MKR: 1.00Hz
BW: 145mHz
TPC 35. 1/f Noise Corner, VS = ± 5 V, AV = 1,000
VCC
R1
R2
I1
R7
R6
R8
I4
D3
Q17
D8
QC1
Q4
1x
Q2
CF2
Q14
Q8
D5
Q10
Q9
2x
OUT
CF1
Q13
2x
Q21
CC2
1x
1x
1x
Q7
Q1
D4
2x
Q3
+IN
Q12
Q6
Q5
2x
Q22
D9
QL1
Q11
I5
Q18
D6
2x
QC2
Q19
1x
Q23
R5
–IN
R3A
R3B
CC1
R4A
R9
I3
I2
Q16
Q15
R4B
D7
1.5x
D10
1x
VEE
1*
5*
*OP196 ONLY
TPC 36. Simplified Schematic
REV. C
Q20
–11–
OP196/OP296/OP496
The OP196 family of operational amplifiers is comprised of singlesupply, micropower, rail-to-rail input and output amplifiers. Input
offset voltage (VOS) is only 300 µV maximum, while the output
will deliver ±5 mA to a load. Supply current is only 50 µA, while
bandwidth is over 450 kHz and slew rate is 0.3 V/µs. TPC 36 is
a simplified schematic of the OP196—it displays the novel circuit design techniques used to achieve this performance.
the supply rails. In the circuit of Figure 2, the source amplitude is ± 15 V, while the supply voltage is only ± 5 V. In this
case, a 2 kΩ source resistor limits the input current to 5 mA.
5V
VOLTAGE – 5V/DIV
APPLICATIONS INFORMATION
Functional Description
Input Overvoltage Protection
The OPx96 family of op amps uses a composite PNP/NPN
input stage. Transistor Q1 in Figure 36 has a collector-base
voltage of 0 V if +IN = VEE. If +IN then exceeds VEE, the junction will be forward biased and large diode currents will flow,
which may damage the device. The same situation applies to
+IN on the base of transistor Q5 being driven above VCC. Therefore, the inverting and noninverting inputs must not be driven
above or below either supply rail unless the input current is
limited.
Figure 1 shows the input characteristics for the OPx96 family.
This photograph was generated with the power supply pins
connected to ground and a curve tracer’s collector output drive
connected to the input. As shown in the figure, when the input
voltage exceeds either supply by more than 0.6 V, internal
pn-junctions energize and permit current flow from the inputs
to the supplies. If the current is not limited, the amplifier may
be damaged. To prevent damage, the input current should be
limited to no more than 5 mA.
VS = 5V
AV = 1
100
90
VIN
0
VOUT
0
10
0%
5V
1ms
TIME – 1ns/DIV
Figure 2. Output Voltage Phase Reversal Behavior
Input Offset Voltage Nulling
The OP196 provides two offset adjust terminals that can be
used to null the amplifier’s internal VOS. In general, operational
amplifier terminals should never be used to adjust system offset
voltages. A 100 kΩ potentiometer, connected as shown in Figure 3, is recommended to null the OP196’s offset voltage. Offset
nulling does not adversely affect TCVOS performance, providing
that the trimming potentiometer temperature coefficient does
not exceed ± 100 ppm/°C.
V+
OP196
INPUT CURRENT – mA
6
4
7
2
8
6
4
100
90
3
5
1
2
100k⍀
0
V–
–2
–4
10
Figure 3. Offset Nulling Circuit
0%
–6
Driving Capacitive Loads
–8
–1.5 –1 –0.5 0 0.5 1 1.5
INPUT VOLTAGE – V
Figure 1. Input Overvoltage I-V Characteristics of the
OPx96 Family
OP196 family amplifiers are unconditionally stable with capacitive loads less than 170 pF. When driving large capacitive loads
in unity-gain configurations, an in-the-loop compensation
technique is recommended, as illustrated in Figure 4.
RG
Output Phase Reversal
RF
VIN
Some other operational amplifiers designed for single-supply
operation exhibit an output voltage phase reversal when their
inputs are driven beyond their useful common-mode range.
Typically for single-supply bipolar op amps, the negative supply
determines the lower limit of their common-mode range. With
these common-mode limited devices, external clamping diodes
are required to prevent input signal excursions from exceeding
the device’s negative supply rail (i.e., GND) and triggering
output phase reversal.
CF
RX
OP296
VOUT
CL
RX =
RO RG
RF
WHERE RO = OPEN-LOOP OUTPUT RESISTANCE
CF =
The OPx96 family of op amps is free from output phase reversal
effects due to its novel input structure. Figure 2 illustrates the
performance of the OPx96 op amps when the input is driven
beyond the supply rails. As previously mentioned, amplifier
input current must be limited if the inputs are driven beyond
I+
( |AICL| ) ( RFR+ RG ) CL RO
F
Figure 4. In-the-Loop Compensation Technique for
Driving Capacitive Loads
–12–
REV. C
OP196/OP296/OP496
same potential and no current flows in R1. Since there is no
current flow in R1, the same condition must exist in R2; thus,
the output of the circuit tracks the input signal. When the input
signal is below 0 V, the output voltage of A1 is forced to 0 V.
This condition now forces A2 to operate as an inverting voltage
follower because the noninverting terminal of A2 is also at 0 V.
The output voltage of VOUTA is then a full-wave rectified
version of the input signal. A resistor in series with A1’s
noninverting input protects the ESD diodes when the input
signal goes below ground.
A Micropower False-Ground Generator
Some single supply circuits work best when inputs are biased
above ground, typically at 1/2 of the supply voltage. In these
cases, a false-ground can be created by using a voltage divider
buffered by an amplifier. One such circuit is shown in Figure 5.
This circuit will generate a false-ground reference at 1/2 of the
supply voltage, while drawing only about 55 µA from a 5 V
supply. The circuit includes compensation to allow for a 1 µF
bypass capacitor at the false-ground output. The benefit of a
large capacitor is that not only does the false-ground present a
very low dc resistance to the load, but its ac impedance is low as well.
Square Wave Oscillator
The oscillator circuit in Figure 7 demonstrates how a rail-to-rail
output swing can reduce the effects of power supply variations
on the oscillator’s frequency. This feature is especially valuable
in battery powered applications, where voltage regulation may
not be available. The output frequency remains stable as the
supply voltage changes because the RC charging current, which
is derived from the rail-to-rail output, is proportional to the
supply voltage. Since the Schmitt trigger threshold level is also
proportional to supply voltage, the frequency remains relatively
independent of supply voltage. For a supply voltage change
from 9 V to 5 V, the output frequency only changes about 4 Hz.
The slew rate of the amplifier limits the oscillation frequency to
a maximum of about 200 Hz at a supply voltage of 5 V.
5V OR 12V
10k⍀
0.022␮F
240k⍀
2
7
100⍀
OP196
1␮F
4
3
240k⍀
2.5V OR 6V
6
1␮F
Figure 5. A Micropower False-Ground Generator
Single-Supply Half-Wave and Full-Wave Rectifiers
An OP296, configured as a voltage follower operating from a
single supply, can be used as a simple half-wave rectifier in low
frequency (<400 Hz) applications. A full-wave rectifier can be
configured with a pair of OP296s as illustrated in Figure 6.
V+
100k⍀
R2
100k⍀
R1
100k⍀
59k⍀
2Vp-p
6
2k⍀
A1
1
4
2
1V
INPUT
A2
8
3
5
1/2
OP296
500mV
7
1/2
OP296
VOUTA
FULL-WAVE
RECTIFIED
OUTPUT
1/2
OP296/
OP496
FREQ OUT
fOSC =
1
< 200Hz @ V+ = 5V
RC
Figure 7. Square Wave Oscillator Has Stable Frequency
Regardless of Supply Voltage Changes
VOUTB
HALF-WAVE
RECTIFIED
OUTPUT
A 3 V Low Dropout, Linear Voltage Regulator
Figure 8 shows a simple 3 V voltage regulator design. The regulator can deliver 50 mA load current while allowing a 0.2 V
dropout voltage. The OP296’s rail-to-rail output swing easily
drives the MJE350 pass transistor without requiring special
drive circuitry. With no load, its output can swing to less than
the pass transistor’s base-emitter voltage, turning the device
nearly off. At full load, and at low emitter-collector voltages, the
transistor beta tends to decrease. The additional base current is
easily handled by the OP296 output.
500µs
100
90
f = 500Hz
10
0%
500mV
Figure 6. Single-Supply Half-Wave and Full-Wave
Rectifiers Using an OP296
The circuit works as follows: When the input signal is above
0 V, the output of amplifier A1 follows the input signal. Since
the noninverting input of amplifier A2 is connected to A1’s
output, op amp loop control forces A2’s inverting input to the
same potential. The result is that both terminals of R1 are at the
REV. C
4
C
VOUTB
(FULL-WAVE
OUTPUT)
2
R
(HALF-WAVE
OUTPUT)
VOUTA
8
1
5V
<500Hz
3
100k⍀
The AD589 provides a 1.235 V reference voltage for the regulator. The OP296, operating with a noninverting gain of 2.43,
drives the base of the MJE350 to produce an output voltage of
3.0 V. Since the MJE350 operates in an inverting (commonemitter) mode, the output feedback is applied to the OP296’s
noninverting input.
–13–
OP196/OP296/OP496
IL < 50mA
MJE 350
VO
VIN
5V TO 3.2V
44.2k⍀
1%
8
1
100␮F
3
1/2
OP296
30.9k⍀
1%
2
4
1000pF
43k⍀
1.235V
AD589
Figure 8. 3 V Low Dropout Voltage Regulator
Figure 9 shows the regulator’s recovery characteristics when its
output underwent a 20 mA to 50 mA step current change.
2V
STEP 50mA
CURRENT
CONTROL
WAVEFORM 30mA
OUTPUT
100
90
The next two DACs, B and C, sum their outputs into the other
OP296 amplifier. In this circuit DAC C provides the coarse
output voltage setting and DAC B is used for fine adjustment.
The insertion of R1 in series with DAC B attenuates its contribution to the voltage sum node at the DAC C output.
A High-Side Current Monitor
In the design of power supply control circuits, a great deal of
design effort is focused on ensuring a pass transistor’s long-term
reliability over a wide range of load current conditions. As a result,
monitoring and limiting device power dissipation is of prime
importance in these designs. The circuit illustrated in Figure 11
is an example of a 5 V, single-supply high-side current monitor
that can be incorporated into the design of a voltage regulator
with fold-back current limiting or a high current power supply
with crowbar protection. This design uses an OP296’s rail-torail input voltage range to sense the voltage drop across a 0.1 Ω
current shunt. A p-channel MOSFET is used as the feedback
element in the circuit to convert the op amp’s differential input
voltage into a current. This current is then applied to R2 to generate a voltage that is a linear representation of the load current.
The transfer equation for the current monitor is given by:
R

Monitor Output = R2 ×  SENSE  × I L
 R1 
10
0%
10mV
50µs
For the element values shown, the Monitor Output’s transfer
characteristic is 2.5 V/A.
Figure 9. Output Step Load Current Recovery
RSENSE
0.1⍀
Buffering a DAC Output
IL
5V
Multichannel TrimDACs® such as the AD8801/AD8803, are
widely used for digital nulling and similar applications. These
DACs have rail-to-rail output swings, with a nominal output
resistance of 5 kΩ. If a lower output impedance is required, an
OP296 amplifier can be added. Two examples are shown in
Figure 10. One amplifier of an OP296 is used as a simple buffer
to reduce the output resistance of DAC A. The OP296 provides
rail-to-rail output drive while operating down to a 3 V supply
and requiring only 50 µA of supply current.
5V
5V
R1
100⍀
3
8
1/2
OP296
2
1
4
S
G
M1
3N163
MONITOR
OUTPUT
D
R2
2.49k⍀
5V
Figure 11. A High-Side Load Current Monitor
VREFH VDD
SIMPLE BUFFER
0V TO 5V
+4.983V
+1.1mV
VH
VL
R1
100k⍀
VH
VL
AD8801/
AD8803
VREFL
A Single-Supply RTD Amplifier
OP296
VH
VL
SUMMER CIRCUIT
WITH FINE TRIM
ADJUSTMENT
GND
DIGITAL INTERFACING
OMITTED FOR CLARITY
Figure 10. Buffering a TrimDAC OutputTPC
The circuit in Figure 12 uses three op amps on the OP496 to
produce a bridge driver for an RTD amplifier while operating
from a single 5 V supply. The circuit takes advantage of the
OP496’s wide output swing to generate a bridge excitation
voltage of 3.9 V. An AD589 provides a 1.235 V reference for
the bridge current. Op amp A1 drives the bridge to maintain
1.235 V across the parallel combination of the 6.19 kΩ and
2.55 MΩ resistors, which generates a 200 µA current source.
This current divides evenly and flows through both halves of
the bridge. Thus, 100 µA flows through the RTD to generate
an output voltage which is proportional to its resistance. For
improved accuracy, a 3-wire RTD is recommended to balance
the line resistance in both 100 Ω legs of the bridge.
TrimDAC is a registered trademark of Analog Devices Inc.
–14–
REV. C
OP196/OP296/OP496
GAIN = 259
200⍀
10-TURNS
5V
26.7k⍀
26.7k⍀
100⍀
RTD
100⍀
2.55M⍀
A1
AD589
37.4k⍀
A3
392⍀ 392⍀
100k⍀
VOUT
A2
1/4
OP496
6.17k⍀
1/4
OP496
1/4
OP496
Amplifiers A2 and A3 are configured in a two op amp instrumentation amplifier configuration. For ease of measurement,
the IA resistors are chosen to produce a gain of 259, so that
each 1°C increase in temperature results in a 10 mV increase in
the output voltage. To reduce measurement noise, the bandwidth of the amplifier is limited. A 0.1 µF capacitor, connected
in parallel with the 100 kΩ resistor on amplifier A3, creates a
pole at 16 Hz.
20k⍀
100k⍀
0.1␮F
NOTE:
ALL RESISTORS 1% OR BETTER
5V
Figure 12. A Single-Supply RTD Amplifier
* OP496 SPICE Macro-model
REV. C, 5/95
*
ARG / ADSC
*
* Copyright 1995 by Analog Devices, Inc.
*
* Refer to “README.DOC” file for License Statement.
* Use of this model indicates your acceptance of the
* terms and provisions in the License Statement.
*
* Node assignments
*
Noninverting input
*
Inverting input
*
Positive supply
*
Negative supply
*
Output
*
*
.SUBCKT OP496
1
2
99
50
49
*
* INPUT STAGE
*
IREF 21
50
1U
QB1 21
21
99
99
QP
1
QB2 22
21
99
99
QP
1
QB3 4
21
99
99
QP
1.5
QB4 22
22
50
50
QN
2
QB5 11
22
50
50
QN
3
Q1
5
4
7
50
QN
2
Q2
6
4
8
50
QN
2
Q3
4
4
7
50
QN
1
Q4
4
4
8
50
QN
1
Q5
50
1
7
99
QP
2
Q6
50
3
8
99
QP
2
EOS 3
2
POLY(1)
(17,98) 35U 1
Q7
99
1
9
50
QN
2
Q8
99
3
10
50
QN
2
Q9
12
11
9
99
QP
2
Q10 13
11
10
99
QP
2
Q11 11
11
9
99
QP
1
Q12 11
11
10
99
QP
1
R1
99
5
50K
R2
99
6
50K
R3
12
50
50K
R4
13
50
50K
IOS 1
2
0.75N
C10 5
6
3.183P
C11 12
13
3.183P
REV. C
CIN 1
2
1P
*
* GAIN STAGE
*
EREF 98 0
POLY(2)
(99,0) (50,0) 0
G1
98 15 POLY(2)
(6,5)
(13,12) 0
R10 15 98 251.641MEG
CC
15 49 8P
D1
15 99 DX
D2
50 15 DX
*
* COMMON-MODE STAGE
*
ECM 16 98 POLY(2)
(1,98) (2,98) 0
R11 16 17 1MEG
R12 17 98 10
*
* OUTPUT STAGE
*
ISY
99 50 20U
EIN 35 50 POLY(1)
(15,98) 1.42735
Q24 37 35 36
50 QN
1
QD4 37 37 38
99 QP
1
Q27 40 37 38
99 QP
1
R5
36 39 150K
R6
99 38 45K
Q26 39 42 50
50 QN
3
QD5 40 40 39
50 QN
1
Q28 41 40 44
50 QN
1
QL1 37 41 99
99 QP
1
R7
99 41 10.7K
I4
99 43 2U
QD7 42 42 50
50 QN
2
QD6 43 43 42
50 QN
2
Q29 47 43 44
50 QN
1
Q30 44 45 50
50 QN
1.5
QD10 45 46 50
50 QN
1
R9
45 46 175
Q31 46 47 48
99 QP
1
QD8 47 47 48
99 QP
1
QD9 48 48 51
99 QP
5
R8
99 51 2.9K
I5
99 46 1U
Q32 49 48 99
99 QP
10
Q33 49 44 50
50 QN
4
.MODEL
DX D()
.MODEL
QN NPN(BF=120VAF=100)
.MODEL
QP PNP(BF=80 VAF=60)
.ENDS
–15–
0.5 0.5
10U 10U
0.5 0.5
1
OP196/OP296/OP496
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
14-Lead Plastic DIP
(N-14)
0.430 (10.92)
0.348 (8.84)
8
5
1
4
0.795 (20.19)
0.725 (18.42)
0.280 (7.11)
0.240 (6.10)
0.060 (1.52)
0.015 (0.38)
PIN 1
0.210 (5.33)
MAX
14
8
1
7
0.325 (8.25)
0.300 (7.62)
0.130
(3.30)
MIN
SEATING
0.022 (0.558)
0.070 (1.77)
PLANE
0.100
0.014 (0.356) (2.54) 0.045 (1.15)
BSC
0.160 (4.06)
0.115 (2.93)
0.210 (5.33)
MAX
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
0.015 (0.381)
0.008 (0.204)
5
1
4
PIN 1
0.3444 (8.75)
0.3367 (8.55)
0.0500 0.0192 (0.49)
(1.27) 0.0138 (0.35)
BSC
8°
0°
8
1
7
0.0098 (0.25)
0.0040 (0.10)
0.0500
(1.27)
BSC
SEATING
PLANE
0.0500 (1.27)
0.0160 (0.41)
14
SEATING
PLANE
8°
0°
0.0500 (1.27)
0.0160 (0.41)
8
0.256 (6.50)
0.246 (6.25)
0.177 (4.50)
0.169 (4.30)
0.256 (6.50)
0.246 (6.25)
0.177 (4.50)
0.169 (4.30)
5
1
4
PIN 1
0.006 (0.15)
0.002 (0.05)
0.0099 (0.25)
0.0075 (0.19)
0.201 (5.10)
0.193 (4.90)
0.122 (3.10)
0.114 (2.90)
1
0.0192 (0.49)
0.0138 (0.35)
0.0196 (0.50)
x 45°
0.0099 (0.25)
14-Lead TSSOP
(RU-14)
8-Lead TSSOP
(RU-8)
8
0.2440 (6.20)
0.2284 (5.80)
0.0688 (1.75)
0.0532 (1.35)
PIN 1
0.0196 (0.50)
x 45°
0.0099 (0.25)
0.0098 (0.25)
0.0075 (0.19)
14
7
PIN 1
0.0256 (0.65)
BSC
0.0433
(1.10)
MAX
0.0118 (0.30)
0.0075 (0.19)
0.0079 (0.20)
0.0035 (0.090)
0.006 (0.15)
0.002 (0.05)
8°
0°
0.028 (0.70)
0.020 (0.50)
SEATING
PLANE
0.0433
(1.10)
MAX
0.0256
(0.65)
BSC
0.0118 (0.30)
0.0075 (0.19)
0.0079 (0.20)
0.0035 (0.090)
8°
0°
PRINTED IN U.S.A.
SEATING
PLANE
0.1574 (4.00)
0.1497 (3.80)
0.2440 (6.20)
0.2284 (5.80)
0.0688 (1.75)
0.0532 (1.35)
0.0098 (0.25)
0.0040 (0.10)
0.015 (0.381)
0.008 (0.204)
SEATING
PLANE
14-Lead Narrow-Body SOIC
(SO-14)
0.1968 (5.00)
0.1890 (4.80)
8
0.100 0.070 (1.77)
(2.54) 0.045 (1.15)
BSC
0.022 (0.558)
0.014 (0.356)
8-Lead Narrow Body SOIC
(SO-8)
0.1574 (4.00)
0.1497 (3.80)
0.325 (8.25)
0.300 (7.62) 0.195 (4.95)
0.115 (2.93)
0.060 (1.52)
0.015 (0.38)
PIN 1
0.195 (4.95)
0.115 (2.93)
0.280 (7.11)
0.240 (6.10)
C00312–0–1/02(C)
8-Lead Plastic DIP
(N-8)
0.028 (0.70)
0.020 (0.50)
Revision History
Location
Page
Data Sheet changed from REV. B to REV. C.
Edits to TYPICAL PERFORMANCE CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
–16–
REV. C