Microchip MCP6292 1.0 ma, 10 mhz rail-to-rail op amp Datasheet

MCP6291/1R/2/3/4/5
1.0 mA, 10 MHz Rail-to-Rail Op Amp
Features
Description
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The Microchip Technology Inc. MCP6291/1R/2/3/4/5
family of operational amplifiers (op amps) provide wide
bandwidth for the current. This family has a 10 MHz
Gain Bandwidth Product (GBWP) and a 65° phase
margin. This family also operates from a single supply
voltage as low as 2.4V, while drawing 1 mA (typical)
quiescent current. In addition, the MCP6291/1R/2/3/4/5
supports rail-to-rail input and output swing, with a
common mode input voltage range of VDD + 300 mV to
VSS – 300 mV. This family of operational amplifiers is
designed with Microchip’s advanced CMOS process.
Gain Bandwidth Product: 10 MHz (typical)
Supply Current: IQ = 1.0 mA
Supply Voltage: 2.4V to 6.0V
Rail-to-Rail Input/Output
Extended Temperature Range: -40°C to +125°C
Available in Single, Dual and Quad Packages
Single with CS (MCP6293)
Dual with CS (MCP6295)
Applications
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The MCP6295 has a Chip Select (CS) input for dual op
amps in an 8-pin package. This device is manufactured
by cascading the two op amps, with the output of
op amp A being connected to the non-inverting input of
op amp B. The CS input puts the device in a Low-power
mode.
Automotive
Portable Equipment
Photodiode Amplifier
Analog Filters
Notebooks and PDAs
Battery-Powered Systems
The MCP6291/1R/2/3/4/5 family operates over the
Extended Temperature Range of -40°C to +125°C. It
also has a power supply range of 2.4V to 6.0V.
Design Aids
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SPICE Macro Models
FilterLab® Software
Mindi™ Simulation Tool
MAPS (Microchip Advanced Part Selector)
Analog Demonstration and Evaluation Boards
Application Notes
Package Types
NC 1
VIN
_
8 NC
2
VSS 4
7 VDD
VIN+ 3
7 VDD
6 VOUT
5 NC
4 VIN–
VIN+ 3
6 VDD
-
5 CS
4 VIN–
VOUTA 1
14 VOUTD
- + + - 13 VIND_
VINA+ 3
12 VIND+
VDD 4
VOUTB 7
VOUTA 1
_
VINA 2
4 VIN–
VINA_ 2
VINB+ 5
VINB_ 6
© 2007 Microchip Technology Inc.
-
MCP6294
PDIP, SOIC, TSSOP
SOT-23-6
VOUT 1
VSS 2
VIN+ 3
MCP6292
PDIP, SOIC, MSOP
5 VSS
VOUT 1
VDD 2
-
MCP6293
+
VSS 4
8 CS
+
5 VDD
VSS 2
6 VOUT
MCP6293
PDIP, SOIC, MSOP
VIN_ 2
VIN+ 3
SOT-23-5
VOUT 1
5 NC
NC 1
MCP6291R
SOT-23-5
+
+
VIN+ 3
MCP6291
+
MCP6291
PDIP, SOIC, MSOP
11 VSS
10 VINC+
-+ +- 9 V _
INC
VINA+ 3
8 VDD
7 VOUTB
- +
+ -
VSS 4
6 VINB_
5 VINB+
MCP6295
PDIP, SOIC, MSOP
VOUTA/VINB+ 1
VINA_ 2
VINA+ 3
VSS 4
8 VDD
7 VOUTB
- +
+ -
_
6 VINB
5 CS
8 VOUTC
DS21812E-page 1
MCP6291/1R/2/3/4/5
1.0
ELECTRICAL
CHARACTERISTICS
Absolute Maximum Ratings †
VDD – VSS ........................................................................7.0V
Current at Input Pins .....................................................±2 mA
† Notice: Stresses above those listed under “Absolute
Maximum Ratings” may cause permanent damage to the
device. This is a stress rating only and functional operation of
the device at those or any other conditions above those
indicated in the operational listings of this specification is not
implied. Exposure to maximum rating conditions for extended
periods may affect device reliability.
†† See Section 4.1.2 “Input Voltage and Current Limits”.
Analog Inputs (VIN+, VIN–) †† ........ VSS – 1.0V to VDD + 1.0V
All Other Inputs and Outputs ......... VSS – 0.3V to VDD + 0.3V
Difference Input Voltage ...................................... |VDD – VSS|
Output Short Circuit Current .................................Continuous
Current at Output and Supply Pins ............................±30 mA
Storage Temperature....................................–65°C to +150°C
Maximum Junction Temperature (TJ) ......................... .+150°C
ESD Protection On All Pins (HBM; MM) .............. ≥ 4 kV; 400V
DC ELECTRICAL SPECIFICATIONS
Electrical Characteristics: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VOUT ≈ VDD/2,
VCM = VDD/2, VL = VDD/2, RL = 10 kΩ to VL and CS is tied low (refer to Figure 1-2 and Figure 1-3).
Parameters
Sym
Min
Typ
Max
Units
Conditions
Input Offset Voltage
VOS
-3.0
—
+3.0
mV
VCM = VSS (Note 1)
Input Offset Voltage
(Extended Temperature)
VOS
-5.0
—
+5.0
mV
TA = -40°C to +125°C,
VCM = VSS (Note 1)
Input Offset Temperature Drift
ΔVOS/ΔTA
—
±1.7
—
µV/°C
TA = -40°C to +125°C,
VCM = VSS (Note 1)
Power Supply Rejection Ratio
PSRR
70
90
—
dB
VCM = VSS (Note 1)
IB
—
±1.0
—
pA
Note 2
At Temperature
IB
—
50
200
pA
TA = +85°C (Note 2)
At Temperature
IB
—
2
5
nA
TA = +125°C (Note 2)
Input Offset Current
IOS
—
±1.0
—
pA
Note 3
Common Mode Input Impedance
ZCM
—
1013||6
—
Ω||pF
Note 3
Differential Input Impedance
ZDIFF
—
1013||3
—
Ω||pF
Note 3
Common Mode Input Range
VCMR
VSS − 0.3
—
VDD + 0.3
V
Common Mode Rejection Ratio
CMRR
70
85
—
dB
VCM = -0.3V to 2.5V, VDD = 5V
Common Mode Rejection Ratio
CMRR
65
80
—
dB
VCM = -0.3V to 5.3V, VDD = 5V
AOL
90
110
—
dB
VOUT = 0.2V to VDD – 0.2V,
VCM = VSS (Note 1)
VOL, VOH
VSS + 15
—
VDD – 15
mV
0.5V Input Overdrive
ISC
—
±25
—
mA
VDD
2.4
—
6.0
V
IQ
0.7
1.0
1.3
mA
Input Offset
Input Bias, Input Offset Current and Impedance
Input Bias Current
Common Mode (Note 4)
Open-Loop Gain
DC Open-Loop Gain (Large Signal)
Output
Maximum Output Voltage Swing
Output Short Circuit Current
Power Supply
Supply Voltage
Quiescent Current per Amplifier
Note 1:
2:
3:
4:
5:
TA = -40°C to +125°C (Note 5)
IO = 0
The MCP6295’s VCM for op amp B (pins VOUTA/VINB+ and VINB–) is VSS + 100 mV.
The current at the MCP6295’s VINB– pin is specified by IB only.
This specification does not apply to the MCP6295’s VOUTA/VINB+ pin.
The MCP6295’s VINB– pin (op amp B) has a common mode range (VCMR) of VSS + 100 mV to VDD – 100 mV.
The MCP6295’s VOUTA/VINB+ pin (op amp B) has a voltage range specified by VOH and VOL.
All parts with date codes November 2007 and later have been screened to ensure operation at VDD = 6.0V. However,
the other minimum and maximum specifications are measured at 2.4V and or 5.5V.
DS21812E-page 2
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
AC ELECTRICAL SPECIFICATIONS
Electrical Characteristics: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2,
VOUT ≈ VDD/2, VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low (refer to Figure 1-2 and Figure 1-3).
Parameters
Sym
Min
Typ
Max
Units
Conditions
AC Response
Gain Bandwidth Product
GBWP
—
10.0
—
MHz
Phase Margin at Unity-Gain
PM
—
65
—
°
Slew Rate
SR
—
7
—
V/µs
G = +1 V/V
Noise
Input Noise Voltage
Eni
—
4.2
—
µVP-P
Input Noise Voltage Density
eni
—
8.7
—
nV/√Hz
f = 0.1 Hz to 10 Hz
f = 10 kHz
Input Noise Current Density
ini
—
3
—
fA/√Hz
f = 1 kHz
MCP6293/MCP6295 CHIP SELECT (CS) SPECIFICATIONS
Electrical Characteristics: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2,
VOUT ≈ VDD/2, VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low (refer to Figure 1-2 and Figure 1-3).
Parameters
Sym
Min
Typ
Max
Units
Conditions
CS Logic Threshold, Low
VIL
VSS
—
0.2 VDD
V
CS Input Current, Low
ICSL
—
0.01
—
µA
CS Logic Threshold, High
VIH
0.8 VDD
—
VDD
V
CS Input Current, High
ICSH
—
0.7
2
µA
CS = VDD
GND Current per Amplifier
ISS
—
-0.7
—
µA
CS = VDD
Amplifier Output Leakage
—
—
0.01
—
µA
CS = VDD
CS Low to Valid Amplifier Output,
Turn-on Time
tON
—
4
10
µs
CS Low ≤ 0.2 VDD, G = +1 V/V,
VIN = VDD/2, VOUT = 0.9 VDD/2,
VDD = 5.0V
CS High to Amplifier Output High-Z
tOFF
—
0.01
—
µs
CS High ≥ 0.8 VDD, G = +1 V/V,
VIN = VDD/2, VOUT = 0.1 VDD/2
VHYST
—
0.6
—
V
VDD = 5V
CS Low Specifications
CS = VSS
CS High Specifications
Dynamic Specifications (Note 1)
Hysteresis
Note 1:
The input condition (VIN) specified applies to both op amp A and B of the MCP6295. The dynamic specification is tested
at the output of op amp B (VOUTB).
© 2007 Microchip Technology Inc.
DS21812E-page 3
MCP6291/1R/2/3/4/5
TEMPERATURE SPECIFICATIONS
Electrical Characteristics: Unless otherwise indicated, VDD = +2.4V to +5.5V and VSS = GND.
Parameters
Sym
Min
Typ
Max
Units
Operating Temperature Range
TA
-40
—
+125
°C
Storage Temperature Range
TA
-65
—
+150
°C
Conditions
Temperature Ranges
Note
Thermal Package Resistances
Thermal Resistance, 5L-SOT-23
θJA
—
256
—
°C/W
Thermal Resistance, 6L-SOT-23
θJA
—
230
—
°C/W
Thermal Resistance, 8L-PDIP
θJA
—
85
—
°C/W
Thermal Resistance, 8L-SOIC
θJA
—
163
—
°C/W
Thermal Resistance, 8L-MSOP
θJA
—
206
—
°C/W
Thermal Resistance, 14L-PDIP
θJA
—
70
—
°C/W
Thermal Resistance, 14L-SOIC
θJA
—
120
—
°C/W
Thermal Resistance, 14L-TSSOP
θJA
—
100
—
°C/W
Note:
The Junction Temperature (TJ) must not exceed the Absolute Maximum specification of +150°C.
1.1
CS
VIL
VIH
tOFF
tON
VOUT
ISS
0.7 µA
(typical)
ICS
The test circuits used for the DC and AC tests are
shown in Figure 1-2 and Figure 1-2. The bypass
capacitors are laid out according to the rules discussed
in Section 4.6 “Supply Bypass”.
Hi-Z
Hi-Z
-0.7 µA
(typical)
Test Circuits
-1.0 mA
(typical)
10 nA
(typical)
-0.7 µA
(typical)
0.7 µA
(typical)
FIGURE 1-1:
Timing Diagram for the
Chip Select (CS) pin on the MCP6293 and
MCP6295.
VDD
VIN
RN
0.1 µF 1 µF
VOUT
MCP629X
CL
VDD/2 RG
RL
RF
VL
FIGURE 1-2:
AC and DC Test Circuit for
Most Non-Inverting Gain Conditions.
VDD
VDD/2
RN
0.1 µF 1 µF
VOUT
MCP629X
CL
VIN
RG
RL
RF
VL
FIGURE 1-3:
AC and DC Test Circuit for
Most Inverting Gain Conditions.
DS21812E-page 4
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
2.0
TYPICAL PERFORMANCE CURVES
Note:
The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.
25%
Percentage of Occurrences
20%
840 Samples
VCM = VSS
TA = -40°C to +125°C
15%
10%
5%
Input Offset Voltage (mV)
FIGURE 2-4:
60
70
80
90
100
350
FIGURE 2-5:
TA = +125 °C.
Input Bias Current at
VDD = 2.4V
Input Offset Voltage (µV)
Input Offset Voltage (µV)
400
300
250
200
TA = -40°C
TA = +25°C
TA = +85°C
TA = +125°C
150
100
50
0
-0.5
0.0
0.5
1.0
1.5
2.0
2.5
Common Mode Input Voltage (V)
FIGURE 2-3:
Input Offset Voltage vs.
Common Mode Input Voltage at VDD = 2.4V.
© 2007 Microchip Technology Inc.
10
8
6
4
2
0
-2
Input Bias Current (pA)
Input Bias Current (pA)
FIGURE 2-2:
TA = +85 °C.
3000
50
2800
40
2600
30
2400
20
2200
10
2000
0
0%
1800
0%
1600
5%
5%
1400
10%
10%
1200
15%
15%
1000
20%
20%
800
25%
210 Samples
TA = +125°C
600
30%
25%
0
35%
Percentage of Occurrences
210 Samples
TA = 85°C
Input Offset Voltage Drift.
400
Input Offset Voltage.
30%
40%
Percentage of Occurrences
Input Offset Voltage Drift (µV/°C)
200
FIGURE 2-1:
-4
-6
-8
0%
2.8
2.4
2.0
1.6
1.2
0.8
0.4
0.0
-0.4
-0.8
-1.2
-1.6
-2.0
-2.4
840 Samples
VCM = VSS
-10
12%
11%
10%
9%
8%
7%
6%
5%
4%
3%
2%
1%
0%
-2.8
Percentage of Occurrences
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
3.0
Input Bias Current at
800
VDD = 5.5V
750
700
650
600
550
500
450
400
350
300
250
200
-0.5 0.0 0.5 1.0 1.5 2.0
TA = +125°C
TA = +85°C
TA = +25°C
TA = -40°C
2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
Common Mode Input Voltage (V)
FIGURE 2-6:
Input Offset Voltage vs.
Common Mode Input Voltage at VDD = 5.5V.
DS21812E-page 5
MCP6291/1R/2/3/4/5
TYPICAL PERFORMANCE CURVES (CONTINUED)
700
650
600
550
500
450
400
350
300
250
200
150
100
10,000
VCM = VSS
Representative Part
Input Bias, Offset Currents
(pA)
Input Offset Voltage (µV)
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
VDD = 5.5V
VDD = 2.4V
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
VCM = VDD
VDD = 5.5V
1,000
Input Bias Current
100
Input Offset Current
10
1
5.5
25
35
45
Output Voltage (V)
FIGURE 2-7:
Output Voltage.
Input Offset Voltage vs.
65
75
85
95
105 115 125
FIGURE 2-10:
Input Bias, Input Offset
Currents vs. Ambient Temperature.
120
110
100
110
90
PSRR, CMRR (dB)
CMRR, PSRR (dB)
55
Ambient Temperature (°C)
CMRR
80
PSRR-
70
PSRR+
60
50
40
100
CMRR
90
PSRR
VCM = VSS
80
70
30
20
60
1.E+00
1.E+01
1
10
1.E+02
1.E+03
100
1.E+04
1k
1.E+05
10k
-50
1.E+06
100k
1M
-25
0
Frequency (Hz)
CMRR, PSRR vs.
FIGURE 2-11:
Temperature.
55
2.5
45
2.0
Input Bias, Offset Currents
(nA)
Input Bias, Offset Currents
(pA)
FIGURE 2-8:
Frequency.
Input Bias Current
35
25
15
5
Input Offset Current
-5
TA = +85°C
VDD = 5.5V
-15
-25
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Common Mode Input Voltage (V)
FIGURE 2-9:
Input Bias, Offset Currents
vs. Common Mode Input Voltage at TA = +85°C.
DS21812E-page 6
25
50
75
100
125
Ambient Temperature (°C)
CMRR, PSRR vs. Ambient
TA = +125°C
VDD = 5.5V
1.5
Input Bias Current
1.0
0.5
0.0
Input Offset Current
-0.5
-1.0
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Common Mode Input Voltage (V)
FIGURE 2-12:
Input Bias, Offset Currents
vs. Common Mode Input Voltage at TA = +125°C.
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
TYPICAL PERFORMANCE CURVES (CONTINUED)
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
1000
1.2
1.0
0.8
TA = +125°C
TA = +85°C
TA = +25°C
TA = -40°C
0.6
0.4
0.2
0.0
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
100
10
VOL - VSS
VDD - VOH
1
0.01
0.1
Power Supply Voltage (V)
FIGURE 2-13:
Quiescent Current vs.
Power Supply Voltage.
16
-30
14
80
-60
Phase
60
-90
1k
10k 100k
1M
90
-210
10M 100M
75
8
70
6
65
4
60
PM, VDD = 5.5V
PM, VDD = 2.4V
2
-50
-25
0
25
50
75
100
50
125
Open-Loop Gain, Phase vs.
FIGURE 2-17:
Gain Bandwidth Product,
Phase Margin vs. Ambient Temperature.
12
Slew Rate (V/µs)
10
VDD = 5.5V
VDD = 2.4V
1
Falling Edge, VDD = 5.5V
VDD = 2.4V
8
6
4
2
Rising Edge, VDD = 5.5V
VDD = 2.4V
1M
1.E+07
100k
1.E+06
10k
1.E+05
1k
1.E+04
0
1.E+03
Maximum Output Voltage
Swing (V P-P)
55
Ambient Temperature (°C)
10
0.1
80
10
Frequency (Hz)
FIGURE 2-14:
Frequency.
85
GBWP, VDD = 5.5V
GBWP, VDD = 2.4V
12
0
1.E+08
100
1.E+07
1.E-01
10
1.E+06
-180
1.E+05
0
1.E+04
-150
1.E+03
20
1.E+02
-120
1.E+01
40
Gain Bandwidth Product
(MHz)
0
Gain
1.E+00
Open-Loop Gain (dB)
100
1
10
FIGURE 2-16:
Output Voltage Headroom
vs. Output Current Magnitude.
Open-Loop Phase (°)
120
-20
0.1
1
Output Current Magnitude (mA)
Phase Margin (°)
Quiescent Current
(mA/Amplifier)
1.4
Ouput Voltage Headroom (mV)
1.6
10M
-50
-25
Frequency (Hz)
FIGURE 2-15:
Maximum Output Voltage
Swing vs. Frequency.
© 2007 Microchip Technology Inc.
0
25
50
75
100
125
Ambient Temperature (°C)
FIGURE 2-18:
Temperature.
Slew Rate vs. Ambient
DS21812E-page 7
MCP6291/1R/2/3/4/5
TYPICAL PERFORMANCE CURVES (CONTINUED)
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
11
Input Noise Voltage Density
(nV/ √ Hz)
Input Noise Voltage Density
(nV/ √ Hz)
1,000
100
10
1
0.1
1.E-01
1.E+00
1
1.E+01
1.E+02
10
100
1.E+03
1.E+04
1k
10k
1.E+05
1.E+06
100k
10
9
8
f = 10 kHz
VDD = 5.0V
7
6
5
4
3
2
1
0
1M
0.0
0.5
Frequency (Hz)
FIGURE 2-19:
vs. Frequency.
Input Noise Voltage Density
1.5
2.5
3.0
3.5
4.0
4.5
5.0
140
Channel-to-Channel
Separation (dB)
30
25
20
15
TA = +125°C
TA = +85°C
TA = +25°C
TA = -40°C
10
5
0
130
120
110
100
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
1
10
Power Supply Voltage (V)
1.2
1.4
Op-Amp turns on here
0.8
Hysteresis
0.6
0.4
0.2
1.6
CS swept
high to low
CS swept
low to high
Quiescent Current
(mA/Amplifier)
1.0
FIGURE 2-23:
Channel-to-Channel
Separation vs. Frequency (MCP6292, MCP6294
and MCP6295 only).
VDD = 2.4V
Op-Amp shuts off here
100
Frequency (kHz)
FIGURE 2-20:
Output Short Circuit Current
vs. Power Supply Voltage.
Quiescent Current
(mA/Amplifier)
2.0
FIGURE 2-22:
Input Noise Voltage Density
vs. Common Mode Input Voltage at 10 kHz.
35
Ouptut Short Circuit Current
(mA)
1.0
Common Mode Input Voltage (V)
VDD = 5.5V
Op Amp shuts off
Op Amp turns on
Hysteresis
1.2
1.0
0.8
CS swept
high to low
0.6
CS swept
low to high
0.4
0.2
0.0
0.0
0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4
Chip Select Voltage (V)
FIGURE 2-21:
Quiescent Current vs.
Chip Select (CS) Voltage at VDD = 2.4V
(MCP6293 and MCP6295 only).
DS21812E-page 8
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Chip Select Voltage (V)
FIGURE 2-24:
Quiescent Current vs.
Chip Select (CS) Voltage at VDD = 5.5V
(MCP6293 and MCP6295 only).
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
TYPICAL PERFORMANCE CURVES (CONTINUED)
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
5.0
5.0
G = +1V/V
VDD = 5.0V
4.5
Output Voltage (V)
Output Voltage (V)
4.0
3.5
3.0
2.5
2.0
1.5
1.0
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0.5
0.0
G = -1V/V
VDD = 5.0V
4.5
0.E+00
1.E-06
2.E-06
3.E-06
4.E-06
5.E-06
6.E-06
7.E-06
8.E-06
9.E-06
0.0
1.E-05
0.E+00
1.E-06
2.E-06
3.E-06
4.E-06
FIGURE 2-25:
Pulse Response.
5.E-06
6.E-06
7.E-06
Large-Signal Non-inverting
FIGURE 2-28:
Response.
9.E-06
1.E-05
Large-Signal Inverting Pulse
G = -1V/V
Output Voltage (10 mV/div)
Output Voltage (10 mV/div)
G = +1V/V
Time (200 ns/div)
Time (200 ns/div)
Small-Signal Non-inverting
3.0
2.0
1.5
Output On
VOUT
1.0
0.5
Output High-Z
0.0
0.E+00
5.E-06
1.E-05
2.E-05
2.E-05
3.E-05
3.E-05
4.E-05
4.E-05
5.E-05
5.E-05
Time (5 µs/div)
FIGURE 2-27:
Chip Select (CS) to
Amplifier Output Response Time at VDD = 2.4V
(MCP6293 and MCP6295 only).
© 2007 Microchip Technology Inc.
Small-Signal Inverting Pulse
6.0
VDD = 2.4V
G = +1V/V
VIN = VSS
CS Voltage
2.5
FIGURE 2-29:
Response.
Chip Select, Output Voltages
(V)
FIGURE 2-26:
Pulse Response.
Chip Select, Output Voltages
(V)
8.E-06
Time (1 µs/div)
Time (1 µs/div)
VDD = 5.5V
G = +1V/V
VIN = VSS
5.5
CS Voltage
5.0
4.5
4.0
3.5
VOUT
3.0
Output On
2.5
2.0
1.5
1.0
Output High-Z
0.5
0.0
0.E+00
5.E-06
1.E-05
2.E-05
2.E-05
3.E-05
3.E-05
4.E-05
4.E-05
5.E-05
5.E-05
Time (5 µs/div)
FIGURE 2-30:
Chip Select (CS) to
Amplifier Output Response Time at VDD = 5.5V
(MCP6293 and MCP6295 only).
DS21812E-page 9
MCP6291/1R/2/3/4/5
TYPICAL PERFORMANCE CURVES (CONTINUED)
Note: Unless otherwise indicated, TA = +25°C, VDD = +2.4V to +5.5V, VSS = GND, VCM = VDD/2, VOUT ≈ VDD/2,
VL = VDD/2, RL = 10 kΩ to VL, CL = 60 pF, and CS is tied low.
6
+125°C
+85°C
+25°C
-40°C
-1.0 -0.9 -0.8 -0.7 -0.6 -0.5 -0.4 -0.3 -0.2 -0.1 0.0
Input Voltage (V)
FIGURE 2-31:
Measured Input Current vs.
Input Voltage (below VSS).
DS21812E-page 10
Input, Output Voltage (V)
Input Current Magnitude (A)
1.E-02
10m
1m
1.E-03
100µ
1.E-04
10µ
1.E-05
1µ
1.E-06
100n
1.E-07
10n
1.E-08
1n
1.E-09
100p
1.E-10
10p
1.E-11
1p
1.E-12
VDD = 5.0V
G = +2V/V
5
4
VOUT
VIN
3
2
1
0
-1
-15
-14
-13
-12
-11
-10
-9
-8
-7
-6
-5
Time (1 ms/div)
FIGURE 2-32:
The MCP6291/1R/2/3/4/5
Show No Phase Reversal.
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
3.0
PIN DESCRIPTIONS
Descriptions of the pins are listed in Table 3-1 (single op amps) and Table 3-2 (dual and quad op amps).
TABLE 3-1:
PIN FUNCTION TABLE FOR SINGLE OP AMPS
MCP6291
MCP6293
MCP6291R
SOT-23-6
1
6
1
4
4
2
3
3
3
7
5
2
4
2
5
SOT-23-5
6
1
2
3
VOUT
Analog Output
4
VIN–
Inverting Input
3
VIN+
Non-inverting Input
7
6
VDD
Positive Power Supply
4
2
VSS
Negative Power Supply
—
—
—
8
5
CS
Chip Select
—
—
1,5
—
NC
No Internal Connection
MCP6292
PIN FUNCTION TABLE FOR DUAL AND QUAD OP AMPS
MCP6294
MCP6295
Symbol
1
1
—
VOUTA
Analog Output (op amp A)
2
2
2
VINA–
Inverting Input (op amp A)
Non-inverting Input (op amp A)
3
3
3
VINA+
8
4
8
VDD
Description
Positive Power Supply
5
5
—
VINB+
Non-inverting Input (op amp B)
6
6
6
VINB–
Inverting Input (op amp B)
7
7
7
VOUTB
Analog Output (op amp B)
—
8
—
VOUTC
Analog Output (op amp C)
—
9
—
VINC–
Inverting Input (op amp C)
—
10
—
VINC+
Non-inverting Input (op amp C)
Negative Power Supply
4
11
4
VSS
—
12
—
VIND+
Non-inverting Input (op amp D)
—
13
—
VIND–
Inverting Input (op amp D)
—
14
—
VOUTD
Analog Output (op amp D)
—
—
1
VOUTA/VINB+
—
—
5
CS
Analog Output (op amp A)/Non-inverting Input (op amp B)
Chip Select
Analog Outputs
The output pins are low-impedance voltage sources.
3.2
Analog Inputs
The non-inverting and inverting inputs are highimpedance CMOS inputs with low bias currents.
3.3
Description
1,5,8
TABLE 3-2:
3.1
Symbol
PDIP, SOIC,
MSOP
PDIP, SOIC,
MSOP
MCP6295’s VOUTA/VINB+ Pin
For the MCP6295 only, the output of op amp A is
connected directly to the non-inverting input of
op amp B; this is the VOUTA/VINB+ pin. This connection
makes it possible to provide a Chip Select pin for duals
in 8-pin packages.
© 2007 Microchip Technology Inc.
3.4
Chip Select Digital Input
This is a CMOS, Schmitt-triggered input that places the
part into a low power mode of operation.
3.5
Power Supply Pins
The positive power supply (VDD) is 2.4V to 6.0V higher
than the negative power supply (VSS). For normal
operation, the other pins are between VSS and VDD.
Typically, these parts are used in a single (positive)
supply configuration. In this case, VSS is connected to
ground and VDD is connected to the supply. VDD will
need bypass capacitors
DS21812E-page 11
MCP6291/1R/2/3/4/5
4.0
APPLICATION INFORMATION
The MCP6291/1R/2/3/4/5 family of op amps is
manufactured using Microchip’s state of the art CMOS
process, specifically designed for low-cost, low-power
and general purpose applications. The low supply
voltage, low quiescent current and wide bandwidth
makes the MCP6291/1R/2/3/4/5 ideal for battery-powered applications.
4.1
VDD, and dump any currents onto VDD. When
implemented as shown, resistors R1 and R2 also limit
the current through D1 and D2.
VDD
D1
V1
Rail-to-Rail Inputs
4.1.1
R1
INPUT VOLTAGE AND CURRENT
LIMITS
The ESD protection on the inputs can be depicted as
shown in Figure 4-1. This structure was chosen to
protect the input transistors, and to minimize input bias
current (IB). The input ESD diodes clamp the inputs
when they try to go more than one diode drop below
VSS. They also clamp any voltages that go too far
above VDD; their breakdown voltage is high enough to
allow normal operation, and low enough to bypass
quick ESD events within the specified limits.
VDD Bond
Pad
Input
Stage
Bond
VIN–
Pad
VSS Bond
Pad
FIGURE 4-1:
Structures.
Simplified Analog Input ESD
In order to prevent damage and/or improper operation
of these op amps, the circuit they are in must limit the
currents and voltages at the VIN+ and VIN– pins (see
Absolute Maximum Ratings †” at the beginning of
Section 1.0 “Electrical Characteristics”). Figure 4-2
shows the recommended approach to protecting these
inputs. The internal ESD diodes prevent the input pins
(VIN+ and VIN–) from going too far below ground, and
the resistors R1 and R2 limit the possible current drawn
out of the input pins. Diodes D1 and D2 prevent the
input pins (VIN+ and VIN–) from going too far above
DS21812E-page 12
VOUT
R2
VSS – (minimum expected V1)
2 mA
VSS – (minimum expected V2)
R2 >
2 mA
R1 >
FIGURE 4-2:
Inputs.
Protecting the Analog
It is also possible to connect the diodes to the left of the
resistor R1 and R2. In this case, the currents through
the diodes D1 and D2 need to be limited by some other
mechanism. The resistors then serve as in-rush current
limiters; the DC current into the input pins (VIN+ and
VIN–) should be very small.
A significant amount of current can flow out of the
inputs when the common mode voltage (VCM) is below
ground (VSS); see Figure 2-31. Applications that are
high impedance may need to limit the usable voltage
range.
4.1.3
VIN+ Bond
Pad
MCP629X
V2
PHASE REVERSAL
The MCP6291/1R/2/3/4/5 op amp is designed to
prevent phase reversal when the input pins exceed the
supply voltages. Figure 2-32 shows the input voltage
exceeding the supply voltage without any phase reversal.
4.1.2
D2
NORMAL OPERATION
The input stage of the MCP6291/1R/2/3/4/5 op amps
use two differential CMOS input stages in parallel. One
operates at low common mode input voltage (VCM),
while the other operates at high VCM. WIth this topology, the device operates with VCM up to 0.3V past
either supply rail. The input offset voltage (VOS) is measured at VCM = VSS - 0.3V and VDD + 0.3V to ensure
proper operation.
The transition between the two input stages occurs
when VCM = VDD - 1.1V. For the best distortion and gain
linearity, with non-inverting gains, avoid this region of
operation.
4.2
Rail-to-Rail Output
The output voltage range of the MCP6291/1R/2/3/4/5
op amp is VDD – 15 mV (min.) and VSS + 15 mV
(maximum) when RL = 10 kΩ is connected to VDD/2
and VDD = 5.5V. Refer to Figure 2-16 for more
information.
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
4.3
Capacitive Loads
4.4
Driving large capacitive loads can cause stability
problems for voltage feedback op amps. As the load
capacitance increases, the feedback loop’s phase
margin decreases and the closed-loop bandwidth is
reduced. This produces gain peaking in the frequency
response, with overshoot and ringing in the step
response. A unity-gain buffer (G = +1) is the most
sensitive to capacitive loads, though all gains show the
same general behavior.
When driving large capacitive loads with these op
amps (e.g., > 100 pF when G = +1), a small series
resistor at the output (RISO in Figure 4-3) improves the
feedback loop’s phase margin (stability) by making the
output load resistive at higher frequencies. The
bandwidth will be generally lower than the bandwidth
with no capacitive load.
–
RISO
MCP629X
VOUT
+
VIN
CL
MCP629X Chip Select
The MCP6293 and MCP6295 are single and dual op
amps with Chip Select (CS), respectively. When CS is
pulled high, the supply current drops to 0.7 µA (typical)
and flows through the CS pin to VSS. When this
happens, the amplifier output is put into a high-impedance state. By pulling CS low, the amplifier is enabled.
The CS pin has an internal 5 MΩ (typical) pull-down
resistor connected to VSS, so it will go low if the CS pin
is left floating. Figure 1-1 shows the output voltage and
supply current response to a CS pulse.
4.5
Cascaded Dual Op Amps
(MCP6295)
The MCP6295 is a dual op amp with Chip Select (CS).
The Chip Select input is available on what would be the
non-inverting input of a standard dual op amp (pin 5).
This is available because the output of op amp A
connects to the non-inverting input of op amp B, as
shown in Figure 4-5. The Chip Select input, which can
be connected to a microcontroller I/O line, puts the
device in Low-power mode. Refer to Section 4.4
“MCP629X Chip Select”.
VOUTA/VINB+ VINB–
FIGURE 4-3:
Output Resistor, RISO
stabilizes large capacitive loads.
1
Figure 4-4 gives recommended RISO values for
different capacitive loads and gains. The x-axis is the
normalized load capacitance (CL/GN), where GN is the
circuit's noise gain. For non-inverting gains, GN and the
Signal Gain are equal. For inverting gains, GN is
1+|Signal Gain| (e.g., -1 V/V gives GN = +2 V/V).
VINA–
VINA+
6
2
3
B
A
7
VOUTB
MCP6295
5
CS
100
Recommended R ISO (Ω)
FIGURE 4-5:
The output of op amp A is loaded by the input impedance of op amp B, which is typically 1013Ω||6 pF, as
specified in the DC specification table (Refer to
Section 4.3 “Capacitive Loads” for further details
regarding capacitive loads).
GN = 1 V/V
GN ≥ 2 V/V
10
10
100
1,000
Cascaded Gain Amplifier.
10,000
Normalized Load Capacitance; CL/GN (pF)
FIGURE 4-4:
Recommended RISO Values
for Capacitive Loads.
The common mode input range of these op amps is
specified in the data sheet as VSS – 300 mV and
VDD + 300 mV. However, since the output of op amp A
is limited to VOL and VOH (20 mV from the rails with a
10 kΩ load), the non-inverting input range of op amp B
is limited to the common mode input range of
VSS + 20 mV and VDD – 20 mV.
After selecting RISO for your circuit, double-check the
resulting frequency response peaking and step
response overshoot. Modify RISO's value until the
response is reasonable. Bench evaluation and
simulations with the MCP6291/1R/2/3/4/5 SPICE
macro model are helpful.
© 2007 Microchip Technology Inc.
DS21812E-page 13
MCP6291/1R/2/3/4/5
4.6
Supply Bypass
4.8
With this family of operational amplifiers, the power
supply pin (VDD for single supply) should have a local
bypass capacitor (i.e., 0.01 µF to 0.1 µF) within 2 mm
for good high-frequency performance. It also needs a
bulk capacitor (i.e., 1 µF or larger) within 100 mm to
provide large, slow currents. This bulk capacitor can be
shared with nearby analog parts.
4.7
Unused Op Amps
An unused op amp in a quad package (MCP6294)
should be configured as shown in Figure 4-6. These
circuits prevent the output from toggling and causing
crosstalk. Circuits A sets the op amp at its minimum
noise gain. The resistor divider produces any desired
reference voltage within the output voltage range of the
op amp; the op amp buffers that reference voltage.
Circuit B uses the minimum number of components
and operates as a comparator, but it may draw more
current.
¼ MCP6294 (A)
In applications where low input bias current is critical,
Printed Circuit Board (PCB) surface-leakage effects
need to be considered. Surface leakage is caused by
humidity, dust or other contamination on the board.
Under low humidity conditions, a typical resistance
between nearby traces is 1012Ω. A 5V difference would
cause 5 pA of current to flow, which is greater than the
MCP6291/1R/2/3/4/5 family’s bias current at 25°C
(1 pA, typical).
The easiest way to reduce surface leakage is to use a
guard ring around sensitive pins (or traces). The guard
ring is biased at the same voltage as the sensitive pin.
An example of this type of layout is shown in
Figure 4-7.
VIN–
VIN+
VSS
¼ MCP6294 (B)
VDD
R1
PCB Surface Leakage
VDD
Guard Ring
VDD
R2
VREF
FIGURE 4-7:
for Inverting Gain.
1.
R2
V REF = V DD ⋅ -----------------R1 + R2
FIGURE 4-6:
Unused Op Amps.
2.
DS21812E-page 14
Example Guard Ring Layout
For Inverting Gain and Transimpedance
Amplifiers (convert current to voltage, such as
photo detectors):
a. Connect the guard ring to the non-inverting
input pin (VIN+). This biases the guard ring
to the same reference voltage as the op
amp (e.g., VDD/2 or ground).
b. Connect the inverting pin (VIN–) to the input
with a wire that does not touch the PCB
surface.
Non-inverting Gain and Unity-Gain Buffer:
a. Connect the non-inverting pin (VIN+) to the
input with a wire that does not touch the
PCB surface.
b. Connect the guard ring to the inverting input
pin (VIN–). This biases the guard ring to the
common mode input voltage.
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
4.9
Application Circuits
4.9.1
4.9.3
MULTIPLE FEEDBACK LOW-PASS
FILTER
The MCP6291/1R/2/3/4/5 op amp can be used in
active-filter applications. Figure 4-8 shows an inverting,
third-order, multiple feedback low-pass filter that can be
used as an anti-aliasing filter.
R1
R2
R4
VOUT
VIN
C1
R3
C4
C3
CASCADED OP AMP
APPLICATIONS
The MCP6295 provides the flexibility of Low-power
mode for dual op amps in an 8-pin package. The
MCP6295 eliminates the added cost and space in
battery-powered applications by using two single op
amps with Chip Select lines or a 10-pin device with one
Chip Select line for both op amps. Since the two op
amps are internally cascaded, this device cannot be
used in circuits that require active or passive elements
between the two op amps. However, there are several
applications where this op amp configuration with
Chip Select line becomes suitable. The circuits below
show possible applications for this device.
4.9.3.1
MCP6291
VDD/2
FIGURE 4-8:
Pass Filter.
Multiple Feedback Low-
Load Isolation
With the cascaded op amp configuration, op amp B can
be used to isolate the load from op amp A. In applications where op amp A is driving capacitive or low
resistance loads in the feedback loop (such as an
integrator circuit or filter circuit), the op amp may not
have sufficient source current to drive the load. In this
case, op amp B can be used as a buffer.
This filter, and others, can be designed using
Microchip’s Filter design software. Refer to Section 5.0
“Design Aids”
4.9.2
B
PHOTODIODE AMPLIFIER
VOUTB
A
Figure 4-9 shows a photodiode biased in the photovoltaic mode for high precision. The resistor R converts
the diode current ID to the voltage VOUT. The capacitor
is used to limit the bandwidth or to stabilize the circuit
against the diode’s capacitance (it is not always
needed).
MCP6295
Load
CS
FIGURE 4-10:
Buffer.
Isolating the Load with a
C
R
ID
VOUT
light
MCP6291
VDD/2
FIGURE 4-9:
Photodiode Amplifier.
© 2007 Microchip Technology Inc.
DS21812E-page 15
MCP6291/1R/2/3/4/5
4.9.3.2
Cascaded Gain
4.9.3.4
Figure 4-11 shows a cascaded gain circuit configuration with Chip Select. Op amps A and B are configured
in a non-inverting amplifier configuration. In this configuration, it is important to note that the input offset voltage of op amp A is amplified by the gain of op amp A
and B, as shown below:
V OUT = V IN G A G B + V OSA G A G B + V OSB G B
Buffered Non-inverting Integrator
Figure 4-13 shows a lossy non-inverting integrator that
is buffered and has a Chip Select input. Op amp A is
configured as a non-inverting integrator. In this configuration, matching the impedance at each input is
recommended. R F is used to provide a feedback loop
at frequencies << 1/(2πR1C1) and makes this a lossy
integrator (it has a finite gain at DC). Op amp B is used
to isolate the load from the integrator.
Where:
R2
GA
=
op amp A gain
GB
=
op amp B gain
VOSA
=
op amp A input offset voltage
VOSB
=
op amp B input offset voltage
C2
RF
VIN
R1
B
A
MCP6295
Therefore, it is recommended to set most of the gain
with op amp A and use op amp B with relatively small
gain (e.g., a unity-gain buffer).
C1
CS
R 1 C 1 = ( R 2 || R F )C 2
R4
R3
R2
R1
FIGURE 4-13:
Buffered Non-inverting
Integrator with Chip Select.
4.9.3.5
B
A
VIN
Figure 4-14 uses an active compensator (op amp B) to
compensate for the non-ideal op amp characteristics
introduced at higher frequencies. This circuit uses
op amp B as a unity-gain buffer to isolate the
integration capacitor C1 from op amp A and drives the
capacitor with low-impedance source. Since both op
amps are matched very well, they provide a high quality
integrator.
CS
4.9.3.3
Cascaded Gain Circuit
Difference Amplifier
Figure 4-12 shows op amp A as a difference amplifier
with Chip Select. In this configuration, it is
recommended to use well-matched resistors (e.g.,
0.1%) to increase the Common Mode Rejection Ratio
(CMRR). Op amp B can be used for additional gain or
as a unity-gain buffer to isolate the load from the
difference amplifier.
R4
VIN2
VIN1
R2
R2
Inverting Integrator with Active
Compensation and Chip Select
VOUT
MCP6295
FIGURE 4-11:
Configuration.
VOUT
VIN
R1
C1
B
VOUT
A
MCP6295
R3
CS
R1
B
A
R1
VOUT
FIGURE 4-14:
Compensation.
Integrator Circuit with Active
MCP6295
CS
FIGURE 4-12:
DS21812E-page 16
Difference Amplifier Circuit.
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
4.9.3.6
Second-Order MFB Low-Pass Filter
with an Extra Pole-Zero Pair
Figure 4-15 is a second-order multiple feedback lowpass filter with Chip Select. Use the FilterLab® software
from Microchip to determine the R and C values for the
op amp A’s second-order filter. Op amp B can be used
to add a pole-zero pair using C3, R6 and R7.
R6
R1
C1
R3
C3
R7
R2
VIN
R5
C2
B
A
Capacitorless Second-Order
Low-Pass filter with Chip Select
The low-pass filter shown in Figure 4-17 does not
require external capacitors and uses only three
external resistors; the op amp’s GBWP sets the corner
frequency. R1 and R2 are used to set the circuit gain
and R3 is used to set the Q. To avoid gain peaking in
the frequency response, Q needs to be low (lower
values need to be selected for R3). Note that the
amplifier bandwidth varies greatly over temperature
and process. However, this configuration provides a
low cost solution for applications with high bandwidth
requirements.
VOUT
MCP6295
R4
4.9.3.8
VIN
R1
R2
R3
CS
FIGURE 4-15:
Second-Order Multiple
Feedback Low-Pass Filter with an Extra PoleZero Pair.
4.9.3.7
Second-Order Sallen-Key Low-Pass
Filter with an Extra Pole-Zero Pair
Figure 4-16 is a second-order, Sallen-Key low-pass
filter with Chip Select. Use the FilterLab® software from
Microchip to determine the R and C values for the op
amp A’s second-order filter. Op amp B can be used to
add a pole-zero pair using C3, R5 and R6.
R2
R4
R3
VIN
R1
R5
B
VREF
VOUT
MCP6295
CS
FIGURE 4-17:
Capacitorless Second-Order
Low-Pass Filter with Chip Select.
C3
R6
B
A
A
VOUT
MCP6295
C1
C2
CS
FIGURE 4-16:
Second-Order Sallen-Key
Low-Pass Filter with an Extra Pole-Zero Pair and
Chip Select.
© 2007 Microchip Technology Inc.
DS21812E-page 17
MCP6291/1R/2/3/4/5
5.0
DESIGN AIDS
Microchip provides the basic design tools needed for
the MCP6291/1R/2/3/4/5 family of op amps.
5.1
SPICE Macro Model
The latest SPICE macro model for the MCP6291/1R/2/
3/4/5 op amps is available on the Microchip web site at
www.microchip.com. This model is intended to be an
initial design tool that works well in the op amp’s linear
region of operation over the temperature range. See
the model file for information on its capabilities.
Bench testing is a very important part of any design and
cannot be replaced with simulations. Also, simulation
results using this macro model need to be validated by
comparing them to the data sheet specifications and
characteristic curves.
5.2
FilterLab® Software
Microchip’s FilterLab® software is an innovative
software tool that simplifies analog active filter (using
op amps) design. Available at no cost from the
Microchip web site at www.microchip.com/filterlab, the
FilterLab design tool provides full schematic diagrams
of the filter circuit with component values. It also
outputs the filter circuit in SPICE format, which can be
used with the macro model to simulate actual filter
performance.
5.3
Mindi™ Simulator Tool
Microchip’s Mindi™ simulator tool aids in the design of
various circuits useful for active filter, amplifier and
power-management applications. It is a free online
simulation tool available from the Microchip web site at
www.microchip.com/mindi. This interactive simulator
enables designers to quickly generate circuit diagrams,
simulate circuits. Circuits developed using the Mindi
simulation tool can be downloaded to a personal
computer or workstation.
5.4
5.5
Analog Demonstration and
Evaluation Boards
Microchip offers a broad spectrum of Analog Demonstration and Evaluation Boards that are designed to
help you achieve faster time to market. For a complete
listing of these boards and their corresponding user’s
guides and technical information, visit the Microchip
web site at www.microchip.com/analogtools.
Two of our boards that are especially useful are:
• P/N SOIC8EV: 8-Pin SOIC/MSOP/TSSOP/DIP
Evaluation Board
• P/N SOIC14EV: 14-Pin SOIC/TSSOP/DIP Evaluation Board
5.6
Application Notes
The following Microchip Application Notes are available on the Microchip web site at www.microchip. com/
appnotes and are recommended as supplemental reference resources.
ADN003: “Select the Right Operational Amplifier for
your Filtering Circuits”, DS21821
AN722: “Operational Amplifier Topologies and DC
Specifications”, DS00722
AN723: “Operational Amplifier AC Specifications and
Applications”, DS00723
AN884: “Driving Capacitive Loads With Op Amps”,
DS00884
AN990: “Analog Sensor Conditioning Circuits – An
Overview”, DS00990
These application notes and others are listed in the
design guide:
“Signal Chain Design Guide”, DS21825
MAPS (Microchip Advanced Part
Selector)
MAPS is a software tool that helps semiconductor
professionals efficiently identify Microchip devices that
fit a particular design requirement. Available at no cost
from the Microchip web site at www.microchip.com/
maps, the MAPS is an overall selection tool for
Microchip’s product portfolio that includes Analog,
Memory, MCUs and DSCs. Using this tool you can
define a filter to sort features for a parametric search of
devices and export side-by-side technical comparison
reports. Helpful links are also provided for Data sheets,
Purchase, and Sampling of Microchip parts.
DS21812E-page 18
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
6.0
PACKAGING INFORMATION
6.1
Package Marking Information
5-Lead SOT-23 (MCP6291 and MCP6291R)
Device
XXNN
Example:
Code
MCP6291
CJNN
MCP6291R
EVNN
CJ25
Note: Applies to 5-Lead SOT-23
Example:
6-Lead SOT-23 (MCP6283)
Device
XXNN
MCP6293
Code
CMNN
Note: Applies to 6-Lead SOT-23
8-Lead MSOP
CM25
Example:
XXXXXX
6291E
YWWNNN
436256
8-Lead PDIP (300 mil)
XXXXXXXX
XXXXXNNN
YYWW
MCP6291
E/P256
0436
8-Lead SOIC (150 mil)
XXXXXXXX
XXXXYYWW
NNN
e3
*
MCP6291
e3
E/P^^256
0743
OR
Example:
MCP6291
E/SN0436
256
Legend: XX...X
Y
YY
WW
NNN
Note:
Example:
OR
MCP6291E
e3
SN^^0743
256
Customer-specific information
Year code (last digit of calendar year)
Year code (last 2 digits of calendar year)
Week code (week of January 1 is week ‘01’)
Alphanumeric traceability code
Pb-free JEDEC designator for Matte Tin (Sn)
This package is Pb-free. The Pb-free JEDEC designator ( e3 )
can be found on the outer packaging for this package.
In the event the full Microchip part number cannot be marked on one line, it will
be carried over to the next line, thus limiting the number of available
characters for customer-specific information.
© 2007 Microchip Technology Inc.
DS21812E-page 19
MCP6291/1R/2/3/4/5
Package Marking Information (Continued)
14-Lead PDIP (300 mil) (MCP6294)
Example:
XXXXXXXXXXXXXX
XXXXXXXXXXXXXX
YYWWNNN
MCP6294-E/P
0436256
MCP6294
e3
E/P^^
0743256
OR
14-Lead SOIC (150 mil) (MCP6294)
Example:
XXXXXXXXXX
XXXXXXXXXX
YYWWNNN
MCP6294ESL
0436256
MCP6294
E/SL^^
e3
0436256
OR
14-Lead TSSOP (MCP6294)
DS21812E-page 20
Example:
XXXXXX
YYWW
6294EST
0436
NNN
256
© 2007 Microchip Technology Inc.
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DS21812E-page 22
© 2007 Microchip Technology Inc.
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© 2007 Microchip Technology Inc.
DS21812E-page 25
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DS21812E-page 26
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DS21812E-page 27
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DS21812E-page 29
MCP6291/1R/2/3/4/5
NOTES:
DS21812E-page 30
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
APPENDIX A:
REVISION HISTORY
Revision E (November 2007)
The following is the list of modifications:
1.
2.
3.
4.
5.
6.
7.
8.
Updated notes to Section 1.0 “Electrical Characteristics”. Increased absolute maximum voltage range of input pins. Increased maximum
operating supply voltage (VDD).
Added Test Circuits.
Added Figure 2-31 and Figure 2-32.
Added Section 4.1.1 “Phase Reversal”,
Section 4.1.2 “Input Voltage and Current
Limits”, and Section 4.1.3 “Normal Operation”.
Added Section 4.7 “Unused Op Amps”.
Updated Section 5.0 “Design Aids”.
Corrected Package Markings.
Updated Package Outline Drawing.
Revision D (December 2004)
The following is the list of modifications:
1.
2.
3.
4.
5.
6.
Added SOT-23-5 packages for the MCP6291
and MCP6291R single op amps.
Added SOT-23-6 package for the MCP6293
single op amp.
Added Section 3.0 “Pin Descriptions”.
Corrected application circuits (Section 4.9
“Application Circuits”).
Added SOT-23-5 and SOT-23-6 packages and
corrected
package
marking
information
(Section 6.0 “Packaging Information”).
Added Appendix A: Revision History.
Revision C (June 2004)
• Undocumented changes.
Revision B (October 2003)
• Undocumented changes.
Revision A (June 2003)
• Original data sheet release.
© 2007 Microchip Technology Inc.
DS21812E-page 31
MCP6291/1R/2/3/4/5
NOTES:
DS21812E-page 32
© 2007 Microchip Technology Inc.
MCP6291/1R/2/3/4/5
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.
PART NO.
Device
–
X
/XX
Temperature
Range
Package
Examples:
a)
b)
c)
Device:
MCP6291:
MCP6291T:
MCP6291RT:
MCP6292:
MCP6292T:
MCP6293:
MCP6293T:
MCP6294:
MCP6294T:
MCP6295:
MCP6295T:
Single Op Amp
Single Op Amp
(Tape and Reel)
(SOIC, MSOP, SOT-23-5)
Single Op Amp
(Tape and Reel) (SOT-23-5)
Dual Op Amp
Dual Op Amp
(Tape and Reel) (SOIC, MSOP)
Single Op Amp with Chip Select
Single Op Amp with Chip Select
(Tape and Reel)
(SOIC, MSOP, SOT-23-6)
Quad Op Amp
Quad Op Amp
(Tape and Reel) (SOIC, TSSOP)
Dual Op Amp with Chip Select
Dual Op Amp with Chip Select
(Tape and Reel) (SOIC, MSOP)
d)
e)
a)
b)
c)
d)
a)
b)
Temperature Range:
E
= -40° C to +125° C
Package:
OT = Plastic Small Outline Transistor (SOT-23), 5-lead
(MCP6291, MCP6291R)
CH = Plastic Small Outline Transistor (SOT-23), 6-lead
(MCP6293)
MS = Plastic MSOP, 8-lead
P
= Plastic DIP (300 mil body), 8-lead, 14-lead
SN = Plastic SOIC, (3.90 mm body), 8-lead
SL = Plastic SOIC (3.90 mm body), 14-lead
ST = Plastic TSSOP (4.4 mm body), 14-lead
c)
d)
Extended Temperature,
8 lead SOIC package.
MCP6291-E/MS: Extended Temperature,
8 lead MSOP package.
MCP6291-E/P:
Extended Temperature,
8 lead PDIP package.
MCP6291T-E/OT: Tape and Reel,
Extended Temperature,
5 lead SOT-23 package.
MCP6291RT-E/OT: Tape and Reel,
Extended Temperature,
5 lead SOT-23 package.
MCP6292-E/SN:
Extended Temperature,
8 lead SOIC package.
MCP6292-E/MS: Extended Temperature,
8 lead MSOP package.
MCP6292-E/P:
Extended Temperature,
8 lead PDIP package.
MCP6292T-E/SN: Tape and Reel,
Extended Temperature,
8 lead SOIC package.
MCP6293-E/SN:
Extended Temperature,
8 lead SOIC package.
MCP6293-E/MS: Extended Temperature,
8 lead MSOP package.
MCP6293-E/P:
Extended Temperature,
8 lead PDIP package.
MCP6293T-E/CH: Tape and Reel,
Extended Temperature,
6 lead SOT-23 package.
a)
MCP6294-E/P:
b)
MCP6294T-E/SL:
c)
MCP6294-E/SL:
d)
MCP6294-E/ST:
a)
MCP6295-E/SN:
b)
c)
d)
© 2007 Microchip Technology Inc.
MCP6291-E/SN:
Extended Temperature,
14 lead PDIP package.
Tape and Reel,
Extended Temperature,
14 lead SOIC package.
Extended Temperature,
14 lead SOIC package.
Extended Temperature,
14 lead TSSOP package.
Extended Temperature,
8 lead SOIC package.
MCP6295-E/MS: Extended Temperature,
8 lead MSOP package.
MCP6295-E/P:
Extended Temperature,
8 lead PDIP package.
MCP6295T-E/SN: Tape and Reel,
Extended Temperature,
8 lead SOIC package.
DS21812E-page 33
MCP6291/1R/2/3/4/5
NOTES:
DS21812E-page 34
© 2007 Microchip Technology Inc.
Note the following details of the code protection feature on Microchip devices:
•
Microchip products meet the specification contained in their particular Microchip Data Sheet.
•
Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the
intended manner and under normal conditions.
•
There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our
knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data
Sheets. Most likely, the person doing so is engaged in theft of intellectual property.
•
Microchip is willing to work with the customer who is concerned about the integrity of their code.
•
Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not
mean that we are guaranteeing the product as “unbreakable.”
Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our
products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts
allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.
Information contained in this publication regarding device
applications and the like is provided only for your convenience
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
MICROCHIP MAKES NO REPRESENTATIONS OR
WARRANTIES OF ANY KIND WHETHER EXPRESS OR
IMPLIED, WRITTEN OR ORAL, STATUTORY OR
OTHERWISE, RELATED TO THE INFORMATION,
INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights.
Trademarks
The Microchip name and logo, the Microchip logo, Accuron,
dsPIC, KEELOQ, KEELOQ logo, microID, MPLAB, PIC,
PICmicro, PICSTART, PRO MATE, rfPIC and SmartShunt are
registered trademarks of Microchip Technology Incorporated
in the U.S.A. and other countries.
AmpLab, FilterLab, Linear Active Thermistor, Migratable
Memory, MXDEV, MXLAB, SEEVAL, SmartSensor and The
Embedded Control Solutions Company are registered
trademarks of Microchip Technology Incorporated in the
U.S.A.
Analog-for-the-Digital Age, Application Maestro, CodeGuard,
dsPICDEM, dsPICDEM.net, dsPICworks, dsSPEAK, ECAN,
ECONOMONITOR, FanSense, FlexROM, fuzzyLAB,
In-Circuit Serial Programming, ICSP, ICEPIC, Mindi, MiWi,
MPASM, MPLAB Certified logo, MPLIB, MPLINK, PICkit,
PICDEM, PICDEM.net, PICLAB, PICtail, PowerCal,
PowerInfo, PowerMate, PowerTool, REAL ICE, rfLAB, Select
Mode, Smart Serial, SmartTel, Total Endurance, UNI/O,
WiperLock and ZENA are trademarks of Microchip
Technology Incorporated in the U.S.A. and other countries.
SQTP is a service mark of Microchip Technology Incorporated
in the U.S.A.
All other trademarks mentioned herein are property of their
respective companies.
© 2007, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.
Printed on recycled paper.
Microchip received ISO/TS-16949:2002 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.
© 2007 Microchip Technology Inc.
DS21812E-page 35
WORLDWIDE SALES AND SERVICE
AMERICAS
ASIA/PACIFIC
ASIA/PACIFIC
EUROPE
Corporate Office
2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7200
Fax: 480-792-7277
Technical Support:
http://support.microchip.com
Web Address:
www.microchip.com
Asia Pacific Office
Suites 3707-14, 37th Floor
Tower 6, The Gateway
Harbour City, Kowloon
Hong Kong
Tel: 852-2401-1200
Fax: 852-2401-3431
India - Bangalore
Tel: 91-80-4182-8400
Fax: 91-80-4182-8422
India - New Delhi
Tel: 91-11-4160-8631
Fax: 91-11-4160-8632
Austria - Wels
Tel: 43-7242-2244-39
Fax: 43-7242-2244-393
Denmark - Copenhagen
Tel: 45-4450-2828
Fax: 45-4485-2829
India - Pune
Tel: 91-20-2566-1512
Fax: 91-20-2566-1513
France - Paris
Tel: 33-1-69-53-63-20
Fax: 33-1-69-30-90-79
Japan - Yokohama
Tel: 81-45-471- 6166
Fax: 81-45-471-6122
Germany - Munich
Tel: 49-89-627-144-0
Fax: 49-89-627-144-44
Atlanta
Duluth, GA
Tel: 678-957-9614
Fax: 678-957-1455
Boston
Westborough, MA
Tel: 774-760-0087
Fax: 774-760-0088
Chicago
Itasca, IL
Tel: 630-285-0071
Fax: 630-285-0075
Dallas
Addison, TX
Tel: 972-818-7423
Fax: 972-818-2924
Detroit
Farmington Hills, MI
Tel: 248-538-2250
Fax: 248-538-2260
Kokomo
Kokomo, IN
Tel: 765-864-8360
Fax: 765-864-8387
Los Angeles
Mission Viejo, CA
Tel: 949-462-9523
Fax: 949-462-9608
Santa Clara
Santa Clara, CA
Tel: 408-961-6444
Fax: 408-961-6445
Toronto
Mississauga, Ontario,
Canada
Tel: 905-673-0699
Fax: 905-673-6509
Australia - Sydney
Tel: 61-2-9868-6733
Fax: 61-2-9868-6755
China - Beijing
Tel: 86-10-8528-2100
Fax: 86-10-8528-2104
China - Chengdu
Tel: 86-28-8665-5511
Fax: 86-28-8665-7889
Korea - Daegu
Tel: 82-53-744-4301
Fax: 82-53-744-4302
China - Fuzhou
Tel: 86-591-8750-3506
Fax: 86-591-8750-3521
Korea - Seoul
Tel: 82-2-554-7200
Fax: 82-2-558-5932 or
82-2-558-5934
China - Hong Kong SAR
Tel: 852-2401-1200
Fax: 852-2401-3431
Malaysia - Kuala Lumpur
Tel: 60-3-6201-9857
Fax: 60-3-6201-9859
China - Nanjing
Tel: 86-25-8473-2460
Fax: 86-25-8473-2470
Malaysia - Penang
Tel: 60-4-227-8870
Fax: 60-4-227-4068
China - Qingdao
Tel: 86-532-8502-7355
Fax: 86-532-8502-7205
Philippines - Manila
Tel: 63-2-634-9065
Fax: 63-2-634-9069
China - Shanghai
Tel: 86-21-5407-5533
Fax: 86-21-5407-5066
Singapore
Tel: 65-6334-8870
Fax: 65-6334-8850
China - Shenyang
Tel: 86-24-2334-2829
Fax: 86-24-2334-2393
Taiwan - Hsin Chu
Tel: 886-3-572-9526
Fax: 886-3-572-6459
China - Shenzhen
Tel: 86-755-8203-2660
Fax: 86-755-8203-1760
Taiwan - Kaohsiung
Tel: 886-7-536-4818
Fax: 886-7-536-4803
China - Shunde
Tel: 86-757-2839-5507
Fax: 86-757-2839-5571
Taiwan - Taipei
Tel: 886-2-2500-6610
Fax: 886-2-2508-0102
China - Wuhan
Tel: 86-27-5980-5300
Fax: 86-27-5980-5118
Thailand - Bangkok
Tel: 66-2-694-1351
Fax: 66-2-694-1350
Italy - Milan
Tel: 39-0331-742611
Fax: 39-0331-466781
Netherlands - Drunen
Tel: 31-416-690399
Fax: 31-416-690340
Spain - Madrid
Tel: 34-91-708-08-90
Fax: 34-91-708-08-91
UK - Wokingham
Tel: 44-118-921-5869
Fax: 44-118-921-5820
China - Xian
Tel: 86-29-8833-7252
Fax: 86-29-8833-7256
10/05/07
DS21812E-page 36
© 2007 Microchip Technology Inc.

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