MOTOROLA MC1374 Tv modulator circuit Datasheet

Order this document by MC1374/D
The MC1374 includes an FM audio modulator, sound carrier oscillator, RF
oscillator, and RF dual input modulator. It is designed to generate a TV signal
from audio and video inputs. The MC1374’s wide dynamic range and low
distortion audio make it particularly well suited for applications such as video
tape recorders, video disc players, TV games and subscription decoders.
• Single Supply, 5.0 V to 12 V
•
•
•
•
•
•
•
TV MODULATOR CIRCUIT
SEMICONDUCTOR
TECHNICAL DATA
Channel 3 or 4 Operation
Variable Gain RF Modulator
Wide Dynamic Range
Low Intermodulation Distortion
Positive or Negative Sync
14
Low Audio Distortion
1
Few External Components
P SUFFIX
PLASTIC PACKAGE
CASE 646
ORDERING INFORMATION
Device
Operating
Temperature Range
Package
MC1374P
TA = 0° to +70°C
Plastic DIP
Figure 1. Simplified Application
V
Channel 3
4
+
S1
C8
0.001
C2
56
R4
6.8k
+
C3
120
C14
0.01
L2
C5
0.001
R5
3.3k
6
9
5
10
4
C4
50
8
R7
75Ω
0.22µH
L3
C15
0.001
0.22µH
L4
Output
R2
470
+
3
t
7
L1
VPin 1
VPin 11
D1
MPN3404
5–25
C7
R3
470
C1
0.001
C9
0.001
R10
10k
R1
470
4
+VCC = 12V
+
U1
MC1374
C12
47
C13
22
R9
560
11
3
12
2
13
1
C11
22
R14
56k
C16
47
+
+
R8
2.2k
R12
180k
14
D2
1N914
C10
10µF
Video In
+
R6
2.2k
Shaded Parts Optional
R13
30k
R11
220
Audio In
C6
1µF
L1 – 4 Turns #22, 1/4″ Dia.
L2 – 40 Turns, #36, 3/16″ Dia.
 Motorola, Inc. 1996
MOTOROLA ANALOG IC DEVICE DATA
Rev 0
1
MC1374
MAXIMUM RATINGS (TA = 25°C, unless otherwise noted.)
Value
Unit
14
Vdc
0 to +70
°C
–65 to +150
°C
150
°C
1.25
10 mW/°C
W
Rating
Supply Voltage
Operating Ambient Temperature Range
Storage Temperature Range
Junction Temperature
Power Dissipation Package
Derate above 25°C
ELECTRICAL CHARACTERISTICS (VCC = 12 Vdc, TA = 25°C, fc = 67.25 MHz, Figure 4 circuit, unless otherwise noted.)
Characteristics
Min
Typ
Max
Unit
5.0
12
12
V
AM OSCILLATOR/MODULATOR
Operating Supply Voltage
Supply Current (Figure 1)
–
13
–
mA
0.25
1.0
1.0
V Pk
RF Output (Pin 9, R7 = 75 Ω, No External Load)
–
170
–
mV pp
Carrier Suppression
36
40
–
dB
Linearity (75% to 12.5% Carrier, 15 kHz to 3.58 MHz)
–
–
2.0
%
5.0
7.0
10
%
Video Input Dynamic Range (Sync Amplitude)
Differential Gain Distortion (IRE Test Signal)
Differential Phase Distortion (3.58 MHz IRE Test Signal)
–
1.5
2.0
Degrees
920 kHz Beat (3.58 MHz @ 30%, 4.5 MHz @ 25%)
–
–57
–
dB
Video Bandwidth (75 Ω Input Source)
30
–
–
MHz
Oscillator Frequency Range
–
105
–
MHz
Internal Resistance across Tank (Pin 6 to Pin 7)
Internal Capacitance across Tank (Pin 6 to Pin 7)
–
–
1.8
4.0
–
–
kΩ
pF
ELECTRICAL CHARACTERISTICS (TA = 25°C, VCC = 12 Vdc, 4.5 MHz, Test circuit of Figure 11, unless otherwise noted.)
Min
Typ
Max
Unit
Frequency Range of Modulator
Frequency Shift versus Temperature (Pin 14 open)
Frequency Shift versus VCC (Pin 14 open)
Output Amplitude (Pin 3 not loaded)
Output Harmonics, Unmodulated
14
–
–
–
–
4.5
0.2
–
900
–
14
0.3
4.0
–
–40
MHz
kHz/°C
kHz/V
mVpp
dB
Modulation Sensitivity
1.7 MHz
4.5 MHz
10.7 MHz
–
–
–
0.20
0.24
0.80
–
–
–
MHz/V
Audio Distortion (±25 kHz Deviation, Optimized Bias Pin 14)
Audio Distortion (±25 kHz Deviation, Pin 14 self biased)
Incidental AM (±25 kHz FM)
–
–
–
0.6
1.4
2.0
1.0
–
–
%
Audio Input Resistance (Pin 14 to ground)
Audio Input Capacitance (Pin 14 to ground)
–
–
6.0
5.0
–
–
kΩ
pF
Stray Tuning Capacitance (Pin 3 to ground)
Effective Oscillator Source Impedance (Pin 3 to load)
–
–
5.0
2.0
–
–
pF
kΩ
2
MOTOROLA ANALOG IC DEVICE DATA
Characteristics
FM OSCILLATOR/MODULATOR
MC1374
Figure 2. TV Modulator
Bias
Section
R10
FM Oscillator/Modulator
Sound Carrier
Audio In
OSC B+
14
4
R12
6.0k
R11
AM Modulator
Sound Carrier
Oscillator
3
2
VCC
8
AM Oscillator
RF Out
9
RF Tank
7
6
R16
Q21
Q7
Q22
Q1
Q2
R13
325
Q19 Q20
Q12 Q13
Q14 Q15
R17
Q25
C1
Q24
R14
Q3
Q6
Q4
Q5
Q10
Q11
R15
D1
R1
R2
R3
5
Gnd
R4
R5
1
Sound Carrier
In
Q9
13
R6
12
Gain
Q16
R7
Q17
R8
I2 = 1.15 mA
Q8
I1 = 1.15 mA
Q27
I1 = 1.15 mA
Q26
Q23
Q18
R9
11
Video In
GENERAL INFORMATION
The MC1374 contains an RF oscillator, RF modulator, and
a phase shift type FM modulator, arranged to permit good
printed circuit layout of a complete TV modulation system.
The RF oscillator is similar to the one used in MC1373, and is
coupled internally in the same way. Its frequency is controlled
by an external tank on Pins 6 and 7, or by a crystal circuit, and
will operate to approximately 105 MHz. The video modulator
is a balanced type as used in the well known MC1496.
Modulated sound carrier and composite video information
can be put in separately on Pins 1 and 11 to minimize
unwanted crosstalk. A single resistor on Pins 12 and 13 is
selected to set the modulator gain. The RF output at Pin 9 is
a current source which drives a load connected from Pin 9 to
VCC.
The FM system was designed specifically for the TV
intercarrier function. For circuit economy, one phase shift
circuit was built into the ship. Still, it will operate from 1.4 MHz
to 14 MHz, low enough to be used in a cordless telephone
MOTOROLA ANALOG IC DEVICE DATA
base station (1.76 MHz), and high enough to be used as an
FM IF test signal source (10.7 MHz). At 4.5 MHz, a deviation
of ± 25 kHz can be achieved with 0.6% distortion (typical).
In the circuit above, devices Q1 through Q7 are active in
the oscillator function. Differential amplifier Q3, Q4, Q5, and
Q6 acts as a gain stage, sinking current from input section
Q1, Q2 and the phase shift network R17, C1. Input amplifier
Q1, Q2 can vary the amount of “in phase” Q4 current to be
combined with phase shifter current in load resistor R16. The
R16 voltage is applied to emitter follower Q7 which drives an
external L–C circuit. Feedback from the center of the L–C
circuit back to the base of Q6 closes the loop. As audio input
is applied which would offset the stable oscillatory phase, the
frequency changes to counteract. The input to Pin 14 can
include a dc feedback current for AFC over a limited range.
The modulated FM signal from Pin 3 is coupled to Pin 1 of
the RF modulator and is then modulated onto the AM carrier.
3
MC1374
4
In television, one of the most serious concerns is the
prevention of the intermodulation of color (3.58 MHz) and
sound (4.5 MHz) frequencies, which causes a 920 kHz signal
to appear in the spectrum. Very little (3rd order) nonlinearity is
needed to cause this problem. The results in Figure 6 are
unsatisfactory, and demonstrate that too much of the
available dynamic range of the MC1374 has been used.
Figures 8 and 10 show that by either reducing standard
signal level, or reducing gain, acceptable results may be
obtained.
At VHF frequencies, small imbalances within the device
introduce substantial amounts of 2nd harmonic in the RF
output. At 67 MHz, the 2nd harmonic is only 6 to 8 dB below
the maximum fundamental. For this reason, a double pi low
pass filter is shown in the test circuit of Figure 3 and works
well for Channel 3 and 4 lab work. For a fully commercial
application, a vestigial sideband filter will be required. The
general form and approximate values are shown in Figure 19.
It must be exactly aligned to the particular channel.
Figure 3. AM Modulator Transfer Function
2I1RL
RF Output
V(p–p)
AM Section
The AM modulator transfer function in Figure 3 shows that
the video input can be of either polarity (and can be applied at
either input). When the voltages on Pin 1 and Pin 11 are
equal, the RF output is theoretically zero. As the difference
between VPin 11 and VPin 1 increases, the RF output
increases linearly until all of the current from both I1 current
sources (Q8 and Q9) is flowing in one side of the modulator.
This occurs when ±(VPin11 – VPin1) = I1 RG, where I1 is
typically 1.15 mA. The peak–to–peak RF output is the 2I1 RL.
Usually the value of RL is chosen to be 75 Ω to ease the
design of the output filter and match into TV distribution
systems. The theoretical range of input voltage and RG is
quite wide, but noise and available sound level limit the useful
video (sync tip) amplitude to between 0.25 Vpk and 1.0 Vpk.
It is recommended that the value of RG be chosen so that
only about half of the dynamic range will be used at sync tip
level.
The operating window of Figure 5 shows a cross–hatched
area where Pin 1 and Pin 11 voltages must always be in order
to avoid saturation in any part of the modulator. The letter φ
represents one diode drop, or about 0.75 V. The oscillator
Pins 6 and 7 must be biased to a level of VCC – φ – 2I1 RL (or
lower) and the input Pins 1 and 11 must always be at least 2φ
below that. It is permissible to operate down to 1.6 V,
saturating the current sources, but whenever possible, the
minimum should be 3φ above ground.
The oscillator will operate dependably up to about
105 MHz with a broad range of tank circuit component
values. It is desirable to use a small L and a large C to
minimize the dependence on IC internal capacitance. An
operating Q between 10 and 20 is recommended. The values
of R1, R2 and R3 are chosen to produce the desired Q and to
set the Pin 6 and 7 dc voltage as discussed above.
Unbalanced operation, i.e., Pin 6 or 7 bypassed to ground, is
not recommended. Although the oscillator will still run, and
the modulator will produce a useable signal, this mode
causes substantial base–band video feedthrough.
Bandswitching, as Figure 1 shows, can still be accomplished
economically without using the unbalanced method.
The oscillator frequency with respect to temperature in the
test circuit shows less than ±20 kHz total shift from 0° to 50°C
as shown in Figure 7. At higher temperatures the slope
approaches 2.0 kHz/°C. Improvement in this region would
require a temperature compensating tuning capacitor of the
N75 family.
Crystal control is feasible using the circuit shown in Figure
21. The crystal is a 3rd overtone series type, used in series
resonance. The L1, C2 resonance is adjusted well below the
crystal frequency and is sufficiently tolerant to permit fixed
values. A frequency shift versus temperature of less than
1.0 Hz/°C can be expected from this approach. The resistors
Ra and Rb are to suppress parasitic resonances.
Coupling of output RF to wiring and components on Pins 1
and 11 can cause as much as 300 kHz shift in carrier (at
67 MHz) over the video input range. A careful layout can
keep this shift below 10 kHz. Oscillator may also be
inadvertently coupled to the RF output, with the undesired
effect of preventing a good null when V11 = V1. Reasonable
care will yield carrier rejection ratios of 36 to 40 dB below sync
tip level carrier.
0
+I1RG
–I1RG
Differential Input, V11–V1 (V)
Figure 4. AM Test Circuit
R2
470
0.1µH
L1
0.001
470
R3
C2 56
R1
470
6
V1
10µF
+
7
1
VCC
8
RL
75
11
22µH
Video
Input
22
1.0k
V11
RF
9
12
22µH
47
22
13 5
RG
MOTOROLA ANALOG IC DEVICE DATA
Figure 5. The Operating Window
Figure 6. 920 kHz Beat
0
[dB]
–10
–20
(fc) AMPLITUDE
12
R = 75 Ω
11 I L= 1.15 mA
1
VCC
10
VCC – 2I1RL
9.0
VCC – φ – 2I1RL
8.0 V – 3φ – 2I R
CC
1 L
7.0
3φ
6.0
Recommended
V1 & V11
5.0
Operating Region
4.0
3.0
2.0
Absolute Min = 1.6 V
(2φ + Sat)
1.0
0
5.0
6.0
7.0
8.0
9.0
10
11
(fc ± 920 kHz) AMPLITUDE
AM MODULATOR INPUT VOLTAGE PIN 1 OR PIN 11 (V)
MC1374
–30
–40
a
–60
–70
–80
12
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4
DIFFERENTIAL INPUT (V11 – V1) [Vdc)
VCC, SUPPLY VOLTAGE (Vdc)
Figure 8. 920 kHz Beat
10
0
fc ≈ 61.25 MHz
VCC = 12 Vdc
–10
[dB]
(fc ± 920 kHz) AMPLITUDE
–10
–20
–30
–40
–50
–60
–20
(fc) AMPLITUDE
0
FREQUENCY SHIFT (kHz)
b
–50
Figure 7. RF Oscillator Frequency
versus Temperature
–30
Initial Video = 0.5 Vdc
Chroma (3.58 MHz) = 150 mVpp
Sound (4.5 MHz) a) = 125 mVpp
b) = 250 mVpp
Gain Resistor RG = 1.0 kΩ
–40
–50
b
–60
a
–70
–70
–80
0
25
50
75
100
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4
DIFFERENTIAL INPUT (V11 – V1) [Vdc)
TA, AMBIENT TEMPERATURE (°C)
Figure 9. RF Oscillator Frequency
versus Supply Voltage
Figure 10. 920 kHz Beat
0
0
–10
[dB]
10
–20
–30
–40
TA = 25°C
fc = 61.25 MHz
–50
–60
–70
5.0
–20
–30
(fc) AMPLITUDE
–10
(fc ± 920 kHz) AMPLITUDE
NORMALIZED FREQUENCY (kHz)
Initial Video = 1.0 Vdc
Chroma (3.58 MHz) = 300 mVpp
Sound (4.5 MHz) a) = 250 mVpp
b) = 500 mVpp
Gain Resistor RG = 1.0 kΩ
Initial Video = 1.0 Vdc
Chroma (3.58 MHz) = 300 mVpp
Sound (4.5 MHz) a) = 250 mVpp
b) = 500 mVpp
Gain Resistor (RG) = 2.2 kΩ
–40
–50
–60
b
a
–70
–80
6.0
7.0
8.0
9.0
10
VCC, SUPPLY VOLTAGE (V)
MOTOROLA ANALOG IC DEVICE DATA
11
12
0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.5 1.6 1.8 2.0 2.2 2.4 2.8
DIFFERENTIAL INPUT (V11 – V1) [Vdc)
5
MC1374
6
The source impedance of Pin 3 is approximately 2.0 kΩ, and
the open circuit amplitude is about 900 mV pp for the test
circuit shown in Figure 11.
The application circuit of Figure 1 shows the
recommended approach to coupling the FM output from Pin 3
to the AM modulator input, Pin 1. The input impedance at Pin
1 is very high, so the intercarrier level is determined by the
source impedance of Pin 3 driving through C4 into the video
bias circuit impedance of R4 and R5, about 2.2 k. This
provides an intercarrier level of 500 mV pp, which is correct
for the 1.0 V peak video level chosen in this design. Resistor
R6 and the input capacitance of Pin 1 provide some
decoupling of stray pickup of RF oscillator or AM output which
may be coupled to the sound circuitry.
Figure 11. FM Test Circuit
fo
C3
L2
(MHz) (pF) (µH)
10.7
12
10
4.5
120
10
1.76
200
40
VCC
7
8
6
9
5
10
4
11
3
12
2
0.001
µF 1
13
C14
0.01µF
Intercarrier
Sound Output
(Use FET Probe)
C3
120pF
L2
10µH
C5
14
Optional Bias R
(See Text)
R12 C6
+ 1µF
R13
Audio
Input
Figure 12. Modulator Sensitivity
2.0
MAXIMUM CENTER-FREQUENCY
SLOPE (∆ f/∆ Vin ) (MHz/V)
FM Section
The oscillator center is approximately the resonance of the
inductor L2 from Pin 2 to Pin 3 and the effective capacitance
C3 from Pin 3 to ground. For overall oscillator stability, it is
best to keep XL in the range of 300 Ω to 1.0 kΩ.
The modulator transfer characteristic at 4.5 MHz is shown
in Figure 15. Transfer curves at other frequencies have a very
similar shape, but differ in deviation per input volt, as shown in
Figures 13 and 17.
Most applications will not require DC connection to the
audio input, Pin 14. However, some improvements can be
achieved by the addition of biasing circuitry. The unaided
device will establish its own Pin 14 bias at 4 θ, or about 3.0 V.
This bias is a little too high for optimum modulation linearity.
Figure 14 shows better than 2 to 1 improvement in distortion
between the unaided device and pulling Pin 14 down to 2.6 V
to 2.7 V. This can be accomplished by a simple divider, if the
supply voltage is relatively constant.
The impedance of the divider has a bearing on the
frequency versus temperature stability of the FM system. A
divider of 180 kΩ and 30 kΩ (for VCC = 12 V) will give good
temperature stabilization results. However, as Figure 18
shows, a divider is not a good method if the supply voltage
varies. The designer must make the decisions here, based
on considerations of economy, distortion and temperature
requirements and power supply capability. If the distortion
requirements are not stringent, then no bias components are
needed. If, in this case, the temperature compensation needs
to be improved in the high ambient area, the tuning capacitor
from Pin 3 to ground can be selected from N75 or N150
temperature compensation types.
Another reason for DC input to Pin 14 is the possibility of
automatic frequency control. Where high accuracy of
inter–carrier frequency is required, it may be desirable to feed
back the DC output of an AFC or phase detector for nominal
carrier frequency control. Only limited control range could be
used without adversely affecting the distortion performance,
but very little frequency compensation will be needed.
One added convenience in the FM section is the separate
Pin “oscillator B+” which permits disabling of the sound
system during alignment of the AM section. Usually it can be
hard wired to the VCC source without decoupling.
Standard practice in television is to provide pre–emphasis
of higher audio frequencies at the transmitter and a matching
de–emphasis in the TV receiver audio amplifier. The purpose
of this is to counteract the fact that less energy is usually
present in the higher frequencies, and also that fewer
modulation sidebands are within the deviation window. Both
factors degrade signal to noise ration. Pre–emphasis of 75 µs
is standard practice. For cases where it has not been
provided, a suitable pre–emphasis network is covered in
Figure 20.
It would seem natural to take the FM system output from
Pin 2, the emitter follower output, but this output is high in
harmonic content. Taking the output from Pin 3 sacrifices
somewhat in source impedance but results in a clean output
fundamental, with all harmonics more than 40 dB down. This
choice removes the need for additional filtering components.
1.8
1.6
TA = 25°C
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
1.4
2.0
3.0
4.0 5.0 6.0 7.0 8.0 9.0 10
fosc, OSCILLATOR FREQUENCY [MHz]
14
MOTOROLA ANALOG IC DEVICE DATA
MC1374
Figure 14. Distortion versus Modulation Depth
5.0
TA = 25°C
(1.76 MHz)
2.0
VCC = 12 V
TA = 25°C
fc = 4.5 MHz
VCC = 12 V
4.0
1.9
VCC = 5.0 V, 9.0 V
DISTORTION (%)
fosc , OSCILLATOR FREQUENCY (MHz)
Figure 13. Modulator Transfer Function
2.1
1.8
1.7
1.6
1.5
3.0
Self Bias (2.9–3.0 V)
2.0
Optimum Bias (2.6–2.7 V)
1.0
1.4
1.3
0
0
1.0
2.0
3.0
4.0
5.0
DC INPUT VOLTAGE, PIN 14 (V)
6.0
7.0
0
25
VCC = 12 V
4.54
VCC = 5.0 V, 9.0 V
4.53
f, FREQUENCY (MHz)
fosc , OSCILLATOR FREQUENCY (MHz)
4.7
4.6
4.5
4.4
4.3
VCC = 12 V
Pin 14 V to 2.6 V
4.52
4.51
180 k/30 k Divider
4.50
4.49
Pin 14 Open
4.48
4.2
4.1
0
1.0
2.0
3.0
4.0
5.0
DC INPUT VOLTAGE, PIN 14 (V)
6.0
4.47
7.0
0
11.6
TA = 25°C
(10.7 MHz)
11.4
25
50
75
TA, AMBIENT TEMPERATURE (°C)
4.50
12 V
9.0 V VCC
5.0 V
Pin 14 to 2.6 V Source
4.49
11.2
11.0
10.8
10.6
10.4
10.2
10.0
4.48
Pin 14 Open
4.47
4.46
Pin14 – 180 k/ 30 k Divider
4.45
4.44
TA = 25°C
4.43
9.8
0
1.0
2.0
3.0
4.0
5.0
DC INPUT VOLTAGE, PIN 14 (V)
MOTOROLA ANALOG IC DEVICE DATA
6.0
100
Figure 18. FM System Frequency versus VCC
f, FREQUENCY (MHz)
fosc , OSCILLATOR FREQUENCY (MHz)
Figure 17. Modulator Transfer Function
9.6
100
4.55
TA = 25°C
(4.5 MHz)
4.8
75
Figure 16. FM System Frequency
versus Temperature
Figure 15. Modulator Transfer Function
4.9
50
DEVIATION (kHz)
7.0
4.42
4.0
5.0
6.0
7.0
8.0
9.0
10
VCC, SUPPLY VOLTAGE (Vdc)
11
12
7
MC1374
Figure 19. A Channel 4 Vestigial Sideband Filter
VCC
8
RL = 75Ω
8.2pF
24Ω
2.7k
Both transformer windings
4T #23 AWG
close wound on 1/4″ ID
on common axis, 3/8″ spacing.
39
pF
33pF
8.2pF 24Ω
33pF
33pF
24Ω
ATTENUATION (dB)
9
Output
75Ω
0
–10
–20
–30
–40
–50
–60
–70
Ch. 4
Pix
61
100Ω
8T #23 AWG
close wound on 1/8″ ID,
knife tuned to trap Channel 3
61.25 MHz.
Ch. 4
S
65
69
73
f, FREQUENCY (MHz)
RELATIVE OUTPUT/INPUT (dB)
Figure 20. Audio Pre–Emphasis Circuit
C = 0.0012µF
CC = 0.1µF
– +
“Flat”
Audio
Input
14
r = 56kΩ
R
6.0kΩ
Audio
Input
5
Gnd
1
2 π RC
25
20
15
10
5
1
2 π (r + R)CC
1
2 π rC
0
–5
21
210
2100
21k
f, FREQUENCY (MHz)
Pre–emphasis = 75 µs = rC =
1
2 π (2100 Hz)
Figure 21. Crystal Controlled RF Oscillator
for Channel 3, 61.25 MHz
VCC
R1
C1
0.001
R2
470
470
61.252
MHz
R3
56pF
Ra
180
470
C2
L1
0.15µH
Rb
6
18
7
MC1374
NOTE: See Application Note AN829 for further information.
8
MOTOROLA ANALOG IC DEVICE DATA
MC1374
OUTLINE DIMENSIONS
P SUFFIX
PLASTIC PACKAGE
CASE 646–06
ISSUE L
14
8
1
7
B
NOTES:
1. LEADS WITHIN 0.13 (0.005) RADIUS OF TRUE
POSITION AT SEATING PLANE AT MAXIMUM
MATERIAL CONDITION.
2. DIMENSION L TO CENTER OF LEADS WHEN
FORMED PARALLEL.
3. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.
4. ROUNDED CORNERS OPTIONAL.
A
F
L
C
J
N
H
G
D
SEATING
PLANE
MOTOROLA ANALOG IC DEVICE DATA
K
M
DIM
A
B
C
D
F
G
H
J
K
L
M
N
INCHES
MIN
MAX
0.715
0.770
0.240
0.260
0.145
0.185
0.015
0.021
0.040
0.070
0.100 BSC
0.052
0.095
0.008
0.015
0.115
0.135
0.300 BSC
0_
10_
0.015
0.039
MILLIMETERS
MIN
MAX
18.16
19.56
6.10
6.60
3.69
4.69
0.38
0.53
1.02
1.78
2.54 BSC
1.32
2.41
0.20
0.38
2.92
3.43
7.62 BSC
0_
10_
0.39
1.01
9
MC1374
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola
was negligent regarding the design or manufacture of the part. Motorola and
are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.
How to reach us:
USA / EUROPE / Locations Not Listed: Motorola Literature Distribution;
P.O. Box 20912; Phoenix, Arizona 85036. 1–800–441–2447 or 602–303–5454
JAPAN: Nippon Motorola Ltd.; Tatsumi–SPD–JLDC, 6F Seibu–Butsuryu–Center,
3–14–2 Tatsumi Koto–Ku, Tokyo 135, Japan. 03–81–3521–8315
MFAX: [email protected] – TOUCHTONE 602–244–6609
INTERNET: http://Design–NET.com
ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park,
51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298
10
◊
*MC1374/D*
MOTOROLA ANALOG IC DEVICE
DATA
MC1374/D