AD AD8602ARM-REEL Precision cmos single-supply rail-to-rail input/output wideband operational amplifier Datasheet

Precision CMOS Single-Supply
Rail-to-Rail Input/Output Wideband
Operational Amplifiers
AD8601/AD8602/AD8604
FEATURES
Low Offset Voltage: 500 ␮V Max
Single-Supply Operation: 2.7 V to 5.5 V
Low Supply Current: 750 ␮A/Amplifier
Wide Bandwidth: 8 MHz
Slew Rate: 5 V/␮s
Low Distortion
No Phase Reversal
Low Input Currents
Unity Gain Stable
APPLICATIONS
Current Sensing
Barcode Scanners
PA Controls
Battery-Powered Instrumentation
Multipole Filters
Sensors
ASIC Input or Output Amplifiers
Audio
GENERAL DESCRIPTION
The AD8601, AD8602, and AD8604 are single, dual, and quad
rail-to-rail input and output single-supply amplifiers featuring very
low offset voltage and wide signal bandwidth. These amplifiers
use a new, patented trimming technique that achieves superior
performance without laser trimming. All are fully specified to
operate on a 3 V to 5 V single supply.
The combination of low offsets, very low input bias currents,
and high speed make these amplifiers useful in a wide variety of
applications. Filters, integrators, diode amplifiers, shunt current
sensors, and high impedance sensors all benefit from the combination of performance features. Audio and other ac applications
benefit from the wide bandwidth and low distortion. For the
most cost-sensitive applications, the D grades offer this ac performance with lower dc precision at a lower price point.
Applications for these amplifiers include audio amplification for
portable devices, portable phone headsets, bar code scanners,
portable instruments, cellular PA controls, and multipole filters.
The ability to swing rail-to-rail at both the input and output
enables designers to buffer CMOS ADCs, DACs, ASICs, and
other wide output swing devices in single-supply systems.
FUNCTIONAL BLOCK DIAGRAM
14-Lead TSSOP
(RU Suffix)
OUT A 1
5-Lead SOT-23
(RT Suffix)
14
OUT D
OUT A 1
2
13
ⴚIN D
Vⴚ 2
ⴙIN A 3
12
ⴙIN D
ⴚIN A
Vⴙ 4
AD8604
11
Vⴚ
ⴙIN B 5
10
ⴙIN C
ⴚIN B
6
9
ⴚIN C
OUT B 7
8
OUT C
14-Lead SOIC
(R Suffix)
OUT A 1
14 OUT D
ⴚIN A 2
13 ⴚIN D
ⴙIN A 3
Vⴙ 4
5 Vⴙ
AD8601
ⴙIN 3
4 ⴚIN
8-Lead MSOP
(RM Suffix)
OUT A 1
8
Vⴙ
7
OUT B
ⴙIN A 3
6
ⴚIN B
Vⴚ 4
5
ⴙIN B
ⴚIN A
2
AD8602
12 ⴙIN D
AD8604
11 Vⴚ
ⴙIN B 5
10 ⴙIN C
ⴚIN B 6
9
ⴚIN C
OUT B 7
8
OUT C
8-Lead SOIC
(R Suffix)
OUT A 1
ⴚIN A 2
ⴙIN A 3
Vⴚ 4
8 Vⴙ
AD8602
7 OUT B
6 ⴚIN B
5 ⴙIN B
The AD8601, AD8602, and AD8604 are specified over the
extended industrial (–40°C to +125°C) temperature range. The
AD8601, single, is available in the tiny 5-lead SOT-23 package.
The AD8602, dual, is available in 8-lead MSOP and narrow
SOIC surface-mount packages. The AD8604, quad, is available
in 14-lead TSSOP and narrow SOIC packages.
SOT, MSOP, and TSSOP versions are available in tape and
reel only.
REV. D
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties that
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
www.analog.com
Fax: 781/326-8703
© 2003 Analog Devices, Inc. All rights reserved.
AD8601/AD8602/AD8604–SPECIFICATIONS
ELECTRICAL CHARACTERISTICS
Parameter
Symbol
INPUT CHARACTERISTICS
Offset Voltage (AD8601/AD8602) VOS
Offset Voltage (AD8604)
Input Bias Current
Input Offset Current
VOS
IB
IOS
Input Voltage Range
Common-Mode Rejection Ratio
Large Signal Voltage Gain
CMRR
AVO
Offset Voltage Drift
∆VOS/∆T
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
Output Voltage Low
VOL
Output Current
Closed-Loop Output Impedance
IOUT
ZOUT
(VS = 3 V, VCM = VS/2, TA = 25ⴗC, unless otherwise noted.)
Conditions
Min
0 V ≤ VCM ≤ 1.3 V
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
0 V ≤ VCM ≤ 3 V*
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 1.3 V
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 3.0 V*
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
A Grade
Typ
Max
80
350
80
350
0.2
25
150
0.1
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 3 V
VO = 0.5 V to 2.5 V,
RL = 2 kΩ , VCM = 0 V
IL = 1.0 mA
–40°C ≤ TA ≤ +125°C
IL = 1.0 mA
–40°C ≤ TA ≤ +125°C
0
68
500
700
1,100
750
1,800
2,100
600
800
1,600
800
2,200
2,400
60
100
1,000
30
50
500
3
83
Min
D Grade
Typ
Max
65
µV
µV
µV
µV
µV
µV
µV
µV
µV
µV
µV
µV
pA
pA
pA
pA
pA
pA
V
dB
1,100
1,300
1,100
1,300
0.2
25
150
0.1
0
52
Unit
6,000
7,000
7,000
6,000
7,000
7,000
6,000
7,000
7,000
6,000
7,000
7,000
200
200
1,000
100
100
500
3
30
100
2
20
60
2
V/mV
µV/°C
2.92
2.88
2.95
2.92
2.88
2.95
V
V
mV
mV
mA
Ω
20
35
50
20
± 30
12
f = 1 MHz, AV = 1
± 30
12
35
50
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
PSRR
ISY
VS = 2.7 V to 5.5 V
VO = 0 V
–40°C ≤ TA ≤ +125°C
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Gain Bandwidth Product
Phase Margin
SR
tS
GBP
⌽o
RL = 2 kΩ
To 0.01%
5.2
<0.5
8.2
50
5.2
<0.5
8.2
50
V/µs
µs
MHz
Degrees
en
en
in
f = 1 kHz
f = 10 kHz
33
18
0.05
33
18
0.05
nV/√Hz
nV/√Hz
pA/√Hz
NOISE PERFORMANCE
Voltage Noise Density
Current Noise Density
67
80
680
56
1,000
1,300
72
680
dB
1,000 µA
1,300 µA
*For VCM between 1.3 V and 1.8 V, V OS may exceed specified value.
Specifications subject to change without notice.
–2–
REV. D
AD8601/AD8602/AD8604
ELECTRICAL CHARACTERISTICS
Parameter
Symbol
INPUT CHARACTERISTICS
Offset Voltage (AD8601/AD8602) VOS
Offset Voltage (AD8604)
VOS
Input Bias Current
IB
Input Offset Current
IOS
Input Voltage Range
Common-Mode Rejection Ratio
Large Signal Voltage Gain
CMRR
AVO
Offset Voltage Drift
∆VOS/∆T
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
(VS = 5.0 V, VCM = VS/2, TA = 25ⴗC, unless otherwise noted.)
Conditions
Min
0 V ≤ VCM ≤ 5 V
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 5 V
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 5 V
VO = 0.5 V to 4.5 V,
RL = 2 kΩ, VCM = 0 V
IL = 1.0 mA
IL = 10 mA
–40°C ≤ TA ≤ +125°C
IL = 1.0 mA
IL = 10 mA
–40°C ≤ TA ≤ +125°C
f = 1 MHz, AV = 1
PSRR
ISY
VS = 2.7 V to 5.5 V
VO = 0 V
NOISE PERFORMANCE
Voltage Noise Density
Current Noise Density
89
80
4.925
4.7
4.6
4.975
4.77
15
125
67
80
750
RL = 2 kΩ
To 0.01%
< 1% Distortion
⌽o
67
60
2
µV/°C
4.975
4.77
± 50
10
V
V
V
mV
mV
mV
mA
Ω
72
750
dB
1,200 µA
0.2
0.1
6
25
0
56
20
30
175
250
15
125
56
6,000
7,000
6,000
7,000
200
200
1,000
100
100
500
5
30
175
250
1,500 µA
1,500
6
<1.0
360
8.4
6
<1.0
360
8.4
V/µs
µs
kHz
MHz
55
55
Degrees
nV/√Hz
nV/√Hz
pA/√Hz
en
en
f = 1 kHz
f = 10 kHz
33
18
33
18
in
f = 1 kHz
0.05
0.05
–3–
Unit
µV
µV
µV
µV
pA
pA
pA
pA
pA
pA
V
dB
V/mV
1,300
4.925
4.7
4.6
1,200
D Grade
Typ
Max
1,300
± 50
10
–40°C ≤ TA ≤ +125°C
Specifications subject to change without notice.
REV. D
0
74
30
500
1,300
600
1,700
60
100
1,000
30
50
500
5
Min
2
IOUT
ZOUT
Phase Margin
0.1
6
25
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
Output Current
Closed-Loop Output Impedance
SR
tS
BWp
GBP
80
0.2
VOL
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Full Power Bandwidth
Gain Bandwidth Product
80
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
Output Voltage Low
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
A Grade
Typ
Max
AD8601/AD8602/AD8604
ABSOLUTE MAXIMUM RATINGS*
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VS
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . ± 6 V
Storage Temperature Range
R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
AD8601/AD8602/AD8604 . . . . . . . . . . . . –40°C to +125°C
Junction Temperature Range
R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
ESD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 kV HBM
Package Type
␪JA*
␪JC
Unit
5-Lead SOT-23 (RT)
8-Lead SOIC (R)
8-Lead MSOP (RM)
14-Lead SOIC (R)
14-Lead TSSOP (RU)
230
158
210
120
180
92
43
45
36
35
°C/W
°C/W
°C/W
°C/W
°C/W
*␪JA is specified for worst-case conditions, i.e., ␪JA is specified for device in
socket for PDIP packages; ␪JA is specified for device soldered onto a circuit
board for surface-mount packages.
*Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
ORDERING GUIDE
Model
Temperature
Range
Package
Description
Package
Option
AD8601ART-R2
AD8601ART-REEL
AD8601ART-REEL7
AD8601DRT-R2
AD8601DRT-REEL
AD8601DRT-REEL7
AD8602AR
AD8602AR-REEL7
AD8602AR-R2
AD8602DR
AD8602DR-REEL
AD8602DR-REEL7
AD8602ARM-R2
AD8602ARM-REEL
AD8602DRM-REEL
AD8604AR
AD8604AR-REEL
AD8604AR-REEL7
AD8604DR
AD8604DR-REEL
AD8604ARU
AD8604ARU-REEL
AD8604DRU
AD8604DRU-REEL
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead TSSOP
14-Lead TSSOP
14-Lead TSSOP
14-Lead TSSOP
RT-5
RT-5
RT-5
RT-5
RT-5
RT-5
R-8
R-8
R-8
R-8
R-8
R-8
RM-8
RM-8
RM-8
R-14
R-14
R-14
R-14
R-14
RU-14
RU-14
RU-14
RU-14
Branding
AAA
AAA
AAA
AAD
AAD
AAD
ABA
ABA
ABD
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although the
AD8601/AD8602/AD8604 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
–4–
REV. D
Typical Performance Characteristics– AD8601/AD8602/AD8604
60
3,000
50
QUANTITY – Amplifiers
2,500
QUANTITY – Amplifiers
VS = 5V
TA = 25ⴗC TO 85ⴗC
VS = 3V
TA = 25ⴗC
VCM = 0V TO 3V
2,000
1,500
1,000
0
ⴚ1.0
0
ⴚ0.8 ⴚ0.6 ⴚ0.4 ⴚ0.2
0.2
0.4
0.6
INPUT OFFSET VOLTAGE – mV
0
1.0
1.5
VS = 5V
TA = 25ⴗC
VCM = 0V TO 5V
2
3
4
5
6
TCVOS – ␮V/ⴗC
7
8
9
10
VS = 3V
TA = 25ⴗC
1.0
INPUT OFFSET VOLTAGE – mV
2,500
1
TPC 4. Input Offset Voltage Drift Distribution
3,000
QUANTITY – Amplifiers
20
0
0.8
TPC 1. Input Offset Voltage Distribution
2,000
1,500
1,000
500
0.5
0
ⴚ0.5
ⴚ1.0
ⴚ1.5
0
ⴚ1.0
0
ⴚ0.8 ⴚ0.6 ⴚ0.4 ⴚ0.2
0.2
0.4
0.6
INPUT OFFSET VOLTAGE – mV
ⴚ2.0
0.8
1.0
TPC 2. Input Offset Voltage Distribution
0
1.0
1.5
2.0
COMMON-MODE VOLTAGE – V
0.5
2.5
3.0
TPC 5. Input Offset Voltage vs. Common-Mode Voltage
1.5
60
VS = 3V
TA = 25ⴗC TO 85ⴗC
VS = 5V
TA = 25ⴗC
1.0
INPUT OFFSET VOLTAGE – mV
50
QUANTITY – Amplifiers
30
10
500
40
30
20
10
0.5
0
ⴚ0.5
ⴚ1.0
ⴚ1.5
ⴚ2.0
0
0
1
2
3
4
5
6
TCVOS – ␮V/ⴗC
7
8
9
10
0
1
2
3
COMMON-MODE VOLTAGE – V
4
5
TPC 6. Input Offset Voltage vs. Common-Mode Voltage
TPC 3. Input Offset Voltage Drift Distribution
REV. D
40
–5–
AD8601/AD8602/AD8604
300
30
VS = 3V
VS = 3V
INPUT OFFSET CURRENT – pA
INPUT BIAS CURRENT – pA
250
200
150
100
50
25
20
15
10
5
0
ⴚ40 ⴚ25 ⴚ10
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
0
ⴚ40 ⴚ25 ⴚ10
125
TPC 7. Input Bias Current vs. Temperature
80
95
110
125
30
VS = 5V
VS = 5V
INPUT OFFSET CURRENT – pA
250
INPUT BIAS CURRENT – pA
20
35
50
65
TEMPERATURE – ⴗC
TPC 10. Input Offset Current vs. Temperature
300
200
150
100
50
25
20
15
10
5
0
ⴚ40 ⴚ25 ⴚ10
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
0
ⴚ40 ⴚ25 ⴚ10
125
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
125
TPC 8. Input Bias Current vs. Temperature
TPC 11. Input Offset Current vs. Temperature
5
10k
VS = 2.7V
TA = 25ⴗC
VS = 5V
TA = 25ⴗC
4
1k
OUTPUT VOLTAGE – mV
INPUT BIAS CURRENT – pA
5
3
2
1
100
SOURCE
SINK
10
1
0
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
COMMON-MODE VOLTAGE – V
4.5
0.1
0.001
5.0
TPC 9. Input Bias Current vs. Common-Mode Voltage
0.01
0.1
1
LOAD CURRENT – mA
10
100
TPC 12. Output Voltage to Supply Rail vs. Load Current
–6–
REV. D
AD8601/AD8602/AD8604
10k
35
VS = 5V
TA = 25ⴗC
VS = 2.7V
30
OUTPUT VOLTAGE – mV
OUTPUT VOLTAGE – mV
1k
SOURCE
100
SINK
10
25
VOL @ 1mA LOAD
20
15
10
1
5
0.1
0.001
0.1
1
LOAD CURRENT – mA
0.01
10
0
ⴚ40 ⴚ25 ⴚ10
100
TPC 13. Output Voltage to Supply Rail vs. Load Current
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
125
TPC 16. Output Voltage Swing vs. Temperature
5.1
2.67
VS = 5V
VS = 2.7V
5.0
2.66
VOH @ 1mA LOAD
OUTPUT VOLTAGE – V
OUTPUT VOLTAGE – V
5
4.9
4.8
VOH @ 10mA LOAD
4.7
2.65
VOH @ 1mA LOAD
2.64
2.63
4.6
4.5
ⴚ40 ⴚ25 ⴚ10
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
2.62
ⴚ40 ⴚ25 ⴚ10
125
TPC 14. Output Voltage Swing vs. Temperature
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
125
TPC 17. Output Voltage Swing vs. Temperature
250
VS = 5V
100
150
VOL @ 10mA LOAD
100
45
40
90
20
135
0
180
–20
–40
50
VOL @ 1mA LOAD
0
ⴚ40 ⴚ25 ⴚ10
5
20
35
50
65
TEMPERATURE – ⴗC
–60
80
95
110
125
1k
TPC 15. Output Voltage Swing vs. Temperature
REV. D
60
PHASE SHIFT – Degrees
80
GAIN – dB
OUTPUT VOLTAGE – mV
200
VS = 3V
RL = NO LOAD
TA = 25ⴗC
10k
100k
1M
FREQUENCY – Hz
10M
100M
TPC 18. Open-Loop Gain and Phase vs. Frequency
–7–
AD8601/AD8602/AD8604
3.0
VS = 5V
RL = NO LOAD
TA = 25ⴗC
2.5
60
45
40
90
20
135
0
180
–20
OUTPUT SWING – V p-p
GAIN – dB
80
PHASE SHIFT – Degrees
100
–40
2.0
VS = 2.7V
VIN = 2.6V p-p
RL = 2k⍀
TA = 25ⴗC
AV = 1
1.5
1.0
0.5
–60
1k
10k
100k
1M
FREQUENCY – Hz
10M
0
1k
100M
TPC 19. Open-Loop Gain and Phase vs. Frequency
10k
100k
FREQUENCY – Hz
1M
10M
TPC 22. Closed-Loop Output Voltage Swing vs. Frequency
6
CLOSED-LOOP GAIN – dB
40
AV = 100
5
OUTPUT SWING – V p-p
VS = 3V
TA = 25ⴗC
AV = 10
20
AV = 1
0
4
3
VS = 5V
VIN = 4.9V p-p
RL = 2k⍀
TA = 25ⴗC
AV = 1
2
1
1k
100k
1M
FREQUENCY – Hz
10k
10M
0
1k
100M
TPC 20. Closed-Loop Gain vs. Frequency
10k
100k
FREQUENCY – Hz
1M
10M
TPC 23. Closed-Loop Output Voltage Swing vs. Frequency
200
CLOSED-LOOP GAIN – dB
40
180
AV = 100
AV = 10
20
AV = 1
0
VS = 3V
TA = 25ⴗC
160
OUTPUT IMPEDANCE – ⍀
VS = 5V
TA = 25ⴗC
140
AV = 100
120
100
AV = 10
80
AV = 1
60
40
20
1k
10k
100k
1M
FREQUENCY – Hz
10M
0
100
100M
TPC 21. Closed-Loop Gain vs. Frequency
1k
10k
100k
FREQUENCY – Hz
1M
10M
TPC 24. Output Impedance vs. Frequency
–8–
REV. D
AD8601/AD8602/AD8604
160
200
VS = 5V
TA = 25ⴗC
140
POWER SUPPLY REJECTION – dB
180
OUTPUT IMPEDANCE – ⍀
160
140
120
AV = 100
100
AV = 10
80
AV = 1
60
40
120
100
80
60
40
20
0
ⴚ20
20
0
100
1k
10k
100k
FREQUENCY – Hz
1M
ⴚ40
100
10M
TPC 25. Output Impedance vs. Frequency
SMALL SIGNAL OVERSHOOT – %
COMMON-MODE REJECTION – dB
60
100
80
60
40
20
0
ⴚ20
1k
10k
100k
FREQUENCY – Hz
1M
50
ⴚOS
40
30
+OS
20
10
100
CAPACITANCE – pF
1k
70
VS = 5V
TA = 25ⴗC
140
60
120
SMALL SIGNAL OVERSHOOT – %
COMMON-MODE REJECTION – dB
10M
TPC 29. Small Signal Overshoot vs. Load Capacitance
160
100
80
60
40
20
0
ⴚ20
50
VS = 5V
RL =
TA = 25ⴗC
AV = 1
40
30
20
ⴚOS
10
+OS
1k
10k
100k
FREQUENCY – Hz
1M
0
10
10M 20M
TPC 27. Common-Mode Rejection Ratio vs. Frequency
REV. D
1M
VS = 2.7V
RL =
TA = 25ⴗC
AV = 1
0
10
10M 20M
TPC 26. Common-Mode Rejection Ratio vs. Frequency
ⴚ40
10k
100k
FREQUENCY – Hz
70
VS = 3V
TA = 25ⴗC
120
ⴚ40
1k
TPC 28. Power Supply Rejection Ratio vs. Frequency
160
140
VS = 5V
TA = 25ⴗC
100
CAPACITANCE – pF
1k
TPC 30. Small Signal Overshoot vs. Load Capacitance
–9–
AD8601/AD8602/AD8604
0.1
VS = 5V
TA = 25ⴗC
VS = 5V
RL = 10k⍀
0.01
0.8
0.6
RL = 600⍀
RL = 2k⍀
G=1
RL = 10k⍀
0.001
0.4
0.2
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
0.0001
125
100
20
1k
FREQUENCY – Hz
10k
20k
TPC 34. Total Harmonic Distortion + Noise vs. Frequency
TPC 31. Supply Current per Amplifier vs. Temperature
1.0
64
VS = 3V
VOLTAGE NOISE DENSITY – nV/ Hz
SUPPLY CURRENT PER AMPLIFIER – mA
RL = 2k⍀
G = 10
0
ⴚ40 ⴚ25 ⴚ10
0.8
0.6
0.4
0.2
VS = 2.7V
TA = 25ⴗC
56
48
40
32
24
16
8
0
ⴚ40 ⴚ25 ⴚ10
5
20
35
50
65
TEMPERATURE – ⴗC
80
95
110
0
125
TPC 32. Supply Current per Amplifier vs. Temperature
0.8
208
0.7
182
0.6
0.5
0.4
0.3
0.2
5
10
15
FREQUENCY – kHz
20
25
VS = 2.7V
TA = 25ⴗC
156
130
104
78
52
26
0.1
0
0
TPC 35. Voltage Noise Density vs. Frequency
VOLTAGE NOISE DENSITY – nV/ Hz
SUPPLY CURRENT PER AMPLIFIER – mA
RL = 600⍀
1.0
THD + N – %
SUPPLY CURRENT PER AMPLIFIER – mA
1.2
0
0
1
2
3
4
SUPPLY VOLTAGE – V
5
6
TPC 33. Supply Current per Amplifier vs. Supply Voltage
0
0.5
1.0
1.5
FREQUENCY – kHz
2.0
2.5
TPC 36. Voltage Noise Density vs. Frequency
–10–
REV. D
AD8601/AD8602/AD8604
VS = 5V
TA = 25ⴗC
VS = 5V
TA = 25ⴗC
182
156
VOLTAGE – 2.5␮V/DIV
VOLTAGE NOISE DENSITY – nV/ Hz
208
130
104
78
52
26
0
0
0.5
1.0
1.5
FREQUENCY – kHz
2.0
2.5
TIME – 1s/DIV
TPC 37. Voltage Noise Density vs. Frequency
TPC 40. 0.1 Hz to 10 Hz Input Voltage Noise
64
VOLTAGE NOISE DENSITY – nV/ Hz
VS = 5V
RL = 10k⍀
CL = 200pF
TA = 25ⴗC
VS = 5V
TA = 25ⴗC
56
48
40
32
24
16
8
50.0mV/DIV
0
0
5
10
15
FREQUENCY – kHz
20
200ns/DIV
25
TPC 38. Voltage Noise Density vs. Frequency
TPC 41. Small Signal Transient Response
VS = 2.7V
RL = 10k⍀
CL = 200pF
TA = 25ⴗC
VOLTAGE – 2.5␮V/DIV
VS = 2.7V
TA = 25ⴗC
50.0mV/DIV
200ns/DIV
TIME – 1s/DIV
TPC 39. 0.1 Hz to 10 Hz Input Voltage Noise
REV. D
TPC 42. Small Signal Transient Response
–11–
VS = 5V
RL = 10k⍀
CL = 200pF
AV = 1
TA = 25ⴗC
VIN
VOLTAGE – 1V/DIV
VOLTAGE – 1.0V/DIV
AD8601/AD8602/AD8604
VOUT
TIME – 400ns/DIV
TIME – 2.0␮s/DIV
TPC 43. Large Signal Transient Response
TPC 46. No Phase Reversal
VS = 2.7V
RL = 10k⍀
CL = 200pF
AV = 1
TA = 25ⴗC
VS = 5V
RL = 10k⍀
VO = 2V p-p
TA = 25ⴗC
VOLTAGE – V
VOLTAGE – 500mV/DIV
VS = 5V
RL = 10k⍀
AV = 1
TA = 25ⴗC
VIN
+0.1%
ERROR
VOUT
ⴚ0.1%
ERROR
VIN TRACE – 0.5V/DIV
VOUT TRACE – 10mV/DIV
TIME – 100ns/DIV
TIME – 400ns/DIV
TPC 44. Large Signal Transient Response
TPC 47. Settling Time
2.0
VS = 2.7V
TA = 25ⴗC
1.5
1.0
OUTPUT SWING – V
VOLTAGE – 1V/DIV
VIN
VS = 2.7V
RL = 10k⍀
AV = 1
TA = 25ⴗC
VOUT
0.1%
0.01%
0.5
0
ⴚ0.5
0.1%
ⴚ1.0
0.01%
ⴚ1.5
ⴚ2.0
300
TIME – 2.0␮s/DIV
350
400
450
500
550
600
SETTLING TIME – ns
TPC 45. No Phase Reversal
TPC 48. Output Swing vs. Settling Time
–12–
REV. D
AD8601/AD8602/AD8604
Rail-to-Rail Input Stage
5
The input common-mode voltage range of the AD860x extends
to both positive and negative supply voltages. This maximizes the
usable voltage range of the amplifier, an important feature for
single-supply and low voltage applications. This rail-to-rail
input range is achieved by using two input differential pairs, one
NMOS and one PMOS, placed in parallel. The NMOS pair is
active at the upper end of the common-mode voltage range, and
the PMOS pair is active at the lower end.
OUTPUT SWING – V
3
2
1
0.1%
0.01%
0
0.1%
ⴚ1
0.01%
ⴚ2
ⴚ3
ⴚ4
ⴚ5
0
200
400
600
800
1,000
SETTLING TIME – ns
TPC 49. Output Swing vs. Settling Time
THEORY OF OPERATION
The AD8601/AD8602/AD8604 family of amplifiers are rail-torail input and output precision CMOS amplifiers that operate
from 2.7 V to 5.0 V of power supply voltage. These amplifiers
use Analog Devices’ DigiTrim® technology to achieve a higher
degree of precision than available from most CMOS amplifiers.
DigiTrim technology is a method of trimming the offset voltage of the amplifier after it has already been assembled. The
advantage in post-package trimming lies in the fact that it corrects any offset voltages due to the mechanical stresses of
assembly. This technology is scalable and used with every
package option, including SOT-23-5, providing lower offset
voltages than previously achieved in these small packages.
The NMOS and PMOS input stages are separately trimmed
using DigiTrim to minimize the offset voltage in both differential pairs. Both NMOS and PMOS input differential pairs are
active in a 500 mV transition region, when the input commonmode voltage is between approximately 1.5 V and 1 V below the
positive supply voltage. Input offset voltage will shift slightly in
this transition region, as shown in TPCs 5 and 6. Commonmode rejection ratio will also be slightly lower when the input
common-mode voltage is within this transition band. Compared
to the Burr Brown OPA2340 rail-to-rail input amplifier, shown
in Figure 1, the AD860x, shown in Figure 2, exhibits lower
offset voltage shift across the entire input common-mode range,
including the transition region.
The DigiTrim process is done at the factory and does not add
additional pins to the amplifier. All AD860x amplifiers are
available in standard op amp pinouts, making DigiTrim completely transparent to the user. The AD860x can be used in any
precision op amp application.
0.7
0.4
0.1
ⴚ0.2
ⴚ0.5
ⴚ0.8
ⴚ1.1
The input stage of the amplifier is a true rail-to-rail architecture,
allowing the input common-mode voltage range of the op amp
to extend to both positive and negative supply rails. The voltage
swing of the output stage is also rail-to-rail and is achieved by
using an NMOS and PMOS transistor pair connected in a common-source configuration. The maximum output voltage swing
is proportional to the output current, and larger currents will
limit how close the output voltage can get to the supply rail.
This is a characteristic of all rail-to-rail output amplifiers. With
1 mA of output current, the output voltage can reach within
20 mV of the positive rail and within 15 mV of the negative rail.
At light loads of >100 kΩ, the output swings within ~1 mV of
the supplies.
The open-loop gain of the AD860x is 80 dB, typical, with a load
of 2 kΩ. Because of the rail-to-rail output configuration, the
gain of the output stage and the open-loop gain of the amplifier
are dependent on the load resistance. Open-loop gain will decrease with smaller load resistances. Again, this is a characteristic
inherent to all rail-to-rail output amplifiers.
ⴚ1.4
0
1
2
3
4
5
VCM – V
Figure 1. Burr Brown OPA2340UR Input Offset
Voltage vs. Common-Mode Voltage, 24 SOIC
Units @ 25°C
0.7
0.4
0.1
VOS – mV
4
VOS – mV
VS = 5V
TA = 25ⴗC
ⴚ0.2
ⴚ0.5
ⴚ0.8
ⴚ1.1
ⴚ1.4
0
1
2
3
4
5
VCM – V
Figure 2. AD8602AR Input Offset Voltage vs.
Common-Mode Voltage, 300 SOIC Units @ 25°C
REV. D
–13–
AD8601/AD8602/AD8604
Input Overvoltage Protection
10pF
(OPTIONAL)
As with any semiconductor device, if a condition could exist
that would cause the input voltage to exceed the power supply,
the device’s input overvoltage characteristic must be considered.
Excess input voltage will energize internal PN junctions in the
AD860x, allowing current to flow from the input to the supplies.
4.7M⍀
VOUT
4.7V/␮A
D1
AD8601
This input current will not damage the amplifier, provided it is
limited to 5 mA or less. This can be ensured by placing a resistor in series with the input. For example, if the input voltage
could exceed the supply by 5 V, the series resistor should be at
least (5 V/5 mA) = 1 kΩ. With the input voltage within the
supply rails, a minimal amount of current is drawn into the
inputs, which, in turn, causes a negligible voltage drop across
the series resistor. Therefore, adding the series resistor will
not adversely affect circuit performance.
Figure 3. Amplifier Photodiode Circuit
High- and Low-Side Precision Current Monitoring
Overdrive Recovery
Overdrive recovery is defined as the time it takes the output of
an amplifier to come off the supply rail when recovering from
an overload signal. This is tested by placing the amplifier in a
closed-loop gain of 10 with an input square wave of 2 V p-p while
the amplifier is powered from either 5 V or 3 V.
Because of its low input bias current and low offset voltage, the
AD860x can be used for precision current monitoring. The true
rail-to-rail input feature of the AD860x allows the amplifier to
monitor current on either high-side or low-side. Using both
amplifiers in an AD8602 provides a simple method for monitoring
both current supply and return paths for load or fault detection. Figures 4 and 5 demonstrate both circuits.
3V
R2
2.49k⍀
MONITOR
OUTPUT
The AD860x has excellent recovery time from overload conditions. The output recovers from the positive supply rail within
200 ns at all supply voltages. Recovery from the negative rail is
within 500 ns at 5 V supply, decreasing to within 350 ns when
the device is powered from 2.7 V.
Q1
2N3904
3V
R1
100⍀
Power-On Time
1/2 AD8602
Power-on time is important in portable applications, where the
supply voltage to the amplifier may be toggled to shut down the
device to improve battery life. Fast power-up behavior ensures
that the output of the amplifier will quickly settle to its final
voltage, improving the power-up speed of the entire system.
Once the supply voltage reaches a minimum of 2.5 V, the AD860x
will settle to a valid output within 1 µs. This turn-on response
time is faster than many other precision amplifiers, which can
take tens or hundreds of microseconds for their outputs to settle.
Figure 4. A Low-Side Current Monitor
RSENSE
0.1⍀
IL
V+
3V
3V
R1
100⍀
1/2
AD8602
Using the AD8602 in High Source Impedance Applications
The CMOS rail-to-rail input structure of the AD860x allows
these amplifiers to have very low input bias currents, typically
0.2 pA. This allows the AD860x to be used in any application
that has a high source impedance or must use large value resistances around the amplifier. For example, the photodiode
amplifier circuit shown in Figure 3 requires a low input bias
current op amp to reduce output voltage error. The AD8601
minimizes offset errors due to its low input bias current and low
offset voltage.
Q1
2N3905
MONITOR
OUTPUT
R2
2.49k⍀
Figure 5. A High-Side Current Monitor
Voltage drop is created across the 0.1 Ω resistor that is proportional to the load current. This voltage appears at the inverting
input of the amplifier due to the feedback correction around the
op amp. This creates a current through R1 which, in turn, pulls
current through R2. For the low-side monitor, the monitor
output voltage is given by
The current through the photodiode is proportional to the incident light power on its surface. The 4.7 MΩ resistor converts
this current into a voltage, with the output of the AD8601
increasing at 4.7 V/µA. The feedback capacitor reduces excess
noise at higher frequencies by limiting the bandwidth of the
circuit to
1
BW =
2π(4.7 MΩ)CF
RETURN TO
GROUND
RSENSE
0.1⍀
(1)


R

Monitor Output = 3V – R2 ×  SENSE  × IL 
 R1 


(2)
Using a 10 pF feedback capacitor limits the bandwidth to approximately 3.3 kHz.
–14–
REV. D
AD8601/AD8602/AD8604
For the high-side monitor, the monitor output voltage is
The AD8601, AD7476, and AD5320 are all available in spacesaving SOT-23 packages.
R

Monitor Output = R2 ×  SENSE  × IL
 R1 
(3)
Using the components shown, the monitor output transfer function is 2.5 V/A.
Using the AD8601 in Single-Supply Mixed-Signal Applications
Single-supply mixed-signal applications requiring 10 or more
bits of resolution demand both a minimum of distortion and a
maximum range of voltage swing to optimize performance. To
ensure that the A/D or D/A converters achieve their best performance, an amplifier often must be used for buffering or signal
conditioning. The 750 µV maximum offset voltage of the
AD8601 allows the amplifier to be used in 12-bit applications
powered from a 3 V single supply, and its rail-to-rail input
and output ensure no signal clipping.
Figure 6 shows the AD8601 used as an input buffer amplifier to
the AD7476, a 12-bit 1 MHz A/D converter. As with most A/D
converters, total harmonic distortion (THD) increases with
higher source impedances. By using the AD8601 in a buffer
configuration, the low output impedance of the amplifier minimizes THD while the high input impedance and low bias current
of the op amp minimizes errors due to source impedance. The
8 MHz gain-bandwidth product of the AD8601 ensures no
signal attenuation up to 500 kHz, which is the maximum Nyquist
frequency for the AD7476.
3V
1␮F
TANT
680nF
4
REF193
0.1␮F 10␮F
1
RS 3
5V
2
V DD 28
LEFTOUT 35
RIGHTOUT 36
␮C/␮P
1␮F
4
5
1
VOUT
0V TO 3.0V
3
2
AD8601
RL
2
Figure 7. Using the AD8601 as a DAC Output
Buffer to Drive Heavy Loads
REV. D
R2
2k⍀
5
U1-B
7
C2
100␮F
6
R5
20⍀
R3
2k⍀
U1 = AD8602D
The SPICE macro-model for the AD860x amplifier is available
and can be downloaded from the Analog Devices website at
www.analog.com. The model will accurately simulate a number
of both dc and ac parameters, including open-loop gain,
bandwidth, phase margin, input voltage range, output voltage
swing versus output current, slew rate, input voltage noise,
CMRR, PSRR, and supply current versus supply voltage. The
model is optimized for performance at 27°C. Although it will
function at different temperatures, it may lose accuracy with
respect to the actual behavior of the AD860x.
3V
1
4
R4
20⍀
SPICE Model
Figure 7 demonstrates how the AD8601 can be used as an output
buffer for the DAC for driving heavy resistive loads. The AD5320
is a 12-bit D/A converter that can be used with clock frequencies up to 30 MHz and signal frequencies up to 930 kHz. The
rail-to-rail output of the AD8601 allows it to swing within 100 mV
of the positive supply rail while sourcing 1 mA of current. The
total current drawn from the circuit is less than 1 mA, or 3 mW
from a 3 V single supply.
AD5320
3
C1
100␮F
Figure 8. A PC100 Compliant Line Output Amplifier
Figure 6. A Complete 3 V 12-Bit 1 MHz A/D
Conversion System
6
U1-A
NOTE: ADDITIONAL PINS
OMITTED FOR CLARITY
SERIAL
INTERFACE
5
1
AD1881
(AC'97)
AD7476/AD7477
3-WIRE
SERIAL
INTERFACE
8
CS
GND
4
5V
VDD
5V
SUPPLY
0.1␮F
SDATA
AD8601
2
Figure 8 shows how an AD8602 can be interfaced with an AC’97
codec to drive the line output. Here, the AD8602 is used as a
unity-gain buffer from the left and right outputs of the AC’97
codec. The 100 µF output coupling capacitors block dc current and the 20 Ω series resistors protect the amplifier from
short circuits at the jack.
SCLK
VIN
VIN
Because of its low distortion and rail-to-rail input and output,
the AD860x is an excellent choice for low-cost, single-supply
audio applications, ranging from microphone amplification to
line output buffering. TPC 34 shows the total harmonic distortion plus noise (THD + N) figures for the AD860x. In unity
gain, the amplifier has a typical THD + N of 0.004%, or –86 dB,
even with a load resistance of 600 Ω. This is compliant with the
PC100 specification requirements for audio in both portable
and desktop computers.
VSS
VDD
5
PC100 Compliance for Computer Audio Applications
–15–
AD8601/AD8602/AD8604
OUTLINE DIMENSIONS
14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
5-Lead Small Outline Transistor Package [SOT-23]
(RT-5)
Dimensions shown in millimeters
Dimensions shown in millimeters
5.10
5.00
4.90
2.90 BSC
5
14
8
4
2.80 BSC
1.60 BSC
4.50
4.40
4.30
1
6.40
BSC
2
3
PIN 1
1
0.95 BSC
7
PIN 1
1.05
1.00
0.80
0.65
BSC
1.20
MAX
0.15
0.05
1.90
BSC
1.30
1.15
0.90
0.30
0.19
0.20
0.09
SEATING COPLANARITY
PLANE
0.10
1.45 MAX
0.75
0.60
0.45
8ⴗ
0ⴗ
0.15 MAX
0.50
0.30
0.22
0.08
10ⴗ
5ⴗ
0ⴗ
SEATING
PLANE
0.60
0.45
0.30
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
COMPLIANT TO JEDEC STANDARDS MO-178AA
14-Lead Standard Small Outline Package [SOIC]
(R-14)
8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters and (inches)
Dimensions shown in millimeters
8.75 (0.3445)
8.55 (0.3366)
4.00 (0.1575)
3.80 (0.1496)
3.00
BSC
14
8
1
7
8
6.20 (0.2441)
5.80 (0.2283)
5
4.90
BSC
3.00
BSC
1
0.25 (0.0098)
0.10 (0.0039)
COPLANARITY
0.10
1.27 (0.0500)
BSC
0.51 (0.0201)
0.31 (0.0122)
0.50 (0.0197)
ⴛ 45ⴗ
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
SEATING
PLANE
4
PIN 1
0.65 BSC
8ⴗ
0.25 (0.0098) 0ⴗ 1.27 (0.0500)
0.40 (0.0157)
0.17 (0.0067)
1.10 MAX
0.15
0.00
0.38
0.22
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MS-012AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
0.23
0.08
8ⴗ
0ⴗ
0.80
0.60
0.40
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-187AA
8-Lead Standard Small Outline Package [SOIC]
(R-8)
Dimensions shown in millimeters and (inches)
5.00 (0.1968)
4.80 (0.1890)
4.00 (0.1574)
3.80 (0.1497)
8
5
1
4
1.27 (0.0500)
BSC
0.25 (0.0098)
0.10 (0.0040)
COPLANARITY
SEATING
0.10
PLANE
6.20 (0.2440)
5.80 (0.2284)
1.75 (0.0688)
1.35 (0.0532)
0.51 (0.0201)
0.31 (0.0122)
0.50 (0.0196)
ⴛ 45ⴗ
0.25 (0.0099)
8ⴗ
0.25 (0.0098) 0ⴗ 1.27 (0.0500)
0.40 (0.0157)
0.17 (0.0067)
COMPLIANT TO JEDEC STANDARDS MS-012AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
–16–
REV. D
AD8601/AD8602/AD8604
Revision History
Location
Page
11/03—Data Sheet changed from REV. C to REV. D.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
3/03—Data Sheet changed from REV. B to REV. C.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
3/03—Data Sheet changed from REV. A to REV. B.
Change to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Change to FUNCTIONAL BLOCK DIAGRAMS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Change to TPC 39 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Changes to Figures 4 and 5 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Changes to Equations 2 and 3 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14, 15
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
REV. D
–17–
–18–
–19–
–20–
C01525–0–11/03(D)