LC2MOS Quad 14-Bit DACs AD7834/AD7835 into one via DIN, SCLK, and FSYNC. The AD7834 has five dedicated package address pins, PA0 to PA4, that can be wired to AGND or VCC to permit up to 32 AD7834s to be individually addressed in a multipackage application. FEATURES Four 14-bit DACs in one package AD7834—serial loading AD7835—parallel 8-bit/14-bit loading Voltage outputs Power-on reset function Maximum/minimum output voltage range of ±8.192 V Maximum output voltage span of 14 V Common voltage reference inputs User-assigned device addressing Clear function to user-defined voltage Surface-mount packages AD7834—28-lead SOIC and PDIP AD7835—44-lead MQFP and PLCC The AD7835 can accept either 14-bit parallel loading or doublebyte loading, where right-justified data is loaded in one 8-bit byte and one 6-bit byte. Data is loaded from the external bus into one of the input latches under the control of the WR, CS, BYSHF, and DAC channel address pins, A0 to A2. GENERAL DESCRIPTION With each device, the LDAC signal is used to update all four DAC outputs simultaneously, or individually, on reception of new data. In addition, for each device, the asynchronous CLR input can be used to set all signal outputs, VOUT1 to VOUT4, to the user-defined voltage level on the device sense ground pin, DSG. On power-on, before the power supplies have stabilized, internal circuitry holds the DAC output voltage levels to within ±2 V of the DSG potential. As the supplies stabilize, the DAC output levels move to the exact DSG potential (assuming CLR is exercised). The AD7834 and AD7835 contain four 14-bit DACs on one monolithic chip. The AD7834 and AD7835 have output voltages in the range ±8.192 V with a maximum span of 14 V. The AD7834 is available in a 28-lead 0.3" SOIC package and a 28-lead 0.6" PDIP package, and the AD7835 is available in a 44-lead MQFP package and a 44-lead PLCC package. APPLICATIONS Process control Automatic test equipment General-purpose instrumentation The AD7834 is a serial input device. Data is loaded in 16-bit format from the external serial bus, MSB first after two leading 0s, FUNCTIONAL BLOCK DIAGRAMS AD7834 PAEN PA3 DAC 1 LATCH AD7835 DAC 1 BYSHF ×1 CONTROL LOGIC AND ADDRESS DECODE PA4 INPUT REGISTER 2 DAC 2 LATCH DB0 DAC 2 ×1 INPUT REGISTER 3 DAC 3 LATCH SERIAL-TOPARALLEL CONVERTER INPUT REGISTER 4 VOUT 3 A1 AGND DGND LDAC DSG Figure 1. AD7834 ADDRESS DECODE A2 VOUT 4 CLR SCLK VREF (–)A VREF (+)A DSGA INPUT REGISTER 1 DAC 1 LATCH INPUT REGISTER 2 DAC 2 LATCH INPUT REGISTER 3 DAC 3 LATCH INPUT REGISTER 4 DAC 4 LATCH DAC 1 ×1 VOUT1 ×1 VOUT2 ×1 VOUT3 DAC 2 DAC 3 A0 DAC 4 ×1 VSS WR CS ×1 DAC 4 LATCH VOUT 2 VDD 14 INPUT BUFFER DAC 3 FSYNC DIN VOUT 1 01006-001 PA2 INPUT REGISTER 1 VCC VREF (–) VREF (+) VSS DB13 PA0 PA1 VDD DAC 4 ×1 VOUT4 CLR AGND DGND LDAC VREF (–)B VREF (+)B DSGB 01006-002 VCC Figure 2. AD7835 Rev. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2003–2007 Analog Devices, Inc. All rights reserved. AD7834/AD7835 TABLE OF CONTENTS Features .............................................................................................. 1 Power-On with CLR Low, LDAC High ................................... 17 Applications....................................................................................... 1 Power-On with LDAC Low, CLR High ................................... 17 General Description ......................................................................... 1 Loading the DAC and Using the CLR Input .......................... 17 Functional Block Diagrams............................................................. 1 DSG Voltage Range .................................................................... 18 Revision History ............................................................................... 2 Power-On of the AD7834/AD7835.............................................. 19 Specifications..................................................................................... 3 Microprocessor Interfacing........................................................... 20 AC Performance Characteristics ................................................ 5 AD7834 to 80C51 Interface ...................................................... 20 Timing Specifications .................................................................. 6 AD7834 to 68HC11 Interface ................................................... 20 Absolute Maximum Ratings............................................................ 7 AD7834 to ADSP-2101 Interface ............................................. 20 Thermal Resistance ...................................................................... 7 AD7834 to DSP56000/DSP56001 Interface............................ 21 ESD Caution.................................................................................. 7 AD7834 to TMS32020/TMS320C25 Interface....................... 21 Pin Configurations and Function Descriptions ........................... 8 Interfacing the AD7835—16-Bit Interface.............................. 21 Typical Performance Characteristics ........................................... 11 Interfacing the AD7835—8-Bit Interface................................ 22 Terminology .................................................................................... 13 Applications Information .............................................................. 23 Theory of Operation ...................................................................... 14 Serial Interface to Multiple AD7834s ...................................... 23 DAC Architecture....................................................................... 14 Opto-Isolated Interface ............................................................. 23 Data Loading—AD7834 Serial Input Device ......................... 14 Automated Test Equipment ...................................................... 23 Data Loading—AD7835 Parallel Loading Device ................. 14 Power Supply Bypassing and Grounding................................ 24 Unipolar Configuration............................................................. 15 Outline Dimensions ....................................................................... 25 Bipolar Configuration................................................................ 16 Ordering Guide .......................................................................... 27 Controlled Power-On of the Output Stage.................................. 17 REVISION HISTORY 8/07—Rev. C to Rev. D Changes to Table 5 ........................................................................... 7 Added Table 6.................................................................................... 7 Changes to Table 8............................................................................ 9 Updated Outline Dimensions ....................................................... 25 Changes to Ordering Guide .......................................................... 27 7/05—Rev. B to Rev. C Updated Format..................................................................Universal Changes to Figure 40...................................................................... 25 Changes to Ordering Guide .......................................................... 27 7/03—Rev. A to Rev. B Revision 0: Initial Version Rev. D | Page 2 of 28 AD7834/AD7835 SPECIFICATIONS VCC = 5 V ± 5%; VDD = 15 V ± 5%; VSS = −15 V ± 5%; AGND = DGND = 0 V; TA 1 = TMIN to TMAX, unless otherwise noted. Table 1. Parameter ACCURACY Resolution Relative Accuracy Differential Nonlinearity Full-Scale Error TMIN to TMAX Zero-Scale Error Gain Error Gain Temperature Coefficient 2 A B S Unit 14 ±2 ±0.9 14 ±1 ±0.9 14 ±2 ±0.9 Bits LSB max LSB max ±5 ±4 ±0.5 4 ±5 ±4 ±0.5 4 ±8 ±5 ±0.5 4 mV max mV max mV typ ppm FSR/°C typ 20 50 20 50 20 50 ppm FSR/°C max μV max 30 ±1 0/8.192 −8.192/0 5/14 30 ±1 0/8.192 −8.192/0 7/14 30 ±1 0/8.192 −8.192/0 5/14 MΩ typ μA max V min/max V min/max V min/max ±2 ±2 ±2 μA max 2.4 2.4 2.4 V min VINL, Input Low Voltage 0.8 0.8 0.8 V max IINH, Input Current ±10 ±10 ±10 μA max CIN, Input Capacitance 10 10 10 pF max 5.0 15.0 −15.0 5.0 15.0 −15.0 5.0 15.0 −15.0 V nom V nom V nom ±5% for specified performance. ±5% for specified performance. ±5% for specified performance. 110 100 0.2 3 6 13 15 13 110 100 0.2 3 6 13 15 13 110 100 0.5 3 6 15 15 15 dB typ dB typ mA max mA max mA max mA max mA max mA max VINH = VCC, VINL = DGND. AD7834: VINH = 2.4 V min, VINL = 0.8 V max. AD7835: VINH = 2.4 V min, VINL = 0.8 V max. AD7834: outputs unloaded. AD7835: outputs unloaded. Outputs unloaded. DC Crosstalk2 REFERENCE INPUTS DC Input Resistance Input Current VREF(+) Range VREF(−) Range VREF(+) − VREF(−) Test Conditions/Comments Guaranteed monotonic over temperature. VREF(+) = +7 V, VREF(−) = −7 V. VREF(+) = +7 V, VREF(−) = −7 V. VREF(+) = +7 V, VREF(−) = −7 V. See the Terminology section. RL = 10 kΩ. Per input. For specified performance. Can go as low as 0 V, but performance is not guaranteed. DEVICE SENSE GROUND INPUTS Input Current DIGITAL INPUTS VINH, Input High Voltage POWER REQUIREMENTS VCC VDD VSS Power Supply Sensitivity ΔFull Scale/ΔVDD ΔFull Scale/ΔVSS ICC IDD ISS 1 2 Temperature range for A, B, and C versions is −40°C to +85°C. Guaranteed by design. Rev. D | Page 3 of 28 Per input. VDSG = −2 V to +2 V. AD7834/AD7835 VCC = 5 V ± 5%; VDD = 12 V ± 5%; VSS = −12 V ± 5%; AGND = DGND = 0 V; TA 1 = TMIN to TMAX, unless otherwise noted. Table 2. Parameter ACCURACY Resolution Relative Accuracy Differential Nonlinearity Full-Scale Error TMIN to TMAX Zero-Scale Error Gain Error Gain Temperature Coefficient 2 A B S Unit 14 ±2 ±0.9 14 ±1 ±0.9 14 ±2 ±0.9 Bits LSB max LSB max ±5 ±4 ±0.5 4 20 50 ±5 ±4 ±0.5 4 20 50 ±8 ±5 ±0.5 4 20 50 mV max mV max mV typ ppm FSR/°C typ ppm FSR/°C max μV max 30 ±1 0/8.192 −5/0 5/13.192 30 ±1 0/8.192 −5/0 7/13.192 30 ±1 0/8.192 −5/0 5/13.192 MΩ typ μA max V min/max V min/max V min/max ±2 ±2 ±2 μA max 2.4 2.4 2.4 V min VINL, Input Low Voltage 0.8 0.8 0.8 V max IINH, Input Current ±10 ±10 ±10 μA max CIN, Input Capacitance 10 10 10 pF max 5.0 15.0 −15.0 5.0 15.0 −15.0 5.0 15.0 −15.0 V nom V nom V nom ±5% for specified performance. ±5% for specified performance. ±5% for specified performance. 110 100 0.2 3 6 13 15 13 110 100 0.2 3 6 13 15 13 110 100 0.5 3 6 15 15 15 dB typ dB typ mA max mA max mA max mA max mA max mA max VINH = VCC, VINL = DGND. AD7834: VINH = 2.4 V min, VINL = 0.8 V max. AD7835: VINH = 2.4 V min, VINL = 0.8 V max. AD7834: outputs unloaded. AD7835: outputs unloaded. Outputs unloaded. DC Crosstalk2 REFERENCE INPUTS DC Input Resistance Input Current VREF(+) Range VREF(−) Range VREF(+) − VREF(−) Test Conditions/Comments Guaranteed monotonic over temperature. VREF(+) = +5 V, VREF(−) = –5 V. VREF(+) = +5 V, VREF(−) = −5 V. VREF(+) = +5 V, VREF(−) = −5 V. See the Terminology section. RL = 10 kΩ. Per input. For specified performance. Can go as low as 0 V, but performance is not guaranteed. DEVICE SENSE GROUND INPUTS Input Current DIGITAL INPUTS VINH, Input High Voltage POWER REQUIREMENTS VCC VDD VSS Power Supply Sensitivity ΔFull Scale/ΔVDD ΔFull Scale/ΔVSS ICC IDD ISS 1 2 Temperature range for A, B, and C versions is −40°C to +85°C. Guaranteed by design. Rev. D | Page 4 of 28 Per input. VDSG = −2 V to +2 V. AD7834/AD7835 AC PERFORMANCE CHARACTERISTICS These characteristics are included for design guidance and are not subject to production testing. Table 3. Parameter DYNAMIC PERFORMANCE Output Voltage Settling Time A B S Unit (typ) Test Conditions/Comments 10 10 10 μs Digital-to-Analog Glitch Impulse 120 120 120 nV-s DC Output Impedance Channel-to-Channel Isolation DAC-to-DAC Crosstalk Digital Crosstalk 0.5 100 25 3 0.5 100 25 3 0.5 100 25 3 Ω dB nV-s nV-s Digital Feedthrough—AD7834 Digital Feedthrough—AD7835 Output Noise Spectral Density at 1 kHz 0.2 1.0 40 0.2 1.0 40 0.2 1.0 40 nV-s nV-s nV/√Hz Full-scale change to ±1/2 LSB. DAC latch contents alternately loaded with all 0s and all 1s. Measured with VREF(+) = VREF(−) = 0 V. DAC latch alternately loaded with all 0s and all 1s. See the Terminology section. See the Terminology section; applies to the AD7835 only. See the Terminology section. Feedthrough to DAC output under test due to change in digital input code to another converter. Effect of input bus activity on DAC output under test. Rev. D | Page 5 of 28 All 1s loaded to DAC. VREF(+) = VREF(−) = 0 V. AD7834/AD7835 TIMING SPECIFICATIONS VCC = 5 V ± 5%; VDD = 11.4 V to 15.75 V; VSS = −11.4 V to −15.75 V; AGND = DGND = 0 V 1 . Table 4. Parameter AD7834-SPECIFIC t1 2 t22 t32 t4 t5 t6 t7 t8 t9 t21 AD7835-SPECIFIC t11 t12 t13 t14 t15 t16 t17 t18 t19 t20 GENERAL t10 1 2 Limit at TMIN, TMAX Unit Description 100 50 30 30 40 30 10 0 40 20 ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min SCLK cycle time SCLK low SCLK high time FSYNC, PAEN setup time FSYNC, PAEN hold time Data setup time Data hold time LDAC to FSYNC setup time LDAC to FSYNC hold time Delay between write operations 15 15 0 0 40 40 10 0 0 0 ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min A0, A1, A2, BYSHF to CS setup time A0, A1, A2, BYSHF to CS hold time CS to WR setup time CS to WR hold time WR pulse width Data setup time Data hold time LDAC to CS setup time CS to LDAC setup time LDAC to CS hold time 40 ns min LDAC, CLR pulse width All input signals are specified with tr = tf = 5 ns (10% to 90% of 5 V) and time from a voltage level of 1.6 V. Rise and fall times should be no longer than 50 ns. 1ST 2ND CLK CLK t1 24TH CLK A0 A1 A2 BYSHF SCLK t4 t2 t 11 t5 t3 CS FSYNC t 21 MSB LDAC (PER-CHANNEL UPDATE) D23 t13 D22 D1 WR D0 t 10 t8 t 14 t 15 LSB t16 t17 DB0 TO DB13 t9 01006-003 LDAC (SIMULTANEOUS UPDATE) t7 t10 LDAC (SIMULTANEOUS UPDATE) t19 t 18 LDAC (PER-CHANNEL UPDATE) Figure 3. AD7834 Timing Diagram t 20 Figure 4. AD7835 Timing Diagram Rev. D | Page 6 of 28 01006-004 t6 DIN t 12 AD7834/AD7835 ABSOLUTE MAXIMUM RATINGS TA = 25°C unless otherwise noted. Transient currents of up to 100 mA do not cause SCR latch-up. VCC must not exceed VDD by more than 0.3 V. If it is possible for this to happen during power supply sequencing, the diode protection scheme shown in Figure 5 can be used to provide protection. VDD Table 5. VDD to AGND VSS to AGND AGND to DGND Digital Inputs to DGND VREF(+) to VREF(–) VREF(+) to AGND VREF(–) to AGND DSG to AGND VOUT (1–4) to AGND Operating Temperature Range, TA Industrial (A Version) Storage Temperature Range Junction Temperature, TJ (max) Power Dissipation, PD (max) Lead Temperature Soldering Rating −0.3 V to +7 V, or VDD + 0.3 V (whichever is lower) −0.3 V to +17 V +0.3 V to –17 V −0.3 V to +0.3 V −0.3 V to VCC + 0.3 V −0.3 V to +18 V VSS – 0.3 V to VDD + 0.3 V VSS – 0.3 V to VDD + 0.3 V VSS – 0.3 V to VDD + 0.3 V VSS – 0.3 V to VDD + 0.3 V −40°C to +85°C −65°C to +150°C 150°C (TJ − TA)/θJA JEDEC Industry Standard J-STD-020 SD103C VDD VCC AD7834/ AD7835 01006-005 Parameter VCC to DGND VCC IN4148 Figure 5. Diode Protection THERMAL RESISTANCE θJA is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. Table 6. Thermal Resistance Package Type PDIP SOIC MQFP PLCC ESD CAUTION Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. D | Page 7 of 28 θJA 75 75 95 55 Unit °C/W °C/W °C/W °C/W AD7834/AD7835 PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS VSS 1 28 AGND DSG 2 27 NC VREF(–) 3 26 NC VREF(+) 4 25 NC NC 5 24 NC VOUT2 6 23 VDD DGND 8 21 VOUT3 VCC 9 20 CLR SCLK 10 19 LDAC DIN 11 18 FSYNC PA0 12 17 PAEN PA1 13 16 PA4 PA2 14 15 PA3 AD7834 NC = NO CONNECT 01006-006 TOP VIEW VOUT4 7 (Not to Scale) 22 VOUT1 Figure 6. AD7834 PDIP and SOIC Pin Configuration Table 7. AD7834 Pin Function Descriptions Pin No. 1 2 Pin Mnemonic VSS DSG 3 4 5, 24, 25, 26, 27 22, 6, 21, 7 8 9 10 VREF(−) VREF(+) NC VOUT1 to VOUT4 DGND VCC SCLK 11 12,13,14,15,16 DIN PA0 to PA4 17 PAEN 18 FSYNC 19 LDAC 20 CLR 23 28 VDD AGND Description Negative Analog Power Supply: −15 V ± 5% or −12 V ± 5%. Device Sense Ground Input. Used in conjunction with the CLR input for power-on protection of the DACs. When CLR is low, the DAC outputs are forced to the potential on the DSG pin. Negative Reference Input. The negative reference voltage is referred to AGND. Positive Reference Input. The positive reference voltage is referred to AGND. No Connect. DAC Outputs. Digital Ground. Logic Power Supply: 5 V ± 5%. Clock Input. Used for writing data to the device; data is clocked into the input register on the falling edge of SCLK. Serial Data Input. Package Address Inputs. These inputs are hardwired high (VCC) or low (DGND) to assign dedicated package addresses in a multipackage environment. Package Address Enable Input. When low, this input allows normal operation of the device. When high, the device ignores the package address, but not the channel address, in the serial data stream and loads the serial data into the input registers. This feature is useful in a multipackage application where it can be used to load the same data into the same channel in each package. Frame Sync Input. Active low logic input used, in conjunction with DIN and SCLK, to write data to the device with serial data expected after the falling edge of this signal. The contents of the 24-bit serial-to-parallel input register are transferred on the rising edge of this signal. Load DAC Input (Level Sensitive). This input signal, in conjunction with the FSYNC input signal, determines how the analog outputs are updated. If LDAC is maintained high while new data is being loaded into the device’s input registers, no change occurs on the analog outputs. Subsequently, when LDAC is brought low, the contents of all four input registers are transferred into their respective DAC latches, updating all of the analog outputs simultaneously. Asynchronous Clear Input (Level Sensitive, Active Low). When this input is brought low, all analog outputs are switched to the externally set potential on the DSG pin. When CLR is brought high, the signal outputs remain at the DSG potential until LDAC is brought low. When LDAC is brought low, the analog outputs are switched back to reflect their individual DAC output levels. As long as CLR remains low, the LDAC signals are ignored, and the signal outputs remain switched to the potential on the DSG pin. Positive Analog Power Supply: 15 V ± 5% or 12 V ± 5%. Analog Ground. Rev. D | Page 8 of 28 NC VREF(–)B 1 VREF(+)B VSS VDD 2 AGND NC 3 NC VREF(–)A 4 44 43 42 41 40 PIN 1 IDENTIFIER NC 7 33 NC PIN 1 IDENTIFIER 5 39 NC 32 DSGB DSGA 8 38 DSGB VOUT1 3 31 VOUT3 VOUT1 9 37 VOUT3 VOUT2 4 30 VOUT4 VOUT2 10 DSGA 2 NC 5 AD7835 A2 6 TOP VIEW (Not to Scale) A1 7 A0 8 29 DB13 NC 11 28 DB12 A2 12 27 DB11 A1 13 26 DB10 A0 14 36 VOUT4 35 DB13 AD7835 34 DB12 TOP VIEW (Not to Scale) 33 DB11 32 DB10 CLR 9 25 DB9 CLR 15 31 DB9 LDAC 10 24 DB8 LDAC 16 30 DB8 BYSHF 11 23 DB7 BYSHF 17 29 DB7 Figure 7. AD7835 MQFP Pin Configuration DB6 DB4 DB5 DB3 DB2 DB1 DB0 DGND VCC CS NC = NO CONNECT WR 18 19 20 21 22 23 24 25 26 27 28 01006-007 DB6 DB5 DB4 DB3 DB2 DB1 DB0 VCC DGND CS NC = NO CONNECT WR 12 13 14 15 16 17 18 19 20 21 22 01006-008 NC 1 6 VREF(+)A 44 43 42 41 40 39 38 37 36 35 34 NC NC VREF(+)B VREF(–)B NC AGND VDD VSS VREF(+)A NC NC VREF(–)A AD7834/AD7835 Figure 8. AD7835 PLCC Pin Configuration Table 8. AD7835 Pin Function Descriptions Pin No. MQFP 1, 5, 33, 34, 37, 41, 44 Pin No. PLCC 3, 6, 7, 11, 39, 40, 43 Pin Mnemonic NC Description No Connect. 2 8 DSGA 3, 4, 31, 30 8, 7, 6 9, 10, 37, 36 14, 13, 12 VOUT1 to VOUT4 A0, A1, A2 9 15 CLR 10 16 LDAC 11 17 BYSHF 12 18 CS 13 19 WR 14 15 20 21 VCC DGND Device Sense Ground A Input. Used in conjunction with the CLR input for power-on protection of the DACs. When CLR is low, DAC outputs VOUT1 and VOUT2 are forced to the potential on the DSGA pin. DAC Outputs. Address Inputs. A0 and A1 are decoded to select one of the four input latches for a data transfer. A2 is used to select all four DACs simultaneously. Asynchronous Clear Input (Level Sensitive, Active Low). When this input is brought low, all analog outputs are switched to the externally set potentials on the DSG pins (VOUT1 and VOUT2 follow DSGA, and VOUT3 and VOUT4 follow DSGB). When CLR is brought high, the signal outputs remain at the DSG potentials until LDAC is brought low. When LDAC is brought low, the analog outputs are switched back to reflect their individual DAC output levels. As long as CLR remains low, the LDAC signals are ignored, and the signal outputs remain switched to the potential on the DSG pins. Load DAC Input (Level Sensitive). This input signal, in conjunction with the WR and CS input signals, determines how the analog outputs are updated. If LDAC is maintained high while new data is being loaded into the device’s input registers, no change occurs on the analog outputs. Subsequently, when LDAC is brought low, the contents of all four input registers are transferred into their respective DAC latches, updating the analog outputs simultaneously. Alternatively, if LDAC is brought low while new data is being entered, the addressed DAC latch and corresponding analog output are updated immediately on the rising edge of WR. Byte Shift Input. When low, it shifts the data on DB0 to DB7 into the DB8 to DB13 half of the input register. Level-Triggered Chip Select Input (Active Low). The device is selected when this input is low. Level-Triggered Write Input (Active Low). When active, it is used in conjunction with CS to write data over the input databus. Logic Power Supply: 5 V ± 5%. Digital Ground. Rev. D | Page 9 of 28 AD7834/AD7835 Pin No. MQFP 16 to 29 Pin No. PLCC 22 to 35 Pin Mnemonic DB0 to DB13 32 38 DSGB 36, 35 42, 41 VREF(+)B, VREF(−)B Description Parallel Data Inputs. The AD7835 can accept a straight 14-bit parallel word on DB0 to DB13, where DB13 is the MSB and the BYSHF input is hardwired to a logic high. Alternatively for byte loading, the bottom eight data inputs, DB0 to DB7, are used for data loading, and the top six data inputs, DB8 to DB13, should be hardwired to a logic low. The BYSHF control input selects whether 8 LSBs or 6 MSBs of data are being loaded into the device. Device Sense Ground B Input. Used in conjunction with the CLR input for power-on protection of the DACs. When CLR is low, DAC outputs VOUT3 and VOUT4 are forced to the potential on the DSGB pin. Reference Inputs for DACs 3 and 4. These reference voltages are referred to AGND. 38 39 40 42, 43 44 1 2 4, 5 AGND VDD VSS VREF(+)A, VREF(−)A Analog Ground. Positive Analog Power Supply: 15 V ± 5% or 12 V ± 5%. Negative Analog Power Supply: −15 V ± 5% or −12 V ± 5%. Reference Inputs for DAC 1 and DAC 2. These reference voltages are referred to AGND. Rev. D | Page 10 of 28 AD7834/AD7835 TYPICAL PERFORMANCE CHARACTERISTICS 1.0 0.50 0.8 0.45 0.6 0.40 0.4 0.35 0.2 0.30 0.15 0.10 0 2 4 6 8 10 CODE/1000 12 14 DAC 2 0.20 –0.6 –1.0 DAC 4 0.25 –0.4 –0.8 DAC 3 TEMP = 25°C ALL DACs FROM 1 DEVICE 0.05 0 16 01006-012 INL (LSB) 0 –0.2 01006-009 INL (LSB) DAC 1 0 2.5 5.0 8.0 VREF(+) (V) Figure 9. Typical INL Plot Figure 12. Typical INL vs. VREF(+), VREF(+) – VREF(−) = 5 V 0.5 0.8 0.4 ALL DACs FROM ONE DEVICE 0.7 0.3 0.6 DAC 1 DAC 3 0.5 0.1 INL (LSB) DNL (LSB) 0.2 0 –0.1 DAC 4 0.4 DAC 2 0.3 –0.2 0.2 –0.5 0.1 01006-010 –0.4 0 2 4 6 8 10 CODE/1000 12 14 01006-013 –0.3 0 –40 16 Figure 13. Typical INL vs. Temperature Figure 10. Typical DNL Plot 1.0 0.9 0.8 0.8 0.6 0.7 0.4 DAC (LSB) 0.6 0.5 0.4 0.3 0.2 0 –0.2 –0.4 0.2 0.1 0 0 1 2 3 4 5 6 7 01006-014 –0.6 01006-011 INL (LSB) 85 25 TEMPERATURE (°C) –0.8 –1.0 8 VREF(+) (V) Figure 11. Typical INL vs. VREF(+), VREF(−) = −6 V 0 2 4 6 8 10 CODE/1000 12 Figure 14. Typical DAC-to-DAC Matching Rev. D | Page 11 of 28 14 16 AD7834/AD7835 0.7 0.6 –2.985 8 VERT = 100mV/DIV HORIZ = 1μs/DIV VERT = 10mV/DIV HORIZ = 1µs/DIV 6 –3.005 4 –3.025 0.3 VOLTS VOLTS 0.4 0.2 2 VREF (+) = +7V VREF (–) = –3V –3.065 0 0.1 –3.045 VOLTS 0.5 0 01006-015 VERT = 2V/DIV HORIZ = 1µs/DIV –0.2 Figure 15. Typical Digital/Analog Glitch Impulse 6 7.225 4 7.200 2 VREF(+) = +7V VREF(–) = –3V 7.175 VOLTS VERT = 2V/DIV HORIZ = 1.2μs/DIV 7.150 0 7.125 –2 VERT = 25mV/DIV HORIZ = 2.5μs/DIV 7.100 –4 01006-016 VOLTS Figure 17. Settling Time(−) 7.250 8 –3.105 –4 Figure 16. Settling Time(+) Rev. D | Page 12 of 28 01006-017 –3.085 –2 –0.1 AD7834/AD7835 TERMINOLOGY Relative Accuracy Relative accuracy or endpoint linearity is a measure of the maximum deviation from a straight line passing through the endpoints of the DAC transfer function. It is measured after adjusting for zero error and full-scale error. It is normally expressed in LSBs or as a percentage of full-scale reading. Differential Nonlinearity Differential nonlinearity is the difference between the measured change and the ideal 1 LSB change between any two adjacent codes. A specified differential nonlinearity of 1 LSB maximum ensures monotonicity. DC Crosstalk Although the common input reference (IR) voltage signals are internally buffered, small IR drops in individual DAC reference inputs across the die mean that an update to one channel produces a dc output change in one or more channel outputs. The four DAC outputs are buffered by op amps sharing common VDD and VSS power supplies. If the dc load current changes in one channel due to an update, a further dc change occurs in one or more of the channel outputs. This effect is most obvious at high load currents and is reduced as the load currents are reduced. With high impedance loads, the effect is virtually unmeasurable. Output Voltage Settling Time This is the amount of time it takes for the output to settle to a specified level for a full-scale input change. Digital-to-Analog Glitch Impulse This is the amount of charge injected into the analog output when the inputs change state. It is specified as the area of the glitch in nV-secs. It is measured with the reference inputs connected to 0 V and the digital inputs toggled between all 1s and all 0s. DAC-to-DAC Crosstalk DAC-to-DAC crosstalk is defined as the glitch impulse that appears at the output of one converter due to both the digital change and the subsequent analog output (O/P) change at another converter. It is specified in nV-secs. Digital Crosstalk The glitch impulse transferred to the output of one converter due to a change in digital input code to the other converter is defined as the digital crosstalk and is specified in nV-secs. Digital Feedthrough When the device is not selected, high frequency logic activity on its digital inputs can be capacitively coupled both across and through the device to show up as noise on the VOUT pins. This noise is digital feedthrough. DC Output Impedance DC output impedance is the effective output source resistance. It is dominated by package lead resistance. Full-Scale Error Full-scale error is the error in DAC output voltage when all 1s are loaded into the DAC latch. Ideally, the output voltage, with all 1s loaded into the DAC latch, should be VREF(+) – 1 LSB. Full-scale error does not include zero-scale error. Zero-Scale Error Zero-scale error is the error in the DAC output voltage when all 0s are loaded into the DAC latch. Ideally, the output voltage, with all 0s in the DAC latch, is equal to VREF(−). Zero-scale error is due mainly to offsets in the output amplifier. Gain Error Gain error is defined as (full-scale error) − (zero-scale error). Channel-to-Channel Isolation Channel-to-channel isolation refers to the proportion of input signal from the reference input of one DAC that appears at the output of the other DAC. It is expressed in decibels (dB). The AD7834 has no specification for channel-to-channel isolation because it has one reference for all DACs. Channel-to-channel isolation is specified for the AD7835. Rev. D | Page 13 of 28 AD7834/AD7835 THEORY OF OPERATION DAC ARCHITECTURE Table 9. D23 Control Each channel consists of a segmented 14-bit R-2R voltage-mode DAC. The full-scale output voltage range is equal to the entire reference span of VREF(+) – VREF(−). The DAC coding is straight binary; all 0s produce an output of VREF(−); all 1s produce an output of VREF(+) − 1 LSB. D23 0 1 Control Function Ignore the following 23 bits of information. Use the following 23 bits of address and data as normal. D22 and D21 D22 and D21 are decoded to select one of the four DAC channels within a device, as shown in Table 10. The analog output voltage of each DAC channel reflects the contents of its own DAC latch. Data is transferred from the external bus to the input register of each DAC latch on a per channel basis. The AD7835 has a feature whereby the A2 pin data can be transferred from the input databus to all four input registers simultaneously. Table 10. D22, D21 Control Bringing the CLR line low switches all the signal outputs, VOUT1 to VOUT4, to the voltage level on the DSG pin. The signal outputs are held at this level after the removal of the CLR signal and do not switch back to the DAC outputs until the LDAC signal is exercised. D20 to D16 DATA LOADING—AD7834 SERIAL INPUT DEVICE A write operation transfers 24 bits of data to the AD7834. The first 8 bits are control data and the remaining 16 bits are DAC data (see Figure 18). The control data identifies the DAC channel to be updated with new data and which of 32 possible packages the DAC resides in. In any communication with the device, the first 8 bits must always be control data. The DAC output voltages, VOUT1 to VOUT4, can be updated to reflect new data in the DAC input registers in one of two ways. The first method normally keeps LDAC high and only pulses LDAC low momentarily to update all DAC latches simultaneously with the contents of their respective input registers. The second method ties LDAC low and channel updating occurs on a per channel basis after new data has been clocked into the AD7834. With LDAC low, the rising edge of FSYNC transfers the new data directly into the DAC latch, updating the analog output voltage. Data being shifted into the AD7834 enters a 24-bit long shift register. If more than 24 bits are clocked in before FSYNC goes high, the last 24 bits transmitted are used as the control data and DAC data. Individual bit functions are shown in Figure 18. D23 D22 0 0 1 1 D21 0 1 0 1 Control Function Select Channel 1 Select Channel 2 Select Channel 3 Select Channel 4 D20 and D16 determine the package address. The five address bits allow up to 32 separate packages to be individually decoded. Successful decoding is accomplished when these five bits match up with the five hardwired pins on the physical package. D15 to D0 D15 and D0 provide DAC data to be loaded into the identified DAC input register. This data must have two leading 0s followed by 14 bits of data, MSB first. The MSB is in location D13 of the 24-bit data stream. DATA LOADING—AD7835 PARALLEL LOADING DEVICE Data is loaded into the AD7835 in either straight 14-bit wide words or in two 8-bit bytes. In systems that transfer 14-bit wide data, the BYSHF input should be hardwired to VCC. This sets up the AD7835 as a straight 14-bit parallel-loading DAC. In 8-bit bus systems where it is required to transfer data in two bytes, it is necessary to have the BYSHF input under logic control. In such a system, the top six pins of the device databus, DB8 to DB13, must be hardwired to DGND. New low byte data is loaded into the lower eight places of the selected input register by carrying out a write operation while holding BYSHF high. A second write operation is subsequently executed with BYSHF low and the 6 MSBs on the DB0 to DB5 inputs (DB5 = MSB). D23 determines whether the following 23 bits of address and data should be used or ignored. This is effectively a software chip select bit. D23 is the first bit to be transmitted in the 24-bit long word. Rev. D | Page 14 of 28 AD7834/AD7835 NOTE: D23 IS THE FIRST BIT TRANSMITTED IN THE SERIAL WORD. D23 D22 D21 D20 D19 D18 D17 D16 D15 D14 D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0 LSB, DB0 SECOND LSB, DB1 THIRD LSB, DB2 CONTROL BIT TO USE/IGNORE FOLLOWING 23 BITS OF INFORMATION DB3 CHANNEL ADDRESS MSB, D1 DB4 CHANNEL ADDRESS LSB, D2 DB5 DB6 PACKAGE ADDRESS MSB, PA4 DB7 PACKAGE ADDRESS, PA2 PACKAGE ADDRESS, PA1 PACKAGE ADDRESS LSB, PA0 01006-018 DB8 DB9 DB10 THIRD MSB, DB11 SECOND MSB, DB12 MSB, DB13 SECOND LEADING ZERO FIRST LEADING ZERO PACKAGE ADDRESS, PA3 Figure 18. Bit Assignments for 24-Bit Data Stream of AD7834 To avoid the DAC output going to an intermediate value during a 2-byte transfer, LDAC should not be tied low permanently but should be held high until the two bytes are written to the input register. When the selected input register has been loaded with the two bytes, LDAC should then be pulsed low to update the DAC latch and, consequently, perform the digital-to-analog conversion. In many applications, it may be acceptable to allow the DAC output to go to an intermediate value during a 2-byte transfer. In such applications, LDAC can be tied low, thus using one less control line. The actual DAC input register that is being written to is determined by the logic levels present on the device address lines, as shown in Table 11. Table 11. AD7835—Address Line Truth Table A2 0 0 0 0 1 A1 0 0 1 1 X A0 0 1 0 1 X DAC Selected DAC 1 DAC 2 DAC 3 DAC 4 All DACs selected gives the code table for unipolar operation of the AD7834/ AD7835. 2 6 8 AD586 C1 1nF 5 +15V +5V VDD VCC VREF(+) VOUT (0V TO 5V) VOUT AD7834/ AD78351 R1 10kΩ AGND 4 VREF(–) DGND VSS SIGNAL GND SIGNAL GND –15V 1ADDITIONAL PINS OMITTED FOR CLARITY 01006-019 When 14-bit transfers are being used, the DAC output voltages, VOUT1 to VOUT4, can be updated to reflect new data in the DAC input registers in one of two ways. The first method normally keeps LDAC high and only pulses LDAC low momentarily to update all DAC latches simultaneously with the contents of their respective input registers. The second method ties LDAC low, and channel updating occurs on a per channel basis after new data is loaded to an input register. Figure 19. Unipolar 5 V Operation Offset and gain can be adjusted in Figure 19 as follows: • • To adjust offset, disconnect the VREF(−) input from 0 V, load the DAC with all 0s, and adjust the VREF(−) voltage until VOUT = 0 V. To adjust gain, load the AD7834/AD7835 with all 1s and adjust R1 until VOUT = 5 V(16383/16384) = 4.999695 V. Many circuits do not require these offset and gain adjustments. In these circuits, R1 can be omitted. Pin 5 of the AD586 can be left open circuit, and Pin 2 (VREF(−)) of the AD7834/AD7835 is tied to 0 V. Table 12. Code Table for Unipolar Operation 1 , 2 UNIPOLAR CONFIGURATION Figure 19 shows the AD7834/AD7835 in the unipolar binary circuit configuration. The VREF(+) input of the DAC is driven by the AD586, a 5 V reference. VREF(−) is tied to ground. Table 12 Binary Number in DAC Latch MSB LSB 11 1111 1111 1111 Analog Output (VOUT) VREF (16383/16384) V 10 01 00 00 VREF (8192/16384) V VREF (8191/16384) V VREF (1/16384) V 0V 1 2 0000 1111 0000 0000 0000 1111 0000 0000 0000 1111 0001 0000 VREF = VREF(+); VREF(−) = 0 V for unipolar operation. For VREF(+) = 5 V, 1 LSB = 5 V/214 = 5 V/16384 = 305 μV. Rev. D | Page 15 of 28 AD7834/AD7835 BIPOLAR CONFIGURATION +15V +5V VDD VCC In Figure 20, full-scale and bipolar zero adjustments are provided by varying the gain and balance on the AD588. R2 varies the gain on the AD588 while R3 adjusts the offset of both the +5 V and –5 V outputs together with respect to ground. R1 39kΩ 4 6 7 C1 1μF 2 3 9 AD588 R2 100kΩ 1 5 14 10 11 15 16 VREF(+) VOUT AD7834/ AD78351 VOUT (–5V TO +5V) AGND VREF(–) DGND VSS 1ADDITIONAL 8 13 SIGNAL GND PINS OMITTED FOR CLARITY 01006-020 R3 100kΩ 12 –15V For bipolar-zero adjustment, the DAC is loaded with 1000 . . . 0000 and R3 is adjusted until VOUT = 0 V. Full scale is adjusted by loading the DAC with all 1s and adjusting R2 until VOUT = 5(8191/8192) V = 4.99939 V. When bipolar zero and full-scale adjustment are not needed, R2 and R3 are omitted. Pin 12 on the AD588 should be connected to Pin 11, and Pin 5 should be left floating. Figure 20. Bipolar ±5 V Operation Figure 20 shows the AD7834/AD7835 setup for ±5 V operation. The AD588 provides precision ±5 V tracking outputs that are fed to the VREF(+) and VREF(−) inputs of the AD7834/AD7835. The code table for bipolar operation of the AD7834/AD7835 is shown in Table 13. Table 13. Code Table for Bipolar Operation 1, 2 Binary Number in DAC Latch MSB LSB 11 1111 1111 1111 10 0000 0000 0001 10 0000 0000 0000 01 1111 1111 1111 00 0000 0000 0001 00 0000 0000 0000 1 2 Analog Output (VOUT) VREF(−) + VREF (16383/16384) V VREF(−) + VREF (8193/16384) V VREF(−) + VREF (8192/16384) V VREF(−) + VREF (8191/16384) V VREF(−) + VREF (1/16384) V VREF(−) V VREF = VREF(+) – VREF(−). For VREF(+) = +5 V and VREF(−) = –5 V, 1 LSB = 10 V/214 = 10 V/16384 = 610 μV. Rev. D | Page 16 of 28 AD7834/AD7835 CONTROLLED POWER-ON OF THE OUTPUT STAGE G1 A block diagram of the output stage of the AD7834/AD7835 is shown in Figure 21. It is capable of driving a load of 10 kΩ in parallel with 200 pF. G1 to G6 are transmission gates used to control the power-on voltage present at VOUT. G1 and G2 are also used in conjunction with the CLR input to set VOUT to the userdefined voltage present at the DSG pin. G6 DAC VOUT G3 G4 G2 R 01006-023 G5 G1 G6 DAC DSG VOUT Figure 23. Output Stage with VDD > 10 V and CLR Low G3 VOUT is disconnected from the DSG pin by the opening of G5 but tracks the voltage present at DSG via the unity gain buffer. G4 G2 R POWER-ON WITH LDAC LOW, CLR HIGH 01006-021 DSG Figure 21. Block Diagram of AD7834/AD7835 Output Stage POWER-ON WITH CLR LOW, LDAC HIGH The output stage of the AD7834/AD7835 is designed to allow output stability during power-on. If CLR is kept low during power-on, and power is applied to the part, G1, G4, and G6 are open while G2, G3, and G5 are closed (see Figure 22). G1 G6 DAC VOUT In many applications of the AD7834/AD7835, LDAC is kept continuously low, updating the DAC after each valid data transfer. If LDAC is low when power is applied, G1 is closed and G2 is open, connecting the output of the DAC to the input of the output amplifier. G3 and G5 are closed and G4 and G6 are open, connecting the amplifier as a unity gain buffer, as before. VOUT is connected to DSG via G5 and R (a thin-film resistance between DSG and VOUT) until VDD and VSS reach approximately ±10 V. Then, the internal power-on circuitry opens G3 and G5 and closes G4 and G6. This is the situation shown in Figure 24. At this point, VOUT is at the same voltage as the DAC output. G3 G1 G4 VOUT R DSG G3 01006-022 G5 G6 DAC G2 G4 G2 G5 Figure 22. Output Stage with VDD < 10 V VOUT is kept within a few hundred millivolts of DSG via G5 and R. R is a thin-film resistor between DSG and VOUT. The output amplifier is connected as a unity gain buffer via G3, and the DSG voltage is applied to the buffer input via G2. The amplifier output is thus at the same voltage as the DSG pin. The output stage remains configured as in Figure 22 until the voltage at VDD and VSS reaches approximately ±10 V. At this point, the output amplifier has enough headroom to handle signals at its input and has also had time to settle. The internal power-on circuitry opens G3 and G5 and closes G4 and G6 (see Figure 23). As a result, the output amplifier is connected in unity gain mode via G4 and G6. The DSG voltage is still applied to the noninverting input via G2. This voltage appears at VOUT. R DSG 01006-024 G5 Figure 24. Output Stage with LDAC Low LOADING THE DAC AND USING THE CLR INPUT When LDAC goes low, it closes G1 and opens G2 as in Figure 24. The voltage at VOUT now follows the voltage present at the output of the DAC. The output stage remains connected in this manner until a CLR signal is applied. Then, the situation reverts (see Figure 23). Once again, VOUT remains at the same voltage as DSG until LDAC goes low. This reconnects the DAC output to the unity gain buffer. Rev. D | Page 17 of 28 AD7834/AD7835 DSG VOLTAGE RANGE During power-on, the VOUT pins of the AD7834/AD7835 are connected to the relevant DSG pins via G6 and the thin-film resistor, R. The DSG potential must obey the maximum ratings at all times. Thus, the voltage at DSG must always be within the range VSS – 0.3 V to VDD + 0.3 V. However, to keep the voltages at the VOUT pins of the AD7834/AD7835 within ±2 V of the relevant DSG potential during power-on, the voltage applied to DSG should also be kept within the range AGND – 2 V to AGND + 2 V. Once the AD7834/AD7835 have powered on and the on-chip amplifiers have settled, the situation is as shown in Figure 23. Any voltage subsequently applied to the DSG pin is buffered by the same amplifier that buffers the DAC output voltage in normal operation. Thus, for specified operations, the maximum voltage applied to the DSG pin increases to the maximum allowable VREF(+) voltage, and the minimum voltage applied to DSG is the minimum VREF(−) voltage. After the AD7834 or AD7835 has fully powered on, the outputs can track any DSG voltage within this minimum/maximum range. Rev. D | Page 18 of 28 AD7834/AD7835 POWER-ON OF THE AD7834/AD7835 In some systems, it is necessary to introduce one or more Schottky diodes between pins to prevent the above situations arising at power-on. These diodes are shown in Figure 25. However, in most systems, with careful consideration given to power supply sequencing, the above rules are adhered to, and protection diodes are not necessary. Rev. D | Page 19 of 28 VREF(+) AD78341 SD103C 1N5711 1N5712 VREF(–) 1ADDITIONAL PINS OMITTED FOR CLARITY Figure 25. Power-On Protection 01006-025 Power is normally applied to the AD7834/AD7835 in the following sequence: first VDD and VSS, then VCC, and then VREF(+) and VREF(−). The VREF pins are not allowed to float when power is applied to the part. VREF(+) is not allowed to go below VREF(−) − 0.3 V. VREF(−) is not allowed to go below VSS − 0.3 V. VDD is not allowed to go below VCC − 0.3 V. AD7834/AD7835 MICROPROCESSOR INTERFACING A serial interface between the AD7834 and the 80C51 microcontroller is shown in Figure 26. TXD of the 80C51 drives SCLK of the AD7834, while RXD drives the serial data line of the part. The 80C51 provides the LSB of its SBUF register as the first bit in the serial data stream. The AD7834 expects the MSB of the 24-bit write first. Therefore, the user has to ensure that data in the SBUF register is arranged correctly so the data is received MSB first by the AD7834/AD7835. When data is to be transmitted to the part, P3.3 is taken low. Data on RXD is valid on the falling edge of TXD. The 80C51 transmits its data in 8-bit bytes with only eight falling clock edges occurring in the transmit cycle. To load data to the AD7834, P3.3 is left low after the first 8 bits are transferred. A second byte is then transferred, with P3.3 still kept low. After the third byte has been transferred, the P3.3 line is taken high. AD78341 CLR P3.4 LDAC P3.3 FSYNC TXD SCLK RXD DIN 1ADDITIONAL PINS OMITTED FOR CLARITY AD78341 68HC11 1 PC5 CLR PC6 LDAC PC7 FSYNC SCK SCLK MOSI 1ADDITIONAL PINS DIN OMITTED FOR CLARITY Figure 27. AD7834 to 68HC11 Interface In Figure 27, LDAC and CLR are controlled by the PC6 and PC5 port outputs, respectively. As with the 80C51, each DAC of the AD7834 can be updated after each 3-byte transfer, or all DACs can be simultaneously updated after 12 bytes are transferred. AD7834 TO ADSP-2101 INTERFACE Figure 26. AD7834 to 80C51 Interface LDAC and CLR on the AD7834 are also controlled by 80C51 port outputs. The user can bring LDAC low after every three bytes have been transmitted to update the DAC, which has been programmed. Alternatively, it is possible to wait until all the input registers have been loaded (12-byte transmits) and then update the DAC outputs. An interface between the AD7834 and the ADSP-2101 is shown in Figure 28. In the interface shown, SPORT0 is used to transfer data to the part. SPORT1 is configured for alternate functions. FO, the flag output on SPORT0, is connected to LDAC and is used to load the DAC latches. In this way, data is transferred from the ADSP-2101 to all the input registers in the DAC, and the DAC latches are updated simultaneously. In the application shown, the CLR pin on the AD7834 is controlled by circuitry that monitors the power in the system. POWER MONITOR CLR FO AD7834 TO 68HC11 INTERFACE Figure 27 shows a serial interface between the AD7834 and the 68HC11 microcontroller. SCK of the 68HC11 drives SCLK of the AD7834, while the MOSI output drives the serial data line, DIN, of the AD7834. The FSYNC signal is derived from Port Line PC7. For correct operation of this interface, the 68HC11 should be configured so that its CPOL bit is 0 and its CPHA bit is 1. When data is to be transferred to the part, PC7 is taken low. When the 68HC11 is configured like this, data on MOSI is valid on the falling edge of SCK. The 68HC11 transmits its serial data in 8-bit bytes, MSB first. The AD7834 also expects the MSB of the 24-bit write first. Eight falling clock edges occur in the transmit cycle. AD78341 ADSP-21011 LDAC TFS FSYNC SCK SCLK DT 1ADDITIONAL PINS DIN OMITTED FOR CLARITY 01006-028 P3.5 01006-026 80C51 1 To load data to the AD7834, PC7 is left low after the first eight bits are transferred. A second byte of data is then transmitted serially to the AD7834. Then, a third byte is transmitted and, when this transfer is complete, the PC7 line is taken high. 01006-027 AD7834 TO 80C51 INTERFACE Figure 28. AD7834 to ADSP-2101 Interface The AD7834 requires 24 bits of serial data framed by a single FSYNC pulse. It is necessary that this FSYNC pulse stay low until all the data is transferred. This can be provided by the ADSP-2101 in one of two ways. Both require setting the serial word length of the SPORT to 12 bits, with the following conditions: internal SCLK, alternate framing mode, and active low framing signal. Rev. D | Page 20 of 28 AD7834/AD7835 CLOCK/ TIMER TMS32020/ TMS320C251 DSP56000/ DSP560011 SC0 CLR SC1 LDAC SC2 FSYNC SCK SCLK STD DIN PINS OMITTED FOR CLARITY SCLK CLKX DIN DX PINS OMITTED FOR CLARITY Figure 30. AD7834 to TMS32020/TMS320C25 Interface INTERFACING THE AD7835—16-BIT INTERFACE The AD7835 can be interfaced to a variety of microcontrollers or DSP processors, both 8-bit and 16-bit. Figure 31 shows the AD7835 interfaced to a generic 16-bit microcontroller/DSP processor. BYSHF is tied to VCC in this interface. The lower address lines from the processor are connected to A0, A1, and A2 on the AD7835 as shown. The upper address lines are decoded to provide a chip select signal for the AD7835. They are also decoded, in conjunction with the lower address lines if need be, to provide an LDAC signal. Alternatively, LDAC can be driven by an external timing circuit or just tied low. The data lines of the processor are connected to the data lines of the AD7835. Selection options available for the DACs are provided in Table 11. MICROCONTROLLER/ DSP PROCESSOR1 01006-029 1ADDITIONAL AD78341 FSYNC FSX 1ADDITIONAL Figure 29 shows a serial interface between the AD7834 and the DSP56000/DSP56001. The serial port is configured for a word length of 24 bits, gated clock, and FSL0 and FSL1 control bits each set to 0. Normal mode synchronous operation is selected, which allows the use of SC0 and SC1 as outputs controlling CLR and LDAC, respectively. The framing signal on SC2 has to be inverted before being applied to FSYNC. SCK is internally generated on the DSP56000/DSP56001 and is applied to SCLK on the AD7834. Data from the DSP56000/DSP56001 is valid on the falling edge of SCK. LDAC CLR XF AD7834 TO DSP56000/DSP56001 INTERFACE AD78341 01006-030 First, data can be transferred using the autobuffering feature of the ADSP-2101, sending two 12-bit words directly after each other. This ensures a continuous transmit frame synchronization (TFS ) pulse. Second, the first data word is loaded to the serial port, the subsequent generated interrupt is trapped, and then the second data word is sent immediately after the first. Again, this produces a continuous TFS pulse that frames the 24 data bits. Figure 29. AD7834 to DSP56000/DSP56001 Interface AD78351 VCC BYSHF D13 D13 D0 D0 DATABUS A serial interface between the AD7834 and the TMS32020/ TMS320C25 DSP processor is shown in Figure 30. The CLKX and FSX signals for the TMS32020/TMS32025 are generated using an external clock/timer circuit. The CLKX and FSX pins are configured as inputs. The TMS32020/ TMS320C25 are set up for an 8-bit serial data length. Data can then be written to the AD7834 by writing three bytes to the serial port of the TMS32020/TMS320C25. In the configuration shown in Figure 30, the CLR input on the AD7834 is controlled by the XF output on the TMS32020/TMS320C25. The clock/timer circuit controls the LDAC input on the AD7834. Alternatively, LDAC can also be tied to ground to allow automatic update of the DAC latches after each transfer. UPPER BITS OF ADDRESS BUS ADDRESS DECODE A2 A1 A0 R/W 1ADDITIONAL Rev. D | Page 21 of 28 CS LDAC A2 A1 A0 WR PINS OMITTED FOR CLARITY Figure 31. AD7835 16-Bit Interface 01006-031 AD7834 TO TMS32020/TMS320C25 INTERFACE AD7834/AD7835 INTERFACING THE AD7835—8-BIT INTERFACE Figure 32 shows an 8-bit interface between the AD7835 and a generic 8-bit microcontroller/DSP processor. Pin D13 to Pin D8 of the AD7835 are tied to DGND. Pin D7 to Pin D0 of the processor are connected to Pin D7 to Pin D0 of the AD7835. BYSHF is driven by the A0 line of the processor. This maps the DAC upper bits and lower bits into adjacent bytes in the processor address space. Table 14 shows the truth table for addressing the DACs in the AD7835. For example, if the base address for the DACs in the processor address space is decoded by the upper address bits to location HC000, then the upper and lower bits of the first DAC are at locations HC000 and HC001, respectively. D13 MICROCONTROLLER/ DSP PROCESSOR1 D8 AD78351 DGND D7 D7 D0 D0 DATABUS ADDRESS DECODE LDAC A3 A2 A2 A1 A1 A0 BYSHF WR A0 R/W 1ADDITIONAL CS PINS OMITTED FOR CLARITY Table 14. DAC Channel Decoding, 8-Bit Interface A3 x 1 0 0 0 0 0 0 0 0 Processor Address Lines A2 A1 A0 X X 0 X X 1 0 0 0 0 0 1 0 1 0 0 1 1 1 0 0 1 0 1 1 1 0 1 1 1 01006-032 UPPER BITS OF ADDRESS BUS When writing to the DACs, the lower eight bits must be written first, followed by the upper six bits. The upper six bits should be output on data lines D0 to D5. Once again, the upper address lines of the processor are decoded to provide a CS signal. They are also decoded in conjunction with lines A3 to A0 to provide an LDAC signal. Alternatively, LDAC can be driven by an external timing circuit or, if it is acceptable to allow the DAC output to go to an intermediate value between 8-bit writes, LDAC can be tied low. Figure 32. AD7835 8-Bit Interface Rev. D | Page 22 of 28 DAC Selected Upper 6 bits of all DACs Lower 8 bits of all DACs Upper 6 bits, DAC 1 Lower 8 bits, DAC 1 Upper 6 bits, DAC 2 Lower 8 bits, DAC 2 Upper 6 bits, DAC 3 Lower 8 bits, DAC 3 Upper 6 bits, DAC 4 Lower 8-bits, DAC 4 AD7834/AD7835 APPLICATIONS INFORMATION Figure 33 shows how the package address pins of the AD7834 are used to address multiple AD7834s. This figure shows only 10 devices, but up to 32 AD7834s can each be assigned a unique address by hardwiring each of the package address pins to VCC or DGND. Normal operation of the device occurs when PAEN is low. When serial data is being written to the AD7834s, only the device with the same package address as the package address contained in the serial data accepts data into the input registers. Conversely, if PAEN is high, the package address is ignored, and the data is loaded into the same channel on each package. Figure 34 shows a 5-channel isolated interface to the AD7834. Multiple devices are connected to the outputs of the opto-coupler and controlled as for serial interfacing. To reduce the number of opto-isolators, the PAEN line doesn’t need to be controlled if it is not used. If the PAEN line is not controlled by the microcontroller, it should be tied low at each device. If simultaneous updating of the DACs is not required, the LDAC pin on each part can be tied permanently low and another opto-isolator is not needed. VCC MICROCONTROLLER The primary limitation with multiple packages is the output update rate. For example, if an output update rate of 10 kHz is required, 100 μs are available to load all DACs. Assuming a serial clock frequency of 10 MHz, it takes 2.5 μs to load data to one DAC. Thus, 40 DACs or 10 packages can be updated in this time. As the update rate requirement decreases, the number of possible packages increases. MICROCONTROLLER CONTROL OUT SYNC OUT SERIAL CLOCK OUT SERIAL DATA OUT PAEN LDAC FSYNC SCLK DIN DIN VCC PA0 PA1 PA2 PA3 PA4 DIN PA0 PA1 PA2 PA3 PA4 1ADDITIONAL PINS OMITTED FOR CLARITY VCC 01006-033 DEVICE 9 TO FSYNCs TO SCLKs SERIAL CLOCK OUT TO DINs SERIAL DATA OUT OPTO-COUPLER The AD7834/AD7835 are particularly suited for use in an automated test environment. Figure 35 shows the AD7835 providing the necessary voltages for the pin driver and the window comparator in a typical ATE pin electronics configuration. Two AD588s are used to provide reference voltages for the AD7835. In the configuration shown, the AD588s are configured so that the voltage at Pin 1 is 5 V greater than the voltage at Pin 9 and the voltage at Pin 15 is 5 V less than the voltage at Pin 9. AD78341 PAEN LDAC FSYNC SCLK TO LDACs AUTOMATED TEST EQUIPMENT PA0 PA1 PA2 PA3 PA4 DEVICE 1 CONTROL OUT Figure 34. Opto-Isolated Interface AD78341 PAEN LDAC FSYNC SCLK TO PAENs SYNC OUT AD78341 DEVICE 0 CONTROL OUT CONTROL OUT 01006-034 SERIAL INTERFACE TO MULTIPLE AD7834S Figure 33. Serial Interface to Multiple AD7834s OPTO-ISOLATED INTERFACE In many process control applications, it is necessary to provide an isolation barrier between the controller and the unit being controlled. Opto-isolators can provide voltage isolation in excess of 3 kV. The serial loading structure of the AD7834 makes it ideal for opto-isolated interfaces because the number of interface lines is kept to a minimum. One AD588 is used as a reference for DAC 1 and DAC 2. These DACs are used to provide high and low levels for the pin driver. The pin driver can have an associated offset. This can be nulled by applying an offset voltage to Pin 9 of the AD588. First, the code 1000 . . . 0000 is loaded into the DAC 1 latch, and the pin driver output is set to the DAC 1 output. The VOFFSET voltage is adjusted until 0 V appears between the pin driver output and DUT GND. This causes both VREF(+)A and VREF(−)A to be offset with respect to AGND by an amount equal to VOFFSET. However, the output of the pin driver varies from −5 V to +5 V with respect to DUT GND as the DAC input code varies from 000 . . . 000 to 111 . . . 111. The VOFFSET voltage is also applied to the DSGA pin. When a clear is performed on the AD7835, the output of the pin driver is 0 V with respect to DUT GND. Rev. D | Page 23 of 28 AD7834/AD7835 VOFFSET +15V –15V 2 3 1 +15V VREF(+)A 15 14 AD588 VOUT2 DSG A 0.1µF 10 11 12 DSG B 16 4 6 8 13 10 11 12 1µF 3 1 AD588 15 14 –15V AD78351 +15V –15V 2 PIN DRIVER VREF(–)A 9 1µF VOUT1 DUT GND VDUT VOUT3 VREF(+)B DUT GND VOUT4 VREF (–)B AGND 7 1ADDITIONAL 9 DUT GND WINDOW COMPARATOR TO TESTER PINS OMITTED FOR CLARITY 01006-035 4 6 8 13 7 If the AD7834/AD7835 are the only devices requiring an AGND to DGND connection, then the ground planes should be connected at the AGND and DGND pins of the AD7834/ AD7835. If the AD7834/AD7835 are in a system where multiple devices require an AGND to DGND connection, the connection can still be made at one point only, a star ground point, which can be established as close as possible to the AD7834/AD7835. 16 Figure 35. ATE Application The other AD588 provides a reference voltage for DAC 3 and DAC 4. These provide the reference voltages for the window comparator shown in Figure 35. Pin 9 of this AD588 is connected to DUT GND. This causes VREF(+)B and VREF(−)B to be referenced to DUT GND. As DAC 3 and DAC 4 input codes vary from 000 . . . 000 to 111 . . . 111, VOUT3 and VOUT4 vary from −5 V to +5 V with respect to DUT GND. DUT GND is also connected to DSGB. When the AD7835 is cleared, VOUT3 and VOUT4 are cleared to 0 V with respect to DUT GND. Care must be taken to ensure that the maximum and minimum voltage specifications for the AD7835 reference voltages are followed as shown in Figure 35. Digital lines running under the device must be avoided because they couple noise onto the die. The analog ground plane can run under the AD7834/AD7835 to avoid noise coupling. The power supply lines of the AD7834/AD7835 can use as large a trace as possible to provide low impedance paths and reduce the effects of glitches on the power supply line. Fast switching signals, such as clocks, should be shielded with digital ground to avoid radiating noise to other parts of the board. These signals should never be run near the analog inputs. Avoid crossover of digital and analog signals. Traces on opposite sides of the board should run at right angles to each other. This reduces the effects of feedthrough through the board. A microstrip method is best but not always possible with a double-sided board. With this method, the component side of the board is dedicated to ground plane while signal traces are placed on the solder side. The AD7834/AD7835 must have ample supply bypassing located as close as possible to the package, ideally right up against the device. Figure 36 shows the recommended capacitor values of 10 μF in parallel with 0.1 μF on each of the supplies. The 10 μF capacitors are the tantalum bead type. The 0.1 μF capacitor can have low effective series resistance (ESR) and effective series inductance (ESI), such as the common ceramic types, which provide a low impedance path to ground at high frequencies to handle transient currents due to internal logic switching. POWER SUPPLY BYPASSING AND GROUNDING Rev. D | Page 24 of 28 VCC 10μF DGND 0.1μF VDD AD7834/ AD78351 0.1μF 10μF AGND VSS 0.1μF 1ADDITIONAL PINS OMITTED FOR CLARITY Figure 36. Power Supply Decoupling 10μF 01006-036 In any circuit where accuracy is important, careful consideration of the power supply and ground return layout helps to ensure the rated performance. The printed circuit boards on which the AD7834/AD7835 are mounted should be designed so the analog and digital sections are separated and confined to certain areas of the boards. This facilitates the use of ground planes that can be easily separated. A minimum etch technique is generally best for ground planes because it gives the best shielding. Digital and analog ground planes should be joined at only one place. AD7834/AD7835 OUTLINE DIMENSIONS 18.10 (0.7126) 17.70 (0.6969) 15 28 7.60 (0.2992) 7.40 (0.2913) 1 14 10.65 (0.4193) 10.00 (0.3937) 2.65 (0.1043) 2.35 (0.0925) 0.30 (0.0118) 0.10 (0.0039) COPLANARITY 0.10 1.27 (0.0500) BSC 0.51 (0.0201) 0.31 (0.0122) SEATING PLANE 0.75 (0.0295) 0.25 (0.0098) 45° 8° 0° 0.33 (0.0130) 0.20 (0.0079) 1.27 (0.0500) 0.40 (0.0157) 060706-A COMPLIANT TO JEDEC STANDARDS MS-013-AE CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 37. 28-Lead Standard Small Outline Package [SOIC_W] Wide Body (RW-28) Dimensions shown in millimeters and (inches) 1.565 (39.75) 1.380 (35.05) 28 15 0.580 (14.73) 0.485 (12.31) 1 14 0.625 (15.88) 0.600 (15.24) 0.100 (2.54) BSC 0.250 (6.35) MAX 0.195 (4.95) 0.125 (3.17) 0.015 (0.38) GAUGE PLANE 0.015 (0.38) MIN 0.200 (5.08) 0.115 (2.92) SEATING PLANE 0.022 (0.56) 0.014 (0.36) 0.005 (0.13) MIN 0.700 (17.78) MAX 0.015 (0.38) 0.008 (0.20) COMPLIANT TO JEDEC STANDARDS MS-011 CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. CORNER LEADS MAY BE CONFIGURED AS WHOLE LEADS. Figure 38. 28-Lead Plastic Dual In-Line Package [PDIP] Wide Body (N-28-2) Dimensions shown in inches and (millimeters) Rev. D | Page 25 of 28 071006-A 0.070 (1.78) 0.050 (1.27) AD7834/AD7835 0.180 (4.57) 0.165 (4.19) 0.048 (1.22) 0.042 (1.07) 0.056 (1.42) 0.042 (1.07) 6 40 39 7 0.021 (0.53) 0.013 (0.33) PIN 1 IDENTIFIER 17 0.630 (16.00) 0.590 (14.99) 0.050 (1.27) BSC TOP VIEW (PINS DOWN) (PINS UP) 0.032 (0.81) 0.026 (0.66) 29 28 18 BOTTOM VIEW 0.656 (16.66) SQ 0.650 (16.51) 0.045 (1.14) R 0.025 (0.64) 0.120 (3.05) 0.090 (2.29) 0.695 (17.65) SQ 0.685 (17.40) COMPLIANT TO JEDEC STANDARDS MO-047-AC CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 39. 44-Lead Plastic Leaded Chip Carrier [PLCC} (P-44A) Dimensions shown in inches and (millimeters) 1.03 0.88 0.73 14.15 13.90 SQ 13.65 2.45 MAX 34 44 1.95 REF 1 33 PIN 1 SEATING PLANE 10.20 10.00 SQ 9.80 TOP VIEW (PINS DOWN) 2.20 2.00 1.80 0.23 0.11 23 11 0.25 MIN 0.10 COPLANARITY 7° 0° VIEW A VIEW A 22 12 0.80 BSC LEAD PITCH 0.45 0.30 LEAD WIDTH ROTATED 90° CCW COMPLIANT TO JEDEC STANDARDS MO-112-AA-1 Figure 40. 44-Lead Metric Quad Flat Package [MQFP] (S-44-2) Dimensions show in millimeters Rev. D | Page 26 of 28 041807-A 0.048 (1.22) 0.042 (1.07) 0.020 (0.51) MIN AD7834/AD7835 ORDERING GUIDE Model AD7834AR AD7834AR-REEL AD7834ARZ 1 AD7834ARZ-REEL1 AD7834BR AD7834BR-REEL AD7834BRZ1 AD7834BRZ-REEL1 AD7834AN AD7834ANZ1 AD7834BN AD7834BNZ1 AD7835AP AD7835AP-REEL AD7835APZ1 AD7835APZ-REEL1 AD7835AS AD7835AS-REEL AD7835ASZ1 AD7835ASZ-REEL1 1 Temperature Range −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C Linearity Error (LSBs) ±2 ±2 ±2 ±2 ±1 ±1 ±1 ±1 ±2 ±2 ±1 ±1 ±2 ±2 ±2 ±2 ±2 ±2 ±2 ±2 DNL (LSBs) ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 ±0.9 Z = RoHS Compliant Part. Rev. D | Page 27 of 28 Package Description 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead SOIC_W 28-Lead PDIP 28-Lead PDIP 28-Lead PDIP 28-Lead PDIP 44-Lead PLCC 44-Lead PLCC 44-Lead PLCC 44-Lead PLCC 44-Lead-MQFP 44-Lead-MQFP 44-Lead-MQFP 44-Lead-MQFP Package Option RW-28 RW-28 RW-28 RW-28 RW-28 RW-28 RW-28 RW-28 N-28-2 N-28-2 N-28-2 N-28-2 P-44A P-44A P-44A P-44A S-44-2 S-44-2 S-44-2 S-44-2 AD7834/AD7835 NOTES ©2003–2007 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. C01006-0-8/07(D) Rev. D | Page 28 of 28