LTC4000-1 High Voltage High Current Controller for Battery Charging with Maximum Power Point Control Description Features n n n n n n n n n n Maximum Power Control: Solar Panel Input Compatible Complete High Performance Battery Charger When Paired with a DC/DC Converter Wide Input and Output Voltage Range: 3V to 60V Input Ideal Diode for Low Loss Reverse Blocking and Load Sharing Output Ideal Diode for Low Loss PowerPath™ and Load Sharing with the Battery Programmable Charge Current: ±1% Accuracy ±0.25% Accurate Programmable Float Voltage Programmable C/X or Timer Based Charge Termination NTC Input for Temperature Qualified Charging 28-Lead 4mm × 5mm QFN or SSOP Packages The LTC®4000-1 is a high voltage, high performance controller that converts many externally compensated DC/DC power supplies into full-featured battery chargers with maximum power point control. In contrast to the LTC4000, the LTC4000-1 has an input voltage regulation loop instead of the input current regulation loop. Features of the LTC4000-1’s battery charger include: accurate (±0.25%) programmable float voltage, selectable timer or current termination, temperature qualified charging using an NTC thermistor, automatic recharge, C/10 trickle charge for deeply discharged cells, bad battery detection and status indicator outputs. The battery charger also includes precision current sensing that allows lower sense voltages for high current applications. The LTC4000-1 supports intelligent PowerPath control. An external PFET provides low loss reverse current protection. Another external PFET provides low loss charging or discharging of the battery. This second PFET also facilitates an instant-on feature that provides immediate downstream system power even when connected to a heavily discharged or shorted battery. Applications n n n Solar Powered Battery Charger Systems Battery Charger with High Impedance Input Source, e.g., Fuel Cell or Wind Turbine Battery Equipped Industrial or Portable Military Equipments The LTC4000-1 is available in a low profile 28-lead 4mm × 5mm QFN and SSOP packages. L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and PowerPath is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Typical Application 10.8V at 10A Charger for Three LiFePO4 Cells with a Solar Panel Input 5mΩ IN LT3845A Si7135DP OUT VC 100µF 14.7k ITH 1.15M 47nF CC IID IGATE CSP 5mΩ CSN BGATE Si7135DP BAT CLN IN OFB 127k LTC4000-1 1µF 332k FBG 133k IFB 20k BFB 3V 1.13M NTC IIMON TMR CL 10nF 0.1µF 24.9k 10k GND BIAS CX 22.1k Solar Panel Input Regulation, Achieves Max Power Point to Greater than 98% VOUT 12V, 15A 1µF 10k VBAT 10.8V FLOAT 10A MAX CHARGE CURRENT 3-CELL LiFePO4 BATTERY PACK 20 INPUT REGULATION VOLTAGE: VINREG (V) SOLAR PANEL INPUT <60V OPEN CIRCUIT VOLTAGE 17.6V PEAK POWER VOLTAGE TA = 25°C 18 16 14 98% TO 95% PEAK POWER 12 100% TO 98% PEAK POWER 10 1 5 6 7 8 9 2 3 4 CHARGER OUTPUT CURRENT: IRCS (A) 10 40001 TA01b 40001 TA01a 40001f 1 LTC4000-1 Absolute Maximum Ratings (Note 1) IN, CLN, IID, CSP, CSN, BAT........................ –0.3V to 62V IN-CLN, CSP-CSN.............................................–1V to 1V OFB, BFB, FBG............................................ –0.3V to 62V FBG.............................................................–1mA to 2mA IGATE............Max (VIID, VCSP) – 10V to Max (VIID, VCSP) BGATE........Max (VBAT, VCSN) – 10V to Max (VBAT, VCSN) ENC, CX, NTC, VM....................................–0.3V to VBIAS IFB, CL, TMR, IIMON, CC..........................–0.3V to VBIAS BIAS..............................................–0.3V to Min (6V, VIN) IBMON...................................–0.3V to Min (VBIAS, VCSP) ITH................................................................ –0.3V to 6V CHRG, FLT, RST........................................... –0.3V to 62V CHRG, FLT, RST...........................................–1mA to 2mA Operating Junction Temperature Range (Note 2).................................................................. 125°C Lead Temperature (Soldering, 10 sec) SSOP Package................................................... 300°C Storage Temperature Range................... –65°C to 150°C Pin Configuration TOP VIEW 26 RST CL 4 25 VM TMR 5 24 GND GND 6 23 IN FLT 7 22 CLN CHRG 8 21 CC BIAS 9 20 ITH NTC 10 19 IID FBG 11 18 IGATE BFB 12 17 OFB BAT 13 16 CSP BGATE 14 15 CSN ITH 27 IIMON 3 CC 2 CX CLN IBMON 28 27 26 25 24 23 IN 28 IFB GND ENC 1 IID TOP VIEW 22 IGATE VM 1 RST 2 21 OFB IIMON 3 20 CSP IFB 4 19 CSN 29 GND ENC 5 18 BGATE IBMON 6 17 BAT CX 7 16 BFB CL 8 15 FBG NTC BIAS CHRG FLT GND TMR 9 10 11 12 13 14 UFD PACKAGE 28-LEAD (4mm × 5mm) PLASTIC QFN TJMAX = 125°C, θJA = 43°C/W, θJC = 4°C/W EXPOSED PAD (PIN 29) IS GND, MUST BE SOLDERED TO PCB GN PACKAGE 28-LEAD PLASTIC SSOP TJMAX = 125°C, θJA = 80°C/W, θJC = 25°C/W Order Information LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTC4000EUFD-1#PBF LTC4000EUFD-1#TRPBF 40001 28-Lead (4mm × 5mm) Plastic QFN –40°C to 125°C LTC4000IUFD-1#PBF LTC4000IUFD-1#TRPBF 40001 28-Lead (4mm × 5mm) Plastic QFN –40°C to 125°C LTC4000EGN-1#PBF LTC4000EGN-1#TRPBF LTC4000GN-1 28-Lead Plastic SSOP –40°C to 125°C LTC4000IGN-1#PBF LTC4000IGN-1#TRPBF LTC4000GN-1 28-Lead Plastic SSOP –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 40001f 2 LTC4000-1 Electrical Characteristics The l denotes the specifications which apply over the full operating junction temperature range, otherwise specifications are at TA = 25°C. VIN = VCLN = 3V to 60V unless otherwise noted (Notes 2, 3). SYMBOL PARAMETER VIN Input Supply Operating Range IIN Input Quiescent Operating Current IBAT Battery Pin Operating Current Battery Only Quiescent Current CONDITIONS MIN l TYP 3 MAX 60 0.4 UNITS V mA VIN ≥ 3V, VCSN = VCSP ≥ VBAT l 50 100 µA VIN = 0V, VCSN = VCSP ≤ VBAT l 10 20 μA 0.4 V Shutdown ENC Input Voltage Low l ENC Input Voltage High l 1.5 –4 –2 l 1.5 2.5 l 0.985 1.000 ENC Pull-Up Current VENC = 0V ENC Open Circuit Voltage VENC = Open V –0.5 µA V Voltage Regulation VIFB_REG Input Feedback Voltage IFB Input Current VBFB_REG ± 0.1 Battery Feedback Voltage BFB Input Current VOFB_REG VIFB = 1.0V OFB Input Current l 1.133 1.120 1.136 1.136 l 1.176 1.193 VBFB = 1.2V Output Feedback Voltage RFBG Ground Return Feedback Resistance Rising Recharge Battery Threshold Voltage VRECHRG(HYS) Recharge Battery Threshold Voltage Hysteresis % of VBFB_REG 1.139 1.147 l 96.9 VOUT(INST_ON) Instant-On Battery Voltage Threshold % of VBFB_REG VLOBAT Falling Low Battery Threshold Voltage % of VBFB_REG l VLOBAT(HYS) Low Battery Threshold Voltage Hysteresis % of VBFB_REG V µA 100 400 Ω 97.6 98.3 % 0.5 l V V µA 1.204 ± 0.1 l % of VBFB_REG V µA ± 0.1 VOFB = 1.2V VRECHRG(RISE) 1.010 % 82 86 90 % 65 68 71 % 3 % Current Monitoring and Regulation VOS Ratio of Monitored-Current Voltage to Sense Voltage VIN,CLN ≤ 50mV, VIIMON/VIN,CLN VCSP,CSN ≤ 50mV, VIBMON/VCSP,CSN Sense Voltage Offset VCSP,CSN ≤ 50mV, VCSP = 60V or VIN,CLN ≤ 50mV, VIN = 60V (Note 4) CLN, CSP, CSN Common Mode Range (Note 4) l l 18.5 21 V/V –300 300 µV 3 60 V CLN Pin Current 20 ±1 µA CSP Pin Current VIGATE = Open, VIID = 0V 90 μA CSN Pin Current VBGATE = Open, VBAT = 0V 45 μA ICL Pull-Up Current for the Charge Current Limit Programming Pin ICL_TRKL Pull-Up Current for the Charge Current Limit Programming Pin in Trickle Charge Mode VBFB < VLOBAT l –55 –50 –45 μA l –5.5 –5.0 –4.5 μA 40 90 140 kΩ Input Current Monitor Resistance to GND Charge Current Monitor Resistance to GND A5 Error Amp Offset for the Charge Current Loop (See Figure 1) Maximum Programmable Current Limit Voltage Range VCL = 0.8V 40 90 140 kΩ l –10 0 10 mV l 0.985 1.0 1.015 V 40001f 3 LTC4000-1 Electrical Characteristics The l denotes the specifications which apply over the full operating junction temperature range, otherwise specifications are at TA = 25°C. VIN = VCLN = 3V to 60V unless otherwise noted (Notes 2, 3). SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS Charge Termination CX Pin Pull-Up Current VCX = 0.1V l –5.5 –5.0 –4.5 µA VCX,IBMON(OS) CX Comparator Offset Voltage, IBMON Falling VCX = 0.1V l 0.5 10 25 mV VCX,IBMON(HYS) CX Comparator Hysteresis Voltage 5 mV TMR Pull-Up Current VTMR = 0V –5.0 μA TMR Pull-Down Current VTMR = 2V 5.0 μA TMR Pin Frequency CTMR = 0.01μF 400 500 600 Hz 2.1 2.5 V tT Charge Termination Time CTMR = 0.1μF l 2.3 2.9 3.5 h tT/tBB Ratio of Charge Terminate Time to Bad Battery CTMR = 0.1μF Indicator Time l 3.95 4 4.05 h/h VNTC(COLD) NTC Cold Threshold VNTC Rising, % of VBIAS l 73 75 77 % VNTC(HOT) NTC Hot Threshold VNTC Falling, % of VBIAS l 33 35 37 % VNTC(HYS) NTC Thresholds Hysteresis % of VBIAS VNTC(OPEN) NTC Open Circuit Voltage % of VBIAS RNTC(OPEN) NTC Open Circuit Input Resistance TMR Threshold for CX Termination l 5 l 45 50 % 55 300 % kΩ Voltage Monitoring and Open Drain Status Pins VVM(TH) VM Input Falling Threshold VVM(HYS) VM Input Hysteresis VM Input Current l 1.176 VVM = 1.2V 1.193 1.204 V 40 mV ±0.1 µA IRST,CHRG,FLT(LKG) Open Drain Status Pins Leakage Current VPIN = 60V VRST,CHRG,FLT(VOL) Open Drain Status Pins Voltage Output Low IPIN = 1mA l ±1 µA Input PowerPath Forward Regulation Voltage VIID,CSP, 3V ≤ VCSP ≤ 60V l 0.1 Input PowerPath Fast Reverse Turn-Off Threshold Voltage VIID,CSP, 3V ≤ VCSP ≤ 60V, VIGATE = VCSP – 2.5V, ∆IIGATE/∆ VIID,CSP ≥ 100μA/mV l Input PowerPath Fast Forward Turn-On Threshold Voltage VIID,CSP, 3V ≤ VCSP ≤ 60V, VIGATE = VIID – 1.5V, ∆IIGATE/∆ VIID,CSP ≥ 100μA/mV l Input Gate Turn-Off Current VIID = VCSP, VIGATE = VCSP – 1.5V –0.3 μA Input Gate Turn-On Current VCSP = VIID – 20mV, VIGATE = VIID – 1.5V 0.3 μA IIGATE(FASTOFF) Input Gate Fast Turn-Off Current VCSP = VIID + 0.1V, VIGATE = VCSP – 5V –0.5 mA IIGATE(FASTON) Input Gate Fast Turn-On Current VCSP = VIID – 0.2V, VIGATE = VIID – 1.5V 0.7 mA VIGATE(ON) Input Gate Clamp Voltage IIGATE = 2µA, VIID = 12V to 60V, VCSP = VIID – 0.5V, Measure VIID – VIGATE l 13 15 V Input Gate Off Voltage IIGATE = – 2μA, VIID = 3V to 59.5V, VCSP = VIID + 0.5V, Measure VCSP – VIGATE l 0.45 0.7 V 0.4 V 8 20 mV –90 –50 –20 mV 40 80 130 mV Input PowerPath Control 40001f 4 LTC4000-1 Electrical Characteristics The l denotes the specifications which apply over the full operating junction temperature range, otherwise specifications are at TA = 25°C. VIN = VCLN = 3V to 60V unless otherwise noted (Notes 2, 3). SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS Battery PowerPath Control Battery Discharge PowerPath Forward Regulation Voltage VBAT,CSN, 2.8V ≤ VBAT ≤ 60V l 0.1 8 20 mV Battery PowerPath Fast Reverse Turn-Off Threshold Voltage VBAT,CSN, 2.8V ≤ VBAT ≤ 60V, Not Charging, VBGATE = VCSN – 2.5V, ∆IBGATE/∆VBAT,CSN ≥ 100μA/mV l –90 –50 –20 mV Battery PowerPath Fast Forward Turn-On Threshold Voltage VBAT,CSN, 2.8V ≤ VCSN ≤ 60V, VBGATE = VBAT – 1.5V, ∆IBGATE/∆ VBAT,CSN ≥ 100μA/mV l 40 80 130 mV Battery Gate Turn-Off Current VBGATE = VCSN – 1.5V, VCSN ≥ VBAT, VOFB < VOUT(INST_ON) and Charging in Progress, or VCSN = VBAT and Not Charging –0.3 μA Battery Gate Turn-On Current VBGATE = VBAT – 1.5V, VCSN ≥ VBAT, VOFB > VOUT(INST_ON) and Charging in Progress, or VCSN = VBAT – 20mV 0.3 μA IBGATE(FASTOFF) Battery Gate Fast Turn-Off Current VCSN = VBAT + 0.1V and Not Charging, VBGATE = VCSN – 5V –0.5 mA IBGATE(FASTON) Battery Gate Fast Turn-On Current VCSN = VBAT – 0.2V, VBGATE = VBAT – 1.5V 0.7 mA VBGATE(ON) Battery Gate Clamp Voltage IBGATE = 2μA, VBAT = 12V to 60V, VCSN = VBAT – 0.5V, Measure VBAT – VBGATE Battery Gate Off Voltage IBGATE = – 2μA, VBAT = 2.8V to 59.5V, l VCSN = VBAT + 0.5V and not Charging, Measure VCSN – VBGATE l 13 15 V 0.45 0.7 V 2.9 3.5 V –10 BIAS Regulator Output and Control Pins VBIAS BIAS Output Voltage No Load ΔVBIAS BIAS Output Voltage Load Regulation IBIAS = – 0.5mA –0.5 BIAS Output Short-Circuit Current VBIAS = 0V –20 mA Transconductance of Error Amp CC = 1V 0.5 mA/V l Open Loop DC Voltage Gain of Error Amp CC = Open IITH(PULL_UP) Pull-Up Current on the ITH Pin VITH = 0V, CC = 0V IITH(PULL_DOWN) Pull-Down Current on the ITH Pin VITH = 0.4V, CC = Open Open Loop DC Voltage Gain of ITH Driver ITH = Open Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTC4000-1 is tested under conditions such that TJ ≈ TA. The LTC4000E-1 is guaranteed to meet specifications from 0°C to 85°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization and correlation with statistical process controls. The LTC4000I-1 is guaranteed over the full –40°C to 125°C operating junction temperature range. Note that the maximum ambient temperature consistent with 2.4 80 –6 l 0.5 –5 % dB –4 μA 1 mA 60 dB these specifications is determined by specific operating conditions in conjunction with board layout, the rated package thermal impedance and other environmental factors. The junction temperature (TJ, in °C) is calculated from the ambient temperature (TA, in °C) and power dissipation (PD, in Watts) according to the following formula: TJ = TA + (PD • θJA), where θJA (in °C/W) is the package thermal impedance. Note 3: All currents into pins are positive; all voltages are referenced to GND unless otherwise noted. Note 4: These parameters are guaranteed by design and are not 100% tested. 40001f 5 LTC4000-1 Typical Performance Characteristics Input Quiescent Current and Battery Quiescent Current Over Temperature 1.0 Input Voltage Regulation Feedback, Battery Float Voltage Feedback, Output Voltage Regulation Feedback and VM Falling Threshold Over Temperature Battery Only Quiescent Current Over Temperature 1.20 100 VIN = VBAT = 15V VCSN = 15.5V IIN 1.18 VBAT = 60V 10 1.16 PIN VOLTAGE (V) 1 IBAT (µA) IIN/IBAT (mA) IBAT VBAT = 3V 0.1 1.015 1.010 –47.5 1.005 ICL (µA) VOUT(INST_ON) VIBMON (V) PERCENT OF VBFB_REG (%) Maximum Programmable Current Limit Voltage Over Temperature CL Pull-Up Current Over Temperature –50.0 75 0.995 0.990 60 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) –55.0 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G04 40001 G06 CX Comparator Offset Voltage with VIBMON Falling Over Temperature Current Sense Offset Voltage Over Common Mode Voltage Range 300 VMAX(IN,CLN) = VMAX(CSP, CSN) = 15V 200 100 VOS (µV) VOS(CSP, CSN) 0 VOS(IN, CSN) VOS(CSP, CSN) 0 VOS(IN, CSN) –100 –200 –200 –300 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) –300 40001 G07 VCX,IBMON (mV) 200 VOS (µV) 0.985 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G05 Current Sense Offset Voltage Over Temperature –100 1.000 –52.5 VLOBAT 65 100 40001 G03 –45.0 80 300 VIFB_REG –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) VRECHRG(RISE) 90 70 1.06 40001 G02 100 85 1.08 1.00 0.001 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) Battery Thresholds: Rising Recharge, Instant-On Regulation and Falling Low Battery As a Percentage of Battery Float Feedback Over Temperature VBFB_REG 1.00 1.02 40001 G01 95 1.12 1.04 0.01 0 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) VOFB_REG 1.14 VBAT = 15V 0.1 VVM(TH) 0 3 10 20 30 40 50 VMAX(IN, CLN) /VMAX(CSP, CSN) (V) 60 40001 G08 20 19 18 17 16 15 14 13 12 11 10 9 8 7 6 5 4 3 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G09 40001f 6 LTC4000-1 Typical Performance Characteristics Charge Termination Time with 0.1µF Timer Capacitor Over Temperature NTC Thresholds Over Temperature 3.5 80 VNTC(COLD) 75 3.3 14 12 2.9 2.7 65 60 55 VNTC(OPEN) 50 45 VNTC(HOT) 40 2.5 VIID,CSP / VBAT,CSN (mV) PERCENT OF VBIAS (%) 70 3.1 TT (h) PowerPath Forward Voltage Regulation Over Temperature 15.0 VIID = VBAT = 15V PowerPath Turn-Off Gate Voltage Over Temperature 600 VIID = VBAT = 15V 0 –30 VCSP,IGATE/VCSN,BGATE (mV) 30 VCSP = VCSN = 15V 550 14.5 VIGATE (ON)/VBGATE(ON) (V) 14.0 13.5 13.0 12.5 12.0 500 450 400 350 300 –60 11.5 250 –90 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 11.0 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 200 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G13 BIAS Voltage at 0.5mA Load Over Temperature ITH Pull-Down Current Over Temperature 3.2 1.5 1.4 3.1 VIN = 60V VIN = 15V 2.9 2.8 VIN = 3V 2.7 2.5 VITH = 0.4V 1.3 IITH(PULL-DOWN) (mA) 3.0 ITH Pull-Down Current vs VITH 2.0 1.2 1.1 1.0 0.9 0.8 0.7 2.6 40001 G15 40001 G14 IITH(PULL-DOWN) (mA) VIID,CSP /VBAT,CSN (mV) 40001 G12 PowerPath Turn-On Gate Clamp Voltage Over Temperature 90 VBIAS (V) 4 40001 G11 PowerPath Fast Off, Fast On and Forward Regulation Over Temperature 60 VIID = VBAT = 60V 6 0 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 30 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G10 120 VIID = VBAT = 3V 8 2 35 2.3 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) VIID = VBAT = 15V 10 1.5 1.0 0.5 0.6 2.5 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G16 0.5 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 40001 G17 0 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 VITH (V) 1 40001 G18 40001f 7 LTC4000-1 Pin Functions (QFN/SSOP) VM (Pin 1/Pin 25): Voltage Monitor Input. High impedance input to an accurate comparator with a 1.193V threshold (typical). This pin controls the state of the RST output pin. Connect a resistor divider (RVM1, RVM2) between the monitored voltage and GND, with the center tap point connected to this pin. The falling threshold of the monitored voltage is calculated as follows: VVM _ RST R +R = VM1 VM2 • 1.193V RVM2 where RVM2 is the bottom resistor between the VM pin and GND. Tie to the BIAS pin if voltage monitoring function is not used. RST (Pin 2/Pin 26): High Voltage Open Drain Reset Output. When the voltage at the VM pin is below 1.193V, this status pin is pulled low. When driven low, this pin can disable a DC/DC converter when connected to the converter’s enable pin. This pin can also drive an LED to provide a visual status indicator of a monitored voltage. Short this pin to GND when not used. IIMON (Pin 3/Pin 27): Input Current Monitor. The voltage on this pin is 20 times (typical) the sense voltage (VIN,CLN) across the input current sense resistor(RIS), therefore providing a voltage proportional to the input current. Connect an appropriate capacitor to this pin to obtain a voltage representation of the time-average input current. Leave this pin open when input current monitoring function is not needed. IFB (Pin 4/Pin 28): Input Voltage Feedback Pin. This pin is a high impedance input pin used to sense the input voltage level. In regulation, the input voltage loop sets the voltage on this feedback pin to 1.000V. When the input feedback voltage drops below 1.000V, the ITH pin is pulled down to reduce the load on the input source. Connect this pin to the center node of a resistor divider between the IN pin and GND to set the input voltage regulation level. This regulation level can then be obtained as follows: R VIN _ REG = OFB1 + 1 • 1.000V ROFB2 If the input voltage regulation feature is not used, connect the IFB pin to the BIAS pin. ENC (Pin 5/Pin 1): Enable Charging Pin. High impedance digital input pin. Pull this pin above 1.5V to enable charging and below 0.5V to disable charging. Leaving this pin open causes the internal 2µA pull-up current to pull the pin to 2.5V (typical). IBMON (Pin 6/Pin 2): Battery Charge Current Monitor. The voltage on this pin is 20 times (typical) the sense voltage (VCSP,CSN) across the battery current sense resistor (RCS), therefore providing a voltage proportional to the battery charge current. Connect an appropriate capacitor to this pin to obtain a voltage representation of the time-average battery charge current. Short this pin to GND to disable charge current limit feature. CX (Pin 7/Pin 3): Charge Current Termination Programming. Connect the charge current termination programming resistor (RCX) to this pin. This pin is a high impedance input to a comparator and sources 5μA of current. When the voltage on this pin is greater than the charge current monitor voltage (VIBMON), the CHRG pin 40001f 8 LTC4000-1 Pin Functions (QFN/SSOP) turns high impedance indicating that the CX threshold is reached. When this occurs, the charge current is immediately terminated if the TMR pin is shorted to the BIAS pin, otherwise charging continues until the charge termination timer expires. The charge current termination value is determined using the following formula: IC / X = (0.25µA • R CX ) − 0.5mV R CS Where RCS is the sense resistor connected to the CSP and the CSN pins. Note that if RCX = RCL ≤ 19.1kΩ, where RCL is the charge current programming resistor, then the charge current termination value is one tenth the full charge current, more familiarly known as C/10. Short this pin to GND to disable CX termination. CL (Pin 8/Pin 4): Charge Current Limit Programming. Connect the charge current programming resistor (RCL) to this pin. This pin sources 50µA of current. The regulation loop compares the voltage on this pin with the charge current monitor voltage (VIBMON), and drives the ITH pin accordingly to ensure that the programmed charge current limit is not exceeded. The charge current limit is determined using the following formula: R ICLIM = 2.5µA • CL RCS Where RCS is the sense resistor connected to the CSP and the CSN pins. Leave the pin open for the maximum charge current limit of 50mV/RCS. TMR (Pin 9/Pin 5): Charge Timer. Attach 1nF of external capacitance (CTMR) to GND for each 104 seconds of charge termination time and 26 seconds of bad battery indicator time. Short to GND to prevent bad battery indicator time and charge termination time from expiring – allowing a continuous trickle charge and top off float voltage regulation charge. Short to BIAS to disable bad battery detect and enable C/X charging termination. GND (Pins 10, 28, 29/Pins 6, 24): Device Ground Pins. Connect the ground pins to a suitable PCB copper ground plane for proper electrical operation. The QFN package exposed pad must be soldered to PCB ground for rated thermal performance. FLT, CHRG (Pin 11, Pin 12/Pin 7, Pin 8): Charge Status Indicator Pins. These pins are high voltage open drain pull down pins. The FLT pin pulls down when there is an under or over temperature condition during charging or when the voltage on the BFB pin stays below the low battery threshold during charging for a period longer than the bad battery indicator time. The CHRG pin pulls down during a charging cycle. Please refer to the application information section for details on specific modes indicated by the combination of the states of these two pins. Pull up each of these pins with an LED in series with a resistor to a voltage source to provide a visual status indicator. Short these pins to GND when not used. BIAS (Pin 13/Pin 9): 2.9V Regulator Output. Connect a capacitor of at least 470nF to bypass this 2.9V regulated voltage output. Use this pin to bias the resistor divider to set up the voltage at the NTC pin. 40001f 9 LTC4000-1 Pin Functions (QFN/SSOP) NTC (Pin 14/Pin 10): Thermistor Input. Connect a thermistor from NTC to GND, and a corresponding resistor from BIAS to NTC. The voltage level on this pin determines if the battery temperature is safe for charging. The charge current and charge timer are suspended if the thermistor indicates a temperature that is unsafe for charging. Once the temperature returns to the safe region, charging resumes. Leave the pin open or connected to a capacitor to disable the temperature qualified charging function. FBG (Pin 15/Pin 11): Feedback Ground Pin. This is the ground return pin for the resistor dividers connected to the BFB and OFB pins. As soon as the voltage at IN is valid (>3V typical), this pin has a 100Ω resistance to GND. When the voltage at IN is not valid, this pin is disconnected from GND to ensure that the resistor dividers connected to the BFB and OFB pins do not continue to drain the battery when the battery is the only available power source. BFB (Pin 16/Pin 12): Battery Feedback Voltage Pin. This pin is a high impedance input pin used to sense the battery voltage level. In regulation, the battery float voltage loop sets the voltage on this pin to 1.136V (typical). Connect this pin to the center node of a resistor divider between the BAT pin and the FBG pin to set the battery float voltage. The battery float voltage can then be obtained as follows: VFLOAT = RBFB2 + RBFB1 • 1.136V RBFB2 BAT (Pin 17/Pin 13): Battery Pack Connection. Connect the battery to this pin. This pin is the anode of the battery ideal diode driver (the cathode is the CSN pin). BGATE (Pin 18/Pin 14): External Battery PMOS Gate Drive Output. When not charging, the BGATE pin drives the external PMOS to behave as an ideal diode from the BAT pin (anode) to the CSN pin (cathode). This allows efficient delivery of any required additional power from the battery to the downstream system connected to the CSN pin. When charging a heavily discharged battery, the BGATE pin is regulated to set the output feedback voltage (OFB pin) to 86% of the battery float voltage (0.974V typical). This allows the instant-on feature, providing an immediate valid voltage level at the output when the LTC4000-1 is charging a heavily discharged battery. Once the voltage on the OFB pin is above the 0.974V typical value, then the BGATE pin is driven low to ensure an efficient charging path from the CSN pin to the BAT pin. CSN (Pin 19/Pin 15): Charge Current Sense Negative Input and Battery Ideal Diode Cathode. Connect a sense resistor between this pin and the CSP pin. The LTC4000-1 senses the voltage across this sense resistor and regulates it to a voltage equal to 1/20th (typical) of the voltage set at the CL pin. The maximum regulated sense voltage is 50mV. The CSN pin is also the cathode input of the battery ideal diode driver (the anode input is the BAT pin). Tie this pin to the CSP pin if no charge current limit is desired. Refer to the Applications Information section for complete details. CSP (Pin 20/Pin 16): Charge Current Sense Positive Input and Input Ideal Diode Cathode. Connect a sense resistor between this pin and the CSN pin for charge current sensing and regulation. This input should be tied to CSN to disable the charge current regulation function. This pin is also the cathode of the input ideal diode driver (the anode is the IID pin). 40001f 10 LTC4000-1 Pin Functions (QFN/SSOP) OFB (Pin 21/Pin 17): Output Feedback Voltage Pin. This pin is a high impedance input pin used to sense the output voltage level. In regulation, the output voltage loop sets the voltage on this feedback pin to 1.193V. Connect this pin to the center node of a resistor divider between the CSP pin and the FBG pin to set the output voltage when battery charging is terminated and all the output load current is provided from the input. The output voltage can then be obtained as follows: VOUT + ROFB1 R = OFB2 • 1.193V ROFB2 When charging a heavily discharged battery (such that VOFB < VOUT(INST_ON)), the battery PowerPath PMOS connected to BGATE is regulated to set the voltage on this feedback pin to 0.974V (approximately 86% of the battery float voltage). The instant-on output voltage is then as follows: VOUT(INST _ ON) = ROFB2 + ROFB1 • 0.974V ROFB2 IGATE (Pin 22/Pin 18): Input PMOS Gate Drive Output. The IGATE pin drives the external PMOS to behave as an ideal diode from the IID pin (anode) to the CSP pin (cathode). IID (Pin 23/Pin 19): Input Ideal Diode Anode. This pin is the anode of the input ideal diode driver (the cathode is the CSP pin). ITH (Pin 24/Pin 20): High Impedance Control Voltage Pin. When any of the regulation loops (input voltage, charge current, battery float voltage or the output voltage) indicate that its limit is reached, the ITH pin will sink current (up to 1mA) to regulate that particular loop at the limit. In many applications, this ITH pin is connected to the control/ compensation node of a DC/DC converter. Without any external pull-up, the operating voltage range on this pin is GND to 2.5V. With an external pull-up, the voltage on this pin can be pulled up to 6V. Note that the impedance connected to this pin affects the overall loop gain. For details, refer to the Applications Information section. CC (Pin 25/Pin 21): Converter Compensation Pin. Connect an R-C network from this pin to the ITH pin to provide a suitable loop compensation for the converter used. Refer to the Applications Information section for discussion and procedure on choosing an appropriate R-C network for a particular DC/DC converter. CLN (Pin 26/Pin 22): Input Current Sense Negative Input. Connect a sense resistor between this pin and the IN pin. The LTC4000-1 senses the voltage across this sense resistor and sets the voltage on the IIMON pin equal to 20 times this voltage. Tie this pin to the IN pin if the input current monitoring feature is not used. Refer to the Applications Information section for complete details. IN (Pin 27/Pin 23): Input Supply Voltage: 3V to 60V. Supplies power to the internal circuitry and the BIAS pin. Connect the power source to the downstream system and the battery charger to this pin. This pin is also the positive sense pin for the input current monitor. Connect a sense resistor between this pin and the CLN pin. Tie this pin to CLN if the input current monitoring feature is not used. A local 0.1µF bypass capacitor to ground is recommended on this pin. 40001f 11 LTC4000-1 Block Diagram RIS CIN RVM1 OUT DC/DC CONVERTER CCLN RC IN CLN RST VM – CIBMON CC ITH CC IID IBMON IGATE CSP CP1 RVM2 1.193V 8mV + + – – + A8 gm = 0.33m A9 gm = 0.33m 60k A1 +– INPUT IDEAL DIODE DRIVER 8mV gm A11 RIFB1 A4 IFB 1V RIFB2 gm– BIAS A5 –g m + – ROFB1 5µA/ 50µA 1V gm+ CL – A7 + – IN LDO, BG, REF CBIAS BATTERY IDEAL DIODE AND INSTANT-ON DRIVER ITH AND CC DRIVER A10 BGATE ENABLE CHARGING 0.974V 60k RCS CSN LINEAR GATE DRIVER AND VOLTAGE CLAMP A2 IIMON CIIMON A6 + – REF gm RCL OFB gm BIAS OFB 1.193V CP6 BFB – 0.771V ROFB2 1.136V + BFB + CP4 TOO COLD – – RBFB2 1.109V FBG NTC FAULT + RBFB1 + CP5 NTC SYSTEM LOAD CL CIID – + IN LOGIC CP3 – CP2 BAT – BIAS TOO HOT + CBAT 5µA 10mV –+ BIAS + – RNTC CX BATTERY PACK 2µA TMR CTMR RCX OSCILLATOR GND ENC CHRG FLT 40001 BD R3 Figure 1. LTC4000-1 Functional Block Diagram 40001f 12 LTC4000-1 Operation Overview The LTC4000-1 is designed to simplify the conversion of any externally compensated DC/DC converter into a high performance battery charger with PowerPath control. It only requires the DC/DC converter to have a control or external-compensation pin (usually named VC or ITH) whose voltage level varies in a positive monotonic way with its output. The output variable can be either output voltage or output current. For the following discussion, refer to the Block Diagram in Figure 1. The LTC4000-1 includes four different regulation loops: input voltage, charge current, battery float voltage and output voltage (A4-A7). Whichever loop requires the lowest voltage on the ITH pin for its regulation controls the external DC/DC converter. The input voltage regulation loop ensures that the input voltage level does not drop below the programmed level. The charge current regulation loop ensures that the programmed battery charge current limit (using a resistor at CL) is not exceeded. The float voltage regulation loop ensures that the programmed battery stack voltage (using a resistor divider from BAT to FBG via BFB) is not exceeded. The output voltage regulation loop ensures that the programmed system output voltage (using a resistor divider from CSP to FBG via OFB) is not exceeded. The LTC4000-1 also provides monitoring pins for the input current and charge current at the IIMON and IBMON pins respectively. The LTC4000-1 features an ideal diode controller at the input from the IID pin to the CSP pin and a PowerPath controller at the output from the BAT pin to the CSN pin. The output PowerPath controller behaves as an ideal diode controller when not charging. When charging, the output PowerPath controller has two modes of operation. If VOFB is greater than VOUT(INST_ON), BGATE is driven low. When VOFB is less than VOUT(INST_ON), a linear regulator implements the instant-on feature. This feature provides regulation of the BGATE pin so that a valid voltage level is immediately available at the output when the LTC4000-1 is charging an over-discharged, dead or short faulted battery. The state of the ENC pin determines whether charging is enabled. When ENC is grounded, charging is disabled and the battery float voltage loop is disabled. Charging is enabled when the ENC pin is left floating or pulled high (≥1.5V) The LTC4000-1 offers several user configurable battery charge termination schemes. The TMR pin can be configured for either C/X termination, charge timer termination or no termination. After a particular charge cycle terminates, the LTC4000-1 features an automatic recharge cycle if the battery voltage drops below 97.6% of the programmed float voltage. Trickle charge mode drops the charge current to one tenth of the normal charge current (programmed using a resistor from the CL pin to GND) when charging into an over discharged or dead battery. When trickle charging, a capacitor on the TMR pin can be used to program a time out period. When this bad battery timer expires and the battery voltage fails to charge above the low battery threshold (VLOBAT), the LTC4000-1 will terminate charging and indicate a bad battery condition through the status pins (FLT and CHRG). The LTC4000-1 also includes an NTC pin, which provides temperature qualified charging when connected to an NTC thermistor thermally coupled to the battery pack. To enable this feature, connect the thermistor between the NTC and the GND pins, and a corresponding resistor from the BIAS pin to the NTC pin. The LTC4000-1 also provides a charging status indicator through the FLT and the CHRG pins. Aside from biasing the thermistor-resistor network, the BIAS pin can also be used for a convenient pull up voltage. This pin is the output of a low dropout voltage regulator that is capable of providing up to 0.5mA of current. The regulated voltage on the BIAS pin is available as soon as the IN pin is within its operating range (≥3V). Input Ideal Diode The input ideal diode feature provides low loss conduction and reverse blocking from the IID pin to the CSP pin. This reverse blocking prevents reverse current from the output (CSP pin) to the input (IID pin) which causes unnecessary drain on the battery and in some cases may result in unexpected DC/DC converter behavior. The ideal diode behavior is achieved by controlling an external PMOS connected to the IID pin (drain) and the 40001f 13 LTC4000-1 Operation CSP pin (source). The controller (A1) regulates the external PMOS by driving the gate of the PMOS device such that the voltage drop across IID and CSP is 8mV (typical). When the external PMOS ability to deliver a particular current with an 8mV drop across its source and drain is exceeded, the voltage at the gate clamps at VIGATE(ON) and the PMOS behaves like a fixed value resistor (RDS(ON)). Input Voltage Regulation One of the loops driving the ITH and CC pins is the input voltage regulation loop (Figure 2). This loop prevents the input voltage from dropping below the programmed level. RIS IN CCLN (OPTIONAL) IN CLN LTC4000-1 CC RIFB1 RIFB2 IFB 1V – + A4 CC – + ITH Once the battery voltage is above VLOBAT, the charge current regulation loop begins charging in full power constantcurrent mode. In this case, the programmed full charge current is set with a resistor on the CL pin. Depending on available input power and external load conditions, the battery charger may not be able to charge at the full programmed rate. The external load is always prioritized over the battery charge current. The input voltage programming is always observed, and only additional power is available to charge the battery. When system loads are light, battery charge current is maximized. DC/DC INPUT CIN loop to set the battery charge current to 10% of the programmed full-scale value. If the TMR pin is connected to a capacitor or open, the bad battery detection timer is enabled. When this bad battery detection timer expires and the battery voltage is still below VLOBAT, the battery charger automatically terminates and indicates, via the FLT and CHRG pins, that the battery was unresponsive to charge current. RC TO DC/DC 40001 FO2 Figure 2. Input Voltage Regulation Loop When the input source is high impedance, the input voltage drops as the load current increases. In that case there exists a voltage level at which the available power from the input is maximum. For example, solar panels often specify VMP, corresponding to the panel voltage at which maximum power is achieved. With the LTC4000-1 input voltage regulation, this maximum power voltage level can be programmed at the IFB pin. The input voltage regulation loop regulates ITH to ensure that the input voltage level does not drop below this programmed level. Battery Charger Overview In addition to the input voltage regulation loop, the LTC4000-1 regulates charge current, battery voltage and output voltage. When a battery charge cycle begins, the battery charger first determines if the battery is over-discharged. If the battery feedback voltage is below VLOBAT, an automatic trickle charge feature uses the charge current regulation Once the float voltage is achieved, the battery float voltage regulation loop takes over from the charge current regulation loop and initiates constant voltage charging. In constant voltage charging, charge current slowly declines. Charge termination can be configured with the TMR pin in several ways. If the TMR pin is tied to the BIAS pin, C/X termination is selected. In this case, charging is terminated when constant voltage charging reduces the charge current to the C/X level programmed at the CX pin. Connecting a capacitor to the TMR pin selects the charge timer termination and a charge termination timer is started at the beginning of constant voltage charging. Charging terminates when the termination timer expires. When continuous charging at the float voltage is desired, tie the TMR pin to GND to disable termination. Upon charge termination, the PMOS connected to BGATE behaves as an ideal diode from BAT to CSN. The diode function prevents charge current but provides current to the system load as needed. If the system load can be completely supplied from the input, the battery PMOS turns off. While terminated, if the input voltage loop is not in regulation, the output voltage regulation loop takes over to ensure that the output voltage at CSP remains in control. 40001f 14 LTC4000-1 Operation The output voltage regulation loop regulates the voltage at the CSP pin such that the output feedback voltage at the OFB pin is 1.193V. If the system load requires more power than is available from the input, the battery ideal diode controller provides supplemental power from the battery. When the battery voltage discharges below 97.1% of the float voltage (VBFB < VRECHRG(FALL)), the automatic recharge feature initiates a new charge cycle. Charge Current Regulation The first loop involved in a normal charging cycle is the charge current regulation loop (Figure 3). This loop drives the ITH and CC pins. This loop ensures that the charge current sensed through the charge current sense resistor (RCS) does not exceed the programmed full charge current. BAT PMOS CIBMON (OPTIONAL) CSP CSN + – A9 gm = 0.33m 60k BIAS RCL LTC4000-1 BFB + – FBG 1.136V A6 CC CC – + ITH RC TO DC/DC 40001 FO4 Figure 4. Battery Float Voltage Regulation Loop with FBG Output Voltage Regulation When charging terminates and the system load is completely supplied from the input, the PMOS connected to BGATE is turned off. In this scenario, the output voltage regulation loop takes over from the battery float voltage regulation loop (Figure 5). The output voltage regulation loop regulates the voltage at the CSP pin such that the output feedback voltage at the OFB pin is 1.193V. ROFB1 CCSP IBMON RBFB2 BAT TO SYSTEM RIS CSP RBFB1 50µA AT NORMAL 1V 5µA AT TRICKLE ROFB2 LTC4000-1 CSP LTC4000-1 OFB + – FBG 1.193V A7 CC CC – + ITH RC TO DC/DC CC + – – A5 CC – + 40001 FO5 RC ITH TO DC/DC Figure 5. Output Voltage Regulation Loop with FBG Battery Instant-On and Ideal Diode CL 40001 FO3 Figure 3. Charge Current Regulation Loop Battery Voltage Regulation Once the float voltage is reached, the battery voltage regulation loop takes over from the charge current regulation loop (Figure 4). The float voltage level is programmed using the feedback resistor divider between the BAT pin and the FBG pin with the center node connected to the BFB pin. Note that the ground return of the resistor divider is connected to the FBG pin. The FBG pin disconnects the resistor divider load when VIN < 3V to ensure that the float voltage resistor divider does not consume battery current when the battery is the only available power source. For VIN ≥ 3V, the typical resistance from the FBG pin to GND is 100Ω. The LTC4000-1 controls the external PMOS connected to the BGATE pin with a controller similar to the input ideal diode controller driving the IGATE pin. When not charging, the PMOS behaves as an ideal diode between the BAT (anode) and the CSN (cathode) pins. The controller (A2) regulates the external PMOS to achieve low loss conduction by driving the gate of the PMOS device such that the voltage drop from the BAT pin to the CSN pin is 8mV. When the ability to deliver a particular current with an 8mV drop across the PMOS source and drain is exceeded, the voltage at the gate clamps at VBGATE(ON) and the PMOS behaves like a fixed value resistor (RDS(ON)). The ideal diode behavior allows the battery to provide current to the load when the input supply is in current limit or the DC/DC converter is slow to react to an immediate load increase at the output. In addition to the ideal diode 40001f 15 LTC4000-1 Operation behavior, BGATE also allows current to flow from the CSN pin to the BAT pin during charging. There are two regions of operation when current is flowing from the CSN pin to the BAT pin. The first is when charging into a battery whose voltage is below the instant-on threshold (VOFB < VOUT(INST_ON)). In this region of operation, the controller regulates the voltage at the CSP pin to be approximately 86% of the final float voltage level (VOUT(INST_ON)). This feature provides a CSP voltage significantly higher than the battery voltage when charging into a heavily discharged battery. This instant-on feature allows the LTC4000-1 to provide sufficient voltage at the output (CSP pin), independent of the battery voltage. The second region of operation is when the battery feedback voltage is greater than or equal to the instant-on threshold (VOUT(INST_ON)). In this region, the BGATE pin is driven low and clamped at VBGATE(ON) to allow the PMOS to turn completely on, reducing any power dissipation due to the charge current. Battery Temperature Qualified Charging The battery temperature is measured by placing a negative temperature coefficient (NTC) thermistor close to the battery pack. The comparators CP3 and CP4 implement the temperature detection as shown in the Block Diagram in Figure 1. The rising threshold of CP4 is set at 75% of VBIAS (cold threshold) and the falling threshold of CP3 is set at 35% of VBIAS (hot threshold). When the voltage at the NTC pin is above 75% of VBIAS or below 35% of VBIAS then the LTC4000-1 pauses any charge cycle in progress. When the voltage at the NTC pin returns to the range of 40% to 70% of VBIAS, charging resumes. When charging is paused, the external charging PMOS turns off and charge current drops to zero. If the LTC4000-1 is charging in the constant voltage mode and the charge termination timer is enabled, the timer pauses until the thermistor indicates a return to a valid temperature. If the battery charger is in the trickle charge mode and the bad battery detection timer is enabled, the bad battery timer pauses until the thermistor indicates a return to a valid temperature. Input UVLO and Voltage Monitoring The regulated voltage on the BIAS pin is available as soon as VIN ≥ 3V. When VIN ≥ 3V, the FBG pin is pulled low to GND with a typical resistance of 100Ω and the rest of the chip functionality is enabled. When the IN pin is high impedance and a battery is connected to the BAT pin, the BGATE pin is pulled down with a 2μA (typical) current source to hold the battery PMOS gate voltage at VBGATE(ON) below VBAT. This allows the battery to power the output. The total quiescent current consumed by LTC4000-1 from the battery when IN is not valid is typically ≤ 10µA. Besides the internal input UVLO, the LTC4000-1 also provides voltage monitoring through the VM pin. The RST pin is pulled low when the voltage on the VM pin falls below 1.193V (typical). On the other hand, when the voltage on the VM pin rises above 1.233V (typical), the RST pin is high impedance. One common use of this voltage monitoring feature is to ensure that the converter is turned off when the voltage at the input is below a certain level. In this case, connect the RST pin to the DC/DC converter chip select or enable pin (see Figure 6). RIS IN RVM1 IN VM IN CLN – DC/DC CONVERTER EN RST CP1 RVM2 1.193V + LTC4000-1 40001 FO6 Figure 6. Input Voltage Monitoring with RST Connected to the EN Pin of the DC/DC Converter 40001f 16 LTC4000-1 Applications Information Input Ideal Diode PMOS Selection The input external PMOS is selected based on the expected maximum current, power dissipation and reverse voltage drop. The PMOS must be able to withstand a gate to source voltage greater than VIGATE(ON) (15V maximum) or the maximum regulated voltage at the IID pin, whichever is less. A few appropriate external PMOS for a number of different requirements are shown at Table 1. The voltage on the IIMON pin can be filtered further by putting a capacitor on the pin (CIIMON). Charge Current Limit Setting and Monitoring The regulated full charge current is set according to the following formula: Table 1. PMOS RDS(ON) AT VGS = 10V (Ω) MAX ID (A) SiA923EDJ 0.054 4.5 –20 Vishay Si9407BDY 0.120 4.7 –60 Vishay Si4401BDY 0.014 10.5 –40 Vishay Si4435DDY 0.024 11.4 –30 Vishay SUD19P06-60 0.060 18.3 –60 Vishay Si7135DP 0.004 60 –30 Vishay PART NUMBER is strongly recommended. Where the highest accuracy is important, pick the value of CCLN such that the AC content is less than or equal to 50% of the average voltage across the sense resistor. MAX VDS (V) MANUFACTURER Note that in general the larger the capacitance seen on the IGATE pin, the slower the response of the ideal diode driver. The fast turn off and turn on current is limited to –0.5mA and 0.7mA typical respectively (IIGATE(FASTOFF) and IIGATE(FASTON)). If the driver can not react fast enough to a sudden increase in load current, most of the extra current is delivered through the body diode of the external PMOS. This increases the power dissipation momentarily. It is important to ensure that the PMOS is able to withstand this momentary increase in power dissipation. Input Current Monitoring The input current through the sense resistor is available for monitoring through the IIMON pin. The voltage on the IIMON pin varies with the current through the sense resistor as follows: VIIMON = 20 • IRIS • RIS = 20 • ( VIN – VCLN ) If the input current is noisy, add a filter capacitor to the CLN pin to reduce the AC content. For example, when using a buck DC/DC converter, the use of a CCLN capacitor RCS = VCL 20 • ICLIM where VCL is the voltage on the CL pin. The CL pin is internally pulled up with an accurate current source of 50µA. Therefore, an equivalent formula to obtain the charge current limit is: RCL = ICLIM • RCS R ⇒ ICLIM = CL • 2.5µA 2.5µA RCS The charge current through the sense resistor is available for monitoring through the IBMON pin. The voltage on the IBMON pin varies with the current through the sense resistor as follows: VIBMON = 20 • IRCS • RCS = 20 • ( VCSP – VCSN ) The regulation voltage level at the IBMON pin is clamped at 1V with an accurate internal reference. At 1V on the IBMON pin, the charge current limit is regulated to the following value: ICLIM(MAX)(A) = 0.050V RCS (Ω) When this maximum charge current limit is desired, leave the CL pin open or set it to a voltage >1.05V such that amplifier A5 can regulate the IBMON pin voltage accurately to the internal reference of 1V. When the output current waveform of the DC/DC converter or the system load current is noisy, it is recommended that 40001f 17 LTC4000-1 Applications Information a capacitor is connected to the CSP pin (CCSP). This is to reduce the AC content of the current through the sense resistor (RCS). Where the highest accuracy is important, pick the value of CCSP such that the AC content is less than or equal to 50% of the average voltage across the sense resistor. Similar to the IIMON pin, the voltage on the IBMON pin is filtered further by putting a capacitor on the pin (CIBMON). This filter capacitor should not be arbitrarily large as it will slow down the overall compensated charge current regulation loop. For details on the loop compensation, refer to the Compensation section. Battery Float Voltage Programming When the value of RBFB1 is much larger than 100Ω, the final float voltage is determined using the following formula: V RBFB1 = FLOAT – 1 RBFB2 1.136V When higher accuracy is important, a slightly more accurate final float voltage can be determined using the following formula: R R +R VFLOAT = BFB1 BFB2 •1.136V – BFB1 • VFBG RBFB2 RBFB2 where VFBG is the voltage at the FBG pin during float voltage regulation, which accounts for all the current from all resistor dividers that are connected to this pin (RFBG = 100Ω typical). Low Battery Trickle Charge Programming and Bad Battery Detection When charging into an over-discharged or dead battery (VBFB < VLOBAT), the pull-up current at the CL pin is reduced to 10% of the normal pull-up current. Therefore, the trickle charge current is set using the following formula: RCL = ICLIM(TRKL) • RCS 0.25µA ⇒ ICLIM(TRKL) = 0.25µA • RCL RCS Therefore, when 50µA•RCL is less than 1V, the following relation is true: ICLIM(TRKL) = ICLIM 10 Once the battery voltage rises above the low battery voltage threshold, the charge current level rises from the trickle charge current level to the full charge current level. The LTC4000-1 also features bad battery detection. This detection is disabled if the TMR pin is grounded or tied to BIAS. However, when a capacitor is connected to the TMR pin, a bad battery detection timer is started as soon as trickle charging starts. If at the end of the bad battery detection time the battery voltage is still lower than the low battery threshold, charging is terminated and the part indicates a bad battery condition by pulling the FLT pin low and leaving the CHRG pin high impedance. The bad battery detection time can be programmed according to the following formula: CTMR (nF) = tBADBAT (h) • 138.5 Note that once a bad battery condition is detected, the condition is latched. In order to re-enable charging, remove the battery and connect a new battery whose voltage causes BFB to rise above the recharge battery threshold (VRECHRG(RISE)). Alternatively toggle the ENC pin or remove and reapply power to IN. C/X Detection, Charge Termination and Automatic Recharge Once the constant voltage charging is reached, there are two ways in which charging can terminate. If the TMR pin is tied to BIAS, the battery charger terminates as soon as the charge current drops to the level programmed by the CX pin. The C/X current termination level is programmed according to the following formula: RCX = IC/ X • RCS (0.25µA • RCX ) − 0.5mV + 0.5mV ⇒ IC/X = 0.25µA RCS 40001f 18 LTC4000-1 Applications Information where RCS is the charge current sense resistor connected between the CSP and the CSN pins. When the voltage at BFB is higher than the recharge threshold (97.6% of float), the C/X comparator is enabled. In order to ensure proper C/X termination coming out of a paused charging condition, connect a capacitor on the CX pin according to the following formula: CCX = 100CBGATE where CBGATE is the total capacitance connected to the BGATE pin. For example, a typical capacitance of 1nF requires a capacitor greater than 100nF connected to the CX pin to ensure proper C/X termination behavior. If a capacitor is connected to the TMR pin, as soon as the constant voltage charging is achieved, a charge termination timer is started. When the charge termination timer expires, the charge cycle terminates. The total charge termination time can be programmed according to the following formula: CTMR (nF) = t TERMINATE (h) • 34.6 If the TMR pin is grounded, charging never terminates and the battery voltage is held at the float voltage. Note that regardless of which termination behavior is selected, the CHRG and FLT pins will both assume a high impedance state as soon as the charge current falls below the programmed C/X level. As in the battery float voltage calculation, when higher accuracy is important, a slightly more accurate output is determined using the following formula: R R +R VOUT = OFB1 OFB2 • 1.193V – OFB1 • VFBG ROFB2 ROFB2 where VFBG is the voltage at the FBG pin during output voltage regulation, which accounts for all the current from all resistor dividers that are connected to this pin. Battery Instant-On and Ideal Diode External PMOS Consideration The instant-on voltage level is determined using the following formula: ROFB1 + ROFB2 • 0.974V ROFB2 Note that ROFB1 and ROFB2 are the same resistors that program the output voltage regulation level. Therefore, the output voltage regulation level is always 122.5% of the instant-on voltage level. VOUT(INST _ ON) = During instant-on operation, it is critical to consider the charging PMOS power dissipation. When the battery voltage is below the low battery threshold (VLOBAT), the power dissipation in the PMOS can be calculated as follows: PTRKL = [0.86 • VFLOAT – VBAT ] • ICLIM(TRKL) where ICLIM(TRKL) is the trickle charge current limit. After the charger terminates, the LTC4000-1 automatically restarts another charge cycle if the battery feedback voltage drops below 97.1% of the programmed final float voltage (VRECHRG(FALL)). When charging restarts, the CHRG pin pulls low and the FLT pin remains high impedance. On the other hand, when the battery voltage is above the low battery threshold but still below the instant-on threshold, the power dissipation can be calculated as follows: Output Voltage Regulation Programming where ICLIM is the full scale charge current limit. The output voltage regulation level is determined using the following formula: For example, when charging a 3-cell Lithium Ion battery with a programmed full charged current of 1A, the float voltage is 12.6V, the bad battery voltage level is 8.55V and the instant-on voltage level is 10.8V. During instant-on operation and in the trickle charge mode, the worst case V ROFB1 = OUT − 1 • ROFB2 1.193 PINST _ ON = [0.86 • VFLOAT – VBAT ] • ICLIM 40001f 19 LTC4000-1 Applications Information maximum power dissipation in the PMOS is 1.08W. When the battery voltage is above the bad battery voltage level, then the worst case maximum power dissipation is 2.25W. RBFB1 + RBFB2 • 1.136V RBFB2 +R R = OFB1 OFB2 • 1.193V ROFB2 VFLOAT = VOUT When overheating of the charging PMOS is a concern, it is recommended that the user add a temperature detection circuit that pulls down on the NTC pin. This pauses charging whenever the external PMOS temperature is too high. A sample circuit that performs this temperature detection function is shown in Figure 7. VOUT(INST _ ON) = ROFB1 + ROFB2 • 0.974V ROFB2 In the typical application, VOUT is set higher than VFLOAT to ensure that the battery is charged fully to its intended float voltage. On the other hand, VOUT should not be programmed too high since VOUT(INST_ON), the minimum voltage on CSP, depends on the same resistors ROFB1 and ROFB2 that set VOUT. As noted before, this means that the output voltage regulation level is always 122.5% of the instant-on voltage. The higher the programmed value of VOUT(INST_ON), the larger the operating region when the charger PMOS is driven in the linear region where it is less efficient. Similar to the input external PMOS, the charging external PMOS must be able to withstand a gate to source voltage greater than VBGATE(ON) (15V maximum) or the maximum regulated voltage at the CSP pin, whichever is less. Consider the expected maximum current, power dissipation and instant-on voltage drop when selecting this PMOS. The PMOS suggestions in Table 1 are an appropriate starting point depending on the application. Float Voltage, Output Voltage and Instant-On Voltage Dependencies If ROFB1 and ROFB2 are set to be equal to RBFB1 and RBFB2 respectively, then the output voltage is set at 105% of the float voltage and the instant-on voltage is set at 86% of the float voltage. Figure 8 shows the range of possible The formulas for setting the float voltage, output voltage and instant-on voltage are repeated here: TO SYSTEM CSP RCS LTC4000-1 VISHAY CURVE 2 NTC RESISTOR THERMALLY COUPLED WITH CHARGING PMOS RNTC2 CSN BGATE M2 R4 = RNTC2 AT 25°C BAT BIAS R3 CBIAS 162k 2N7002L NTC Li-Ion BATTERY PACK RNTC1 LTC1540 – + RISING TEMPERATURE THRESHOLD SET AT 90°C 20k VOLTAGE HYSTERESIS CAN BE PROGRAMMED FOR TEMPERATURE HYSTERESIS 86mV ≈ 10°C 40001 F07 Figure 7. Charging PMOS Overtemperature Detection Circuit Protecting PMOS from Overheating 40001f 20 LTC4000-1 Applications Information POSSIBLE OUTPUT VOLTAGE RANGE 105% NOMINAL OUTPUT VOLTAGE NOMINAL FLOAT VOLTAGE POSSIBLE INSTANT-ON VOLTAGE RANGE 100% MINIMUM PRACTICAL OUTPUT VOLTAGE 100% 100% 86% NOMINAL INSTANT-ON VOLTAGE MINIMUM PRACTICAL INSTANT-ON VOLTAGE 81.6% 75% 40001 F08 Figure 8. Possible Voltage Ranges for VOUT and VOUT(INST_ON) in Ideal Scenario output voltages that can be set for VOUT(INST_ON) and VOUT with respect to VFLOAT to ensure the battery can be fully charged in an ideal scenario. Taking into account possible mismatches between the resistor dividers as well as mismatches in the various regulation loops, VOUT should not be programmed to be less than 105% of VFLOAT to ensure that the battery can be fully charged. This automatically means that the instant-on voltage level should not be programmed to be less than 86% of VFLOAT. Battery Temperature Qualified Charging To use the battery temperature qualified charging feature, connect an NTC thermistor, RNTC, between the NTC pin and the GND pin, and a bias resistor, R3, from the BIAS pin to the NTC pin (Figure 9). Thermistor manufacturer datasheets usually include either a temperature lookup table or a formula relating temperature to the resistor value at that corresponding temperature. In a simple application, R3 is a 1% resistor with a value equal to the value of the chosen NTC thermistor at 25°C (R25). In this simple setup, the LTC4000-1 will pause charging when the resistance of the NTC thermistor drops to 0.54 times the value of R25. For a Vishay Curve 2 thermistor, this corresponds to approximately 41.5°C. As the temperature drops, the resistance of the NTC thermistor rises. The LTC4000-1 is also designed to pause charging when the value of the NTC thermistor increases to three times the value of R25. For a Vishay Curve 2 thermistor, this corresponds to approximately –1.5°C. With Vishay Curve 2 thermistor, the hot and cold comparators each have approximately 5°C of hysteresis to prevent oscillation about the trip point. The hot and cold threshold can be adjusted by changing the value of R3. Instead of simply setting R3 to be equal to R25, R3 is set according to one of the following formulas: R3 = RNTC at cold_ threshold 3 or BIAS LTC4000-1 R3 CBIAS NTC BAT NTC RESISTOR THERMALLY COUPLED WITH BATTERY PACK RNTC 40001 F09 R3 = 1.857 • RNTC at hot _ threshold Notice that with only one degree of freedom (i.e. adjusting the value of R3), the user can only use one of the formulas above to set either the cold or hot threshold but not both. If the value of R3 is set to adjust the cold threshold, the value of the NTC resistor at the hot threshold is then Figure 9. NTC Thermistor Connection 40001f 21 LTC4000-1 Applications Information equal to 0.179 • RNTC at cold_threshold. Similarly, if the value of R3 is set to adjust the hot threshold, the value of the NTC resistor at the cold threshold is then equal to 5.571 • RNTC at cold_threshold. Note that changing the value of R3 to be larger than R25 will move both the hot and cold threshold lower and vice versa. For example, using a Vishay Curve 2 thermistor whose nominal value at 25°C is 100k, the user can set the cold temperature to be at 5°C by setting the value of R3 = 75k, which automatically then sets the hot threshold at approximately 50°C. It is possible to adjust the hot and cold threshold independently by introducing another resistor as a second degree of freedom (Figure 10). The resistor RD in effect reduces the sensitivity of the resistance between the NTC pin and ground. Therefore, intuitively this resistor will move the hot threshold to a hotter temperature and the cold threshold to a colder temperature. BIAS LTC4000-1 R3 CBIAS NTC RD For example, this method can be used to set the hot and cold thresholds independently to 60°C and –5°C. Using a Vishay Curve 2 thermistor whose nominal value at 25°C is 100k, the formula results in R3 = 130k and RD = 41.2k for the closest 1% resistors values. To increase thermal sensitivity such that the valid charging temperature band is much smaller than 40°C, it is possible to put a PTC (positive thermal coefficient) resistor in series with R3 between the BIAS pin and the NTC pin. This PTC resistor also needs to be thermally coupled with the battery. Note that this method increases the number of thermal sensing connections to the battery pack from one wire to three wires. The exact value of the nominal PTC resistor required can be calculated using a similar method as described above, keeping in mind that the threshold at the NTC pin is always 75% and 35% of VBIAS. Leaving the NTC pin floating or connecting it to a capacitor disables all NTC functionality. Battery Voltage Temperature Compensation BAT NTC RESISTOR THERMALLY COUPLED WITH BATTERY PACK if the user finds that a negative value is needed for RD, the two temperature thresholds selected are too close to each other and a higher sensitivity thermistor is needed. RNTC 40001 F10 Figure 10. NTC Thermistor Connection with Desensitizing Resistor RD The value of R3 and RD can now be set according to the following formula: Some battery chemistries have charge voltage requirements that vary with temperature. Lead-acid batteries in particular experience a significant change in charge voltage requirements as temperature changes. For example, manufacturers of large lead-acid batteries recommend a float charge of 2.25V/cell at 25°C. This battery float voltage, however, has a temperature coefficient which is typically specified at –3.3mV/°C per cell. 1.219 • RNTC at hot _ threshold The LTC4000-1 employs a resistor feedback network to program the battery float voltage. manipulation of this network makes for an efficient implementation of various temperature compensation schemes of battery float voltage. Note the important caveat that this method can only be used to desensitize the thermal effect on the thermistor and hence push the hot and cold temperature thresholds apart from each other. When using the formulas above, A simple solution for tracking such a linear voltage dependence on temperature is to use the LM234 3-terminal temperature sensor. This creates an easily programmable linear temperature dependent characteristic. RNTC at cold_ threshold – RNTC at hot _ threshold 2.461 RD = 0.219 • RNTC at cold_ threshold – R3 = 40001f 22 LTC4000-1 Applications Information (TC = –19.8mV/°C and VFLOAT(25°C) = 13.5V) and RSET = 2.43k into the equation, we obtained the following values: RBFB1 = 210k and RBFB2 = 13.0k. 14.4 14.2 14.0 VFLOAT (V) 13.8 3-Step Charging for Lead-Acid Battery 13.6 13.4 13.2 13.0 12.8 12.6 –10 0 20 40 10 30 TEMPERATURE (°C) 60 50 40001 F11 Figure 11. Lead-Acid 6-Cell Float Charge Voltage vs Temperature Using LM234 with the Feedback Network TRICKLE CHARGE BAT CONSTANT CURRENT RBFB1 210k TERMINATION V+ R RSET 2.43k BFB RBFB2 13.0k BATTERY VOLTAGE V– 6-CELL LEAD-ACID BATTERY CHARGE CURRENT 40001 F12 Figure 12. Battery Voltage Temperature Compensation Circuit RBFB1 = –RSET • (TC • 4405) and RBFB1 • 1.136V 0.0677 VFLOAT(25°C) + RBFB1 • R – 1.136V SET 40001 F13 CHARGE TIME Figure 13. Li-Ion Typical Charging Cycle In the circuit shown in Figure 12, RBFB2 = CONSTANT VOLTAGE LM234 LTC4000-1 FBG The LTC4000-1 naturally lends itself to charging applications requiring a constant current step followed by constant voltage. Furthermore, the LTC4000-1 additional features such as trickle charging, bad battery detection and C/X or timer termination makes it an excellent fit for Lithium based battery charging applications. Figure 13 and Table 2 show the normal steps involved in Lithium battery charging. Table 2. Lithium Based Battery Charging Steps STEP CHARGE METHOD DURATION Trickle Charge Constant Current at a Lower Current Value, Usually 1/10th of Full Charge Current Until Battery Voltage Rises Above Low Battery Threshold Constant Current at Full Charge Current Until Battery Voltage Reaches Float Voltage Constant Current Time Limit Set at TMR Pin No Time Limit Where: TC = temperature coefficient in V/°C and VFLOAT(25°C) is the desired battery float voltage at 25°C in V. Constant Voltage Constant Voltage For example, a 6-cell lead-acid battery has a float charge voltage that is commonly specified at 2.25V/cell at 25°C or 13.5V, and a –3.3mV/°C per cell temperature coefficient or –19.8mV/°C. Substituting these two parameters Recharge Initiate Constant Current Again When Battery Voltage Drops Below Recharge Threshold Terminate Either When Charge Current Falls to the Programmed Level at the CX Pin or after the Termination Timer at TMR Pin Expires 40001f 23 LTC4000-1 Applications Information On the other hand, the LTC4000-1 is also easily configurable to handle lead-acid based battery charging. One of the common methods used in lead-acid battery charging is called 3-step charging (Bulk, Absorption and Float). Figure 14 and Table 3 summarize the normal steps involved in a typical 3-step charging of a lead-acid battery. FROM DC/DC OUTPUT LTC4000-1 CSP RCS CSN BAT FBG RBFB2 BFB RBFB1 RBFB3 CX BATTERY VOLTAGE BULK CHARGE ABSORPTION FLOAT (STORAGE) RCX CL CHRG LEAD-ACID BATTERY RCL 40001 F15 Figure 15. 3-Step Lead-Acid Circuit Configuration CHARGE CURRENT 40001 F14 CHARGE TIME When a charging cycle is initiated, the CHRG pin is pulled low. The charger first enters the bulk charge step, charging the battery with a constant current programmed at the CL pin: Figure 14. Lead-Acid 3-Step Charging Cycle Table 3. Lead-Acid Battery Charging Steps STEP CHARGE METHOD DURATION Bulk Charge Constant Current Until Battery Voltage Reaches Absorption Voltage Absorption Constant Voltage at the Absorption Voltage Level Terminate When Charge Current Falls to the Programmed Level at the CX Pin Float (Storage) Constant Voltage at the Lower Float Voltage Level (Float Voltage Is Lower than the Absorption Voltage) Indefinite No Time Limit Recharge Initiate Bulk Charge Again When Battery Voltage Drops Below Recharge Threshold Figure 15 shows the configuration needed to implement this 3-step lead-acid battery charging with the LTC4000-1. ICLIM = MIN( 50mV, 2.5µA • RCL ) RCS When the battery voltage rises to the Absorption voltage level: R (R + RBFB3 ) + 1 • 1.136V VABSRP = BFB1 BFB2 RBFB2RBFB3 the charger enters the Absorption step, charging the battery at a constant voltage at this absorption voltage level. As the charge current drops to the C/X level: ICLIM = (0.25µA • RCX ) – 0.5mV RCS the CHRG pin turns high impedance and now the charger enters the Float (Storage) step, charging the battery voltage at the constant float voltage level: R VFLOAT = BFB1 + 1 • 1.136V RBFB2 40001f 24 LTC4000-1 Applications Information Note that in this configuration, the recharge threshold is 97.6% of the float voltage level. When the battery voltage drops below this level, the whole 3-step charging cycle is reinitiated starting with the bulk charge. Some systems require trickle charging of an over discharged lead-acid battery. This feature can be included using the CL pin of the LTC4000-1. In the configuration shown in Figure 15, when the battery voltage is lower than 68% of the Absorption level, the pull-up current on the CL pin is reduced to 10% of the normal pull-up current. Therefore, the trickle charge current can be set at the following level: ICLIM = MIN( 50mV, 0.25µA • RCL ) RCS If this feature is not desired, leave the CL pin open to set the regulation voltage across the charge current sense resistor (RCS) always at 50mV. The FLT and CHRG Indicator Pins The FLT and CHRG pins in the LTC4000-1 provide status indicators. Table 4 summarizes the mapping of the pin states to the part status. Table 4. FLT and CHRG Status Indicator FLT CHRG 0 0 STATUS NTC Over Ranged – Charging Paused 1 0 Charging Normally 0 1 Charging Terminated and Bad Battery Detected 1 1 VIBMON < (VC/X – 10mV) where 1 indicates a high impedance state and 0 indicates a low impedance pull-down state. Note that VIBMON < (VCX – 10mV) corresponds to charge termination only if the C/X termination is selected. If the charger timer termination is selected, constant voltage charging may continue for the remaining charger timer period even after the indicator pins indicate that VIBMON < (VCX – 10mV). This is also true when no termination is selected, constant voltage charging will continue even after the indicator pins indicate that VIBMON < (VCX – 10mV). The BIAS Pin For ease of use the LTC4000-1 provides a low dropout voltage regulator output on the BIAS pin. Designed to provide up to 0.5mA of current at 2.9V, this pin requires at least 470nF of low ESR bypass capacitance for stability. Use the BIAS pin as the pull-up source for the NTC resistor networks, since the internal reference for the NTC circuitry is based on a ratio of the voltage on the BIAS pin. Furthermore, various 100k pull-up resistors can be conveniently connected to the BIAS pin. Setting the Input Voltage Monitoring Resistor Divider The falling threshold voltage level for this monitoring function can be calculated as follows: V RVM1 = VM _ RST – 1 • R VM2 1.193V where RVM1 and RVM2 form a resistor divider connected between the monitored voltage and GND, with the center tap point connected to the VM pin as shown in Figure 6. The rising threshold voltage level can be calculated similarly. Input Voltage Programming Connecting a resistor divider from VIN to the IFB pin enables programming of a minimum input supply voltage. This feature is typically used to program the peak power voltage for a high impedance input source. Referring to Figure 2, the input voltage regulation level is determined using the following formula: V RIFB1 = IN _ REG – 1 RIFB2 1V Where VIN_REG is the minimum regulation input voltage level, below which the current draw from the input source is reduced. Combining the Input Voltage Programming and the Input Voltage Monitoring Resistor Divider When connected to the same input voltage node, the input voltage monitoring and the input voltage regulation resistor divider can be combined (see Figure 16). 40001f 25 LTC4000-1 Applications Information RIS IN DC/DC INPUT CCLN (OPTIONAL) CIN RVM3 IN CLN VM – 1.193V + TO DC/DC EN PIN RST CP1 CVM CC RVM4 IFB RIFB2 1V – + A4 LTC4000-1 CC – + RC ITH TO DC/DC COMPENSATION PIN 40001 F16 Figure 16. Input Voltage Monitoring and Input Voltage Regulation Resistor Divider Combined In this configuration use the following formula to determine the values of the three resistors: 1.193V VIN _ REG RVM3 = 1– RIFB2 VVM _ RST 1V MPPT Temperature Compensation – Solar Panel Example The input regulation loop of the LTC4000-1 allows a user to program a minimum input supply voltage regulation level allowing for high impedance source to provide maximum available power. With typical high impedance source such as a solar panel, this maximum power point varies with temperature. A typical solar panel is comprised of a number of seriesconnected cells, each cell being a forward-biased p-n junction. As such, the open-circuit voltage (VOC) of a solar cell has a temperature coefficient that is similar to a common p-n junction diode, about –2mV/°C. The peak power point voltage (VMP) for a crystalline solar panel can be approximated as a fixed percentage of VOC, so the temperature coefficient for the peak power point is similar to that of VOC. Panel manufacturers typically specify the 25°C values for VOC, VMP and the temperature coefficient for VOC, making determination of the temperature coefficient for VMP of a typical panel straight forward. V RVM4 = 1.193 IN _ REG – 1 RIFB2 VVM _ RST When the RST pin of the LTC4000-1 is connected to the SHDN or RUN pin of the converter, it is recommended that the value of VIN_REG is set higher than the VVM_RST pin by a significant margin. This is to ensure that any voltage noise or ripple on the input supply pin does not cause the RST pin to shut down the converter prematurely, preventing the input regulation loop from functioning as expected. As discussed in the input current monitoring section, noise issues on the input node can be reduced by placing a large filter capacitor on the CLN node (CCLN). To further reduce the effect of any noise on the monitoring function, another filter capacitor placed on the VM pin (CVM) is recommended. PANEL VOLTAGE Note that for the RVM4 value to be positive, the ratio of VIN_REG to VVM_RST has to be greater than 0.838. VOC TEMP CO. VOC(25°C) VOC VMP(25°C) VOC – VMP VMP 5 15 25 35 TEMPERATURE (°C) 45 55 40001 F17 Figure 17. Temperature Characteristic of a Solar Panel Open Circuit and Peak Power Point Voltages In a manner similar to the battery float voltage temperature compensation, implementation of the MPPT temperature compensation can be accomplished by incorporating an LM234 into the input voltage feedback network. Using the 40001f 26 LTC4000-1 Applications Information feedback network in Figure 18, a similar set of equations can be used to determine the resistor values: RIFB1 = –RSET • (TC • 4405) and RIFB2 = RIFB1 • 1V 0.0677 VMP(25°C) + RIFB1 • R – 1V SET Where: TC = temperature coefficient in V/°C, and VMP(25°C) = maximum power point voltage at 25°C in V. VIN IN LM234 V+ R V– RSET 1k LTC4000-1 RIFB1 348k IFB RIFB2 8.66k 40001 F18 Figure 18. Maximum Power Point Voltage Temperature Compensation Feedback Network For example, given a common 36-cell solar panel that has the following specified characteristics: Open circuit voltage (VOC) = 21.7V Maximum power voltage (VMP) = 17.6V Open-circuit voltage temperature coefficient (VOC) = –78mV/°C As the temperature coefficient for VMP is similar to that of VOC, the specified temperature coefficient for VOC (TC) of –78mV/°C and the specified peak power voltage (VMP(25°C)) of 17.6V can be inserted into the equations to calculate the appropriate resistor values for the temperature compensation network in Figure 18. With RSET equal to 1kΩ, then: RSET = 1kΩ, RIFB1 = 348kΩ, RIFB2 = 8.66kΩ. typical sinking capability of the LTC4000-1 at the ITH pin is 1mA at 0.4V with a maximum voltage range of 0V to 6V. It is imperative that the local feedback of the DC/DC converter be set up such that during regulation of any of the LTC4000-1 loops this local loop is out of regulation and sources as much current as possible from its ITH/VC pin. For example for a DC/DC converter regulating its output voltage, it is recommended that the converter feedback divider is programmed to be greater than 110% of the output voltage regulation level programmed at the OFB pin. There are four feedback loops to consider when setting up the compensation for the LTC4000-1. As mentioned before these loops are: the input voltage loop, the charge current loop, the float voltage loop and the output voltage loop. All of these loops have an error amp (A4-A7) followed by another amplifier (A10) with the intermediate node driving the CC pin and the output of A10 driving the ITH pin as shown in Figure 19. The most common compensation network of a series capacitor (CC) and resistor (RC) between the CC pin and the ITH pin is shown here. Each of the loops has slightly different dynamics due to differences in the feedback signal path. The analytic description of the input voltage regulation loop is included in the Appendix section. Please refer to the LTC4000 data sheet for the analytic description of the other three loops. In most situations, an alternative empirical approach to compensation, as described here, is more practical. A4-A7 gm4-7 = 0.2m + – LTC4000-1 RO4-7 CC A10 gm10 = 0.1m – + ITH CC RC RO10 40001 F11 Figure 19. Error Amplifier Followed by Output Amplifier Driving CC and ITH Pins Compensation Empirical Loop Compensation In order for the LTC4000-1 to control the external DC/DC converter, it has to be able to overcome the sourcing bias current of the ITH or VC pin of the DC/DC converter. The Based on the analytical expressions and the transfer function from the ITH pin to the input and output current of the external DC/DC converter, the user can analytically 40001f 27 LTC4000-1 Applications Information determine the complete loop transfer function of each of the loops. Once these are obtained, it is a matter of analyzing the gain and phase bode plots to ensure that there is enough phase and gain margin at unity crossover with the selected values of RC and CC for all operating conditions. may cause a blinking scope display and higher frequencies may not allow sufficient settling time for the output transient. Amplitude of the generator output is typically set at 5VP-P to generate a 100mAP-P load variation. For lightly loaded outputs (IOUT < 100mA), this level may be too high for small signal response. If the positive and negative transition settling waveforms are significantly different, amplitude should be reduced. Actual amplitude is not particularly important because it is the shape of the resulting regulator output waveform which indicates loop stability. Even though it is clear that an analytical compensation method is possible, sometimes certain complications render this method difficult to tackle. These complications include the lack of easy availability of the switching converter transfer function from the ITH or VC control node to its input or output current, and the variability of parameter values of the components such as the ESR of the output capacitor or the RDS(ON) of the external PFETs. A 2-pole oscilloscope filter with f = 10kHz is used to block switching frequencies. Regulators without added LC output filters have switching frequency signals at their outputs which may be much higher amplitude than the low frequency settling waveform to be studied. The filter frequency is high enough for most applications to pass the settling waveform with no distortion. Therefore a simpler and more practical way to compensate the LTC4000-1 is provided here. This empirical method involves injecting an AC signal into the loop, observing the loop transient response and adjusting the CC and RC values to quickly iterate towards the final values. Much of the detail of this method is derived from Application Note 19 which can be found at www.linear.com using AN19 in the search box. Oscilloscope and generator connections should be made exactly as shown in Figure 20 to prevent ground loop errors. The oscilloscope is synced by connecting the channel B probe to the generator output, with the ground clip of the second probe connected to exactly the same place as channel A ground. The standard 50Ω BNC sync output of the generator should not be used because of ground loop errors. It may also be necessary to isolate either the generator or oscilloscope from its third wire (earth Figure 20 shows the recommended setup to inject an AC-coupled output load variation into the loop. A function generator with 50Ω output impedance is coupled through a 50Ω/1000µF series RC network to the regulator output. Generator frequency is set at 50Hz. Lower frequencies SWITCHING CONVERTER GND ITH 1k 0.015µF RC CC CLN ITH CC CSP LTC4000-1 IN IOUT A 10k B 1500pF 50Ω 1W 1000µF (OBSERVE POLARITY) SCOPE GROUND CLIP CSN GND BAT BGATE VIN 50Ω GENERATOR f = 50Hz 40001 F20 Figure 20. Empirical Loop Compensation Setup 40001f 28 LTC4000-1 Applications Information ground) connection in the power plug to prevent ground loop errors in the scope display. These ground loop errors are checked by connecting channel A probe tip to exactly the same point as the probe ground clip. Any reading on channel A indicates a ground loop problem. Once the proper setup is made, finding the optimum values for the frequency compensation network is fairly straightforward. Initially, CC is made large (≥1μF) and RC is made small (≈10k). This nearly always ensures that the regulator will be stable enough to start iteration. Now, if the regulator output waveform is single-pole over damped (see the waveforms in Figure 21), the value of CC is reduced in steps of about 2:1 until the response becomes slightly under damped. Next, RC is increased in steps of 2:1 to introduce a loop zero. This will normally improve damping and allow the value of CC to be further reduced. Shifting back and forth between RC and CC variations will allow one to quickly find optimum values. If the regulator response is under damped with the initial large value of CC, RC should be increased immediately before larger values of CC are tried. This will normally bring about the over damped starting condition for further iteration. The optimum values for RC and CC normally means the smallest value for CC and the largest value for RC which still guarantee well damped response, and which result in GENERATOR OUTPUT REGULATOR OUTPUT WITH LARGE CC, SMALL RC WITH REDUCED CC, SMALL RC EFFECT OF INCREASED RC FURTHER REDUCTION IN CC MAY BE POSSIBLE IMPROPER VALUES WILL CAUSE OSCILLATIONS 40001 F21 Figure 21. Typical Output Transient Response at Various Stability Level the largest loop bandwidth and hence loop settling that is as rapid as possible. The reason for this approach is that it minimizes the variations in output voltage caused by input ripple voltage and output load transients. A switching regulator which is grossly over damped will never oscillate, but it may have unacceptably large output transients following sudden changes in input voltage or output loading. It may also suffer from excessive overshoot problems on startup or short circuit recovery. To guarantee acceptable loop stability under all conditions, the initial values chosen for RC and CC should be checked under all conditions of input voltage and load current. The simplest way of accomplishing this is to apply load currents of minimum, maximum and several points in between. At each load current, input voltage is varied from minimum to maximum while observing the settling waveform. If large temperature variations are expected for the system, stability checks should also be done at the temperature extremes. There can be significant temperature variations in several key component parameters which affect stability; in particular, input and output capacitor value and their ESR, and inductor permeability. The external converter parametric variations also need some consideration especially the transfer function from the ITH/VC pin voltage to the output variable (voltage or current). The LTC4000-1 parameters that vary with temperature include the transconductance and the output resistance of the error amplifiers (A4-A7). For modest temperature variations, conservative over damping under worst-case room temperature conditions is usually sufficient to guarantee adequate stability at all temperatures. One measure of stability margin is to vary the selected values of both RC and CC by 2:1 in all four possible combinations. If the regulator response remains reasonably well damped under all conditions, the regulator can be considered fairly tolerant of parametric variations. Any tendency towards an under damped (ringing) response indicates that a more conservative compensation may be needed. 40001f 29 LTC4000-1 Applications Information Design Example • RCL is set at 24.9kΩ such that the voltage at the CL pin is 1.25V. Similar to the IIMON pin, the regulation voltage on the IBMON pin is clamped at 1V with an accurate internal reference. Therefore, the charge current limit is set at 10A according to the following formula: In this design example, the LTC4000-1 is paired with the LT3845A buck converter to create a 10A, 3-cell LiFePO4 battery charger. The circuit is shown on the front page and is repeated here in Figure 22. • With RIFB2 set at 20k, the input voltage monitoring falling threshold is set at 15V and the input voltage regulation level is set at 17.6V according to the following formulas: ICLIM(MAX) = 0.050V 0.050V = = 10A RCS 5mΩ • The trickle charge current level is consequently set at 1.25A, according to the following formula: 1.193V 17.6V RVM3 = 1− 20kΩ = 324kΩ 15V 1V ICLIM(TRKL) = 0.25µA • 17.6V RVM4 = 1.193V − 1 20kΩ = 8.06kΩ 15V 24.9kΩ = 1.25A 5mΩ • The battery float voltage is set at 10.8V according to the following formula: • The input current sense resistor is set at 5mΩ. Therefore, the voltage at the IIMON pin is related to the input current according to the following formula: 10.8 RBFB1 = − 1 • 133kΩ ≈ 1.13MΩ 1.136 VIIMON = (0.1Ω) • IRIS SOLAR PANEL INPUT <60V OPEN CIRCUIT VOLTAGE 17.6V PEAK POWER VOLTAGE 5mΩ LT3845A IN BIAS VC SHDN 1M 324k 20k 1.15M 47nF ITH CC IID IGATE CSP 5mΩ Si7135DP CSN BGATE BAT 1µF OFB VM 8.06k VOUT 12V, 15A 100µF 14.7k RST CLN IN Si7135DP OUT 127k LTC4000-1 3.0V FBG 133k IFB ENC CHRG FLT IIMON BFB 1.13M NTC IBMON TMR 10k GND BIAS BIAS 10nF 10nF CX CL 0.1µF 24.9k 22.1k 1µF 10k NTHS0603 N02N1002J VBAT 10.8V FLOAT 10A MAX CHARGE CURRENT 3-CELL Li-Ion BATTERY PACK 40001 F22 Figure 22. 10.8V at 10A Charger for Three LiFePO4 Cells with Solar Panel Input 40001f 30 LTC4000-1 Applications Information • The bad battery detection time is set at 43 minutes according to the following formula: CTMR (nF) = tBADBAT (h) • 138.5 = 43 • 138.5 = 100nF 60 • The charge termination time is set at 2.9 hours according to the following formula: CTMR (nF) = t TERMINATE (h) • 34.6 = 2.9 • 34.6 = 100nF • The C/X current termination level is programmed at 1A according to the following formula: RCX = (1A • 5mΩ) + 0.5mV ≈ 22.1kΩ 0.25µA Note that in this particular solution, the timer termination is selected since a capacitor connects to the TMR pin. Therefore, this C/X current termination level only applies to the CHRG indicator pin. • The output voltage regulation level is set at 12V according to the following formula: 12 ROFB1 = − 1 • 127kΩ ≈ 1.15MΩ 1.193 • The instant-on voltage level is consequently set at 9.79V according to the following formula: VINST _ ON = Therefore, depending on the layout and heat sink available to the charging PMOS, the suggested PMOS over temperature detection circuit included in Figure 7 may need to be included. • The range of valid temperature for charging is set at –1.5°C to 41.5°C by picking a 10k Vishay Curve 2 NTC thermistor that is thermally coupled to the battery, and connecting this in series with a regular 10k resistor to the BIAS pin. • For compensation, the procedure described in the empirical loop compensation section is followed. As recommended, first a 1µF CC and 10k RC is used, which sets all the loops to be stable. For an example of typical transient responses, the charge current regulation loop when VOFB is regulated to VOUT(INST_ON) is used here. Figure 23 shows the recommended setup to inject a DC-coupled charge current variation into this particular loop. The input to the CL pin is a square wave at 70Hz with the low level set at 120mV and the high level set at 130mV, corresponding to a 1.2A and 1.3A charge current (100mA charge current step). Therefore, in this particular example the trickle charge current regulation stability is examined. Note that the nominal trickle charge current in this example is programmed at 1.25A (RCL = 24.9kΩ). 1150kΩ + 127kΩ • 0.974V = 9.79V 127kΩ The worst-case power dissipation during instant-on operation can be calculated as follows: B A 10k 1500pF 1k IBMON 0.015µF LTC4000-1 • During trickle charging: PTRKL = [0.86 • VFLOAT – VBAT ] • ICLIM _ TRKL = [0.86 • 10.8] • 1A = 9.3W CL SQUARE WAVE GENERATOR f = 60Hz 40001 F23 • And beyond trickle charging: PINST _ ON = [0.86 • VFLOAT – VBAT ] • ICLIM = [0.86 • 10.8 – 7.33] • 10A Figure 23. Charge Current Regulation Loop Compensation Setup = 19.3W 40001f 31 LTC4000-1 Applications Information With CC = 1µF, RC = 10k at VIN = 20V, VBAT = 7V, VCSP regulated at 9.8V and a 0.2A output load condition at CSP, the transient response for a 100mA charge current step observed at IBMON is shown in Figure 24. 10 15 5 10 0 5 VIBMON (mV) 5mV/DIV VIBMON (mV) 5mV/DIV 15 The transient response now indicates an overall under damped system. As noted in the empirical loop compensation section, the value of RC is now increased iteratively until RC = 20k. The transient response of the same loop with CC = 22nF and RC = 20k is shown in Figure 26. –5 –10 –15 –20 –15 –10 5 0 5ms/DIV –5 10 15 20 –15 –20 –15 –10 Figure 24. Transient Response of Charge Current Regulation Loop Observed at IBMON When VOFB is Regulated to VOUT(INST_ON) with CC = 1µF, RC = 10k for a 100mA Charge Current Step The transient response shows a small overshoot with slow settling indicating a fast minor loop within a well damped overall loop. Therefore, the value of CC is reduced iteratively until CC = 22nF. The transient response of the same loop with CC = 22nF and RC = 10k is shown in Figure 25. 15 VIBMON (mV) 5mV/DIV 10 5 0 –5 –10 –5 5 0 5ms/DIV 10 15 20 –5 –10 25 40001 F24 –15 –20 –15 –10 0 25 40001 F25 Figure 25. Transient Response of Charge Current Regulation Loop Observed at IBMON When VOFB is Regulated to VOUT(INST_ON) with CC = 22nF, RC = 10k for a 100mA Charge Current Step –5 5 0 5ms/DIV 10 15 20 25 40001 F26 Figure 26. Transient Response of Charge Current Regulation Loop Observed at IBMON When VOFB is Regulated to VOUT(INST_ON) with CC = 22nF, RC = 20k for a 100mA Charge Current Step Note that the transient response is close to optimum with some overshoot and fast settling. If after iteratively increasing the value of RC, the transient response again indicates an over damped system, the step of reducing CC can be repeated. These steps of reducing CC followed by increasing RC can be repeated continuously until one arrives at a stable loop with the smallest value of CC and the largest value of RC. In this particular example, these values are found to be CC = 22nF and RC = 20kΩ. After arriving at these final values of RC and CC, the stability margin is checked by varying the values of both RC and CC by 2:1 in all four possible combinations. After which the setup condition is varied, including varying the input voltage level and the output load level and the transient response is checked at these different setup conditions. Once the desired responses on all different conditions are obtained, the values of RC and CC are noted. 40001f 32 LTC4000-1 Applications Information This same procedure is then repeated for the other four loops: the input voltage regulation, the output voltage regulation, the battery float voltage regulation and finally the charge current regulation when VOFB > VOUT(INST_ON). Note that the resulting optimum values for each of the loops may differ slightly. The final values of CC and RC are then selected by combining the results and ensuring the most conservative response for all the loops. This usually entails picking the largest value of CC and the smallest value of RC based on the results obtained for all the loops. In this particular example, the value of CC is finally set to 47nF and RC = 14.7kΩ. Board Layout Considerations In the majority of applications, the most important parameter of the system is the battery float voltage. Therefore, the user needs to be extra careful when placing and routing the feedback resistor RBFB1 and RBFB2. In particular, the battery sense line connected to RBFB1 and the ground return line for the LTC4000-1 must be Kelvined back to where the battery output and the battery ground are located respectively. Figure 27 shows this Kelvin sense configuration. For accurate current sensing, the sense lines from RIS and RCS (Figure 27) must be Kelvined back all the way to the sense resistors terminals. The two sense lines of each resistor must also be routed close together and away from noise sources to minimize error. Furthermore, current filtering capacitors should be placed strategically to ensure that very little AC current is flowing through these sense resistors as mentioned in the applications section. The decoupling capacitors CIN and CBIAS must be placed as close to the LTC4000-1 as possible. This allows as short a route as possible from CIN to the IN and GND pins, as well as from CBIAS to the BIAS and GND pins. In a typical application, the LTC4000-1 is paired with an external DC/DC converter. The operation of this converter often involves high dV/dt switching voltage as well as high currents. Isolate these switching voltages and currents from the LTC4000-1 section of the board as much as possible by using good board layout practices. These include separating noisy power and signal grounds, having a good low impedance ground plane, shielding whenever necessary, and routing sensitive signals as short as possible and away from noisy sections of the board. SWITCHING CONVERTER GND ITH SYSTEM LOAD RC CC ITH CC CLN RIS IID IGATE CSP RCS LTC4000-1 IN CSN BGATE BAT RBFB1 BFB VIN RBFB2 GND FBG 40001 F27 Figure 27. Kelvin Sense Lines Configuration for LTC4000-1 40001f 33 LTC4000-1 Applications Information Appendix—The Loop Transfer Functions The Input Voltage Regulation Loop When a series resistor (RC) and capacitor (CC) is used as the compensation network as shown in Figure 19, the transfer function from the input of A4-A7 to the ITH pin is simply as follows: The feedback signal for the input voltage regulation loop is the voltage on the IFB pin, which is connected to the center node of the resistor divider between the input voltage (connected to the IN pin) and GND. This voltage is compared to an internal reference (1.000V typical) by the transconductance error amplifier A4. This amplifier then drives the output transconductance amplifier (A10) to appropriately adjust the voltage on the ITH pin driving the external DC/DC converter to regulate the output voltage observed by the IFB pin. This loop is shown in detail in Figure 28. 1 C s+1 RC – C gm10 VITH (s) = gm4-7 RO4-7 •CCs VFB where gm4-7 is the transconductance of error amplifier A4A7, typically 0.5mA/V; gm10 is the output amplifier (A10) transconductance, RO4-7 is the output impedance of the error amplifier, typically 50MΩ; and RO10 is the effective output impedance of the output amplifier, typically 10MΩ with the ITH pin open circuit. Note this simplification is valid when gm10 • RO10 • RO4-7 • CC = AV10 • RO4-7 • CC is much larger than any other poles or zeroes in the system. Typically AV10 • RO4-7 = 5 • 1010 with the ITH pin open circuit. The exact value of gm10 and RO10 depends on the pull-up current and impedance connected to the ITH pin respectively. In most applications, compensation of the loops involves picking the right values of RC and CC. Aside from picking the values of RC and CC, the value of gm10 may also be adjusted. The value of gm10 can be adjusted higher by increasing the pull-up current into the ITH pin and its value can be approximated as: gm10 Assuming RIS << RIN << (RIFB1 + RIFB2), the simplified loop transmission is as follows: 1 CCs + 1 RC – gm10 • Gmi (s) • LIV (s) = gm4 p CCs RIFB2 RIN • R C + C s + 1 ( ) IN IN CLN RIFB where Gmip(s) is the transfer function from VITH to the input current of the external DC/DC converter, RIN is the equivalent output impedance of the input source, and RIFB = RIFB1 + RIFB2. RIS IN CIN I + 5µA = ITH 50mV The higher the value of gm10, the smaller the lower limit of the value of RC would be. This lower limit is to prevent the presence of the right half plane zero. Even though all the loops share this transfer function from the error amplifier input to the ITH pin, each of the loops has a slightly different dynamic due to differences in the feedback signal path. DC/DC INPUT CCLN (OPTIONAL) IN RIFB1 RIFB2 CLN A4 gm4 = 0.5m IFB 1V – + RO4 LTC4000-1 CC A10 gm10 = 0.1m – + CC ITH RC TO DC/DC RO10 40001 F28 Figure 28. Simplified Linear Model of the Input Voltage Regulation Loop 40001f 34 V– V+ 8.66k 1k R LM234 348k 47µF 100k 1.10M 20mΩ 3.0V 1µF BIAS 49.9k 1.5nF CLN IN ENC FLT IFB VM BG SW TG SENSE+ BURST_EN VFB VCC BOOST LT3845A VIN RST 10nF IIMON ITH 14.7k – SHDN VC SENSE fSET SGND SYNC CSS 2.2µF 182k 16.2k 10nF IBMON CC 47nF 1µF BAS521 BSC123NO8NS3 0.1µF BSC123NO8NS3 CL 24.9k TMR LTC4000-1 1N4148 B160 CX 20k Si7135DP NTC 40001 F29 CHRG BFB FBG OFB CSN BGATE BAT IID IGATE CSP BIAS 1µF 33µF ×3 GND BIAS 3mΩ WÜRTH ELEKTRONIC 74435561100 10µH 442k 13.0k R V+ 6-CELL LEAD-ACID BATTERY V– LM234 2.4k 210k 15mΩ VOUT 13.5V Figure 29. Solar Panel Input, 6-Cell Lead-Acid, 3-Step Battery Charger with 3.3A Bulk Charge Current, 14.1V at 25°C Absorption Voltage and 13.5V at 25°C Float Voltage. Temperature Compensation of Battery Float Voltage at –19.8mV/°C. Temperature Compensation of Solar Panel Input VMP at –78mV/°C with VMP = 17.6V at 25°C SOLAR PANEL INPUT <40V OPEN CIRCUIT VOLTAGE 17.6V PEAK POWER VOLTAGE LTC4000-1 Typical Applications 40001f 35 HIGH IMPEDANCE INPUT SOURCE 8V TO 18V WITH PEAK POWER VOLTAGE AT 11.7V 36 1µF 100k 10nF GND CL 22.1k CX 1µF Si7135DP 10k 107k 107k 1.87M NTHS0603 N02N1002J BFB NTC FBG BAT OFB IID IGATE CSP CSN BGATE TMR 150µF 22µF ×5 GND BIAS 22.1k 232k BSC027N04 10µF LTC4000-1 CC 10k 22nF BSC027N04 0.1µF BAS140W INTVCC 28.7k 10nF IBMON ITH ITH VFB TG VBIAS BG SW BOOST SENSE– LTC3786 IIMON FREQ SS RUN PGOOD INTVCC PLLINMODE 1nF 100Ω PA1494.362NL 3.3µH SENSE+ 100Ω RST ENC CHRG FLT IFB VM IN CLN 0.1µF 4.7µF INTVCC 150µF 22µF ×4 2.5mΩ Figure 30. 21V at 5A Boost Converter 5-Cell Li-Ion Battery Charger for High Impedance Input Sources Such as Solar Cell, Fuel Cell or Wind Turbine Generator 10k 7.5k 100k 3.3mΩ RNTC 1.87M 40001 F30 5-CELL Li-Ion BATTERY PACK TENERGY SSIP PACK 30104 Si7135DP 10mΩ VOUT 22V, 5A LTC4000-1 Typical Applications 40001f VIN 18V TO 72V 2.2µF ×2 0.1µF 15.8k 221k FS VCC 681Ω SYNC GND FB OC ITH ISENSE • • • BAS516 1.5k VOUT PDS1040 VOUT 10nF 14.7k 100nF VM 150k 10nF IIMON IBMON ENC CHRG FLT RST ITH CC 100k 100µF ×3 CL IN 22.1k TMR 100nF LTC4000-1 CLN 1µF 20mΩ CX IFB NTC BFB FBG OFB BAT BGATE CSN CSP IGATE GND BIAS 22.1k IID SiA923EDJ Figure 31. 18V to 72VIN to 4.2V at 2.0A Isolated Flyback Single-Cell Li-Ion Battery Charger with 2.9h Timer Termination and 0.22A Trickle Charge Current 13.6k 0.04Ω VCC 150pF 68Ω BAS516 ISO1 PS2801-1-K BAS516 3.01k FDC2512 1µF GATE MMBTA42 VCC LTC3805-5 75k SSFLT RUN PDZ6.8B 6.8V 221k TR1 PA1277NL 1µF 10k 115k 115k 309k RNTC 309k 10nF 40001 F31 NTHS0603 N02N1002J SINGLE-CELL Li-Ion BATTERY PACK SiA923EDJ 25mΩ VSYS 4.4V, 2.5A LTC4000-1 Typical Applications 40001f 37 LTC4000-1 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. UFD Package 28-Lead Plastic QFN (4mm × 5mm) (Reference LTC DWG # 05-08-1712 Rev B) 0.70 ±0.05 4.50 ±0.05 3.10 ±0.05 2.50 REF 2.65 ±0.05 3.65 ±0.05 PACKAGE OUTLINE 0.25 ±0.05 0.50 BSC 3.50 REF 4.10 ±0.05 5.50 ±0.05 RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED 4.00 ±0.10 (2 SIDES) 0.75 ±0.05 R = 0.05 TYP PIN 1 NOTCH R = 0.20 OR 0.35 × 45° CHAMFER 2.50 REF R = 0.115 TYP 27 28 0.40 ±0.10 PIN 1 TOP MARK (NOTE 6) 1 2 5.00 ±0.10 (2 SIDES) 3.50 REF 3.65 ±0.10 2.65 ±0.10 (UFD28) QFN 0506 REV B 0.200 REF 0.00 – 0.05 0.25 ±0.05 0.50 BSC BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING PROPOSED TO BE MADE A JEDEC PACKAGE OUTLINE MO-220 VARIATION (WXXX-X). 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 40001f 38 LTC4000-1 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. GN Package 28-Lead Plastic SSOP (Narrow .150 Inch) (Reference LTC DWG # 05-08-1641 Rev B) .386 – .393* (9.804 – 9.982) .045 ±.005 28 27 26 25 24 23 22 21 20 19 18 17 1615 .254 MIN .033 (0.838) REF .150 – .165 .229 – .244 (5.817 – 6.198) .0165 ±.0015 .150 – .157** (3.810 – 3.988) .0250 BSC 1 RECOMMENDED SOLDER PAD LAYOUT .015 ±.004 × 45° (0.38 ±0.10) .0075 – .0098 (0.19 – 0.25) 2 3 4 5 6 7 8 9 10 11 12 13 14 .0532 – .0688 (1.35 – 1.75) .004 – .0098 (0.102 – 0.249) 0° – 8° TYP .016 – .050 (0.406 – 1.270) NOTE: 1. CONTROLLING DIMENSION: INCHES INCHES 2. DIMENSIONS ARE IN (MILLIMETERS) .008 – .012 (0.203 – 0.305) TYP .0250 (0.635) BSC GN28 REV B 0212 3. DRAWING NOT TO SCALE 4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE 40001f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 39 LTC4000-1 Typical Application 5.6Ω IHLP6767GZ ER4R7M01 4.7µH 390pF 3.6Ω B240A SOLAR PANEL INPUT <40V OPEN CIRCUIT VOLTAGE 11.8V PEAK POWER VOLTAGE 4mΩ Q2 Q4 1800pF B240A Q5 0.01Ω Q3 Si7135DP LM234 V+ 270µF V– 0.22µF 0.01Ω 0.22µF R 1.24k 3.3µF ×5 TG1 1k SW1 1.24k + BG1 SENSE – SENSE BG2 SW2 BOOST1 VOUT 15V, 5A 330µF ×2 22µF ×2 TG2 BOOST2 DFLS160 DFLS160 INTVCC INTVCC 10µF MODE/PLLIN VIN 1µF 100k LTC3789 VINSNS PGOOD 309k IOSENSE+ IOSENSE– VOUTSNS BZT52C5V6 121k FREQ EXTVCC ILIM RUN 154k VFB SS ITH SGND 10µF PGND1 8.06k 0.01µF 10mΩ 14.7k RST CLN IN 210k ITH 100nF CC IID IGATE CSP CSN BGATE Si7343DP 1µF VM BAT OFB LTC4000-1 16.2k 26.7k IFB 8.66k ENC CHRG FLT Q2: SiR422DP Q3: SiR496DP Q4: SiR422DP Q5: SiR496DP FBG 118k IIMON IBMON CL TMR 10nF 10nF CX GND BFB NTC BIAS 1.37M 0.1µF 18.2k 22.1k 1µF 4-CELL LiFePO4 BATTERY PACK RNTC 10k 40001 F32 Figure 32. Solar Panel Input 6V to 36VIN to 14.4V at 4.5A Buck Boost Converter 4-Cell LiFePO4 Battery Charger with 2.9h Timer Termination and 0.22A Trickle Charge Current NTHS0603 N02N1002J Related Parts PART NUMBER DESCRIPTION COMMENTS LTC4000 High Voltage High Current Controller for Battery Charging and Power Management Similar to LTC4000-1 with Input Current Regulation LTC3789 High Efficiency, Synchronous, 4 Switch Buck-Boost Controller Improved LTC3780 with More Features LT3845 High Voltage Synchronous Current Mode Step-Down Controller with Adjustable Operating Frequency For Medium/High Power, High Efficiency Supplies LT3650 High Voltage 2A Monolithic Li-Ion Battery Charger 3mm × 3mm DFN-12 and MSOP-12 Packages LT3651 High Voltage 4A Monolithic Li-Ion Battery Charger 4A Synchronous Version of LT3650 Family LT3652/LT3652HV Power Tracking 2A Battery Chargers Multi-Chemistry, Onboard Termination LTC4009 High Efficiency, Multi-Chemistry Battery Charger Low Cost Version of LTC4008, 4mm × 4mm QFN-20 LTC4012 High Efficiency, Multi-Chemistry Battery Charger with PowerPath Control Similar to LTC4009 Adding PowerPath Control LT3741 High Power, Constant Current, Constant Voltage, Step-Down Controller Thermally Enhanced 4mm × 4mm QFN and 20-Pin TSSOP 40001f 40 Linear Technology Corporation LT 0712 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com LINEAR TECHNOLOGY CORPORATION 2012