Intersil EL5172IYZ 250mhz differential line receiver Datasheet

EL5172, EL5372
®
Data Sheet
January 25, 2008
250MHz Differential Line Receivers
Features
The EL5172 and EL5372 are single and triple high
bandwidth amplifiers designed to extract the difference
signal from noisy environments. They are primarily targeted
for applications such as receiving signals from twisted-pair
lines or any application where common mode noise injection
is likely to occur.
• Differential input range ±2.3V
FN7311.8
• 250MHz 3dB bandwidth
• 800V/µs slew rate
• 60mA maximum output current
• Single 5V or dual ±5V supplies
The EL5172 and EL5372 are stable for a gain of one and
requires two external resistors to set the voltage gain.
The output common mode level is set by the reference pin
(VREF), which has a -3dB bandwidth of over 120MHz.
Generally, this pin is grounded but it can be tied to any
voltage reference.
The output can deliver a maximum of ±60mA and is short
circuit protected to withstand a temporary overload
condition.
The EL5172 is available in the 8 Ld SOIC and 8 Ld MSOP
packages and the EL5372 in a 24 Ld QSOP package. Both
are specified for operation over the full -40°C to +85°C
temperature range.
• Low power - 5mA to 6mA per channel
• Pb-free available (RoHS compliant)
Applications
• Twisted-pair receivers
• Differential line receivers
• VGA over twisted-pair
• ADSL/HDSL receivers
• Differential to single-ended amplification
• Reception of analog signals in a noisy environment
Pinouts
EL5372
(24 LD QSOP)
TOP VIEW
EL5172
(8 LD SOIC, MSOP)
TOP VIEW
FB 1
IN+ 2
IN- 3
REF 4
+
-
8 OUT
REF1 1
7 VS-
INP1 2
6 VS+
INN1 3
5 EN
24 NC
+
-
22 OUT1
21 NC
NC 4
20 VSP
REF2 5
INP2 6
+
-
17 FB2
NC 8
16 OUT2
REF3 9
15 EN
INP3 10
NC 12
1
19 VSN
18 NC
INN2 7
INN3 11
23 FB1
+
-
14 FB3
13 OUT3
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2002-2005, 2008. All Rights Reserved.
All other trademarks mentioned are the property of their respective owners.
EL5172, EL5372
Ordering Information
PART NUMBER
PART MARKING
PACKAGE
PKG. DWG. #
EL5172IS
5172IS
8 Ld SOIC (150 mil)
MDP0027
EL5172IS-T7*
5172IS
8 Ld SOIC (150 mil)
MDP0027
EL5172IS-T13*
5172IS
8 Ld SOIC (150 mil)
MDP0027
EL5172ISZ (Note)
5172ISZ
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
EL5172ISZ-T7* (Note)
5172ISZ
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
EL5172ISZ-T13* (Note)
5172ISZ
8 Ld SOIC (150 mil) (Pb-free)
MDP0027
EL5172IY
h
8 Ld MSOP (3.0mm)
MDP0043
EL5172IY-T7*
h
8 Ld MSOP (3.0mm)
MDP0043
EL5172IY-T13*
h
8 Ld MSOP (3.0mm)
MDP0043
EL5172IYZ (Note)
BAAWA
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL5172IYZ-T7* (Note)
BAAWA
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL5172IYZ-T13* (Note)
BAAWA
8 Ld MSOP (3.0mm) (Pb-free)
MDP0043
EL5372IU
EL5372IU
24 Ld QSOP (150 mil)
MDP0040
EL5372IU-T7*
EL5372IU
24 Ld QSOP (150 mil)
MDP0040
EL5372IU-T13*
EL5372IU
24 Ld QSOP (150 mil)
MDP0040
EL5372IUZ (Note)
EL5372IUZ
24 Ld QSOP (150 mil) (Pb-free)
MDP0040
EL5372IUZ-T7* (Note)
EL5372IUZ
24 Ld QSOP (150 mil) (Pb-free)
MDP0040
EL5372IUZ-T13* (Note)
EL5372IUZ
24 Ld QSOP (150 mil) (Pb-free)
MDP0040
*Please refer to TB347 for details on reel specifications.
NOTE: These Intersil Pb-free plastic packaged products employ special Pb-free material sets; molding compounds/die attach materials and 100%
matte tin plate PLUS ANNEAL - e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations.
Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J
STD-020.
2
FN7311.8
January 25, 2008
EL5172, EL5372
Absolute Maximum Ratings (TA = +25°C)
Thermal Information
Supply Voltage (VS+ to VS-) . . . . . . . . . . . . . . . . . . . . . . . . . . . .12V
Maximum Output Current. . . . . . . . . . . . . . . . . . . . . . . . . . . . ±60mA
Storage Temperature Range . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . +135°C
Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C
Pb-free reflow profile . . . . . . . . . . . . . . . . . . . . . . . . . .see link below
http://www.intersil.com/pbfree/Pb-FreeReflow.asp
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and
result in failures not covered by warranty.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are
at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
VS+ = +5V, VS- = -5V, TA = +25°C, VIN = 0V, RL = 500Ω, RF = 0, RG = OPEN, CL = 2.7pF, Unless Otherwise
Specified.
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
BW
-3dB Bandwidth
AV =1, CL = 2.7pF
250
MHz
AV =2, RF = 1000Ω, CL = 2.7pF
70
MHz
AV =10, RF = 1000Ω, CL = 2.7pF
10
MHz
25
MHz
BW
±0.1dB Bandwidth
AV =1, CL = 2.7pF
SR
Slew Rate
VOUT = 3VP-P, 20% to 80%, EL5172
550
800
1000
V/µs
VOUT = 3VP-P, 20% to 80%, EL5372
550
700
1000
V/µs
tSTL
Settling Time to 0.1%
tOVR
GBWP
VOUT = 2VP-P
10
ns
Output Overdrive Recovery Time
20
ns
Gain Bandwidth Product
100
MHz
VREFBW (-3dB) VREF -3dB Bandwidth
AV =1, CL = 2.7pF
120
MHz
VREFSR
VREF Slew Rate
VOUT = 2VP-P, 20% to 80%
600
V/µs
VN
Input Voltage Noise
at f = 11kHz
26
nV/√Hz
IN
Input Current Noise
at f = 11kHz
2
pA/√Hz
HD2
Second Harmonic Distortion
VOUT = 1VP-P, 5MHz
-66
dBc
VOUT = 2VP-P, 50MHz
-63
dBc
VOUT = 1VP-P, 5MHz
-84
dBc
VOUT = 2VP-P, 50MHz
-76
dBc
HD3
Third Harmonic Distortion
dG
Differential Gain at 3.58MHz
RL = 150Ω, AV = 2
0.04
%
dθ
Differential Phase at 3.58MHz
RL = 150Ω, AV = 2
0.41
°
eS
Channel Separation at 100kHz
EL5372 only
90
dB
INPUT CHARACTERISTICS
VOS
Input Referred Offset Voltage
IIN
Input Bias Current (VIN, VINB, VREF)
RIN
Differential Input Resistance
300
kΩ
CIN
Differential Input Capacitance
1
pF
DMIR
Differential Input Range
±2.1
±2.38
CMIR+
Common Mode Positive Input Range at VIN+, VIN-
3.3
3.5
CMIR-
Common Mode Positive Input Range at VIN+, VIN-
VREFIN+
Reference Input Positive Voltage Range
VIN+ = VIN- = 0V
VREFIN-
Reference Input Negative Voltage Range
VIN+ = VIN- = 0V
3
-14
±7
±25
mV
-6
-3
µA
-4.5
3.3
±2.5
V
-4.3
3.7
-3.9
V
V
-3.6
FN7311.8
January 25, 2008
EL5172, EL5372
Electrical Specifications
VS+ = +5V, VS- = -5V, TA = +25°C, VIN = 0V, RL = 500Ω, RF = 0, RG = OPEN, CL = 2.7pF, Unless Otherwise
Specified. (Continued)
PARAMETER
DESCRIPTION
CONDITIONS
CMRR
Input Common Mode Rejection Ratio
VIN = ±2.5V
Gain
Gain Accuracy
VIN = 1
MIN
TYP
75
95
0.985
1
3.3
3.63
MAX
UNIT
dB
1.015
V
OUTPUT CHARACTERISTICS
VOUT
Positive Output Voltage Swing
RL = 500Ω to GND
Negative Output Voltage Swing
RL = 500Ω to GND
IOUT(Max)
Maximum Output Current
RL = 10Ω
ROUT
Output Impedance
-3.87
±60
V
-3.5
V
±95
mA
100
mΩ
SUPPLY
VSUPPLY
Supply Operating Range
IS (on)
Power Supply Current Per Channel - Enabled
IS (off)+
Positive Power Supply Current - Disabled
IS (off)-
Negative Power Supply Current - Disabled
PSRR
Power Supply Rejection Ratio
VS+ to VS-
4.75
11
V
5.6
7
mA
EN pin tied to 4.8V, EL5172
80
100
µA
EN pin tied to 4.8V, EL5372
1.7
5
µA
-150
-120
-90
µA
50
58
dB
4.6
VS from ±4.5V to ±5.5V
ENABLE
tEN
Enable Time
150
ns
tDS
Disable Time
1.4
µs
VIH
EN Pin Voltage for Power-up
VIL
EN Pin Voltage for Shut-down
IIH-EN
EN Pin Input Current High Per Channel
At VEN = 5V
IIL-EN
EN Pin Input Current Low Per Channel
At VEN = 0V
4
VS+ - 1.5
VS+ - 0.5
V
40
-10
V
-3
60
µA
µA
FN7311.8
January 25, 2008
EL5172, EL5372
Pin Descriptions
EL5172
EL5372
PIN NAME
PIN FUNCTION
1
FB
Feedback input
2
IN+
Non-inverting input
3
IN-
Inverting input
4
REF
5
EN
Enabled when this pin is floating or the applied voltage ≤ VS+ - 1.5
6
VS+
Positive supply voltage
7
VS-
Negative supply voltage
8
OUT
Output voltage
Sets the common mode output voltage level
1, 5, 9
REF1, 2, 3
Reference input, controls common-mode output voltage
2, 6, 10
INP1, 2, 3
Non-inverting inputs
3, 7, 11
INN1, 2, 3
Inverting inputs
4, 8, 12, 18, 21, 24
NC
13, 16, 22
OUT1, 2, 3
14, 17, 23
FB1, 2, 3
15
EN
19
VSN
Negative supply
20
VSP
Positive supply
5
No connect; grounded for best crosstalk performance
Non-inverting outputs
Feedback from outputs
Enabled when this pin is floating or the applied voltage ≤ VS+ - 1.5
FN7311.8
January 25, 2008
Connection Diagrams
RG
RF = 0Ω
-5V
1 FB
OUT 8
6
INP
2 INP
VSN 7
INN
3 INN
VSP 6
REF
4 REF
EN 5
RS2
50Ω
RS2
50Ω
RS3
50Ω
VOUT
CL
2.7pF
RL
500Ω
EN
EL5172
+5V
REF1
1 REF1
NC 24
INP1
2 INP1
FB1 23
INN1
3 INN1
OUT1 22
+5V
RF
OUT1
CL1
2.7pF
NC 21
4 NC
REF2
5 REF2
VSP 20
INP2
6 INP2
VSN 19
INN2
7 INN2
NC 18
RL1
500Ω
RG
RF
FB2 17
8 NC
REF3
9 REF3
OUT2
OUT2 16
INP3
10 INP3
EN 15
INN3
11 INN3
FB3 14
RL2
500Ω
RG
RF
RSP1
50Ω
RSN1
50Ω
RSR1
50Ω
RSP2
50Ω
RSN2
50Ω
RSR2
50Ω
RSP3
50Ω
RSN3
50Ω
RSR3
50Ω
12 NC
OUT3
OUT3 13
EL5372
-5V
FN7311.8
January 25, 2008
ENABLE
CL2
2.7pF
CL3
2.7pF
RL3
500Ω
EL5172, EL5372
RG
EL5172, EL5372
Typical Performance Curves
AV = 1, RL = 500Ω, CL = 2.7pF
AV = 1, RL = 100Ω, CL = 2.7pF
4
3
3
2
2
MAGNITUDE (dB)
MAGNITUDE (dB)
4
1
0
VS = ±5V
-1
-2
-3
-4
1
0
-1
-2
VS = ±5V
-3
-4
VS = ±2.5V
VS = ±2.5V
-5
-5
-6
1M
10M
100M
-6
1M
1G
FREQUENCY (Hz)
VS = ±5V, AV = 1, RL = 500Ω
5
3
4
2
3
MAGNITUDE (dB)
NORMALIZED GAIN (dB)
VS = ±5V, RL = 500Ω, CL = 2.7pF
1
0
AV = 1
-1
-2
AV = 2
AV = 5
AV = 10
CL = 56pF
CL = 33pF
2
CL = 15pF
1
0
-1
CL = 10pF
-2
CL = 2.7pF
-3
-4
-5
-6
1M
10M
100M
-5
1M
1G
FIGURE 3. FREQUENCY RESPONSE vs VARIOUS GAIN
VS = ±5V, AV = 1, RL = 500Ω
1G
VS = ±5V, AV = 2, RL = 500Ω, CL = 2.7pF
4
CL = 56pF
3
3
CL = 33pF
2
1
CL = 15pF
0
CL = 10pF
-2
CL = 2.7pF
-3
-4
NORMALIZED GAIN (dB)
4
-5
1M
100M
FIGURE 4. FREQUENCY RESPONSE vs CL
5
-1
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
MAGNITUDE (dB)
1G
FIGURE 2. FREQUENCY RESPONSE vs SUPPLY VOLTAGE
4
-4
100M
FREQUENCY (Hz)
FIGURE 1. FREQUENCY RESPONSE vs SUPPLY VOLTAGE
-3
10M
2
1
RF = 1kΩ
0
RF = 500Ω
-1
-2
RF = 200Ω
-3
-4
-5
10M
100M
FREQUENCY (Hz)
FIGURE 5. FREQUENCY RESPONSE vs CL
7
1G
-6
1M
10M
100M
1G
FREQUENCY (Hz)
FIGURE 6. FREQUENCY RESPONSE FOR VARIOUS RF
FN7311.8
January 25, 2008
EL5172, EL5372
Typical Performance Curves
AV = 1, RL = 500Ω, CL = 2.7pF
60
270
50
225
2
40
180
1
30
135
20
90
10
45
0
0
0
GAIN (dB)
NORMINALIZED GAIN (dB)
3
VS = ±5V
-1
-2
VS = ±2.5V
-3
PHASE (°)
4
(Continued)
-10
-45
-4
-20
-90
-5
-30
-135
-6
1M
-40
10k
10M
100M
1G
1M
100k
FREQUENCY (Hz)
10M
100M
-180
500M
FREQUENCY (Hz)
FIGURE 7. FREQUENCY RESPONSE FOR VREF
FIGURE 8. OPEN LOOP GAIN
100
0
-20
10
-30
PSRR (dB)
IMPEDENCE (Ω)
-10
1
-40
PSRR+
-50
-60
-70
PSRR-
-80
0.1
10k
100k
1M
10M
-90
100M
FREQUENCY (Hz)
1k
100k
10k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 9. OUTPUT IMPEDANCE vs FREQUENCY
FIGURE 10. PSRR vs FREQUENCY
100
1k
VOLTAGE NOISE (nV/√Hz)
CURRENT NOISE (pA/√Hz)
90
80
CMRR (dB)
70
60
50
40
30
20
100
EN
10
IN
10
0
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 11. CMRR vs FREQUENCY
8
1G
1
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FIGURE 12. VOLTAGE AND CURRENT NOISE vs FREQUENCY
FN7311.8
January 25, 2008
EL5172, EL5372
Typical Performance Curves
(Continued)
0
-45
-10
-50
-20
DISTORTION (dB)
-30
GAIN (dB)
VS = ±5V, RL = 500Ω, f = 5MHz
-40
CH1 <=> CH2, CH2 <=> CH3
-50
-60
-70
CH1 <=> CH3
-80
HD2
-55
-60
(A V
HD2
-65
HD3 (A V = 2)
= 1)
-70
-75
HD3 (AV = 1)
-80
-90
-100
100k
10M
1M
100M
-85
1G
1
4
3
2
FREQUENCY (Hz)
DISTORTION (dB)
-55
-40
(A
V =2
)
HD2 (A
V = 2)
-60
-65
HD2 (AV = 1)
-70
-75
-80
200
300
HD2
400
500
600
700
800
(A V =
2)
HD3 (A V
-60
HD2 (A V
-70
= 2)
= 1)
HD3 (AV = 1)
-80
-90
HD3 (AV = 1)
-85
-80
100
VS = ±5V, RL = 500Ω, VOP-P = 1V FOR AV = 1,
VOP-P = 2V for AV = 2
-50
DISTORTION (dB)
HD
3
7
6
FIGURE 14. HARMONIC DISTORTION vs OUTPUT VOLTAGE
VS = ±5V, f = 5MHz, VOP-P = 1V @AV = 1,
VOP-P = 2V @AV = 2
-50
5
VOP-P (V)
FIGURE 13. CHANNEL ISOLATION vs FREQUENCY
-45
= 2)
(A V
900 1000
-100
RLOAD (Ω)
0
5
10
15
20
25
30
35
40
FREQUENCY (MHz)
FIGURE 15. HARMONIC DISTORTION vs LOAD RESISTANCE
FIGURE 16. HARMONIC DISTORTION vs FREQUENCY
50mV/DIV
0.5V/DIV
10ns/DIV
FIGURE 17. SMALL SIGNAL TRANSIENT RESPONSE
9
10ns/DIV
FIGURE 18. LARGE SIGNAL TRANSIENT RESPONSE
FN7311.8
January 25, 2008
EL5172, EL5372
Typical Performance Curves
(Continued)
M = 400ns, CH1 = 200mV/DIV, CH2 = 5V/DIV
M = 100ns, CH1 = 200mV/DIV, CH2 = 5V/DIV
CH1
CH1
CH2
CH2
400ns/DIV
100ns/DIV
FIGURE 19. ENABLED RESPONSE
FIGURE 20. DISABLED RESPONSE
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.4
1.0
POWER DISSIPATION (W)
POWER DISSIPATION (W)
1.2
870mW
0.8
QSOP24
θJA = +115°C/W
625mW
0.6
SOIC8
θJA = +160°C/W
0.4 486mW
MSOP8
θJA = +206°C/W
0.2
0
1.2
1.136W
1.0
909mW
0.8
QSOP24
θJA = +88°C/W
870mW
SOIC8
θJA = +110°C/W
0.6
MSOP8/10
θJA = +115°C/W
0.4
0.2
0
0
25
50
75 85 100
125
150
0
25
AMBIENT TEMPERATURE (°C)
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 21. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FIGURE 22. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
Simplified Schematic
VS+
I1
I2
I3
RD1
I4
RD2
R3
R4
Q8
VIN+
Q1
VINQ2
FBP
Q3
FBN
Q4
Q7
VB1
Q9
x1
VOUT
Q6
25
VB2
CC
R1
R2
VS-
10
FN7311.8
January 25, 2008
EL5172, EL5372
Description of Operation and Application
Information
Product Description
The EL5172 and EL5372 are wide bandwidth, low power
and single/differential ended to single ended output
amplifiers. The EL5172 is a single channel differential to
single ended amplifier. The EL5372 is a triple channel
differential to single ended amplifier. The EL5172 and
EL5372 are internally compensated for closed loop gain of
+1 or greater. Connected in gain of 1 and driving a 500Ω
load, the EL5172 and EL5372 have a -3dB bandwidth of
250MHz. Driving a 150Ω load at gain of 2, the bandwidth is
about 50MHz. The bandwidth at the REF input is about
450MHz. The EL5172 and EL5372 are available with a
power-down feature to reduce the power while the amplifier
is disabled.
Input, Output and Supply Voltage Range
The EL5172 and EL5372 have been designed to operate
with a single supply voltage of 5V to 10V or a split supplies
with its total voltage from 5V to 10V. The amplifiers have an
input common mode voltage range from -4.3V to 3.3V for
±5V supply. The differential mode input range (DMIR)
between the two inputs is about from -2.3V to +2.3V. The
input voltage range at the REF pin is from -3.6V to 3.3V. If
the input common mode or differential mode signal is outside
the above-specified ranges, it will cause the output signal to
be distorted.
The output of the EL5172 and EL5372 can swing from -3.8V
to 3.6V at 500Ω load at ±5V supply. As the load resistance
becomes lower, the output swing is reduced respectively.
Over All Gain Settings
The gain setting for the EL5172 and the EL5372 is similar to
the conventional operational amplifier. The output voltage is
equal to the difference of the inputs plus VREF and then
times the gain.
RF ⎞
⎛
V O = ( V IN + – V IN - + V REF ) × ⎜ 1 + --------⎟
R
⎝
G⎠
EN
VIN+
VIN-
+
Σ
VREF
FB
G/B
+
RF
VO
Choice of Feedback Resistor and Gain Bandwidth
Product
For applications that require a gain of +1, no feedback
resistor is required. Just short the OUT pin to the FB pin. For
gains greater than +1, the feedback resistor forms a pole
with the parasitic capacitance at the inverting input. As this
pole becomes smaller, the amplifier's phase margin is
reduced. This causes ringing in the time domain and
peaking in the frequency domain. Therefore, RF has some
maximum value that should not be exceeded for optimum
performance. If a large value of RF must be used, a small
capacitor in the few Pico farad range in parallel with RF can
help to reduce the ringing and peaking at the expense of
reducing the bandwidth.
The bandwidth of the EL5172 and EL5372 depends on the
load and the feedback network. RF and RG appear in
parallel with the load for gains other than +1. As this
combination gets smaller, the bandwidth falls off.
Consequently, RF also has a minimum value that should not
be exceeded for optimum bandwidth performance. For a
gain of +1, RF = 0 is optimum. For the gains other than +1,
optimum response is obtained with RF between 500Ω to
1kΩ. For AV = 2 and RF = RG = 1kΩ, the BW is about 80MHz
and the frequency response is very flat.
The EL5172 and EL5372 have a gain bandwidth product of
100MHz. For gains ≥5, its bandwidth can be predicted by
Equation 1:
Gain × BW = 100MHz
(EQ. 1)
Driving Capacitive Loads and Cables
The EL5172 and EL5372 can drive 56pF capacitance in
parallel with 500Ω load to ground with 4dB of peaking at gain
of +1. If less peaking is desired in applications, a small
series resistor (usually between 5Ω to 50Ω) can be placed in
series with each output to eliminate most peaking. However,
this will reduce the gain slightly. If the gain setting is greater
than 1, the gain resistor RG can then be chosen to make up
for any gain loss which may be created by the additional
series resistor at the output.
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, a back-termination series resistor at the
amplifier's output will isolate the amplifier from the cable and
allow extensive capacitive drive. However, other applications
may have high capacitive loads without a back-termination
resistor. Again, a small series resistor at the output can help
to reduce peaking.
Disable/Power-Down
RG
FIGURE 23.
11
The EL5172 and EL5372 can be disabled and its outputs
placed in a high impedance state. The turn-off time is about
1.4µs and the turn-on time is about 150ns. When disabled,
the amplifier's supply current is reduced to 80µA for IS+ and
FN7311.8
January 25, 2008
EL5172, EL5372
120µA for IS- typically, thereby effectively eliminating the
power consumption. The amplifier's power-down can be
controlled by standard CMOS signal levels at the ENABLE
pin. The applied logic signal is relative to VS+ pin. Letting the
EN pin float or applying a signal that is less than 1.5V below
VS+ will enable the amplifier. The amplifier will be disabled
when the signal at EN pin is above VS+ - 0.5V. If a TTL
signal is used to control the enabled/disabled function,
Figure 24 could be used to convert the TTL signal to CMOS
signal.
V OUT
PD MAX = V S × I SMAX + ( V S + – V OUT ) × -------------------- × i
R
(EQ. 3)
LOAD
For sinking, use Equation 4:
(EQ. 4)
PD MAX = [ V S × I SMAX + ( V OUT – V S - ) × I LOAD ] × i
Where:
5V
• VS = Total supply voltage
10k
• ISMAX = Maximum quiescent supply current per channel
EN
1k
For sourcing, use Equation 3:
• VOUT = Maximum output voltage of the application
CMOS/TTL
• RLOAD = Load resistance
• ILOAD = Load current
FIGURE 24.
• i = Number of channels
Output Drive Capability
The EL5172 and EL5372 have internal short circuit
protection. Its typical short circuit current is ±95mA. If the
output is shorted indefinitely, the power dissipation could
easily increase such that the part will be destroyed.
Maximum reliability is maintained if the output current never
exceeds ±60mA. This limit is set by the design of the internal
metal interconnections.
Power Dissipation
With the high output drive capability of the EL5172 and
EL5372, it is possible to exceed the +135°C absolute
maximum junction temperature under certain load current
conditions. Therefore, it is important to calculate the
maximum junction temperature for the application to
determine if the load conditions or package types need to be
modified for the amplifier to remain in the safe operating
area.
The maximum power dissipation allowed in a package is
determined according to Equation 2:
T JMAX – T AMAX
PD MAX = --------------------------------------------Θ JA
(EQ. 2)
• TJMAX = Maximum junction temperature
• TAMAX = Maximum ambient temperature
• θJA = Thermal resistance of the package
By setting the two PDMAX equations equal to each other, we
can solve the output current and RLOAD to avoid the device
overheat.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high frequency device, a good printed circuit
board layout is necessary for optimum performance. Lead
lengths should be as short as possible. The power supply
pin must be well bypassed to reduce the risk of oscillation.
For normal single supply operation, where the VS- pin is
connected to the ground plane, a single 4.7µF tantalum
capacitor in parallel with a 0.1µF ceramic capacitor from VS+
to GND will suffice. This same capacitor combination should
be placed at each supply pin to ground if split supplies are to
be used. In this case, the VS- pin becomes the negative
supply rail.
For good AC performance, parasitic capacitance should be
kept to a minimum. Use of wire wound resistors should be
avoided because of their additional series inductance. Use
of sockets should also be avoided if possible. Sockets add
parasitic inductance and capacitance that can result in
compromised performance. Minimizing parasitic capacitance
at the amplifier's inverting input pin is very important. The
feedback resistor should be placed very close to the
inverting input pin. Strip line design techniques are
recommended for the signal traces.
Assuming the REF pin is tied to GND for VS = ±5V
application, the maximum power dissipation actually
produced by an IC is the total quiescent supply current times
the total power supply voltage, plus the power in the IC due
to the load, or:
12
FN7311.8
January 25, 2008
EL5172, EL5372
Typical Applications
0Ω
50
VFB
50Ω
EL5173,
EL5373
OR
EL5172,
EL5372
VIN
50
VINB
EL5172,
EL5372
VOUT
50Ω
ZO = 100Ω
VREF
FIGURE 25. TWISTED PAIR CABLE RECEIVER
As the signal is transmitted through a cable, the high
frequency signal will be attenuated. One way to compensate
for this loss is to boost the high frequency gain at the
receiver side.
R3
R1
R2
GAIN
(dB)
C1
1 + R2/R1
VFB
50Ω
VIN
VINB
ZO = 100Ω
EL5172,
EL5372
VOUT
1 + R2/(R1 + R3)
50Ω
VREF
fA
fC
f
FIGURE 26. COMPENSATED LINE RECEIVER
Level Shifter and Signal Summer
The EL5172 and EL5372 contains two pairs of differential
pair input stages, which make sure that the inputs are all
high impedance inputs. To take advantage of the two high
impedance inputs, the EL5172 and EL5372 can be used as
a signal summer to add two signals together. One signal can
be applied to VIN+, the second signal can be applied to REF
and VIN- is ground. The output is equal to Equation 5:
V O = ( V IN + + V REF ) × Gain
(EQ. 5)
Also, the EL5172 and EL5372 can be used as a level shifter
by applying a level control signal to the REF input.
13
FN7311.8
January 25, 2008
EL5172, EL5372
Small Outline Package Family (SO)
A
D
h X 45¬
(N/2)+1
N
A
PIN #1
I.D. MARK
E1
E
c
SEE DETAIL ‚Äö
1
(N/2)
B
L1
0.010 M C A B
e
H
C
A2
GAUGE
PLANE
SEATING
PLANE
A1
0.004 C
0.010 M C A B
L
b
0.010
4¬¨Ðó
DETAIL X
MDP0027
SMALL OUTLINE PACKAGE FAMILY (SO)
INCHES
SYMBOL
SO-14
SO16 (0.300”)
(SOL-16)
SO20
(SOL-20)
SO24
(SOL-24)
SO28
(SOL-28)
TOLERANCE
NOTES
A
0.068
0.068
0.068
0.104
0.104
0.104
0.104
MAX
-
A1
0.006
0.006
0.006
0.007
0.007
0.007
0.007
±0.003
-
A2
0.057
0.057
0.057
0.092
0.092
0.092
0.092
±0.002
-
b
0.017
0.017
0.017
0.017
0.017
0.017
0.017
±0.003
-
c
0.009
0.009
0.009
0.011
0.011
0.011
0.011
±0.001
-
D
0.193
0.341
0.390
0.406
0.504
0.606
0.704
±0.004
1, 3
E
0.236
0.236
0.236
0.406
0.406
0.406
0.406
±0.008
-
E1
0.154
0.154
0.154
0.295
0.295
0.295
0.295
±0.004
2, 3
e
0.050
0.050
0.050
0.050
0.050
0.050
0.050
Basic
-
L
0.025
0.025
0.025
0.030
0.030
0.030
0.030
±0.009
-
L1
0.041
0.041
0.041
0.056
0.056
0.056
0.056
Basic
-
h
0.013
0.013
0.013
0.020
0.020
0.020
0.020
Reference
-
16
20
24
28
Reference
-
N
SO-8
SO16
(0.150”)
8
14
16
Rev. M 2/07
NOTES:
1. Plastic or metal protrusions of 0.006” maximum per side are not included.
2. Plastic interlead protrusions of 0.010” maximum per side are not included.
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994
14
FN7311.8
January 25, 2008
EL5172, EL5372
Quarter Size Outline Plastic Packages Family (QSOP)
MDP0040
A
QUARTER SIZE OUTLINE PLASTIC PACKAGES FAMILY
D
(N/2)+1
N
INCHES
SYMBOL QSOP16 QSOP24 QSOP28 TOLERANCE NOTES
E
PIN #1
I.D. MARK
E1
1
(N/2)
A
0.068
0.068
0.068
Max.
-
A1
0.006
0.006
0.006
±0.002
-
A2
0.056
0.056
0.056
±0.004
-
b
0.010
0.010
0.010
±0.002
-
c
0.008
0.008
0.008
±0.001
-
D
0.193
0.341
0.390
±0.004
1, 3
E
0.236
0.236
0.236
±0.008
-
E1
0.154
0.154
0.154
±0.004
2, 3
e
0.025
0.025
0.025
Basic
-
L
0.025
0.025
0.025
±0.009
-
L1
0.041
0.041
0.041
Basic
-
N
16
24
28
Reference
-
B
0.010
C A B
e
H
C
SEATING
PLANE
0.007
0.004 C
b
C A B
Rev. F 2/07
NOTES:
L1
A
1. Plastic or metal protrusions of 0.006” maximum per side are not
included.
2. Plastic interlead protrusions of 0.010” maximum per side are not
included.
c
SEE DETAIL "X"
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994.
0.010
A2
GAUGE
PLANE
L
A1
4¬¨Ðó
DETAIL X
15
FN7311.8
January 25, 2008
EL5172, EL5372
Mini SO Package Family (MSOP)
0.25 M C A B
D
MINI SO PACKAGE FAMILY
(N/2)+1
N
E
MDP0043
A
E1
MILLIMETERS
PIN #1
I.D.
1
B
(N/2)
e
H
C
SEATING
PLANE
0.10 C
N LEADS
SYMBOL
MSOP8
MSOP10
TOLERANCE
NOTES
A
1.10
1.10
Max.
-
A1
0.10
0.10
±0.05
-
A2
0.86
0.86
±0.09
-
b
0.33
0.23
+0.07/-0.08
-
c
0.18
0.18
±0.05
-
D
3.00
3.00
±0.10
1, 3
E
4.90
4.90
±0.15
-
E1
3.00
3.00
±0.10
2, 3
e
0.65
0.50
Basic
-
L
0.55
0.55
±0.15
-
L1
0.95
0.95
Basic
-
N
8
10
Reference
-
0.08 M C A B
b
Rev. D 2/07
NOTES:
1. Plastic or metal protrusions of 0.15mm maximum per side are not
included.
L1
2. Plastic interlead protrusions of 0.25mm maximum per side are
not included.
A
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994.
c
SEE DETAIL "X"
A2
GAUGE
PLANE
L
A1
0.25
3¬¨Ðó
DETAIL X
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16
FN7311.8
January 25, 2008