EL5367 ® Data Sheet November 9, 2004 1GHz Triple Current Feedback Amplifier Features The EL5367 triple amplifier is of the current feedback variety and exhibits a very high bandwidth of 1GHz at AV = +1 and 800MHz at AV = +2. This makes this amplifier ideal for today’s high speed video and monitor applications, as well as a number of RF and IF frequency designs. • Gain-of-1 bandwidth = 1GHz With a total supply current of just 25mA and the ability to run from a single supply voltage from 5V to 12V, this amplifier offers very high performance for little power consumption. • Low noise = 1.7nV/√Hz The EL5367 is available in a 16-pin QSOP package and is specified for operation over the full -40°C to +85°C temperature range. Applications FN7457.1 • Gain-of-2 bandwidth = 800MHz • 6000V/µs slew rate • Single and dual supply operation from 5V to 12V • 8.5mA supply current • Video amplifiers • Cable drivers Pinout • RGB amplifiers EL5367 (16-PIN QSOP) TOP VIEW • Test equipment • Instrumentation INMA 1 16 VSPA • Current-to-voltage converters VSMA 2 15 OUTA Ordering Information INPA 3 14 INMB VSMB 4 13 VSPB GND 5 12 OUTB INPB 6 11 INMC VSMC 7 10 VSPC INPC 8 9 OUTC 1 PART NUMBER PACKAGE TAPE & REEL PKG. DWG. # EL5367IU 16-Pin QSOP - MDP0040 EL5367IU-T7 16-Pin QSOP 7” MDP0040 EL5367IU-T13 16-Pin QSOP 13” MDP0040 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2002-2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners. EL5367 Absolute Maximum Ratings (TA = 25°C) Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA IOUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±200mA I into VIN+, VIN- . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±4mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . VS- -0.5V to VS+ +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Die Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . +125°C CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, RF = 392Ω for AV = 1, RF = 250Ω for AV = 2, RL = 150Ω, TA = 25°C, unless otherwise specified. DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE BW -3dB Bandwidth (per channel) AV = +1 1000 MHz AV = +2 800 MHz 100 MHz 6000 V/µs 8 ns BW1 0.1dB Bandwidth (per channel) AV = +2 SR Slew Rate VO = -2.5V to +2.5V, AV = +2 tS 0.1% Settling Time VOUT = -2.5V to +2.5V, AV = -1 eN Input Voltage Noise 1.7 nV/√Hz iN- IN- Input Current Noise 19 pA/√Hz iN+ IN+ Input Current Noise 50 pA/√Hz dG Differential Gain Error (Note 1) 0.01 % dP Differential Phase Error (Note 1) 0.03 ° 3000 DC PERFORMANCE VOS Offset Voltage TCVOS Input Offset Voltage Temperature Coefficient ROL Transimpedance -5 Measured from TMIN to TMAX -0.5 5 3.52 0.5 1.1 mV µV/°C 2.5 MΩ INPUT CHARACTERISTICS CMIR Common Mode Input Range (guaranteed by CMRR test) ±3 ±3.3 V CMRR Common Mode Rejection Ratio 52 57 66 dB -ICMR - Input Current Common Mode Rejection 0 0.7 1 µA/V +IIN + Input Current -25 0.7 25 µA -IIN - Input Current -25 8.5 25 µA RIN Input Resistance 50 130 250 kΩ CIN Input Capacitance 1.5 pF OUTPUT CHARACTERISTICS VO IOUT Output Voltage Swing Output Current 2 RL = 150Ω to GND ±3.6 ±3.8 ±4.1 V RL = 1kΩ to GND ±3.8 ±4.0 ±4.2 V RL = 10Ω to GND ±110 ±160 ±200 mA FN7457.1 November 9, 2004 EL5367 Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, RF = 392Ω for AV = 1, RF = 250Ω for AV = 2, RL = 150Ω, TA = 25°C, unless otherwise specified. (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT 9.3 mA SUPPLY IS Supply Current - Enabled No load, VIN = 0V 7.5 8.5 PSRR Power Supply Rejection Ratio DC, VS = ±4.75V to ±5.25V 70 50 -IPSR - Input Current Power Supply Rejection DC, VS = ±4.75V to ±5.25V -0.5 0.2 dB 1 µA/V NOTE: 1. Standard NTSC test, AC signal amplitude = 286mV, f = 3.58MHz. 3 FN7457.1 November 9, 2004 EL5367 Typical Performance Curves 4 VCC=5V VEE=-5V 3 RL=150Ω RF=368 RF=392 RF=662 1 RF=511 -1 RF=608 RF=698 -3 RF=806 RF=900 -5 100K 1M 10M RF=1K 100M NORMALIZED MAGNITUDE (dB) NORMALIZED MAGNITUDE (dB) 5 VCC=5V VEE=-5V 2 RL=150Ω RF=392Ω RG=392 -2 RG=93 -4 RG=43 -6 100K 1G RG=186 0 1M FREQUENCY (Hz) FIGURE 1. FREQUENCY RESPONSE AS THE FUNCTION OF RF VCC=+5V VEE=-5V 3 RL=150Ω RF=392Ω C=2.5pF 1 C=1.5pF C=1pF -3 C=0pF -5 100K 1M 10M 100M 1G VCC=+5V VEE=-5V 3 RL=150Ω RF=RG=392Ω NORMALIZED MAGNITUDE (dB) C=2.5pF C=1.5pF -1 C=1pF -3 C=0pF -5 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 3. FREQENCY RESPONSE vs CIN FIGURE 4. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS CIN- VCC, VEE=5V VCC=+5V VEE=-5V RL=150Ω RF=392Ω RF=220 RG=220 2 C=4.7pF 1 FREQUENCY (Hz) 4 1G 5 C=4.7pF -1 100M FIGURE 2. FREQUENCY RESPONSE AS THE FUNCTION OF THE GAIN NORMALIZED MAGNITUDE (dB) NORMALIZED MAGNITUDE (dB) 5 10M FREQUENCY (Hz) 0 0.5V/DIV RF=220 RG=100 -2 -4 -6 1M 10M 100M 1G 2ns/DIV FREQUENCY (Hz) FIGURE 5. INVERTING FREQUENCY RESPONSE FOR GAIN OF 1 AND 2 4 FIGURE 6. RISE AND FALL TIME FN7457.1 November 9, 2004 EL5367 Typical Performance Curves (Continued) 4 RL=150Ω RF=300Ω 2 RG=300Ω NORMALIZED MAGNITUDE (dB) NORMALIZED MAGNITUDE (dB) 4 6.0V 5.0V 0 2.5V -2 3.0V -4 -6 100K 1M 10M 100M RL=150Ω RF=220 2 RG=220Ω 0 5.0V -2 6.0V -4 -6 1M 1G 10M FREQUENCY (Hz) VCC, VEE=2.5V 45 -45 ROL 10K 2.5V -135 5.0V PHASE (°) ROL (Ω) 100K -225 1K PHASE -315 100 100K 1M 10M 100M 10 VCC, VEE=5V GAIN=2 1 100m 10m 1G 10K 100K FREQUENCY (Hz) PSRR (VEE) (dB) PSRR (VCC) (dB) 100M 0 VCC=5V 10 VEE=-5V RL=150Ω 20 RF=402Ω RG=402Ω 30 40 50 VCC=5V 10 VEE=-5V RL=150Ω 20 RF=402Ω RG=402Ω 30 40 50 60 60 70 70 1K 10M FIGURE 10. CLOSED LOOP OUTPUT IMPEDANCE vs FREQUENCY 0 100 1M FREQUENCY (Hz) FIGURE 9. TRANSIMPEDANCE MAGNITUDE AND PHASE AS THE FUNCTION OF THE FREQUENCY 80 1G FIGURE 8. INVERTING AMPLIFIER, FREQUENCY RESPONSE AS THE FUNCTION OF VCC, VEE GAIN - 1 OUTPUT IMPDEANCE (Ω) 2.5V 5.0V 6.0V 100M FREQUENCY (Hz) FIGURE 7. FREQUENCY RESPONSE AS THE FUNCTION OF THE POWER SUPPLY VOLTAGE 1M 2.5V 3.5V 10K 100K 1M 10M 100M 80 100 1K 10K 100K 1M FREQUENCY (Hz) FREQUENCY (Hz) FIGURE 11. PSRR +5V FIGURE 12. PSRR -5V 5 10M 100M FN7457.1 November 9, 2004 EL5367 Typical Performance Curves (Continued) 10 3 RF=RG=392Ω NORMALIZED MAGNITUDE (dB) 20 0 CMRR (dB) -10 -20 -30 -40 2.5V -50 6.0V -60 -70 -80 5.0V 3.5V 1K 100K 10K 10M 1M 100M 1 -1 -3 V =5V CC VEE=-5V RL=150Ω -5 GAIN=2 LOAD=150Ω INPUT LEVEL=3VP-P -7 100K 1M 10M FREQUENCY (Hz) 1G FREQUENCY (Hz) FIGURE 14. LARGE SIGNAL RESPONSE FIGURE 13. COMMON MODE REJECTION AS THE FUNCTION OF THE FREQUENCY AND POWER SUPPLY VOLTAGE 2 -50 VCC, VEE=5V -55 RL=150Ω AV=2 ±3.0V DISTORTION (dB) ±6.0V 1.5 VOUTP-P (V) 100M ±5.0V 1 ±2.5V 0.5 THD -60 -65 -70 2ND HD -75 3RD HD -80 0 100 200 300 400 500 600 700 800 900 -85 1K 1 6 11 FIGURE 15. TOUT vs FREQUENCY AND VCC, VEE -74 -78 2ND HD -80 3RD HD -82 5 6 7 8 9 10 11 12 TOTAL SUPPLY VOLTAGE (V) FIGURE 17. HARMONIC DISTORTION vs SUPPLY VOLTAGE 6 31 36 f=5MHz RL=150Ω -10 AV=2 VO=2VP-P -30 -50 THD -70 -84 -86 26 10 VCC, VEE=5V RL=150Ω AV=2 THD 21 FIGURE 16. DISTORTION vs FREQUENCY DISTORTION (dB) DISTORTION (dB) -76 16 FREQUENCY (MHz) FREQUENCY (Hz) -90 3RD HD 5 6 2ND HD 7 8 9 10 11 12 TOTAL SUPPLY VOLTAGE (V) FIGURE 18. HARMONIC DISTORTION vs SUPPLY VOLTAGE FN7457.1 November 9, 2004 EL5367 Typical Performance Curves (Continued) -50 f=10MHz RL=150Ω AV=2 -60 VO=2VP-P DISTORTION (dB) DISTORTION (dB) -50 THD -70 2ND HD 3RD HD -80 f=20MHz RL=150Ω -55 A =2 V VO=2VP-P -60 -65 THD -70 2ND HD -75 -90 5 6 7 8 9 10 11 -80 12 3RD HD 5 6 7 TOTAL SUPPLY VOLTAGE (V) 8 9 10 11 12 TOTAL SUPPLY VOLTAGE (V) FIGURE 19. DISTORTION vs POWER SUPPLY VOLTAGE FIGURE 20. DISTORTION vs POWER SUPPLY VOLTAGE 8.5 1.4 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 8.3 POWER DISSIPATION (W) SUPPLY CURRENT (mA) 8.4 IS+ 8.2 8.1 8 7.9 IS- 7.8 7.7 7.6 7.5 7.4 2.5 3 3.5 4 4.5 5 5.5 1.2 1 893mW 0.8 θ JA 0.6 0.4 0.2 0 6 0 25 SUPPLY VOLTAGE (V) 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE 1.2 POWER DISSIPATION (W) QS O = 1 P1 6 12 °C /W FIGURE 22. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1 0.8 633mW 0.6 θJ 0.4 QS A =1 OP 58 16 °C /W 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 23. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 7 FN7457.1 November 9, 2004 EL5367 Pin Descriptions 16-PIN QSOP PIN NAME FUNCTION 3 INPA Non-inverting input 6 INPB Non-inverting input 8 INPC Non-inverting input 1 INMA Inverting 14 INMB Inverting 11 INMC Inverting 2 VSMA Negative supply 4 VSMB Negative supply 7 VSMC Negative supply 16 VSPA Positive supply 13 VSPB Positive supply 10 VSPC Positive supply 15 OUTA Output 12 OUTB Output 9 OUTC Output Applications Information Product Description The EL5367 is a current-feedback operational amplifier that offers a wide -3dB bandwidth of 1GHz and a low supply current of 8.5mA per amplifier. The EL5367 works with supply voltages ranging from a single 5V to 10V and it is also capable of swinging to within 1V of either supply on the output. Because of their current-feedback topology, the EL5367 does not have the normal gain-bandwidth product associated with voltage-feedback operational amplifiers. Instead, its -3dB bandwidth remains relatively constant as closed-loop gain is increased. This combination of high bandwidth and low power, together with aggressive pricing make the EL5367 an ideal choice for many low-power/highbandwidth applications such as portable, handheld, or battery-powered equipment. Power Supply Bypassing and Printed Circuit Board Layout As with any high frequency device, good printed circuit board layout is necessary for optimum performance. Low impedance ground plane construction is essential. Surface mount components are recommended, but if leaded components are used, lead lengths should be as short as possible. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 4.7µF tantalum capacitor in parallel with a 0.01µF capacitor has been shown to work well when placed at each supply pin. 8 For good AC performance, parasitic capacitance should be kept to a minimum, especially at the inverting input. (See the Capacitance at the Inverting Input section) Even when ground plane construction is used, it should be removed from the area near the inverting input to minimize any stray capacitance at that node. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in additional peaking and overshoot. Capacitance at the Inverting Input Any manufacturer’s high-speed voltage- or current-feedback amplifier can be affected by stray capacitance at the inverting input. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground. But for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of large value feedback and gain resistors exacerbates the problem by further lowering the pole frequency (increasing the possibility of oscillation). The EL5367 frequency response is optimized with the resistor values in Figure 3. With the high bandwidth of this amplifier, these resistor values might cause stability problems when combined with parasitic capacitance, thus ground plane is not recommended around the inverting input pin of the amplifier. Feedback Resistor Values The EL5367 has been designed and specified at a gain of +2 with RF approximately 392Ω. This value of feedback resistor gives 800MHz of -3dB bandwidth at AV = 2 with about 0.5dB of peaking. Since the EL5367 is current-feedback amplifier, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response for Various RF and RG, bandwidth and peaking can be easily modified by varying the value of the feedback resistor. Because the EL5367 is a current-feedback amplifier, its gain-bandwidth product is not a constant for different closedloop gains. This feature actually allows the EL5367 to maintain reasonable constant -3dB bandwidth for different gains. As gain is increased, bandwidth decreases slightly while stability increases. Since the loop stability is improving with higher closed-loop gains, it becomes possible to reduce the value of RF below the specified 250Ω and still retain stability, resulting in only a slight loss of bandwidth with increased closed-loop gain. FN7457.1 November 9, 2004 EL5367 Supply Voltage Range and Single-Supply Operation The EL5367 has been designed to operate with supply voltages having a span of greater than 5V and less than 10V. In practical terms, this means that the EL5367 will operate on dual supplies ranging from ±2.5V to ±5V. With singlesupply, they will operate from 5V to 10V. As supply voltages continue to decrease, it becomes necessary to provide input and output voltage ranges that can get as close as possible to the supply voltages. The EL5367 has an input range which extends to within 1.8V of either supply. So, for example, on ±5V supplies, the EL5367 has an input range which spans ±3.2V. The output range of the EL5367 is also quite large, extending to within 1V of the supply rail. On a ±5V supply, the output is therefore capable of swinging from -4V to +4V. Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150Ω, because of the change in output current with DC level. Previously, good differential gain could only be achieved by running high idle currents through the output transistors (to reduce variations in output impedance.) These currents were typically comparable to the entire 8.5mA supply current of each EL5367 amplifier. Special circuitry has been incorporated in the EL5367 to reduce the variation of output impedance with current output. This results in dG and dP specifications of 0.01% and 0.03°, while driving 150Ω at a gain of 2. Current Limiting The EL5367 has no internal current-limiting circuitry. If the output is shorted, it is possible to exceed the Absolute Maximum Rating for output current or power dissipation, potentially resulting in the destruction of the device. Power Dissipation With the high output drive capability of the EL5367, it is possible to exceed the 125°C Absolute Maximum junction temperature under certain very high load current conditions. Generally speaking when RL falls below about 25Ω, it is important to calculate the maximum junction temperature (TJMAX) for the application to determine if power supply voltages, load conditions, or package type need to be modified for the EL5367 to remain in the safe operating area. These parameters are calculated as follows: T JMAX = T MAX + ( θ JA × n × PD MAX ) where: TMAX = Maximum ambient temperature θJA = Thermal resistance of the package n = Number of amplifiers in the package PDMAX = Maximum power dissipation of each amplifier in the package PDMAX for each amplifier can be calculated as follows: V OUTMAX PD MAX = ( 2 × V S × I SMAX ) + ( V S – V OUTMAX ) × ---------------------------R L where: Output Drive Capability VS = Supply voltage In spite of the low 8.5mA of supply current, the EL5367 is capable of providing a minimum of ±110mA of output current. With so much output drive, the EL5367 is capable of driving 50Ω loads to both rails, making it an excellent choice for driving isolation transformers in telecommunications applications. ISMAX = Maximum supply current of 1A VOUTMAX = Maximum output voltage (required) RL = Load resistance Driving Cables and Capacitive Loads When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5367 from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5Ω and 50Ω) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the peaking. 9 FN7457.1 November 9, 2004 EL5367 Typical Application Circuits 0.1µF 250Ω 250Ω +5V IN+ IN- 0.1µF +5V VS+ 1/3 OUT EL5367 VS- IN+ 0.1µF IN- VS+ 1/3 OUT EL5367 VS- -5V 250Ω 5Ω VOUT +5V IN- VS+ 1/3 OUT EL5367 VS- -5V 250Ω +5V VIN 5Ω VIN IN+ IN- 0.1µF VS+ 1/3 OUT EL5367 VS- VOUT 0.1µF -5V -5V 250Ω 0.1µF 0.1µF 0.1µF IN+ 250Ω 250Ω FIGURE 24. INVERTING 200mA OUTPUT CURRENT DISTRIBUTION AMPLIFIER FIGURE 25. FAST-SETTLING PRECISION AMPLIFIER 0.1µF 0.1µF +5V IN+ IN- +5V IN+ VS+ 1/3 OUT EL5367 VS- IN- 250Ω 120Ω +5V 250Ω 250Ω 1kΩ 0.1µF 240Ω VS+ 1/3 OUT EL5367 VS- 0.1µF 120Ω +5V 0.1µF VOUT- IN+ 1kΩ IN- VS+ 1/3 OUT EL5367 VS- -5V VIN 250Ω 250Ω 0.1µF -5V 0.1µF VOUT+ 0.1µF IN- VS- 0.1µF -5V IN+ VS+ 1/3 OUT EL5367 VOUT 0.1µF -5V 250Ω TRANSMITTER 250Ω RECEIVER FIGURE 26. DIFFERENTIAL LINE DRIVER/RECEIVER 10 FN7457.1 November 9, 2004 EL5367 Package Outline Drawing NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at <http://www.intersil.com/design/packages/index.asp> All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 11 FN7457.1 November 9, 2004