Power LNK614DG Energy-efficient, accurate cv/cc switcher for adapters and charger Datasheet

LNK603-606/613-616
LinkSwitch-II Family
®
Energy-Efficient, Accurate CV/CC Switcher
for Adapters and Chargers
Product Highlights
Dramatically Simplifies CV/CC Converters
• Eliminates optocoupler and all secondary CV/CC control circuitry
• Eliminates all control loop compensation circuitry
Advanced Performance Features
• Compensates for transformer inductance tolerances
• Compensates for input line voltage variations
• Compensates for cable voltage drop (LNK61X series)
• Compensates for external component temperature variations
• Very tight IC parameter tolerances using proprietary trimming
technology
• Frequency jittering greatly reduces EMI filter cost
• Even tighter output tolerances achievable with external resistor
selection/trimming
• Programmable switching frequency up to 85 kHz to reduce
transformer size
Wide Range
High Voltage
DC Input
LinkSwitch-II
Green Package
• Halogen free and RoHS compliant package
Applications
• Chargers for cell/cordless phones, PDAs, MP3/portable audio
devices, adapters, LED drivers, etc.
Description
The LinkSwitch-II dramatically simplifies low power CV/CC
charger designs by eliminating an optocoupler and secondary
control circuitry. The device introduces a revolutionary control
technique to provide very tight output voltage and current
regulation, compensating for transformer and internal parameter
tolerances along with input voltage variations.
FB
BP/M
S
PI-4960-011510
(a) Typical Application Schematic
VO
Advanced Protection/Safety Features
• Auto-restart protection reduces power delivered by >95% for
output short circuit and control loop faults (open and shorted
components)
• Hysteretic thermal shutdown – automatic recovery reduces
power supply returns from the field
• Meets high voltage creepage requirements between DRAIN and
all other pins both on the PCB and at the package
EcoSmart ® – Energy Efficient
• Easily meets all global energy efficiency regulations
• No-load consumption below 30 mW at 230 VAC with optional
external bias winding
• ON/OFF control provides constant efficiency down to very light
loads – ideal for CEC and ENERGY STAR 2.0 regulations
• No current sense resistors – maximizes efficiency
D
±5%
±10%
IO
PI-4906-041008
(b) Output Characteristic
Figure 1.
Typical Application/Performance – Not a Simplified Circuit (a) and
Output Characteristic Envelope (b). (see Application Section for
more information).
Output Power Table
Product3
85-265 VAC
Adapter
Open Frame2
1
LNK603/613PG/DG
2.5 W
3.3 W
LNK604/614PG/DG
3.5 W
4.1 W
LNK605/615PG/DG
4.5 W
5.1 W
LNK606/616PG/GG/DG
5.5 W
6.1 W
Table 1. Output Power Table.
Notes:
1. Minimum continuous power in a typical non-ventilated enclosed adapter
measured at +50 °C ambient, device, TJ <100 °C.
2. Maximum practical continuous power in an open frame design with adequate
heatsinking, measured at 50 °C ambient (see Key Applications Considerations
section for more information).
3. Packages: P: DIP-8C, G: SMD-8C, D: SO-8C.
The device incorporates a 700 V power MOSFET, a novel ON/OFF
control state machine, a high voltage switched current source for
self biasing, frequency jittering, cycle-by-cycle current limit and
hysteretic thermal shutdown circuitry onto a monolithic IC.
www.powerint.com
January 2010
LNK603-606/613-616
DRAIN
(D)
REGULATOR
6V
BYPASS
(BP/M)
+
+
FEEDBACK
(FB)
VTH
-
D
Q
FB
OUT
6V
5V
Reset
STATE
MACHINE
-
VILIMIT
tSAMPLE-OUT
ILIM
CABLE DROP
COMPENSATION
VILIMIT
FAULT
Auto-Restart
Open-Loop
FB
6.5 V
INDUCTANCE
CORRECTION
tSAMPLE-INPUT
Drive
DCMAX
THERMAL
SHUTDOWN
DCMAX
SAMPLE
DELAY
tSAMPLE-OUT
tSAMPLE-INPUT
OSCILLATOR
SOURCE
(S)
+
SOURCE
(S)
CONSTANT
CURRENT
ILIM
VILIMIT
-
Current Limit
Comparator
LEADING
EDGE
BLANKING
PI-4908-041508
Figure 2
Functional Block Diagram.
Pin Functional Description
DRAIN (D) Pin:
This pin is the power MOSFET drain connection. It provides
internal operating current for both start-up and steady-state
operation.
BYPASS/MULTI-FUNCTIONAL PROGRAMMABLE
(BP/M) Pin:
This pin has multiple functions:
1. It is the connection point for an external bypass capacitor for
the internally generated 6 V supply.
2. It is a mode selection for the cable drop compensation for
LNK61X series.
FEEDBACK (FB) Pin:
During normal operation, switching of the power MOSFET is
controlled by this pin. This pin senses the AC voltage on the bias
winding. This control input regulates both the output voltage in
CV mode and output current in CC mode based on the flyback
voltage of the bias winding. The internal inductance correction
circuit uses the forward voltage on the bias winding to sense the
bulk capacitor voltage.
P Package (DIP-8C)
G Package (SMD-8C)
FB
1
8
S
BP/M
2
7
S
6
D
5
4
3a
D Package (SO-8C)
FB
1
8
S
BP/M
2
7
S
6
S
5
S
S
S
D
4
3b
PI-3491-012808
Figure 3.
Pin Configuration.
SOURCE (S) Pin:
This pin is internally connected to the output MOSFET source for
high voltage power and control circuit common returns.
2
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
LinkSwitch-II Functional Description
The LinkSwitch-II combines a high voltage power MOSFET
switch with a power supply controller in one device. Similar to
the LinkSwitch-LP and TinySwitch-III it uses ON/OFF control to
regulate the output voltage. In addition, the switching frequency
is modulated to regulate the output current to provide a
constant current characteristic. The LinkSwitch-II controller
consists of an oscillator, feedback (sense and logic) circuit, 6 V
regulator, over-temperature protection, frequency jittering,
current limit circuit, leading-edge blanking, inductance
correction circuitry, frequency control for constant current
regulation and ON/OFF state machine for CV control.
Inductance Correction Circuitry
If the primary magnetizing inductance is either too high or low
the converter will automatically compensate for this by adjusting
the oscillator frequency. Since this controller is designed to
operate in discontinuous-conduction mode the output power is
directly proportional to the set primary inductance and its
tolerance can be completely compensated with adjustments to
the switching frequency.
Constant Current (CC) Operation
As the output voltage and therefore the flyback voltage across
the bias winding increases, the FEEDBACK pin voltage increases.
The switching frequency is adjusted as the FEEDBACK pin
voltage increases to provide a constant output current regulation.
The constant current circuit and the inductance correction
circuit are designed to operate concurrently in the CC region.
Auto-Restart and Open-Loop Protection
In the event of a fault condition such as an output short or an
open loop condition the LinkSwitch-II enters into an appropriate
protection mode as described below.
In the event the FEEDBACK pin voltage during the flyback
period falls below 0.7 V before the FEEDBACK pin sampling
delay (~2.5 ms) for a duration in excess of ~450 ms (auto-restart
on-time (t AR-ON) the converter enters into auto-restart, wherein
the power MOSFET is disabled for 2 seconds (~18% autorestart duty cycle). The auto-restart alternately enables and
disables the switching of the power MOSFET until the fault
condition is removed.
In addition to the conditions for auto-restart described above, if
the sensed FEEDBACK pin current during the forward period of
the conduction cycle (switch “on” time) falls below 120 mA, the
converter annunciates this as an open-loop condition (top
resistor in potential divider is open or missing) and reduces the
auto-restart time from 450 msec to approximately 6 clock cycles
(90 ms), whilst keeping the disable period of 2 seconds.
Over-Temperature Protection
The thermal shutdown circuitry senses the die temperature. The
threshold is set at 142 °C typical with a 60 °C hysteresis. When
the die temperature rises above this threshold (142 °C) the
power MOSFET is disabled and remains disabled until the die
temperature falls by 60 °C, at which point the MOSFET is
re-enabled.
Constant Voltage (CV) Operation
As the FEEDBACK pin approaches VFBth from the constant
current regulation mode, the power supply transitions into CV
operation. The switching frequency at this point is at its
maximum value, corresponding to the peak power point of the
CCCV characteristic. The controller regulates the feedback pin
voltage to remain at VFBth using an ON/OFF state-machine. The
FEEDBACK pin voltage is sampled 2.5 ms after the turn-off of
the high voltage switch. At light loads the current limit is also
reduced to decrease the transformer flux density.
Current Limit
The current limit circuit senses the current in the power
MOSFET. When this current exceeds the internal threshold
(ILIMIT ), the power MOSFET is turned off for the remainder of that
cycle. The leading edge blanking circuit inhibits the current limit
comparator for a short time (tLEB) after the power MOSFET is
turned on. This leading edge blanking time has been set so that
current spikes caused by capacitance and rectifier reverse
recovery time will not cause premature termination of the MOSFET
conduction. The LinkSwitch-II also contains a “di/dt” correction
feature to minimize CC variation across the input line range.
Output Cable Compensation
This compensation provides a constant output voltage at the
end of the cable over the entire load range in CV mode. As the
converter load increases from no-load to the peak power point
(transition point between CV and CC) the voltage drop introduced
across the output cable is compensated by increasing the
FEEDBACK pin reference voltage. The controller determines the
output load and therefore the correct degree of compensation
based on the output of the state machine. Cable drop
compensation for a 24 AWG (0.3 W) cable is selected with
CBP = 1 mF and for a 26 AWG (0.49 W) cable with CPB = 10 mF.
6.0 V Regulator
The 6 V regulator charges the bypass capacitor connected to
the BYPASS pin to 6 V by drawing a current from the voltage on
the DRAIN, whenever the MOSFET is off. The BYPASS pin is
the internal supply voltage node. When the MOSFET is on, the
device runs off of the energy stored in the bypass capacitor.
Extremely low power consumption of the internal circuitry
allows the LinkSwitch-II to operate continuously from the
current drawn from the DRAIN pin. A bypass capacitor value of
either 1 mF or 10 mF is sufficient for both high frequency
decoupling and energy storage.
3
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Rev. F 01/10
LNK603-606/613-616
Applications Example
C6
R7
1 nF
100 V 200 Ω
L1
1.5 mH
5
C3
820 pF 3
1 kV
R2
470 kΩ
D1
1N4007
D2
1N4007
R3
300 Ω
C1
4.7 µF
400 V
D3
1N4007
D4
1N4007
C2
4.7 µF
400 V
5 V, 555 mA
10
8
1
RF1
8.2 Ω
2W
AC
Input
T1
EE16
D7
SS14
C7
680 µF
10 V
2
DC
Output
VR1
2MM5230B-7
4.7 V
4
D5
1N4007
D
R8
200 Ω
NC
LinkSwitch-II
D6
U1
LNK613DG LL4148
R5
13 kΩ
1%
FB
BP
S
C4
1 µF
25 V
R4
6.2 kΩ C5
10 µF
16 V
R6
8.87 kΩ
1%
PI-5111-050808
Figure 4.
Energy Efficient USB Charger Power Supply (74% Average Efficiency, <30 mW No-load Input Power).
Circuit Description
This circuit shown in Figure 4 is configured as a primary-side
regulated flyback power supply utilizing the LNK613DG. With
an average efficiency of 74% and <30 mW no-load input power
this design easily exceeds the most stringent current energy
efficiency requirements.
Input Filter
AC input power is rectified by diodes D1 through D4. The
rectified DC is filtered by the bulk storage capacitors C1 and
C2. Inductor L1, C1 and C2 form a pi (π) filter, which attenuates
conducted differential-mode EMI noise. This configuration
along with Power Integrations transformer E-shield™ technology
allow this design to meet EMI standard EN55022 class B with
good margin without requiring a Y capacitor, even with the
output connected to safety earth ground. Fusible resistor RF1
provides protection against catastrophic failure. This should be
suitably rated (typically a wire wound type) to withstand the
instantaneous dissipation while the input capacitors charge
when first connected to the AC line.
LNK 613 Primary
The LNK613DG device (U1) incorporates the power switching
device, oscillator, CC/CV control engine, startup, and protection
functions. The integrated 700 V MOSFET provides a large drain
voltage margin in universal input AC applications, increasing
reliability and also reducing the output diode voltage stress by
allowing a greater transformer turns ratio. The device is
completely self-powered from the BYPASS pin and decoupling
capacitor C4. For the LNK61X devices, the bypass capacitor
value also selects the amount of output cable voltage drop
compensation. A 1 mF value selects the standard compensation.
A 10 mF value selects the enhanced compensation. Table 2
shows the amount of compensation for each device and
bypass capacitor value. The LNK60x devices do not provide
cable drop compensation.
The optional bias supply formed by D6 and C5 provides the
operating current for U1 via resistor R4. This reduces the
no-load consumption from ~200 mW to <30 mW and also
increases light load efficiency.
The rectified and filtered input voltage is applied to one side of
the primary winding of T1. The other side of the transformer’s
primary winding is driven by the integrated MOSFET in U1. The
leakage inductance drain voltage spike is limited by an RCD-R
clamp consisting of D5, R2, R3, and C3.
Output Rectification
The secondary of the transformer is rectified by D7, a 1 A, 40 V
Schottky barrier type for higher efficiency, and filtered by C7. If
lower efficiency is acceptable then this can be replaced with a
1 A PN junction diode for lower cost. In this application C7 was
sized to meet the required output voltage ripple specification
without requiring a post LC filter. To meet battery self discharge
requirement the pre-load resistor has been replaced with a
series resistor and Zener network (R8 and VR1). However in
designs where this is not a requirement a standard 1 kW
resistor can be used.
Output Regulation
The LNK613 regulates the output using ON/OFF control in the
constant voltage (CV) regulation region of the output character-
4
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
istic and frequency control for constant current (CC) regulation.
The feedback resistors (R5 and R6) were selected using
standard 1% resistor values to center both the nominal output
voltage and constant current regulation thresholds.
Key Application Considerations
Output Power Table
The data sheet maximum output power table (Table 1) represents the maximum practical continuous output power level
that can be obtained under the following assumed conditions:
LinkSwitch-II Output Cable Voltage Drop Compensation
Device
LNK613
LNK614
LNK615
LNK616
1. The minimum DC input voltage is 90 V or higher at 85 VAC
input. The value of the input capacitance should be large
enough to meet these criteria for AC input designs.
2. Secondary output of 5 V with a Schottky rectifier diode.
3. Assumed efficiency of 70%.
4. Discontinuous mode operation (KP >1.3).
5. The part is board mounted with SOURCE pins soldered to a
sufficient area of copper to keep the SOURCE pin temperature at or below 90 °C.
6. Ambient temperature of 50 °C for open frame designs and
an internal enclosure temperature of 60 °C for adapter
designs.
Note: Higher output power are achievable if an output CC
tolerance >±10% is acceptable, allowing the device to be
operated at a higher SOURCE pin temperature.
Output Tolerance
LinkSwitch-II provides an overall output tolerance (including line,
component variation and temperature) of ±5% for the output
voltage in CV operation and ±10% for the output current during
CC operation over a junction temperature range of 0 °C to 100 °C
for the P/G package. For the D package (SO8) additional CC
variance may occur due to stress caused by the manufacturing
flow (i.e. solder-wave immersion or IR reflow). A sample power
supply build is recommended to verify production tolerances for
each design.
BYPASS Pin Capacitor Selection
Table 2.
BYPASS Pin
Capacitor Value
Output Voltage
Change Factor
1 μF
1.035
10 μF
1.055
1 μF
1.045
10 μF
1.065
1 μF
1.050
10 μF
1.070
1 μF
1.060
10 μF
1.090
Cable Compensation Change Factor vs Device and BYPASS Pin
Capacitor Value.
The output voltage that is entered into PIXls design spreadsheet
is the voltage at the end of the output cable when the power
supply is delivering maximum power. The output voltage at the
terminals of the supply is the value measured at the end of the
cable multiplied by the output voltage change factor.
LinkSwitch-II Layout Considerations
Circuit Board Layout
LinkSwitch-II is a highly integrated power supply solution that
integrates on a single die, both, the controller and the high
voltage MOSFET. The presence of high switching currents and
voltages together with analog signals makes it especially
important to follow good PCB design practice to ensure stable
and trouble free operation of the power supply. See Figure 5 for
a recommended circuit board layout for LinkSwitch-II.
When designing a printed circuit board for the LinkSwitch-II
based power supply, it is important to follow the following
guidelines:
Single Point Grounding
Use a single point (Kelvin) connection at the negative terminal of
the input filter capacitor for the LinkSwitch-II SOURCE pin and
bias winding return. This improves surge capabilities by
returning surge currents from the bias winding directly to the
input filter capacitor.
For LinkSwitch-II 60x Family of Devices (without output
cable voltage drop compensation)
A 1 mF BYPASS pin capacitor is recommended. The capacitor
voltage rating should be greater than 7 V. The capacitor’s
dielectric material is not important but tolerance of capacitor
should be ≤ ±50%. The capacitor must be physically located
close to the LinkSwitch-II BYPASS pin.
Bypass Capacitor
The BYPASS pin capacitor should be located as close as
possible to the SOURCE and BYPASS pins.
For LinkSwitch-II 61x Family of Devices (with output cable
voltage drop compensation)
The amount of output cable compensation can be selected with
the value of the BYPASS pin capacitor. A value of 1 mF selects
the standard cable compensation. A 10 mF capacitor selects
the enhanced cable compensation. Table 2 shows the amount
of compensation for each LinkSwitch-II device and capacitor
value. The capacitor can be either ceramic or electrolytic but
tolerance and temperature variation should be ≤ ±50%.
Thermal Considerations
The copper area connected to the SOURCE pins provides the
LinkSwitch-II heat sink. A good estimate is that the LinkSwitch-II
will dissipate 10% of the output power. Provide enough copper
area to keep the SOURCE pin temperature below 90 °C. Higher
temperatures are allowable only if an output current (CC)
tolerance above ±10% is acceptable. In this case a maximum
SOURCE pin temperature below 110 °C is recommended to
provide margin for part to part RDS(ON) variation.
Feedback Resistors
Place the feedback resistors directly at the FEEDBACK pin of
the LinkSwitch-II device. This minimizes noise coupling.
5
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Rev. F 01/10
LNK603-606/613-616
Input Stage
R1
C1
Feedback
Resistors
R2
D1
D2
U1
R6
D4
RF1
S
C3
S
S
D5
LinkSwitch-II
R5
FB
BP
D
C7
C5
C8
D3
Bypass Supply
Components
AC
Input
Figure 5.
D7
C4
Bypass
Capacitor
D3
C6
R4
S
R1
R8
T1
C2
R3
L2
Output Filter
Output
Capacitors
Diode Snubber
Primary Clamp
R9
Preload
Resistor
Spark
Gap
DC
Output
PI-5110-050508
PCB Layout Example Showing 5.1 W Design Using P Package.
Secondary Loop Area
To minimize leakage inductance and EMI the area of the loop
connecting the secondary winding, the output diode and the
output filter capacitor should be minimized. In addition,
sufficient copper area should be provided at the anode and
cathode terminal of the diode for heatsinking. A larger area is
preferred at the quiet cathode terminal. A large anode area can
increase high frequency radiated EMI.
Electrostatic Discharge Spark Gap
An trace is placed along the isolation barrier to form one
electrode of a spark gap. The other electrode on the secondary
is formed by the output return node. The spark gap directs
ESD energy from the secondary back to the AC input. The
trace from the AC input to the spark gap electrode should be
spaced away from other traces to prevent unwanted arcing
occurring and possible circuit damage.
Drain Clamp Optimization
LinkSwitch-II senses the feedback winding on the primary side
to regulate the output. The voltage that appears on the feedback winding is a reflection of the secondary winding voltage
while the internal MOSFET is off. Therefore any leakage
inductance induced ringing can affect output regulation. Optimizing
the drain clamp to minimize the high frequency ringing will give
the best regulation. Figure 6 shows the desired drain voltage
waveform compared to Figure 7 with a large undershoot due to
the leakage inductance induced ring. This will reduce the
output voltage regulation performance. To reduce this adjust
the value of the resistor in series with the clamp diode.
Addition of a Bias Circuit for Higher Light Load Efficiency
and Lower No-load Input Power Consumption.
The addition of a bias circuit can decrease the no-load input
power from ~200 mW down to less than 30 mW at 230 VAC
input. Light load efficiency also increases which may avoid the
need to use a Schottky barrier vs PN junction output diode
while still meeting average efficiency requirements.
The power supply schematic shown in Figure 4 has the bias
circuit incorporated. Diode D6, C5 and R4 form the bias circuit.
As the output voltage is less than 8 V, an additional transformer
winding is needed, AC stacked on top of the feedback winding.
This provides a high enough voltage to supply the BYPASS pin
even during low switching frequency operation at no-load.
In Figure 4 the additional bias winding (from pin 2 to pin 1) is
stacked on top of the feedback winding (pin 4 to pin 2). Diode
D6 rectifies the output and C5 is the filter capacitor. A 10 uF
capacitor is recommended to hold up the bias voltage at low
switching frequencies. The capacitor type is not critical but the
voltage rating should be above the maximum value of VBIAS.
The recommended current into the BYPASS pin is equal to IC
supply current (~0.5 mA) at the minimum bias winding voltage.
The BYPASS pin current should not exceed 3 mA at the maximum
bias winding voltage. The value of R4 is calculated according to
(VBIAS – VBP)/IS2, where VBIAS (10 V typ.) is the voltage across C5, IS2
(0.5 mA typ.) is the IC supply current and VBP (6.2 V typ.) is the
6
Rev. F 01/10
www.powerint.com
An overshoot
is acceptable
PI-5094-042408
PI-5093-041408
LNK603-606/613-616
Negative ring may
increase output
ripple and/or
degrade output
regulation
Figure 6.
Desired Drain Voltage Waveform with Minimal Leakage
Ringing Undershoot.
Figure 7.
L1
1 mH
5
TI
EE13
C3
820 pF 3
1 kV
R2
470 kΩ
D1
1N4007
Undesirable Drain Voltage Waveform with Large Leakage
Ring Undershoot.
D2
1N4007
C1
4.7 µF
400 V
AC
Input
D3
1N4007
C2
4.7 µF
400 V
1 kΩ
DC
Output
2
4
D5
1N4007
D4
1N4007
8
D7
SL13
C7
470 µF
10 V
R3
300 Ω
RF1
8.2 Ω
2W
10
D
LinkSwitch-II
U1
LNK613DG
NC
R5
13 kΩ
1%
FB
BP
S
C4
1 µF
50 V
R6
9.31 kΩ
1%
PI-5116-050808
Figure 8.
LinkSwitch-II Flyback Power Supply Without Bias Supply.
BYPASS pin voltage. The parameters IS2 and VBP are provided in
the parameter table of the LinkSwitch-II data sheet. Diode D6 can
be any low cost diode such as FR102, 1N4148 or BAV19/20/21.
Quick Design Checklist
As with any power supply design, all LinkSwitch-II designs
should be verified on the bench to make sure that component
specifications are not exceeded under worst-case conditions.
The following minimum set of tests is strongly recommended:
1. Maximum drain voltage – Verify that peak VDS does not exceed
680 V at the highest input voltage and maximum output power.
2. Maximum drain current – At maximum ambient temperature,
maximum input voltage and maximum output load, verify
drain current waveforms at start-up for any signs of trans-
former saturation and excessive leading edge current spikes.
LinkSwitch-II has a leading edge blanking time of 170 ns to
prevent premature termination of the ON-cycle.
3. Thermal check – At maximum output power, both minimum
and maximum input voltage and maximum ambient temperature; verify that temperature specifications are not exceeded
for LinkSwitch-II, transformer, output diodes and output
capacitors. Enough thermal margin should be allowed for
part-to-part variation of the RDS(ON) of LinkSwitch-II, as specified
in the data sheet. To assure 10% CC tolerance a maximum
SOURCE pin temperature of 90 ºC is recommended.
Design Tools
Up-to-date information on design tools can be found at the
Power Integrations web site: www.powerint.com
7
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Rev. F 01/10
LNK603-606/613-616
Absolute Maximum Ratings(1,4)
DRAIN Voltage ............................................ ..............-0.3 V to 700 V
DRAIN Peak Current: LNK603/613....................320 (480) mA(4)
LNK604/614................... 400 (600) mA(4)
LNK605/615................... 504 (750) mA(4)
LNK606/616................... 654 (980) mA(4)
Peak Negative Pulsed Drain Current ............................. -100 mA(2)
FEEDBACK Pin Voltage .................................................-0.3 V to 9 V
FEEDBACK Pin Current ....................................................... 100 mA
BYPASS Pin Voltage ................................................... -0.3 V to 9 V
Storage Temperature ............................................ -65 °C to 150 °C
Operating Junction Temperature.........................-40 °C to 150 °C
Lead Temperature(3) .................................................................260 °C
Notes:
1. All voltages referenced to SOURCE, TA = 25 °C.
2. Duration not to exceed 2 msec.
3. 1/16 in. from case for 5 seconds.
4. The higher peak DRAIN current is allowed while the DRAIN voltage is simultaneously less than 400 V.
5. Maximum ratings specified may be applied, one at a time without causing permanent damage to the product. Exposure to Absolute Maximum ratings for extended
periods of time may affect product reliability.
Thermal Impedance
Thermal Impedance: P or G Package:
(qJA) ....................................70 °C/W(2); 60 °C/W(3)
(qJC)(1) ......................................................... 11 °C/W
D Package:
(qJA .....................................100 °C/W(2); 80 °C/W(3)
(qJC)(1) ......................................................30 °C/W
Parameter
Symbol
Notes:
1. Measured on pin 8 (SOURCE) close to plastic interface.
2. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper clad.
3. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper clad.
Conditions
SOURCE = 0 V; TJ = 0 to 100 °C
(Unless Otherwise Specified)
Min
Typ
Max
LNK603/6
59
66
73
LNK613/6
58
65
72
Units
Control Functions
TJ = 25 °C, VFB = VFBth
tON × IFB = 2 mA-ms
(See Note 1,7)
Output Frequency
fOSC
Frequency Ratio
(Constant Current)
fRATIO(CC)
TJ = 25 °C
Between VFB = 1.0 V and VFB = 1.6 V
1.59
1.635
1.68
Frequency Ratio
(Inductance Correction)
fRATIO(IC)
Between tON × IFB = 1.6 mA × ms
and tON × IFB = 2 mA × ms
1.160
1.215
1.265
Peak-Peak Jitter Compared to
Average Frequency, TJ = 25 °C
Frequency Jitter
Ratio of Output Frequency at Auto-Restart
fOSC(AR)
TJ = 25 °C
Relative to fOSC
Maximum Duty Cycle
DCMAX
(Note 4,5)
FEEDBACK Pin
Voltage
VFBth
FEEDBACK Pin
Voltage Temperature
Coefficient
TCVFB
FEEDBACK Pin
Voltage at Turn-OFF
Threshold
VFB(AR)
Cable Compensation
Factor
υFB
TJ = 25 °C
See Figure 19,
CBP = 10 mF
±7
12
16.5
%
21
55
LNK603/604P
LNK603/604D
LNK605P, LNK605D
LNK606P/G/D
LNK613/614P
LNK613/614/615D
LNK615P
LNK616P/G/D
1.815
1.855
1.835
1.775
1.935
1.975
1.975
1.935
1.840
1.880
1.860
1.800
1.960
2.000
2.000
1.960
LNK613
See Figure 19
LNK614
See Figure 19
0.72
CBP = 1 mF
CBP = 10 mF
CBP = 1 mF
1.035
1.055
1.045
CBP = 10 mF
1.065
%
%
1.865
1.905
1.885
1.825
1.985
2.025
2.025
1.985
-0.01
0.65
kHz
V
%/°C
0.79
V
8
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
Parameter
Symbol
Conditions
SOURCE = 0 V; TJ = 0 to 100 °C
(Unless Otherwise Specified)
Min
Typ
Max
Units
Control Functions (cont.)
Cable Compensation
Factor
Switch ON-Time
LNK615
See Figure 19
υFB
tON
LNK616
See Figure 19
fOSC = 66 kHz
VFB = VFBth
(Note 5)
CBP = 1 mF
1.05
CBP = 10 mF
1.07
CBP = 1 mF
1.06
CBP = 10 mF
1.09
IFB = -500 mA
4
IFB = -1 mA
2
IFB = -1.5 mA
1.33
IFB = -2 mA
1
Minimum Switch
ON-Time
tON(min)
(Note 5)
FEEDBACK Pin
Sampling Delay
tFB
See Figure 19
IS1
FB Voltage > VFBth
DRAIN Supply
Current
BYPASS Pin
Charge Current
IS2
ICH1
ICH2
700
FB Voltage = VFBth -0.1,
Switch ON-Time = tON
(MOSFET Switching at fOSC)
VBP = 0 V
VBP = 4 V
ms
2.35
ns
2.55
2.75
280
330
LNK6X3/4
440
520
LNK6X5
480
560
LNK6X6
520
600
LNK6X3/4
-5.0
-3.4
-1.8
LNK6X5/6
-7.0
-4.8
-2.5
LNK6X3/4
-4.0
-2.3
-1.0
LNK6X5/6
-5.6
-3.2
-1.4
ms
mA
mA
BYPASS Pin Voltage
VBP
5.65
6.00
6.25
V
BYPASS Pin
Voltage Hysteresis
VBPH
0.70
1.00
1.20
V
VSHUNT
6.2
6.5
6.8
V
LNK6X3
di/dt = 50 mA/ms , TJ = 25 °C
186
200
214
LNK6X4
di/dt = 60 mA/ms , TJ = 25 °C
233
250
267
LNK6X5
di/dt = 70 mA/ms , TJ = 25 °C
293
315
337
LNK6X6
di/dt = 100 mA/ms , TJ = 25 °C
382
410
438
0.975
1.000
1.025
170
215
135
142
BYPASS Pin
Shunt Voltage
Circuit Protection
Current Limit
Normalized Output
Current
Leading Edge
Blanking Time
Thermal Shutdown
Temperature
Thermal Shutdown
Hysteresis
ILIMIT
IO
tLEB
TSD
TSDH
TJ = 25 °C
See Figure 21, (See Note 6)
TJ = 25 °C
(See Note 5)
mA
60
ns
150
°C
°C
9
www.powerint.com
Rev. F 01/10
LNK603-606/613-616
Parameter
Symbol
Conditions
SOURCE = 0 V; TJ = 0 to 100 °C
(Unless Otherwise Specified)
Min
Typ
Max
TJ = 25 °C
24
28
TJ = 100 °C
36
42
TJ = 25 °C
24
28
TJ = 100 °C
36
42
TJ = 25 °C
16
19
TJ = 100 °C
24
28
TJ = 25 °C
9.6
11
TJ = 100 °C
14
17
Units
Output
LNK6X3
ID = 50 mA
ON-State
Resistance
LNK6X4
ID = 50 mA
RDS(ON)
LNK6X5
ID = 62 mA
LNK6X6
ID = 82 mA
OFF-State
Leakage
Breakdown
Voltage
IDSS1
VDS = 560 V See Figure 20
TJ = 125 °C See Note 3
IDSS2
VDS = 375 V See Figure 20
TJ = 50 °C
BVDSS
TJ = 25 °C
See Figure 20
DRAIN Supply
Voltage
Auto-Restart
ON-Time
tAR-ON
Auto-Restart
OFF-Time
tAR-OFF
Open-Loop
FEEDBACK Pin
Current Threshold
50
mA
15
700
V
50
V
tON × IFB = 2 mA-ms, fOSC = 12 kHz
VFB = 0
See Notes 1, 5
IOL
Open-Loop
ON-Time
W
450
1.2
ms
2
s
See Note 5
-120
mA
See Note 5
90
ms
NOTES:
1. Auto-restart ON-time is a function of switching frequency programmed by tonx IFB and minimum frequency in CC mode.
2. The current limit threshold is compensated to cancel the effect of current limit delay. As a result the output current stays constant
across the input line range.
3. IDSS1 is the worst case OFF state leakage specification at 80% of BVDSS and maximum operating junction temperature. IDSS2 is a
typical specification under worst case application conditions (rectified 265 VAC) for no-load consumption calculations.
4. When the duty-cycle exceeds DCMAX the LinkSwitch-II operates in on-time extension mode.
5. This parameter is derived from characterization.
6. Mechanical stress induced during the assembly may cause shift in this parameter. This shift has no impact on the ability of
LinkSwitch-II to meet ±10% in mass production given the design follows recommendation in AN-44 and good manufacturing practice
7. The switching frequency is programmable between 60 kHz and 85 kHz.
10
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
Typical Performance Characteristics
0.800
0.600
0.400
0.200
0.000
-40
-15
10
35
60
85
1.000
0.800
0.600
0.400
0.200
0.000
-40
110 135
PI-5086-041008
1.000
1.200
Frequency
(Normalized to 25 °C)
PI-5085-040508
Current Limit
(Normalized to 25 °C)
1.200
-15
Temperature (°C)
PI-5087-040508
Frequency Ratio
(Normalized to 25 °C)
1.000
0.800
0.600
0.400
0.200
-15
10
35
60
85
0.800
0.600
0.400
0.200
-15
0.800
0.600
0.400
0.200
35
60
85
Temperature (°C)
Figure 13. Feedback Voltage vs. Temperature.
35
60
85
110 135
110 135
Figure 12. Frequency Ratio vs. Temperature (Inductor Current).
PI-5090-040508
1.200
Normalized Output Current
(Normalized to 25 °C)
1.000
10
Temperature (°C)
PI-5089-040508
Feedback Voltage
(Normalized to 25 °C)
1.200
10
110 135
1.000
0.000
-40
110 135
Figure 11. Frequency Ratio vs. Temperature (Constant Current).
-15
85
1.200
Temperature (°C)
0.000
-40
60
Figure 10. Output Frequency vs. Temperature.
1.200
0.000
-40
35
PI-5088-040508
Current Limit vs. Temperature.
Frequency Ratio
(Normalized to 25 °C)
Figure 9.
10
Temperature (°C)
1.000
0.800
0.600
0.400
0.200
0.000
-40
-15
10
35
60
85
110 135
Temperature (°C)
Figure 14. Normalized Output Current vs. Temperature.
11
www.powerint.com
Rev. F 01/10
LNK603-606/613-616
Typical Performance Characteristics (cont.)
TCASE=25 °C
TCASE=100 °C
250
Drain Current (mA)
1.0
200
150
100
Scaling Factors:
LNK6X3 1.0
LNK6X4 1.0
LNK6X5 1.5
LNK6X6 2.5
50
0.9
0
25
50
0
75 100 125 150
0
Junction Temperature (°C)
6
8
10
Figure 16. Output Characteristic.
50
PI-5083-040408
1000
100
40
Power (mW)
Drain Capacitance (pF)
4
DRAIN Voltage (V)
Figure 15. Breakdown vs. Temperature.
Scaling Factors:
LNK6X3 1.0
LNK6X4 1.0
LNK6X5 1.5
LNK6X6 2.5
10
2
PI-5084-040408
-50 -25
PI-5082-040408
300
PI-2213-012301
Breakdown Voltage
(Normalized to 25 °C)
1.1
Scaling Factors:
LNK6X3 1.0
LNK6X4 1.0
LNK6X5 1.5
LNK6X6 2.5
30
20
10
0
1
0
100
200
300
400
Drain Voltage (V)
Figure 17. COSS vs. Drain Voltage.
500
600
0
200
400
600
DRAIN Voltage (V)
Figure 18. Drain Capacitance Power.
12
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
LinkSwitch-II
VIN +
FB
S
BP
S
D
S
10 µF
+
6.2 V
VOUT
S
500 Ω
+
2V
PI-4961-022708
1) Raise VBP voltage from 0 V to 6.2 V, down to 4.5 V, up to 6.2 V
2) Raise VIN until cycle skipping occurs at VOUT to measure VFBth
3) Reduce VIN until cycle skipping stops at VOUT to measure VFBth-. Cable drop compensaion factor is υFB = VFBth / VFBth4) Apply 1.5 V at VIN and measure tFB delay from start of cycle falling edge to the next falling edge
Figure 19. Test Set-up for Feedback Pin Measurements.
LinkSwitch-II
5 µF
50 kΩ
10 kΩ
1 µF
FB
S
BP
S
.1 µF
S
D
4 kΩ
VIN
S1
S
S2
+
16 V
Curve
Tracer
To measure BVDSS, IDSS1, and IDSS2 follow these steps:
1) Close S1, open S2
2) Power-up VIN source (16 V)
3) Open S1, close S2
4) Measure I/V characteristics of Drain pin using the curve tracer
PI-4962-040308
Figure 20. Test Set-up for Leakage and Breakdown Tests.
13
www.powerint.com
Rev. F 01/10
LNK603-606/613-616
470 pF
680 µF
200 V
3.3 V
RO
+
VO
200 Ω
11.5 kΩ
+
50 V
LinkSwitch-II
FB
S
BP
S
S
10 µF
D
7.15 kΩ
S
1)The transformer inductance is chosen to set the value of tON × IFB to 2 mA × µS
2) RO is chosen to operate test circuit in the CC region
3) VO is measured
4) Output current is VO / RO
PI-4963-022708
Figure 21. Test Set-up for Output Current Measurements.
14
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
DIP-8C (P Package)
-E-
⊕D S
.004 (.10)
.240 (6.10)
.260 (6.60)
Pin 1
-D-
.367 (9.32)
.387 (9.83)
.057 (1.45)
.068 (1.73)
(NOTE 6)
.125 (3.18)
.145 (3.68)
-T-
Notes:
1. Package dimensions conform to JEDEC specification
MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP)
package with .300 inch row spacing.
2. Controlling dimensions are inches. Millimeter sizes are
shown in parentheses.
3. Dimensions shown do not include mold flash or other
protrusions. Mold flash or protrusions shall not exceed
.006 (.15) on any side.
4. Pin locations start with Pin 1, and continue counter-clockwise to Pin 8 when viewed from the top. The notch and/or
dimple are aids in locating Pin 1. Pin 3 is omitted.
5. Minimum metal to metal spacing at the package body for
the omitted lead location is .137 inch (3.48 mm).
6. Lead width measured at package body.
7. Lead spacing measured with the leads constrained to be
perpendicular to plane T.
.015 (.38)
MINIMUM
SEATING
PLANE
.008 (.20)
.015 (.38)
.120 (3.05)
.140 (3.56)
.100 (2.54) BSC
.014 (.36)
.022 (.56)
.048 (1.22)
.053 (1.35)
⊕T E D
.300 (7.62) BSC
(NOTE 7)
.137 (3.48)
MINIMUM
P08C
.300 (7.62)
.390 (9.91)
S .010 (.25) M
PI-3933-101507
SMD-8C (G Package)
⊕ D S .004 (.10)
.046 .060
.060 .046
-E-
.080
.086
Pin 1
.137 (3.48)
MINIMUM
Solder Pad Dimensions
.367 (9.32)
.387 (9.83)
.420
.057 (1.45)
.068 (1.73)
(NOTE 5)
.125 (3.18)
.145 (3.68)
.032 (.81)
.037 (.94)
.286
Pin 1
.100 (2.54) (BSC)
-D-
.186
.372 (9.45)
.388 (9.86)
⊕ E S .010 (.25)
.240 (6.10)
.260 (6.60)
Notes:
1. Controlling dimensions are
inches. Millimeter sizes are
shown in parentheses.
2. Dimensions shown do not
include mold flash or other
protrusions. Mold flash or
protrusions shall not exceed
.006 (.15) on any side.
3. Pin locations start with Pin 1,
and continue counter-clockwise to Pin 8 when viewed
from the top. Pin 3 is omitted.
4. Minimum metal to metal
spacing at the package body
for the omitted lead location
is .137 inch (3.48 mm).
5. Lead width measured at
package body.
6. D and E are referenced
datums on the package
body.
.048 (1.22)
.053 (1.35)
.004 (.10)
.009 (.23)
.004 (.10)
.012 (.30)
.036 (0.91)
.044 (1.12)
0°- 8°
G08C
PI-4015-101507
15
www.powerint.com
Rev. F 01/10
LNK603-606/613-616
SO-8C
4
B
0.10 (0.004) C A-B 2X
2
DETAIL A
4.90 (0.193) BSC
A
4
8
D
5
2 3.90 (0.154) BSC
GAUGE
PLANE
SEATING
PLANE
6.00 (0.236) BSC
0-8
C
1.04 (0.041) REF
0.10 (0.004) C D
2X
1
Pin 1 ID
4
0.25 (0.010)
BSC
0.40 (0.016)
1.27 (0.050)
0.20 (0.008) C
2X
7X 0.31 - 0.51 (0.012 - 0.020)
0.25 (0.010) M C A-B D
1.27 (0.050) BSC
1.25 - 1.65
(0.049 - 0.065)
1.35 (0.053)
1.75 (0.069)
o
DETAIL A
0.10 (0.004)
0.25 (0.010)
0.10 (0.004) C
H
7X
SEATING PLANE
0.17 (0.007)
0.25 (0.010)
C
Reference
Solder Pad
Dimensions
+
2.00 (0.079)
+
D07C
4.90 (0.193)
+
+
1.27 (0.050)
Notes:
1. JEDEC reference: MS-012.
2. Package outline exclusive of mold flash and metal burr.
3. Package outline inclusive of plating thickness.
4. Datums A and B to be determined at datum plane H.
5. Controlling dimensions are in millimeters. Inch dimensions
are shown in parenthesis. Angles in degrees.
0.60 (0.024)
PI-4526-040207
Part Ordering Information
• LinkSwitch Product Family
• II Series Number
• Package Identifier
G
Plastic Surface Mount DIP
P
Plastic DIP
D
Plastic SO-8
• Package Material
G
GREEN: Halogen Free and RoHS Compliant
• Tape & Reel and Other Options
Blank
LNK 615
D G - TL
TL
Standard Configurations
Tape & Reel, 1 k pcs minimum for G Package. 2.5 k pcs for D Package. Not available
for P Package.
16
Rev. F 01/10
www.powerint.com
LNK603-606/613-616
17
www.powerint.com
Rev. F 01/10
Revision
Notes
Date
C
Final data sheet
06/08
D
Auto-restart time modified PCN-09131
03/09
E
Introduced Max current limit when V DRAIN is below 400 V
07/09
F
Added LNK616DG and LNK606DG.
01/10
For the latest updates, visit our website: www.powerint.com
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power
Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES
NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED
WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS.
Patent Information
The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered by
one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A
complete list of Power Integrations patents may be found at www.powerint.com. Power Integrations grants its customers a license under
certain patent rights as set forth at http://www.powerint.com/ip.htm.
Life Support Policy
POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein:
1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant
injury or death to the user.
2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause
the failure of the life support device or system, or to affect its safety or effectiveness.
The PI logo, TOPSwitch, TinySwitch, LinkSwitch, DPA-Switch, PeakSwitch, EcoSmart, Clampless, E-Shield, Filterfuse, StakFET, PI Expert
and PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies.
©2010, Power Integrations, Inc.
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