AD AD7858LARZ 3 v to 5 v single supply, 200 ksps 8-channel, 12-bit sampling adc Datasheet

a
FEATURES
Specified for V DD of 3 V to 5.5 V
AD7858—200 kSPS; AD7858L—100 kSPS
System and Self-Calibration with Autocalibration on
Power-Up
Eight Single-Ended or Four Pseudo-Differential Inputs
Low Power
AD7858: 12 mW (VDD = 3 V)
AD7858L: 4.5 mW (V DD = 3 V)
Automatic Power-Down After Conversion (25 ␮W)
Flexible Serial Interface:
8051/SPI™/QSPI™/␮P Compatible
24-Lead DIP, SOIC, and SSOP Packages
APPLICATIONS
Battery-Powered Systems (Personal Digital Assistants,
Medical Instruments, Mobile Communications)
Pen Computers
Instrumentation and Control Systems
High-Speed Modems
GENERAL DESCRIPTION
The AD7858/AD7858L are high-speed, low-power, 12-bit
ADCs that operate from a single 3 V or 5 V power supply, the
AD7858 being optimized for speed and the AD7858L for low
power. The ADC powers up with a set of default conditions at
which time it can be operated as a read-only ADC. The ADC
contains self-calibration and system calibration options to ensure accurate operation over time and temperature and have a
number of power-down options for low-power applications.
The part powers up with a set of default conditions and can
operate as a read-only ADC.
The AD7858 is capable of 200 kHz throughput rate while the
AD7858L is capable of 100 kHz throughput rate. The input
track-and-hold acquires a signal in 500 ns and features a
pseudo-differential sampling scheme. The AD7858/AD7858L
voltage range is 0 to VREF with straight binary output coding.
Input signal range is to the supply and the part is capable of converting full power signals to 100 kHz.
CMOS construction ensures low power dissipation of typically
4.5 mW for normal operation and 1.15 mW in power-down
mode with a throughput rate of 10 kSPS (VDD = 3 V). The part
is available in 24-lead, 0.3 inch-wide dual-in-line package
(DIP), 24-lead small outline (SOIC), and 24-lead small shrink
outline (SSOP) packages.
3 V to 5 V Single Supply, 200 kSPS
8-Channel, 12-Bit Sampling ADC
AD7858/AD7858L
FUNCTIONAL BLOCK DIAGRAM
AVDD
AGND
AIN1
I/P
MUX
AD7858/
AD7858L
T/H
AIN8
DVDD
2.5V
REFERENCE
COMP
REFIN /REF OUT
DGND
BUF
CREF1
CHARGE
REDISTRIBUTION
DAC
CLKIN
CREF2
CAL
SAR AND ADC
CONTROL
CALIBRATION
MEMORY AND
CONTROLLER
CONVST
BUSY
SLEEP
SERIAL INTERFACE/CONTROL REGISTER
SYNC
DIN
DOUT
SCLK
PRODUCT HIGHLIGHTS
1. Specified for 3 V and 5 V supplies.
2. Automatic calibration on power-up.
3. Flexible power management options including automatic
power-down after conversion.
4. Operates with reference voltages from 1.2 V to VDD.
5. Analog input range from 0 V to VDD.
6. Eight single-ended or four pseudo-differential input channels.
7. System and self-calibration.
8. Versatile serial I/O port (SPI/QSPI/8051/µP).
9. Lower power version AD7858L.
See page 31 for data sheet index.
SPI and QSPI are trademarks of Motorola, Inc.
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
World Wide Web Site: http://www.analog.com
Fax: 781/326-8703
© Analog Devices, Inc., 2000
1, 2
(AV = DV = +3.0 V to +5.5 V, REF /REF = 2.5 V External
AD7858/AD7858L–SPECIFICATIONS
Reference unless otherwise noted, f
= 4 MHz (1.8 MHz B Grade (0ⴗC to +70ⴗC), 1 MHz A and B Grades (–40ⴗC to +85ⴗC) for L Version); f
=
DD
DD
IN
OUT
CLKIN
SAMPLE
200 kHz (AD7858), 100 kHz (AD7858L); SLEEP = Logic High; TA = TMIN to TMAX, unless otherwise noted.) Specifications in ( ) apply to the AD7858L.
Parameter
DYNAMIC PERFORMANCE
Signal to Noise + Distortion Ratio3
(SNR)
Total Harmonic Distortion (THD)
Peak Harmonic or Spurious Noise
Intermodulation Distortion (IMD)
Second Order Terms
Third Order Terms
Channel-to-Channel Isolation
DC ACCURACY
Resolution
Integral Nonlinearity
Differential Nonlinearity
Total Unadjusted Error
Unipolar Offset Error
Unipolar Offset Error Match
Positive Full-Scale Error
Positive Full-Scale Error Match
ANALOG INPUT
Input Voltage Ranges
Leakage Current
Input Capacitance
REFERENCE INPUT/OUTPUT
REFIN Input Voltage Range
Input Impedance
REFOUT Output Voltage
REFOUT Tempco
LOGIC INPUTS
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IIN
Input Capacitance, CIN4
A Version1 B Version1
Units
Test Conditions/Comments
70
71
dB min
–78
–78
–78
–78
dB max
dB max
Typically SNR is 72 dB
VIN = 10 kHz Sine Wave, fSAMPLE = 200 kHz (100 kHz)
VIN = 10 kHz Sine Wave, fSAMPLE = 200 kHz (100 kHz)
VIN = 10 kHz Sine Wave, fSAMPLE = 200 kHz (100 kHz)
–78
–78
–90
–80
–80
–90
dB typ
dB typ
dB typ
fa = 9.983 kHz, fb = 10.05 kHz, fSAMPLE = 200 kHz (100 kHz)
fa = 9.983 kHz, fb = 10.05 kHz, fSAMPLE = 200 kHz (100 kHz)
VIN = 25 kHz
12
±1
±1
12
±1
± 0.5
(± 1)
Any Channel
(± 1)
±1
±1
Bits
LSB max
LSB max
LSB max
LSB max
LSB max
±1
±5
± 2.5
(± 3)
(± 1.5)
1.5
±4
± 1.5
1
±1
±5
± 2.5
(± 3)
(± 1.5)
1.5
±4
± 1.5
1
LSB typ
LSB max
LSB max
LSB max
LSB max
LSB max
LSB max
LSB max
LSB max
0 to VREF
0 to VREF
Volts
±1
20
±1
20
µA max
pF typ
2.3/VDD
150
2.3/2.7
20
2.3/VDD
150
2.3/2.7
20
V min/max
kΩ typ
V min/max
ppm/°C typ
Functional from 1.2 V
2.4
2.1
0.8
0.6
± 10
10
2.4
2.1
0.8
0.6
± 10
10
V min
V min
V max
V max
µA max
pF max
AVDD = DVDD = 4.5 V to 5.5 V
AVDD = DVDD = 3.0 V to 3.6 V
AVDD = DVDD = 4.5 V to 5.5 V
AVDD = DVDD = 3.0 V to 3.6 V
Typically 10 nA, VIN = 0 V or VDD
LOGIC OUTPUTS
Output High Voltage, VOH
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance4
Output Coding
CONVERSION RATE
Conversion Time
Track/Hold Acquisition Time
4
4
2.4
2.4
0.4
0.4
± 10
± 10
10
10
Straight (Natural) Binary
V min
V min
V max
µA max
pF max
4.6 (18)
µs max
µs max
µs min
0.4 (1)
4.6
(10)
0.4 (1)
–2–
2.5 V External Reference VDD = 3 V, VDD = 5 V (B Grade Only)
5 V External Reference VDD = 5 V
(L Version, 5 V External Reference, VDD = 5 V)
(L Version)
Guaranteed No Missed Codes to 12 Bits. 2.5 V External
Reference VDD = 3 V, 5 V External Reference, VDD = 5 V
Typically ± 2 LSBs
5 V External Reference, VDD = 5 V
(L Version)
(L Version, 5 V External Reference, VDD = 5 V)
5 V External Reference, VDD = 5 V
i.e., AIN(+) – AIN(–) = 0 to VREF, AIN(–) can be biased
up but AIN(+) cannot go below AIN(–)
ISOURCE = 200 µA
AVDD = DVDD = 4.5 V to 5.5 V
AVDD = DVDD = 3.0 V to 3.6 V
ISINK = 0.8 mA
(L Versions Only, –40°C to +85°C, 1 MHz CLKIN)
(L Versions Only, 0°C to +70°C, 1.8 MHz CLKIN)
(L Versions Only)
REV. B
AD7858/AD7858L
Parameter
DYNAMIC PERFORMANCE
AVDD, DVDD
IDD
Normal Mode5
Sleep Mode6
With External Clock On
With External Clock Off
Normal-Mode Power Dissipation
Sleep Mode Power Dissipation
With External Clock On
With External Clock Off
SYSTEM CALIBRATION
Offset Calibration Span7
Gain Calibration Span7
A Version1
B Version1
Units
+3.0/+5.5
+3.0/+5.5
V min/max
6 (1.9)
5.5 (1.9)
6 (1.9)
5.5 (1.9)
mA max
mA max
AVDD = DVDD = 4.5 V to 5.5 V. Typically 4.5 mA (1.5)
AVDD = DVDD = 3.0 V to 3.6 V. Typically 4.0 mA (1.5 mA)
10
10
µA typ
400
400
µA typ
5
5
µA max
200
200
µA typ
33 (10.5)
20 (6.85)
33 (10.5)
20 (6.85)
mW max
mW max
Full Power-Down. Power Management Bits in Control
Register Set as PMGT1 = 1, PMGT0 = 0
Partial Power-Down. Power Management Bits in
Control Register Set as PMGT1 = 1, PMGT0 = 1
Typically 1 µA. Full Power-Down. Power Management Bits
in Control
Register Set as PMGT1 = 1, PMGT0 = 0
Partial Power-Down. Power Management Bits in Control
Register Set as PMGT1 = 1, PMGT0 = 1
VDD = 5.5 V. Typically 25 mW (8); SLEEP = VDD
VDD = 3.6 V. Typically 15 mW (5.4); SLEEP = VDD
55
36
27.5
18
55
36
27.5
18
µW typ
µW typ
µW max
µW max
VDD = 5.5 V. SLEEP = 0 V
VDD = 3.6 V. SLEEP = 0 V
VDD = 5.5 V. Typically 5.5 µW; SLEEP = 0 V
VDD = 3.6 V. Typically 3.6 µW; SLEEP = 0 V
V max/min
V max/min
Allowable Offset Voltage Span for Calibration
Allowable Full-Scale Voltage Span for Calibration
+0.05 × VREF/–0.05 × VREF
+1.025 × VREF/–0.975 × VREF
Test Conditions/Comments
NOTES
1
Temperature ranges as follows: A, B Versions: –40°C to +85°C. For L Versions, A and B Versions f CLKIN = 1 MHz over –40°C to +85°C temperature range,
B Version f CLKIN = 1.8 MHz over 0°C to +70°C temperature range.
2
Specifications apply after calibration.
3
SNR calculation includes distortion and noise components.
4
Sample tested @ +25°C to ensure compliance.
5
All digital inputs @ DGND except for CONVST, SLEEP, CAL, and SYNC @ DVDD. No load on the digital outputs. Analog inputs @ AGND.
6
CLKIN @ DGND when external clock off. All digital inputs @ DGND except for CONVST, SLEEP, CAL, and SYNC @ DVDD. No load on the digital
outputs. Analog inputs @ AGND.
7
The Offset and Gain Calibration Spans are defined as the range of offset and gain errors that the AD7858/AD7858L can calibrate. Note also that these are voltage
spans and are not absolute voltages ( i.e., the allowable system offset voltage presented at AIN(+) for the system offset error to be adjusted out will be AIN(–)
± 0.05 × VREF, and the allowable system full-scale voltage applied between AIN(+) and AIN(–) for the system full-scale voltage error to be adjusted out will be
VREF ± 0.025 × VREF). This is explained in more detail in the Calibration section of the data sheet.
Specifications subject to change without notice.
REV. B
–3–
AD7858/AD7858L
(AVDD = DVDD = +3.0 V to +5.5 V; fCLKIN = 4 MHz for AD7858 and 1.8/1 MHz for AD7858L;
A
MIN to TMAX , unless otherwise noted)
TIMING SPECIFICATIONS1 T = T
Limit at TMIN, TMAX
(A, B Versions)
5V
3V
Units
Description
500
4
1.8
1
4
100
90
4.6
10 (18)
–0.4 tSCLK
⫿0.4 tSCLK
90
90
115
60
30
0.4 tSCLK
0.4 tSCLK
50
50/0.4 tSCLK
50
130
90
2.5 tCLKIN
2.5 tCLKIN
31.25
kHz min
MHz max
MHz max
MHz max
MHz max
ns min
ns max
µs max
µs max
ns min
ns min/max
ns max
ns max
ns max
ns min
ns min
ns min
ns min
ns min
ns min/max
ns max
ns max
ns max
ns max
ns max
ms typ
Master Clock Frequency
t125
t13
t146
t15
t16
tCAL7
500
4
1.8
1
4
100
50
4.6
10 (18)
–0.4 tSCLK
⫿0.4 tSCLK
50
50
75
40
20
0.4 tSCLK
0.4 tSCLK
30
30/0.4 tSCLK
50
90
50
2.5 tCLKIN
2.5 tCLKIN
31.25
tCAL17
27.78
27.78
ms typ
tCAL27
3.47
3.47
ms typ
Parameter
fCLKIN
2
fSCLK
t1 3
t2
tCONVERT
t3
t4 4
t5 4
t6 4
t7
t8
t9
t10
t11
L Version, 0°C to +70°C, B Grade Only
L Version, –40°C to +85°C
CONVST Pulsewidth
CONVST↓ to BUSY↑ Propagation Delay
Conversion Time = 18 tCLKIN
L Version 1.8 (1) MHz CLKIN. Conversion Time = 18 tCLKIN
SYNC↓ to SCLK↓ Setup Time (Noncontinuous SCLK Input)
SYNC↓ to SCLK↓ Setup Time (Continuous SCLK Input)
Delay from SYNC↓ Until DOUT Three-State Disabled
Delay from SYNC↓ Until DIN Three-State Disabled
Data Access Time After SCLK↓
Data Setup Time Prior to SCLK↑
Data Valid to SCLK Hold Time
SCLK High Pulsewidth
SCLK Low Pulsewidth
SCLK↑ to SYNC↑ Hold Time (Noncontinuous SCLK)
(Continuous SCLK)
Delay from SYNC↑ Until DOUT Three-State Enabled
Delay from SCLK↑ to DIN Being Configured as Output
Delay from SCLK↑ to DIN Being Configured as Input
CAL↑ to BUSY↑ Delay
CONVST↓ to BUSY↑ Delay in Calibration Sequence
Full Self-Calibration Time, Master Clock Dependent
(125013 tCLKIN)
Internal DAC Plus System Full-Scale Calibration Time, Master
Clock Dependent (111114 tCLKIN)
System Offset Calibration Time, Master Clock Dependent
(13899 tCLKIN)
NOTES
1
Sample tested at +25°C to ensure compliance. All input signals are specified with tr = tf = 5 ns (10% to 90% of V DD) and timed from a voltage level of 1.6 V.
See Table XI and timing diagrams for different interface modes and Calibration.
2
Mark/Space ratio for the master clock input is 40/60 to 60/40.
3
The CONVST pulsewidth will apply here only for normal operation. When the part is in power-down mode, a different CONVST pulsewidth will apply
(see Power-Down section).
4
Measured with the load circuit of Figure 1 and defined as the time required for the output to cross 0.8 V or 2.4 V.
5
t12 is derived form the measured time taken by the data outputs to change 0.5 V when loaded with the circuit of Figure 1. The measured number is then extrapolated
back to remove the effects of charging or discharging the 100 pF capacitor. This means that the time, t 12, quoted in the timing characteristics is the true bus
relinquish time of the part and is independent of the bus loading.
6
t14 is derived form the measured time taken by the data outputs to change 0.5 V when loaded with the circuit of Figure 1. The measured number is then
extrapolated back to remove the effects of charging or discharging the 100 pF capacitor. This means that the time quoted in the Timing Characteristics is the
true delay of the part in turning off the output drivers and configuring the DIN line as an input. Once this time has elapsed the user can drive the DIN line
knowing that a bus conflict will not occur.
7
The typical time specified for the calibration times is for a master clock of 4 MHz. For the L version the calibration times will be longer than those quoted here due to
the 1.8/1 MHz master clock.
Specifications subject to change without notice.
–4–
REV. B
AD7858/AD7858L
TYPICAL TIMING DIAGRAMS
Figures 2 and 3 show typical read and write timing diagrams for
serial Interface Mode 2. The reading and writing occurs after
conversion in Figure 2, and during conversion in Figure 3. To
attain the maximum sample rate of 100 kHz (AD7858L) or
200 kHz (AD7858), reading and writing must be performed
during conversion as in Figure 3. At least 400 ns acquisition
time must be allowed (the time from the falling edge of BUSY
to the next rising edge of CONVST) before the next conversion
begins to ensure that the part is settled to the 12-bit level. If the
user does not want to provide the CONVST signal, the conversion can be initiated in software by writing to the control register.
1.6mA
TO
OUTPUT
PIN
IOL
+2.1V
CL
100pF
200␮A
IOH
Figure 1. Load Circuit for Digital Output Timing
Specifications
tCONVERT = 4.6␮s MAX, 10␮s MAX FOR L VERSION
t1 = 100ns MIN, t4 = 50/90ns MAX 5V/3V, t7 = 40/60ns MIN 5V/3V
t1
CONVST (I/P)
tCONVERT
t2
BUSY (O/P)
SYNC (I/P)
t3
5
t4
t6
THREE-STATE
DOUT (O/P)
6
t6
DB15
16
t10
t12
DB11
DB0
THREESTATE
t8
t7
DIN (I/P)
t11
t9
1
SCLK (I/P)
DB15
DB11
DB0
Figure 2. AD7858/AD7858L Timing Diagram for Interface Mode 2 (Reading/Writing After Conversion)
tCONVERT = 4.6␮s MAX, 10␮s MAX FOR L VERSION
t1 = 100ns MIN, t4 = 50/90ns MAX 5V/3V, t7 = 40/60ns MIN 5V/3V
t1
CONVST (I/P)
tCONVERT
t2
BUSY (O/P)
SYNC (I/P)
t3
5
t4
DOUT (O/P)
THREE-STATE
6
t6
t6
DB15
DB11
16
t10
t12
DB0
THREESTATE
t8
t7
DIN (I/P)
t11
t9
1
SCLK (I/P)
DB15
DB11
DB0
Figure 3. AD7858/AD7858L Timing Diagram for Interface Mode 2 (Reading/Writing During Conversion)
REV. B
–5–
AD7858/AD7858L
ABSOLUTE MAXIMUM RATINGS 1
SOIC, SSOP Package, Power Dissipation . . . . . . . . . . 450 mW
θJA Thermal Impedance . . . 75°C/W (SOIC) 115°C/W (SSOP)
θJC Thermal Impedance . . . . 25°C/W (SOIC) 35°C/W (SSOP)
Lead Temperature, Soldering
Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . +215°C
Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . +220°C
(TA = +25°C unless otherwise noted)
AVDD to AGND . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
DVDD to DGND . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
AVDD to DVDD . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +0.3 V
Analog Input Voltage to AGND . . . . –0.3 V to AVDD + 0.3 V
Digital Input Voltage to DGND . . . . –0.3 V to DVDD + 0.3 V
Digital Output Voltage to DGND . . . –0.3 V to DVDD + 0.3 V
REFIN/REFOUT to AGND . . . . . . . . . –0.3 V to AVDD + 0.3 V
Input Current to Any Pin Except Supplies2 . . . . . . . ± 10 mA
Operating Temperature Range
Commercial (A, B Versions) . . . . . . . . . . . –40°C to +85°C
Storage Temperature Range . . . . . . . . . . . –65°C to +150°C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
Plastic DIP Package, Power Dissipation . . . . . . . . . . 450 mW
θJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . 105°C/W
θJC Thermal Impedance . . . . . . . . . . . . . . . . . . . . 34.7°C/W
Lead Temperature, (Soldering, 10 sec) . . . . . . . . . . +260°C
NOTES
1
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2
Transient currents of up to 100 mA will not cause SCR latch-up.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the AD7858/AD7858L features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
AD7858AN
AD7858BN
AD7858LAN3
AD7858LBN3
AD7858AR
AD7858BR
AD7858LAR3
AD7858LBR3
AD7858LARS3
EVAL-AD7858CB4
EVAL-CONTROL BOARD5
Linearity Power
Error
Dissipation Package
(LSB)1
(mW)
Options2
±1
± 1/2
±1
±1
±1
± 1/2
±1
±1
±1
20
20
6.85
6.85
20
20
6.85
6.85
6.85
ESD SENSITIVE DEVICE
PIN CONFIGURATIONS
DIP, SOIC, AND SSOP
ORDERING GUIDE
Model
WARNING!
N-24
N-24
N-24
N-24
R-24
R-24
R-24
R-24
RS-24
CONVST 1
24 SYNC
BUSY 2
23 SCLK
SLEEP 3
22 CLKIN
REFIN /REFOUT 4
AVDD 5
21 DIN
AD7858/
AD7858L
20 DOUT
AGND 6
TOP VIEW 19 DGND
CREF1 7 (Not to Scale) 18 DVDD
CREF2 8
17 CAL
AIN1 9
16 AIN8
AIN2 10
15 AIN7
AIN3 11
14 AIN6
AIN4 12
13 AIN5
NOTES
1
Linearity error here refers to integral linearity error.
2
N = Plastic DIP; R = SOIC; RS = SSOP.
3
L signifies the low-power version.
4
This can be used as a stand-alone evaluation board or in conjunction with the EVALCONTROL BOARD for evaluation/demonstration purposes.
5
This board is a complete unit allowing a PC to control and communicate with all
Analog Devices evaluation boards ending in the CB designators.
–6–
REV. B
AD7858/AD7858L
PIN FUNCTION DESCRIPTIONS
Pin
Mnemonic
Description
1
CONVST
2
BUSY
3
SLEEP
4
REFIN/REFOUT
5
6
7
AVDD
AGND
CREF1
8
CREF2
Convert Start. Logic Input. A low to high transition on this input puts the track/hold into its hold mode
and starts conversion. When this input is not used, it should be tied to DVDD.
Busy Output. The busy output is triggered high by the falling edge of CONVST or rising edge of CAL,
and remains high until conversion is completed. BUSY is also used to indicate when the AD7858/
AD7858L has completed its on-chip calibration sequence.
Sleep Input/Low-Power Mode. A Logic 0 initiates a sleep, and all circuitry is powered down including the
internal voltage reference provided there is no conversion or calibration being performed. Calibration
data is retained. A Logic 1 results in normal operation. See Power-Down section for more details.
Reference Input/Output. This pin is connected to the internal reference through a series resistor and is
the reference source for the analog-to-digital converter. The nominal reference voltage is 2.5 V and this
appears at the pin. This pin can be overdriven by an external reference or can be taken as high as AVDD.
When this pin is tied to AVDD, or when an externally applied reference approaches AVDD, the CREF1 pin
should also be tied to AVDD.
Analog Positive Supply Voltage, +3.0 V to +5.5 V.
Analog Ground. Ground reference for track/hold, reference, and DAC.
Reference Capacitor (0.1 µF Multilayer Ceramic). This external capacitor is used as a charge source for
the internal DAC. The capacitor should be tied between the pin and AGND.
Reference Capacitor (0.01 µF Ceramic Disc). This external capacitor is used in conjunction with the onchip reference. The capacitor should be tied between the pin and AGND.
Analog Inputs. Eight analog inputs that can be used as eight single-ended inputs (referenced to AGND)
or four pseudo-differential inputs. Channel configuration is selected by writing to the control register.
Both the positive and negative inputs cannot go below AGND or above AVDD at any time. Also the positive input cannot go below the negative input. See Table III for channel selection.
Calibration Input. This pin has an internal pull-up current source of 0.15 µA. A Logic 0 on this pin resets
all calibration control logic and initiates a calibration on its rising edge. There is the option of connecting
a 10 nF capacitor from this pin to DGND to allow for an automatic self-calibration on power-up. This
input overrides all other internal operations. If the autocalibration is not required, this pin should be tied
to a logic high.
Digital Supply Voltage, +3.0 V to +5.5 V.
Digital Ground. Ground reference point for digital circuitry.
Serial Data Output. The data output is supplied to this pin as a 16-bit serial word.
Serial Data Input. The data to be written is applied to this pin in serial form (16-bit word). This pin can
act as an input pin or as a I/O pin depending on the serial interface mode the part is in (see Table X).
Master clock signal for the device (4 MHz AD7858, 1.8 MHz AD7858L). Sets the conversion and calibration times.
Serial Port Clock. Logic Input. The user must provide a serial clock on this input.
Frame Sync. Logic Input. This pin is level triggered active low and frames the serial clock for the read
and write operations (see Table IX).
9–16 AIN1–AIN8
17
CAL
18
19
20
21
DVDD
DGND
DOUT
DIN
22
CLKIN
23
24
SCLK
SYNC
REV. B
–7–
AD7858/AD7858L
TERMINOLOGY1
Integral Nonlinearity
Total Harmonic Distortion
Total harmonic distortion (THD) is the ratio of the rms sum of
harmonics to the fundamental. For the AD7858/AD7858L, it is
defined as:
This is the maximum deviation from a straight line passing
through the endpoints of the ADC transfer function. The endpoints of the transfer function are zero scale, a point 1/2 LSB
below the first code transition, and full scale, a point 1/2 LSB
above the last code transition.
THD ( dB ) = 20 log
Differential Nonlinearity
2
2
2
2
2
(V2 + V3 + V4 + V5 + V6 )
V1
This is the difference between the measured and the ideal 1 LSB
change between any two adjacent codes in the ADC.
where V1 is the rms amplitude of the fundamental and V2, V3,
V4, V5, and V6 are the rms amplitudes of the second through the
sixth harmonics.
Total Unadjusted Error
Peak Harmonic or Spurious Noise
This is the deviation of the actual code from the ideal code taking all errors into account (Gain, Offset, Integral Nonlinearity, and
other errors) at any point along the transfer function.
Unipolar Offset Error
This is the deviation of the first code transition (00 . . . 000 to
00 . . . 001) from the ideal AIN(+) voltage (AIN(–) + 1/2 LSB).
Positive Full-Scale Error
This is the deviation of the last code transition from the ideal
AIN(+) voltage (AIN(–) + Full Scale – 1.5 LSB) after the offset
error has been adjusted out.
Peak harmonic or spurious noise is defined as the ratio of the
rms value of the next largest component in the ADC output
spectrum (up to fS/2 and excluding dc) to the rms value of the
fundamental. Normally, the value of this specification is determined by the largest harmonic in the spectrum, but for parts
where the harmonics are buried in the noise floor, it will be a
noise peak.
Intermodulation Distortion
With inputs consisting of sine waves at two frequencies, fa and
fb, any active device with nonlinearities will create distortion
products at sum and difference frequencies of mfa ± nfb where
m, n = 0, 1, 2, 3, etc. Intermodulation distortion terms are
those for which neither m nor n are equal to zero. For example,
the second order terms include (fa + fb) and (fa – fb), while the
third order terms include (2fa + fb), (2fa – fb), (fa + 2fb), and
(fa – 2fb).
Channel-to-Channel Isolation
Channel-to-channel isolation is a measure of crosstalk between
the channels. It is measured by applying a full-scale 25 kHz
signal to the other seven channels and determining how much
that signal is attenuated in the channel of interest. The figure
given is the worst case for all channels.
Track/Hold Acquisition Time
The track/hold amplifier returns into track mode and the end of
conversion. Track/hold acquisition time is the time required for
the output of the track/hold amplifier to reach its final value,
within ± 1/2 LSB, after the end of conversion.
Signal to (Noise + Distortion) Ratio
This is the measured ratio of signal to (noise + distortion) at the
output of the A/D converter. The signal is the rms amplitude of
the fundamental. Noise is the sum of all nonfundamental signals
up to half the sampling frequency (fS/2), excluding dc. The ratio
is dependent on the number of quantization levels in the digitization process; the more levels, the smaller the quantization noise.
The theoretical signal to (noise + distortion) ratio for an ideal
N-bit converter with a sine wave input is given by:
Testing is performed using the CCIF standard where two input
frequencies near the top end of the input bandwidth are used. In
this case, the second order terms are usually distanced in frequency from the original sine waves, while the third order terms
are usually at a frequency close to the input frequencies. As a
result, the second and third order terms are specified separately.
The calculation of the intermodulation distortion is as per the
THD specification where it is the ratio of the rms sum of the
individual distortion products to the rms amplitude of the sum
of the fundamentals expressed in dBs.
Signal to (Noise + Distortion) = (6.02 N +1.76) dB
Thus for a 12-bit converter, this is 74 dB.
1
AIN(+) refers to the positive input of the pseudo differential pair, and AIN(–)
refers to the negative analog input of the pseudo differential pair or to AGND
depending on the channel configuration.
–8–
REV. B
AD7858/AD7858L
ON-CHIP REGISTERS
The AD7858/AD7858L powers up with a set of default conditions. The only writing required is to select the channel configuration.
Without performing any other write operations the AD7858/AD7858L still retains the flexibility for performing a full power-down
and a full self-calibration.
Extra features and flexibility, such as performing different power-down options, different types of calibrations including system
calibration, and software conversion start, can be selected by further writing to the part.
The AD7858/AD7858L contains a Control Register, ADC Output Data Register, Status Register, Test Register, and
10 Calibration Registers. The control register is write-only, the ADC output data register and the status register are read-only, and
the test and calibration registers are both read/write registers. The Test Register is used for testing the part and should not be written to.
Addressing the On-Chip Registers
Writing
A write operation to the AD7858/AD7858L consists of 16 bits. The two MSBs, ADDR0 and ADDR1, are decoded to determine
which register is addressed, and the subsequent 14 bits of data are written to the addressed register. It is not until all 16 bits are
written that the data is latched into the addressed registers. Table I shows the decoding of the address bits while Figure 4 shows the
overall write register hierarchy.
Table I. Write Register Addressing
ADDR1
ADDR0
Comment
0
0
0
1
1
0
1
1
This combination does not address any register so the subsequent 14 data bits are ignored.
This combination addresses the TEST REGISTER. The subsequent 14 data bits are written to the test
register.
This combination addresses the CALIBRATION REGISTERS. The subsequent 14 data bits are written
to the selected calibration register.
This combination addresses the CONTROL REGISTER. The subsequent 14 data bits are written to the
control register.
Reading
To read from the various registers the user must first write to Bits 6 and 7 in the Control Register, RDSLT0 and RDSLT1. These
bits are decoded to determine which register is addressed during a read operation. Table II shows the decoding of the read address
bits while Figure 5 shows the overall read register hierarchy. The power-up status of these bits is 00 so that the default read will be
from the ADC output data register.
Once the read selection bits are set in the Control Register, all subsequent read operations that follow will be from the selected register until the read selection bits are changed in the Control Register.
Table II. Read Register Addressing
RDSLT1
RDSLT0 Comment
0
0
0
1
1
1
0
1
All successive read operations will be from ADC OUTPUT DATA REGISTER. This is the power-up
default setting. There will always be 4 leading zeros when reading from the ADC Output Data Register.
All successive read operations will be from TEST REGISTER.
All successive read operations will be from CALIBRATION REGISTERS.
All successive read operations will be from STATUS REGISTER.
RDSLT1, RDSLT0
DECODE
ADDR1, ADDR0
DECODE
01
10
TEST
REGISTER
CALSLT1, CALSLT0
DECODE
GAIN(1)
OFFSET(1)
DAC(8)
GAIN(1)
OFFSET(1)
00
01
00
11
CALIBRATION
REGISTERS
OFFSET(1)
10
ADC OUTPUT
DATA REGISTER
CONTROL
REGISTER
10
TEST
REGISTER
GAIN(1)
OFFSET(1)
DAC(8)
GAIN(1)
11
CALSLT1, CALSLT0
DECODE
Figure 4. Write Register Hierarchy/Address Decoding
REV. B
01
00
11
CALIBRATION
REGISTERS
GAIN(1)
OFFSET(1)
01
OFFSET(1)
10
STATUS
REGISTER
GAIN(1)
11
Figure 5. Read Register Hierarchy/Address Decoding
–9–
AD7858/AD7858L
CONTROL REGISTER
The arrangement of the Control Register is shown below. The control register is a write only register and contains 14 bits of data.
The control register is selected by putting two 1s in ADDR1 and ADDR0. The function of the bits in the control register are described below. The power-up status of all bits is 0.
MSB
SGL/DIFF
RDSLT0
CH2
CH1
CH0
PMGT1
PMGT0
RDSLT1
2/3 MODE
CONVST
CALMD
CALSLT1
CALSLT0
STCAL
LSB
CONTROL REGISTER BIT FUNCTION DESCRIPTION
Bit
Mnemonic
Comment
13
SGL/DIFF
12
11
10
9
8
7
6
5
CH2
CH1
CH0
PMGT1
PMGT0
RDSLT1
RDSLT0
2/3 MODE
A 0 in this bit position configures the input channels in pseudo-differential mode. A 1 in this bit position
configures the input channels in single-ended mode (see Table III).
These three bits are used to select the channel on which the conversion is performed. The channels can
be configured as eight single-ended channels or four pseudo-differential channels. The default selection
is AIN1 for the positive input and AIN2 for the negative input (see Table III for channel selection).
Power Management Bits. These two bits are used with the SLEEP pin for putting the part into various
Power-Down Modes (see Power-Down section for more details).
Theses two bits determine which register is addressed for the read operations (see Table II).
4
CONVST
3
2
1
0
CALMD
CALSLT1
CALSLT0
STCAL
Interface Mode Select Bit. With this bit set to 0, Interface Mode 2 is enabled. With this bit set to 1,
Interface Mode 1 is enabled where DIN is used as an output as well as an input. This bit is set to 0 by
default after every read cycle; thus when using the Two-Wire Interface Mode, this bit needs to be set to
1 in every write cycle.
Conversion Start Bit. A logic one in this bit position starts a single conversion, and this bit is automatically reset to 0 at the end of conversion. This bit may also be used in conjunction with system calibration
(see Calibration section.)
Calibration Mode Bit. A 0 here selects self-calibration, and a 1 selects a system calibration (see Table IV).
Calibration Selection Bits and Start Calibration Bit. These bits have two functions.
With the STCAL bit set to 1 the CALSLT1 and CALSLT0 bits determine the type of calibration per
formed by the part (see Table IV). The STCAL bit is automatically reset to 0 at the end of calibration.
With the STCAL bit set to 0 the CALSLT1 and CALSLT0 bits are decoded to address the calibration
register for read/write of calibration coefficients (see section on the Calibration Registers for more details).
–10–
REV. B
AD7858/AD7858L
Table III. Channel Selection
SGL/DIFF
CH2
CH1
CH0
AIN(+)*
AIN(–)*
0
0
0
0
0
0
0
0
0
0
1
1
0
1
0
1
AIN1
AIN3
AIN5
AIN7
AIN2
AIN4
AIN6
AIN8
0
0
0
0
1
1
1
1
0
0
1
1
0
1
0
1
AIN2
AIN4
AIN6
AIN8
AIN1
AIN3
AIN5
AIN7
1
1
1
1
0
0
0
0
0
0
1
1
0
1
0
1
AIN1
AIN3
AIN5
AIN7
AGND
AGND
AGND
AGND
1
1
1
1
1
1
1
1
0
0
1
1
0
1
0
1
AIN2
AIN4
AIN6
AIN8
AGND
AGND
AGND
AGND
*AIN(+) refers to the positive input seen by the AD7858/AD7858L sample and hold circuit,
*AIN(–) refers to the negative input seen by the AD7858/AD7858L sample and hold circuit.
Table IV. Calibration Selection
CALMD
CALSLT1
CALSLT0
Calibration Type
0
0
0
A Full Internal Calibration is initiated where the Internal DAC is calibrated
followed by the Internal Gain Error, and finally the Internal Offset Error is
calibrated out. This is the default setting.
0
0
1
Here the Internal Gain Error is calibrated out followed by the Internal Offset
Error calibrated out.
0
1
0
This calibrates out the Internal Offset Error only.
0
1
1
This calibrates out the Internal Gain Error only.
1
0
0
A Full System Calibration is initiated here where first the Internal DAC is
calibrated followed by the System Gain Error, and finally the System Offset
Error is calibrated out.
1
0
1
Here the System Gain Error is calibrated out followed by the System Offset
Error.
1
1
0
This calibrates out the System Offset Error only.
1
1
1
This calibrates out the System Gain Error only.
REV. B
–11–
AD7858/AD7858L
STATUS REGISTER
The arrangement of the Status Register is shown below. The status register is a read-only register and contains 16 bits of data. The
status register is selected by first writing to the control register and putting two 1s in RDSLT1 and RDSLT0. The function of the bits
in the status register are described below. The power-up status of all bits is 0.
START
WRITE TO CONTROL REGISTER
SETTING RDSLT0 = RDSLT1 = 1
READ STATUS REGISTER
Figure 6. Flowchart for Reading the Status Register
MSB
ZERO
BUSY
SGL/DIFF
CH2
RDSLT1
RDSLT0
2/3 MODE
X
CH1
CALMD
CH0
PMGT1
PMGT0
CALSLT1
CALSLT0
STCAL
LSB
STATUS REGISTER BIT FUNCTION DESCRIPTION
Bit
Mnemonic
Comment
15
ZERO
This bit is always 0.
14
BUSY
Conversion/Calibration Busy Bit. When this bit is 1, it indicates that there is a conversion
or calibration in progress. When this bit is 0, there is no conversion or calibration in progress.
13
12
11
10
SGL/DIFF
CH2
CH1
CH0
These four bits indicate the channel selected for conversion (see Table III).
9
8
PMGT1
PMGT0
Power management bits. These bits along with the SLEEP pin will indicate if the part is in a
power-down mode or not. See Table VI for description.
7
6
RDSLT1
RDSLT0
Both of these bits are always 1, indicating it is the status register being read (see Table II).
5
2/3 MODE
Interface Mode Select Bit. With this bit at 0, the device is in Interface Mode 2. With this bit at
1, the device is in Interface Mode 1. This bit is reset to 0 after every read cycle.
4
X
Don’t care bit.
3
CALMD
Calibration Mode Bit. A 0 in this bit indicates a self-calibration is selected, and a 1 in this bit
indicates a system calibration is selected (see Table IV).
2
1
0
CALSLT1
CALSLT0
STCAL
Calibration Selection Bits and Start Calibration Bit. The STCAL bit is read as a 1 if a
calibration is in progress and as a 0 if there is no calibration in progress. The CALSLT1 and
CALSLT0 bits indicate which of the calibration registers are addressed for reading and writing
(see section on the Calibration Registers for more details).
–12–
REV. B
AD7858/AD7858L
CALIBRATION REGISTERS
The AD7858/AD7858L has 10 calibration registers in all, eight for the DAC, one for the offset, and one for gain. Data can be written
to or read from all 10 calibration registers. In self- and system calibration the part automatically modifies the calibration registers; only if the
user needs to modify the calibration registers should an attempt be made to read from and write to the calibration registers.
Addressing the Calibration Registers
The calibration selection bits in the control register CALSLT1 and CALSLT0 determine which of the calibration registers are addressed (see Table V). The addressing applies to both the read and write operations for the calibration registers. The user should not
attempt to read from and write to the calibration registers at the same time.
Table V. Calibration Register Addressing
CALSLT1
CALSLT0
Comment
0
0
1
1
0
1
0
1
This combination addresses the Gain (1), Offset (1) and DAC Registers (8). Ten registers in total.
This combination addresses the Gain (1) and Offset (1) Registers. Two registers in total.
This combination addresses the Offset Register. One register in total.
This combination addresses the Gain Register. One register in total.
Writing to/Reading from the Calibration Registers
For writing to the calibration registers a write to the control
register is required to set the CALSLT0 and CALSLT1 bits.
For reading from the calibration registers a write to the control
register is required to set the CALSLT0 and CALSLT1 bits,
but also to set the RDSLT1 and RDSLT0 bits to 10 (this addresses the calibration registers for reading). The calibration
register pointer is reset on writing to the control register setting
the CALSLT1 and CALSLT0 bits, or upon completion of all
the calibration register write/read operations. When reset it
points to the first calibration register in the selected write/read
sequence. The calibration register pointer will point to the gain
calibration register upon reset in all but one case, this case being
where the offset calibration register is selected on its own
(CALSLT1 = 1, CALSLT0 = 0). Where more than one calibration register is being accessed the calibration register pointer will
be automatically incremented after each calibration register
write/read operation. The order in which the 10 calibration
registers are arranged is shown in Figure 7. The user may abort
at any time before all the calibration register write/read operations are completed, and the next control register write operation will reset the calibration register pointer. The flow chart in
Figure 8 shows the sequence for writing to the calibration registers and Figure 9 for reading.
When reading from the calibration registers there will always be
two leading zeros for each of the registers. When operating in
Serial Interface Mode 1 the read operations to the calibration
registers cannot be aborted. The full number of read operations
must be completed (see section on Serial Interface Mode 1
Timing for more detail).
CALIBRATION REGISTERS
CAL REGISTER
ADDRESS POINTER
CALIBRATION REGISTER
ADDRESS POINTER
POSITION IS DETERMINED
BY THE NUMBER OF
CALIBRATION REGISTERS
ADDRESSED AND THE
NUMBER OF READ/WRITE
OPERATIONS
GAIN REGISTER
(1)
OFFSET REGISTER
(2)
DAC 1ST MSB REGISTER
(3)
.
.
.
.
.
.
.
.
.
.
.
.
.
.
CAL REGISTER POINTER IS
AUTOMATICALLY RESET
WRITE TO CAL REGISTER
(ADDR1 = 1, ADDR0 = 0)
CAL REGISTER POINTER IS
AUTOMATICALLY INCREMENTED
LAST
REGISTER
WRITE
OPERATION
OR
ABORT
?
NO
FINISHED
Figure 8. Flowchart for Writing to the Calibration Registers
(10)
Figure 7. Calibration Register Arrangements
REV. B
WRITE TO CONTROL REGISTER SETTING STCAL = 0
AND CALSLT1, CALSLT0 = 00, 01, 10, 11
YES
.
.
.
.
.
.
.
DAC 8TH MSB REGISTER
START
–13–
AD7858/AD7858L
Q. If a +20 mV offset is present in the analog input signal and the
reference voltage is 2.5 V what code needs to be written to the
offset register to compensate for the offset?
START
WRITE TO CONTROL REGISTER SETTING STCAL = 0, RDSLT1 = 1,
RDSLT0 = 0, AND CALSLT1, CALSLT0 = 00, 01, 10, 11
A. 2.5 V reference implies that the resolution in the offset register is 5% × 2.5 V/213 = 0.015 mV. +20 mV/0.015 mV =
1310.72; rounding to the nearest number gives 1311. In
binary terms this is 0101 0001 1111. Therefore, decrease the
offset register by 0101 0001 1111.
CAL REGISTER POINTER IS
AUTOMATICALLY RESET
This method of compensating for offset in the analog input
signal allows for fine tuning the offset compensation. If the
offset on the analog input signal is known, there will be no need
to apply the offset voltage to the analog input pins and do a
system calibration. The offset compensation can take place in
software.
READ CAL REGISTER
CAL REGISTER POINTER IS
AUTOMATICALLY INCREMENTED
LAST
REGISTER
READ
OPERATION
OR
ABORT
?
Adjusting the Gain Calibration Register
The gain calibration register contains 16 bits, two leading 0s
and 14 data bits. The data bits are binary weighted as in the
offset calibration register. The gain register value is effectively
multiplied by the analog input to scale the conversion result
over the full range. Increasing the gain register compensates for
a smaller analog input range and decreasing the gain register
compensates for a larger input range. The maximum analog
input range that the gain register can compensate for is 1.025
times the reference voltage, and the minimum input range is
0.975 times the reference voltage.
NO
YES
FINISHED
Figure 9. Flowchart for Reading from the Calibration
Registers
Adjusting the Offset Calibration Register
The offset calibration register contains 16 bits, two leading zeros,
and 14 data bits. By changing the contents of the offset register
different amounts of offset on the analog input signal can be
compensated for. Increasing the number in the offset calibration
register compensates for negative offset on the analog input
signal, and decreasing the number in the offset calibration register compensates for positive offset on the analog input signal.
The default value of the offset calibration register is 0010 0000
0000 0000 approximately. This is not an exact value, but the
value in the offset register should be close to this value. Each of
the 14 data bits in the offset register is binary weighted; the
MSB has a weighting of 5% of the reference voltage, the MSB-1
has a weighting of 2.5%, the MSB-2 has a weighting of 1.25%,
and so on down to the LSB which has a weighting of 0.0006%.
This gives a resolution of ± 0.0006% of VREF approximately.
More accurately the resolution is ± (0.05 × VREF )/213 volts =
± 0.015 mV, with a 2.5 V reference. The maximum offset that
can be compensated for is ± 5% of the reference voltage, which
equates to ± 125 mV with a 2.5 V reference and ± 250 mV with
a 5 V reference.
–14–
REV. B
AD7858/AD7858L
CIRCUIT INFORMATION
The AD7858/AD7858L is a fast, 12-bit single supply A/D converter. The part requires an external 4 MHz/1.8 MHz master
clock (CLKIN), two CREF capacitors, a CONVST signal to start
conversion, and power supply decoupling capacitors. The part
provides the user with track/hold, on-chip reference, calibration
features, A/D converter, and serial interface logic functions on a
single chip. The A/D converter section of the AD7858/AD7858L
consists of a conventional successive-approximation converter
based around a capacitor DAC. The AD7858/AD7858L accepts
an analog input range of 0 to +VDD where the reference can be
tied to VDD. The reference input to the part is buffered on-chip.
A major advantage of the AD7858/AD7858L is that a conversion
can be initiated in software as well as applying a signal to the
CONVST pin. Another innovative feature of the AD7858/
AD7858L is self-calibration on power-up, which is initiated
having a capacitor from the CAL pin to AGND, to give superior
dc accuracy. See Automatic Calibration on Power-Up section.
The part is available in a 24-pin SSOP package and this offers
the user considerable space-saving advantages over alternative
solutions. The AD7858L version typically consumes only
5.5 mW making it ideal for battery-powered applications.
CONVERTER DETAILS
The master clock for the part must be applied to the CLKIN
pin. Conversion is initiated on the AD7858/AD7858L by pulsing
the CONVST input or by writing to the control register and
setting the CONVST bit to 1. On the rising edge of CONVST
(or at the end of the control register write operation), the onchip track/hold goes from track to hold mode. The falling edge
of the CLKIN signal that follows the rising edge of the CONVST
signal initiates the conversion, provided the rising edge of
CONVST occurs at least 10 ns typically before this CLKIN
edge. The conversion cycle will take 16.5 CLKIN periods from
this CLKIN falling edge. If the 10 ns setup time is not met, the
conversion will take 17.5 CLKIN periods. The maximum specified conversion time is 4.6 µs for the AD7858 (18tCLKIN,
CLKIN = 4 MHz) and 10 µs for the AD7858L (18tCLKIN,
CLKIN = 1.8 MHz). When a conversion is completed, the
BUSY output goes low, and then the result of the conversion
can be read by accessing the data through the serial interface.
To obtain optimum performance from the part, the read operation should not occur during the conversion or 400 ns prior to
the next CONVST rising edge. However, the maximum
throughput rates are achieved by reading/writing during conversion, and reading/writing during conversion is likely to degrade
the Signal to (Noise + Distortion) by only 0.5 dBs. The AD7858
can operate at throughput rates up to 200 kHz, 100 kHz for the
AD7858L. For the AD7858 a conversion takes 18 CLKIN
periods; 2 CLKIN periods are needed for the acquisition time
giving a full cycle time of 5 µs (= 200 kHz, CLKIN = 4 MHz).
For the AD7858L 100 kHz throughput can be obtained as
follows: the CLKIN and CONVST signals are arranged to give
a conversion time of 16.5 CLKIN periods as described above,
1.5 CLKIN periods are allowed for the acquisition time. This
gives a full cycle time of 10 µs (=100 kHz, CLKIN = 1.8 MHz).
When using the software conversion start for maximum throughput the user must ensure the control register write operation
extends beyond the falling edge of BUSY. The falling edge of
BUSY resets the CONVST bit to 0 and allows it to be reprogrammed to 1 to start the next conversion.
TYPICAL CONNECTION DIAGRAM
Figure 10 shows a typical connection diagram for the AD7858/
AD7858L. The AGND and the DGND pins are connected
together at the device for good noise suppression. The CAL pin
has a 0.01 µF capacitor to enable an automatic self-calibration
on power-up. The conversion result is output in a 16-bit word
with four leading zeros followed by the MSB of the 12-bit result.
Note that after the AVDD and DVDD power-up the part will
4MHz/1.8MHz OSCILLATOR
200kHz/100kHz PULSE GENERATOR
ANALOG SUPPLY
+3V TO +5V
10␮F
MASTER CLOCK
INPUT
0.1␮F
0.1␮F
CONVERSION
START INPUT
AVDD DVDD
0V TO 2.5V
INPUT
0.1␮F
0.01␮F
DVDD
0.01␮F
AIN(–)
SCLK
CREF1
CREF2
OSCILLOSCOPE
CLKIN
AIN(+)
CH1
SERIAL CLOCK
INPUT
CONVST
AD7858/
AD7858L
SLEEP
CH2
SYNC
CH3
FRAME SYNC INPUT
DIN
CH5
DOUT
AGND
AUTO CAL ON
POWER-UP
CH4
SERIAL DATA INPUT
CAL
SERIAL DATA
OUTPUT
DGND
0.1␮F
INTERNAL/
EXTERNAL
REFERENCE
OPTIONAL
AD780/
EXTERNAL
REF-192
REFERENCE
DATA GENERATOR
PULSE GENERATOR
Figure 10. Typical Circuit
REV. B
–15–
4 LEADING
ZEROS FOR
ADC DATA
AD7858/AD7858L
For applications where power consumption is a major concern
then the SLEEP pin can be connected to DGND. See PowerDown section for more detail on low power applications.
ANALOG INPUT
The equivalent circuit of the analog input section is shown in
Figure 11. During the acquisition interval the switches are both
in the track position and the AIN(+) charges the 20 pF capacitor
through the 125 Ω resistance. On the rising edge of CONVST
switches SW1 and SW2 go into the hold position retaining
charge on the 20 pF capacitor as a sample of the signal on
AIN(+). The AIN(–) is connected to the 20 pF capacitor, and
this unbalances the voltage at node A at the input of the comparator. The capacitor DAC adjusts during the remainder of the
conversion cycle to restore the voltage at node A to the correct
value. This action transfers a charge, representing the analog
input signal, to the capacitor DAC which in turn forms a digital
representation of the analog input signal. The voltage on the
AIN(–) pin directly influences the charge transferred to the
capacitor DAC at the hold instant. If this voltage changes during the conversion period, the DAC representation of the analog
input voltage will be altered. Therefore it is most important that
the voltage on the AIN(–) pin remains constant during the conversion period. Furthermore it is recommended that the AIN(–)
pin is always connected to AGND or to a fixed dc voltage.
For ac applications, removing high frequency components from
the analog input signal is recommended by use of an RC lowpass filter on the AIN(+) pin as shown in Figure 13. In applications where harmonic distortion and signal to noise ratio are
critical the analog input should be driven from a low impedance
source. Large source impedances will significantly affect the ac
performance of the ADC. This may necessitate the use of an
input buffer amplifier. The choice of the op amp will be a function of the particular application.
When no amplifier is used to drive the analog input the source
impedance should be limited to low values. The maximum
source impedance will depend on the amount of total harmonic
distortion (THD) that can be tolerated. The THD will increase
as the source impedance increases and performance will degrade. Figure 12 shows a graph of the total harmonic distortion
versus analog input signal frequency for different source impedances. With the setup as in Figure 13, the THD is at the –90 dB
level. With a source impedance of 1 kΩ and no capacitor on the
AIN(+) pin, the THD increases with frequency.
–72
THD vs. FREQUENCY FOR DIFFERENT
SOURCE IMPEDANCES
–76
RIN = 1k⍀
THD – dB
require approximately 150 ms for the internal reference to settle
and for the automatic calibration on power-up to be completed.
Acquisition Time
The track and hold amplifier enters its tracking mode on the
falling edge of the BUSY signal. The time required for the track
and hold amplifier to acquire an input signal will depend on
how quickly the 20 pF input capacitance is charged. The acquisition time is calculated using the formula:
–80
–84
RIN = 50⍀, 10nF
AS IN FIGURE 13
–88
–92
0
tACQ = 9 × (RIN + 125 Ω) × 20 pF
where RIN is the source impedance of the input signal, and
125 Ω, 20 pF is the input R, C.
125⍀
TRACK
AIN(+)
AIN(–)
125⍀
SW1
HOLD
CAPACITOR
DAC
20pF
NODE A
SW2
TRACK
HOLD
COMPARATOR
CREF2
Figure 11. Analog Input Equivalent Circuit
DC/AC Applications
20
40
60
INPUT FREQUENCY – kHz
80
100
Figure 12. THD vs. Analog Input Frequency
In a single supply application (both 3 V and 5 V), the V+ and
V– of the op amp can be taken directly from the supplies to the
AD7858/AD7858L which eliminates the need for extra external
power supplies. When operating with rail-to-rail inputs and
outputs, at frequencies greater than 10 kHz care must be taken
in selecting the particular op amp for the application. In particular for single supply applications the input amplifiers should be
connected in a gain of –1 arrangement to get the optimum performance. Figure 13 shows the arrangement for a single supply
application with a 50 Ω and 10 nF low-pass filter (cutoff frequency 320 kHz) on the AIN(+) pin. Note that the 10 nF is a
capacitor with good linearity to ensure good ac performance.
Recommended single supply op amps are the AD820 and the
AD820-3 V.
For dc applications high source impedances are acceptable
provided there is enough acquisition time between conversions
to charge the 20 pF capacitor. The acquisition time can be
calculated from the above formula for different source impedances. For example with RIN = 5 kΩ, the required acquisition
time will be 922 ns.
+3V TO +5V
10k⍀
VIN
(0 TO VREF)
10k⍀
V+
10␮F
0.1␮F
50⍀
10k⍀
VREF
10k⍀
V+ AD820
AD820-3V
10nF
(NPO)
TO AIN(+) OF
AD7858/AD7858L
Figure 13. Analog Input Buffering
–16–
REV. B
AD7858/AD7858L
Input Range
REFERENCE SECTION
The analog input range for the AD7858/AD7858L is 0 V to
VREF. The AIN(–) pin on the AD7858/AD7858L can be biased
up above AGND, if required. The advantage of biasing the
lower end of the analog input range away from AGND is that
the user does not need to have the analog input swing all the
way down to AGND. This has the advantage in true singlesupply applications that the input amplifier does not need to
swing all the way down to AGND. The upper end of the analog
input range is shifted up by the same amount. Care must be
taken so that the bias applied does not shift the upper end of the
analog input above the AVDD supply. In the case where the
reference is the supply, AVDD, the AIN(–) must be tied to
AGND.
For specified performance, it is recommended that when using
an external reference this reference should be between 2.3 V
and the analog supply AVDD. The connections for the relevant
reference pins are shown in the typical connection diagrams. If
the internal reference is being used, the REFIN/REFOUT pin
should have a 100 nF capacitor connected to AGND very close
to the REFIN/REFOUT pin. These connections are shown in
Figure 16.
AIN(+)
VIN = 0 TO VREF
TRACK AND HOLD
AMPLIFIER
DOUT
AIN(–)
If the internal reference is required for use external to the ADC,
it should be buffered at the REFIN/REFOUT pin and a 100 nF
connected from this pin to AGND. The typical noise performance
for the internal reference, with 5 V supplies, is 150 nV/√Hz @
1 kHz and dc noise is 100 µV p-p.
ANALOG SUPPLY
+3V TO +5V
STRAIGHT
BINARY
FORMAT
10␮F
0.1␮F
0.1␮F
AVDD
DVDD
CREF1
AD7858/
AD7858L
0.1␮F
CREF2
Figure 14. 0 to VREF Input Configuration
AD7858/
AD7858L
0.01␮F
Transfer Function
For the AD7858/AD7858L input range the designed code transitions occur midway between successive integer LSB values
(i.e., 1/2 LSB, 3/2 LSBs, 5/2 LSBs . . . FS – 3/2 LSBs). The
output coding is straight binary with 1 LSB = FS/4096 = 3.3 V/
4096 = 0.8 mV when VREF = 3.3 V. The ideal input/output
transfer characteristic is shown in Figure 15.
OUTPUT
CODE
111...111
111...110
111...101
111...100
000...011
1LSB = FS
4096
000...010
REFIN/REFOUT
0.1␮F
Figure 16. Relevant Connections When Using Internal
Reference
The other option is that the REFIN/REFOUT pin be overdriven
by connecting it to an external reference. This is possible due to
the series resistance from the REFIN/REFOUT pin to the internal
reference. This external reference can have a range that includes
AVDD. When using AVDD as the reference source, the 100 nF
capacitor from the REFIN/REFOUT pin to AGND should be as
close as possible to the REFIN/REFOUT pin, and also the CREF1
pin should be connected to AVDD to keep this pin at the same
level as the reference. The connections for this arrangement are
shown in Figure 17. When using AVDD it may be necessary to
add a resistor in series with the AVDD supply. This will have the
effect of filtering the noise associated with the AVDD supply.
000...001
ANALOG SUPPLY
+3V TO +5V
000...000
0V 1LSB
10␮F
0.1␮F
0.1␮F
+FS –1LSB
VIN = (AIN(+) – AIN(–)), INPUT VOLTAGE
AVDD
Figure 15. AD7858/AD7858L Transfer Characteristic
DVDD
CREF1
0.1␮F
CREF2
AD7858/
AD7858L
0.01␮F
REFIN/REFOUT
0.1␮F
Figure 17. Relevant Connections When Using AVDD as the
Reference
REV. B
–17–
AD7858/AD7858L
PERFORMANCE CURVES
–78
AVDD = DVDD = 3.3V/5.0V,
Figure 18 shows a typical FFT plot for the AD7858 at 200 kHz
sample rate and 10 kHz input frequency.
100mVp-p SINE WAVE ON AVDD
–80
0
–82
–20
PSRR – dB
AVDD = DVDD = 3.3V
fSAMPLE = 200kHz
fIN = 10kHz
SNR = 72.04dB
THD = –88.43dB
3.3V
–84
–40
SNR – dB
–86
5.0V
–60
–88
–80
–90
0
–100
20
40
60
INPUT FREQUENCY – kHz
80
100
Figure 20. PSRR vs. Frequency
–120
0
20
40
60
FREQUENCY – kHz
80
100
Figure 18. FFT Plot
Figure 19 shows the SNR vs. Frequency for different supplies
and different external references.
74
AVDD = DVDD WITH 2.5V REFERENCE
UNLESS STATED OTHERWISE
S(N+D) RATIO – dB
73
5.0V SUPPLIES, WITH 5V REFERENCE
72
5.0V SUPPLIES
5.0V SUPPLIES, L VERSION
71
3.3V SUPPLIES
70
69
0
20
40
60
INPUT FREQUENCY – kHz
80
100
Figure 19. SNR vs. Frequency
Figure 20 shows the Power Supply Rejection Ratio vs. Frequency for the part. The Power Supply Rejection Ratio is defined as the ratio of the power in adc output at frequency f to
the power of a full-scale sine wave.
PSRR (dB) = 10 log (Pf/Pfs)
Pf = Power at frequency f in adc output, Pfs = power of a
full-scale sine wave. Here a 100 mV peak-to-peak sine wave is
coupled onto the AVDD supply while the digital supply is left
unaltered. Both the 3.3 V and 5.0 V supply performances are
shown.
POWER-DOWN OPTIONS
The AD7858 provides flexible power management to allow the
user to achieve the best power performance for a given throughput rate. The power management options are selected by
programming the power management bits, PMGT1 and PMGT0,
in the control register and by use of the SLEEP pin. Table VI
summarizes the power-down options that are available and how
they can be selected by using either software, hardware, or a
combination of both. The AD7858 can be fully or partially
powered down. When fully powered down, all the on-chip circuitry is powered down and IDD is 1 µA typ. If a partial powerdown is selected, then all the on-chip circuitry except the reference
is powered down and IDD is 400 µA typ. The choice of full or partial power-down does not give any significant improvement in
throughput with a power-down between conversions. This is
discussed in the next section–Power-Up Times. However, a
partial power-down does allow the on-chip reference to be used
externally even though the rest of the AD7858 circuitry is powered down. It also allows the AD7858 to be powered up faster
after a long power-down period when using the on-chip reference (See Power-Up Times–Using On-Chip Reference).
When using the SLEEP pin, the power management bits PMGT1
and PMGT0 should be set to zero (default status on power-up).
Bringing the SLEEP pin logic high ensures normal operation,
and the part does not power down at any stage. This may be
necessary if the part is being used at high throughput rates when
it is not possible to power down between conversions. If the user
wishes to power down between conversions at lower throughput
rates (i.e. <100 kSPS for the AD7858) to achieve better power
performances, then the SLEEP pin should be tied logic low.
If the power-down options are to be selected in software only,
then the SLEEP pin should be tied logic high. By setting the
power management bits PMGT1 and PMGT0 as shown in
Table VI, a Full Power-Down, Full Power-Up, Full PowerDown Between Conversions, and a Partial Power-Down Between Conversions can be selected.
–18–
REV. B
AD7858/AD7858L
Table VI. Power Management Options
PMGT1 PMGT0 SLEEP
Bit
Bit
Pin
0
0
Comment
0
0
0
0
1
1
X
1
1
0
1
X
X
Full Power-Down if Not
Calibrating or Converting
(Default Condition
After Power-On)
Normal Operation
Normal Operation
(Independent of the SLEEP Pin)
Full Power-Down
Partial Power-Down if Not
Converting
A typical connection diagram for a low power application is
shown in Figure 21 (AD7858L is the low power version of the
AD7858).
ANALOG
SUPPLY
+3V
CURRENT,
I = 1.5mA
TYP
10␮F
0.1␮F
0.1␮F
AVDD DVDD
0V TO 2.5V
INPUT
AIN(+)
CLKIN
AD7858/
AD7858L
CREF1
CONVST
0.01␮F
CREF2
SCLK
AUTO POWER
DOWN AFTER
CONVERSION
0.01␮F
AUTO CAL
ON
POWER-UP
MASTER
CLOCK
INPUT
SLEEP
100kHz
PULSE
GENERATOR
START CONVERSION ON RISING EDGE
5␮s
CONVERSION
START INPUT
CONVST
tCONVERT
SERIAL CLOCK
INPUT
BUSY
CAL
DOUT
AGND
DIN
SERIAL DATA
OUTPUT
LOW
POWER
␮C/␮P
SERIAL DATA
INPUT
REFIN /REFOUT
INTERNAL
REFERENCE
0.1␮F
REF192
POWER-UP
NORMAL
FULL
TIME
OPERATION POWER-DOWN
SYNC
DGND
OPTIONAL
EXTERNAL
REFERENCE
Figure 21. Typical Low Power Circuit
POWER-UP TIMES
Using an External Reference
When the AD7858 is powered up, the part is powered up from
one of two conditions. First, when the power supplies are initially powered up and, secondly, when the part is powered up
from either a hardware or software power-down (see last section).
When AVDD and DVDD are powered up, the AD7858 should be
left idle for approximately 32 ms (4 MHz CLK) to allow for the
autocalibration if a 10 nF cap is placed on the CAL pin, (see
Calibration section). During power-up the functionality of the
SLEEP pin is disabled, i.e., the part will not power down until
the end of the calibration if SLEEP is tied logic low. The autocalibration on power-up can be disabled if the CAL pin is tied to
REV. B
The AD7858 powers up from a full hardware or software
power-down in 5 µs typ. This limits the throughput which the
part is capable of to 104 kSPS for the AD7858 operating with a
4 MHz CLK and 66 kSPS for the AD7858L with a 1.8 MHz
CLK when powering down between conversions. Figure 22
shows how power-down between conversions is implemented
using the CONVST pin. The user first selects the power-down
between conversions option by using the SLEEP pin and the
power management bits, PMGT1 and PMGT0, in the control
register, (see last section). In this mode the AD7858 automatically enters a full power-down at the end of a conversion, i.e.,
when BUSY goes low. The falling edge of the next CONVST
pulse causes the part to power up. Assuming the external reference is left powered up, the AD7858 should be ready for normal
operation 5 µs after this falling edge. The rising edge of CONVST
initiates a conversion so the CONVST pulse should be at least
5 µs wide. The part automatically powers down on completion
of the conversion.
POWER-UP ON FALLING EDGE
AIN(–)
0.1␮F
1.8MHz
OSCILLATOR
a logic high. If the autocalibration is disabled, then the user must
take into account the time required by the AD7858 to power-up
before a self-calibration is carried out. This power-up time is the
time taken for the AD7858 to power up when power is first
applied (300 µs) typ) or the time it takes the external reference
to settle to the 12-bit level–whichever is the longer.
POWER-UP
TIME
Figure 22. Power-Up Timing When Using CONVST Pin
NOTE: Where the software CONVST is used or automatic full
power-down, the part must be powered up in software with an
extra write setting PMGT1 = 0 and PMGT0 = 1 before a conversion is initiated in the next write. Automatic partial powerdown after a calibration is not possible; the part must be
powered down manually. If software calibrations are to be used
when operating in the partial power-down mode, then three
separate writes are required. The first initiates the type of calibration required, the second write powers the part down into
partial power-down mode, while the third write powers the part
up again before the next calibration command is issued.
Using the Internal (On-Chip) Reference
As in the case of an external reference, the AD7858 can powerup from one of two conditions, power-up after the supplies are
connected or power-up from hardware/software power-down.
When using the on-chip reference and powering up when AVDD
and DVDD are first connected, it is recommended that the powerup calibration mode be disabled as explained above. When using
the on-chip reference, the power-up time is effectively the time
it takes to charge up the external capacitor on the REFIN/REFOUT
pin. This time is given by the equation:
tUP = 9 × R × C
where R ≅ 150 kΩ and C = external capacitor.
–19–
AD7858/AD7858L
The recommended value of the external capacitor is 100 nF;
this gives a power-up time of approximately 135 ms before a
calibration is initiated and normal operation should commence.
10
SWITCH OPENS
DURING POWER-DOWN
REFIN/REFOUT
AD7858
ON-CHIP
REFERENCE
EXTERNAL
CAPACITOR
BUF
TO OTHER
CIRCUITRY
Figure 23. On-Chip Reference During Power-Down
POWER VS. THROUGHPUT RATE
The main advantage of a full power-down after a conversion is
that it significantly reduces the power consumption of the part
at lower throughput rates. When using this mode of operation,
the AD7858 is only powered up for the duration of the conversion. If the power-up time of the AD7858 is taken to be 5 µs
and it is assumed that the current during power-up is 4 mA typ,
then power consumption as a function of throughput can easily
be calculated. The AD7858 has a conversion time of 4.6 µs
with a 4 MHz external clock. This means the AD7858 consumes 4 mA typ, (or 12 mW typ VDD = 3 V) for 9.6 µs in every
conversion cycle if the device is powered down at the end of a
conversion. If the throughput rate is 1 kSPS, the cycle time is
1000 µs and the average power dissipated during each cycle is
(9.6/1000) × (12 mW) = 115 µW. The graph, Figure 24, shows
the power consumption of the AD7858 as a function of throughput. Table VII lists the power consumption for various throughput rates.
POWER – mW
AD7858 (4MHz CLK)
When CREF is fully charged, the power-up time from a hardware
or software power-down reduces to 5 µs. This is because an
internal switch opens to provide a high impedance discharge
path for the reference capacitor during power-down—see Figure
23. An added advantage of the low charge leakage from the
reference capacitor during power-down is that even though the
reference is being powered down between conversions, the
reference capacitor holds the reference voltage to within
0.5 LSBs with throughput rates of 100 samples/second and
over with a full power-down between conversions. A high input
impedance op amp like the AD707 should be used to buffer this
reference capacitor if it is being used externally. Note, if the
AD7858 is left in its power-down state for more than 100 ms,
the charge on CREF will start to leak away and the power-up
time will increase. If this long power-up time is a problem, the
user can use a partial power-down for the last conversion so the
reference remains powered up.
Power
1 kSPS
10 kSPS
115 µW
1.15 mW
AD7858L (1.8MHz CLK)
0.1
0.01
0
5
10
15
25
35
20
30
THROUGHPUT – kSPS
40
45
50
Figure 24. Power vs. Throughput Rate
CALIBRATION SECTION
Calibration Overview
The automatic calibration that is performed on power-up ensures that the calibration options covered in this section will not
be required in a significant amount of applications. The user
will not have to initiate a calibration unless the operating conditions change (CLKIN frequency, analog input mode, reference
voltage, temperature, and supply voltages). The AD7858/
AD7858L have a number of calibration features that may be
required in some applications and there are a number of advantages in performing these different types of calibration. First,
the internal errors in the ADC can be reduced significantly to
give superior dc performance, and secondly, system offset and
gain errors can be removed. This allows the user to remove
reference errors (whether it be internal or external reference)
and to make use of the full dynamic range of the AD7858/
AD7858L by adjusting the analog input range of the part for a
specific system.
There are two main calibration modes on the AD7858/AD7858L,
self-calibration and system calibration. There are various options in both self-calibration and system calibration as outlined
previously in Table IV. All the calibration functions can be
initiated by pulsing the CAL pin or by writing to the control
register and setting the STCAL bit to one. The timing diagrams
that follow involve using the CAL pin.
The duration of each of the different types of calibrations is
given in Table VIII for the AD7858 with a 4 MHz master clock.
These calibration times are master clock dependent. Therefore,
the calibrating times for the AD7858L (CLKIN = 1.8 MHz)
will be longer than those quoted in Table VIII.
Table VII. Power Consumption vs. Throughput
Throughput Rate
1
–20–
Table VIII. Calibration Times (AD7858 with 4 MHz CLKIN)
Type of Self- or
System Calibration
Time
Full
Offset + Gain
Offset
Gain
31.25 ms
6.94 ms
3.47 ms
3.47 ms
REV. B
AD7858/AD7858L
Automatic Calibration on Power-On
The CAL pin has a 0.15 µA pull-up current source connected
to it internally to allow for an automatic full self-calibration on
power-on. A full self-calibration will be initiated on power-on if
a capacitor is connected from the CAL pin to DGND. The
internal current source connected to the CAL pin charges up
the external capacitor and the time required to charge the external capacitor will depend on the size of the capacitor itself. This
time should be large enough to ensure that the internal reference is settled before the calibration is performed. A 33 nF
capacitor is sufficient to ensure that the internal reference has
settled (see Power-Up Times) before a calibration is initiated
taking into account trigger level and current source variations
on the CAL pin. However, if an external reference is being
used, this reference must have stabilized before the automatic
calibration is initiated (a larger capacitor on the CAL pin
should be used if the external reference has not settled when the
autocalibration is initiated). Once the capacitor on the CAL pin
has charged, the calibration will be performed which will take
32 ms (4 MHz CLKIN). Therefore the autocalibration should
be complete before operating the part. After calibration, the
part is accurate to the 12-bit level and the specifications quoted
on the data sheet apply. There will be no need to perform
another calibration unless the operating conditions change or
unless a system calibration is required.
Self-Calibration Description
There are four different calibration options within the selfcalibration mode. First, there is a full self-calibration where the
DAC, internal gain, and internal offset errors are calibrated out.
Then, there is the (Gain + Offset) self-calibration which calibrates out the internal gain error and then the internal offset
errors. The internal DAC is not calibrated here. Finally, there
are the self-offset and self-gain calibrations which calibrate out
the internal offset errors and the internal gain errors respectively.
The internal capacitor DAC is calibrated by trimming each of
the capacitors in the DAC. It is the ratio of these capacitors to
each other that is critical, and so the calibration algorithm ensures that this ratio is at a specific value by the end of the calibration routine. For the offset and gain there are two separate
capacitors, one of which is trimmed when an offset or gain
calibration is performed. Again, it is the ratio of these capacitors
to the capacitors in the DAC that is critical and the calibration
algorithm ensures that this ratio is at a specified value for both
the offset and gain calibrations.
For the self- (gain + offset), self-offset, and self-gain calibrations
the BUSY line will be triggered high by the rising edge of the
CAL signal (or the end of the write to the control register if
calibration is initiated in software) and will stay high for the
full duration of the self-calibration. The length of time that
the BUSY is high will depend on the type of self-calibration
that is initiated. Typical figures are given in Table VIII. The
timing diagrams for the other self-calibration options will be
similar to that outlined in Figure 25.
t1 = 100ns MIN,
t15 = 2.5 tCLKIN MAX,
tCAL = 125013 tCLKIN
t1
CAL (I/P)
t15
BUSY (O/P)
tCAL
Figure 25. Timing Diagram for Full Self-Calibration
System Calibration Description
System calibration allows the user to take out system errors
external to the AD7858/AD7858L as well as calibrate the errors
of the AD7858/AD7858L itself. The maximum calibration
range for the system offset errors is ± 5% of VREF and for the
system gain errors is ± 2.5% of VREF. This means that the maximum allowable system offset voltage applied between the
AIN(+) and AIN(–) pins for the calibration to adjust out this
error is ± 0.05 × VREF (i.e., the AIN(+) can be 0.05 × VREF above
AIN(–) or 0.05 × VREF below AIN(–)). For the System gain error
the maximum allowable system full-scale voltage that can be
applied between AIN(+) and AIN(–) for the calibration to
adjust out this error is VREF ± 0.025 × VREF ( i.e., the AIN(+)
above AIN(–)). If the system offset or system gain errors are
outside the ranges mentioned the system calibration algorithm
will reduce the errors as much as the trim range allows.
Figures 26 through 28 illustrate why a specific type of system
calibration might be used. Figure 26 shows a system offset
calibration (assuming a positive offset) where the analog input
range has been shifted upwards by the system offset after the
system offset calibration is completed. A negative offset may
also be accounted for by a system offset calibration.
The zero-scale error is adjusted for an offset calibration, and
the positive full-scale error is adjusted for a gain calibration.
MAX SYSTEM FULL SCALE
IS ⴞ2.5% FROM VREF
The diagram of Figure 25 shows the timing for a full selfcalibration. Here the BUSY line stays high for the full length of
the self-calibration. A self-calibration is initiated by bringing the
CAL pin low (which initiates an internal reset) and then high
again or by writing to the control register and setting the STCAL
bit to 1 (note that if the part is in a power-down mode the CAL pulsewidth must take account of the power-up time ). The BUSY line is
triggered high from the rising edge of CAL (or the end of the
write to the control register if calibration is initiated in software), and BUSY will go low when the full self-calibration is
complete after a time tCAL as shown in Figure 25.
REV. B
VREF + SYS OFFSET
VREF – 1LSB
VREF –1LSB
Self-Calibration Timing
–21–
ANALOG
INPUT
RANGE
SYSTEM OFFSET
ANALOG
INPUT
RANGE
CALIBRATION
SYS OFFSET
AGND
SYS OFFSET
AGND
MAX SYSTEM OFFSET
IS ⴞ5% OF VREF
MAX SYSTEM OFFSET
IS ⴞ5% OF VREF
Figure 26. System Offset Calibration
AD7858/AD7858L
Figure 27 shows a system gain calibration (assuming a system
full scale greater than the reference voltage) where the analog
input range has been increased after the system gain calibration
is completed. A system full-scale voltage less than the reference
voltage may also be accounted for by a system gain calibration.
MAX SYSTEM FULL SCALE
IS ⴞ2.5% FROM VREF
system (gain + offset) calibrations will be sufficient. If the system errors are large (close to the specified limits of the calibration range) three system (gain + offset) calibrations may be
required to reduced the offset and gain errors to at least the 12bit level. There will never be any need to perform more than
three system (offset + gain) calibrations.
MAX SYSTEM FULL SCALE
IS ⴞ2.5% FROM VREF
SYS F.S.
VREF – 1LSB
The zero scale error is adjusted for an offset calibration and the
positive full-scale error is adjusted for a gain calibration.
SYS F.S.
VREF – 1LSB
ANALOG
INPUT
RANGE
SYSTEM GAIN
System Calibration Timing
The calibration timing diagram in Figure 29 is for a full system
calibration where the falling edge of CAL initiates an internal
reset before starting a calibration (note that if the part is in powerdown mode the CAL pulsewidth must take account of the power-up
time). If a full system calibration is to be performed in software
it is easier to perform separate gain and offset calibrations so
that the CONVST bit in the control register does not have to be
programmed in the middle of the system calibration sequence.
The rising edge of CAL starts calibration of the internal DAC
and causes the BUSY line to go high. If the control register is
set for a full system calibration, the CONVST must be used
also. The full-scale system voltage should be applied to the
analog input pins from the start of calibration. The BUSY line
will go low once the DAC and System Gain Calibration are
complete. Next the system offset voltage is applied to the AIN
pin for a minimum setup time (tSETUP) of 100 ns before the
rising edge of the CONVST and remain until the BUSY signal
goes low. The rising edge of the CONVST starts the system
offset calibration section of the full system calibration and also
causes the BUSY signal to go high. The BUSY signal will go
low after a time tCAL2 when the calibration sequence is complete. In some applications not all the input channels may be
used. In this case it may be useful to dedicate two input channels for the system calibration, one which has the system offset
voltage applied to it, and one which has the system full scale
voltage applied to it. When a system offset or gain calibration is
performed, the channel selected should correspond to the system offset or system full-scale voltage channel.
ANALOG
INPUT
RANGE
CALIBRATION
AGND
AGND
Figure 27. System Gain Calibration
Finally in Figure 28 both the system offset and gain are accounted for by the a system offset followed by a system gain
calibration. First the analog input range is shifted upwards by
the positive system offset and then the analog input range is
adjusted at the top end to account for the system full scale.
MAX SYSTEM FULL SCALE
IS ⴞ2.5% FROM VREF
MAX SYSTEM FULL SCALE
IS ⴞ2.5% FROM VREF
SYS F.S.
VREF –1LSB
ANALOG
INPUT
RANGE
SYS OFFSET
AGND
VREF + SYS OFFSET
SYS F.S.
VREF – 1LSB
SYSTEM OFFSET
CALIBRATION
ANALOG
FOLLOWED BY
INPUT
RANGE
SYSTEM GAIN
CALIBRATION
MAX SYSTEM OFFSET
IS ⴞ5% OF VREF
SYS OFFSET
AGND
MAX SYSTEM OFFSET
IS ⴞ5% OF VREF
Figure 28. System (Gain + Offset) Calibration
System Gain and Offset Interaction
The inherent architecture of the AD7858/AD7858L leads to an
interaction between the system offset and gain errors when a
system calibration is performed. Therefore, it is recommended
to perform the cycle of a system offset calibration followed by a
system gain calibration twice. Separate system offset and system
gain calibrations reduce the offset and gain errors to at least the
12-bit level. By performing a system offset CAL first and a
system gain calibration second, priority is given to reducing the
gain error to zero before reducing the offset error to zero. If the
system errors are small, a system offset calibration would be
performed, followed by a system gain calibration. If the system
errors are large (close to the specified limits of the calibration
range), this cycle would be repeated twice to ensure that the
offset and gain errors were reduced to at least the 12-bit level.
The advantage of doing separate system offset and system gain
calibrations is that the user has more control over when the
analog inputs need to be at the required levels, and the
CONVST signal does not have to be used.
The timing for a system (gain + offset) calibration is very similar
to that of Figure 29 the only difference being that the time tCAL1
will be replaced by a shorter time of the order of tCAL2 as the
internal DAC will not be calibrated. The BUSY signal will
signify when the gain calibration is finished and when the part is
ready for the offset calibration.
t1 = 100ns MIN, t14 = 50/90ns MIN 5V/3V,
t15 = 2.5 tCLKIN MAX, tCAL1 = 111114 tCLKIN,
tCAL2 = 13899 tCLKIN
t1
CAL (I/P)
t15
BUSY (O/P)
tCAL2
tCAL1
Alternatively, a system (gain + offset) calibration can be
performed. It is recommended to perform three system (gain +
offset) calibrations to reduce the offset and gain errors to the
12-bit level. For the system (gain + offset) calibration priority is
given to reducing the offset error to zero before reducing the
gain error to zero. Thus if the system errors are small then two
–22–
t16
CONVST (I/P)
tSETUP
AIN (I/P)
VSYSTEM FULL SCALE
VOFFSET
Figure 29. Timing Diagram for Full System Calibration
REV. B
AD7858/AD7858L
The timing diagram for a system offset or system gain calibration is shown in Figure 30. Here again the CAL is pulsed and
the rising edge of the CAL initiates the calibration sequence (or
the calibration can be initiated in software by writing to the
control register). The rising edge of the CAL causes the BUSY
line to go high and it will stay high until the calibration sequence is finished. The analog input should be set at the correct
level for a minimum setup time (tSETUP) of 100 ns before the rising
edge of CAL and stay at the correct level until the BUSY signal
goes low.
t1
CAL (I/P)
t15
tCAL2
VSYSTEM FULL SCALE OR VSYSTEM OFFSET
AIN (I/P)
When writing to the part via the DIN line there is the possibility
of writing data into the incorrect registers, such as the test register for instance, or writing the incorrect data and corrupting the
serial interface. The SYNC pin acts as a reset. Bringing the
SYNC pin high resets the internal shift register. The first data
bit after the next SYNC falling edge will now be the first bit of a
new 16-bit transfer. It is also possible that the test register contents were altered when the interface was lost. Therefore, once
the serial interface is reset it may be necessary to write the 16-bit
word 0100 0000 0000 0010 to restore the test register to its
default value. Now the part and serial interface are completely
reset. It is always useful to retain the ability to program the
SYNC line from a port of the µController/DSP to have the
ability to reset the serial interface.
Table X summarizes the interface modes provided by the
AD7858/AD7858L. It also outlines the various µP/µC to which
the particular interface is suited.
BUSY (O/P)
tSETUP
Resetting the Serial Interface
Interface Mode 1 may only be set by programming the control
register (see section on Control Register).
Figure 30. Timing Diagram for System Gain or System
Offset Calibration
Some of the more popular µProcessors, µControllers, and the
DSP machines that the AD7858/AD7858L will interface to
directly are mentioned here. This does not cover all µCs, µPs,
and DSPs. A more detailed timing description on each of the
interface modes follows.
SERIAL INTERFACE SUMMARY
Table IX details the two interface modes and the serial clock
edges from which the data is clocked out by the AD7858/
AD7858L (DOUT Edge) and that the data is latched in on
(DIN Edge).
Table X. Interface Mode Description
In both interface Modes 1 and 2 the SYNC is gated with the
SCLK. Thus the SYNC↓ may clock out the MSB of data. Subsequent bits will be clocked out by the Serial Clock, SCLK. The
condition for the SYNC↓ clocking out the MSB of data is as
follows:
The falling edge of SYNC will clock out the MSB if the serial clock
is low when the SYNC goes low.
If this condition is not the case, the SCLK will clock out the
MSB. If a noncontinuous SCLK is used, it should idle high.
Table IX. SCLK Active Edges
Interface Mode
Edge
DOUT Edge
DIN
1, 2
SCLK↓
SCLK↑
REV. B
–23–
Interface
Mode
␮Processor/
␮Controller
Comment
1
8XC51
8XL51
PIC17C42
(2-Wire)
(DIN Is an Input/
Output Pin)
2
68HC11
68L11
68HC16
PIC16C64
ADSP21xx
DSP56000
DSP56001
DSP56002
DSP56L002
(3-Wire, SPI)
(Default Mode)
AD7858/AD7858L
automatically revert back to an input after a time, t14. Note that
a continuous SCLK shown by the dotted waveform in Figure 35
can be used provided that the SYNC is low for only 16 clock
pulses in each of the read and write cycles.
DETAILED TIMING SECTION
Mode 1 (2-Wire 8051 Interface)
The read and writing takes place on the DIN line and the conversion is initiated by pulsing the CONVST pin (note that in
every write cycle the 2/3 MODE bit must be set to 1). The
conversion may be started by setting the CONVST bit in the
control register to 1 instead of using the CONVST pin.
Below in Figure 31 and in Figure 32 are the timing diagrams for
Operating Mode 1 in Table X where we are in the 2-wire interface mode. Here the DIN pin is used for both input and output
as shown. The SYNC input is level triggered active low and can
be pulsed (Figure 31) or can be constantly low (Figure 32).
In Figure 31 the part samples the input data on the rising edge
of SCLK. After the 16th rising edge of SCLK the DIN is configured as an output. When the SYNC is taken high the DIN is
three-stated. Taking SYNC low disables the three-state on the
DIN pin and the first SCLK falling edge clocks out the first data
bit. Once the 16 clocks have been provided the DIN pin will
In Figure 32 the SYNC line is tied low permanently and this
results in a different timing arrangement. With SYNC tied low
permanently the DIN pin will never be three-stated. The 16th
rising edge of SCLK configures the DIN pin as an input or an
output as shown in the diagram. Here no more than 16 SCLK
pulses must occur for each of the read and write operations.
If reading from and writing to the calibration registers in this
interface mode, all the selected calibration registers must be
read from or written to. The read and write operations cannot
be aborted. When reading from the calibration registers, the
DIN pin will remain as an output for the full duration of all the
calibration register read operations. When writing to the calibration registers, the DIN pin will remain as an input for the full
duration of all the calibration register write operations.
t3 = –0.4tSCLK MIN (NONCONTINUOUS SCLK) ⴞ0.4tSCLK ns MIN/MAX (CONTINUOUS SCLK),
t6 = 75/115ns MAX (5V/3V), t7 = 40/60ns MIN (5V/3V), t8 = 20/30ns MIN (5V/3V)
POLARITY PIN LOGIC HIGH
SYNC (I/P)
t11
t3
t11
t3
1
SCLK (I/P)
16
t7
t8
DIN (I/O)
1
16
t5
DB15
t14
t6
t12
DB0
t6
DB15
DB0
THREE-STATE
DATA WRITE
DATA READ
DIN BECOMES AN OUTPUT
DIN BECOMES AN INPUT
Figure 31. Timing Diagram for Read/Write Operation with DIN as an Input/Output
(i.e., Mode 1)
t6 = 75/115ns MAX (5V/3V), t7 = 40/60ns MIN (5V/3V), t8 = 20/30ns MIN (5V/3V),
t13 = 90/130ns MAX (5V/3V), t14 = 50/90ns MIN (5V/3V)
POLARITY PIN LOGIC HIGH
SCLK (I/P)
1
16
t7
t8
DIN (I/O)
1
t6
t13
DB15
16
6
t14
t6
DB0
DB15
DB0
DATA WRITE
DATA READ
DIN BECOMES AN INPUT
Figure 32. Timing Diagram for Read/Write Operation with DIN as an Input/Output
and SYNC Input Tied Low (i.e., Interface Mode 1)
–24–
REV. B
AD7858/AD7858L
SYNC going low disables the three-state on the DOUT pin.
The first falling edge of the SCLK after the SYNC going low
clocks out the first leading zero on the DOUT pin. The DOUT
pin is three-stated again a time t12 after the SYNC goes high.
With the DIN pin the data input has to be set up a time t7 before the SCLK rising edge as the part samples the input data on
the SCLK rising edge in this case. If resetting the interface is
required, the SYNC must be taken high and then low.
Mode 2 (3-Wire SPI/QSPI Interface Mode)
This is the DEFAULT INTERFACE MODE.
In Figure 33 below we have the timing diagram for interface
Mode 2 which is the SPI/QSPI interface mode. Here the SYNC
input is active low and may be pulsed or tied permanently low.
If SYNC is permanently low, 16 clock pulses must be applied to
the SCLK pin for the part to operate correctly, otherwise with a
pulsed SYNC input a continuous SCLK may be applied provided SYNC is low for only 16 SCLK cycles. In Figure 33 the
t3 = –0.4tSCLK MIN (NONCONTINUOUS SCLK) ⴞ0.4tSCLK ns MIN/MAX (CONTINUOUS SCLK),
t6 = 75/115ns MAX (5V/3V), t7 = 40/60ns MIN (5V/3V), t8 = 20/30ns MIN (5V/3V),
t11 = 30/50ns MIN (NONCONTINUOUS SCLK) (5V/3V), (30/50)/0.4tSCLK ns MIN/MAX
POLARITY PIN LOGIC HIGH
(CONTINUOUS SCLK) (5V/3V)
SYNC (I/P)
t11
t3
SCLK (I/P)
t9
1
2
3
4
THREE-STATE
DB15
t7
DIN (I/P)
6
16
t12
t6
t6
DOUT (O/P)
5
t10
t5
DB15
DB14
DB13
DB12
DB11
DB0
THREE-STATE
t8
t8
DB14
DB10
DB13
DB12
DB11
DB10
DB0
Figure 33. SPI/QSPI Mode 2 Timing Diagram for Read/Write Operation
with DIN Input, DOUT Output, and SYNC Input
REV. B
–25–
AD7858/AD7858L
CONFIGURING THE AD7858/AD7858L
The AD7858/AD7858L contains 14 on-chip registers which can
be accessed via the serial interface. In the majority of applications it
will not be necessary to access all of these registers. Here the
CLKIN signal is applied directly after power-on; the CLKIN
signal must be present to allow the part to perform a calibration.
This automatic calibration will be completed approximately 32 ms
after the AD7858 has powered up (4 MHz CLK).
For accessing the on-chip registers it is necessary to write to the
part. To change the channel from the default channel setting
the user will be required to write to the part. To enable Serial
Interface Mode 1 the user must also write to the part. Figure 34
and 35 outline flowcharts of how to configure the AD7858/
AD7858L Serial Interface Modes 1 and 2 respectively. The
continuous loops on all diagrams indicate the sequence for more
than one conversion. The options of using a hardware (pulsing
the CONVST pin) or software (setting the CONVST bit to 1)
conversion start, and reading/writing during or after conversion
are shown in Figures 34 and 35. If the CONVST pin is never
used then it should be tied to DVDD permanently. Where reference is made to the BUSY bit equal to a Logic 0, to indicate the
end of conversion, the user in this case would poll the BUSY bit
in the status register.
Interface Mode 1 Configuration
Figure 34 shows the flowchart for configuring the part in Interface Mode 1. This mode of operation can only be enabled by
writing to the control register and setting the 2/3 MODE bit.
Reading and writing cannot take place simultaneously in this
mode as the DIN pin is used for both reading and writing.
START
POWER-ON, APPLY CLKIN SIGNAL,
WAIT FOR AUTOMATIC CALIBRATION
SERIAL
INTERFACE
MODE
?
1
YES
INITIATE
CONVERSION
IN
SOFTWARE
?
NO
APPLY SYNC (IF REQUIRED), SCLK, WRITE
TO CONTROL REGISTER SETTING CHANNEL
TWO-WIRE MODE
APPLY SYNC (IF REQUIRED), SCLK,
WRITE TO CONTROL REGISTER
SETTING CHANNEL AND TWO-WIRE MODE
WRITE
TO CONTROL REGISTER SETTING CONVST
BIT TO 1 (SEE NOTE)
PULSE CONVST PIN
YES
WAIT APPROX. 200ns AFTER
CONVST RISING EDGE OR AFTER END
OF CONTROL REGISTER WRITE
READ
DATA
DURING
CONVERSION
?
NO
WAIT FOR BUSY SIGNAL TO GO LOW
OR
WAIT FOR BUSY BIT = 0
APPLY SYNC (IF REQUIRED), SCLK, READ
PREVIOUS CONVERSION RESULT ON DIN PIN
APPLY SYNC (IF REQUIRED), SCLK, READ
CURRENT CONVERSION RESULT ON DIN PIN
NOTE:
TWO SEPARATE WRITES ARE REQUIRED TO SET A NEW CHANNEL ADDRESS AND INITIATE A
CONVERSION ON THAT NEW CHANNEL IN SOFTWARE AS THE ACQUISITION TIME (2 tCLKIN)
MUST ELAPSE BEFORE THE CONVERSION BEGINS. IF BOTH COMMANDS ARE ISSUED IN THE ONE
WRITE THE RESULT OF THIS CONVERSION SHOULD BE DISCARDED AND THE NEXT
CONVERSION ON THAT SAME CHANNEL WILL PROVIDE CORRECT RESULTS.
Figure 34. Flowchart for Setting Up, Reading, and Writing in Interface Mode 1
–26–
REV. B
AD7858/AD7858L
that no valid data is written to any of the registers. When using
the software conversion start and transferring data during conversion Note 1 must be obeyed.
Interface Mode 2 Configuration
Figure 35 shows the flowchart for configuring the part in Interface Mode 2. In this case the read and write operations take
place simultaneously via the serial port. Writing all 0s ensures
START
POWER-ON, APPLY CLKIN SIGNAL,
WAIT FOR AUTOMATIC CALIBRATION
SERIAL
INTERFACE
MODE
?
2
INITIATE
CONVERSION
IN
SOFTWARE
?
YES
NO
PULSE CONVST PIN
TRANSFER
DATA DURING
CONVERSION
?
YES
APPLY SYNC (IF REQUIRED), SCLK, WRITE
TO CONTROL REGISTER SETTING CHANNEL,
(SEE NOTE 1)
NO
YES
WAIT APPROX 200ns AFTER
CONVST RISING EDGE
APPLY SYNC (IF REQUIRED), SCLK, READ
PREVIOUS CONVERSION RESULT ON DOUT
PIN, AND WRITE CHANNEL SELECTION
APPLY SYNC (IF REQUIRED), SCLK, WRITE
TO CONTROL REGISTER SETTING CHANNEL
TRANSFER
DATA DURING
CONVERSION
?
WRITE TO CONTROL REGISTER
SETTING CONVST BIT TO 1,
READ PREVIOUS RESULT ON
DOUT PIN (SEE NOTES 1&2)
WRITE TO CONTROL REGISTER SETTING
CONVST BIT TO 1, READ
CURRENT CONVERSION RESULT
ON DOUT PIN (SEE NOTE 2)
NO
WAIT FOR BUSY SIGNAL TO GO LOW
OR
WAIT FOR BUSY BIT = 0
WAIT FOR BUSY SIGNAL TO GO LOW
OR
WAIT FOR BUSY BIT = 0
APPLY SYNC (IF REQUIRED), SCLK,
READ CURRENT CONVERSION RESULT
ON DOUT PIN, AND WRITE CHANNEL
SELECTION
NOTES
1WHEN USING THE SOFTWARE CONVERSION START AND TRANSFERRING DATA DURING CONVERSION THE USER MUST ENSURE THE CONTROL REGISTER
WRITE OPERATION EXTENDS BEYOND THE FALLING EDGE OF BUSY. THE FALLING EDGE OF BUSY RESETS THE CONVST BIT TO 0 AND ONLY AFTER THIS
TIME CAN IT BE REPROGRAMMED TO 1 TO START THE NEXT CONVERSION.
2TWO SEPARATE WRITES ARE REQUIRED TO SET A NEW CHANNEL ADDRESS AND INITIATE A CONVERSION ON THAT NEW CHANNEL IN SOFTWARE AS
THE ACQUISITION TIME (2 tCLKIN) MUST ELAPSE BEFORE THE CONVERSION BEGINS. IF BOTH COMMANDS ARE ISSUED IN THE ONE WRITE THE
RESULT OF THIS CONVERSION SHOULD BE DISCARDED AND THE NEXT CONVERSION ON THAT SAME CHANNEL WILL PROVIDE CORRECT RESULTS.
Figure 35. Flowchart for Setting Up, Reading, and Writing in Interface Mode 2
REV. B
–27–
AD7858/AD7858L
MICROPROCESSOR INTERFACING
OPTIONAL
In many applications, the user may not require the facility of
writing to most of the on-chip registers. The only writing necessary is to set the input channel configuration. After this the
CONVST is applied, a conversion is performed, and the result
may be read using the SCLK to clock out the data from the
output register on to the DOUT pin. At the same time a write
operation occurs and this may consist of all 0s where no data is
written to the part or may set a different input channel configuration for the next conversion. The SCLK may be connected to
the CLKIN pin if the user does not want to have to provide
separate serial and master clocks. With this arrangement the
SYNC signal must be low for 16 SCLK cycles for the read and
write operations.
CONVST
CLKIN
4MHz/1.8MHz
8XC51/L51
MASTER
SYNC
DIN
DOUT
CONVST
CLKIN
P3.1
SCLK
P3.0
DIN
(INT0/P3.2)
OPTIONAL
SLAVE
BUSY
SYNC
Figure 37. 8XC51/PIC16C42 Interface
AD7858/AD7858L to 68HC11/16/L11/PIC16C42 Interface
CONVERSION START
4MHz/1.8MHz
MASTER CLOCK
SCLK
AD7858/
AD7858L
AD7858/AD7858L
SYNC SIGNAL TO
GATE THE SCLK
SERIAL DATA INPUT
SERIAL DATA
OUTPUT
Figure 36. Simplified Interface Diagram
AD7858/AD7858L to 8XC51 Interface
Figure 37 shows the AD7858/AD7858L interface to the
8XC51. The 8XL51 is for interfacing to the AD7858/AD7858L
when the supply is at 3 V. The 8XC51 only runs at 5 V. The
8XC51 is in Mode 0 operation. This is a two-wire interface
consisting of the SCLK and the DIN which acts as a bidirectional line. The SYNC is tied low. The BUSY line can be used
to give an interrupt driven system but this would not normally
be the case with the 8XC51. For the 8XC51 12 MHz version
the serial clock will run at a maximum of 1 MHz so the serial
interface of the AD7858/AD7858L will only be running at
1 MHz. The CLKIN signal must be provided separately to the
AD7858/AD7858L from a port line on the 8XC51 or from a
source other than the 8XC51. Here the SCLK cannot be tied to
the CLKIN as the SYNC is tied low permanently. The CONVST
signal can be provided from an external timer or conversion can
be started in software if required. The sequence of events would
typically be to write to the control register via the DIN line setting
a conversion start and the 2-wire interface mode (this would be
performed in two 8-bit writes), wait for the conversion to be
finished (4.6 µs with 4 MHz CLKIN), read the conversion result
data on the DIN line (this would be performed in two 8-bits
reads), and repeat the sequence. The maximum serial frequency
will be determined by the data access and hold times of the
8XC51 and the AD7858/AD7858L.
Figure 38 shows the AD7858/AD7858L SPI/QSPI interface to
the 68HC11/16/L11/PIC16C42. The 68L11 is for interfacing to
the AD7858/AD7858L when the supply is 3 V. The AD7858/
AD7858L is in Interface Mode 2. The SYNC line is not used
and is tied to DGND. The µController is configured as the master, by setting the MSTR bit in the SPCR to 1, and provides the
serial clock on the SCK pin. For all the µControllers the CPOL
bit is set to 1 and for the 68HC11/16/L11 the CPHA bit is set to
1. The CLKIN and CONVST signals can be supplied from the
µController or from separate sources. The BUSY signal can be
used as an interrupt to tell the µController when the conversion
is finished, then the reading and writing can take place. If required the reading and writing can take place during conversion
and there will be no need for the BUSY signal in this case.
OPTIONAL
AD7858/AD7858L
4MHz/1.8MHz
68HC11/L11/16
DVDD
CLKIN
SPI
SS
MASTER
SYNC
HC16, QSPI
SCK
MOSI
SLAVE
SCLK
MISO
IRQ
CONVST
DOUT
OPTIONAL
BUSY
DIN
Figure 38. 68HC11 and 68HC16 Interface
For the 68HC16 the word length should be set to 16 bits, and
the SS line should be tied to the SYNC pin for the QSPI interface. The micro-sequencer and RAM associated with the
68HC16 QSPI port can be used to perform a number of read
and write operations, and store the conversion results in
memory, independent of the CPU. This is especially useful when
reading the conversion results from all eight channels consecutively. The command section of the QSPI port RAM would be
programmed to perform a conversion on one channel, read the
conversion result, perform a conversion on the next channel,
read the conversion result, and so on until all eight conversion
results are stored into the QSPI RAM.
–28–
REV. B
AD7858/AD7858L
A typical sequence of events would be to write to the control
register via the DIN line setting a conversion start and at the
same time reading data from the previous conversion on the
DOUT line (both the read and write operations would each be
two 8-bit operations, one 16-bit operation for the 68HC16),
wait for the conversion to be finished (= 4.6 µs for AD7858
with 4 MHz CLKIN), and then repeat the sequence. The maximum serial frequency will be determined by the data access and
hold times of the µControllers and the AD7858/AD7858L.
AD7858/AD7858L to ADSP-21xx Interface
Figure 39 shows the AD7858/AD7858L interface to the ADSP21xx. The ADSP-21xx is the master and the AD7858/AD7858L
is the slave. The AD7858/AD7858L is in Interface Mode 2.
For the ADSP-21xx the bits in the serial port control register
should be set up as TFSR = RFSR = 1 (need a frame sync for
every transfer), SLEN = 15 (16-bit word length), TFSW =
RFSW = 1 (alternate framing mode for transmit and receive
operations), INVRFS = INVTFS = 1 (active low RFS and
TFS), IRFS = 0, ITFS = 1 (External RFS and internal TFS),
and ISCLK = 1 (internal serial clock). The CLKIN and
CONVST signals can be supplied from the ADSP-21xx or
from an external source. The serial clock from the ADSP-21xx
must be inverted before the SCLK pin of the AD7858/AD7858L.
This SCLK could also be used to drive the CLKIN input of the
AD7858/AD7858L. The BUSY signal indicates when the conversion is finished and may not be required. The data access
and hold times of the ADSP-21xx and the AD7858/AD7858L
allow for a serial clock of 4 MHz/1.8 MHz at 5 V and 3.3 MHz/
1.8 MHz at 3 V supplies.
AD7858/AD7858L to DSP56000/1/2/L002 Interface
Figure 40 shows the AD7858/AD7858L to DSP56000/1/2/
L002 interface. Here the DSP5600x is the master and the
AD7858 is the slave. The AD7858/AD7858L is in Interface
Mode 2. The DSP56L002 is used when the AD7858/AD7858L
is being operated at 3 V. The setting of the bits in the registers
of the DSP5600x would be for synchronous operation (SYN =
1), internal frame sync (SCD2 = 1), gated internal clock (GCK
= 1, SCKD = 1), 16-bit word length (WL1 = 1, WL0 = 0). Since
a gated clock is used here the SCLK cannot be tied to the CLKIN
of the AD7858/AD7858L. The SCLK from the DSP5600x
must be inverted before it is applied to the AD7858/AD7858L.
Again the data access and hold times of the DSP5600x and
the AD7858/AD7858L allows for a SCLK of 4 MHz/1.8 MHz.
OPTIONAL
AD7858/AD7858L
CONVST
ADSP-21xx
4MHz/1.8MHz
SCK
MASTER
CLKIN
SCLK
DR
DOUT
RFS
SYNC
SLAVE
TFS
IRQ
DT
OPTIONAL
BUSY
DIN
Figure 39. ADSP-21xx Interface
REV. B
–29–
OPTIONAL
AD7858/AD7858L
4MHz/1.8MHz
DSP56000/1/2/L002
MASTER
CONVST
CLKIN
SCK
SCLK
SRD
DOUT
SYNC
SC2
IRQ
STD
SLAVE
OPTIONAL
BUSY
DIN
Figure 40. DSP56000/1/2 Interface
AD7858/AD7858L
APPLICATION HINTS
Grounding and Layout
The analog and digital supplies to the AD7858/AD7858L are
independent and separately pinned out to minimize coupling
between the analog and digital sections of the device. The part
has very good immunity to noise on the power supplies as can
be seen by the PSRR vs. Frequency graph. However, care
should still be taken with regard to grounding and layout.
The printed circuit board that houses the AD7858/AD7858L
should be designed such that the analog and digital sections are
separated and confined to certain areas of the board. This facilitates the use of ground planes that can be separated easily. A
minimum etch technique is generally best for ground planes as
it gives the best shielding. Digital and analog ground planes
should only be joined in one place. If the AD7858/AD7858L is
the only device requiring an AGND to DGND connection,
then the ground planes should be connected at the AGND and
DGND pins of the AD7858/AD7858L. If the AD7858/
AD7858L is in a system where multiple devices require AGND
to DGND connections, the connection should still be made at
one point only, a star ground point which should be established
as close as possible to the AD7858/AD7858L.
Avoid running digital lines under the device as these will couple
noise onto the die. The analog ground plane should be allowed
to run under the AD7858/AD7858L to avoid noise coupling.
The power supply lines to the AD7858/AD7858L should use as
large a trace as possible to provide low impedance paths and
reduce the effects of glitches on the power supply line. Fast
switching signals like clocks should be shielded with digital
ground to avoid radiating noise to other sections of the board,
and clock signals should never be run near the analog inputs.
Avoid crossover of digital and analog signals. Traces on opposite sides of the board should run at right angles to each other.
This will reduce the effects of feedthrough through the board. A
microstrip technique is by far the best but is not always possible
with a double-sided board. In this technique, the component
side of the board is dedicated to ground planes while signals are
placed on the solder side.
Good decoupling is also important. All analog supplies should
be decoupled with 10 µF tantalum in parallel with 0.1 µF capacitors to AGND. All digital supplies should have a 0.1 µF
disc ceramic capacitor to AGND. To achieve the best from
these decoupling components, they must be placed as close as
possible to the device, ideally right up against the device. In
systems where a common supply voltage is used to drive both
the AVDD and DVDD of the AD7858/AD7858L, it is recommended that the system’s AVDD supply be used. In this case
there should be a 10 Ω resistor between the AVDD pin and
DVDD pin. This supply should have the recommended analog
supply decoupling capacitors between the AVDD pin of the
AD7858/AD7858L and AGND and the recommended digital
supply decoupling capacitor between the DVDD pin of the
AD7858/AD7858L and DGND.
Evaluating the AD7858/AD7858L Performance
The recommended layout for the AD7858/AD7858L is outlined in the evaluation board for the AD7858/AD7858L. The
evaluation board package includes a fully assembled and tested
evaluation board, documentation, and software for controlling
the board from the PC via the EVAL-CONTROL BOARD.
The EVAL-CONTROL BOARD can be used in conjunction
with the AD7858/AD7858L Evaluation board, as well as many
other Analog Devices evaluation boards ending in the CB designator, to demonstrate/evaluate the ac and dc performance of the
AD7858/AD7858L.
The software allows the user to perform ac (fast Fourier transform) and dc (histogram of codes) tests on the AD7858/
AD7858L. It also gives full access to all the AD7858/AD7858L
on-chip registers allowing for various calibration and powerdown options to be programmed.
AD785x Family
All parts are 12 bits, 200 kSPS, 3.0 V to 5.5 V.
AD7853 – Single Channel Serial
AD7854 – Single Channel Parallel
AD7858 – Eight Channel Serial
AD7859 – Eight Channel Parallel
–30–
REV. B
AD7858/AD7858L
PAGE INDEX
Topic
Page No.
FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Self-Calibration Description . . . . . . . . . . . . . . . . . . . . . . . 21
GENERAL DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . 1
Self-Calibration Timing . . . . . . . . . . . . . . . . . . . . . . . . . . 21
PRODUCT HIGHLIGHTS . . . . . . . . . . . . . . . . . . . . . . . . . 1
System Calibration Description . . . . . . . . . . . . . . . . . . . . 21
SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
System Gain and Offset Interaction . . . . . . . . . . . . . . . . . 22
TIMING SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . 4
System Calibration Timing . . . . . . . . . . . . . . . . . . . . . . . 22
TYPICAL TIMING DIAGRAMS . . . . . . . . . . . . . . . . . . . . 5
SERIAL INTERFACE SUMMARY . . . . . . . . . . . . . . . . . . 23
ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . 6
Resetting The Serial Interface . . . . . . . . . . . . . . . . . . . . . 23
ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6
DETAILED TIMING SECTION
PIN CONFIGURATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . 6
Mode 1 (2-Wire 8051 Interface) . . . . . . . . . . . . . . . . . . . 24
PIN FUNCTION DESCRIPTIONS . . . . . . . . . . . . . . . . . . 7
Mode 2 (3-Wire SPI/QSPI Interface) . . . . . . . . . . . . . . . . 25
TERMINOLOGY . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
CONFIGURING THE AD7858/AD7858L . . . . . . . . . . . . 26
ON-CHIP REGISTERS
Interface Mode 1 Configuration . . . . . . . . . . . . . . . . . . . . 26
Addressing the On-Chip Registers . . . . . . . . . . . . . . . . . . . 9
Interface Mode 2 Configuration . . . . . . . . . . . . . . . . . . . . 27
CONTROL REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
MICROPROCESSOR INTERFACING . . . . . . . . . . . . . . . 28
STATUS REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
AD7858/AD7858L–8XC51 Interface . . . . . . . . . . . . . . . 28
CALIBRATION REGISTERS . . . . . . . . . . . . . . . . . . . . . . 13
AD7858/AD7858L–68HC11/16/L11/PIC16C42
Addressing the Calibration Registers . . . . . . . . . . . . . . . . 13
Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28
Writing to/Reading from the Calibration Registers . . . . . . 13
AD7858/AD7858L–ADSP-21xx Interface . . . . . . . . . . . . 29
Adjusting the Offset Calibration Registers . . . . . . . . . . . . 14
AD7858/AD7858L–DSP56000/1/2/L002 Interface . . . . . 29
Adjusting the Gain Calibration Register . . . . . . . . . . . . . . 14
APPLICATION HINTS
CIRCUIT INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . 15
Grounding and Layout . . . . . . . . . . . . . . . . . . . . . . . . . . . 30
CONVERTER DETAILS . . . . . . . . . . . . . . . . . . . . . . . . . . 15
Evaluating the AD7858/AD7858L Performance . . . . . . . 30
TYPICAL CONNECTION DIAGRAM . . . . . . . . . . . . . . 15
INDEX . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 31
ANALOG INPUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . 32
Acquisition Time . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
DC/AC Applications . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
Input Range . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
Transfer Function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
REFERENCE SECTION . . . . . . . . . . . . . . . . . . . . . . . . . . 17
PERFORMANCE CURVES . . . . . . . . . . . . . . . . . . . . . . . . 18
POWER-DOWN OPTIONS . . . . . . . . . . . . . . . . . . . . . . . . 18
POWER-UP TIMES
Using an External Reference . . . . . . . . . . . . . . . . . . . . . . 19
Using the Internal (On-Chip) Reference . . . . . . . . . . . . . 19
POWER VS. THROUGHPUT RATE . . . . . . . . . . . . . . . . 20
CALIBRATION SECTION
Calibration Overview . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
Automatic Calibration on Power-On . . . . . . . . . . . . . . . . 21
REV. B
TABLE INDEX
#
Title
Page No.
Table I.
Write Register Addressing . . . . . . . . . . . . . . . . . 9
Table II.
Read Register Addressing . . . . . . . . . . . . . . . . . 9
Table III.
Channel Selection . . . . . . . . . . . . . . . . . . . . . . 11
Table IV.
Calibration Selection . . . . . . . . . . . . . . . . . . . . 11
Table V.
Calibration Register Addressing . . . . . . . . . . . 13
Table VI.
Power Management Options . . . . . . . . . . . . . . 19
Table VII.
Power Consumption vs. Throughput . . . . . . . 20
Table VIII. Calibration Times (AD7858 with 4 MHz
CLKIN) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
Table IX.
SCLK Active Edges . . . . . . . . . . . . . . . . . . . . . 23
Table X.
Interface Mode Description . . . . . . . . . . . . . . . 23
–31–
AD7858/AD7858L
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
24-Lead Plastic DIP (N-24)
24
13
1
12
0.260 ⴞ0.001
(6.61 ⴞ0.03)
C01337–0–6/00
1.228 (31.19)
1.226 (31.14)
0.32 (8.128)
0.30 (7.62)
PIN 1
0.130 (3.30)
0.128 (3.25)
0.02 (0.5)
0.016 (0.41)
0.11 (2.79)
0.09 (2.28)
0.07 (1.78)
0.05 (1.27)
SEATING
PLANE
15ⴗ
0
0.011 (0.28)
0.009 (0.23)
NOTES
1. LEAD NO. 1 IDENTIFIED BY A DOT OR NOTCH.
2. PLASTIC LEADS WILL BE EITHER TIN PLATED OR SOLDER DIPPED
IN ACCORDANCE WITH MIL-M-38510 REQUIREMENTS.
24-Lead Small Outline Package (R-24)
13
1
12
0.096 (2.44)
0.089 (2.26)
PIN 1
0.01 (0.254)
0.006 (0.15)
0.414 (10.52)
0.398 (10.10)
24
0.299 (7.6)
0.291 (7.39)
0.608 (15.45)
0.596 (15.13)
0.05
(1.27)
BSC
6ⴗ
0ⴗ
SEATING
0.013 (0.32)
PLANE
0.009 (0.23)
0.019 (0.49)
0.014 (0.35)
0.03 (0.76)
0.02 (0.51)
0.042 (1.067)
0.018 (0.447)
NOTES
1. LEAD NO. 1 IDENTIFIED BY A DOT.
2. SOIC LEADS WILL BE EITHER TIN PLATED OR SOLDER DIPPED
IN ACCORDANCE WITH MIL-M-38510 REQUIREMENTS.
24-Lead Shrink Small Outline Package (RS-24)
13
1
12
PIN 1
0.008 (0.203) 0.0256
(0.65)
0.002 (0.050) BSC
PRINTED IN U.S.A.
24
0.212 (5.38)
0.205 (5.207)
0.311 (7.9)
0.301 (7.64)
0.328 (8.33)
0.318 (8.08)
0.07 (1.78)
0.066 (1.67)
8ⴗ
0.015 (0.38)
0ⴗ
SEATING
0.010 (0.25) PLANE 0.009 (0.229)
0.005 (0.127)
0.037 (0.94)
0.022 (0.559)
NOTES
1. LEAD NO. 1 IDENTIFIED BY A DOT.
2. LEADS WILL BE EITHER TIN PLATED OR SOLDER DIPPED
IN ACCORDANCE WITH MIL-M-38510 REQUIREMENTS.
–32–
REV. B