AD AD705JR Picoampere input current bipolar op amp Datasheet

a
FEATURES
DC PERFORMANCE
25 mV max Offset Voltage (AD705T)
0.6 mV/8C max Drift (AD705K/T)
100 pA max Input Bias Current (AD705K)
600 pA max IB Over MIL Temperature Range (AD705T)
114 dB min CMRR (AD705K/T)
114 dB min PSRR (AD705T)
200 V/mV min Open Loop Gain
0.5 mV p-p typ Noise, 0.1 Hz to 10 Hz
600 mA max Supply Current
AC PERFORMANCE
0.15 V/µs Slew Rate
800 kHz Unity Gain Crossover Frequency
10,000 pF Capacitive Load Drive Capability
Low Cost
Available in 8-Pin Plastic Mini-DlP, Hermetic Cerdip
and Surface Mount (SOIC) Packages
MIL-STD-883B Processing Available
Dual Version Available: AD706
Quad Version: AD704
APPLICATIONS
Low Frequency Active Filters
Precision Instrumentation
Precision Integrators
PRODUCT DESCRIPTION
The AD705 is a low power bipolar op amp that has the low input bias current of a BiFET amplifier but which offers a significantly lower IB drift over temperature. The AD705 offers many
of the advantages of BiFET and bipolar op amps without their
inherent disadvantages. It utilizes superbeta bipolar input transistors to achieve the picoampere input bias current levels of
FET input amplifiers (at room temperature), while its IB typically only increases 5 times vs. BiFET amplifiers which exhibit a
1000X increase over temperature. This means that, at room
temperature, while a typical BiFET may have less IB than the
AD705, the BiFET’s input current will increase to a level of
several nA at +125°C. Superbeta bipolar technology also permits the AD705 to achieve the microvolt offset voltage and low
noise characteristics of a precision bipolar input amplifier.
The AD705 is a high quality replacement for the industrystandard OP07 amplifier while drawing only one sixth of its
power supply current. Since it has only 1/20th the input bias
current of an OP07, the AD705 can be used with much higher
source impedances, while providing the same level of dc precision. In addition, since the input bias currents are at picoAmp
Picoampere Input Current
Bipolar Op Amp
AD705
CONNECTION DIAGRAM
Plastic Mini-DIP (N)
Cerdip (Q) and
Plastic SOIC (R) Packages
OFFSET
NULL
1
TOP VIEW
8
OFFSET
NULL
–IN
2
7
V+
+IN
3
6
OUTPUT
V–
4
5
OVER
COMP
AD705
levels, the commonly used “balancing” resistor (connected between the noninverting input of a bipolar op amp and ground) is
not required.
The AD705 is an excellent choice for use in low frequency active filters in 12- and 14-bit data acquisition systems, in precision instrumentation and as a high quality integrator.
The AD705 is internally compensated for unity gain and is
available in five performance grades. The AD705J and AD705K
are rated over the commercial temperature range of 0°C to
+70°C. The AD705A and AD705B are rated over the industrial
temperature range of –40°C to +85°C. The AD705T is rated
over the military temperature range of –55°C to +125°C and is
available processed to MIL-STD-883B, Rev. C.
The AD705 is offered in three varieties of 8-pin package: plastic
DIP, hermetic cerdip and surface mount (SOIC). “J” grade
chips are also available.
PRODUCT HIGHLIGHTS
1. The AD705 is a low drift op amp that offers BiFET level
input bias currents, yet has the low IB drift of a bipolar amplifier. It upgrades the performance of circuits using op amps
such as the LT1012.
2. The combination of Analog Devices’ advanced superbeta
processing technology and factory trimming provides both
low drift and high dc precision.
3. The AD705 can be used in applications where a chopper amplifier would normally be required but without the chopper’s
inherent noise and other problems.
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
AD705–SPECIFICATIONS (@ T = +258C, V
A
Parameter
INPUT OFFSET VOLTAGE
Initial Offset
Offset
vs. Temp, Average TC
vs. Supply (PSRR)
TMIN to TMAX
Long Term Stability
Conditions
Min
TMIN to TMAX
VS = ± 2 V to ± 18 V
VS = ± 2.5 V to ± 18 V
110
108
CM
= 0 V, and VS = 615 V dc, unless otherwise noted)
AD705J/A
Typ
Max
30
45
0.2
129
126
0.3
90
150
1.2
60
80
0.3
80
100
150
200
40
40
0.3
80
80
150
200
Min
110
108
AD705K/B
Typ
Max
10
25
0.2
129
126
0.3
35
60
0.6
30
50
0.3
50
70
100
150
30
30
0.3
50
50
100
150
Min
114
108
AD705T
Typ
Max
Units
10
25
0.2
129
126
0.3
25
60
0.6
µV
µV
µV/°C
dB
dB
µV/month
30
50
0.6
90
120
100
150
pA
pA
pA/°C
pA
pA
INPUT BIAS CURRENT 1
VCM = 0 V
VCM = ± 13.5 V
vs. Temp, Average TC
TMIN to TMAX
TMIN to TMAX
INPUT OFFSET CURRENT
VCM = 0 V
VCM = ± 13.5 V
VCM = 0 V
VCM = ± 13.5 V
vs. Temp, Average TC
TMIN to TMAX
TMIN to TMAX
VCM = 0 V
VCM = ± 13.5 V
FREQUENCY RESPONSE
Unity Gain
Crossover Frequency
Slew Rate, Unity Gain
Slew Rate
G = –1
TMIN to TMAX
0.4
0.1
0.05
INPUT IMPEDANCE
Differential
Common Mode
INPUT VOLTAGE NOISE
0.8
0.15
0.15
VCM = ± 13.5 V
TMIN to TMAX
40i2
300i2
0.8
0.15
0.15
MHz
V/µs
V/µs
40i2
300i2
MΩipF
GΩipF
± 14
V
110
108
132
128
114
108
132
128
114
108
132
128
dB
dB
OPEN-LOOP GAIN
VO = ± 12 V
RLOAD = 10 kΩ
TMIN to TMAX
VO = ± 10 V
RLOAD = 2 kΩ
TMIN to TMAX
TEMPERATURE RANGE
FOR RATED PERFORMANCE
Commercial (0°C to +70°C)
Industrial (–40°C to +85°C)
Military (–55°C to +125°C)
0.4
0.1
0.05
± 13.5
50
0.5
17
15
22
1.0
0.5
17
15
22
50
1.0
22
µV p-p
nV/√Hz
nV/√Hz
50
fA/√Hz
300
200
2000
1500
400
300
2000
1500
400
300
2000
1500
V/mV
V/mV
200
150
1000
1000
300
200
1000
1000
300
200
1000
1000
V/mV
V/mV
± 13
613
± 14
± 14
± 15
± 13
613
± 14
± 14
± 15
± 13
613
± 14
± 14
± 15
V
V
mA
10,000
200
pF
Ω
Gain = +1
Open Loop
10,000
200
62.0
TMIN to TMAX
0.8
0.15
0.15
250
450
pA
pA
pA/°C
pA
pA
± 14
f = 10 Hz
POWER SUPPLY
Rated Performance
Operating Range
Quiescent Current
150
350
100
150
± 13.5
INPUT CURRENT NOISE
RLOAD = 10 kΩ
TMIN to TMAX
Short Circuit
30
30
0.4
80
80
600
750
± 14
0.5
17
15
Current
Capacitive Load
Drive Capability
Output Resistance
0.4
0.1
0.05
150
350
± 13.5
0.1 Hz to 10 Hz
f = 10 Hz
f = 1 kHz
OUTPUT CHARACTERISTICS
Voltage Swing
250
450
40i2
300i2
INPUT VOLTAGE RANGE
Common-Mode Voltage
COMMON-MODE
REJECTION RATIO
250
450
± 15
10,000
200
618
600
800
380
400
AD705J
AD705A
62.0
± 15
380
400
618
600
800
62.0
± 15
380
400
618
600
800
V
V
µA
µA
AD705K
AD705B
AD705T
–2–
REV. B
AD705
Parameter
Conditions
Min
PACKAGE OPTIONS
8-Pin Cerdip (Q-8)
8-Pin Plastic Mini-DIP (N-8)
8-Pin SOIC (R-8)
Chips
AD705J/A
Typ
Max
Min
AD705AQ
AD705JN
AD705JR
AD705JCHIPS
TRANSISTOR COUNT
# of Transistors
AD705K/B
Typ
Max
AD705BQ
AD705KN
45
45
Min
AD705T
Typ
Max
Units
AD705TQ
45
NOTES
1
Bias current specifications are guaranteed maximum at either input.
All min and max specifications are guaranteed
Specifications in boldface are tested on all production units at final electrical test. Results from those tests are used to calculate outgoing quality levels.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS 1
METALIZATION PHOTOGRAPH
Dimensions shown in inches and (mm).
0.074 (1.88)
NULL
8
+VS
7
VOUT
6
7
8
6
5 OVER COMP
5
0.0677
(1.72)
1
NULL 1
4
2
–IN 2
3
3
+IN
4 –VS
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 18 V
Internal Power Dissipation2 . . . . . . . . . . . . . . . . . . . 650 mW
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± VS
Differential Input Voltage3 . . . . . . . . . . . . . . . . . . . . . ± 0.7 V
Output Short Circuit Duration . . . . . . . . . . . . . . . . Indefinite
Storage Temperature Range (N, R) . . . . . . . –65°C to +125°C
Storage Temperature Range (Q) . . . . . . . . . –65°C to +150°C
Operating Temperature Range
AD705J/K . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
AD705A/B . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
AD705T . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +125°C
Lead Temperature Range (Soldering 60 sec) . . . . . . . . +300°C
NOTES
1
Stresses above those listed under “Absolute Maximum Ratings” may cause
permanent damage to the device. This is a stress rating only and functional
operation of the device at these or any other conditions above those indicated in
the operational section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect device reliability.
2
Specification is for device in free air:
8-Pin Plastic Package:
θJA = 165°C/Watt
8-Pin Cerdip Package:
θJA = 110°C/Watt
8-Pin Small Outline Package: θJA = 155°C/Watt
3
The input pins of these amplifiers are protected by back-to-back diodes. If the
differential voltage exceeds ± 0.7 V, external series protection resistors should be
added to limit the input current to less than 25 mA.
ORDERING GUIDE
Model
AD705AQ
AD705BQ
AD705JCHIPS
AD705JN
AD705JR
AD705JR-REEL
AD705JR-REEL7
AD705KN
AD705TQ
AD705TQ/883B
Temperature
Range
–40°C to +85°C
–40°C to +85°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
–55°C to +125°C
–55°C to +125°C
Package
Description
8-Pin Ceramic DIP
8-Pin Ceramic DIP
Bare Die
8-Pin Plastic DIP
8-Pin Plastic SOIC
8-Pin Plastic SOIC
8-Pin Plastic SOIC
8-Pin Plastic DIP
8-Pin Ceramic DIP
8-Pin Ceramic DIP
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD705 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
REV. B
–3–
Package
Option
Q-8
Q-8
N-8
R-8
R-8
R-8
N-8
Q-8
Q-8
WARNING!
ESD SENSITIVE DEVICE
AD705–Typical Characteristics (@ +258C, V = 615 V, unless otherwise noted)
S
100
40
NUMBER OF UNITS
NUMBER OF UNITS
120
80
20
40
0
– 80
0
–60 – 40 – 20
0 + 20 +40 +60 +80
INPUT OFFSET VOLTAGE – Microvolts
Figure 1. Typical Distribution of
Input Offset Voltage
0
–120
–60
0
+60
+120
INPUT OFFSET CURRENT – Picoamperes
Figure 3. Typical Distribution of
Input Offset Current
100
35
–0.5
–1.5
+1.5
+1.0
OFFSET VOLTAGE DRIFT – µV/°C
30
OUTPUT VOLTAGE – Volts p-p
–1.0
25
20
15
10
5
+0.5
–VS
0
5
10
15
SUPPLY VOLTAGE – ±Volts
0
1k
20
Figure 4. Input Common-Mode
Voltage Range vs. Supply Voltage
30
20
10
0
CHANGE IN OFFSET VOLTAGE – µV
40
–0.2
0
+0.2
+0.4
OFFSET VOLTAGE DRIFT – µV/°C
Figure 7. Typical Distribution of
Offset Voltage Drift
1.0
1k
10k
100k
1M
10M
SOURCE RESISTANCE – Ω
100M
Figure 6. Offset Voltage Drift vs.
Source Resistance
60
40
3
2
1
20
POSITIVE IB
0
–20
–40
0
–0.4
10
1M
4
SAMPLE SIZE: 85
–55°C TO +125°C
SOURCE RESISTANCE
MAY BE EITHER BALANCED
OR UNBALANCED
0.1
10k
100k
FREQUENCY – Hz
Figure 5. Large Signal Frequency
Response
50
80
–120
0
+60
+120
–60
INPUT BIAS CURRENT – Picoamperes
Figure 2. Typical Distribution of
Input Bias Current
+VS
120
40
INPUT BIAS CURRENT – pA
NUMBER OF UNITS
160
160
60
INPUT COMMON MODE VOLTAGE LIMIT – Volts
(REFERRED TO SUPPLY VOLTAGES)
SAMPLE SIZE: 510
SAMPLE SIZE:
1040
80
NUMBER OF UNITS
200
200
SAMPLE SIZE: 610
0
1
2
3
4
WARM-UP TIME IN MINUTES
5
Figure 8. Change in Input Offset
Voltage vs. Warm-Up Time
–4–
–60
–15
NEGATIVE IB
–10
–5
0
+5
+10
COMMON MODE VOLTAGE – Volts
+15
Figure 9. Input Bias Current vs.
Common-Mode Voltage
REV. B
AD705
1000
CURRENT NOISE – fA/√Hz
VOLTAGE NOISE – nV/√Hz
1000
100
10
100
0.5µV
100Ω
10kΩ
20MΩ
10
VOUT = in(2 • 109Ω)
1
1
10
100
FREQUENCY – Hz
1
1000
Figure 10. Input Noise Voltage
Spectral Density
CMRR – dB
+125°C
180
140
160
120
140
100
120
80
60
–PSRR
80
+ PSRR
40
60
20
40
0
5
10
15
SUPPLY VOLTAGE – ±Volts
0.1
20
Figure 13. Quiescent Supply
Current vs. Supply Voltage
10
100
1k
10k
FREQUENCY – Hz
100k
OPEN LOOP VOLTAGE GAIN
–55°C
+25°C
+125°C
140
0
120
30
100
60
PHASE
90
80
120
60
100k
2
4
6
10
20
40 60
LOAD RESISTANCE – kΩ
100
GAIN
40
150
20
180
Figure 16. Open Loop Gain vs.
Load Resistance over Temperature
REV. B
– 20
0.01 0.1
1
10
100
1k
10k
FREQUENCY – Hz
100k
1M
Figure 15. Power Supply Rejection
vs. Frequency
0
1
20
0.1
1M
Figure 14. Common-Mode
Rejection vs. Frequency
10M
1M
1
+VS
OUTPUT VOLTAGE LIMIT – Volts
(REFERRED TO SUPPLY VOLTAGES)
300
0
10
100
+25°C
350
PHASE SHIFT – Degrees
QUIESCENT CURRENT – µA
450
5
TIME – Seconds
Figure 12. 0.1 Hz to 10 Hz Noise
Voltage
160
+55°C
OPEN LOOP VOLTAGE GAIN
0
1000
Figure 11. Input Noise Current
Spectral Density
500
400
10
100
FREQUENCY – Hz
PSRR – dB
1
–0.5
–1.0
–1.5
+1.5
+1.0
+0.5
–VS
1
10 100 1k 10k 100k 1M 10M
FREQUENCY – Hz
Figure 17. Open Loop Gain and
Phase Shift vs. Frequency
–5–
0
5
10
15
SUPPLY VOLTAGE – ±Volts
Figure 18. Output Voltage Limit vs.
Supply Voltage
20
AD705
1M
0.1
100k
SLEW RATE
0.01
10k
ADDING AN EXTERNAL
CAPACITOR BETWEEN
PIN 5 AND GROUND
INCREASES THE AMPLIFIER'S
COMPENSATION
0.001
1
10
100
1000
1k
10,000
CLOSED LOOP OUTPUT IMPEDANCE – Ω
SLEW RATE – V/µs
GAIN BANDWIDTH
RF
1000
GAIN BANDWIDTH PRODUCT – Hz
1
+VS
100
0.1µF
AV = –1000
10
7
2
AD705
1
VIN
AV = +1
3
VOUT
6
RL
2kΩ
4
CL
0.1
–VS
0.1µF
0.01
IOUT = +1mA
SQUARE WAVE
INPUT
0.001
1
10
100
1k
10k
100k
FREQUENCY – Hz
VALUE OF OVERCOMPENSATION CAPACITOR – pF
Figure 20. Magnitude of Closed
Loop Output Impedance vs.
Frequency
Figure 19. Slew Rate & Gain
Bandwidth Product vs. Value of
Overcompensation Capacitor
Figure 21a. Unity Gain Follower
(For Large Signal Applications,
Resistor RF Limits the Current
Through the Input Protection
Diodes)
5µs
20µs
5µs
100
100
100
90
90
90
10
10
10
0%
0%
0%
20mV
2V
Figure 21b. Unity Gain Follower
Large Signal Pulse Response
RF = 10 kΩ, CL = 50 pF
20mV
Figure 21c. Unity Gain Follower
Small Signal Pulse Response
RF = 0 Ω, CL = 100 pF
Figure 21d. Unity Gain Follower
Small Signal Pulse Response
RF = 0 Ω, CL = 1000 pF
10kΩ
0.1µF
10kΩ
VIN
2
5µs
100
100
90
90
10
10
0%
0%
7
AD705
3
50µs
2V
+VS
4
–VS
VOUT
6
RL
2.5kΩ
CL
0.1µF
20mV
SQUARE WAVE
INPUT
Figure 22a. Unity Gain Inverter
Figure 22b. Unity Gain Inverter
Large Signal Pulse Response
CL = 50 pF
–6–
Figure 22c. Unity Gain Inverter
Small Signal Pulse Response
CL = 100 pF
REV. B
AD705
A High Performance Differential Amplifier Circuit
5µs
Figure 25 shows a high input impedance, differential amplifier
circuit that features a high common-mode voltage, and which
operates at low power. Table I details its performance with
changes in gain. To optimize the common-mode rejection of
this circuit at low frequencies and dc, apply a 1 volt, 1 Hz sine
wave to both inputs. Measuring the output with an oscilloscope,
adjust trimming potentiometer R6 for minimum output. For the
best CMR at higher frequencies, capacitor C2 should be replaced
with a 1.5 pF to 20 pF trimmer capacitor.
100
90
10
0%
20mV
Figure 22d. Unity Gain Inverter Small Signal
Pulse Response C, = 1000 pF
Both the IC socket and any standoffs at the op amp’s input terminals should be made of Teflon* to maintain low input current
drift over temperature.
*Teflon is a registered trademark of E.I. DuPont, Co.
10pF*
C1
5pF
10kΩ
R3
200kΩ
R2
10MΩ
+VS
R5*
0.1µF
+VS
SQUARE WAVE
INPUT
7
2
AD705
5kΩ
VIN
R1
100MΩ
VOUT
6
VIN–
5
3
4
*RESPONSE IS
0.1µF
–VS
0.1µF
AD705
3
NEARLY IDENTICAL
FOR CAPACITANCE
VALUES OF 0 TO 100pF
R4*
7
2
4
SOURCE
0.1µF
–VS
R1'
100MΩ
4.1nF
VIN+
Figure 23a. Follower Connected
in Feed-Forward Mode
GND
R2'
10MΩ
C2
5pF
VOUT
6
DC CMR
ADJUST
R6
500kΩ
CIRCUIT GAIN, G = – R2+R3 (1+ R5 )
R4
R1
VOUT = G (VIN– – VIN+)
COMMON MODE INPUT RANGE =
10 (VS – 1.5V) FOR VS = ±15V,
VCM RANGE = ±135V
RESISTORS R1 AND R1', R2 AND
R2' ARE VICTOREEN MOX-200
1/4 WATT, 1% METAL OXIDE.
*SEE TABLE I
5V
WARNING: POTENTIAL DANGER FROM HIGH SOURCE VOLTAGE.
THIS DIFFERENTIAL AMPLIFIER DOES NOT PROVIDE GALVANIC
ISOLATION. INPUT SOURCE MUST BE REFERRED TO THE SAME
GROUND CONNECTION AS THIS AMPLIFIER.
5µs
100
90
INPUT
Figure 25. A High Performance Differentials
Amplifier Circuit
10
0%
Table I. Typical Performance of Differential Amplifier
Circuit Operating at Various Gains
OUTPUT
5V
Circuit R4
Gain
(V)
Figure 23b. Follower Feed-Forward
Pulse Response
VOS ADJUST
+VS
20kΩ
1
0.1µF
8
2
1
10
100
7
AD705
6
5
3
0.1µF
4
OVERCOMPENSATION
CAPACITOR
–VS
Figure 24. Offset Null and Overcompensation
Connections
REV. B
–7–
R5
(V)
Trimmed
DC CMR
(dB)
1.13 kΩ 10 kΩ
≥85
100 Ω
9.76 kΩ ≥85
10.2 Ω 10 kΩ
≥85
RTI Average Circuit
Drift TC
Bandwidth
(mV/8C)
–3 dB
30
30
30
4.4 kHz
2.8 kHz
930 Hz
AD705
Table II. Recommended Component Values
for the 1 Hz Low-Pass Filter
Table II gives recommended component values for the 1 Hz filter of Figure 26. An unusual characteristic of the AD705 is that
both the input bias current and the input offset current and their
drift remain low over most of the op amps rated temperature
range. Therefore, for most applications, there is no need to use
the normal balancing resistor tied between the noninverting terminal of the op amp and ground. Eliminating the standard balancing resistor reduces board space and lowers circuit noise.
However, this resistor is needed at temperatures above 110°C,
because input bias current starts to change rapidly, as shown by
Figure 27.
Desired Low
Pass Response
Bessel Response
Butterworth Response
0.1 dB Chebychev
0.2 dB Chebychev
0.5 dB Chebychev
1.0 dB Chebychev
Pole
Frequency
(Hz)
Pole Q
1.27
1.00
0.93
0.90
0.85
0.80
0.58
0.707
0.77
0.80
0.86
0.96
C1 Value
C2 Value
(mF)
(mF)
0.14
0.23
0.26
0.28
0.32
0.38
0.11
0.11
0.11
0.11
0.11
0.10
C1357a–2–10/94
A 1 Hz, 2-Pole, Active Filter
Specified values are for a –3 dB point of 1.0 Hz. For other frequencies,
simply scale capacitors C1 and C2 directly; i.e., for 3 Hz Bessel response,
C1 = 0.046 µF, C2 = 0.037 µF.
C1
R2
1MΩ
OFFSET VOLTAGE OF FILTER CIRCUIT (RTI) – µV
+VS
R1
1MΩ
0.1µF
7
3
INPUT
C2
AD705
2
VOUT
6
4
0.1µF
–VS
OPTIONAL BALANCE
RESISTOR NETWORK
R3
2MΩ
WITHOUT THE NETWORK,
PINS 2 AND 6 OF THE AD705
ARE TIED TOGETHER.
C3
0.01µF
CAPACITORS C1, C2 AND C3 ARE SOUTHERN ELECTRONICS MPCC,
POLYCARBONATE, ±5%, 50 VOLT.
90
60
WITHOUT OPTIONAL
BALANCE RESISTOR, R3
30
0
WITH OPTIONAL BALANCE
RESISTOR, R3
–30
–60
–90
–60
–40
–20
0
+20
+40
+60
+80 +100 +120 +140
TEMPERATURE – °C
Figure 26. A 1 Hz, 2-Pole Active Filter
Figure 27. VOS vs. Temperature of 1 Hz Filter
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
Cerdip (Q) Package
0.055 (1.4) MAX
8
8
5
5
8
0.25R
(0.64)
0.25
(6.35)
PIN 1
1
1
4
0.060 (1.52)
0.015 (0.38)
0.200
(5.08)
MAX
0.150
(3.81)
MIN
0.200 (5.08)
0.125 (3.18)
0.154 ± 0.004
(3.91 ± 0.10)
PIN 1
4
0.236 ± 0.012
(6.00 ± 0.20)
4
1
0.100 0.070 (1.78)
(2.54) 0.030 (0.76)
BSC
SEATING
PLANE
0.193 ± 0.008
(4.90 ± 0.10)
0.035 ± 0.01
(0.89 ± 0.25)
0.165 ± 0.01
(4.19 ± 0.25)
0.18 ± 0.03
(4.57 ± 0.76)
0.125 (3.18)
MIN
0.018 ± 0.003
(0.46 ± 0.08)
0.310 (7.87)
0.220 (5.59)
0.100
(2.54)
TYP
0.033
(0.84)
NOM
0.30 (7.62)
REF
0.32 (8.13)
0.29 (7.37)
0-15 °
5
0.31
(7.87)
0.39 (9.91)
MAX
0.405 (10.29) MAX
0.023 (0.58)
0.014 (0.36)
8-Pin SOIC (R) Package
0.098 ± 0.006
(2.49 ± 0.23)
0.008 ± 0.004
(0.203 ± 0.075)
0.0500
(1.27)
BSC
0.017 ± 0.003
(0.42 ± 0.07)
SEATING
PLANE
0.011 ± 0.002
(0.269 ± 0.03)
0.033 ± 0.017
(0.83 ± 0.43)
0.011 ± 0.003
(0.28 ± 0.08)
0.015 (0.38)
0.008 (0.20)
0-15 °
–8–
REV. B
PRINTED IN U.S.A.
0.005 (0.13) MIN
Plastic Mini-DIP (N) Package
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