STV9556 7.5 NS TRIPLE-CHANNEL HIGH VOLTAGE VIDEO AMPLIFIER FEATURES ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ above is required, ensuring a maximum quality of the still pictures or moving video. Perfecly matched with the STV921x ST preamplifiers, it provides a highly performant and very cost effective video system. Triple-channel video amplifier Supply voltage up to 115 V 80V Output dynamic range Perfect for PICTURE BOOST application requiring high video amplitude Pinning for easy PCB layout Supports DC coupling (optimum cost saving) and AC coupling applications. Built-in Voltage Gain: 20 (Typ.) Rise and Fall Times: 7.5 ns (Typ.) Bandwidth: 50 MHz (Typ.) Very low stand-by power consumption Perfectly matched with the STV921x preamplifiers CLIPWATT 11 (Plastic Package) DESCRIPTION The STV9556 is a triple-channel video amplifier designed in a 120V-high voltage technology and able to drive in DC-coupling mode the 3 cathodes of a CRT monitor. The STV9556 supports PICTURE BOOST applications where video amplitude up to 50V or ORDER CODE: STV9556 PIN CONNECTIONS 11 10 9 8 7 6 5 4 3 2 1 OUT1 OUT2 OUT3 GNDP VDD GNDS GNDA IN3 VCC IN2 IN1 Version 4.1 September 2003 1/24 1 Table of Contents 1 BLOCK DIAGRAM . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 2 PIN DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 3 ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 4 THERMAL DATA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 5 ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 6 THEORY OF OPERATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 6.1 General . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 6.2 Output voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 7 POWER DISSIPATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 8 TYPICAL PERFORMANCE CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 9 INTERNAL SCHEMATICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 10 APPLICATION HINTS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 10.1 How to choose the high supply voltage value (VDD) in DC coupling mode . . . . . . . . . . 12 10.2 Arcing Protection: schematics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 10.3 Arcing protection: layout and decoupling . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 10.4 Video response optimization: schematics in DC-coupling mode . . . . . . . . . . . . . . . . . . . 14 10.5 Video response optimization: outputs networks . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 10.6 Video response optimization: inputs networks . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 10.7 Video response optimization: layout and decoupling . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 10.8 AC - Coupling mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 10.9 Stand-by mode, spot suppression . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 10.10 Conclusion . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 11 PACKAGE MECHANICAL DATA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 2 2/24 2 STV9556 1 BLOCK DIAGRAM OUT1 GNDP 11 8 OUT2 10 OUT3 9 STV9556 VDD GNDP VDD GNDP VDD 7 VCC 3 VREF 6 GNDS 2 1 5 IN1 GNDA 2 4 IN2 IN3 PIN DESCRIPTION Pin Name Function 1 IN1 Video Input (channel 1) 2 IN2 Video Input (channel 2) 3 VCC Low Supply Voltage 4 IN3 Video Input (channel 3) 5 GNDA Ground Analog 6 GNDS Ground Substrat 7 VDD 8 GNDP High Supply Voltage Ground Power 9 OUT3 Video output (channel 3) 10 OUT2 Video output (channel 2) 11 OUT1 VIdeo output (channel 1) 3/24 3 STV9556 3 ABSOLUTE MAXIMUM RATINGS Symbol 4 Value Unit VDD High supply voltage 120 V VCC Low supply voltage 16.5 V VESD ESD susceptibility Human Body Model (100pF discharged through 1.5KΩ) EIAJ norm (200pF discharged through 0Ω) 2 300 kV V IOD Output source current (pulsed < 50µs) 80 mA IOG Output sink current (pulsed < 50µs) 80 mA VIN Max Maximum Input Voltage VCC + 0.3 V VIN Min Minimum Input Voltage - 0.5 V TJ Junction Temperature 150 °C TSTG Storage Temperature -20 + 150 °C THERMAL DATA Symbol 4/24 3 Parameter Value Unit Rth (j-c) Junction-Case Thermal Resistance (Max.) Parameter 3 °C/W Rth (j-a) Junction-Ambient Thermal Resistance (Typ.) 35 °C/W STV9556 5 ELECTRICAL CHARACTERISTICS Symbol Parameter Test Conditions Min. Typ Max Unit SUPPLY parameters (VCC = 12V, VDD = 110V, Tamb = 25 °C, unless otherwise specified) VDD High supply voltage 20 110 115 V VCC Low supply voltage 10 12 15 V IDD VDD supply current VOUT = 50V 25 mA IDDS VDD stand-by supply current VCC : switched off (<1.5V) VOUT: low (Note 1) 60 µA ICC VCC supply current VOUT = 50V 60 mA STATIC parameters (VCC = 12V, VDD = 110V, Tamb = 25 °C) VOUT dVOUT/dVDD dVOUT/dT DC output voltage VIN = 1.90 V High voltage supply rejection VOUT = 50V 77 0.5 80 83 % V Output voltage drift versus temperature VOUT = 80V 15 mV/°C Output voltage matching versus temperature (Note 2) VOUT = 80V 1 mV/°C Video input resistor VOUT = 50V 2 kΩ VSATH Output saturation voltage to supply I0 =-60mA (Note 3) VDD - 6.5 V VSATL Output saturation voltage to GND I0 =60mA (Note 3) 11 V d∆VOUT/dT RIN G Video Gain VOUT = 50V 20 LE Linearity error 17 V<VOUT<VDD-15 V 3 VREF Internal voltage reference 5.6 8 % V Note 1: The STV9556 goes into stand-by mode when Vcc is switched off (<1.5V). In stand-by mode, Vout is set to low level. Note 2: Matching measured between each channel. Note 3: Pulsed current width < 50µs 5/24 3 STV9556 ELECTRICAL CHARACTERISTICS (continued) Symbol Parameter Test Conditions Min. Typ Max Unit DYNAMIC parameters (see Figure 1) tR Rise time VDC=50V, ∆V=40VPP 7.2 ns tF Fall time VDC=50V, ∆V=40VPP 8.2 ns 5 % OSR Overshoot, white to black transition OSF Overshoot, black to white transition ∆G Low frequency gain matching (Note 4) 0 VDC = 50V, f=1MHz % 5 % BW Bandwidth at -3dB VDC=50V, ∆V=20VPP 50 MHz tSET 2.5% Settling time VDC=50V, ∆V=40VPP 15 ns CTL Low frequency crosstalk VDC=50V, ∆V=20VPP f = 1 MHz 50 dB CTH High frequency crosstalk VDC=50V, ∆V=20VPP f = 20MHz 32 dB VDC=50V, ∆V=60VPP 10 ns Overshoot white to black or black to white VDC=50V, ∆V=60VPP transition 9 % DYNAMIC parameter in PICTURE BOOST condition (Note 5) tPB OSPB Rise/fall time Note 4: Matching measured between each channel. Note 5: PICTURE BOOST condition (video amplitude at 50V or above) is used in some applications when displaying still picture or moving video. In this condition the high level of contrast improves the pictures quality at the expense of the video performances (tR, tF and Overshoot) which are slightly deteriorated. Figure 1. AC test circuit VCC 50Ω 12V 110V 3 7 VDD OUT RP = 200 Ω 1 11 IN 8 VREF STV9556 6/24 3 VDC CL=8pF GNDP 5 GNDA ∆V STV9556 6 6.1 THEORY OF OPERATION General The STV9556 is a three-channel video amplifier supplied by a low supply voltage: VCC (typ.12V) and a high supply voltage: VDD (up to 115V). The high values of VDD supplying the amplifier output stage allow direct control of the CRT cathodes (DC coupling mode). In DC coupling mode, the application schematic is very simple and only a few external components are needed to drive the cathodes. In particular, there is no need of the DC-restore circuitry which is used in classical AC coupling applications. The output voltage range is wide enough (Figure 2) to provide simultaneously : – Cut-off adjustment (typ. 25V) – Video contrast (typ. up to 40V), – Brightness (with the remaining voltage range). In normal operation, the output video signal must remain inside the linear region whatever the cut-off, brightness and contrast adjustments are. Figure 2. Output signal, level adjustments VDD (A) Top Non-Linear Region 15V (B) Cut-off Adjust. (25V Typ.) Linear region (C) Brightness Adjust. (10V Typ.) Blanking pulse (D) Contrast Adjust. (40V Typ.) Video Signal (E) Bottom Non-Linear Region 17V GND 7/24 3 STV9556 6.2 Output voltage A very simplified schematic of each STV9556 channel is shown in Figure 3. The feedback network of each channel is integrated with a typical built-in voltage gain of G=20 (40k/2k). The output voltage VOUT is given by the following formula: VOUT = (G+1) x VREF - (G x VIN) for G = 20 and VREF = 5.6V, we have VOUT = 117.6 - 20 x VIN Figure 3. Simplified schematic of one channel VDD 40k 2k - IN + VREF GNDA 8/24 GNDP OUT STV9556 7 POWER DISSIPATION The total power dissipation is the sum of the static DC and the dynamic dissipation: PTOT = PSTAT + PDYN. The static DC power dissipation is approximately: PSTAT = VDD x IDD + VCC x ICC The dynamic dissipation is, in the worst case (1 pixel On/ 1 pixel Off pattern): PDYN = 3 VDD x CL x VOUT(PP) x f x K (see Note 6) where f is the video frequency and K the ratio between the active line and the total horizontal line duration. Example: for VDD = 110V, VCC = 12V, IDD = 25mA, ICC = 60mA, VOUT = 40 VPP, f = 40MHz, CL = 8pF and K = 0.72. We have: PSTAT = 3.47W and PDYN = 3.04W Therefore: PTOT = 6.51W. Note 6: This worst thermal case must only be considered for TJmax calculation. Nevertheless, during the average life of the circuit, the conditions are closer to the white picture conditions. 9/24 STV9556 8 TYPICAL PERFORMANCE CHARACTERISTICS VDD=110V, VCC=12V, CL=8pF, RP=200Ω, ∆V=40VPP, unless otherwise specified - see Figure 1 Figure 4. STV9556 pulse response Figure 5. V OUT versus VIN 7.2 overshoot = 5% 120 100 Vout (V) 80 60 40 20 0 8.2 overshoot = 0% 0 1 2 3 4 5 6 Vin (V) Figure 6. Power dissipation vs frequency Figure 7. Speed versus temperature 8.00 Vdd=110V 9 6.00 Vdd=100 4.00 Tf 8.5 5.00 Speed (ns) Power dissipation (W) 7.00 Vdd=90 3.00 8 Tr 7.5 2.00 7 1.00 50 60 70 80 Case Temperature (°C) 0.00 10 20 30 Frequency (MHz) (72% active time) 40 100 50 Figure 8. Speed versus offset Figure 9. Speed versus load capacitance 13 STV9556 Speed vs Offset (Vdc) 10 12 11 Speed (ns) 9 Speed (ns) 90 8 Tf 7 10 Tf 9 Tr 8 Tr 7 6 40 45 50 55 Offset (Vdc) 60 65 70 6 8 10 12 14 Load capacitor (pF) 10/24 16 18 20 STV9556 9 INTERNAL SCHEMATICS Figure 10. RGB inputs Figure 11. RGB outputs VDD VCC OUT IN pins 1, 2, 4 pins 9, 10, 11 GNDS GNDS Figure 12. VDD Figure 13. VCC VCC VDD GNDS GNDS Figure 14. GNDP Figure 15. GNDA GNDA GNDP GNDS GNDS 11/24 STV9556 10 APPLICATION HINTS 10.1 How to choose the high supply voltage value (VDD) in DC coupling mode The VDD high supply voltage must be chosen carefully. It must be high enough to provide the necessary video adjustment but set to minimum value to avoid unecessary power dissipation. Example (see Figure 2): The following example shows how the optimum VDD voltage value is determined: – Cut-off adjustment range (B) : 25V – Max contrast (D) : 40V Case 1: 10V Brightness (C) adjusted by the preamplifier : VDD = A + B + C + D + E VDD = 15V + 25V + 10V + 40V + 17V = 107V Case 2: 10V Brightness (C) adjusted by the G1 anode: VDD = A + B + D + E VDD = 15V + 25V + 40V + 17V = 97V 10.2 Arcing Protection: schematics As the amplifier outputs are connected to the CRT cathodes, special attention must be given to protect them against possible arcing inside the CRT. Protection must be considered when starting the design of the video CRT board. It should always be implemented before starting to adjust the dynamic video response of the system. The arcing network that we recommend (see Figure 16) provides efficient protection without deteriorating the amplifier video performances. The total resistance between the amplifier and the CRT cathode (R10+R11) protects the device against overvoltages. We recommend to use R10+R11 > 200 Ω. Spark gaps are strongly recommended for arcing protection. 12/24 STV9556 Figure 16. Arcing protection network (one channel) VDD R19(**) C12(*) 100nF/250V 33-40Ω VDD C24 4.7µF/150V C18 100nF D12 FDH400 OUT L1 R10 STV9556 0.33µH 110Ω/0.5W C29(***) 0.22µF GNDS GNDA D13 FDH400 R11 A CRT 110Ω/0.5W F1 Spark gap 200V B GNDP R29(***) 1-10Ω (*): To be connected as close as possible to the device (**): R19 must be mandatorily used (***): Ground separation network 10.3 Arcing protection: layout and decoupling Several layout precautions have to be considered to get the optimum arcing protection: Sparkgap grounding: when an arc occurs, the energy must flow through the CRT ground without reaching the amplifier. This is obtained by connecting the sparkgap grounding (point B) to the CRT ground (socket) via a wide/short trace. Conversely the point B must be connected to the amplifier ground via a longer/narrower trace. Grounding separation: In order to set apart the amplifer ground and CRT ground, the R29/C29 network (Figure 16) can be used. Amplifier grounding: The 3 grounds GNDS, GNDA and GNDP must be connected together as close as possible to the device. 13/24 STV9556 10.4 Video response optimization: schematics in DC-coupling mode The dynamic video response is optimized by carefully designing the supply decoupling of the video board (see Section 10.7), the tracks (see Section 10.7), then by adjusting the input/output component network (see Section 10.5). For dynamic measurements such as rise/fall time and bandwidth, a 8pF load is used (total load including the parasitic capacitance of the PC board and CRT Socket). When used in kit with the STV921x preamplifier from ST, the preamplifier bandwidth register (BW, register 13) must be set to minimum (o dec) for an application with t R/tF>5.5ns. Figure 17. Video response optimization for one channel - DC coupling application C11 4.7µF C10(*) 100nF C24 4.7µF C12(*) 100nF R19(***) VCC Reference Input Network #1 IN OUT R1(**) 51Ω C2 10pF VDD 33-40Ω STV9556 C1 1.5nF STV921x VDD - + VREF OUT R10 L1 R11 CRT 110Ω 0.33µH 110Ω GNDS GNDA GNDP Caution: For Application with Tr/Tf>5.5ns, the PreAmplifier bandwidth register (BW, Register 13) must be set to minimum value (0 dec) (*): To be connected as close as possible to the device (**): R1 must be not be higher than 100Ω (***): R19 must be mandatorily used 2 other Input Networks (Network #2 and #3 below) can be used in replacement of the reference Input Network #1. See Application note AN1510 for complete description. Input Network #2 Input Network #3 L1 0.33µH IN R1 82Ω 14/24 C2 10pF IN R1 33Ω C2 15pF STV9556 10.5 Video response optimization: outputs networks The output network (R10/L1/R11) is used to adjust the amplifier video performances. Once R10 and R11 resistors are set to protect the application against arcing (R10 + R11>200Ω), it is possible to increase the bandwidth by increasing L1. 10.6 Video response optimization: inputs networks The input network also plays an important role in the device dynamic behaviour. We recommend to use the reference input network #1, which is described in Figure 17, but 2 other networks (#2 and #3) can be used to better match the required performances and the video board layout. Refer to the application note referenced AN1510 for the complete description of these input networks. 10.7 Video response optimization: layout and decoupling The decoupling of VCC and VDD through good quality HF capacitors (respectively C10 and C12) close to the device is necessary to improve the dynamic performance of the video signal. Careful attention has to be given to the three output channels of the amplifier. Capacitor: The parasitic capacitive load on the amplifier outputs must be as small as possible. Figure 9 from Section 8 clearly shows the deterioration of the tR/tF when the capacitive load increases. Reducing this capacitive load is achieved by moving away the output tracks from the other tracks (especially ground) and by using thin tracks (<0.5mm), see Figure 17. Cross talk: Output and input tracks must be set apart. The STV9556 pin-out allows the easy separation of input and output tracks on opposite sides of the amplifier (see Figure 21). Length: Connection between amplifier output and cathode must be as short and direct as possible. 15/24 STV9556 10.8 AC - Coupling mode The STV9556 can be used in AC-Coupling mode in kit with the TDA9207/9212 preamplifier from ST. As for the DC-coupling mode, the STV9556 drives perfectly the video signal in PICTURE BOOST conditions. A typical schematic is given on the Figure 18 below. Figure 18. Video response optimization for one channel - AC coupling application C11 4.7µF C10(*) 100nF C24 4.7µF C12(*) 100nF R19(***) VDD VCC Reference Input Network #1 (****) STV9556 C1 1.5nF TDA9207 R1(**) 51Ω C2 10pF C OUT IN OUT VDD 33-40Ω R10 - L1 C1 R11 1µF 110Ω CRT + 110Ω 0.33µH VREF GNDS Vrestore GNDA GNDP Cut-off DC Restore circuitry Caution: For Application with Tr/Tf>5.5ns, the PreAmplifier bandwidth register (BW, Register 13) must be set to minimum value (0 dec) (*): To be connected as close as possible to the device (**): R1 must be not be higher than 100Ω (***): R19 must be mandatorily used (****): Input Networks #2 and #3 can be used as well The advantage of such an architecture is to use smaller VDD and therefore to have smaller power consumption. This is due to the fact that the STV9556 provides only the video signal and not the cut-off adjustment. The disadvantage is to have an application with more components (DC restore circuitry). Note that it is mandatory to keep the output video signal (point C) inside the linear area of the amplifier (from 17V to VDD - 15V). 16/24 STV9556 10.9 Stand-by mode, spot suppression The usual way to set a monitor in stand-by mode is to switch-off the Vcc (12V). The STV9556 has an extremely low power consumption (I DDS = 60µA when VCC<1.5V) in stand-by mode and the outputs are set to low level (white picture). To avoid the display of a spot effect during the switch-off phase, it is necessary to adjust the G1 circuitry (Resistors Rx and Cx, see Figure 19) to pull the G1 voltage to low value for a long enough period of time. Figure 19. Stand-by mode, spot effect +80V Cathode 0V Case #1: Low Rx.Cx A spot might appear during the switch-off phase -30V G1 Case #2: High Rx.Cx No spot effect -120V EHT (27kV) Typical G1 generator circuitry G1 R1 Cx -120V Rx -30V 17/24 STV9556 10.10 Conclusion Video response is always a compromise between several parameters. For example, the rise/fall time improvement leads to the overshoot deterioration. The recommended way to optimize the video response is: 1 To set R10+R11 for arcing protection (min. 200 Ω) 2. To adjust R20 and R10+R11. Increasing their value increases the tR/tF values and decrease the overshoot 3. To adjust L1 Increasing L1 speeds up the device but increases the overshoot. 4. To adjust the input network for the final dynamic tunning (e.g.: critical damping) We recommend our customers to use the schematic shown on Figure 23 as a starting point for the video board and then to apply the optimization they need. 18/24 STV9556 Figure 20. STV9556/9555/9553 + TDA9210/STV9211 + STV9936S/P DC-coupling demonstration board: Silk Screen and Trace 19/24 STV9556 Figure 21. Outputs trace (from figure 19) Figure 22. CRT socket trace (from figure 19) 20/24 3.3V 100µF/25V C32 L5 1µH C28 100nF HFLY R41 100Ω VS R39 100Ω SCL R35 100Ω R38 100Ω SDA video J1 U3 VS SCL SDA 14 15 16 TEST GOUT DVSS BOUT DVDD FBLK 10 11 12 AVDD 13 VCO RP AVSS D8 R10 75Ω STV9936S/P R45 15kΩ AVdd R34 330Ω R33 330Ω R32 330Ω Sync J17 7 6 5 4 3 2 1 100µF/25V 100nF L4 1µH VS HS HFLY HEATER G1 3.3V C22 100nF C6 100nF C37 R36 330Ω IN2 ABL IN1 U1 10 9 8 7 6 Power J16 1 2 3 4 5 6 7 8 C26 18 19 20 100pF C16 C27 47µF/25V ZD1 47µF/25V J10 I2C 1 2 3 4 3V0 R37 51Ω 5V 3.3V 47µF/25V 47µF/25V C15 100pF C12 SDA 100pF 10pF C25 C27 5V SCL C13 C24 10pF ABL BLK 110V R17 51Ω C36 1.5nF R13 51Ω 5V R19 2.7kΩ R47 100Ω 11 C23 C33 1.5nF 10pF 51Ω C31 1.5nF R9 C8 12V 47µF/25V 8V R11 2.7Ω R40 100Ω R21 2.7kΩ 12 13 14 C5 100nF 15 12V 8V FBLK SCL SDA OUT3 GNDP OUT2 16 VCCP 17 OUT1 HS/CLP BLK TDA9210 OSD3 OSD2 OSD1 VCCA GNDA 5 IN3 C9 100nF 4 GNDL C4 100nF 3 2 C3 100nF 1 R4 2.7Ω C2 R43 1MΩ Vco R44 5.6kΩ C34 10nF Rp R16 2.7Ω R12 15Ω 1N4148 D5 R8 15Ω 1N4148 D4 5V R2 15Ω ABL R46 5.6kΩ C35 10nF 1N4148 1N4148 D6 5V Red R5 75Ω Green 1N4148 D3 R3 75Ω 8 OVDD ROUT 9 7 6 5 4 HFLY 3 2 1 1 2 3 4 5 6 1N4148 Blue D1 5V C7 4 2 1 100nF In3 In2 In1 Out1 HS1 R28 0Ω R6 R14 R22 110Ω/0.25W 9 C21 10nF/250V optional L1 4.7µF/160V R7 FDH400 J7 GND FDH400 D13 FDH400 D9 R15 R23 G1 RK B G R D11 Heater F1 200V BK F4 200V GK F2 200V 4.7nF/1kV C20 100nF J8 G2 12 GND 1 GND 30Ω/0.5W R31 C19 4.7nF/2kV CRT small neck C14 9 H2 F3 1.5Ω Wednesday October 3, 2001 Version 1.4 Rev. C EVALCRT52/STV955x demoboard (AB25) STMicroelectronics Monitor Business Unit - Video application CMG - Imaging and Display Division (IDD) 12, rue Jules Horowitz - B.P. 217 38019 Grenoble cedex - FRANCE 1N4004 150Ω/0.25W R27 0.33µH 110Ω/0.25W L3 0.33µH 110Ω/0.25W D12 FDH400 FDH400 L2 D7 D10 110V 0.33µH 110Ω/0.25W 110Ω/0.25W 110V 10 110V C18 R29 39Ω FDH400 D2 110V 110Ω/0.25W 11 10nF/250V C10 110V Out3 Out2 STV9556 U2 RadAB20 1 2 3 5 C1 GNDA 100pF GNDS 6 3 Vcc 7 Vdd GNDP 8 R25 100Ω 10 H1 BLK 5 G1 R1 100Ω 7 G2 HS STV9556 Figure 23.STV9556/55/53 + STV9936S/P + TDA9210/STV9211 DC-coupling demo-board schematic 21/24 STV9556 11 PACKAGE MECHANICAL DATA 11 PIN - CLIPWATT V1 H3 H2 S A C Shaded area ewposed from plastic body Typical 30 µm H1 V1 V2 L3 V1 V1 R2 L2 R L1 R1 V R3 D R3 R3 M1 M LEAD#1 E Dimensions 22/24 B G G1 F F1 Millimeters Min. Typ. Inches Max. Min. Typ. Max. A 2.95 3 3.05 0.116 0.118 0.12 B 0.95 1 1.05 0.037 0.039 0.041 C - 0.15 - - 0.006 - D 1.3 1.5 1.7 0.051 0.059 0.061 E 0.49 0.515 0.55 0.0.019 0.02 0.021 F 0.78 0.8 0.86 0.03 0.031 0.034 F1 - 0.05 0.1 - 0.002 0.004 (6) G 1.6 1.7 1.8 0.063 0.067 0.071 G1 16.9 17 17.1 0.665 0.669 0.673 H1 - 12 - - 0.472 - H2 18.55 18.6 18.65 0.73 0.732 0.734 H3 19.9 20 20.1 0.783 0.787 0.791 (5) L 17.7 17.9 18.1 0.696 0.704 0.712 L1 14.35 14.55 14.65 0.564 0.572 0.576 L2 10.9 11 11.1 0.429 0.433 0.437(5) L3 5.4 5.5 5.6 0.212 0.216 0.22 M 2.34 2.54 2.74 0.092 0.1 0.107 M1 2.34 2.54 2.74 0.092 0.1 0.107 R 1.45 - - 0.057 - - STV9556 Dimensions Millimeters Inches Min. Typ. Max. Min. Typ. Max. R1 3.2 3.3 3.4 0.126 0.13 0.134 R2 - 0.3 - - 0.012 - R3 - 0.5 - - 0.019 - S 0.65 0.7 0.75 0.025 0.027 0.029 V 10deg. 10deg. V1 5deg. 5deg. V2 75deg. 75deg. Note 5: “H3 and L2” do not include mold flash or protrusions Mold flash or protrusions shall not exceed 0.15mm per side. Note 6: No intrusions allowed inwards the leads Critical dimensions: Lead split (M1) Total length (L) 23/24 STV9556 Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. The ST logo is a trademark of STMicroelectronics. © 2002 STMicroelectronics - All Rights Reserved Purchase of I2C Components of STMicroelectronics, conveys a license under the Philips I2C Patent. Rights to use these components in a I2C system, is granted provided that the system conforms to the I2C Standard Specifications as defined by Philips. STMicroelectronics GROUP OF COMPANIES Australia - Brazil - Canada - China - Finland - France - Germany - Hong-Kong - Italy - Japan - Malaysia - Malta - Morocco Singapore- The Netherlands - Singapore - Spain - Sweden - Switzerland - United Kingdom - U.S.A. http://www.st.com 24/24 4