@vic LINEAR INTEGRATED CIRCUIT AV2030 14W HI-FI AUDIO AMPLIFIER DESCRIPTION The AVIC AV2030 is a monolithic audio power amplifier integrated circuit. 1 TO-220B FEATURES *Very low external component required. *High current output and high operating voltage. *Low harmonic and crossover distortion. *Built-in Over temperature protection. *Short circuit protection between all pins. *Safety Operating Area for output transistors. 1 TO-220-5 PIN CONFIGURATIONS 1 2 3 4 5 Non inverting input Inverting input -VS Output +VS ABSOLUTE MAXIMUM RATINGS(Ta=25°C) PARAMETER SYMBOL VALUE UNIT Supply Voltage Input Voltage Differential Input Voltage Peak Output Current(internally limited) Total Power Dissipation at Tcase=90°C Storage Temperature Junction Temperature Vs Vi Vdi Io Ptot Tstg Tj +-18 Vs +-15 3.5 20 -40~+150 -40~+150 V V V A W °C °C ELECTRICAL CHARACTERISTICS(Refer to the test circuit, Vs =+-16V,Ta=25°C) PARAMETER SYMBOL Supply Voltage Quiescent Drain Current Input Bias Current Input Offset Voltage Input Offset Current Vs Id Ib Vos Ios TEST CONDITIONS MIN TYP MAX UNIT 40 +-18 60 V mA 0.2 +-2 +-20 2 +-20 +-200 µA MV NA +-6 Vs=+-18v QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 (Continued) d=0.5%,Gv=30dB f=40 to 15,000Hz Output Power Po RL=4Ω RL=8Ω 12 8 14 9 W W 18 W d=10%,Gv=30dB f=1KHz Power Bandwidth Open Loop Voltage Gain B Gvo Closed Loop Voltage Gain Distortion Gvc Input Noise Voltage Input Noise Current Input Resistance(pin 1) Supply Voltage Rejection Thermal Shut-Down Junction Temperature d eN iN Ri SVR Tj RL=4Ω RL=8Ω Po=12W,RL=4Ω, Gv=30dB f=1kHz 11 10~140,000 90 29.5 30 30 .5 dB 0.2 0.5 % 0.1 0.5 % 10 200 0.5 3 80 5 µV pA MΩ 40 50 dB 145 °C Po=0.1 to 12W,RL=4Ω f=40 to 15,000Hz, Gv=30dB Po=0.1 to 8W,RL=8Ω f=40 to 15,000Hz, Gv=30dB B= 22Hz to 22kHz B= 22Hz to 22kHz RL=4Ω,Gv=30dB Rg=22kΩ,fripple=100Hz, Vripple=0.5Veff W Hz dB QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 TEST CIRCUIT +Vs Vi C5 100 µF C1 1 µF C3 100nF D1 1N4001 1 R3 22kΩ 5 UTC TDA2030 2 4 3 C8 R5 R4 1Ω RL D1 R1 22kΩ 1N4001 R3 680Ω C2 22 µF C6 100 µF C4 C7 100nF 220nF -Vs APPLICATION CIRCUIT +Vs Vi C1 1 µF C5 220 µF C3 100nF D1 1N4001 1 R3 22kΩ 5 UTC TDA2030 2 4 3 R3 680Ω C2 22 µF R1 13kΩ R4 1Ω D1 1N4001 C6 100 µF RL C4 C7 100nF 220nF -Vs QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 TYPICAL PERFORMANCE CHARACTERISTICS Fig.2 Open loop frequency response 140 Gv (dB) 180 Phase 100 90 60 0 Phase Fig.3 Output power vs. Supply voltage Po (W) 24 Gv=26dB d=0.5% f=40 to 15kHz 20 RL=4Ω 16 RL=8Ω Gain 20 12 -20 8 -60 1 10 2 10 3 10 4 10 5 10 6 10 4 7 10 24 Frequency (Hz) Fig.4 Total harmonic distortion vs. output power d (%) d (%) 40 44 Vs (V) Po (W) 2 10 Vs=32V Po=4W RL=4Ω Gv=26dB 0 10 Vs=38V RL=8Ω f=15kHz -1 10 36 1 10 Gv=26dB 0 10 32 Fig.5 Two tone CCIF intermodulation distortion 2 10 1 10 28 Order (2f1-f2) -1 10 Vs=32V RL=4Ω Order (2f2-f1) f=1kHz -2 10 -2 10 -1 10 0 10 1 10 Po (W) 2 10 -2 10 1 10 30 Vs=+-15V RL=8Ω 25 3 10 4 10 5 10 Frequency (Hz) Fig.7 Maximum allowable power dissipation vs. ambient temperture Fig.6 Large signal frequency response Vo (Vp-p) 2 10 30 Ptot (W) 25 Vs=+-15V RL=4Ω 20 20 15 10 10 5 1 10 2 10 3 10 Frequency (kHz) 4 10 he a Rt tsin h= k 4° ha C/ vin he W g at Rt sink h= h 8°C avin /W g ink a ts he te ini g inf vin ha /W ink ats 5°C he ty=2 R 15 5 -50 0 50 100 150 200 Tamb (°C) QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 UTC TDA2030 R4 3.3kΩ C4 10 µF C8 2200 µF 4 3 R5 30kΩ BD907 R8 1Ω RL=4Ω C2 22 µF 5 2 R2 56kΩ BD908 1N4001 1 R3 56kΩ C5 220 µF /40V R6 1.5Ω 1N4001 R1 56kΩ C6 0.22 µF Vi C1 2.2 µF C3 0.22 µF +Vs R7 1.5Ω C7 0.22 µF Fig. 8 Single supply high power amplifier(UTC TDA2030+BD908/BD907) TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8 PARAMETER Supply Voltage Quiescent Drain Current Output Power SYMBOL Vs Id Po Voltage Gain Slew Rate Total Harmonic Distortion Input Sensitivity Gv SR d Signal to Noise Ratio S/N Vi TEST CONDITIONS MIN Vs=36V TYP MAX UNIT 36 50 44 V mA d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=39V d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=36V d=0.5%,f=1kHz, RL=4Ω,Vs=39V 35 d=0.5%,RL=4Ω f=1kHz,Vs=36V f=1kHz 35 Po=20W,f=1kHz Po=20W,f=40Hz to 15kHz Gv=20dB,Po=20W, f=1kHz,RL=4Ω RL=4Ω,Rg=10kΩ B=curve A,Po=25W RL=4Ω,Rg=10kΩ B=curve A,Po=25W 28 W 44 19.5 20 8 0.02 0.05 890 108 100 20.5 dB V/µsec % % mV dB QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 TYPICAL PERFORMANCE CHARACTERISTICS Fig. 10 Output power vs. supply voltage Fig. 11 Total harmonic distortion vs. output power Po (W) d (%) Vs=36V RL=4Ω Gv=20dB 45 0 10 35 25 -1 10 f=15kHz 15 f=1kHz 5 24 28 32 34 36 Vs (V) 40 -2 10 -1 10 Fig. 12 Output power vs. Input level 0 10 1 10 Po (W) Fig. 13 Power dissipation vs. output power Ptot (W) Po (W) 20 20 Complete Amplifier Gv=26dB 15 15 Gv=20dB 10 10 5 5 0 100 250 400 550 700 Vi (mV) BD908/ BD907 UTC TDA2030 0 0 8 16 24 32 Po (W) QW-R107-004,B LINEAR INTEGRATED CIRCUIT AV2030 +Vs Vi C5 100 µF C1 1 µF C3 100nF D1 1N4001 1 R3 22kΩ 5 UTC TDA2030 2 4 3 C8 R5 R4 1Ω D2 R1 22kΩ 1N4001 R3 680Ω C6 100 µF C2 22 µF RL C4 C7 100nF 220nF -Vs Fig. 14 Typical amplifier with split power supply Vs+ C6 100 µ F 1 5 UTC TDA2030 4 R1 22kΩ 2 3 C8 IN R3 22kΩ R8 1Ω µF 0.22 C1 220 µ F C7 100nF C4 22 µ F RL 8Ω R4 680Ω R7 22kΩ 5 UTC TDA2030 4 2 Vs- 3 R5 22kΩ C9 1 R2 22kΩ µF 0.22 @vic R9 1Ω C5 22 µ F C2 100 µ F C3 100nF R6 680Ω Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V) QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficulty of precise design due to variable loudspeaker impedance. Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19. The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or low-pass filters. In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100Ω,while that of the Pin (+) is very high, which is also what was wanted. Fig. 18 Power distribution vs. frequency Fig. 19 Active power filter 100 C1 C2 C3 IEC/DIN NOISE SPECTRUM FOR SPEAKER TESTING 80 Vs+ Morden Music Spectrum RL 60 R1 R2 R3 3.3kΩ Vs- 40 100Ω 20 0 1 10 2 10 3 10 4 10 5 10 QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2KΩ,R2=5.6KΩ,R3=33KΩ. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4Ω to 8Ω). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers. 22kΩ 2 33nF 680Ω 22kΩ 1N4001 1.5Ω 1 18nF 22kΩ 5 BD908 4 UTC TDA2030 3 2200 µF 1Ω 100 µF 0.22 µF 1N4001 1.5Ω 3.3kΩ 100Ω BD907 4Ω 1 µF 0.22 µF IN 0.22 µF 2200 µF Vs+ Low-pass 300Hz Woofer Vs+ Band-pass 300Hz to 3kHz 0.22 µF 1N4001 6.8kΩ 3.3nF 2 5 3 1N4001 100 µF 100Ω Vs+ 0.22 µF 1N4001 100 µF 4 3 1N4001 8Ω 1Ω 2 5 UTC TDA2030 0.22 µF 1 22kΩ 12kΩ 0.1 µF 22kΩ 47 µF 2.2kΩ 100Ω 100 µF 22kΩ 0.1 µF Midrange 2.2kΩ High-pass 3kHz Vs+ 220 µF 4 UTC TDA2030 8Ω 1 1Ω 22kΩ 18nF 22kΩ 0.22 µF 0.1 µF 3.3kΩ 0.1 µF High-pass 3kHz Tweeter QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 MUSICAL INSTRUMENTS AMPLIFIERS Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms. TRANSIENT INTER-MODULATION DISTORTION(TIM) Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation(TIM situation.)The best known Fig.21 High power active box for musical instrument Fig.22 Overshoot phenomenon in feedback amplifiers FEEDBACK PATH 20 to 40W Amplifier 汕V4 INPUT V1 PRE AMPLIFIER V2 V3 POWER AMPLIFIER OUTPUT V4 20 to 40W Amplifier V1 20 to 40W Amplifier V2 20 to 40W Amplifier V3 V4 method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in the other direction the opposite is true. QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 Input Signal SR(V/µs) m2 m1 Filtered Output Siganal Fig.23 20kHz sawtooth waveform Fig.24 Inverting sawtooth waveform The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured, the TIM can be found very simply from: VOUT TIM = * 100 Vsawtooth Fig. 25 TIM distortion Vs. Output Power Fig. 26 TIM design diagram(fc=30kHz) 2 10 1 10 TIM(%) UTC2030A BD908/907 Gv=26dB Vs=36V RL=4Ω RC Filter fc=30kHz 1 10 1% =1 % =0 . TI M TI 0 10 M RC Filter fc=30kHz TI -1 10 M =0 .0 1% 0 10 SR(V/米s) -2 10 -1 10 0 10 1 10 Po(W) 2 10 -1 10 -1 10 0 10 1 10 Vo(Vp-p) 2 10 In Fig.25 The experimental results are shown for the 30W amplifier using the UTC2030A as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an effective way to reduce TIM. The Diagram of Fig.26 originated by SGS can be used to find the Slew-Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM. Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver. POWER SUPPLY Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage. QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load. The UTC2030(Vsmax=44V) is particularly suitable for substitution of the standard IC power amplifiers(with Vsmax=36V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.27. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy. In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater in case than for the case of regulated supplied, with space saving and cost reduction. Fig.27 DC characteristics of 50W non-regulated supply Ripple (Vp-p) Vo(V) 36 34 Ripple 4 32 220V Vo 2 3300 µF 30 Vout 0 28 0 Mains(220V) +20% +15% +10% — -10% -15% -20% 0.4 0.8 1.2 1.6 2.0 Io(A) Secondary Voltage 28.8V 27.6V 26.4V 24V 21.6V 20.4V 19.2V DC Output Voltage(Vo) Io=0 43.2V 41.4V 39.6V 36.2V 32.4V 30.6V 28.8V Io=0.1A 42V 40.3V 38.5V 35V 31.5V 29.8V 28V Io=1A 37.5V 35.8V 34.2V 31V 27.8V 26V 24.3 QW-R107-004,B @vic LINEAR INTEGRATED CIRCUIT AV2030 SHORT CIRCUIT PROTECTION The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground. THERMAL SHUT-DOWN The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported since the Tj can not be higher than 150°C 2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption. APPLICATION SUGGESTION The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used. The following table can help the designer. COMPONENT RECOMMENDED VALUE PURPOSE LARGE THAN RECOMMENDED VALUE LARGE THAN RECOMMENDED VALUE R1 22KΩ Increase of Gain Decrease of Gain R2 680Ω Decrease of Gain Increase of Gain R3 22KΩ 1Ω R5 ≈3R2 Increase of input impedance Danger of oscillation at high frequencies with inductive loads. Poor high frequencies attenuation Decrease of input impedance R4 Closed loop gaon setting. Closed loop gaon setting. Non inverting input biasing Frequency stacility C1 1µF C2 22µF C3,C4 0.1µF C5,C6 100µF C7 C8 0.22µF ≈1/(2π*B*R1) D1,D2 1N4001 Upper frequency cutoff Input DC decoupling Inverting DC decoupling Supply voltage bypass Supply voltage bypass Frequency stability Upper frequency cutoff To protect the device against output voltage spikes. Dange of oscillation Increase of low frequencies cutoff Increase of low frequencies cutoff Dange of oscillation Dange of oscillation smaller bandwidth Larger bandwidth Larger bandwidth QW-R107-004,B