ACT4455 Rev 2, 21-Nov-12 36V/5A Step Down DC/DC Converter FEATURES APPLICATIONS • • • • • 7.5V to 36V Input Voltage 40V Input Voltage Surge Up to 5A Output Current • Automotive Industry • Dual-Output Car Charger • LCD-TV Up to 12V Output Voltage GENERAL DESCRIPTION Dual Outputs with Independent Over Current Protection • • • • • • • 7.5% Accurate Over Current Protection (OCP) • • • • • • Auto Recovery into Full Load after Faults ACT4455 is a wide input voltage step-down DC/DC converter with high-side MOSFET integrated. It provides up to 5A continuous output current at 200kHz switching frequency. The converter can be configured as single output or dual outputs with independent over current protection. The converter achieves high efficiency and excellent load and line regulation. The converter enters into hiccup and sleeping mode and the converter power consumption is nearly zero when output is overloaded or shorted to ground. Other protection features includes cycle-by-cycle current limit, under voltage protection and thermal shutdown. The device is available in SOP8-EP package. Integrated 45mΩ High Side Power FET 90% Efficiency at Heavy Load Internal 3ms Soft Startup Low Standby Input Current Sleeping Mode at OCP, OTP and SCP Zero Input and Output Currents at Over Current and Short Circuit Protection Output Cord Voltage Drop Compensation Stable with Low ESR Ceramic Output Capacitors Internal Cycle-by-Cycle Current Control Programmable Over Current Setting SOP-8EP Package Efficiency vs. Load current Output current (V) ACT4455-001 100 VIN = 12V 90 80 VIN = 24V VIN = 32V 70 60 50 0 1000 2000 3000 4000 5000 Efficiency (%) Innovative PowerTM -1- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 ORDERING INFORMATION PART NUMBER OPERATION TEMPERATURE RANGE ACT4455YH-T -40°C to 85°C PACKAGE PINS PACKING SOP-8EP 8 TAPE & REEL PIN CONFIGURATION PIN DESCRIPTIONS PIN NAME DESCRIPTION 1 CS1 The output current of VOUT1 is sensed by this pin. When the voltage on this pin reaches 116mV for 750µs, the IC shuts down for 2.5 seconds before initiating a restartup. 2 SW Switch Output. Connect this pin to the switching end of the external inductor. 3 HSB High Side Bias. This pin acts as the positive rail for the high-side switch’s gate driver. Connect a 22nF-100nF capacitor between HSB and SW pins. 4 GND Ground. 5 COMP 6 FB Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive voltage divider from the output voltage. The feedback threshold is 0.808V. See Setting the Output Voltage. 7 IN Input Supply. Bypass this pin to GND with a 10µF or greater low ESR capacitor. 8 CS2 Exposed Pad Innovative PowerTM Compensation Node. COMP is used to compensate the voltage regulation loop. The output current of VOUT2 is sensed by this pin. When the voltage on this pin reaches 116mV for 750µs, the IC shuts down for 2.5 seconds and then restarts. Exposed Pad. Connect this pad to thick copper plane via copper vias. -2- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 ABSOLUTE MAXIMUM RATINGSc PARAMETER VALUE UNIT -0.3 to 44 V SW to GND -0.3 to VIN + 0.3 V HSB to GND VSW - 0.3 to VSW + 7 V -0.3 to + 6 V 50 °C/W Operating Junction Temperature -40 to 150 °C Storage Junction Temperature -55 to 150 °C 300 °C IN to GND FB, CS1, CS2, COMP to GND Junction to Ambient Thermal Resistance Lead Temperature (Soldering 10 sec.) c: Do not exceed these limits to prevent damage to the device. Exposure to absolute maximum rating conditions for long periods may affect device reliability. Innovative PowerTM -3- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 ELECTRICAL CHARACTERISTICS (VIN = 12V, TA = 25°C, unless otherwise specified.) PARAMETER SYMBOL Feedback Voltage VFB Error Amplifier Voltage Gain AEA Error Amplifier Transconductance GEA Over Voltage Protection Threshold VOVP TEST CONDITIONS 7.5V ≤ VIN ≤ 40V MIN TYP MAX UNIT 798 808 818 mV ∆ICOMP = ± 10µA 4000 V/V 650 µA/V 41 V Max E/A Source Current ISRCMAX VFB = 0.5V 120 µA Max E/A Sink Current ISINKMAX VFB = 1.0V 120 µA High-Side Switch ON-Resistance RDS(ON)1 At 25°C 38 mΩ Low-Side Switch ON-Resistance RDS(ON)2 5 Ω Maximum Duty Cycle DMAX 80 % Switching Frequency FSW Upper Switch Current Limit ILIM 180 Duty Cycle = 65% 200 220 kHz 6.5 A COMP to Current Limit Transconductance GCOMP 5 A/V Minimum on Time TON_MIN 250 ns Input Under Voltage Lockout Threshold VIN_Rise VIN Rising Input Under Voltage Lockout Hysteresis VIN_Falling VIN Falling 6.75 7 7.25 V 650 mV 3.0 ms Internal Soft Startup Time TSS CS1 reference voltage VCS1 113 116 119 mV CS2 reference voltage VCS2 113 116 119 mV Frequency Foldback Threshold Cord Compensation VFB_Foldback VIN = 12V, RFB1=200k, IOUT = 5A Thermal Shutdown Innovative PowerTM -4- 0.65 V 0.35 V 150 °C www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 FUNCTIONAL BLOCK DIAGRAM FUNCTIONAL DESCRIPTION FB is lower than the reference voltage, COMP tends to go higher to increase current to the output. Operation As seen in Functional Block Diagram, the ACT4455 is a current mode controlled regulator. The EA output voltage (COMP voltage) is proportional to the peak inductor current. Over Current and Short Circuit Protection CS pins are connected to the high side of current sensing resistors to prevent output over current. With independent CS1 and CS2 pins, two output currents are detected. If the voltage at either CS pins exceeds 116mV for more than 750µs. The converter shuts down and goes into sleeping mode. A new soft startup is triggered after 2.5s. If the fault condition is un-cleared, the converter shuts down again until over current condition is cleared. With this long-waiting-time hiccup mode, the power consumption at over loading or outputs short is reduced to nearly zero. A switching cycle starts when the rising edge of the Oscillator clock output causes the High-Side Power Switch to turn on and the Low-Side Power Switch to turn off. With the SW side of the inductor now connected to IN, the inductor current ramps up to store energy. The inductor current level is measured by the Current Sense Amplifier and added to the Oscillator ramp signal. If the resulting summation is higher than the COMP voltage, the output of the PWM Comparator goes high. When this happens or when Oscillator clock output goes low, the High-Side Power Switch turns off and the inductor freewheels through the schottky diode causing the inductor current to decrease and magnetic energy to be transferred to output. This state continues until the cycle starts again. The High-Side Power Switch is driven by logic using HSB as the positive rail. This pin is charged to VSW + 5V when the Low-Side Power Switch turns on. The Comp voltage is the integration of the error between FB input and internal 0.808V reference. If Innovative PowerTM Thermal Shutdown The ACT4455 shuts down when its junction temperature exceeds 150°C. The converter triggers a soft-start when the temperature has dropped by 10°C. The soft-restart avoids output over voltage at thermal hiccup. -5- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 APPLICATIONS INFORMATION With a selected inductor value the peak-to-peak inductor current is estimated as: Output Voltage Setting Figure 1: ILPK _ PK = Output Voltage Setting VOUT × (VIN _VOUT ) L × VIN × fSW (4) The peak inductor current is estimated as: I LPK = I LOADMAX + 1 I 2 LPK _ (5) PK The selected inductor should not saturate at ILPK. The maximum output current is calculated as: 1 IOUTMAX = I LIM _ I LPK PK (6) 2 ILIM is the internal current limit, which is typically 6.5A, as shown in Electrical Characteristics Table. _ Figure 1 shows the connections for setting output voltage. Select the proper ratio of the feedback resistors RFB1 and RFB2 based on output voltage. Typically, use RFB2 ≈ 10kΩ determine RFB1 from the following equation: ⎛ V OUT ⎞ R FB 1 = R FB 2 ⎜ −1⎟ 0 . 808 V ⎝ ⎠ the two the and Input Capacitor The input capacitor needs to be carefully selected to maintain sufficiently low ripple at the supply input of the converter. A low ESR capacitor is highly recommended. Since large current flows in and out of this capacitor during switching, its ESR also affects efficiency. (1) Over Current Protection Setting The output over current threshold is calculated by: IOCP1 = IOCP 2 = 116 mV / RSENSE The input capacitance needs to be higher than 10µF. The best choice is the ceramic type, however, low ESR tantalum or electrolytic types may also be used provided that the RMS ripple current rating is higher than 50% of the output current. The input capacitor should be placed close to the IN and G pins of the IC, with the shortest traces possible. In the case of tantalum or electrolytic types, they can be further away if a small parallel 0.1µF ceramic capacitor is placed right next to the IC. (2) It is recommended that 1% or 0.5% high-accuracy current sensing resistor is selected to achieve highaccuracy over current protection. Two over current protection thresholds can be different based on different current sensing resistance. Inductor Selection The inductor maintains a continuous current to the output load. This inductor current has a ripple that is dependent on the inductance value: Output Capacitor Higher inductance reduces the peak-to-peak ripple current. The trade off for high inductance value is the increase in inductor core size and series resistance, and the reduction in current handling capability. In general, select an inductance value L based on ripple current requirement: VRIPPLE = IOUTMAX K RIPPLE RESR + L= × (V ) VOUT IN VOUT VIN fSW ILOADMAX K RIPPLE _ The output capacitor also needs to have low ESR to keep low output voltage ripple. The output ripple voltage is: 2 28 × fSW LC OUT (7) Where IOUTMAX is the maximum output current, KRIPPLE is the ripple factor, RESR is the ESR of the output capacitor, fSW is the switching frequency, L is the inductor value, and COUT is the output capacitance. In the case of ceramic output capacitors, RESR is very small and does not contribute to the ripple. Therefore, a lower capacitance value can be used for ceramic type. In the case of tantalum or electrolytic capacitors, the ripple is dominated by RESR multiplied by the ripple (3) where VIN is the input voltage, VOUT is the output voltage, fSW is the switching frequency, ILOADMAX is the maximum load current, and KRIPPLE is the ripple factor. Typically, choose KRIPPLE = 30% to correspond to the peak-to-peak ripple current being 30% of the maximum load current. Innovative PowerTM VIN -6- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 APPLICATIONS INFORMATION CONT’D current. In that case, the output capacitor is chosen to have sufficiently low ESR. For ceramic output capacitor, typically choose a capacitance of about 22µF. For tantalum or electrolytic capacitors, choose a capacitor with less than 50mΩ ESR. Rectifier Diode Use a Schottky diode as the rectifier to conduct current when the High-Side Power Switch is off. The Schottky diode must have current rating higher than the maximum output current and a reverse voltage rating higher than the maximum input voltage. Innovative PowerTM -7- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 STABILITY COMPENSATION If RCOMP is limited to 15kΩ, then the actual cross over frequency is 6.36 / (VOUTCOUT). Therefore: Figure 2: Stability Compensation CCOMP = 6.67 ×10−6VOUTCOUT c: CCOMP2 is needed only for high ESR output capacitor ⎛ 1.1 × 10 −6 ⎞ RESRCOUT ≥ Min⎜⎜ ,0.012 × VOUT ⎟⎟ C OUT ⎝ ⎠ The feedback loop of the IC is stabilized by the components at the COMP pin, as shown in Figure 2. The DC loop gain of the system is determined by the following equation: 0 . 808 V AVEA G COMP I OUT G EA 2 π AVEA C COMP (8) The second pole P2 is the output pole: fP 2 fP 3 = (11) The following steps should be used to compensate the IC: STEP 1. Set the cross over frequency at 1/10 of the switching frequency via RCOMP: R COMP = = 0 . 48 × 10 VOUT C OUT (Ω) 3 . 18 × 10 R COMP Innovative PowerTM COUT RCOMP CCOMP CCOMP2c 2.5V 47μF SP CAP 5.6kΩ 5.6nF 3.3V 47μF SP CAP 7.5kΩ 4.7nF None 5V 47μF SP CAP 11kΩ 3.3nF None None 2.5V 680μF/6.3V/30mΩ 15kΩ 3.3nF 220pF 3.3V 680μF/6.3V/30mΩ 15kΩ 3.3nF 220pF 5V 680μF/6.3V/30mΩ 15kΩ 4.7nF 220pF Output Cable Resistance Compensation To compensate for resistive voltage drop across the charger's output cable, the ACT4455 integrates a simple, user-programmable cable voltage drop compensation using the impedance at the FB pin. Use the curve in Figure 3 to choose the proper feedback resistance values for cable compensation. RFB1 is the high side resistor of voltage divider. (13) STEP 2. Set the zero fZ1 at 1/4 of the cross over frequency. If RCOMP is less than 15kΩ, the equation for CCOMP is: C COMP = VOUT c: CCOMP2 is needed for high ESR output capacitor. 2 πVOUT C OUT f SW 10 G EA GCOMP × 0 .808 V 8 (17) Typical Compensation for Different Output Voltages and Output Capacitors (12) 2πR COMP C COMP2 COUT RESRCOUT RCOMP Table 1: And finally, the third pole is due to RCOMP and CCOMP2 (if CCOMP2 is used): 1 CCOMP 2 = Table 1 shows some calculated results based on the compensation method above. (10) The first zero Z1 is due to RCOMP and CCOMP: 1 fZ 1 = 2 π R COMP C COMP1 (16) Though CCOMP2 is unnecessary when the output capacitor has sufficiently low ESR, a small value CCOMP2 such as 100pF may improve stability against PCB layout parasitic effects. (9) I OUT = 2 π V OUT C OUT (Ω) And the proper value for CCOMP2 is: The dominant pole P1 is due to CCOMP: fP1 = (15) STEP 3. If the output capacitor’s ESR is high enough to cause a zero at lower than 4 times the cross over frequency, an additional compensation capacitor CCOMP2 is required. The condition for using CCOMP2 is: c AVDC = (F) −5 (F) (14) -8- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 STABILITY COMPENSATION CONT’D In the case of high RFB1 used, the frequency compensation needs to be adjusted correspondingly. As show in Figure 4, adding a capacitor in paralled with RFB1 or increasing the compensation capacitance at COMP pin helps the system stability. single point for best noise immunity. Connect exposed pad to power ground copper area with copper and vias. 4) Use copper plane for power GND for best heat dissipation and noise immunity. 5) Place feedback resistor close to FB pin. Figure 3: 6) Use short trace connecting HSB-CHSB-SW loop Cable Compensation at Various Resistor Divider Values 7) SW pad is noisy node switching from VIN to GND. It should be isolated away from the rest of circuit for good EMI and low noise operation. Delta Output Voltage vs. Output Current Delta Output Voltage (V) 0.5 R 0.4 1 FB = 0k 30 0k 27 0k 24 k 00 =2 v ACT4455-002 0.6 = B1 RF = 1 R FB 0.3 R FB 0.2 1 R FB1 R FB1 0.1 50k =1 = 10 0k RFB1 = 51k 0 0 1000 2000 3000 4000 5000 Output Current (mA) Figure 4: Frequency Compensation for High RFB1 PC Board Layout Guidance When laying out the printed circuit board, the following checklist should be used to ensure proper operation of the IC. 1) Arrange the power components to reduce the AC loop size consisting of CIN, IN pin, SW pin and the schottky diode. 2) Place input decoupling ceramic capacitor CIN as close to IN pin as possible. CIN is connected power GND with vias or short and wide path. 3) Return FB, COMP and ISET to signal GND pin, and connect the signal GND to power GND at a Innovative PowerTM -9- www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 Figure 5: Typical Application Circuit for 5V/4.2A Dual-output Car Charger Table 2: BOM List for 5V/4.2A Dual-output Car Charger ITEM REFERENCE DESCRIPTION MANUFACTURER QTY 1 U1 IC ACT4455YH, SOP-8EP Active-Semi 1 2 C1 Capacitor, Electrolytic, 150µF/50V, 8×8mm Koshin 1 3 C2 Capacitor, Electrolytic, 680µF/10V, 8×11.5mm Koshin 1 4 C3 Capacitor, Ceramic, 10µF/50V, 1206, SMD Murata, TDK 1 5 C4 Capacitor, Ceramic, 4.7nF/25V, 0603, SMD Murata, TDK 1 6 C5 Capacitor, Ceramic, 220pF/25V, 0603, SMD (Optional) Murata, TDK 1 7 C6 Capacitor, Ceramic, 2.2nF/25V, 0603, SMD Murata, TDK 1 8 C7 Capacitor, Ceramic, 1000pF/25V, 0603, SMD (Optional) Murata, TDK 1 9 C8 Capacitor, Ceramic, 100pF/25V, 0603, SMD (Optional) Murata, TDK 1 10 C9 Capacitor, Ceramic, 2200pF/25V, 0805, SMD Murata, TDK 1 11 C10 Capacitor, Ceramic, 2.2µF/16V, 0603, SMD Murata, TDK 1 12 L1 Inductor, 18µH, 5A, 20%, DIP Electronic-Magnetics 1 13 D1 Diode, Schottky, 45V/10A, V10L45 Vishay 1 14 R1, R2 Chip Resistor, 50mΩ, 1206, 1% Murata, TDK 2 15 R3 Chip Resistor, 9.7kΩ, 0603, 1% Murata, TDK 1 16 R4 Chip Resistor, 51kΩ, 0603, 1% Murata, TDK 1 17 R5 Chip Resistor, 15kΩ, 0603, 5% Murata, TDK 1 18 R6 Chip Resistor, 5.1Ω, 1206, 5% Murata, TDK 1 Innovative PowerTM - 10 - www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 TYPICAL PERFORMANCE CHARACTERISTICS (Circuit of Figure 7, RCS1 = RCS2 = 50mΩ, L = 18µH, CIN = 150µF, COUT = 680µF, TA = 25°C, unless otherwise specified.) Efficiency vs. Load current 90 80 Switching Frequency (kHz) VIN = 12V VIN = 24V VIN = 32V 70 60 50 ACT4455-004 Output current (V) Switching Frequency vs. Input Voltage 250 ACT4455-002 100 200 150 100 50 0 0 1000 2000 3000 4000 5 5000 10 15 Efficiency (%) 30 40 35 PK Current limit (mA) 200 150 100 50 ACT4455-006 9 ACT4455-005 Switching Frequency (kHz) 25 Maximum Peak Current vs. Duty Cycle Switching Frequency vs. Feedback Voltage 250 8.5 8 7.5 7 6.5 6 0 0 0.2 0.4 0.6 0.8 1 0.15 0.25 0.35 Feedback Voltage (mV) 0.45 0.55 0.65 0.75 0.85 Duty cycle Input Current vs. Input Voltage at No Load Standby Current vs. Input Voltage 900 12 Input Current (mA) 920 ACT4455-008 14 ACT4455-007 940 Standby Current (µA) 20 Input Voltage (V) 880 860 840 10 8 6 4 2 820 0 800 5 10 15 20 25 30 35 5 40 15 20 25 30 35 40 Input Voltage (V) Input Voltage (V) Innovative PowerTM 10 - 11 - www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 TYPICAL PERFORMANCE CHARACTERISTICS CONT’D (Circuit of Figure 7, RCS1 = RCS2 = 50mΩ, L = 18µH, CIN = 150µF, COUT = 680µF, TA = 25°C, unless otherwise specified.) Input Current at Output Short Output Vcs vs. Temperature 0.18 0.17 0.8 Vcs (V) Input Current (mA) 1 ACT4455-010 ACT4455-009 1.2 0.6 0.16 VCS1 0.15 0.4 0.14 VCS2 0.2 0.13 0 5 10 15 20 25 30 35 -25 40 0 25 Input Voltage (V) 75 100 125 150 SW vs. Output Ripples Start Up ACT4455-012 ACT4455-011 VVINOUT = 12V = 5V IR = 1A OUT LORD = 1.5Ω IISET = 2A VIN = 12V 50 Temperature (°C) VIN = 12V IOUT = 0A CH1 CH1 CH2 CH2 CH1: Ripper, 50mV/div CH2: SW, 10V/div TIME: 2µs/div CH1: VOUT, 2V/div CH2: VIN, 5V/div TIME: 1ms/div SW vs. Output Ripples ACT4455-014 CH1 ACT4455-013 VIN = 12V IOUT = 4.2A Load Step Waveforms VIN = 12V IOUT1 = 0.08-2.1A IOUT2 = 0A CH1 CH2 CH2 CH1: Ripper, 50mV/div CH2: SW, 10V/div TIME: 2µs/div Innovative PowerTM CH1: VOUT Ripple, 200mV/div CH2: IOUT, 2A/div TIME: 400µs/div - 12 - www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 TYPICAL PERFORMANCE CHARACTERISTICS CONT’D (Circuit of Figure 7, RCS1 = RCS2 = 50mΩ, L = 18µH, CIN = 150µF, COUT = 680µF, TA = 25°C, unless otherwise specified.) Load Step Waveforms Short Circuit CH1 VIN = 12V IOUT1 = 2.1A IOUT2 = 0A CH1 ACT4455-016 ACT4455-015 VIN = 12V IOUT1 = 0-2.1A IOUT2 = 2.1A CH2 CH2 CH3 CH1: VOUT Ripper, 200mV/div CH2: IOUT, 2A/div TIME: 400µs/div CH1: VOUT, 5V/div CH2: IL, 2A/div CH3: SW, 10V/div TIME: 400µs/div Short Circuit Short Circuit Recovery ACT4455-018 VIN = 12V IOUT1 = 2.1A IOUT2 = 2.1A ACT4455-017 CH1 VIN = 12V IOUT1 = 2.1A IOUT2 = 0A CH1 CH2 CH2 CH3 CH3 CH1: VOUT, 5V/div CH2: IL, 2A/div CH3: SW, 10V/div TIME: 400µs/div CH1: VOUT, 2V/div CH2: IL, 2A/div CH3: SW, 10V/div TIME: 1ms/div Hiccup Mode Short Circuit Recovery VIN = 12V IOUT1 = 2.1A IOUT2 = 2.1A CH1 ACT4455-020 ACT4455-019 VIN = 12V IOUT1 = 2.1A IOUT2 = 2.1A CH1 CH2 CH2 CH2 CH1: VOUT, 2V/div CH2: IL, 2A/div CH3: SW, 10V/div TIME: 1ms/div Innovative PowerTM CH1: VOUT, 5V/div CH2: SW, 5V/div TIME: 1s/div - 13 - www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 TYPICAL PERFORMANCE CHARACTERISTICS CONT’D (Circuit of Figure 7, RCS1 = RCS2 = 50mΩ, L = 18µH, CIN = 150µF, COUT = 680µF, TA = 25°C, unless otherwise specified.) Input Surge VIN = 24V VOUT = 5V IISET = 2.1A ACT4455-022 CH1 Input Surge ACT4455-021 VIN = 8V-40V IOUT1 = 2.1A IOUT2 = 0 A VIN = 8V-40V IOUT1 = 2.1A IOUT2 = 2.1A CH1 CH2 CH2 CH1: VIN, 10V/div CH2: VOUT Ripper, 200mV/div TIME: 10ms/div Innovative PowerTM CH1: VIN, 10V/div CH2: VOUT Ripper, 200mV/div TIME: 10ms/div - 14 - www.active-semi.com Copyright © 2012 Active-Semi, Inc. ACT4455 Rev 2, 21-Nov-12 PACKAGE OUTLINE SOP-8EP PACKAGE OUTLINE AND DIMENSIONS SYMBOL DIMENSION IN MILLIMETERS DIMENSION IN INCHES MIN MAX MIN MAX A 1.350 1.700 0.053 0.067 A1 0.000 0.100 0.000 0.004 A2 1.350 1.550 0.053 0.061 b 0.330 0.510 0.013 0.020 c 0.170 0.250 0.007 0.010 D 4.700 5.100 0.185 0.200 D1 3.202 3.402 0.126 0.134 E 3.800 4.000 0.150 0.157 E1 5.800 6.200 0.228 0.244 E2 2.313 2.513 0.091 0.099 e 1.270 TYP 0.050 TYP L 0.400 1.270 0.016 0.050 θ 0° 8° 0° 8° Active-Semi, Inc. reserves the right to modify the circuitry or specifications without notice. Users should evaluate each product to make sure that it is suitable for their applications. Active-Semi products are not intended or authorized for use as critical components in life-support devices or systems. Active-Semi, Inc. does not assume any liability arising out of the use of any product or circuit described in this datasheet, nor does it convey any patent license. Active-Semi and its logo are trademarks of Active-Semi, Inc. For more information on this and other products, contact firstname.lastname@example.org or visit http://www.active-semi.com. is a registered trademark of Active-Semi. Innovative PowerTM - 15 - www.active-semi.com Copyright © 2012 Active-Semi, Inc.