LM4941 1.25 Watt Fully Differential Audio Power Amplifier With RF Suppression and Shutdown General Description Key Specifications The LM4941 is a fully differential audio power amplifier primarily designed for demanding applications in mobile phones and other portable communication device applications. It is capable of delivering 1.25 watts of continuous average power to a 8Ω load with less than 1% distortion (THD+N) from a 5VDC power supply. The LM4941 does not require output coupling capacitors or bootstrap capacitors, and therefore is ideally suited for mobile phone and other low voltage applications where minimal power consumption is a primary requirement. The LM4941 also features proprietary internal circuitry that suppresses the coupling of RF signals into the chip. This is important because certain types of RF signals (such as GSM) can couple into audio amplifiers in such a way that part of the signal is heard through the speaker. The RF suppression circuitry in the LM4941 makes it well-suited for portable applications in which strong RF signals generated by an antenna from or a cellular phone or other portable electronic device may couple audibly into the amplifier. Other features include a low-power consumption shutdown mode, internal thermal shutdown protection, and advanced pop & click circuitry. j Improved PSRR at 217Hz j Power Output at 5.0V @ 1% THD (8Ω) j Power Output at 3.3V @ 1% THD j Shutdown Current 95dB (typ) 1.25W (typ) 550mW (typ) 0.1µA (typ) Features n Improved RF suppression, by up to 20dB over previous designs in selected applications n Fully differential amplification n Available in space-saving micro SMD package n Ultra low current shutdown mode n Can drive capacitive loads up to 100pF n Improved pop & click circuitry eliminates noises during turn-on and turn-off transitions n 2.4 - 5.5V operation n No output coupling capacitors, snubber networks or bootstrap capacitors required Applications n Mobile phones n PDAs n Portable electronic devices Typical Application 20170303 FIGURE 1. Typical Audio Amplifier Application Circuit Boomer ® is a registered trademark of National Semiconductor Corporation. © 2006 National Semiconductor Corporation DS201703 www.national.com LM4941 1.25 Watt Fully Differential Audio Power Amplifier With RF Suppression and Shutdown June 2006 LM4941 Connection Diagrams 9 Bump micro SMD Package 20170304 Top View Order Number LM4941TM See NS Package Number TMD09AAA micro SMD Marking 20170302 Top View X = Date Code V = Die Traceability G = Boomer Family H6 = LM4941TM www.national.com 2 Thermal Resistance If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. Soldering Information Supply Voltage θJA (TM) 100˚C/W See AN-1187 6.0V Storage Temperature −65˚C to +150˚C Operating Ratings −0.3V to VDD +0.3V Input Voltage Power Dissipation (Note 3) Internally Limited ESD Susceptibility (Note 4) 2000V ESD Susceptibility (Note 5) Junction Temperature Temperature Range TMIN ≤ TA ≤ TMAX −40˚C ≤ TA ≤ 85˚C 2.4V ≤ VDD ≤ 5.5V Supply Voltage 200V 150˚C Electrical Characteristics VDD = 5V (Notes 1, 2) The following specifications apply for VDD = 5V, AV = 1, and 8Ω load unless otherwise specified. Limits apply for TA = 25˚C. LM4941 Symbol Parameter Conditions Typical Limit (Note 6) (Note 7) 1.7 1.7 2.5 Units (Limits) IDD Quiescent Power Supply Current VIN = 0V, no load VIN = 0V, RL = 8Ω ISD Shutdown Current VSHUTDOWN = GND 0.1 1 µA (max) THD = 1% (max); f = 1 kHz RL = 8Ω 1.25 1.1 W (min) THD = 10% (max); f = 1 kHz RL = 8Ω 1.54 W Po = .7 Wrms; f = 1kHz .04 % Po Output Power THD+N Total Harmonic Distortion + Noise mA (max) Vripple = 200mV sine p-p PSRR Power Supply Rejection Ratio f = 217Hz (Note 8) 95 f = 1kHz (Note 8) 90 70 dB (min) f = 217Hz, VCM = 200mVpp 70 f = 20Hz–20kHz , VCM = 200mVpp 70 dB VIN = 0V 2 mV dB CMRR Common-Mode Rejection Ratio VOS Output Offset VSDIH Shutdown Voltage Input High 1.4 V (min) VSDIL Shutdown Voltage Input Low 0.4 V (max) SNR Signal-to-Noise Ratio PO = 1W, f = 1kHz 108 dB TWU Wake-up Time from Shutdown Cbypass = 1µF 12 ms Electrical Characteristics VDD = 3V (Notes 1, 2) The following specifications apply for VDD = 3V, AV = 1, and 8Ω load unless otherwise specified. Limits apply for TA = 25˚C. LM4941 Symbol Parameter Conditions Typical Limit (Note 6) (Note 7) 1.6 1.6 2.4 1 Units (Limits) IDD Quiescent Power Supply Current VIN = 0V, no load VIN = 0V, RL = 8Ω ISD Shutdown Current VSHUTDOWN = GND 0.1 THD = 1% (max); f = 1 kHz RL = 8Ω 0.43 W THD = 10% (max); f = 1 kHz RL = 8Ω 0.54 W Po = 0.25Wrms; f = 1kHz .05 % Po THD+N Output Power Total Harmonic Distortion + Noise mA (max) µA (max) Vripple = 200mV sine p-p PSRR Power Supply Rejection Ratio f = 217Hz (Note 8) 95 f = 1kHz (Note 8) 90 3 dB www.national.com LM4941 Absolute Maximum Ratings (Note 2) LM4941 Electrical Characteristics VDD = 3V (Notes 1, 2) The following specifications apply for VDD = 3V, AV = 1, and 8Ω load unless otherwise specified. Limits apply for TA = 25˚C. (Continued) LM4941 Symbol Parameter Conditions Typical Limit (Note 6) (Note 7) Units (Limits) CMRR Common-Mode Rejection Ratio f = 217Hz, VCM = 200mVpp 70 dB VOS Output Offset VIN = 0V 2 mV (max) VSDIH Shutdown Voltage Input High VSDIL Shutdown Voltage Input Low TWU Wake-up Time from Shutdown Cbypass 8 1.4 V (min) 0.4 V (max) ms Note 1: All voltages are measured with respect to the ground pin, unless otherwise specified. Note 2: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is functional, but do not guarantee specific performance limits. Electrical Characteristics state DC and AC electrical specifications under particular test conditions which guarantee specific performance limits. This assumes that the device is within the Operating Ratings. Specifications are not guaranteed for parameters where no limit is given, however, the typical value is a good indication of device performance. Note 3: The maximum power dissipation must be derated at elevated temperatures and is dictated by TJMAX, θJA, and the ambient temperature TA. The maximum allowable power dissipation is PDMAX = (TJMAX – TA) / θJA or the number given in Absolute Maximum Ratings, whichever is lower. For the LM4941, see power derating curve for additional information. Note 4: Human body model, 100pF discharged through a 1.5kΩ resistor. Note 5: Machine Model, 220pF – 240pF discharged through all pins. Note 6: Typicals are measured at 25˚C and represent the parametric norm. Note 7: Limits are guaranteed to National’s AOQL (Average Outgoing Quality Level). Note 8: 10Ω terminated input. Note 9: Data taken with BW = 80kHz and AV = 1/1 except where specified. External Components Description (Figure 1) Components Functional Description 1. CS Supply bypass capacitor which provides power supply filtering. Refer to the Power Supply Bypassing section for information concerning proper placement and selection of the supply bypass capacitor. 2. CB Bypass pin capacitor which provides half-supply filtering. Refer to the section, Proper Selection of External Components, for information concerning proper placement and selection of CB. 3. Ri Inverting input resistance which sets the closed-loop gain in conjunction with Rf. 4. Rf Internal feedback resistance which sets the closed-loop gain in conjunction with Ri. www.national.com 4 LM4941 Typical Performance Characteristics (Note 9) THD+N vs Output Power VDD = 3V, RL = 8Ω, f = 1kHz THD+N vs Output Power VDD = 5V, RL = 8Ω, f = 1kHz 20170305 20170306 THD+N vs Frequency VDD = 3V, RL = 8Ω, PO = 250mW THD+N vs Frequency VDD = 5V, RL = 8Ω, PO = 700mW 20170307 20170308 PSRR vs Frequency VDD = 3V, RL = 8Ω, Inputs terminated PSRR vs Frequency VDD = 5V, RL = 8Ω, Inputs terminated 20170309 20170310 5 www.national.com LM4941 Typical Performance Characteristics (Note 9) CMRR vs Frequency VDD = 5V, RL = 8Ω (Continued) CMRR vs Frequency VDD = 3V, RL = 8Ω 20170311 20170312 PSRR vs Common Mode Voltage VDD = 3V, RL = 8Ω, f = 217Hz PSRR vs Common Mode Voltage VDD = 5V, RL = 8Ω, f = 217Hz 20170324 20170323 Power Dissipation vs Output Power VDD = 3V, RL = 8Ω Power Dissipation vs Output Power VDD = 5V, RL = 8Ω 20170315 www.national.com 20170316 6 (Note 9) Output Power vs Supply Voltage RL = 8Ω, Top-THD+N = 10%; Bot-THD+N = 1% LM4941 Typical Performance Characteristics (Continued) Clipping Voltage vs Supply Voltage 20170317 20170318 Output Power vs Load Resistance Top-VDD = 5V, 10% THD+N, Topmid-VDD = 5V, 1% THD+N Bot-VDD = 3V, 10% THD+N, Botmid-VDD = 3V, 1% THD+N 20170319 7 www.national.com LM4941 coupling capacitor is not used in a single-ended output configuration, the half-supply bias across the load would result in both increased internal IC power dissipation as well as permanent loudspeaker damage. Further advantages of bridged mode operation specific to fully differential amplifiers like the LM4941 include increased power supply rejection ratio, common-mode noise reduction, and click and pop reduction. Application Information OPTIMIZING RF IMMUNITY The internal circuitry of the LM4941 suppresses the amount of RF signal that is coupled into the chip. However, certain external factors, such as output trace length, output trace orientation, distance between the chip and the antenna, antenna strength, speaker type, and type of RF signal, may affect the RF immunity of the LM4941. In general, the RF immunity of the LM4941 is application specific. Nevertheless, optimal RF immunity can be achieved by using short output traces and increasing the distance between the LM4941 and the antenna. POWER DISSIPATION Power dissipation is a major concern when designing a successful amplifer, whether the amplifier is bridged or single-ended. Equation 2 states the maximum power dissipation point for a single-ended amplifier operating at a given supply voltage and driving a specified output load. DIFFERENTIAL AMPLIFIER EXPLANATION The LM4941 is a fully differential audio amplifier that features differential input and output stages. Internally this is accomplished by two circuits: a differential amplifier and a common mode feedback amplifier that adjusts the output voltages so that the average value remains VDD / 2. When setting the differential gain, the amplifier can be considered to have "halves". Each half uses an input and feedback resistor (Ri1 and RF1) to set its respective closed-loop gain (see Figure 1). With Ri1 = Ri2 and RF1 = RF2, the gain is set at -RF / Ri for each half. This results in a differential gain of AVD = -RF/Ri PDMAX = (VDD)2 / (2π2RL) Single-Ended However, a direct consequence of the increased power delivered to the load by a bridge amplifier is an increase in internal power dissipation versus a single-ended amplifier operating at the same conditions. PDMAX = 4 * (VDD)2 / (2π2RL) Bridge Mode (3) Since the LM4941 has bridged outputs, the maximum internal power dissipation is 4 times that of a single-ended amplifier. Even with this substantial increase in power dissipation, the LM4941 does not require additional heatsinking under most operating conditions and output loading. From Equation 3, assuming a 5V power supply and an 8Ω load, the maximum power dissipation point is 625mW. The maximum power dissipation point obtained from Equation 3 must not be greater than the power dissipation results from Equation 4: (4) PDMAX = (TJMAX - TA) / θJA (1) It is extremely important to match the input resistors to each other, as well as the feedback resistors to each other for best amplifier performance. See the Proper Selection of External Components section for more information. A differential amplifier works in a manner where the difference between the two input signals is amplified. In most applications, input signals will be 180˚ out of phase with each other. The LM4941 can be used, however, as a single ended input amplifier while still retaining its fully differential benefits because it simply amplifies the difference between the inputs. The LM4941’s θJA in an TMD09XXX package is 100˚C/W. Depending on the ambient temperature, TA, of the system surroundings, Equation 4 can be used to find the maximum internal power dissipation supported by the IC packaging. If the result of Equation 3 is greater than that of Equation 4, then either the supply voltage must be decreased, the load impedance increased, the ambient temperature reduced, or the θJA reduced with heatsinking. In many cases, larger traces near the output, VDD, and GND pins can be used to lower the θJA. The larger areas of copper provide a form of heatsinking allowing higher power dissipation. For the typical application of a 5V power supply, with an 8Ω load, the maximum ambient temperature possible without violating the maximum junction temperature is approximately 110˚C provided that device operation is around the maximum power dissipation point. Recall that internal power dissipation is a function of output power. If typical operation is not around the maximum power dissipation point, the LM4941 can operate at higher ambient temperatures. Refer to the Typical Performance Characteristics curves for power dissipation information. All of these applications provide what is known as a "bridged mode" output (bridge-tied-load, BTL). This results in output signals at Vo1 and Vo2 that are 180˚ out of phase with respect to each other. Bridged mode operation is different from the single-ended amplifier configuration that connects the load between the amplifier output and ground. A bridged amplifier design has distinct advantages over the singleended configuration: it provides differential drive to the load, thus doubling maximum possible output swing for a specific supply voltage. Four times the output power is possible compared with a single-ended amplifier under the same conditions. This increase in attainable output power assumes that the amplifier is not current limited or clipped. In order to choose an amplifier’s closed-loop gain without causing excess clipping, please refer to the Audio Power Amplifier Design section. A bridged configuration, such as the one used in the LM4941, also creates a second advantage over singleended amplifiers. Since the differential outputs, Vo1 and Vo2, are biased at half-supply, no net DC voltage exists across the load. This assumes that the input resistor pair and the feedback resistor pair are properly matched (see Proper Selection of External Components). BTL configuration eliminates the output coupling capacitor required in singlesupply, single-ended amplifier configurations. If an output www.national.com (2) POWER SUPPLY BYPASSING As with any power amplifier, proper supply bypassing is critical for low noise performance and high power supply rejection ratio (PSRR). The capacitor location on both the bypass and power supply pins should be as close to the 8 When using DC coupled inputs, special care must be taken to match the values of the input resistors (Ri1 and Ri2) to each other. Because of the balanced nature of differential amplifiers, resistor matching differences can result in net DC currents across the load. This DC current can increase power consumption, internal IC power dissipation, reduce PSRR, and possibly damaging the loudspeaker. The chart below demonstrates this problem by showing the effects of differing values between the feedback resistors while assuming that the input resistors are perfectly matched. The results below apply to the application circuit shown in Figure 1, and assumes that VDD = 5V, RL = 8Ω, and the system has DC coupled inputs tied to ground. (Continued) device as possible. Typical applications employ a 5V regulator with 10µF and 0.1µF bypass capacitors that increase supply stability. This, however, does not eliminate the need for bypassing the supply nodes of the LM4941. The LM4941 will operate without the bypass capacitor CB, although the PSRR may decrease. A 1µF capacitor is recommended for CB. This value maximizes PSRR performance. Lesser values may be used, but PSRR decreases at frequencies below 1kHz. The issue of CB selection is thus dependant upon desired PSRR and click and pop performance as explained in the section Proper Selection of External Components. SHUTDOWN FUNCTION In order to reduce power consumption while not in use, the LM4941 contains shutdown circuitry that is used to turn off the amplifier’s bias circuitry. The device may then be placed into shutdown mode by toggling the Shutdown Select pin to logic low. The trigger point for shutdown is shown as a typical value in the Supply Current vs Shutdown Voltage graphs in the Typical Performance Characteristics section. It is best to switch between ground and supply for maximum performance. While the device may be disabled with shutdown voltages in between ground and supply, the idle current may be greater than the typical value of 0.1µA. In either case, the shutdown pin should be tied to a definite voltage to avoid unwanted state changes. Tolerance Ri1 Ri2 V02 - V01 ILOAD 20% 0.8R 1.2R -0.500V 62.5mA 10% 0.9R 1.1R -0.250V 31.25mA 5% 0.95R 1.05R -0.125V 15.63mA 1% 0.99R 1.01R -0.025V 3.125mA 0 0 0% R R Since the same variations can have a significant effect on PSRR and CMRR performance, it is highly recommended that the input resistors be matched to 1% tolerance or better for best performance. AUDIO POWER AMPLIFIER DESIGN In many applications, a microcontroller or microprocessor output is used to control the shutdown circuitry, which provides a quick, smooth transition to shutdown. Another solution is to use a single-throw switch in conjunction with an external pull-up resistor. This scheme guarantees that the shutdown pin will not float, thus preventing unwanted state changes. Design a 1W/8Ω Audio Amplifier Given: Power Output Load Impedance Input Level Input Impedance PROPER SELECTION OF EXTERNAL COMPONENTS Proper selection of external components in applications using integrated power amplifiers is critical when optimizing device and system performance. Although the LM4941 is tolerant to a variety of external component combinations, consideration of component values must be made when maximizing overall system quality. The LM4941 is unity-gain stable, giving the designer maximum system flexibility. The LM4941 should be used in low closed-loop gain configurations to minimize THD+N values and maximize signal to noise ratio. Low gain configurations require large input signals to obtain a given output power. Input signals equal to or greater than 1Vrms are available from sources such as audio codecs. Please refer to the Audio Power Amplifier Design section for a more complete explanation of proper gain selection. When used in its typical application as a fully differential power amplifier the LM4941 does not require input coupling capacitors for input sources with DC common-mode voltages of less than VDD. Exact allowable input common-mode voltage levels are actually a function of VDD, Ri, and Rf and may be determined by Equation 5: VCMi < (VDD-1.2)*((Rf+(Ri)/(Rf)-VDD*(Ri / 2Rf) (5) -RF / RI = AVD (6) Bandwidth 1Wrms 8Ω 1Vrms 20kΩ 100Hz–20kHz ± 0.25dB A designer must first determine the minimum supply rail to obtain the specified output power. The supply rail can easily be found by extrapolating from the Output Power vs Supply Voltage graphs in the Typical Performance Characteristics section. A second way to determine the minimum supply rail is to calculate the required VOPEAK using Equation 7 and add the dropout voltages. Using this method, the minimum supply voltage is (Vopeak + (VDO TOP + (VDO BOT )), where VDO BOT and VDO TOP are extrapolated from the Dropout Voltage vs Supply Voltage curve in the Typical Performance Characteristics section. (7) Using the Output Power vs Supply Voltage graph for an 8Ω load, the minimum supply rail just about 5V. Extra supply voltage creates headroom that allows the LM4941 to reproduce peaks in excess of 1W without producing audible distortion. At this time, the designer must make sure that the power supply choice along with the output impedance does not violate the conditions explained in the Power Dissipation section. Once the power dissipation equations have been addressed, the required differential gain can be determined from Equation 8. 9 www.national.com LM4941 Application Information LM4941 Application Information (Continued) fH = 20kHz * 5 = 100kHz The high frequency pole is determined by the product of the desired frequency pole, fH , and the differential gain, AVD . With a AVD = 2.83 and fH = 100kHz, the resulting GBWP = 150kHz which is much smaller than the LM4941 GBWP of 10MHz. This figure displays that if a designer has a need to design an amplifier with a higher differential gain, the LM4941 can still be used without running into bandwidth limitations. (8) Rf / Ri = AVD From Equation 7, the minimum AVD is 2.83. A ratio of Rf to Ri of 2.83 gives Ri = 14kΩ. The final design step is to address the bandwidth requirement which must be stated as a single -3dB frequency point. Five times away from a -3dB point is 0.17dB down from passband response which is better than the required ± 0.25dB specified. www.national.com 10 LM4941 Recommended TM Board Layout 20170321 20170322 Recommended TM Board Layout: Top Layer Recommended TM Board Layout: Top Overlay 20170320 Recommended TM Board Layout: Bottom Layer 11 www.national.com LM4941 Revision History www.national.com Rev Date Description 1.0 06/28/06 Initial WEB release. 12 inches (millimeters) unless otherwise noted micro SMD Package Order Number LM4941TM NS Package Number TMD09AAA X1 = 1.25mm X2 = 1.25mm X3 = 0.6mm National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. 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