TI DAC702

®
DAC701
DAC702
DAC703
DAC
701
DAC
702
DAC
703
Monolithic 16-Bit
DIGITAL-TO-ANALOG CONVERTERS
FEATURES
● VOUT AND IOUT MODELS
● HIGH ACCURACY:
Linearity Error ±0.0015% of FSR max
Differential Linearity Error ±0.003% of FSR
max
● MONOTONIC (at 15 bits) OVER FULL
SPECIFICATION TEMPERATURE RANGE
● PIN-COMPATIBLE WITH DAC70, DAC71,
DAC72
DESCRIPTION
Digital inputs are complementary binary coded and
are TTL-, LSTTL-, 54/74C- and 54/74HC-compatible
over the entire temperature range. Outputs of 0 to
+10V, ±10V, 0 to –2mA, and ±1mA are available.
The DAC70X family comprise of complete 16-bit
digital-to-analog converters that includes a precision
buried-zener voltage reference and a low-noise, fastsettling output operational amplifier (voltage output
models), all on one small monolithic chip. A combination of current-switch design techniques accomplishes
not only 15-bit monotonicity over the entire specified
temperature range, but also a maximum end-point
linearity error of ±0.0015% of full-scale range. Total
full-scale gain drift is limited to ±10ppm/°C maximum
(LH and CH grades).
Digital
Inputs
16-Bit
Ladder
Resistor
Network
And
Current
Switches
● DUAL-IN-LINE PLASTIC AND HERMETIC
CERAMIC AND SOIC
These D/A converters are packaged in hermetic 24-pin
ceramic side-brazed or molded plastic. The DIP-packaged parts are pin-compatible with the voltage and
current output DAC71 and DAC72 model families.
The DAC702 is also pin-compatible with the DAC70
model family. In addition, the DAC703 is offered in a
24-pin SOIC package for surface mount applications.
Reference
Circuit
Reference Output
Common
Summing Junction
Output
Voltage Models
Only
Gain Adjust
+V CC
–V CC
V DD
International Airport Industrial Park • Mailing Address: PO Box 11400, Tucson, AZ 85734 • Street Address: 6730 S. Tucson Blvd., Tucson, AZ 85706 • Tel: (520) 746-1111 • Twx: 910-952-1111
Internet: http://www.burr-brown.com/ • FAXLine: (800) 548-6133 (US/Canada Only) • Cable: BBRCORP • Telex: 066-6491 • FAX: (520) 889-1510 • Immediate Product Info: (800) 548-6132
®
© 1983 Burr-Brown Corporation
SBAS143
PDS-494M
1
DAC701, 702, 703
Printed in U.S.A. March, 1998
SPECIFICATIONS
At +25°C and rated power supplies, unless otherwise noted.
DAC702/703J
PARAMETER
MIN
TYP
DAC701/702/703K
MAX
MIN
TYP
DAC701/702/703B, S
MAX
MIN
TYP
MAX
DAC701/702/703L, C
MIN
TYP
MAX
UNITS
✻
Bits
✻
✻
✻
✻
V
V
µA
mA
INPUT
DIGITAL INPUT
Resolution
Digital Inputs (1)
VIH
VIL
IIH, VI = +2.7V
IIL, VI = +0.4V
✻
16
✻
✻
✻
✻
✻
±0.006
✻
±0.003
±0.012
±0.07
±0.05
±0.30
±0.10
+2.4
–1.0
–0.35
+VCC
+0.8
+40
–0.5
±0.0015
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
±0.003
✻
✻
±0.00075 ±0.0015
✻
±0.006
✻
✻
±0.0015
±0.003
% of FSR
±0.003
✻
✻
±0.006
±0.15
✻
±0.0015
±0.05
✻
±0.003
±0.10
✻
✻
✻
✻
✻
✻
✻
% of FSR
%
% of FSR
✻
TRANSFER CHARACTERISTICS
ACCURACY(2)
Linearity Error(4)
Differential Linearity
Error(4)
Differential Linearity
Error at Bipolar Zero
(DAC702/703)(4)
Gain Error(5)
Zero Error(5, 6)
Monotonicity Over Spec.
Temp Range
13
DRIFT (over specification
temperature range)
Total Error Over
Temperature Range
(all models)(7)
Total Full Scale Drift:
DAC701
DAC702/703
Gain Drift (all models)
Zero Drift:
DAC701
DAC702/703
Differential Linearity
Over Temp.(4)
15
Bits
±0.08
✻
±0.15
±0.05
±0.10
✻
✻
% of FSR
±10
±10
±10
±30
✻
✻
✻
±30
±25
±25
±8.5
±7
±7
±18
±15
±15
±6
✻
±5
±13
✻
±10
ppm of FSR/°C
ppm of FSR/°C
ppm/°C
±5
±15
±2.5
✻
±5
±12
±1.5
±4
±3
±10
✻
±2.5
✻
±5
ppm of FSR/°C
ppm of FSR/°C
Linearity Error
Over Temp.(4)
SETTLING TIME (to
±0.003% of FSR)(8)
DAC701/703 (VOUT Models)
Full Scale Step, 2kΩ Load
1LSB Step at
Worst-Case Code(9)
Slew Rate
DAC702 (IOUT Models)
Full Scale Step (2mA),
10 to 100Ω Load
1kΩ Load
✻
14
% of FSR(3)
±0.012
+0.009,
–0.006
✻
+0.006,
–0.003
% of FSR
±0.012
±0.006
✻
±0.003
% of FSR
✻
µs
4
✻
2.5
10
✻
✻
350
1
✻
✻
±10
0 to +10
✻
✻
8
✻
✻
✻
✻
✻
✻
1000
3
µs
V/µs
✻
✻
✻
✻
✻
✻
✻
✻
ns
µs
OUTPUT
VOLTAGE OUTPUT
MODELS
DAC701 (CSB Code)
DAC703 (COB Code)
Output Current
Output Impedance
Short Circuit to
Common Duration
CURRENT OUTPUT
MODELS
DAC702 (COB Code)(10)
Output Impedance(10)
Compliance Voltage
±5
✻
✻
✻
✻
✻
✻
0.15
✻
✻
✻
Indefinite
✻
✻
✻
±1
2.45
±2.5
✻
✻
✻
✻
✻
✻
✻
✻
✻
®
DAC701, 702, 703
2
V
V
mA
Ω
mA
kΩ
V
SPECIFICATIONS (CONT)
At +25°C and rated power supplies, unless otherwise noted.
DAC702/703J
PARAMETER
MIN
REFERENCE VOLTAGE
Voltage
Source Current Available
for External Loads
Temperature Coefficient
Short Circuit to Common
Duration
TYP
DAC701/702/703K
MAX
DAC701/702/703B, S
DAC701/702/703L, C
MIN
TYP
MAX
MIN
TYP
MAX
MIN
TYP
MAX
UNITS
+6.3
+6.0
+6.3
+6.6
+6.24
+6.3
+6.36
✻
✻
✻
V
+2.5
±10
+1.5
✻
✻
✻
✻
✻
✻
±25
±15
✻
✻
✻
mA
ppm/°C
✻
✻
✻
✻
✻
✻
V
V
V
✻
Indefinite
✻
✻
POWER SUPPLY REQUIREMENTS
Voltage: +VCC
–VCC
VDD
Current (No Load):
DAC702
(IOUT Models)
+VCC
–VCC
VDD
DAC701/703
(VOUT Models)
+VCC
–VCC
VDD
Power Dissipation:
(VDD = +5.0V)(11)
DAC702
DAC701/703
Power Supply Rejection:
+VCC
–VCC
VDD
13.5
13.5
+4.5
✻
✻
✻
✻
✻
✻
+25
–25
+8
✻
✻
✻
+30
–30
+8
15
15
+5
16.5
16.5
+16.5
+10
–13
+4
+16
–18
+4
✻
✻
✻
365
530
±0.0015
±0.0015
±0.0001
±0.006
±0.006
±0.001
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
mA
mA
mA
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
✻
mA
mA
mA
✻
✻
790
940
✻
✻
630
780
✻
✻
✻
✻
mW
mW
✻
✻
✻
✻
✻
✻
✻
✻
✻
±0.003
±0.003
✻
✻
✻
✻
✻
✻
✻
% of FSR/%VCC
% of FSR/%VCC
% of FSR/%VDD
✻
✻
0
✻
+70
✻
°C
°C
°C
°C
°C
TEMPERATURE RANGE
Specification:
B, C Grades
S Grades
J, K, L Grades
Storage: Ceramic
Plastic, SOIC
0
–60
+70
+100
✻
–60
✻
✻
+150
✻
–25
–55
+85
+125
✻
✻
✻ Specification same as model to the left.
NOTES: (1) Digital inputs are TTL, LSTTL, 54/74C, 54/74HC, and 54/74HTC compatible over the operating voltage range of VDD = +5V to +15V and over the specified
temperature range. The input switching threshold remains at the TTL threshold of 1.4V over the supply range of VDD = +5V to +15V. As logic “0” and logic “1” inputs vary over
0V to +0.8V and +2.4V to +10V respectively, the change in the D/A converter output voltage will not exceed ±0.0015% of FSR for the LH and CH grades, ±0.003% of FSR for
the BH grade and ±0.006% of FSR for the KG grade. (2) DAC702 (current-output models) is specified and tested with an external output operational amplifier connected using
the internal feedback resistor in all parameters except settling time. (3) FSR means full-scale range and is 20V for the ±10V range (DAC703), 10V for the 0 to +10V range
(DAC701). FSR is 2mA for the ±1mA range (DAC702). (4) ±0.0015% of full-scale range is equivalent to 1LSB in 15-bit resolution. ±0.003% of full-scale range is equivalent to
1LSB in 14-bit resolution. ±0.006% of full-scale range is equivalent to 1LSB in 13-bit resolution. (5) Adjustable to zero with external trim potentiometer. Adjusting the gain
potentiometer rotates the transfer function around the zero point. (6) Error at input code FFFFH for DAC701, 7FFFH for DAC702 and DAC703. (7) With gain and zero errors
adjusted to zero at +25°C. (8) Maximum represents the 3σ limit. Not 100% tested for this parameter. (9) At the major carry, 7FFFH to 8000H and 8000H to 7FFFH. (10) Tolerance
on output impedance and output current is ±30%. (11) Power dissipation is an additional 40mW when VDD is operated at +15V.
The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumes no
responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject to change without notice.
No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrant any BURR-BROWN
product for use in life support devices and/or systems.
®
3
DAC701, 702, 703
CONNECTION DIAGRAMS
MSB
Reference
Circuit
1
24
2
(2)
+VCC
23
270kΩ
3
(3)
22
0.0022µF
4
21
5
20
3.9MΩ
(3)
Digital
Inputs
6
7
8
9
16-Bit
Ladder
Resistor
Network
and
Current
Switches
10
RF
(4)
–V CC
19
(2)
18
V DD (1)
17
LSB
Voltage Models
Only
(2)
16
15
11
14
12
13
Digital
Inputs
NOTES: (1) Can be tied to +VCC instead of having
separate VDD supply. (2) Decoupling capacitors are
0.1µF to 1.0µF. (3) Potentiometers are 10kΩ to
100kΩ. (4) 5kΩ (DAC701), 10kΩ (DAC702/703).
ABSOLUTE MAXIMUM RATINGS(1)
PIN ASSIGNMENTS
ALL PACKAGES
PIN #
DAC702
DAC701/703
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
Bit 1 (MSB)
Bit 2
Bit 3
Bit 4
Bit 5
Bit 6
Bit 7
Bit 8
Bit 9
Bit 10
Bit 11
Bit 12
Bit 13
Bit 14
Bit 15
Bit 16 (LSB)
RFEEDBACK
VDD
–VCC
Common
IOUT
Gain Adjust
+VCC
+6.3V Reference Output
Bit 1 (MSB)
Bit 2
Bit 3
Bit 4
Bit 5
Bit 6
Bit 7
Bit 8
Bit 9
Bit 10
Bit 11
Bit 12
Bit 13
Bit 14
Bit 15
Bit 16 (LSB)
VOUT
VDD
–VCC
Common
Summing Junction (Zero Adjust)
Gain Adjust
+VCC
+6.3V Reference Output
+VCC to Common ........................................................................ 0V, +18V
–VCC to Common ........................................................................ 0V, –18V
VDD to Common .......................................................................... 0V, +18V
Digital Data Inputs to Common ................................................ –1V, +18V
Reference Out to Common ........................... Indefinite Short to Common
External Voltage Applied to RF (DAC702) ......................................... ±18V
External Voltage Applied to D/A Output (DAC701/703) .......... –5V to +5V
VOUT (DAC701/703) ....................................... Indefinite Short to Common
Power Dissipation ................................................................................. 1W
Storage Temperature ...................................................... –60°C to +150°C
Lead Temperature (soldering, 10s) ................................................. 300°C
NOTE: (1) Stresses above those listed under “Absolute Maximum Ratings”
may cause permanent damage to the device. Exposure to absolute maximum
conditions for extended periods may affect device reliability.
ELECTROSTATIC
DISCHARGE SENSITIVITY
This integrated circuit can be damaged by ESD. Burr-Brown
recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling
and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits
may be more susceptible to damage because very small
parametric changes could cause the device not to meet its
published specifications.
®
DAC701, 702, 703
4
PACKAGE/ORDERING INFORMATION
TEMPERATURE
RANGE
LINEARITY
ERROR, MAX
AT+25°C
(% of FSR)
GAIN
DRIFT,
MAX
(ppm/°C)
PRODUCT
PACKAGE
PACKAGE
DRAWING
NUMBER(1)
DAC703JP
DAC703KP
24-Pin Plastic DIP
24-Pin Plastic DIP
167
167
±1mA, ±10V
±1mA, ±10V
0°C to +70°C
0°C to +70°C
±0.006
±0.003
±30
±25
DAC701KH
DAC702KH
DAC703KH
24-Pin Ceramic DIP
24-Pin Ceramic DIP
24-Pin Ceramic DIP
165
165
165
0 to –2mA, 0 to +10V
±1mA, ±10V
±1mA, ±10V
0°C to +70°C
0°C to +70°C
0°C to +70°C
±0.003
±0.003
±0.003
±25
±25
±25
DAC701BH
DAC702BH
DAC703BH
24-Pin Ceramic DIP
24-Pin Ceramic DIP
24-Pin Ceramic DIP
165
165
165
0 to –2mA, 0 to +10V
±1mA, ±10V
±1mA, ±10V
–25°C to +85°C
–25°C to +85°C
–25°C to +85°C
±0.003
±0.003
±0.003
±15
±15
±15
DAC701LH
DAC702LH
DAC703LH
24-Pin Ceramic DIP
24-Pin Ceramic DIP
24-Pin Ceramic DIP
165
165
165
0 to –2mA, 0 to +10V
±1mA, ±10V
±1mA, ±10V
0°C to +70°C
0°C to +70°C
0°C to +70°C
±0.0015
±0.0015
±0.0015
±10
±10
±10
DAC701CH
DAC702CH
DAC703CH
24-Pin Ceramic DIP
24-Pin Ceramic DIP
24-Pin Ceramic DIP
165
165
165
0 to –2mA, 0 to +10V
±1mA, ±10V
±1mA, ±10V
–25°C to +85°C
–25°C to +85°C
–25°C to +85°C
±0.0015
±0.0015
±0.0015
±10
±10
±10
DAC701SH
DAC702SH
DAC703SH
24-Pin Ceramic DIP
24-Pin Ceramic DIP
24-Pin Ceramic DIP
165
165
165
0 to –2mA, 0 to +10V
±1mA, ±10V
±1mA, ±10V
–55°C to +125°C
–55°C to +125°C
–55°C to +125°C
±0.003
±0.003
±0.003
±15
±15
±15
DAC703JU
DAC703KU
24-Pin SOIC
24-Pin SOIC
239
239
±10V
±10V
0°C to +70°C
0°C to +70°C
±0.006
±0.003
±30
±25
OUTPUT
CONFIGURATION
NOTE: (1) For detailed drawing and dimension table, please see end of data sheet, or Appendix C of Burr-Brown IC Data Book.
®
5
DAC701, 702, 703
DISCUSSION OF
SPECIFICATIONS
Zero Drift
Zero drift is a measure of the change in the output with
FFFFH (DAC701) applied to the digital inputs over the
specified temperature range. For the bipolar models, zero is
measured at 7FFFH (bipolar zero) applied to the digital
inputs. This code corresponds to zero volts (DAC703) or
zero milliamps (DAC702) at the analog output. The maximum change in offset at tMIN or tMAX is referenced to the
zero error at +25°C and is divided by the temperature
change. This drift is expressed in parts per million of full
scale range per degree centigrade (ppm of FSR/°C).
DIGITAL INPUT CODES
The DAC701/702/703 accept complementary digital
input codes in either binary format (CSB, unipolar or
COB, bipolar). The COB models DAC702/703 may be
connected by the user for either complementary offset
binary (COB) or complementary two’s complement (CTC)
codes (see Table I).
ANALOG OUTPUT
DIGITAL
INPUT
CODES
0000H
7FFFH
8000H
FFFFH
DAC701
Complementary
Straight Binary
(CSB)
DAC702/703
Complementary
Offset Binary
(COB)
DAC702/703
Complementary
Two’s Complement
(CTC)*
+ Full Scale
+1/2 Full Scale
+1/2 Full Scale
–1LSB
Zero
+ Full Scale
Bipolar Zero
–1LSB
–1LSB
– Full Scale
+ Full Scale
– Full Scale
Bipolar Zero
SETTLING TIME
Settling time of the D/A is the total time required for the
analog output to settle within an error band around its final
value after a change in digital input. Refer to Figure 1 for
typical values for this family of products.
Voltage Output
Settling times are specified to ±0.003% of FSR (±1/2LSB
for 14 bits) for two input conditions: a full-scale range
change of 20V (DAC703) or 10V (DAC701) and a 1LSB
change at the “major carry,” the point at which the worstcase settling time occurs. (This is the worst-case point since
all of the input bits change when going from one code to the
next).
* Invert the MSB of the COB code with an external inverter to obtain CTC
code.
TABLE I. Digital Input Codes.
ACCURACY
Linearity
This specification describes one of the most important measures of performance of a D/A converter. Linearity error is
the deviation of the analog output from a straight line drawn
through the end points (all bits ON point and all bits OFF
point).
Current Output
Settling times are specified to ±0.003% of FSR for a fullscale range change for two output load conditions: one for
10Ω to 100Ω and one for 1000Ω. It is specified this way
because the output RC time constant becomes the dominant
factor in determining settling time for large resistive loads.
Differential Linearity Error
Differential linearity error (DLE) of a D/A converter is the
deviation from an ideal 1LSB change in the output from one
adjacent output state to the next. A differential linearity error
specification of ±1/2LSB means that the output step sizes
can be between 1/2LSB and 3/2LSB when the input changes
from one adjacent input state to the next. A negative DLE
specification of no more than –1LSB (–0.006% for 14-bit
resolution) insures monotonicity.
Final-Value Error Band, Percent of
Full-Scale Range (±% of FSR)
1
Monotonicity
Monotonicity assures that the analog output will increase or
remain the same for increasing input digital codes. The
DAC701/702/703 are specified to be monotonic to 14 bits
over the entire specification temperature range.
DAC701
DAC703
0.1
0.01
0.001
0.01
RL = 100Ω
RL = 1kΩ
0.1
1
10
Settling Time (µs)
FIGURE 1. Final-Value Error Band vs Full-Scale Range
Settling Time.
DRIFT
Gain Drift
Gain drift is a measure of the change in the full-scale range
output over temperature expressed in parts per million per
degree centigrade (ppm/°C). Gain drift is established by: (1)
testing the end point differences for each D/A at tMIN, +25°C
and tMAX; (2) calculating the gain error with respect to the
+25°C value; and (3) dividing by the temperature change.
COMPLIANCE VOLTAGE
Compliance voltage applies only to current output models. It
is the maximum voltage swing allowed on the output current
pin while still being able to maintain specified accuracy.
®
DAC701, 702, 703
DAC702
6
POWER SUPPLY SENSITIVITY
Power supply sensitivity is a measure of the effect of a
change in a power supply voltage on the D/A converter
output. It is defined as a percent of FSR change in the output
per percent of change in either the positive supply (+VCC),
negative supply (–VCC) or logic supply (VDD) about the
nominal power supply voltages (see Figure 2).
less. The 3.9MΩ and 270kΩ resistors (±20% carbon or
better) should be located close to the D/A converter to
prevent noise pickup. If it is not convenient to use these
high-value resistors, an equivalent “T” network, as shown in
Figure 3, may be substituted in place of the 3.9MΩ part. A
0.001µF to 0.01µF ceramic capacitor should be connected
from Gain Adjust to Common to prevent noise pickup. Refer
to Figures 4 and 5 for the relationship of zero and gain
adjustments to unipolar and bipolar D/A converters.
0.030
≡
3.9MΩ
180kΩ
180kΩ
10kΩ
0.025
0.020
FIGURE 3. Equivalent Resistances.
0.015
+15V
Supply
0.005
+ Full
Scale
0
1LSB
1
10
100
1k
10k
100k
Power Supply Ripple Frequency (Hz)
FIGURE 2. Power Supply Rejection vs Power Supply Ripple
Frequency.
Range of
Zero Adjust
REFERENCE SUPPLY
All models have an internal low-noise +6.3V reference
voltage derived from an on-chip buried zener diode. This
reference voltage, available to the user, has a tolerance of
±5% (KH models) and ±1% (BH models). A minimum of
1.5mA is available for external loads. Since the output
impedance of the reference output is typically 1W, the
external load should remain constant.
Gain Adjust
Rotates
the Line
Input =
FFFFH
Range
of Gain
Adjust
Input =
0000 H
Zero Adjust
Translates
the Line
Digital Input
FIGURE 4. Relationship of Zero and Gain Adjustments for
Unipolar D/A Converters, DAC701.
1LSB
If a varying load is to be driven by the reference supply, an
external buffer amplifier is recommended to drive the load
in order to isolate the bipolar offset (connected internally to
the reference) from load variations.
Range
of Gain
Adjust
+ Full
Scale
Analog Output
OPERATING INSTRUCTIONS
POWER SUPPLY CONNECTIONS
For optimum performance and noise rejection, power supply decoupling capacitors should be added as shown in the
Connection Diagram. 1µF tantalum capacitors should be
located close to the D/A converter.
EXTERNAL ZERO AND GAIN ADJUSTMENT
Zero and gain may be trimmed by installing external zero
and gain potentiometers. Connect these potentiometers as
shown in the Connection Diagram and adjust as described
below. TCR of the potentiometers should be 100ppm/°C or
Input =
FFFFH
Gain
Adjust
Rotates
the Line
Full Scale
Range
+5V
Supply
Full Scale Range
–15V Supply
0.01
Analog Output
% of FSR Error Per % of Change in VSUPPLY
It is specified for DC or low frequency changes. The typical
performance curve in Figure 2 shows the effect of high
frequency changes in power supply voltages.
Input =
0000 H
MSB on All
Others Off 7FFF H
– Full
Scale
Offset
Adjust
Translates
the Line
Range
and
Offset
Adjust
Digital Input
FIGURE 5. Relationship of Zero and Gain Adjustments for
Bipolar D/A Converters, DAC702 and DAC703.
®
7
DAC701, 702, 703
In many applications it is impractical to sense the output
voltage at the output pin. Sensing the output voltage at the
system ground point is permissible with the DAC700 family
because the D/A converter is designed to have a constant
return current of approximately 2mA flowing from Common. The variation in this current is under 20µA (with
changing input codes), therefore R4 can be as large as 3Ω
without adversely affecting the linearity of the D/A converter. The voltage drop across R4 (R4 x 2mA) appears as a
zero error and can be removed with the zero calibration
adjustment. This alternate sensing point (the system ground
point) is shown in Figures 6, 7, and 8.
Zero Adjustment
For unipolar (CSB) configurations, apply the digital input
code that produces zero voltage or zero current output and
adjust the zero potentiometer for zero output.
For bipolar (COB, CTC) configurations, apply the digital
input code that produces zero output voltage or current. See
Table II for corresponding codes and the Connection Diagram for zero adjustment circuit connections. Zero calibration should be made before gain calibration.
Gain Adjustment
Apply the digital input that gives the maximum positive
output voltage. Adjust the gain potentiometer for this positive full scale voltage. See Table II for positive full scale
voltages and the Connection Diagram for gain adjustment
circuit connections.
Figures 7 and 8 show two methods of connecting the current
output models (DAC702) with external precision output op
amps. By sensing the output voltage at the load resistor (ie,
by connecting RF to the output of A1 at RL), the effect of R1
and R2 is greatly reduced. R1 will cause a gain error but is
independent of the value of RL and can be eliminated by
initial calibration adjustments. The effect of R2 is negligible
because it is inside the feedback loop of the output op amp
and is therefore greatly reduced by the loop gain.
INSTALLATION
CONSIDERATIONS
This D/A converter family is laser-trimmed to 14-bit linearity. The design of the device makes the 16-bit resolution
available. If 16-bit resolution is not required, bit 15 and bit
16 should be connected to VDD through a single 1kΩ
resistor.
DAC701
Due to the extremely high resolution and linearity of the
D/A converter, system design problems such as grounding
and contact resistance become very important. For a 16-bit
converter with a 10V full-scale range, 1LSB is 153µV. With
a load current of 5mA, series wiring and connector resistance of only 30mΩ will cause the output to be in error by
1LSB. To understand what this means in terms of a system
layout, the resistance of #23 wire is about 0.021Ω/ft. Neglecting contact resistance, less than 18 inches of wire will
produce a 1LSB error in the analog output voltage!
RF
RDAC
A1
4kΩ
VOUT
R2
RB *
RL
R3
Common
Alternate Ground
Sense Connection
R4
Sense Output
+V
To +VCC
1µF
In Figures 6, 7, and 8, lead and contact resistances are
represented by R1 through R5. As long as the load resistance
RL is constant, R2 simply introduces a gain error and can be
removed during initial calibration. R3 is part of RL, if the
output voltage is sensed at Common, and therefore introduces no error. If RL is variable, then R2 should be less than
RL MIN/216 to reduce voltage drops due to wiring to less than
1LSB. For example, if RL MIN is 5kΩ, then R2 should be less
than 0.08Ω. RL should be located as close as possible to the
D/A converter for optimum performance. The effect of R4 is
negligible.
COM
1µF
To –VCC
±15VDC
Supply
–V
System Ground
Point
+V
To VDD
1µF
COM
+5VDC
Supply
* RB = 2kΩ (DAC701 and DAC703)
FIGURE 6. Output Circuit for Voltage Models.
®
DAC701, 702, 703
5kΩ
8
VOLTAGE OUTPUT MODELS
ANALOG OUTPUT
DAC701 UNIPOLAR
DIGITAL INPUT CODE
1LSB
0000H
FFFFH
(µV)
(V)
(V)
DAC703 BIPOLAR
16-BIT
15-BIT
14-BIT
16-BIT
15-BIT
14-BIT
153
+9.99985
0
305
+9.99969
0
610
+9.99939
0
305
+9.99960
–10.0000
610
+9.99939
–10.0000
1224
+9.99878
–10.0000
ANALOG OUTPUT MODEL
ANALOG OUTPUT
DAC702 BIPOLAR
DIGITAL INPUT CODE
1LSB
0000H
FFFFH
(µA)
(mA)
(mA)
16-BIT
15-BIT
14-BIT
0.031
–0.99997
+1.00000
0.061
–0.99994
+1.00000
0.122
–0.99988
+1.00000
TABLE II. Digital Input and Analog Output Relationships.
If the output cannot be sensed at Common or the system
ground point as mentioned above, the differential output
circuit shown in Figure 8 is recommended. In this circuit the
output voltage is sensed at the load common and not at the
D/A converter common as in the previous circuits. The value
of R6 and R7 must be adjusted for maximum common-mode
rejection at RL. Note that if R3 is negligible, the circuit of
Figure 8 can be reduced to the one shown in Figure 7. Again
the effect of R4 is negligible.
DAC702
The D/A converter and the wiring to its connectors should be
located to provide optimum isolation from sources of RFI
and EMI. The key concept in elimination of RF radiation or
pickup is loop area; therefore, signal leads and their return
conductors should be kept close together. This reduces the
external magnetic field along with any radiation. Also, if a
single lead and its return conductor are wired close together,
they present a small flux-capture cross section for any
external field. This reduces radiation pickup in the circuit.
R1
RF
DAC702
RF *
I OUT
A1
RDAC *
Common
RF *
RB ‡
R1
RF
R2
RL
I OUT
RDAC *
R3
R2
A1
RL
Common
R7
Alternate Ground
Sense Connection
R6
R4
Sense Output
+V
To +VCC
1µF
COM
1µF
–V
To –VCC
1µF
COM
R3
Alternate Ground
Sense Connection
±15VDC
Supply
R4
+V
To +VCC
1µF
System Ground
Point
+V
To VDD
COM
1µF
+5VDC
Supply
DAC702
RB
RF
RDAC
2.45kΩ
10k Ω
2.45kΩ
System Ground
Point
+V
To VDD
DAC702
‡ R should be equal to the output impedance at the current output
B
to compensate for the bias current drift of A1. Use standard 10%,
1/4W carbon composition or equivalent resistors.
FIGURE 7. Preferred External Op Amp Configuration.
±15VDC
Supply
–V
To –VCC
1µF
*
R5
Sense
Output
COM
RF
RDAC
10k Ω
2.45kΩ
+5VDC
Supply
R5 + R7 = RF + R1
R6 = RDAC
FIGURE 8. Differential Sensing Output Op Amp
Configuration.
®
9
DAC701, 702, 703
APPLICATIONS
RF
DRIVING AN EXTERNAL OP AMP
WITH CURRENT OUTPUT D/AS
5k Ω
DAC702 is current output devices and will drive the summing junction of an op amp to produce an output voltage as
shown in Figure 9. Use of the internal feedback resistor is
required to obtain specified gain accuracy and low gain drift.
I OUT
0 to
2mA
4k Ω
VOUT
Common
DAC702 can be scaled for any desired voltage range with an
external feedback resistor, but at the expense of increased
drifts of up to ±50ppm/°C. The resistors in the DAC702 ratio
track to ±1ppm/°C but their absolute TCR may be as high as
±50ppm/°C.
FIGURE 9. External Op Amp Using Internal Feedback
Resistors.
An alternative method of scaling the output voltage of the
D/A converter and preserving the low gain drift is shown in
Figure 10.
RF
5k Ω
0 to
2mA
OUTPUTS LARGER THAN 20V RANGE
For output voltage ranges larger than ±10V, a high voltage
op amp may be employed with an external feedback resistor.
Use IOUT values of ±1mA for bipolar voltage ranges and
–2mA for unipolar voltage ranges (see Figure 11). Use
protection diodes as shown when a high voltage op amp is
used.
I OUT
4k Ω
R1 *
VOUT
I
R2 *
Common
* R1 , R2 TCR < ±10ppm/°C
FIGURE 10. External Op Amp Using Internal and External
Feedback Resistors to Maintain Low Gain Drift.
RF
RF
0 to
2mA
BB3584
4k Ω
VOUT
FIGURE 11. External Op Amp Using External Feedback
Resistors.
®
DAC701, 702, 703
10
IMPORTANT NOTICE
Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue
any product or service without notice, and advise customers to obtain the latest version of relevant information
to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those
pertaining to warranty, patent infringement, and limitation of liability.
TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in
accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent
TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily
performed, except those mandated by government requirements.
Customers are responsible for their applications using TI components.
In order to minimize risks associated with the customer’s applications, adequate design and operating
safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent
that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other
intellectual property right of TI covering or relating to any combination, machine, or process in which such
semiconductor products or services might be or are used. TI’s publication of information regarding any third
party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright  2000, Texas Instruments Incorporated