NCP1086
1.5 A Adjustable and 3.3 V
Fixed Output Linear
Regulator
The NCP1086 linear regulator provides 1.5 A at 3.3 V or adjustable
output voltage. The adjustable output voltage device uses two external
resistors to set the output voltage within a 1.25 V to 5.5 V range.
The regulators is intended for use as post regulator and
microprocessor supply. The fast loop response and low dropout
voltage make this regulator ideal for applications where low voltage
operation and good transient response are important.
The circuit is designed to operate with dropout voltages less than
1.4 V at 1.5 A output current. Device protection includes overcurrent
and thermal shutdown.
This device is pin compatible with LT1086 family of linear
regulators and has lower dropout voltage.
The regulators are available in TO−220−3, surface mount
D2PAK−3, and SOT−223 packages.
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TO−220−3
T SUFFIX
CASE 221A
1
2
•
12
Output Current to 1.5 A
Output Accuracy to ±1% Over Temperature
Dropout Voltage (Typical) 1.05 V @ 1.5 A
Fast Transient Response
Fault Protection Circuitry
♦ Current Limit
♦ Thermal Shutdown
Pb−Free Packages are Available
Tab = VOUT
Pin 1. Adj
2. VOUT
3. VIN
3
D2PAK−3
DP SUFFIX
CASE 418AB
Features
•
•
•
•
•
Adjustable
Output
3
1
SOT−223
ST SUFFIX
CASE 318E
23
3.3 V Fixed
Output
Tab = VOUT
Pin 1. GND
2. VOUT
3. VIN
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 9 of this data sheet.
DEVICE MARKING INFORMATION
See general marking information in the device marking
section on page 10 of this data sheet.
5.0 V
VIN
3.3 V
@ 1.5 A
VOUT
NCP1086
Adj
10 mF
5.0 V
VIN
NCP1086
124 W
1.0%
GND
22 mF
5.0 V
10 mF
5.0 V
200 W
1.0%
Figure 1. Application Diagram, Adjustable Output
© Semiconductor Components Industries, LLC, 2005
May, 2005 − Rev. 6
VOUT
3.3 V
@ 1.5 A
22 mF
5.0 V
Figure 2. Application Diagram, 3.3 V Fixed Output
1
Publication Order Number:
NCP1086/D
NCP1086
MAXIMUM RATINGS*
Parameter
Supply Voltage, VCC
Operating Temperature Range
Junction Temperature
Storage Temperature Range
Lead Temperature Soldering:
Wave Solder (through hole styles only) Note 1
Reflow (SMD styles only) Note 2
ESD Damage Threshold
Value
Unit
7.0
V
−40 to +70
°C
150
°C
−60 to +150
°C
260 Peak
230 Peak
°C
2.0
kV
Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit
values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied,
damage may occur and reliability may be affected.
1. 10 second maximum.
2. 60 second maximum above 183°C.
ELECTRICAL CHARACTERISTICS (CIN = 10 mF, COUT = 22 mF Tantalum, VOUT + VDROPOUT < VIN < 7.0 V, 0°C ≤ TA ≤ 70°C,
TJ ≤ +150°C, unless otherwise specified, Ifull load = 1.5 A.)
Test Conditions
Characteristic
Min
Typ
Max
Unit
1.241
(−1%)
1.254
1.266
(+1%)
V
ADJUSTABLE OUTPUT VOLTAGE
Reference Voltage (Notes 3 and 4)
VIN − VOUT = 1.5 V; VAdj = 0 V,
10 mA ≤ IOUT ≤ 1.5 A
Line Regulation
1.5 V ≤ VIN − VOUT ≤ 5.75 V; IOUT = 10 mA
−
0.02
0.2
%
Load Regulation (Notes 3 and 4)
VIN − VOUT = 1.5 V; 10 mA ≤ IOUT ≤ 1.5 A
−
0.04
0.4
%
Dropout Voltage (Note 5)
IOUT = 1.5 A
−
1.05
1.4
V
Current Limit
VIN − VOUT = 3.0 V; TJ ≥ 25°C
1.6
3.1
−
A
Minimum Load Current (Note 6)
VIN = 7.0 V; VAdj = 0
−
0.6
2.0
mA
Adjust Pin Current
VIN − VOUT = 3.0 V; IOUT = 10 mA
−
50
100
mA
Thermal Regulation (Note 7)
30 ms pulse; TA = 25°C
−
0.002
0.02
%/W
Ripple Rejection (Note 7)
f = 120 Hz; IOUT = 1.5 A; VIN − VOUT = 3.0 V;
VRIPPLE = 1.0 VP−P
−
80
−
dB
Thermal Shutdown (Note 8)
−
150
180
210
°C
Thermal Shutdown Hysteresis (Note 8)
−
−
25
−
°C
3.25
(−1.5%)
3.3
3.35
(+1.5%)
V
FIXED OUTPUT VOLTAGE
Output Voltage (Notes 3 and 4)
VIN − VOUT = 1.5 V, 0 ≤ IOUT ≤ 1.5 A
Line Regulation
2.0 V ≤ VIN − VOUT ≤ 3.7 V; IOUT = 10 mA
−
0.02
0.2
%
Load Regulation (Notes 3 and 4)
VIN − VOUT = 2.0 V; 10 mA ≤ IOUT ≤ 1.5 A
−
0.04
0.4
%
Dropout Voltage (Note 5)
IOUT = 1.5 A
−
1.05
1.4
V
Current Limit
VIN − VOUT = 3.0 V
1.6
3.1
−
A
Quiescent Current
IOUT = 10 mA
−
5.0
10
mA
Thermal Regulation (Note 7)
30 ms pulse; TA = 25°C
−
0.002
0.02
%/W
3. Load regulation and output voltage are measured at a constant junction temperature by low duty cycle pulse testing. Changes in output
voltage due to thermal gradients or temperature changes must be taken into account separately.
4. Specifications apply for an external Kelvin sense connection at a point on the output pin 1/4” from the bottom of the package.
5. Dropout voltage is a measurement of the minimum input/output differential at full load.
6. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set the
output voltage is selected to meet the minimum requirement.
7. Guaranteed by design, not 100% tested in production.
8. Thermal shutdown is 100% functionally tested in production.
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2
NCP1086
ELECTRICAL CHARACTERISTICS (continued) (CIN = 10 mF, COUT = 22 mF Tantalum, VOUT + VDROPOUT < VIN < 7.0 V,
0°C ≤ TA ≤ 70°C, TJ ≤ +150°C, unless otherwise specified, Ifull load = 1.5 A.)
Test Conditions
Characteristic
Min
Typ
Max
Unit
−
80
−
dB
FIXED OUTPUT VOLTAGE (continued)
f = 120 Hz; IOUT = 1.5 A; VIN − VOUT = 3.0 V;
VRIPPLE = 1.0 VP−P
Ripple Rejection (Note 9)
Thermal Shutdown (Note 10)
−
150
180
210
°C
Thermal Shutdown Hysteresis
(Note 10)
−
−
25
−
°C
9. Guaranteed by design, not 100% tested in production.
10. Thermal shutdown is 100% functionally tested in production.
PACKAGE PIN DESCRIPTION, ADJUSTABLE OUTPUT
Package Pin Number
D2PAK−3
TO−220−3
SOT−223
Pin Symbol
1
1
1
Adj
2
2
2
VOUT
3
3
3
VIN
Function
Adjust pin (low side of the internal reference).
Regulated output voltage (case).
Input voltage.
PACKAGE PIN DESCRIPTION, 3.3 V FIXED OUTPUT
Package Pin Number
D2PAK−3
TO−220−3
SOT−223
Pin Symbol
1
1
1
GND
Ground connection.
2
2
2
VOUT
Regulated output voltage (case).
3
3
3
VIN
Function
Input voltage.
VOUT
VIN
VOUT
VIN
Output
Current
Limit
Thermal
Shutdown
− +
Output
Current
Limit
Thermal
Shutdown
Error
Amplifier
Adj
Bandgap
− +
Error
Amplifier
Bandgap
GND
Figure 3. Block Diagram, Adjustable Output
Figure 4. Block Diagram, 3.3 V Fixed Output
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3
NCP1086
TYPICAL PERFORMANCE CHARACTERISTICS
1.05
0.10
TCASE = 0°C
0.08
Output Voltage Deviation (%)
V Drop Out (V)
1.00
0.95
0.90
TCASE = 25°C
0.85
0.80
TCASE = 125°C
0.75
0
300
600
900
IOUT (mA)
1200
0.04
0.00
−0.04
−0.08
−0.12
0
1500
TJ (°C)
Figure 5. Dropout Voltage vs. Output Current
Figure 6. Reference Voltage vs. Temperature
3.5
65
3.1
IO = 10mA
60
ISC (A)
Adjust Pin Current (mA)
70
55
40
0
2.7
2.3
50
1.9
45
20
40
60
80
Temperature (°C)
100
1.5
1.0
120
Voltage Deviation (mV)
200
100
0
VOUT = 3.3 V
COUT = CIN = 22 mF Tantalum
−120
0
−200
1500
750
0
0
1.0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
2.0
3.0
4.0
5.0
VIN − VOUT (V)
7.0
6.0
Figure 8. Short Circuit Current vs VIN − VOUT
Load Step (mA)
Voltage Deviation (mV)
Figure 7. Adjust Pin Current vs. Temperature
(Adjustable Output)
Load Step (mA)
10 20 30 40 50 60 70 80 90 100 110 120 130
9.0
10
Time, ms
Figure 9. Transient Response (Adjustable Output)
200
100
0
−120
0
−200
COUT = CIN = 22 mF Tantalum
1500
750
0
0
1.0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
9.0
10
Time, ms
Figure 10. Transient Response (3.3 V Fixed Output)
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4
85
85
75
75
Ripple Rejection (dB)
Ripple Rejection (dB)
NCP1086
65
55
45
TCASE = 25°C
IOUT = 6A
(VIN − VOUT = 3V)
VRIPPLE = 1.6VPP
CAdj = 0.1 mF
35
25
15
101
102
65
55
45
TCASE = 25°C
IOUT = 6A
(VIN − VOUT = 3V)
VRIPPLE = 1.6VPP
35
25
103
104
Frequency (Hz)
105
15
101
106
Figure 11. Ripple Rejection vs. Frequency
(Adjustable Output)
105
106
0.65
Minimum Load Current (mA)
Output Voltage Deviation, (%)
103
104
Frequency (Hz)
Figure 12. Ripple Rejection vs. Frequency
(3.3 V Fixed Output)
0.100
0.075
0.050
TCASE = 125°C
TCASE = 25°C
0.025
0
0
102
TCASE = 0°C
0.55
TCASE = 125°C
TCASE = 25°C
0.50
0.45
CIN = COUt = 22 mF Tantalum
TCASE = 0°C
1.0
0.60
2.0
0.40
1.0
2.0
3.0
Output Current (A)
4.0
5.0
6.0
7.0
VIN − VOUT (V)
Figure 14. Minimum Load Current vs VIN − VOUT
(Adjustable Output)
Figure 13. Load Regulation vs. Output Current
(Adjustable Output)
APPLICATIONS INFORMATION
A resistor divider network R1 and R2 causes a fixed
current to flow to ground. This current creates a voltage
across R2 that adds to the 1.25 V across R1 and sets the
overall output voltage. The adjust pin current (typically
50 mA) also flows through R2 and adds a small error that
should be taken into account if precise adjustment of VOUT
is necessary.
The output voltage is set according to the formula:
The NCP1086 voltage regulator series provides
adjustable and 3.3 V output voltages at currents up to 1.5 A.
The regulator is protected against overcurrent conditions
and includes thermal shutdown.
The NCP1086 series has a composite PNP−NPN output
transistor and requires an output capacitor for stability. A
detailed procedure for selecting this capacitor is included in
the Stability Considerations section.
VOUT + VREF
Adjustable Operation
The adjustable output device has an output voltage range
of 1.25 V to 5.5 V. An external resistor divider sets the
output voltage as shown in Figure 15. The regulator
maintains a fixed 1.25 V (typical) reference between the
output pin and the adjust pin.
) R2Ǔ ) I
ǒR1 R1
Adj
R2
The term IAdj × R2 represents the error added by the adjust
pin current.
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5
NCP1086
must be able to withstand the short circuit condition
indefinitely while protecting the IC.
R1 is chosen so that the minimum load current is at least
2.0 mA. R1 and R2 should be the same type, e.g. metal film
for best tracking over temperature.
EXTERNAL
VIN
VOUT
VIN
C1
SUPPLY
VOUT
NCP1086
VREF
Adj
R1
C2
VIN
VOUT
NCP1086
Adj
IAdj
R2
VOUT
Figure 15. Resistor Divider Scheme
Figure 16. Short Circuit Protection Circuit for High
Voltage Application
The adjustable output linear regulator has an absolute
maximum specification of 7.0 V for the voltage difference
between VIN and VOUT. However, the IC may be used to
regulate voltages in excess of 7.0 V. The main
considerations in such a design are powerup and short circuit
capability.
In most applications, ramp−up of the power supply to VIN
is fairly slow, typically on the order of several tens of
milliseconds, while the regulator responds in less than one
microsecond. In this case, the linear regulator begins
charging the load as soon as the VIN to VOUT differential is
large enough that the pass transistor conducts current. The
load at this point is essentially at ground, and the supply
voltage is on the order of several hundred mV, with the result
that the pass transistor is in dropout. As the supply to VIN
increases, the pass transistor will remain in dropout, and
current is passed to the load until VOUT reaches the point at
which the IC is in regulation. Further increase in the supply
voltage brings the pass transistor out of dropout. The result
is that the output voltage follows the power supply ramp−up,
staying in dropout until the regulation point is reached. In
this manner, any output voltage may be regulated. There is
no theoretical limit to the regulated voltage as long as the
VIN to VOUT differential of 7.0 V is not exceeded.
However, the possibility of destroying the IC in a short
circuit condition is very real for this type of design. Short
circuit conditions will result in the immediate operation of
the pass transistor outside of its safe operating area.
Overvoltage stresses will then cause destruction of the pass
transistor before overcurrent or thermal shutdown circuitry
can become active. Additional circuitry may be required to
clamp the VIN to VOUT differential to less than 7.0 V if
fail−safe operation is required. One possible clamp circuit is
illustrated in Figure 16; however, the design of clamp
circuitry must be done on an application by application
basis. Care must be taken to ensure the clamp actually
protects the design. Components used in the clamp design
Stability Considerations
The output or compensation capacitor helps determine
three main characteristics of a linear regulator: startup delay,
load transient response and loop stability.
The capacitor value and type is based on cost, availability,
size and temperature constraints. A tantalum or aluminum
electrolytic capacitor is best, since a film or ceramic
capacitor with almost zero ESR can cause instability. The
aluminum electrolytic capacitor is the least expensive
solution. However, when the circuit operates at low
temperatures, both the value and ESR of the capacitor will
vary considerably. The capacitor manufacturers’ data sheet
provides this information.
A 22 mF tantalum capacitor will work for most
applications, but with high current regulators such as the
NCP1086 series the transient response and stability improve
with higher values of capacitance. The majority of
applications for this regulator involve large changes in load
current, so the output capacitor must supply the
instantaneous load current. The ESR of the output capacitor
causes an immediate drop in output voltage given by:
DV + DI
ESR
For microprocessor applications it is customary to use an
output capacitor network consisting of several tantalum and
ceramic capacitors in parallel. This reduces the overall ESR
and reduces the instantaneous output voltage drop under
load transient conditions. The output capacitor network
should be as close as possible to the load for the best results.
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NCP1086
Protection Diodes
When large external capacitors are used with a linear
regulator it is sometimes necessary to add protection diodes.
If the input voltage of the regulator gets shorted, the output
capacitor will discharge into the output of the regulator. The
discharge current depends on the value of the capacitor, the
output voltage and the rate at which VIN drops. In the
NCP1086 series linear regulator, the discharge path is
through a large junction and protection diodes are not
usually needed. If the regulator is used with large values of
output capacitance and the input voltage is instantaneously
shorted to ground, damage can occur. In this case, a diode
connected as shown in Figure 17 or Figure 18 is
recommended.
VIN
VIN
VOUT
RLOAD
Figure 19. Conductor Parasitic Resistance Effects
Can Be Minimized with the Above Grounding
Scheme for Fixed Output Regulators
For the adjustable regulator, the best load regulation
occurs when R1 is connected directly to the output pin of the
regulator as shown in Figure 20. If R1 is connected to the
load, RC is multiplied by the divider ratio and the effective
resistance between the regulator and the load becomes
VOUT
NCP1086
C1
Adj
R1
RC
VOUT
NCP1086
IN4002 (optional)
VIN
VIN
Conductor Parasitic
Resistance
RC
C2
) R2Ǔ
ǒR1 R1
where RC = conductor parasitic resistance.
R2
VIN
Figure 17. Protection Diode Scheme for Large Output
Capacitors (Adjustable Output)
VIN
RC
VOUT
Conductor Parasitic
Resistance
NCP1086
R1
Adj
RLOAD
IN4002 (optional)
VIN
VIN
C1
VOUT
R2
VOUT
NCP1086
GND
C2
Figure 20. Grounding Scheme for the
Adjustable Output Regulator to Minimize
Parasitic Resistance Effects
Figure 18. Protection Diode Scheme for Large Output
Capacitors (3.3 V Fixed Output)
Calculating Power Dissipation and
Heatsink Requirements
Output Voltage Sensing
The NCP1086 linear regulator includes thermal shutdown
and current limit circuitry to protect the device. High power
regulators such as these usually operate at high junction
temperatures so it is important to calculate the power
dissipation and junction temperatures accurately to ensure
that an adequate heatsink is used.
Since the NCP1086 is a three terminal regulator, it is not
possible to provide true remote load sensing. Load
regulation is limited by the resistance of the conductors
connecting the regulator to the load.
For best results the fixed output regulator should be
connected as shown in Figure 19.
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7
NCP1086
Each material in the heat flow path between the IC and the
outside environment has a thermal resistance. Like series
electrical resistances, these resistances are summed to
determine RqJA, the total thermal resistance between the
junction and the surrounding air.
1. Thermal Resistance of the junction to case, RqJC
(°C/W)
2. Thermal Resistance of the case to Heatsink, RqCS
(°C/W)
3. Thermal Resistance of the Heatsink to the ambient
air, RqSA (°C/W)
These are connected by the equation:
The case is connected to VOUT, and electrical isolation
may be required for some applications. Thermal compound
should always be used with high current regulators such as
these.
The thermal characteristics of an IC depend on the
following four factors:
1.
2.
3.
4.
Maximum Ambient Temperature TA (°C)
Power dissipation PD (W)
Maximum junction temperature TJ (°C)
Thermal resistance junction to ambient RqJA (°C/W)
These four are related by the equation
TJ + TA ) PD
RqJA
RqJA + RqJC ) RqCS ) RqSA
(eq. 1)
(eq. 3)
The value for RqJA is calculated using Equation 3 and the
result can be substituted in Equation 1.
The value for RqJC is 3.5°C/W. For a high current
regulator such as the NCP1086 the majority of the heat is
generated in the power transistor section. The value for
RqSA depends on the heatsink type, while RqCS depends on
factors such as package type, heatsink interface (is an
insulator and thermal grease used?), and the contact area
between the heatsink and the package. Once these
calculations are complete, the maximum permissible value
of RqJA can be calculated and the proper heatsink selected.
For further discussion on heatsink selection, see application
note “Thermal Management,” document number
AND8036/D via our website at www.onsemi.com.
The maximum ambient temperature and the power
dissipation are determined by the design while the
maximum junction temperature and the thermal resistance
depend on the manufacturer and the package type.
The maximum power dissipation for a regulator is:
PD(max) + {VIN(max) * VOUT(min)}IOUT(max) ) VIN(max)IQ
(eq. 2)
where:
VIN(max) is the maximum input voltage,
VOUT(min) is the minimum output voltage,
IOUT(max) is the maximum output current, for the application
IQ is the maximum quiescent current at IOUT(max).
A heatsink effectively increases the surface area of the
package to improve the flow of heat away from the IC and
into the surrounding air.
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8
NCP1086
ORDERING INFORMATION
Package
Shipping†
NCP1086D2T−ADJ
D2PAK
50 Units/Rail
NCP1086D2T−ADJR4
D2PAK
NCP1086D2TADJR4G
D2PAK
(Pb−Free)
Device
NCP1086ST−ADJT3
Type
750 Tape & Reel
SOT−223
Adjustable
NCP1086ST−ADJT3G
SOT−223
(Pb−Free)
NCP1086T−ADJ
2500 Tape & Reel
TO220
NCP1086T−ADJG
TO220
(Pb−Free)
50 Units/Rail
NCP1086D2T−033
D2PAK
50 Units/Rail
NCP1086D2T−33R4
D2PAK
D2PAK
(Pb−Free)
NCP1086D2T−33R4G
NCP1086ST−33T3
750 Tape & Reel
SOT−223
3.3 V
NCP1086ST−33T3G
SOT−223
(Pb−Free)
NCP1086T−033
2500 Tape & Reel
TO220
NCP1086T−033G
TO220
(Pb−Free)
50 Units/Rail
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
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NCP1086
MARKING DIAGRAMS
Adjustable Output
TO−220−3
T SUFFIX
CASE 221A
D2PAK−3
D2T SUFFIX
CASE 418AB
3.3 V Fixed Output
SOT−223
ST SUFFIX
CASE 318E
AYW
086−A
NCP1086−A
AWLYWW
NCP1086−A
AWLYWW
TO−220−3
T SUFFIX
CASE 221A
D2PAK−3
D2T SUFFIX
CASE 418AB
SOT−223
ST SUFFIX
CASE 318E
AYW
08633
1086−33
AWLYWW
1086−33
AWLYWW
1
1
1
1
1
1
A
WL, L
YY, Y
WW, W
= Assembly Location
= Wafer Lot
= Year
= Work Week
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10
NCP1086
PACKAGE DIMENSIONS
TO−220−3
T SUFFIX
CASE 221A−08
ISSUE AA
−T−
F
−B−
SEATING
PLANE
C
T
S
4
Q
A
1 2 3
U
H
−Y−
K
L
R
V
G
J
D 3 PL
0.25 (0.010)
M
B
M
Y
N
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11
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
DIM
A
B
C
D
F
G
H
J
K
L
N
Q
R
S
T
U
V
INCHES
MIN
MAX
0.560
0.625
0.380
0.420
0.140
0.190
0.025
0.035
0.139
0.155
0.100 BSC
−−−
0.280
0.012
0.045
0.500
0.580
0.045
0.060
0.200 BSC
0.100
0.135
0.080
0.115
0.020
0.055
0.235
0.255
0.000
0.050
0.045
−−−
MILLIMETERS
MIN
MAX
14.23
15.87
9.66
10.66
3.56
4.82
0.64
0.89
3.53
3.93
2.54 BSC
−−−
7.11
0.31
1.14
12.70
14.73
1.15
1.52
5.08 BSC
2.54
3.42
2.04
2.92
0.51
1.39
5.97
6.47
0.00
1.27
1.15
−−−
NCP1086
PACKAGE DIMENSIONS
D2PAK−3
CASE 418AB−01
ISSUE O
A
K
TERMINAL 4
U
E
S
V
B
M
H
DIM
A
B
C
D
E
G
H
K
L
M
N
P
R
S
U
V
W
L
P
G
W
N
D
NOTES:
1. DIMENSIONS AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. PACKAGE OUTLINE EXCLUSIVE OF MOLD
FLASH AND METAL BURRS.
4. PACKAGE OUTLINE INCLUSIVE OF
PLATING THICKNESS.
5. FOOT LENGTH MEASURED AT INTERCEPT
POINT BETWEEN DATUM A AND LEAD
SURFACE.
R
−A−
C
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12
INCHES
MIN
MAX
0.396
0.406
0.330
0.340
0.170
0.180
0.026
0.036
0.045
0.055
0.100 REF
0.580
0.620
0.055
0.066
0.000
0.010
0.098
0.108
0.017
0.023
0.090
0.110
0°
8°
0.095
0.105
0.30 REF
0.305 REF
0.010
MILLIMETERS
MIN
MAX
10.05
10.31
8.38
8.64
4.31
4.57
0.66
0.91
1.14
1.40
2.54 REF
14.73
15.75
1.40
1.68
0.00
0.25
2.49
2.74
0.43
0.58
2.29
2.79
0°
8°
2.41
2.67
7.62 REF
7.75 REF
0.25
NCP1086
PACKAGE DIMENSIONS
SOT−223
ST SUFFIX
CASE 318E−04
ISSUE K
A
F
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
4
S
1
2
INCHES
DIM MIN
MAX
A
0.249
0.263
B
0.130
0.145
C
0.060
0.068
D
0.024
0.035
F
0.115
0.126
G
0.087
0.094
H 0.0008 0.0040
J
0.009
0.014
K
0.060
0.078
L
0.033
0.041
M
0_
10 _
S
0.264
0.287
B
3
D
L
G
J
C
0.08 (0003)
M
H
MILLIMETERS
MIN
MAX
6.30
6.70
3.30
3.70
1.50
1.75
0.60
0.89
2.90
3.20
2.20
2.40
0.020
0.100
0.24
0.35
1.50
2.00
0.85
1.05
0_
10 _
6.70
7.30
K
SOLDERING FOOTPRINT*
3.8
0.15
2.0
0.079
2.3
0.091
2.3
0.091
6.3
0.248
2.0
0.079
1.5
0.059
SCALE 6:1
mm Ǔ
ǒinches
*For additional information on our Pb−Free strategy
and soldering details, please download the
ON Semiconductor Soldering and Mounting
Techniques Reference Manual, SOLDERRM/D.
PACKAGE THERMAL DATA
Parameter
TO−220−3
D2PAK−3
SOT−223
Unit
RqJC
Typical
3.5
3.5
15
°C/W
RqJA
Typical
50
10−50*
156
°C/W
* Depending on thermal properties of substrate. RqJA = RqJC + RqCA
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NCP1086
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NPC1086/D