LTC4085-1 USB Power Manager with Ideal Diode Controller and 4.1V Li-Ion Charger DESCRIPTIO U FEATURES ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ The LTC®4085-1 is a USB power manager and Li-Ion battery charger designed for portable battery-powered applications. The part controls the total current used by the USB peripheral for operation and battery charging. The total input current can be limited to 20% or 100% of a programmed value up to 1.5A (typically 100mA or 500mA). Battery charge current is automatically reduced such that the sum of the load current and charge current does not exceed the programmed input current limit. Seamless Transition Between Input Power Sources: Li-Ion Battery, USB and 5V Wall Adapter 215mΩ Internal Ideal Diode Plus Optional External Ideal Diode Controller Provide Low Loss PowerPathTM When Wall Adapter/USB Input Not Present Load Dependent Charging Guarantees Accurate USB Input Current Compliance 4.1V Float Voltage Improves Battery Life Span and High Temperature Safety Margin Constant-Current/Constant-Voltage Operation with Thermal Feedback to Maximize Charging Rate Without Risk of Overheating* Selectable 100% or 20% Input Current Limit (e.g., 500mA/100mA) Battery Charge Current Independently Programmable Up to 1.2A Preset 4.1V Charge Voltage with 0.8% Accuracy C/10 Charge Current Detection Output Tiny (4mm × 3mm × 0.75mm) 14-Lead DFN Package The LTC4085-1 includes a complete constant-current/ constant-voltage linear charger for single cell Li-Ion batteries. This 4.1V version of the standard LTC4085 is intended for applications which will be operated or stored above approximately 60°C. Under these conditions, a reduced float voltage will trade-off initial cell capacity for the benefit of increased capacity retention over the life of the battery. A reduced float voltage also minimizes swelling in prismatic and polymer cells, and avoids open CID (pressure fuse) in cylindrical cells. U APPLICATIO S ■ The LTC4085-1 also includes a programmable termination timer, automatic recharging, an end-of-charge status output and an NTC thermistor. Portable USB Devices: Cameras, MP3 Players, PDAs , LT, LTC and LTM are registered trademarks of Linear Technology Corporation. PowerPath is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents, including 6522118, 6700364. Other patents pending. The LTC4085-1 is available in a 14-lead low profile 4mm × 3mm DFN package. U TYPICAL APPLICATIO ILOAD 5V WALL ADAPTER INPUT 4.7μF 600 4.7μF 1k IIN Input and Battery Current vs Load Current RPROG = 100k, RCLPROG = 2k 510Ω IN WALL 500 SUSPEND USB POWER SUSP ACPR 400 100mA 500mA SELECT HPWR OUT PROG LTC4085-1 * CHRG NTC GND 2k 10k ILOAD 300 IBAT (CHARGING) 200 0 IBAT TIMER + 10k 100k IIN 100 BAT CLPROG VNTC GATE CURRENT (mA) 5V (NOM) FROM USB CABLE VBUS TO LDOs, REGs, ETC 0.1μF 0 * OPTIONAL - TO LOWER IBAT (DISCHARGING) WALL = 0V –100 100 200 400 300 ILOAD (mA) 500 600 40851 TA01b IDEAL DIODE IMPEDANCE 40851 TA01 40851f 1 LTC4085-1 U U U W W W AXI U RATI GS U ABSOLUTE PI CO FIGURATIO (Notes 1, 2, 3, 4, 5) Terminal Voltage IN, OUT t < 1ms and Duty Cycle < 1%................... –0.3V to 7V Steady State ............................................. –0.3V to 6V BAT, CHRG, HPWR, SUSP, WALL, ACPR....... –0.3V to 6V NTC, TIMER, PROG, CLPROG .......–0.3V to (VCC + 0.3V) Pin Current (Steady State) IN, OUT, BAT (Note 6)...............................................2.5A Operating Temperature Range.................. –40°C to 85°C Maximum Operating Junction Temperature .......... 110°C Storage Temperature Range................... –65°C to 125°C TOP VIEW IN 1 14 BAT OUT 2 13 GATE CLPROG 3 HPWR 4 SUSP 5 10 ACPR TIMER 6 9 VNTC WALL 7 8 NTC 12 PROG 15 11 CHRG DE PACKAGE 14-LEAD (4mm × 3mm) PLASTIC DFN TJMAX = 125°C, θJA = 40°C/W EXPOSED PAD (PIN 15) IS GND, MUST BE CONNECTED TO PCB U W U ORDER I FOR ATIO LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE LTC4085EDE-1#PBF LTC4085EDE-1#TRPBF 40851 14-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C Consult LTC Marketing for parts specified with wider operating temperature ranges. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ ELECTRICAL CHARACTERISTICS The ● indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k, RCLPROG = 2k, unless otherwise noted. SYMBOL PARAMETER CONDITIONS MIN VIN Input Supply Voltage IN and OUT 4.35 VBAT Input Voltage BAT IIN Input Supply Current IBAT = 0 (Note 7) Suspend Mode; SUSP = 5V Suspend Mode; SUSP = 5V, WALL = 5V, VOUT = 4.8V ● ● ● IOUT Output Supply Current VOUT = 5V, VIN = 0V, NTC = VNTC IBAT Battery Drain Current VUVLO ΔVUVLO TYP MAX UNITS 5.5 V 4.3 V 0.5 50 60 1.2 100 110 mA μA μA ● 0.7 1.4 mA VBAT = 4.3V, Charging Stopped Suspend Mode; SUSP = 5V VIN = 0V, BAT Powers OUT, No Load ● ● ● 15 22 60 27 35 100 μA μA μA Input or Output Undervoltage Lockout VIN Powers Part, Rising Threshold VOUT Powers Part, Rising Threshold ● ● 3.8 2.95 4 3.15 V V Input or Output Undervoltage Lockout VIN Rising – VIN Falling or VOUT Rising – VOUT Falling ILIM Current Limit RCLPROG = 2k (0.1%), HPWR = 5V RCLPROG = 2k (0.1%), HPWR = 0V IIN(MAX) Maximum Input Current Limit (Note 8) 2.4 A RON ON Resistance VIN to VOUT IOUT = 100mA Load 215 mΩ 3.6 2.75 130 mV Current Limit ● ● 475 90 500 100 525 110 mA mA 40851f 2 LTC4085-1 ELECTRICAL CHARACTERISTICS The ● indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k, RCLPROG = 2k, unless otherwise noted. SYMBOL PARAMETER CONDITIONS VCLPROG CLPROG Pin Voltage RPROG = 2k RPROG = 1k ISS Soft Start Inrush Current IN or OUT VCLEN Input Current Limit Enable Threshold Voltage (VIN – VOUT) VIN Rising (VIN – VOUT) VIN Falling VFLOAT Regulated Output Voltage IBAT = 2mA IBAT = 2mA, (0°C – 85°C) IBAT Current Mode Charge Current RPROG = 100k (0.1%), No Load RPROG = 50k (0.1%), No Load IBAT(MAX) Maximum Charge Current (Note 8) ● ● MIN TYP MAX UNITS 0.98 0.98 1 1 1.02 1.02 V V 5 mA/μs 20 50 -60 80 mV mV 4.065 4.058 4.1 4.1 4.135 4.142 V V 465 900 500 1000 535 1080 mA mA Battery Charger ● ● 1.5 A VPROG PROG Pin Voltage RPROG = 100k RPROG = 50k ● ● kEOC Ratio of End-of-Charge Current to Charge Current VBAT = VFLOAT (4.1V) ● ITRIKL Trickle Charge Current VBAT = 2V, RPROG = 100k (0.1%) VTRIKL Trickle Charge Threshold Voltage VCEN Charger Enable Threshold Voltage (VOUT – VBAT) Falling; VBAT = 4V (VOUT – VBAT) Rising; VBAT = 4V VRECHRG Recharge Battery Threshold Voltage VFLOAT – VRECHRG tTIMER TIMER Accuracy VBAT = 4.3V Recharge Time Percent of Total Charge Time 50 % Low Battery Trickle Charge Time Percent of Total Charge Time, VBAT < 2.8V 25 % 105 °C TLIM ● 0.98 0.98 1 1 1.02 1.02 V V 0.085 0.1 0.11 mA/mA 35 50 60 mA 2.75 2.9 3 V 55 80 ● 65 100 -10 Junction Temperature in Constant Temperature Mode mV mV 135 mV 10 % Internal Ideal Diode RFWD Incremental Resistance, VON Regulation IBAT = 100mA 125 mΩ RDIO(ON) ON Resistance VBAT to VOUT IBAT = 600mA 215 mΩ VFWD Voltage Forward Drop (VBAT – VOUT) IBAT = 5mA IBAT = 100mA IBAT = 600mA VOFF Diode Disable Battery Voltage 2.8 V IFWD Load Current Limit, for VON Regulation 550 mA ID(MAX) Diode Current Limit 2.2 A 20 mV ● 10 30 55 160 50 mV mV mV External Ideal Diode VFWD,EDA External Ideal Diode Forward Voltage VGATE = 1.85V; IGATE = 0 Logic VOL Output Low Voltage CHRG, ACPR ISINK = 5mA ● VIH Input High Voltage SUSP, HPWR Pin ● VIL Input Low Voltage SUSP, HPWR Pin ● IPULLDN Logic Input Pull-Down Current SUSP, HPWR 0.1 0.4 1.2 V V 0.4 2 V μA 40851f 3 LTC4085-1 ELECTRICAL CHARACTERISTICS The ● indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k, RCLPROG = 2k, unless otherwise noted. SYMBOL PARAMETER VCHG(SD) Charger Shutdown Threshold Voltage on TIMER ICHG(SD) Charger Shutdown Pull-Up Current on TIMER VWAR CONDITIONS MIN TYP MAX UNITS ● 0.14 VTIMER = 0V ● 5 14 Absolute Wall Input Threshold Voltage VWALL Rising Threshold ● 4.15 4.25 VWAF Absolute Wall Input Threshold Voltage VWALL Falling Threshold VWDR Delta Wall Input Threshold Voltage VWALL – VBAT Rising Threshold VWDF Delta Wall Input Threshold Voltage VWALL – VBAT Falling Threshold IWALL Wall Input Current VWALL = 5V VVNTC VNTC Bias Voltage IVNTC = 500μA INTC NTC Input Leakage Current VNTC = 1V VCOLD Cold Temperature Fault Threshold Voltage Rising Threshold Hysteresis 0.738 • VVNTC 0.018 • VVNTC V V VHOT Hot Temperature Fault Threshold Voltage Falling Threshold Hysteresis 0.326 • VVNTC 0.015 • VVNTC V V VDIS NTC Disable Voltage NTC Input Voltage to GND (Falling) Hysteresis 0.4 μA 4.35 3.12 0 V V 75 ● V mV 25 60 mV 75 150 μA NTC Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: VCC is the greater of VIN, VOUT or VBAT. Note 3: All voltage values are with respect to GND. Note 4: This IC includes overtemperature protection that is intended to protect the device during momentary overload conditions. Junction temperatures will exceed 110°C when overtemperature protection is active. Continuous operation above the specified maximum operating junction temperature may result in device degradation or failure. ● 4.4 4.85 0 ● 75 100 35 V ±1 125 μA mV mV Note 5: The LTC4085E-1 is guaranteed to meet specified performance from 0° to 85°C. Specifications over the –40°C to 85°C operating temperature range are assured by design, characterization and correlation with statistical process controls. Note 6: Guaranteed by long term current density limitations. Note 7: Total input current is equal to this specification plus 1.002 • IBAT where IBAT is the charge current. Note 8: Accuracy of programmed current may degrade for currents greater than 1.5A. 40851f 4 LTC4085-1 U W TYPICAL PERFOR A CE CHARACTERISTICS Input Supply Current vs Temperature 800 700 70 VIN = 5V VBAT = 4.2V RPROG = 100k RCLPROG = 2k 100 VIN = 5V VBAT = 4.2V 60 R PROG = 100k RCLPROG = 2k 50 SUSP = 5V IIN (μA) 600 IIN (μA) Battery Drain Current vs Temperature (BAT Powers OUT, No Load) Input Supply Current vs Temperature (Suspend Mode) 500 400 VIN = 0V 90 VBAT = 4.2V 80 70 IBAT (μA) 900 TA = 25°C unless otherwise noted. 40 30 300 50 40 30 20 200 20 10 100 0 –50 –25 0 25 50 TEMPERATURE (°C) 100 75 10 0 –50 25 50 25 0 TEMPERATURE (°C) 75 40851 G01 0 –50 100 525 1.2 VIN = 5V 108 VBAT = 3.7V RPROG = 100k 106 R CLPROG = 2k 104 VIN = 5V RCLPROG = 2k 1.0 VCLPROG (V) IIN (mA) 100 75 CLPROG Pin Voltage vs Temperature 110 VIN = 5V VBAT = 3.7V RPROG = 100k 515 RCLPROG = 2k 495 25 50 0 TEMPERATURE (°C) 40851 G03 Input Current Limit vs Temperature, HPWR = 0V 505 –25 40851 G02 Input Current Limit vs Temperature, HPWR = 5V IIN (mA) 60 102 100 98 HPWR = 5V 0.8 0.6 0.4 96 485 94 475 –50 90 –50 HPWR = 0V 0.2 92 –25 0 25 50 TEMPERATURE (°C) 75 100 –25 25 50 0 TEMPERATURE (°C) 75 40851 G04 0 25 50 TEMPERATURE (°C) 4.20 VIN = 5V = 4.2V V 1.015 BAT RPROG = 100k = 2k R 1.010 CLPROG 75 100 40851 G06 Battery Regulation (Float) Voltage vs Temperature VFLOAT Load Regulation 1.020 4.120 RPROG = 34k 4.115 4.15 VIN = 5V IBAT = 2mA 4.110 1.005 1.000 0.995 VFLOAT (V) 4.10 VFLOAT (V) VPROG (V) –25 40851 G05 PROG Pin Voltage vs Temperature 4.05 4.105 4.100 4.095 4.00 4.090 0.990 3.95 0.985 0.980 –50 0 –50 100 4.085 3.90 –25 0 50 25 TEMPERATURE (°C) 75 100 40851 G07 0 200 400 600 IBAT (mA) 800 1000 40851 G08 4.080 –50 –25 0 50 25 TEMPERATURE (°C) 75 100 40851 G09 40851f 5 LTC4085-1 U W TYPICAL PERFOR A CE CHARACTERISTICS Battery Current and Voltage vs Time 600 ILOAD = 400mA 250 IBAT (mA) RON (mΩ) 175 300 3 75 2 100 C/10 400 300 200 100 VIN = 5V VBAT = 3.5V θJA = 50°C/W 0 50 25 75 –50 –25 0 TEMPERATURE (°C) TERMINATION 1 100 TIME (min) 0 200 150 40851 G10 600 4085 G112 1000 120 VIN = 5V VOUT = NO LOAD 500 RPROG = 100k RCLPROG = 2k HPWR = 5V 400 VBAT = 3.7V 900 VIN = 0V 800 700 IOUT (mA) IBAT (mA) VIN = 5V VOUT = NO LOAD 100 RPROG = 100k RCLPROG = 2k HPWR = 0V 80 60 200 40 100 20 600 500 400 300 –50°C 0°C 50°C 100°C 200 100 0 0 0.5 1 1.5 2 2.5 VBAT (V) 3.5 3 4 0 0 4.5 0 0.5 1 1.5 2 2.5 VBAT (V) 3 3.5 40851 G13 0 4.5 50 700 3500 3500 600 3000 IOUT (mA) IOUT 300 2500 2000 1500 RDIO 200 1000 100 500 0 0 50 100 VFWD (mV) 150 IOUT (mA) 800 5000 VBAT = 3.7V 4500 VIN = 0V Si2333 PFET 4000 400 200 40851 G16 0 200 150 Ideal Diode Resistance and Current vs Forward Voltage with External Device 5000 VBAT = 3.7V 4500 VIN = 0V Si2333 PFET 4000 VBAT = 3.7V 900 VIN = 0V 500 100 VFWD (mV) 40851 G15 Ideal Diode Current vs Forward Voltage and Temperature with External Device 1000 IOUT (mA), RDIO (mΩ) 4 40851 G14 Ideal Diode Resistance and Current vs Forward Voltage (No External Device) 125 Ideal Diode Current vs Forward Voltage and Temperature (No External Device) Charging from USB, Low Power, IBAT vs VBAT 300 100 40851 G11 Charging from USB, IBAT vs VBAT IBAT (mA) 500 4 400mAhr CELL 100 VIN = 5V RPROG = 100k RCLPROG = 2.1k 0 50 0 150 0 25 50 TEMPERATURE (°C) 5 400 200 –25 600 VBAT AND VCHRG (V) VIN = 5.5V 125 –50 6 VBAT VIN = 5V 200 CHRG IBAT 500 VIN = 4.5V 225 Charge Current vs Temperature (Thermal Regulation) IBAT (mA) Input RON vs Temperature 275 TA = 25°C unless otherwise noted. 3000 2500 2000 1500 –50°C 0°C 50°C 100°C 0 20 60 40 VFWD (mV) 80 100 40851 G17 1000 500 0 0 20 60 40 VFWD (mV) 80 100 40851 G18 40851f 6 LTC4085-1 U W TYPICAL PERFOR A CE CHARACTERISTICS Input Connect Waveforms Input Disconnect Waveforms VIN 5V/DIV VOUT 5V/DIV VIN 5V/DIV VOUT 5V/DIV IIN 0.5A/DIV IBAT 0.5A/DIV IIN 0.5A/DIV IBAT 0.5A/DIV 1ms/DIV VBAT = 3.85V IOUT = 100mA TA = 25°C unless otherwise noted. 1ms/DIV 40851 G19 VBAT = 3.85V IOUT = 100mA Wall Connect Waveforms, VIN = 0V 40851 G20 Wall Disconnect Waveforms, VIN = 0V HPWR 5V/DIV WALL 5V/DIV VOUT 5V/DIV IIN 0.5A/DIV IWALL 0.5A/DIV IBAT 0.5A/DIV IBAT 0.5A/DIV 100μs/DIV VBAT = 3.85V IOUT = 50mA 1ms/DIV 40851 G21 VBAT = 3.85V IOUT = 100mA RPROG = 100k Response to HPWR 40851 G22 Response to Suspend WALL 5V/DIV SUSP 5V/DIV VOUT 5V/DIV IWALL 0.5A/DIV IBAT 0.5A/DIV VOUT 5V/DIV IIN 0.5A/DIV IBAT 0.5A/DIV 1ms/DIV VBAT = 3.85V IOUT = 100mA RPROG = 100k 40851 G23 100μs/DIV VBAT = 3.85V IOUT = 50mA 40851 G24 40851f 7 LTC4085-1 U U U PI FU CTIO S IN (Pin 1): Input Supply. Connect to USB supply, VBUS. Input current to this pin is limited to either 20% or 100% of the current programmed by the CLPROG pin as determined by the state of the HPWR pin. Charge current (to BAT pin) supplied through the input is set to the current programmed by the PROG pin but will be limited by the input current limit if charge current is set greater than the input current limit. OUT (Pin 2): Voltage Output. This pin is used to provide controlled power to a USB device from either USB VBUS (IN) or the battery (BAT) when the USB is not present. This pin can also be used as an input for battery charging when the USB is not present and a wall adapter is applied to this pin. OUT should be bypassed with at least 4.7μF to GND. CLPROG (Pin 3): Current Limit Program and Input Current Monitor. Connecting a resistor, RCLPROG, to ground programs the input to output current limit. The current limit is programmed as follows: ICL (A) = 1000V RCLPROG In USB applications the resistor RCLPROG should be set to no less than 2.1k. The voltage on the CLPROG pin is always proportional to the current flowing through the IN to OUT power path. This current can be calculated as follows: IIN(A) = VCLPROG • 1000 RCLPROG HPWR (Pin 4): High Power Select. This logic input is used to control the input current limit. A voltage greater than 1.2V on the pin will set the input current limit to 100% of the current programmed by the CLPROG pin. A voltage less than 0.4V on the pin will set the input current limit to 20% of the current programmed by the CLPROG pin. A 2μA pull-down is internally applied to this pin to ensure it is low at power up when the pin is not being driven externally. SUSP (Pin 5): Suspend Mode Input. Pulling this pin above 1.2V will disable the power path from IN to OUT. The supply current from IN will be reduced to comply with the USB specification for suspend mode. Both the ability to charge the battery from OUT and the ideal diode function (from BAT to OUT) will remain active. Suspend mode will reset the charge timer if VOUT is less than VBAT while in suspend mode. If VOUT is kept greater than VBAT, such as when a wall adapter is present, the charge timer will not be reset when the part is put in suspend. A 2μA pull-down is internally applied to this pin to ensure it is low at power up when the pin is not being driven externally. TIMER (Pin 6): Timer Capacitor. Placing a capacitor, CTIMER, to GND sets the timer period. The timer period is: t TIMER(Hours) = CTIMER • RPROG • 3Hours 0.1μF • 100k Charge time is increased if charge current is reduced due to undervoltage current limit, load current, thermal regulation and current limit selection (HPWR). Shorting the TIMER pin to GND disables the battery charging functions. 40851f 8 LTC4085-1 U U U PI FU CTIO S WALL (Pin 7): Wall Adapter Present Input. Pulling this pin above 4.25V will disconnect the power path from IN to OUT. The ACPR pin will also be pulled low to indicate that a wall adapter has been detected. NTC (Pin 8): Input to the NTC Thermistor Monitoring Circuits. The NTC pin connects to a negative temperature coeffcient thermistor which is typically co-packaged with the battery pack to determine if the battery is too hot or too cold to charge. If the battery’s temperature is out of range, charging is paused until the battery temperature reenters the valid range. A low drift bias resistor is required from VNTC to NTC and a thermistor is required from NTC to ground. If the NTC function is not desired, the NTC pin should be grounded. VNTC (Pin 9): Output Bias Voltage for NTC. A resistor from this pin to the NTC pin will bias the NTC thermistor. ACPR (Pin 10): Wall Adapter Present Output. Active low open drain output pin. A low on this pin indicates that the wall adapter input comparator has had its input pulled above the input threshold. This feature is disabled if no power is present on IN or OUT or BAT (i.e., below UVLO thresholds). CHRG (Pin 11): Open-Drain Charge Status Output. When the battery is being charged, the CHRG pin is pulled low by an internal N-channel MOSFET. When the timer runs out or the charge current drops below 10% of the programmed charge current (while in voltage mode) or the input supply or output supply is removed, the CHRG pin is forced to a high impedance state. PROG (Pin 12): Charge Current Program. Connecting a resistor, RPROG, to ground programs the battery charge current. The battery charge current is programmed as follows: ICHG(A) = 50, 000V RPROG GATE (Pin 13): External Ideal Diode Gate Pin. This pin can be used to drive the gate of an optional external PFET connected between BAT and OUT. By doing so, the impedance of the ideal diode between BAT and OUT can be reduced. When not in use, this pin should be left floating. It is important to maintain a high impedance on this pin and minimize all leakage paths. BAT (Pin 14): Connect to a single cell Li-Ion battery. This pin is used as an output when charging the battery and as an input when supplying power to OUT. When the OUT pin potential drops below the BAT pin potential, an ideal diode function connects BAT to OUT and prevents VOUT from dropping significantly below VBAT. A precision internal resistor divider sets the final float (charging) potential on this pin. The internal resistor divider is disconnected when IN and OUT are in undervoltage lockout. Exposed Pad (Pin 15): Ground. The exposed package pad is ground and must be soldered to the PC board for proper functionality and for maximum heat transfer. 40851f 9 LTC4085-1 W BLOCK DIAGRA VBUS 1 IN CURRENT LIMIT OUT ILIM_CNTL IIN 1000 1V 3 2k 4 SOFT_START + CL – CLPROG HPWR ENABLE CURRENT_CONTROL CC/CV REGULATOR CHARGER IN 500mA/100mA OUT BAT 25mV 2 25mV – +EDA GATE 13 IDEAL_DIODE ENABLE 105°C DIE TEMP 2μA – + ILIM + – + – BAT TA 14 SOFT_START2 CHARGE_CONTROL PROG + CHG – 12 100k – + 7 10 ICHRG + – 1V +– 25mV WALL ACPR VOLTAGE_DETECT 4.25V + – 0.25V + – 2.9V BATTERY UVLO + – 4.0V RECHARGE UVLO BAT_UV RECHRG 9 CONTROL_LOGIC – + 100k 8 TIMER OSCILLATOR 6 VNTC NTC – + 100k 0.1V + – CLK HOLD TOO C0LD NTCERR CHRG RESET COUNTER STOP 11 NTC TOO HOT 2μA NTC_ENABLE GND SUSP C/10 EOC 4085 BD 40851f 10 LTC4085-1 U OPERATIO The LTC4085-1 is a complete PowerPath controller for battery powered USB applications. The LTC4085-1 is designed to receive power from a USB source, a wall adapter, or a battery. It can then deliver power to an application connected to the OUT pin and a battery connected to the BAT pin (assuming that an external supply other than the battery is present). Power supplies that have limited current resources (such as USB VBUS supplies) should be connected to the IN pin which has a programmable current limit. Battery charge current will be adjusted to ensure that the sum of the charge current and load current does not exceed the programmed input current limit. An ideal diode function provides power from the battery when output/load current exceeds the input current limit or when input power is removed. Powering the load through the ideal diode instead of connecting the load directly to the battery allows a fully charged battery to remain fully charged until external power is removed. Once external power is removed the output drops until the ideal diode is forward biased. The forward biased ideal diode will then provide the output power to the load from the battery. Furthermore, powering switching regulator loads from the OUT pin (rather than directly from the battery) results in shorter battery charge times. This is due to the fact that switching regulators typically require constant input power. When this power is drawn from the OUT pin voltage (rather than the lower BAT pin voltage) the current consumed by the switching regulator is lower leaving more current available to charge the battery. The LTC4085-1 also has the ability to receive power from a wall adapter. Wall adapter power can be connected to the output (load side) of the LTC4085-1 through an external device such as a power Schottky or FET, as shown in Figure 1. The LTC4085-1 has the unique ability to use the output, which is powered by the wall adapter, as a path to charge the battery while providing power to the load. A wall adapter comparator on the LTC4085-1 can be configured to detect the presence of the wall adapter and shut off the connection to the USB to prevent reverse conduction out to the USB bus. 40851f 11 LTC4085-1 U OPERATIO WALL ADAPTER 10 4.25V (RISING) 3.15V (FALLING) ACPR – + WALL 7 + – USB VBUS 1 IN + – 75mV (RISING) 25mV (FALLING) ENABLE CURRENT LIMIT CONTROL OUT 2 LOAD CHRG CONTROL IDEAL DIODE BAT 14 40851 F01 + Li-Ion Figure 1: Simplified Block Diagram—PowerPath 40851f 12 LTC4085-1 U OPERATIO Table 1. Operating Modes—PowerPath States Current Limited Input Power (IN to OUT) WALL PRESENT SUSPEND VIN > 3.8V VIN > (VOUT + 100mV) VIN > (VBAT + 100mV) CURRENT LIMIT ENABLED Y X X X X N X Y X X X N X X N X X N X X X N X N X X X X N N N N Y Y Y Y Battery Charger (OUT to BAT) WALL PRESENT SUSPEND VOUT > 4.35V VOUT > (VBAT + 100mV) CHARGER ENABLED X X X X N X N X N N X X Y Y Y WALL PRESENT SUSPEND VIN VBAT > VOUT VBAT > 2.8V DIODE ENABLED X X X X N N X X X N X N X X X Y Y Y Ideal Diode (BAT to OUT) Operating Modes—Pin Currents vs Programmed Currents (Powered from IN) PROGRAMMING OUTPUT CURRENT BATTERY CURRENT INPUT CURRENT ICL = ICHG IOUT < ICL IOUT = ICL = ICHG IOUT > ICL IBAT = ICL – IOUT IBAT = 0 IBAT = ICL – IOUT IIN = IQ + ICL IIN = IQ + ICL IIN = IQ + ICL ICL > ICHG IOUT < (ICL – ICHG) IOUT > (ICL – ICHG) IOUT = ICL IOUT > ICL IBAT = ICHG IBAT = ICL – IOUT IBAT = 0 IBAT = ICL – IOUT IIN = IQ + ICHG + IOUT IIN = IQ + ICL IIN = IQ + ICL IIN = IQ + ICL ICL < ICHG IOUT < ICL IOUT > ICL IBAT = ICL – IOUT IBAT = ICL – IOUT IIN = IQ + ICL IIN = IQ + ICL 40851f 13 LTC4085-1 U OPERATIO USB Current Limit and Charge Current Control The current limit and charger control circuits of the LTC4085-1 are designed to limit input current as well as control battery charge current as a function of IOUT. The programmed current limit, ICL, is defined as: 1000 1000V ICL = • VCLPROG = RCLPROG RCLPROG The programmed battery charge current, ICHG, is defined as: 50,000 50,000V ICHG = • VPROG = R R PROG PROG Input current, IIN, is equal to the sum of the BAT pin output current and the OUT pin output current: The current limiting circuitry in the LTC4085-1 can and should be configured to limit current to 500mA for USB applications (selectable using the HPWR pin and programmed using the CLPROG pin). The LTC4085-1 reduces battery charge current such that the sum of the battery charge current and the load current does not exceed the programmed input current limit (onefifth of the programmed input current limit when HPWR is low, see Figure 2). The battery charge current goes to zero when load current exceeds the programmed input current limit (one-fifth of the limit when HPWR is low). If the load current is greater than the current limit, the output voltage will drop to just under the battery voltage where the ideal diode circuit will take over and the excess load current will be drawn from the battery. IIN = IOUT + IBAT 120 600 IIN 500 600 IIN 100 500 IIN 80 200 IBAT CHARGING 400 ILOAD 60 40 IBAT CHARGING CURRENT (mA) ILOAD 300 CURRENT (mA) CURRENT (mA) 400 ILOAD 300 200 100 20 100 0 0 0 –100 –20 0 100 200 300 400 ILOAD (mA) 500 600 IBAT (IDEAL DIODE) 40851 F02a (2a) High Power Mode/Full Charge RPROG = 100k and RCLPROG = 2k 0 20 40 60 80 ILOAD (mA) 100 120 IBAT (IDEAL DIODE) IBAT = ICHG –100 IBAT CHARGING 0 100 40851 F02b (2b) Low Power Mode/Full Charge RPROG = 100k and RCLPROG = 2k 200 IBAT = ICL – IOUT 300 400 ILOAD (mA) 500 600 IBAT (IDEAL DIODE) 40851 F02c (2c) High Power Mode with ICL = 500mA and ICHG = 250mA RPROG = 100k and RCLPROG = 2k Figure 2: Input and Battery Currents as a Function of Load Current 40851f 14 LTC4085-1 U OPERATIO Programming Current Limit The formula for input current limit is: 1000 1000V ICL = • VCLPROG = RCLPROG RCLPROG where VCLPROG is the CLPROG pin voltage and RCLPROG is the total resistance from the CLPROG pin to ground. For example, if typical 500mA current limit is required, calculate: RCLPROG = 1V • 1000 = 2k 500mA In USB applications, the minimum value for RCLPROG should be 2.1k. This will prevent the application current from exceeding 500mA due to LTC4085-1 tolerances and quiescent currents. A 2.1k CLPROG resistor will give a typical current limit of 476mA in high power mode (HPWR = 1) or 95mA in low power mode (HPWR = 0). VCLPROG will track the input current according to the following equation: IIN = VCLPROG • 1000 RCLPROG For best stability over temperature and time, 1% metal film resistors are recommended. significantly below the BAT pin voltage. A comparison of the I-V curve of the ideal diode and a Schottky diode can be seen in Figure 3. If the input current increases beyond the programmed input current limit additional current will be drawn from the battery via the internal ideal diode. Furthermore, if power to IN (USB VBUS) or OUT (external wall adapter) is removed, then all of the application power will be provided by the battery via the ideal diode. A 4.7μF capacitor at OUT is sufficient to keep a transition from input power to battery power from causing significant output voltage droop. The ideal diode consists of a precision amplifier that enables a large P-Channel MOSFET transistor whenever the voltage at OUT is approximately 20mV (VFWD) below the voltage at BAT. The resistance of the internal ideal diode is approximately 200mΩ. If this is sufficient for the application then no external components are necessary. However, if more conductance is needed, an external PFET can be added from BAT to OUT. The GATE pin of the LTC4085-1 drives the gate of the PFET for automatic ideal diode control. The source of the external PFET should be connected to OUT and the drain should be connected to BAT. In order to help protect the external PFET in overcurrent situations, it should be placed in close thermal contact to the LTC4085-1. IMAX Ideal Diode from BAT to OUT SLOPE: 1/RDIO(ON) CURRENT (A) The LTC4085-1 has an internal ideal diode as well as a controller for an optional external ideal diode. If a battery is the only power supply available or if the load current exceeds the programmed input current limit, then the battery will automatically deliver power to the load via an ideal diode circuit between the BAT and OUT pins. The ideal diode circuit (along with the recommended 4.7μF capacitor on the OUT pin) allows the LTC4085-1 to handle large transient loads and wall adapter or USB VBUS connect/disconnect scenarios without the need for large bulk capacitors. The ideal diode responds within a few microseconds and prevents the OUT pin voltage from dropping SCHOTTKY DIODE 40851 F03 VFWD FORWARD VOLTAGE (V) (BAT-OUT) Figure 3. LTC4085-1 Schottky Diode vs Forward Voltage Drop 40851f 15 LTC4085-1 U OPERATIO Battery Charger The battery charger circuits of the LTC4085-1 are designed for charging single cell lithium-ion batteries. Featuring an internal P-channel power MOSFET, the charger uses a constant-current/constant-voltage charge algorithm with programmable current and a programmable timer for charge termination. Charge current can be programmed up to 1.5A. The final float voltage accuracy is ±0.8% typical. No blocking diode or sense resistor is required when powering the IN pin. The CHRG open-drain status output provides information regarding the charging status of the LTC4085-1 at all times. An NTC input provides the option of charge qualification using battery temperature. An internal thermal limit reduces the programmed charge current if the die temperature attempts to rise above a preset value of approximately 105°C. This feature protects the LTC4085-1 from excessive temperature, and allows the user to push the limits of the power handling capability of a given circuit board without risk of damaging the LTC4085-1. Another benefit of the LTC4085-1 thermal limit is that charge current can be set according to typical, not worst-case, ambient temperatures for a given application with the assurance that the charger will automatically reduce the current in worst-case conditions. The charge cycle begins when the voltage at the OUT pin rises above the output UVLO level and the battery voltage is below the recharge threshold. No charge current actually flows until the OUT voltage is greater than the output UVLO level and 100mV above the BAT voltage. At the beginning of the charge cycle, if the battery voltage is below 2.8V, the charger goes into trickle charge mode to bring the cell voltage up to a safe level for charging. The charger goes into the fast charge constant-current mode once the voltage on the BAT pin rises above 2.8V. In constant- current mode, the charge current is set by RPROG. When the battery approaches the final float voltage, the charge current begins to decrease as the LTC4085-1 switches to constant-voltage mode. When the charge current drops below 10% of the programmed charge current while in constant-voltage mode the CHRG pin assumes a high impedance state. An external capacitor on the TIMER pin sets the total minimum charge time. When this time elapses the charge cycle terminates and the CHRG pin assumes a high impedance state, if it has not already done so. While charging in constant-current mode, if the charge current is decreased by thermal regulation or in order to maintain the programmed input current limit the charge time is automatically increased. In other words, the charge time is extended inversely proportional to charge current delivered to the battery. For Li-Ion and similar batteries that require accurate final float potential, the internal bandgap reference, voltage amplifier and the resistor divider provide regulation with ±0.8% accuracy. Trickle Charge and Defective Battery Detection At the beginning of a charge cycle, if the battery voltage is low (below 2.8V) the charger goes into trickle charge reducing the charge current to 10% of the full-scale current. If the low battery voltage persists for one quarter of the total charge time, the battery is assumed to be defective, the charge cycle is terminated and the CHRG pin output assumes a high impedance state. If for any reason the battery voltage rises above ~2.8V the charge cycle will be restarted. To restart the charge cycle (i.e. when the dead battery is replaced with a discharged battery), simply remove the input voltage and reapply it or cycle the TIMER pin to 0V. 40851f 16 LTC4085-1 U OPERATIO Programming Charge Current The formula for the battery charge current is: ICHG = (IPROG ) • 50, 000 = VPROG • 50, 000 RPROG where VPROG is the PROG pin voltage and RPROG is the total resistance from the PROG pin to ground. Keep in mind that when the LTC4085-1 is powered from the IN pin, the programmed input current limit takes precedent over the charge current. In such a scenario, the charge current cannot exceed the programmed input current limit. For example, if typical 500mA charge current is required, calculate: 1V RPROG = • 50,000 = 100k 500mA For best stability over temperature and time, 1% metal film resistors are recommended. Under trickle charge conditions, this current is reduced to 10% of the fullscale value. The Charge Timer The programmable charge timer is used to terminate the charge cycle. The timer duration is programmed by an external capacitor at the TIMER pin. The charge time is typically: tTIMER (Hours) = The timer starts when an input voltage greater than the undervoltage lockout threshold level is applied or when leaving shutdown and the voltage on the battery is less than the recharge threshold. At power up or exiting shutdown with the battery voltage less than the recharge threshold the charge time is a full cycle. If the battery is greater than the recharge threshold the timer will not start and charging is prevented. If after power-up the battery voltage drops below the recharge threshold or if after a charge cycle the battery voltage is still below the recharge threshold the charge time is set to one half of a full cycle. The LTC4085-1 has a feature that extends charge time automatically. Charge time is extended if the charge current in constant-current mode is reduced due to load current or thermal regulation. This change in charge time is inversely proportional to the change in charge current. As the LTC4085-1 approaches constant-voltage mode the charge current begins to drop. This change in charge current is due to normal charging operation and does not affect the timer duration. Once a time-out occurs and the voltage on the battery is greater than the recharge threshold, the charge current stops, and the CHRG output assumes a high impedance state if it has not already done so. Connecting the TIMER pin to ground disables the battery charger. CTIMER • RPROG • 3Hours 0.1μF • 100k 40851f 17 LTC4085-1 U OPERATIO CHRG Status Output Pin When the charge cycle starts, the CHRG pin is pulled to ground by an internal N-channel MOSFET capable of driving an LED. When the charge current drops below 10% of the programmed full charge current while in constant-voltage mode, the pin assumes a high impedance state (but charge current continues to flow until the charge time elapses). If this state is not reached before the end of the programmable charge time, the pin will assume a high impedance state when a time-out occurs. The CHRG current detection threshold can be calculated by the following equation: IDETECT = 0.1V 5000V • 50, 000 = RPROG RPROG For example, if the full charge current is programmed to 500mA with a 100k PROG resistor the CHRG pin will change state at a battery charge current of 50mA. Note: The end-of-charge (EOC) comparator that monitors the charge current latches its decision. Therefore, the first time the charge current drops below 10% of the programmed full charge current while in constant-voltage mode will toggle CHRG to a high impedance state. If, for some reason, the charge current rises back above the threshold the CHRG pin will not resume the strong pull-down state. The EOC latch can be reset by a recharge cycle (i.e. VBAT drops below the recharge threshold) or toggling the input power to the part. Current Limit Undervoltage Lockout An internal undervoltage lockout circuit monitors the input voltage and disables the input current limit circuits until VIN rises above the undervoltage lockout threshold. The current limit UVLO circuit has a built-in hysteresis of 125mV. Furthermore, to protect against reverse current in the power MOSFET, the current limit UVLO circuit disables the current limit (i.e. forces the input power path to a high impedance state) if VOUT exceeds VIN. If the current limit UVLO comparator is tripped, the current limit circuits will not come out of shutdown until VOUT falls 50mV below the VIN voltage. Charger Undervoltage Lockout An internal undervoltage lockout circuit monitors the VOUT voltage and disables the battery charger circuits until VOUT 18 rises above the undervoltage lockout threshold. The battery charger UVLO circuit has a built-in hysteresis of 125mV. Furthermore, to protect against reverse current in the power MOSFET, the charger UVLO circuit keeps the charger shut down if VBAT exceeds VOUT. If the charger UVLO comparator is tripped, the charger circuits will not come out of shut down until VOUT exceeds VBAT by 50mV. Suspend The LTC4085-1 can be put in suspend mode by forcing the SUSP pin greater than 1.2V. In suspend mode the ideal diode function from BAT to OUT is kept alive. If power is applied to the OUT pin externally (i.e., a wall adapter is present) then charging will be unaffected. Current drawn from the IN pin is reduced to 50μA. Suspend mode is intended to comply with the USB power specification mode of the same name. NTC Thermistor—Battery Temperature Charge Qualification The battery temperature is measured by placing a negative temperature coefficient (NTC) thermistor close to the battery pack. The NTC circuitry is shown in Figure 4. To use this feature, connect the NTC thermistor (RNTC) between the NTC pin and ground and a resistor (RNOM) from the NTC pin to VNTC. RNOM should be a 1% resistor with a value equal to the value of the chosen NTC thermistor at 25°C (this value is 10k for a Vishay NTHS0603N02N1002J thermistor). The LTC4085-1 goes into hold mode when the resistance (RHOT) of the NTC thermistor drops to 0.48 times the value of RNOM, or approximately 4.8k, which should be at 45°C. The hold mode freezes the timer and stops the charge cycle until the thermistor indicates a return to a valid temperature. As the temperature drops, the resistance of the NTC thermistor rises. The LTC4085-1 is designed to go into hold mode when the value of the NTC thermistor increases to 2.82 times the value of RNOM. This resistance is RCOLD. For a Vishay NTHS0603N02N1002J thermistor, this value is 28.2k which corresponds to approximately 0°C. The hot and cold comparators each have approximately 2°C of hysteresis to prevent oscillation about the trip point. Grounding the NTC pin will disable the NTC function. 40851f LTC4085-1 U U W U APPLICATIO S I FOR ATIO VNTC LTC4085-1 VNTC 9 RNOM 10k NTC LTC4085-1 9 0.738 • VNTC – TOO_COLD 0.738 • VNTC RNOM 124k NTC – TOO_COLD 8 + 8 + RNTC 10k – R1 24.3k – TOO_HOT 0.326 • VNTC TOO_HOT 0.326 • VNTC + + RNTC 100k + + NTC_ENABLE NTC_ENABLE – 0.1V – 0.1V 40851 F04a (4a) 40851 F04b (4b) Figure 4. NTC Circuits Alternate NTC Thermistors The LTC4085-1 NTC trip points were designed to work with thermistors whose resistance-temperature characteristics follow Vishay Dale’s “R-T Curve 2.” The Vishay NTHS0603N02N1002J is an example of such a thermistor. However, Vishay Dale has many thermistor products that follow the “R-T Curve 2” characteristic in a variety of sizes. Furthermore, any thermistor whose ratio of RCOLD to RHOT is about 6.0 will also work (Vishay Dale R-T Curve 2 shows a ratio of 2.816/0.4839 = 5.82). Power conscious designs may want to use thermistors whose room temperature value is greater than 10k. Vishay Dale has a number of values of thermistor from 10k to 100k that follow the “R-T Curve 1.” Using these as indicated in the NTC Thermistor section will give temperature trip points of approximately 3°C and 42°C, a delta of 39°C. This delta in temperature can be moved in either direction by changing the value of RNOM with respect to RNTC. Increasing RNOM will move both trip points to lower temperatures. Likewise, a decrease in RNOM with respect to RNTC will move the trip points to higher temperatures. To calculate RNOM for a shift to lower temperature, for example, use the following equation: RNOM = R COLD • RNTC at 25 °C 2 . 816 where RCOLD is the resistance ratio of RNTC at the desired cold temperature trip point. To shift the trip points to higher temperatures use the following equation: RNOM = RHOT • RNTC at 25 °C 0 . 484 where RHOT is the resistance ratio of RNTC at the desired hot temperature trip point. The following example uses a 100K R-T Curve 1 Thermistor from Vishay Dale. The difference between the trip points is 39°C, from before—and the desired cold trip point of 0°C, would put the hot trip point at about 39°C. The RNOM needed is calculated as follows: RNOM = RCOLD •R at 25°C = 2.816 NTC 3.266 • 100kΩ = 116kΩ 2.816 40851f 19 LTC4085-1 U W U U APPLICATIO S I FOR ATIO The nearest 1% value for RNOM is 115k. This is the value used to bias the NTC thermistor to get cold and hot trip points of approximately 0°C and 39°C, respectively. To extend the delta between the cold and hot trip points, a resistor (R1) can be added in series with RNTC (see Figure 4). The values of the resistors are calculated as follows: RNOM R − RHOT = COLD 2.816 − 0.484 0.484 ⎡ ⎤ R1= ⎢ ⎥ • [RCOLD − RHOT ] − RHOT ⎣ 2.816 − 0.484 ⎦ where RNOM is the value of the bias resistor, RHOT and RCOLD are the values of RNTC at the desired temperature trip points. Continuing the forementioned example with a desired hot trip point of 50°C: RNOM = = R COLD R HOT 2.816 0.484 100k • (3.266 0.3602) 2.816 0.484 = 124.6k,124k nearest 1% 0.484 2.816 0.484 • R1= 100k • ( 3.266 0.3602) 0.3602 = 24.3k The final solution is shown in Figure 4, where RNOM = 124k, R1 = 24.3k and RNTC = 100k at 25°C Using the WALL Pin to Detect the Presence of a Wall Adapter The WALL input pin identifies the presence of a wall adapter (the pin should be tied directly to the adapter output voltage). This information is used to disconnect the input pin, IN, from the OUT pin in order to prevent back conduction to whatever may be connected to the input. It also forces the ACPR pin low when the voltage at the WALL pin exceeds the input threshold. In order for the presence of a wall adapter to be acknowledged, both of the following conditions must be satisfied: 1. The WALL pin voltage exceeds VWAR (approximately 4.25V); and 2. The WALL pin voltage exceeds VWDR (approximately 75mV above VBAT) The input power path (between IN and OUT) is re-enabled and the ACPR pin assumes a high impedance state when either of the following conditions is met: 1. The WALL pin voltage falls below VWDF (approximately 25mV above VBAT); or 2. The WALL pin voltage falls below VWAF (approximately 3.12V) Each of these thresholds is suitably filtered in time to prevent transient glitches on the WALL pin from falsely triggering an event. Power Dissipation The conditions that cause the LTC4085-1 to reduce charge current due to the thermal protection feedback can be approximated by considering the power dissipated in the part. For high charge currents and a wall adapter applied to VOUT, the LTC4085-1 power dissipation is approximately: PD = (VOUT – VBAT) • IBAT Where, PD is the power dissipated, VOUT is the supply voltage, VBAT is the battery voltage, and IBAT is the battery charge current. It is not necessary to perform any worstcase power dissipation scenarios because the LTC4085-1 will automatically reduce the charge current to maintain the die temperature at approximately 105°C. However, the approximate ambient temperature at which the thermal feedback begins to protect the IC is: TA = 105°C – PD • θJA TA = 105°C – (VOUT – VBAT) • IBAT • θJA 40851f 20 LTC4085-1 U W U U APPLICATIO S I FOR ATIO Example: Consider an LTC4085-1 operating from a wall adapter with 5V at VOUT providing 0.8A to a 3V Li-Ion battery. The ambient temperature above which the LTC4085-1 will begin to reduce the 0.8A charge current, is approximately TA = 105°C – (5V – 3V) • 0.8A • 37°C/W TA = 105°C – 1.6W • 37°C/W = 105°C – 59°C = 46°C The LTC4085-1 can be used above 46°C, but the charge current will be reduced below 0.8A. The charge current at a given ambient temperature can be approximated by: IBAT = 105°C – TA ( VOUT – VBAT ) • θJA Consider the above example with an ambient temperature of 55°C. The charge current will be reduced to approximately: IBAT = 105°C – 55°C 50°C = = 0.675A (5V – 3V) • 37°C/W 74°C/A Board Layout Considerations In order to be able to deliver maximum charge current under all conditions, it is critical that the Exposed Pad on the backside of the LTC4085-1 package is soldered to the board. Correctly soldered to a 2500mm2 double-sided 1oz. copper board the LTC4085-1 has a thermal resistance of approximately 37°C/W. Failure to make thermal contact between the Exposed Pad on the backside of the package and the copper board will result in thermal resistances far greater than 37°C/W. As an example, a correctly soldered LTC4085-1 can deliver over 1A to a battery from a 5V supply at room temperature. Without a backside thermal connection, this number could drop to less than 500mA. VIN and Wall Adapter Bypass Capacitor Many types of capacitors can be used for input bypassing. However, caution must be exercised when using multilayer ceramic capacitors. Because of the self resonant and high Q characteristics of some types of ceramic capacitors, high voltage transients can be generated under some start-up conditions, such as connecting the charger input to a hot power source. For more information, refer to Application Note 88. Stability The constant-voltage mode feedback loop is stable without any compensation when a battery is connected. However, a 4.7μF capacitor with a 1Ω series resistor to GND is recommended at the BAT pin to keep ripple voltage low when the battery is disconnected. 40851f 21 LTC4085-1 U TYPICAL APPLICATIO USB Power Control Application with Wall Adapter Input 5V WALL ADAPTER INPUT 4.7μF 1k 510Ω TO LDOs REGs, ETC 4.7μF 510Ω 1Ω* 5V (NOM) FROM USB CABLE VBUS OUT IN 4.7μF CHRG GATE ACPR 1Ω* WALL BAT VNTC LTC4085-1 RNTCBIAS 10k + Li-Ion CELL NTC RNTC 10k SUSPEND USB POWER SUSP 500mA/100mA SELECT HPWR PROG *SERIES 1Ω RESISTOR ONLY NEEDED FOR INDUCTIVE INPUT SUPPLIES CLPROG RPROG 71.5k TIMER GND RCLPROG 2.1k 0.15μF 40851 TA02 40851f 22 LTC4085-1 U PACKAGE DESCRIPTIO DE Package 14-Lead Plastic DFN (4mm × 3mm) (Reference LTC DWG # 05-08-1708 Rev B) 0.70 ±0.05 3.30 ±0.05 3.60 ±0.05 2.20 ±0.05 1.70 ± 0.05 PACKAGE OUTLINE 0.25 ± 0.05 0.50 BSC 3.00 REF RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED R = 0.115 TYP 4.00 ±0.10 (2 SIDES) R = 0.05 TYP 3.00 ±0.10 (2 SIDES) 0.40 ± 0.10 8 14 3.30 ±0.10 1.70 ± 0.10 PIN 1 NOTCH R = 0.20 OR 0.35 × 45° CHAMFER PIN 1 TOP MARK (SEE NOTE 6) (DE14) DFN 0806 REV B 7 0.200 REF 1 0.25 ± 0.05 0.50 BSC 0.75 ±0.05 3.00 REF 0.00 – 0.05 BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING PROPOSED TO BE MADE VARIATION OF VERSION (WGED-3) IN JEDEC PACKAGE OUTLINE MO-229 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 40851f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 23 LTC4085-1 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS Battery Chargers LTC1733 Monolithic Lithium-Ion Linear Battery Charger Standalone Charger with Programmable Timer, Up to 1.5A Charge Current TM LTC1734 Lithium-Ion Linear Battery Charger in ThinSOT Simple ThinSOT Charger, No Blocking Diode, No Sense Resistor Needed LTC1734L Lithium-Ion Linear Battery Charger in ThinSOT Low Current Version of LTC1734; 50mA ≤ ICHRG ≤ 180mA LTC4002 Switch Mode Lithium-Ion Battery Charger Standalone, 4.7V ≤ VIN ≤ 24 V, 500kHz Frequency, 3 Hour Charge Termination LTC4052 Monolithic Lithium-Ion Battery Pulse Charger No Blocking Diode or External Power FET Required, ≤ 1.5A Charge Current LTC4053 USB Compatible Monolithic Li-Ion Battery Charger Standalone Charger with Programmable Timer, Up to 1.25A Charge Current LTC4054 Standalone Linear Li-Ion Battery Charger with Integrated Pass Transistor in ThinSOT Thermal Regulation Prevents Overheating, C/10 Termination, C/10 Indicator, Up to 800mA Charge Current LTC4057 Lithium-Ion Linear Battery Charger Up to 800mA Charge Current, Thermal Regulation, ThinSOT Package LTC4058 Standalone 950mA Lithium-Ion Charger in DFN C/10 Charge Termination, Battery Kelvin Sensing, ±7% Charge Accuracy LTC4059 900mA Linear Lithium-Ion Battery Charger 2mm × 2mm DFN Package, Thermal Regulation, Charge Current Monitor Output LTC4065/LTC4065A Standalone Li-Ion Battery Chargers in 2 × 2 DFN 4.2V, ±0.6% Float Voltage, Up to 750mA Charge Current, 2mm × 2mm DFN, “A” Version has ACPR Function. LTC4411/LTC4412 Low Loss PowerPath Controller in ThinSOT Automatic Switching Between DC Sources, Load Sharing, Replaces ORing Diodes Power Management LTC3405/LTC3405A 300mA (IOUT), 1.5 MHz, Synchronous Step-Down 95% Efficiency, VIN = 2.7V to 6V, VOUT = 0.8V, IQ = 20μA, ISD < 1μA, DC/DC Converter ThinSOT Package LTC3406/LTC3406A 600mA (IOUT), 1.5 MHz, Synchronous Step-Down 95% Efficiency, VIN = 2.5V to 5.5V, VOUT = 0.6V, IQ = 20μA, ISD < 1μA, DC/DC Converter ThinSOT Package LTC3411 1.25A (IOUT), 4 MHz, Synchronous Step-Down DC/DC Converter 95% Efficiency, VIN = 2.5V to 5.5V, VOUT = 0.8V, IQ = 60μA, ISD < 1μA, MS10 Package LTC3440 600mA (IOUT), 2 MHz, Synchronous Buck-Boost DC/DC Converter 95% Efficiency, VIN = 2.5V to 5.5V, VOUT = 2.5V, IQ = 25μA, ISD < 1μA, MS Package LTC3455 Dual DC/DC Converter with USB Power Manager and Li-Ion Battery Charger Seamless Transition Between Power Souces: USB, Wall Adapter and Battery; 95% Efficient DC/DC Conversion LTC4055 USB Power Controller and Battery Charger Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal Regulation, 200mΩ Ideal Diode, 4mm × 4mm QFN16 Package LTC4066 USB Power Controller and Battery Charger Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal Regulation, 50mΩ Ideal Diode, 4mm × 4mm QFN24 Package LTC4085 USB Power Manager with Ideal Diode Controller and Li-Ion Charger Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal Regulation, 200mΩ Ideal Diode with <50mΩ Option, 4mm × 3mm DFN14 Package LTC4089/LTC4089-1/ High Voltage USB Power Manager with Ideal High Efficiency 1.2A Charger from 6V to 36V (40V max) Input Charges Single LTC4089-5 Diode Controller and High Efficiency Li-Ion Battery Cell Li-Ion Batteries Directly from a USB Port, Thermal Regulation; 200mΩ Charger Ideal Diode with <50mΩ option, 3mm × 4mm DFN-14 Package, Bat-Track™ Adaptive Output Control (LTC4089/-1); Fixed 5V Output (LTC4089-5) “-1” for 4.1V Float Voltage Batteries LTC4090 High Voltage USB Power Manager with Ideal High Efficiency 1.2A Charger from 6V to 36V (60V max) Input Charges Single Diode Controller and High Efficiency Li-Ion Battery Cell Li-Ion Batteries Directly from a USB Port, Thermal Regulation; 200mΩ Charger Ideal Diode with <50mΩ option, 3mm × 4mm DFN-14 Package, Bat-Track Adaptive Output Control Bat-Track and ThinSOT are trademarks of Linear Technology Corporation. 40851f 24 Linear Technology Corporation LT 1007 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2006