MAXIM MAX4410EUD

19-2386; Rev 2; 10/02
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Features
♦ No Bulky DC-Blocking Capacitors Required
♦ Ground-Referenced Outputs Eliminate DC-Bias
Voltages on Headphone Ground Pin
♦ No Degradation of Low-Frequency Response Due
to Output Capacitors
♦ 80mW Per Channel into 16Ω
♦ Low 0.003% THD + N
♦ High PSRR (90dB at 1kHz)
♦ Integrated Click-and-Pop Suppression
♦ 1.8V to 3.6V Single-Supply Operation
♦ Low Quiescent Current
♦ Independent Left/Right, Low-Power
Shutdown Controls
♦ Short-Circuit and Thermal Overload Protection
♦ ±8kV ESD-Protected Amplifier Outputs
♦ Available in Space-Saving Packages
16-Bump UCSP (2mm x 2mm x 0.6mm)
14-Pin TSSOP
The MAX4410 operates from a single 1.8V to 3.6V supply,
consumes only 7mA of supply current, has short-circuit
and thermal overload protection, and is specified over the
extended -40°C to +85°C temperature range. The
MAX4410 is available in a tiny (2mm x 2mm x 0.6mm),
16-bump chip-scale package (UCSP™) and a 14-pin
TSSOP package.
Ordering Information
Applications
Notebooks
Cellular Phones
PDAs
MP3 Players
Web Pads
Portable Audio Equipment
PART
MAX4410EBE-T*
MAX4410EUD
TEMP RANGE
PIN/BUMPPACKAGE
-40°C to +85°C
-40°C to +85°C
16 UCSP-16
14 TSSOP
*Future product—contact factory for availability.
Functional Diagram
MAX4410
LEFT
AUDIO
INPUT
SHDNL
SHDNR
RIGHT
AUDIO
INPUT
UCSP is a trademark of Maxim Integrated Products, Inc.
Pin Configurations and Typical Application Circuit appear
at end of data sheet.
________________________________________________________________ Maxim Integrated Products
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
1
MAX4410
General Description
The MAX4410 stereo headphone driver is designed for
portable equipment where board space is at a
premium. The MAX4410 uses a unique, patented,
DirectDrive architecture to produce a ground-referenced output from a single supply, eliminating the need
for large DC-blocking capacitors, saving cost, board
space, and component height.
The MAX4410 delivers up to 80mW per channel into a
16Ω load and has low 0.003% THD + N. A high powersupply rejection ratio (90dB at 1kHz) allows this device to
operate from noisy digital supplies without an additional
linear regulator. The MAX4410 includes ±8kV ESD protection on the headphone outputs. Comprehensive clickand-pop circuitry suppresses audible clicks and pops on
startup and shutdown. Independent left/right, low-power
shutdown controls make it possible to optimize power
savings in mixed mode, mono/stereo applications.
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
ABSOLUTE MAXIMUM RATINGS
Continuous Power Dissipation (TA = +70°C)
14-Pin TSSOP (derate 9.1mW/°C above +70°C) ..........727mW
16-Bump UCSP (derate 15.2mW/°C above +70°C)....1212mW
Junction Temperature ......................................................+150°C
Operating Temperature Range ...........................-40°C to +85°C
Storage Temperature Range .............................-65°C to +150°C
Bump Temperature (soldering) (Note 1)
Infrared (15s) ...............................................................+220°C
Vapor Phase (60s) .......................................................+215°C
Lead Temperature (soldering, 10s) .................................+300°C
PGND to SGND .....................................................-0.3V to +0.3V
PVDD to SVDD .................................................................-0.3V to +0.3V
PVSS to SVSS .........................................................-0.3V to +0.3V
PVDD and SVDD to PGND or SGND .........................-0.3V to +4V
PVSS and SVSS to PGND or SGND ..........................-4V to +0.3V
IN_ to SGND ..........................................................-0.3V to +0.3V
SHDN_ to SGND........................(SGND - 0.3V) to (SVDD + 0.3V)
OUT_ to SGND ............................(SVSS - 0.3V) to (SVDD + 0.3V)
C1P to PGND.............................(PGND - 0.3V) to (PVDD + 0.3V)
C1N to PGND .............................(PVSS - 0.3V) to (PGND + 0.3V)
Output Short Circuit to GND or VDD ...........................Continuous
Note 1: This device is constructed using a unique set of packaging techniques that impose a limit on the thermal profile the device
can be exposed to during board-level solder attach and rework. This limit permits only the use of the solder profiles recommended in the industry-standard specification, JEDEC 020A, paragraph 7.6, Table 3 for IR/VPR and convection reflow.
Preheating is required. Hand or wave soldering is not allowed.
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(PVDD = SVDD = 3V, PGND = SGND = 0, SHDNL = SHDNR = SVDD, C1 = C2 = 2.2µF, RIN = RF = 10kΩ, RL = ∞, TA = TMIN to TMAX,
unless otherwise noted. Typical values are at TA = +25°C.) (Note 2)
PARAMETER
Supply Voltage Range
SYMBOL
VDD
Quiescent Supply Current
IDD
Shutdown Supply Current
I SHDN
CONDITIONS
Guaranteed by PSRR test
MIN
TYP
1.8
UNITS
3.6
V
One channel enabled
4
Two channels enabled
7
11.5
SHDNL = SHDNR = GND
6
10
0.7 x
SVDD
VIH
SHDN_ Thresholds
mA
µA
V
0.3 x
SVDD
VIL
SHDN_ Input Leakage Current
SHDN_ to Full Operation
MAX
-1
tSON
+1
175
µA
µs
CHARGE PUMP
Oscillator Frequency
fOSC
272
320
368
kHz
0.5
2.4
mV
+100
nA
AMPLIFIERS
Input Offset Voltage
VOS
Input Bias Current
IBIAS
Input AC-coupled, RL = 32Ω
-100
1.8V ≤ VDD ≤ 3.6V
Power-Supply Rejection Ratio
Output Power
2
PSRR
POUT
200mVP-P ripple
THD + N = 1%
DC
75
fRIPPLE = 1kHz
90
90
fRIPPLE = 20kHz
55
RL = 32Ω
65
RL = 16Ω
40
80
_______________________________________________________________________________________
dB
mW
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
(PVDD = SVDD = 3V, PGND = SGND = 0, SHDNL = SHDNR = SVDD, C1 = C2 = 2.2µF, RIN = RF = 10kΩ, RL = ∞, TA = TMIN to TMAX,
unless otherwise noted. Typical values are at TA = +25°C.) (Note 2)
PARAMETER
SYMBOL
Total Harmonic Distortion Plus
Noise
CONDITIONS
THD + N
Signal-to-Noise Ratio
fIN = 1kHz
SNR
MIN
TYP
RL = 32Ω,
POUT = 25mW
0.003
RL = 16Ω,
POUT = 50mW
0.003
MAX
UNITS
%
RL = 32Ω, POUT = 20mW, fIN = 1kHz
95
dB
0.8
V/µs
No sustained oscillations
300
pF
RL = 16Ω, POUT = 1.6mW, fIN = 10kHz
70
dB
Thermal Shutdown Threshold
140
°C
Thermal Shutdown Hysteresis
15
°C
±8
kV
Slew Rate
SR
Maximum Capacitive Load
CL
Crosstalk
ESD Protection
Human body model (OUTR, OUTL)
Note 2: All specifications are 100% tested at TA = +25°C; temperature limits are guaranteed by design.
Typical Operating Characteristics
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
MAX4410 toc01
1
1
VDD = 3V
AV = -1V/V
RL = 16Ω
1
VDD = 3V
AV = -2V/V
RL = 16Ω
THD + N (%)
POUT = 50mW
POUT = 10mW
THD + N (%)
POUT = 25mW
POUT = 25mW
0.01
POUT = 10mW
VDD = 3V
AV = -1V/V
RL = 32Ω
0.1
0.1
THD + N (%)
0.1
0.01
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
MAX4410 toc02
POUT = 5mW
0.01
POUT = 10mW
0.001
POUT = 25mW
POUT = 50mW
0.001
0.001
10
100
MAX4410 toc03
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
1k
FREQUENCY (Hz)
10k
100k
0.0001
10
100
1k
FREQUENCY (Hz)
10k
100k
10
100
1k
10k
100k
FREQUENCY (Hz)
_______________________________________________________________________________________
3
MAX4410
ELECTRICAL CHARACTERISTICS (continued)
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
VDD = 3V
AV = -2V/V
RL = 32Ω
VDD = 1.8V
AV = -2V/V
RL = 16Ω
0.1
THD + N (%)
POUT = 5mW
POUT = 5mW
POUT = 10mW
0.01
POUT = 10mW
100
1k
POUT = 10mW
0.01
POUT = 20mW
0.001
0.001
10k
10
100k
100
1k
10k
10
100k
100
1k
10k
100k
FREQUENCY (Hz)
FREQUENCY (Hz)
FREQUENCY (Hz)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
VDD = 1.8V
AV = -1V/V
RL = 32Ω
VDD = 1.8V
AV = -2V/V
RL = 32Ω
100
MAX4410 toc09
1
MAX4410 toc07
1
MAX4410 toc08
10
POUT = 5mW
POUT = 20mW
POUT = 25mW
0.001
VDD = 3V
AV = -1V/V
RL = 16Ω
fIN = 20Hz
10
THD + N (%)
POUT = 20mW
POUT = 10mW
0.01
POUT = 5mW
THD + N (%)
0.1
0.1
THD + N (%)
THD + N (%)
0.1
0.01
MAX4410 toc06
1
VDD = 1.8V
AV = -1V/V
RL = 16Ω
0.1
THD + N (%)
MAX4410 toc05
1
MAX4410 toc04
1
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
POUT = 5mW
0.01
1
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
0.1
POUT = 10mW
0.01
ONE
CHANNEL
POUT = 20mW
0.001
0.001
10
100
1k
10k
10k
100k
50
100
150
200
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
THD + N (%)
1
OUTPUTS IN
PHASE
0.1
OUTPUTS
180° OUT OF
PHASE
150
OUTPUT POWER (mW)
MAX4410 toc12
0.1
ONE
CHANNEL
0.001
0.001
100
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
ONE
CHANNEL
0.001
50
1
0.01
0.01
ONE
CHANNEL
VDD = 3V
AV = -2V/V
RL = 16Ω
fIN = 20Hz
10
THD + N (%)
VDD = 3V
AV = -1V/V
RL = 16Ω
fIN = 10kHz
10
100
MAX4410 toc11
100
MAX4410 toc10
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
0
0
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
0.01
4
1k
OUTPUT POWER (mW)
1
0.1
100
FREQUENCY (Hz)
VDD = 3V
AV = -1V/V
RL = 16Ω
fIN = 1kHz
10
0.001
10
100k
FREQUENCY (Hz)
100
THD + N (%)
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
200
0
50
100
150
OUTPUT POWER (mW)
200
0
50
100
150
OUTPUT POWER (mW)
_______________________________________________________________________________________
200
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
VDD = 3V
AV = -2V/V
RL = 16Ω
fIN = 10kHz
10
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
MAX4410 toc14
VDD = 3V
AV = -2V/V
RL = 16Ω
fIN = 1kHz
10
100
MAX4410 toc13
100
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
MAX4410 toc15
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
VDD = 3V OUTPUTS IN
AV = -1V/V PHASE
RL = 32Ω
fIN = 20Hz
10
0.1
0.01
1
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
0.001
150
200
0.0001
0
50
OUTPUTS
180° OUT OF
PHASE
ONE
CHANNEL
VDD = 3V
AV = -1V/V
RL = 32Ω
fIN = 10kHz
10
THD + N (%)
1
OUTPUTS IN
PHASE
1
0.1
OUTPUTS
180° OUT OF
PHASE
ONE
CHANNEL
0.001
50
75
100
125
VDD = 3V
AV = -1V/V
RL = 32Ω
fIN = 20Hz
10
OUTPUTS IN
PHASE
1
OUTPUTS
180° OUT OF
PHASE
0.1
ONE
CHANNEL
0.001
0
25
50
75
100
0
125
25
50
75
100
125
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
ONE
CHANNEL
10
OUTPUTS IN
PHASE
1
OUTPUTS
180° OUT OF
PHASE
0.1
ONE
CHANNEL
0.01
0.001
50
75
OUTPUT POWER (mW)
100
125
OUTPUTS IN
PHASE
VDD = 1.8V
AV = -1V/V
RL = 16Ω
fIN = 20Hz
10
1
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
0.001
25
100
MAX4410 toc20
VDD = 3V
AV = -2V/V
RL = 32Ω
fIN = 10kHz
THD + N (%)
OUTPUTS
180° OUT OF
PHASE
0.1
100
MAX4410 toc19
OUTPUTS IN
PHASE
1
0
125
OUTPUT POWER (mW)
VDD = 3V
AV = -2V/V
RL = 32Ω
fIN = 1kHz
0.01
100
OUTPUT POWER (mW)
100
10
75
100
0.01
0.001
25
50
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
0.01
0
25
MAX4410 toc21
0.01
0
OUTPUT POWER (mW)
100
THD + N (%)
THD + N (%)
OUTPUTS IN
PHASE
0.1
200
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
MAX4410 toc16
100
10
150
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
VDD = 3V
AV = -1V/V
RL = 32Ω
fIN = 1kHz
100
THD + N (%)
100
MAX4410 toc17
50
OUTPUT POWER (mW)
THD + N (%)
0.001
0.001
0
OUTPUTS
180° OUT OF
PHASE
0.01
ONE
CHANNEL
ONE
CHANNEL
ONE
CHANNEL
0.1
MAX4410 toc18
OUTPUTS
180° OUT OF
PHASE
THD + N (%)
OUTPUTS IN
PHASE
THD + N (%)
THD + N (%)
1
1
ONE
CHANNEL
0.001
0
25
50
75
OUTPUT POWER (mW)
100
125
0
10
20
30
40
50
60
OUTPUT POWER (mW)
_______________________________________________________________________________________
5
MAX4410
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
1
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
10
20
30
40
50
OUTPUTS IN
PHASE
0.1
OUTPUTS
180° OUT OF
PHASE
0.01
ONE
CHANNEL
10
20
30
40
50
60
0
MAX4410 toc24
10
20
30
40
50
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
1
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
0.001
20
30
40
50
60
1
MAX4410 toc27
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
ONE
CHANNEL
0.001
0
10
20
30
40
50
0
60
10
20
30
40
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
10
THD + N (%)
OUTPUTS IN
PHASE
VDD = 1.8V
AV = -1V/V
RL = 32Ω
fIN = 10kHz
1
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
0.1
ONE
CHANNEL
0.01
ONE
CHANNEL
0.001
20
30
OUTPUT POWER (mW)
40
50
VDD = 1.8V
AV = -2V/V
RL = 32Ω
fIN = 20Hz
10
1
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
ONE
CHANNEL
0.001
0.001
10
100
THD + N (%)
VDD = 1.8V
AV = -1V/V
RL = 32Ω
fIN = 1kHz
50
MAX4410 toc30
100
MAX4410 toc28
100
60
0.01
ONE
CHANNEL
0.001
10
VDD = 1.8V
AV = -1V/V
RL = 32Ω
fIN = 20Hz
10
THD + N (%)
THD + N (%)
OUTPUTS
180° OUT OF
PHASE
VDD = 1.8V
AV = -2V/V
RL = 16Ω
fIN = 10kHz
10
100
MAX4410 toc26
MAX4410 toc25
100
ONE
CHANNEL
0
ONE
CHANNEL
0.01
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
0.01
1
OUTPUTS
180° OUT OF
PHASE
0.1
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
0.1
10
OUTPUTS IN
PHASE
OUTPUT POWER (mW)
OUTPUTS IN
PHASE
0
1
OUTPUT POWER (mW)
VDD = 1.8V
AV = -2V/V
RL = 16Ω
fIN = 1kHz
1
10
OUTPUT POWER (mW)
100
10
VDD = 1.8V
AV = -2V/V
RL = 16Ω
fIN = 20Hz
0.001
0
60
100
MAX4410 toc23
1
0.001
0
THD + N (%)
VDD = 1.8V
AV = -1V/V
RL = 16Ω
fIN = 10kHz
10
ONE
CHANNEL
0.001
6
100
MAX4410 toc29
THD + N (%)
10
OUTPUTS IN
PHASE
THD + N (%)
VDD = 1.8V
AV = -1V/V
RL = 16Ω
fIN = 1kHz
MAX4410 toc22
100
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
THD + N (%)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
THD + N (%)
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
0
10
20
30
OUTPUT POWER (mW)
40
50
0
10
20
30
OUTPUT POWER (mW)
_______________________________________________________________________________________
40
50
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
ONE
CHANNEL
0.01
ONE
CHANNEL
20
30
40
10
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
-60
0.01
50
-40
1
10
-60
-20
1
10
100
CROSSTALK vs. FREQUENCY
OUTPUT POWER vs. SUPPLY VOLTAGE
-60
LEFT TO RIGHT
-80
fIN = 1kHz
RL = 16Ω
THD + N = 1%
180
160
OUTPUT POWER (mW)
-40
140
INPUTS 180°
OUT OF PHASE
1
10
100
OUTPUT POWER vs. SUPPLY VOLTAGE
120
100
80
60
INPUTS
IN PHASE
40
RIGHT TO LEFT
300
fIN = 1kHz
RL = 16Ω
THD + N = 10%
250
INPUTS 180°
OUT OF PHASE
200
150
100
INPUTS
IN PHASE
50
20
-100
0
FREQUENCY (Hz)
0.1
FREQUENCY (kHz)
200
MAX4410 toc37
VDD = 3V
POUT = 1.6mW
RL = 16Ω
1
0.01
FREQUENCY (kHz)
0
0.1
-60
-100
0.1
FREQUENCY (kHz)
0.01
-40
-80
0.01
100
MAX4410 toc33
VDD = 1.8V
RL = 32Ω
OUTPUT POWER (mW)
0.1
100
0
-100
0.01
10
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
-80
-100
1
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
-20
-80
0.1
FREQUENCY (kHz)
PSRR (dB)
-40
40
VDD = 3V
RL = 32Ω
PSRR (dB)
PSRR (dB)
-20
30
0
MAX4410 toc34
VDD = 1.8V
RL = 16Ω
20
OUTPUT POWER (mW)
OUTPUT POWER (mW)
0
-60
-100
0
50
MAX4410 toc35
10
-40
-80
0.001
0
CROSSTALK (dB)
MAX4410 toc32
0.1
0.01
0.001
-20
OUTPUTS
180° OUT OF
PHASE
MAX4410 toc36
0.1
-20
MAX4410 toc39
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
1
VDD = 3V
RL = 16Ω
PSRR (dB)
OUTPUTS IN
PHASE
0
MAX4410 toc38
THD + N (%)
1
VDD = 1.8V
AV = -2V/V
RL = 32Ω
fIN = 10kHz
10
THD + N (%)
VDD = 1.8V
AV = -2V/V
RL = 32Ω
fIN = 1kHz
10
100
MAX4410 toc31
100
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
10
100
0
1.8
2.1
2.4
2.7
3.0
SUPPLY VOLTAGE (V)
3.3
3.6
1.8
2.1
2.4
2.7
3.0
3.3
3.6
SUPPLY VOLTAGE (V)
_______________________________________________________________________________________
7
MAX4410
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
OUTPUT POWER vs. SUPPLY VOLTAGE
60
INPUTS
IN PHASE
0
2.7
INPUTS
IN PHASE
60
3.0
20
0
1.8
2.1
2.4
3.0
3.3
3.6
MAX4410 toc43
VDD = 3V
fIN = 1kHz
THD + N = 10%
150
INPUTS 180°
OUT OF PHASE
MAX4410 toc42
INPUTS
IN PHASE
10
100
40
VDD = 1.8V
fIN = 1kHz
THD + N = 1%
INPUTS 180°
OUT OF PHASE
35
INPUTS IN
PHASE
20
100k
10k
OUTPUT POWER vs. LOAD RESISTANCE
30
25
1k
LOAD RESISTANCE (Ω)
45
OUTPUT POWER (mW)
70
60
15
VDD = 1.8V
fIN = 1kHz
THD + N = 10%
INPUTS 180°
OUT OF PHASE
50
40
INPUTS IN
PHASE
30
20
10
INPUTS
IN PHASE
10
5
0
0
100
1k
10k
1k
10k
100k
1k
POWER DISSIPATION
vs. OUTPUT POWER
POWER DISSIPATION
vs. OUTPUT POWER
150
100
INPUTS
IN PHASE
160
140
INPUTS 180°
OUT OF PHASE
120
100
80
60
fIN = 1kHz
RL = 32Ω
VDD = 3V
POUT = POUTL + POUTR
40
50
20
80
120
OUTPUT POWER (mW)
160
200
INPUTS
IN PHASE
fIN = 1kHz
RL = 16Ω
VDD = 1.8V
POUT = POUTL + POUTR
120
100
INPUTS 180°
OUT OF PHASE
80
60
40
20
0
0
140
POWER DISSIPATION (mW)
INPUTS 180°
OUT OF PHASE
180
POWER DISSIPATION (mW)
INPUTS
IN PHASE
100k
10k
POWER DISSIPATION
vs. OUTPUT POWER
200
40
100
LOAD RESISTANCE (Ω)
250
0
10
LOAD RESISTANCE (Ω)
fIN = 1kHz
RL = 16Ω
VDD = 3V
POUT = POUTL + POUTR
300
100
LOAD RESISTANCE (Ω)
400
350
0
10
100k
MAX4410 toc46
10
MAX4410 toc48
50
MAX4410 toc47
OUTPUT POWER (mW)
2.7
OUTPUT POWER vs. LOAD RESISTANCE
OUTPUT POWER vs. LOAD RESISTANCE
8
INPUTS 180°
OUT OF PHASE
60
SUPPLY VOLTAGE (V)
250
100
80
0
SUPPLY VOLTAGE (V)
200
100
20
3.6
3.3
120
40
OUTPUT POWER (mW)
2.4
80
MAX4410 toc44
2.1
100
40
20
1.8
120
VDD = 3V
fIN = 1kHz
THD + N = 1%
140
OUTPUT POWER (mW)
140
80
40
fIN = 1kHz
RL = 32Ω
THD + N = 10% INPUTS 180°
OUT OF PHASE
160
OUTPUT POWER vs. LOAD RESISTANCE
160
MAX4410 toc41
INPUTS 180°
OUT OF PHASE
OUTPUT POWER (mW)
OUTPUT POWER (mW)
100
MAX4410 toc40
fIN = 1kHz
RL = 32Ω
THD + N = 1%
120
180
MAX4410 toc45
OUTPUT POWER vs. SUPPLY VOLTAGE
140
POWER DISSIPATION (mW)
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
0
0
40
80
120
OUTPUT POWER (mW)
160
200
0
10
20
30
40
OUTPUT POWER (mW)
_______________________________________________________________________________________
50
60
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
POWER DISSIPATION
vs. OUTPUT POWER
GAIN/PHASE (dB/DEGREES)
50
INPUTS 180°
OUT OF PHASE
40
30
20
fIN = 1kHz
RL = 32Ω
VDD = 1.8V
POUT = POUTL + POUTR
10
0
0
10
20
30
40
50
60
GAIN
PHASE
VDD = 3V
AV = 1000V/V
RL = 16Ω
100
OUTPUT RESISTANCE (Ω)
-10
GAIN (dB)
10M
10
MAX4410 toc51
0
-20
-30
VDD = 3V
AV = -1V/V
RL = 16Ω
VIN_ = GND
IPVSS = 10mA
NO LOAD
8
6
4
2
-50
100
1M
CHARGE-PUMP OUTPUT RESISTANCE
vs. SUPPLY VOLTAGE
10
10
100k
FREQUENCY (Hz)
GAIN FLATNESS vs. FREQUENCY
-40
10k
1k
OUTPUT POWER (mW)
MAX4410 toc52
POWER DISSIPATION (mW)
MAX4410 toc49
INPUTS
IN PHASE
60
80
60
40
20
0
-20
-40
-60
-80
-100
-120
-140
-160
-180
MAX4410 toc50
GAIN AND PHASE vs. FREQUENCY
70
1k
10k
100k
1M
0
10M
1.8
FREQUENCY (Hz)
2.1
2.4
2.7
3.0
3.6
3.3
SUPPLY VOLTAGE (V)
OUTPUT POWER vs. CHARGE-PUMP
CAPACITANCE AND LOAD RESISTANCE
80
C1 = C2 = 1µF
60
50
C1 = C2 = 0.68µF
40
C1 = C2 = 0.47µF
30
20
fIN = 1kHz
THD + N = 1%
INPUTS IN PHASE
10
VIN = 1VP-P
fIN = 1kHz
RL = 32Ω
AV = -1V/V
-20
OUTPUT SPECTRUM (dB)
OUTPUT POWER (mW)
70
OUTPUT SPECTRUM vs. FREQUENCY
0
MAX4410 toc54
C1 = C2 = 2.2µF
MAX4410 toc53
90
-40
-60
-80
-100
0
-120
10
20
30
40
LOAD RESISTANCE (Ω)
50
0.1
1
10
100
FREQUENCY (kHz)
_______________________________________________________________________________________
9
MAX4410
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, TA = +25°C, unless otherwise noted.)
SHUTDOWN SUPPLY CURRENT
vs. SUPPLY VOLTAGE
SUPPLY CURRENT vs. SUPPLY VOLTAGE
SHDNL = SHDNR = GND
8
SUPPLY CURRENT (µA)
8
MAX4410 toc56
10
MAX4410 toc55
10
SUPPLY CURRENT (mA)
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
6
4
6
4
2
2
0
0
0
0.9
1.8
2.7
0
3.6
0.9
1.8
2.7
3.6
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
POWER-UP/DOWN WAVEFORM
EXITING SHUTDOWN
MAX4410 toc58
MAX4410 toc57
3V
2V/div
VDD
0V
SHDNR
OUT_
OUTR
10mV/div
-100dB
500mV/div
20dB/div
OUT_FFT
fIN = 1kHz
RL = 32Ω
SHDNL = GND
10
200µs/div
RL = 32Ω
VIN_ = GND
200ms/div
FFT: 25Hz/div
______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
PIN
BUMP
TSSOP
UCSP
1
B2
SHDNL
2
A3
PVDD
Charge-Pump Power Supply. Powers charge-pump inverter, charge-pump logic, and
oscillator.
3
A4
C1P
Flying Capacitor Positive Terminal
4
B4
PGND
Power Ground. Connect to SGND.
5
C4
C1N
Flying Capacitor Negative Terminal
6
D4
PVSS
Charge-Pump Output
7
D3
SVSS
Amplifier Negative Power Supply. Connect to PVSS.
8
D2
OUTL
Left-Channel Output
9
D1
SVDD
Amplifier Positive Power Supply. Connect to PVDD.
10
C1
INL
11
C2
OUTR
12
B1
SHDNR
13
A1
INR
14
A2
SGND
NAME
FUNCTION
Active-Low, Left-Channel Shutdown. Connect to VDD for normal operation.
Left-Channel Audio Input
Right-Channel Output
Active-Low, Right-Channel Shutdown. Connect to VDD for normal operation.
Right-Channel Audio Input
Signal Ground. Connect to PGND.
______________________________________________________________________________________
11
MAX4410
Pin Description
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Detailed Description
The MAX4410 stereo headphone driver features Maxim’s
patented DirectDrive architecture, eliminating the large
output-coupling capacitors required by traditional singlesupply headphone drivers. The device consists of two
80mW Class AB headphone drivers, undervoltage lockout (UVLO)/shutdown control, charge-pump, and comprehensive click-and-pop suppression circuitry (see
Typical Application Circuit). The charge pump inverts the
positive supply (PV DD ), creating a negative supply
(PVSS). The headphone drivers operate from these bipolar supplies with their outputs biased about GND (Figure
1). The drivers have almost twice the supply range compared to other 3V single-supply drivers, increasing the
available output power. The benefit of this GND bias is
that the driver outputs do not have a DC component typically VDD/2. Thus, the large DC-blocking capacitors are
unnecessary, improving frequency response while conserving board space and system cost.
Each channel has independent left/right, active-low
shutdown controls, making it possible to optimize
power savings in mixed-mode, mono/stereo operation.
The device features an undervoltage lockout that prevents operation from an insufficient power supply and
click-and-pop suppression that eliminates audible transients on startup and shutdown. Additionally, the
MAX4410 features thermal overload and short-circuit
protection and can withstand ±8kV ESD strikes on the
output pins.
DirectDrive
Traditional single-supply headphone drivers have their
outputs biased about a nominal DC voltage (typically
half the supply) for maximum dynamic range. Large
coupling capacitors are needed to block this DC bias
from the headphone. Without these capacitors, a significant amount of DC current flows to the headphone,
resulting in unnecessary power dissipation and possible damage to both headphone and headphone driver.
Maxim’s patented DirectDrive architecture uses a
charge pump to create an internal negative supply voltage. This allows the outputs of the MAX4410 to be
biased about GND, almost doubling dynamic range
while operating from a single supply. With no DC component, there is no need for the large DC-blocking
capacitors. Instead of two large (220µF, typ) tantalum
capacitors, the MAX4410 charge pump requires two
small ceramic capacitors, conserving board space,
reducing cost, and improving the frequency response
of the headphone driver. See the Output Power vs.
Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics for
12
VDD
VDD/2
VOUT
GND
CONVENTIONAL DRIVER-BIASING SCHEME
+VDD
VOUT
GND
-VDD
DirectDrive BIASING SCHEME
Figure 1. Traditional Driver Output Waveform vs. MAX4410
Output Waveform
details of the possible capacitor sizes. There is a low
DC voltage on the driver outputs due to amplifier offset.
However, the offset of the MAX4410 is typically 0.5mV,
which, when combined with a 32Ω load, results in less
than 16µA of DC current flow to the headphones.
Previous attempts to eliminate the output-coupling capacitors involved biasing the headphone return (sleeve) to
the DC-bias voltage of the headphone amplifiers. This
method raises some issues:
1) When combining a microphone and headphone on
a single connector, the microphone bias scheme
typically requires a 0V reference.
2) The sleeve is typically grounded to the chassis.
Using this biasing approach, the sleeve must be
isolated from system ground, complicating product
design.
3) During an ESD strike, the driver’s ESD structures
are the only path to system ground. Thus, the driver
must be able to withstand the full ESD strike.
______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
LF ROLL OFF (16Ω LOAD)
1
2πRLCOUT
MAX4410 fig02
-3
-5
330µF
220µF
ATTENUATION (dB)
where RL is the headphone impedance and COUT is
the DC-blocking capacitor value. The highpass filter
is required by conventional single-ended, single
power-supply headphone drivers to block the midrail
DC bias component of the audio signal from the
headphones. The drawback to the filter is that it can
attenuate low-frequency signals. Larger values of
COUT reduce this effect but result in physically larger, more expensive capacitors. Figure 2 shows the
relationship between the size of COUT and the resulting low-frequency attenuation. Note that the -3dB
point for a 16Ω headphone with a 100µF blocking
capacitor is 100Hz, well within the normal audio
band, resulting in low-frequency attenuation of the
reproduced signal.
2) The voltage coefficient of the DC-blocking capacitor
contributes distortion to the reproduced audio signal
as the capacitance value varies as a function of the
voltage change across the capacitor. At low frequencies, the reactance of the capacitor dominates
at frequencies below the -3dB point and the voltage
coefficient appears as frequency-dependent distortion. Figure 3 shows the THD + N introduced by two
different capacitor dielectric types. Note that below
100Hz, THD + N increases rapidly.
The combination of low-frequency attenuation and frequency-dependent distortion compromises audio
reproduction in portable audio equipment that emphasizes low-frequency effects such as multimedia laptops, as well as MP3, CD, and DVD players. By
eliminating the DC-blocking capacitors through
DirectDrive technology, these capacitor-related deficiencies are eliminated.
0
-10
-3dB CORNER FOR
100µF IS 100Hz
100µF
-15
33µF
-20
-25
-30
-35
10
1k
100
FREQUENCY (Hz)
Figure 2. Low-Frequency Attenuation for Common DC-Blocking
Capacitor Values
ADDITIONAL THD + N DUE
TO DC-BLOCKING CAPACITORS
10
1
THD + N (%)
f −3dB =
MAX4410 fig03
Low-Frequency Response
In addition to the cost and size disadvantages of the DCblocking capacitors required by conventional headphone amplifiers, these capacitors limit the amplifier’s
low-frequency response and can distort the audio signal.
1) The impedance of the headphone load and the DCblocking capacitor form a highpass filter with the
-3dB point set by:
Charge Pump
The MAX4410 features a low-noise charge pump. The
320kHz switching frequency is well beyond the audio
range, and thus does not interfere with the audio signals. The switch drivers feature a controlled switching
speed that minimizes noise generated by turn-on and
turn-off transients. By limiting the switching speed of the
switches, the di/dt noise caused by the parasitic bond
wire and trace inductance is minimized. Although not
typically required, additional high-frequency noise attenuation can be achieved by increasing the size of C2
(see Typical Application Circuit).
0.1
TANTALUM
0.01
0.001
ALUM/ELEC
0.0001
10
100
1k
10k
100k
FREQUENCY (Hz)
Figure 3. Distortion Contributed by DC-Blocking Capacitors
______________________________________________________________________________________
13
MAX4410
4) When using the headphone jack as a line out to other
equipment, the bias voltage on the sleeve may conflict with the ground potential from other equipment,
resulting in possible damage to the drivers.
Click-and-Pop Suppression
In traditional single-supply audio drivers, the outputcoupling capacitor is a major contributor of audible
clicks and pops. Upon startup, the driver charges the
coupling capacitor to its bias voltage, typically half the
supply. Likewise, on shutdown the capacitor is discharged to GND. This results in a DC shift across the
capacitor, which in turn, appears as an audible transient
at the speaker. Since the MAX4410 does not require
output-coupling capacitors, this does not arise.
Additionally, the MAX4410 features extensive click-andpop suppression that eliminates any audible transient
sources internal to the device. The Power-Up/Down
Waveform in the Typical Operating Characteristics
shows that there are minimal spectral components in the
audible range at the output upon startup or shutdown.
In most applications, the output of the preamplifier driving the MAX4410 has a DC bias of typically half the
supply. At startup, the input-coupling capacitor is
charged to the preamplifier’s DC-bias voltage through
the RF of the MAX4410, resulting in a DC shift across
the capacitor and an audible click/pop. Delaying the
rise of the MAX4410’s SHDN_ signals 4 to 5 time constants (200ms to 300ms) based on RIN and CIN relative
to the start of the preamplifier eliminates this click/pop
caused by the input filter.
Applications Information
Power Dissipation
Under normal operating conditions, linear power amplifiers can dissipate a significant amount of power. The
maximum power dissipation for each package is given
in the Absolute Maximum Ratings section under
Continuous Power Dissipation or can be calculated by
the following equation:
TJ(MAX) − TA
PDISSPKG(MAX) =
θJA
where TJ(MAX) is +150°C, TA is the ambient temperature, and θJA is the reciprocal of the derating factor in
14
°C/W as specified in the Absolute Maximum Ratings
section. For example, θJA of the TSSOP package is
+109.9°C/W.
The MAX4410 has two sources of power dissipation,
the charge pump and the two drivers. If the power dissipation for a given application exceeds the maximum
allowed for a given package, either reduce V DD ,
increase load impedance, decrease the ambient temperature, or add heat sinking to the device. Large output, supply, and ground traces improve the maximum
power dissipation in the package.
Thermal overload protection limits total power dissipation in the MAX4410. When the junction temperature
exceeds +140°C, the thermal protection circuitry disables the amplifier output stage. The amplifiers are
enabled once the junction temperature cools by 15°C.
This results in a pulsing output under continuous thermal overload conditions.
Output Power
The device has been specified for the worst-case scenario— when both inputs are in phase. Under this condition, the drivers simultaneously draw current from the
charge pump, leading to a slight loss in headroom of
VSS. In typical stereo audio applications, the left and
right signals have differences in both magnitude and
phase, subsequently leading to an increase in the maximum attainable output power. Figure 4 shows the two
extreme cases for in and out of phase. In reality, the
available power lies between these extremes.
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
MAX4410 fig04
Shutdown
The MAX4410 features two shutdown controls allowing
either channel to be shut down or muted independently.
SHDNL controls the left channel while SHDNR controls
the right channel. Driving either SHDN_ low disables the
respective channel, sets the driver output impedance to
about 1kΩ, and reduces the supply current to less than
10µA. When both SHDN_ inputs are driven low, the
charge pump is also disabled, further reducing supply
current draw to 6µA. The charge pump is enabled once
either SHDN_ input is driven high.
VDD = 3V
AV = -1V/V
RL = 16Ω
fIN = 10kHz
10
THD + N (%)
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
1
OUTPUTS IN
PHASE
0.1
OUTPUTS
180° OUT OF
PHASE
0.01
ONE
CHANNEL
0.001
0
50
100
150
200
OUTPUT POWER (mW)
Figure 4. Output Power vs. Supply Voltage with Inputs In/Out
of Phase
______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
An additional benefit of the MAX4410 is the internally
generated, negative supply voltage (-VDD). This voltage
is used by the MAX4410 to provide the ground-referenced output level. It can, however, also be used to
power other devices within a design. Current draw from
this negative supply (PVSS) should be limited to 5mA,
exceeding this will affect the operation of the headphone driver. The negative supply voltage appears on
the PVSS pin. A typical application is a negative supply
to adjust the contrast of LCD modules.
When considering the use of PVSS in this manner, note
that the charge-pump voltage at PVSS is roughly proportional to -VDD and is not a regulated voltage. The
charge-pump output impedance plot appears in the
Typical Operating Characteristics.
Component Selection
Gain-Setting Resistors
External feedback components set the gain of the
MAX4410. Resistors RF and RIN (see Typical Application
Circuit) set the gain of each amplifier as follows:
R 
AV = −  F 
 RIN 
To minimize VOS, set RF equal to 10kΩ. Values other
than 10kΩ increase VOS due to the input bias current,
which in turn increases the amount of DC current flow
to the speaker.
Compensation Capacitor
The stability of the MAX4410 is affected by the value of
the feedback resistor (RF). The combination of RF and
the input and parasitic trace capacitance introduces an
additional pole. Adding a capacitor in parallel with RF
compensates for this pole. Under typical conditions
with proper layout, the device is stable without the
additional capacitor.
Input Filtering
The input capacitor (CIN), in conjunction with RIN, forms a
highpass filter that removes the DC bias from an incoming signal (see Typical Application Circuit). The AC-coupling capacitor allows the amplifier to bias the signal to
an optimum DC level. Assuming zero-source impedance,
the -3dB point of the highpass filter is given by:
f −3dB =
1
2πRINCIN
Choose RIN according to the Gain-Setting Resistors section. Choose the CIN such that f-3dB is well below the
lowest frequency of interest. Setting f-3dB too high affects
the low-frequency response of the amplifier. Use capacitors whose dielectrics have low-voltage coefficients,
such as tantalum or aluminum electrolytic. Capacitors
with high-voltage coefficients, such as ceramics, may
result in increased distortion at low frequencies.
Other considerations when designing the input filter
include the constraints of the overall system and the
actual frequency band of interest. Although high-fidelity
audio calls for a flat-gain response between 20Hz and
20kHz, portable voice-reproduction devices such as
cellular phones and two-way radios need only concentrate on the frequency range of the spoken human voice
(typically 300Hz to 3.5kHz). In addition, speakers used
in portable devices typically have a poor response
below 150Hz. Taking these two factors into consideration, the input filter may not need to be designed for a
20Hz to 20kHz response, saving both board space and
cost due to the use of smaller capacitors.
Charge-Pump Capacitor Selection
Use capacitors with an ESR less than 100mΩ for optimum performance. Low-ESR ceramic capacitors minimize the output resistance of the charge pump. For
best performance over the extended temperature
range, select capacitors with an X7R dielectric. Table 1
lists suggested manufacturers.
Flying Capacitor (C1)
The value of the flying capacitor (C1) affects the load
regulation and output resistance of the charge pump. A
C1 value that is too small degrades the device’s ability
to provide sufficient current drive, which leads to a loss
of output voltage. Increasing the value of C1 improves
load regulation and reduces the charge-pump output
resistance to an extent. See the Output Power vs.
Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics. Above
2.2µF, the on-resistance of the switches and the ESR of
C1 and C2 dominate.
Table 1. Suggested Capacitor Manufacturers
PHONE
FAX
Taiyo Yuden
SUPPLIER
800-348-2496
847-925-0899
www.t-yuden.com
WEBSITE
TDK
847-803-6100
847-390-4405
www.component.tdk.com
Note: Please indicate you are using the MAX4410 when contacting these component suppliers.
______________________________________________________________________________________
15
MAX4410
Powering Other Circuits from a
Negative Supply
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Output Capacitor (C2)
The output capacitor value and ESR directly affect the
ripple at PVSS. Increasing the value of C2 reduces output ripple. Likewise, decreasing the ESR of C2
reduces both ripple and output resistance. Lower
capacitance values can be used in systems with low
maximum output power levels. See the Output Power
vs. Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics.
Power-Supply Bypass Capacitor
The power-supply bypass capacitor (C3) lowers the output impedance of the power supply, and reduces the
impact of the MAX4410’s charge-pump switching transients. Bypass PVDD with C3, the same value as C1, and
place it physically close to the PVDD and PGND pins
(refer to the MAX4410 EV kit for a suggested layout).
Adding Volume Control
The addition of a digital potentiometer provides simple
volume control. Figure 5 shows the MAX4410 with the
MAX5408 dual log taper digital potentiometer used as
an input attenuator. Connect the high terminal of the
MAX5408 to the audio input, the low terminal to ground
and the wiper to CIN. Setting the wiper to the top position passes the audio signal unattenuated. Setting the
wiper to the lowest position fully attenuates the input.
Layout and Grounding
Proper layout and grounding are essential for optimum
performance. Connect PGND and SGND together at a
single point on the PC board. Connect all components
associated with the charge pump (C2 and C3) to the
PGND plane. Connect PVDD and SVDD together at the
device. Connect PV SS and SV SS together at the
device. Bypassing of both supplies is accomplished
by charge-pump capacitors C2 and C3 (see Typical
Application Circuit). Place capacitors C2 and C3 as
close to the device as possible. Route PGND and all
traces that carry switching transients away from SGND
and the traces and components in the audio signal
path. Refer to the layout example in the MAX4410 EV
kit datasheet.
When using the MAX4410 in a UCSP package, make
sure the traces to OUTR (bump C2) are wide enough
to handle the maximum expected current flow. Multiple
traces may be necessary.
UCSP Considerations
For general UCSP information and PC layout considerations, refer to the Maxim Application Note: WaferLevel Ultra Chip-Scale Package.
RF
LEFT AUDIO
INPUT
5 H0
CIN
W0A 7
6
RIN
10
INL
OUTL
8
L0
MAX4410
MAX5408
RIGHT AUDIO 12 H1
INPUT
CIN
W1A 10
RIN
13
INR
OUTR
11
11 L1
RF
Figure 5. MAX4410 and MAX5408 Volume Control Circuit
16
______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
CIN
1µF
1.8V to 3.6V
RF
10kΩ
RIN
10kΩ
LEFT
CHANNEL
AUDIO IN
C3
2.2µF
2
(A3)
9
(D1)
1
(B2)
PVDD
SVDD
SHDNL
10
(C1)
12
(B1)
INL
SHDNR
SVDD
OUTL
SGND
UVLO/
SHUTDOWN
CONTROL
3
(A4) C1P
HEADPHONE
JACK
SVSS
CHARGE
PUMP
C1
2.2µF
8
(D2)
CLICK-AND-POP
SUPPRESSION
5
(C4) C1N
SVDD
SGND
MAX4410
PVSS
6
(D4)
C2
2.2µF
SVSS PGND
7
(D3)
4
(B4)
OUTR
SGND
INR
14
(A2)
13
(A1)
CIN
1µF
RIN
10kΩ
11
(C2)
SVSS
RF
10kΩ
RIGHT
CHANNEL
AUDIO IN
( ) DENOTE BUMPS FOR UCSP.
______________________________________________________________________________________
17
MAX4410
Typical Application Circuit
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Pin Configurations
TOP VIEW
(BUMP SIDE
DOWN)
MAX4410
TOP VIEW
1
2
3
4
INR
SGND
PVDD
C1P
A
SHDNL 1
B
SHDNR
PGND
SHDNL
2
13 INR
C1P
3
12 SHDNR
PGND 4
MAX4410
C1N 5
C
INL
D
14 SGND
PVDD
SVDD
C1N
OUTR
OUTL
SVSS
11 OUTR
10 INL
PVSS 6
9
SVDD
SVSS 7
8
OUTL
PVSS
TSSOP
UCSP (B16-2)
Chip Information
TRANSISTOR COUNT: 4295
PROCESS: BiCMOS
18
______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
16L,UCSP.EPS
______________________________________________________________________________________
19
MAX4410
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.)
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.)
TSSOP4.40mm.EPS
MAX4410
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
20 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600
© 2002 Maxim Integrated Products
Printed USA
is a registered trademark of Maxim Integrated Products.