DS5784AB 02

®
RT5784A/B
2A, 6V, 1.5MHz, 25μ
μA IQ, ACOTTM Synchronous Step-Down
Converter
General Description
Features
The RT5784A/B is a high-performance, Advanced Constant
On-Time (ACOTTM) monolithic synchronous step-down
DC/DC converter that can deliver up to 2A output current
from a 2.5V to 6V input supply. The proprietary ACOT
control architecture features quick transient response and
provides stable operation with small ceramic output
capacitors and without complicated external
compensation. The switching ripple voltage is easily
smoothed-out by small package filtering elements due to
a constant switching frequency of 1.5MHz and the
maximum duty cycle of 100% allows the device to operate
at low dropout use. With internal low on-resistance power
switches and extremely low quiescent current, the
RT5784A/B displays excellent efficiency and good behavior
across a range of applications.
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Dramatically Fast Transient Response
Steady 1.5MHz ±200kHz Switching Frequency
Very Low Input Quiescent and Shutdown Currents
Advanced COT Control Loop Design
Optimized for Ceramic Output Capacitors
2.5V to 6V Input Voltage Range
Accurate Voltage Reference 0.6V ±2%
Integrated 100mΩ
Ω/60mΩ
Ω MOSFETs
Internal Start-Up into Pre-biased Outputs
Power Good Indicator
Enable Control
Over-Current and Over-Temperature Protections
Under-Voltage Protection with Hiccup Mode
RoHS Compliant and Halogen Free
Applications
Cycle-by-cycle current limit provides protection against
shorted outputs, input under-voltage lock-out, output
under-voltage protection, and thermal shutdown provide
safe and smooth operation in all operating conditions. The
RT5784A/B is available in the WDFN-8JL 2x1.5 (FC)
package.
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Mobile Phones and Handheld Devices
STB, Cable Modem, and xDSL Platforms
WLAN ASIC Power / Storage (SSD and HDD)
General Purpose for POL LV Buck Converter
Simplified Application Circuit
VIN
VIN
RPGOOD
PGOOD
Enable
LX
CIN
VOUT
R1
RT5784A/B
PGOOD
L
CFF
COUT
FB
R2
EN
VOUT
PGND
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DS5784A/B-02 January 2016
AGND
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RT5784A/B
Ordering Information
Pin Configurations
RT5784
(TOP VIEW)
Package Type
QWF : WDFN-8JL 2x1.5 (FC) (W-Type)
EN
FB
AGND
VOUT
Lead Plating System
G : Green (Halogen Free and Pb Free)
PSM/PWM
A : PSM/PWM
B : Force-PWM
1
8
2
7
3
6
4
5
PGOOD
VIN
LX
PGND
WDFN-8JL 2x1.5 (FC)
Note :
Marking Information
Richtek products are :
RT5784AGQWF

ments of IPC/JEDEC J-STD-020.

01 : Product Code
RoHS compliant and compatible with the current require-
01W
W : Date Code
Suitable for use in SnPb or Pb-free soldering processes.
RT5784BGQWF
00 : Product Code
00W
W : Date Code
Functional Pin Description
Pin No.
Pin Name
Pin Function
1
EN
Enable Control Input. Connecting this pin to logic high can enable the device and
connecting this pin to GND can disable the device.
2
FB
Feedback Voltage Input. This pin is used to set the desired output voltage via an
external resistive divider. The feedback reference voltage is 0.6V typically.
3
AGND
Analog Ground. Provides the ground return path for control circuitry and internal
reference.
4
VOUT
Output Voltage Sense Input. This pin is used to monitor and adjust output voltage for
superior load transient regulation.
5
PGND
Power Ground. This pin must be soldered to a large PCB and connected to analog
ground for maximum power dissipation.
6
LX
Switch Node. LX is the switching node that supplies power to the output and connect
the output LC filter from LX to the output load.
7
VIN
Supply Input. Supplies the power to the internal control circuit as well as the power
switches of the device. Drive VIN with a 2.5V to 6V power source and bypass VIN to
PGND with a suitably large capacitor to eliminate noise on the input to the IC.
8
PGOOD
Power Good Indicator Output. This pin is an open-drain logic output that is pulled to
ground when the output voltage is lower or higher than its specified threshold under
the conditions of UVP, OTP, dropout, EN shutdown, or during slow start.
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RT5784A/B
Function Block Diagram
VOUT
EN
UVLO
OTP
FB
AGND
Shutdown
Control
Error Amplifier
+
+
VREF
TON
Comparator
+
-
Ramp
Generator
Logic
Control
Current
Limit
Detector
PGOOD
+
AZC
VFB
LX
VIN
Driver
LX
LX
LX
PGND
-
Operation
The RT5784A/B is a low voltage synchronous step-down
converter that can support input voltage ranging from 2.5V
to 6V and the output current can be up to 2A. The RT5784A/
B uses ACOTTM mode control. To achieve good stability
with low-ESR ceramic capacitors, the ACOT uses a virtual
inductor current ramp generated inside the IC. This internal
ramp signal replaces the ESR ramp normally provided by
the output capacitor's ESR. The ramp signal and other
internal compensations are optimized for low-ESR ceramic
output capacitors.
In steady-state operation, the feedback voltage, with the
virtual inductor current ramp added, is compared to the
reference voltage. When the combined signal is less than
the reference, the on-time one-shot is triggered, as long
as the minimum off-time one-shot is clear and the
measured inductor current (through the synchronous
rectifier) is below the current limit. The on-time one-shot
turns on the high-side switch and the inductor current
ramps up linearly. After the on-time, the high-side switch
is turned off and the synchronous rectifier is turned on
and the inductor current ramps down linearly. At the same
time, the minimum off-time one-shot is triggered to prevent
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DS5784A/B-02 January 2016
another immediate on-time during the noisy switching
time and allow the feedback voltage and current sense
signals to settle. The minimum off-time is kept short so
that rapidly-repeated on-times can raise the inductor
current quickly when needed.
Under-Voltage Protection (UVLO)
The UVLO continuously monitors the VCC voltage to make
sure the device works properly. When the VCC is high
enough to reach the UVLO high threshold voltage, the
step-down converter softly starts or pre-bias to its regulated
output voltage. When the VCC decreases to its low
threshold voltage, the device shuts down.
Power Good
When the output voltage is higher than PGOOD rising
threshold, the PGOOD flag is high.
Output Under-Voltage Protection (UVP)
When the output voltage is lower than 66% reference
voltage after soft-start, the UVP is triggered.
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RT5784A/B
Over-Current Protection (OCP)
The RT5784A/B senses the current signal when the highside and low-side MOSFET turns on. As a result, The
OCP is a cycle-by-cycle current limit. If an over-current
condition occurs, the converter turns off the next on pulse
until inductor current drops below the OCP limit. The delay
time of high-side MOSFET OCP trigger is 100ns. If the
OCP is continually activated and the load current is larger
than the current provided by the converter, the output
voltage drops. Also, when the output voltage triggers the
UVP also, the current will drop to ZC and trigger the resoft-start sequence.
Soft-Start
An internal current source charges an internal capacitor
to build the soft-start ramp voltage. The typical soft-start
time is 1.5ms.
Over-Temperature Protection (OTP)
The RT5784A/B has an over-temperature protection. When
the device triggers the OTP, the device shuts down until
the temperature is back to normal.
PWM Frequency and Adaptive On-Time Control
The on-time can be roughly estimated by the equation :
TON =
VOUT
1

where fOSC is nominal 1.5MHz
VIN
fOSC
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DS5784A/B-02 January 2016
RT5784A/B
Absolute Maximum Ratings
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(Note 1)
Supply Input Voltage, VIN ----------------------------------------------------------------------------------------LX Pin Switch Voltage ---------------------------------------------------------------------------------------------<10ns -----------------------------------------------------------------------------------------------------------------Other Pins ------------------------------------------------------------------------------------------------------------Power Dissipation, PD @ TA = 25°C
WDFN-8JL 2x1.5 (FC) ---------------------------------------------------------------------------------------------Package Thermal Resistance (Note 2)
WDFN-8JL 2x1.5 (FC), θJA ----------------------------------------------------------------------------------------Junction Temperature ----------------------------------------------------------------------------------------------Lead Temperature (Soldering, 10 sec.) ------------------------------------------------------------------------Storage Temperature Range -------------------------------------------------------------------------------------ESD Susceptibility (Note 3)
HBM (Human Body Model) ----------------------------------------------------------------------------------------
Recommended Operating Conditions
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−0.3V to 7V
−0.3V to 7.3V
−5V to 8.5V
−0.3V to 5V
0.91W
110°C/W
150°C
260°C
−65°C to 150°C
2kV
(Note 4)
Supply Input Voltage, VIN ----------------------------------------------------------------------------------------- 2.5V to 6V
Junction Temperature Range -------------------------------------------------------------------------------------- −40°C to 125°C
Ambient Temperature Range -------------------------------------------------------------------------------------- −40°C to 85°C
Electrical Characteristics
(VIN = 5V, TA = 25°C, unless otherwise specified)
Parameter
Symbol
Test Conditions
Min
Typ
Max
Unit
Supply Voltage
Input Operating Voltage
VIN
2.5
--
6
Under-Voltage Lockout
Threshold Rising
VUVLO
2.15
2.3
2.45
Under-Voltage Lockout
Threshold Hysteresis
∆VUVLO
--
260
--
mV
Shutdown Current
ISHDN
VEN = 0V
--
0
1
A
Quiescent Current
IQ
For RT5784A VLX no switching.
RT5784B
---
25
600
---
A
VIH
VEN Rising
1.2
--
--
VIL
VEN Falling
--
--
0.4
Feedback Voltage
VFB
2.5V  VIN  6V
0.588
0.6
0.612
V
Feedback Input Current
IFB
VFB = 0.6V
--
10
--
nA
2.8
3.2
4.2
V
Enable Voltage
Enable Threshold Voltage
V
Feedback Voltage
Current Limit
High-Side Switch Peak
Current Limit
ILIM_H
Low-Side Switch Valley
Current Limit
ILIM_L
A
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2.5
3.4
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RT5784A/B
Parameter
Symbol
Test Conditions
Min
Typ
Max
Unit
1300
1500
1700
kHz
--
60
--
Switching
Switching Frequency
fS
VOUT = 1.2V
Minimum Off-Time
Internal MOSFET
High-Side On-Resistance
RDS(ON)_H
--
100
--
Low-Side On-Resistance
RDS(ON)_L
--
60
--
VEN = 0V, VIN = 6V, VLX = 0V and
5.5V
--
0
1
A
EN from low to high and VOUT is
meet 95%
--
1.7
--
ms
Power Good Rising
Threshold
VFB Rising (Good)
--
95
--
VFB Rising (Fault)
--
110
--
Power Good Falling
Threshold
VFB Falling (Fault)
--
90
--
VFB Falling (Good)
--
105
--
--
50
--
s
--
--
0.4
V
--
550
--
k
4.9
--
--
V
Switch Leakage Current
m
Soft-Start
Fixed Soft-Start Time
tSS
Power Good
Power Good Enable Delay
Time
Power Good Sink Current
Capability
Power Good Internal
Resistance
Power Good Asserting
Voltage
IPGOOD sinks 1mA
VPGOOD
VIN = 5V, VFB = 0.6V
(Note 5)
%VFB
Over-Temperature Protection
Thermal Shutdown
TSD
(Note 5)
--
150
--
Thermal Shutdown
Hysteresis
∆TSD
(Note 5)
--
30
--
C
Note 1. Stresses beyond those listed “Absolute Maximum Ratings” may cause permanent damage to the device. These are
stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in
the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions may
affect device reliability.
Note 2. θJA is measured at TA = 25°C on a high effective thermal conductivity four-layer test board per JEDEC 51-7. The first
layer of copper area is filled. θJC is measured at the exposed pad of the package.
Note 3. Devices are ESD sensitive. Handling precaution is recommended.
Note 4. The device is not guaranteed to function outside its operating conditions.
Note 5. Guaranteed by design.
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RT5784A/B
Typical Application Circuit
VIN
2.5V to 6V
7
RPGOOD
100k
CIN
10µF
LX
6
L
VOUT
R1
RT5784A/B
8
PGOOD
VIN
PGOOD
FB 2
R2
1 EN
Enable
CFF
COUT
10µF
VOUT 4
PGND
5
AGND
3
Table 1. Suggested Component Values
VOUT (V)
R1 (k)
R2 (k)
L (H)
COUT (F)
1
200
300
1
10
1.2
200
200
1
10
1.8
200
100
1.4
10
2.5
200
63.2
1.4
10
3.3
200
44.2
1.4
10
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RT5784A/B
Typical Operating Characteristics
Efficiency vs. Output Current
Output Voltage vs. Output Current
100
1.40
90
VIN = 3.3V
VIN = 4V
VIN = 5V
VIN = 5.5V
VIN = 6V
70
60
50
1.35
Output Voltage (V)
Efficiency (%)
80
40
30
20
1.30
VIN = 3.3V
VIN = 4V
VIN = 5V
VIN = 5.5V
VIN = 6V
1.25
1.20
10
VOUT = 1.2V
0
0.001
VOUT = 1.2V
1.15
0.01
0.1
1
10
0
0.5
Output Current (A)
1
1.5
2
Output Current (A)
UVLO Threshold vs. Temperature
EN Threshold vs. Temperature
2.5
1.00
Rising
EN Threshold (V)
UVLO Threshold (V)
0.90
2.3
2.1
Falling
1.9
0.80
Falling
0.70
Rising
0.60
0.50
1.7
0.40
VOUT = 1.2V, IOUT = 0A
VOUT = 1.2V, IOUT = 1A
1.5
0.30
-50
-25
0
25
50
75
100
125
-50
-25
0
Temperature (°C)
25
50
75
100
125
Temperature (°C)
Output Voltage vs. Temperature
Output Voltage vs. Temperature
1.24
3.40
3.39
3.38
Output Voltage (V)
Output Voltage (V)
1.23
1.22
1.21
1.20
1.19
3.37
3.36
3.35
3.34
3.33
3.32
3.31
3.30
VOUT = 1.2V, IOUT = 1A
1.18
3.29
VOUT = 3.3V, IOUT = 1A
3.28
-50
-25
0
25
50
75
100
Temperature (°C)
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125
-50
-25
0
25
50
75
100
125
Temperature (°C)
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DS5784A/B-02 January 2016
RT5784A/B
Reference Voltage vs. Temperature
Soft-Start Time vs. Temperature
0.618
1.66
Soft-Start Time (ms)
Reference Voltage (V)
1.64
0.612
0.606
0.600
0.594
0.588
VIN = 5V
0.582
1.62
1.60
1.58
1.56
1.54
1.52
1.50
1.48
VIN = 5V, VOUT = 3.3V
1.46
-50
-25
0
25
50
75
100
125
-50
-25
0
25
50
75
Temperature (°C)
temperature (°C)
Load Transient Response
Output Ripple Voltage
VOUT
(20mV/Div)
VOUT
(20mV/Div)
IOUT
(1A/Div)
VLX
(2V/Div)
VIN = 5V, VOUT = 1.2V,
IOUT = 1A to 2A, L = 1μH
100
125
VIN = 5V, VOUT = 1.2V,
IOUT = 2A, L = 1μH
Time (100μs/Div)
Time (400ns/Div)
Power On from VIN
Power Off from VIN
VIN
(4V/Div)
VIN
(4V/Div)
VOUT
(1V/Div)
VOUT
(1V/Div)
VLX
(5V/Div)
VLX
(5V/Div)
ILX
(1A/Div)
ILX
(1A/Div)
VIN = 5V, VOUT = 1.2V,
IOUT = 2A, L = 1μH
VIN = 5V, VOUT = 1.2V,
IOUT = 2A, L = 1μH
Time (2ms/Div)
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Time (5ms/Div)
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RT5784A/B
Power On from EN
EN
(2V/Div)
EN
(2V/Div)
VOUT
(1V/Div)
VOUT
(1V/Div)
VLX
(5V/Div)
VLX
(5V/Div)
ILX
(1A/Div)
ILX
(1A/Div)
VIN = 5V, VOUT = 1.2V,
IOUT = 2A, L = 1μH
Time (2ms/Div)
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Power Off from EN
VIN = 5V, VOUT = 1.2V,
IOUT = 2A, L = 1μH
Time (40μs/Div)
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RT5784A/B
Application Information
The RT5784A/B is a single-phase step-down converter.
Advance Constant-on-Time (ACOT) with fast transient
response. An internal 0.6V reference allows the output
voltage to be precisely regulated for low output voltage
applications. A fixed switching frequency (1.5MHz)
oscillator and internal compensation are integrated to
minimize external component count. Protection features
include over current protection, under voltage protection
and over temperature protection.
Inductor Selection
The consideration of inductor selection includes
inductance, RMS current rating and, saturation current
rating. The inductance selection is generally flexible and
is optimized for the low cost, low physical size, and high
system performance.
Choosing lower inductance to reduce physical size and
cost, and it is useful to improve the transient response.
However, it causes the higher inductor peak current and
output ripple voltage to decrease system efficiency.
Conversely, higher inductance increase system efficiency,
but the physical size of inductor will become larger and
transient response will be slow because more transient
time is required to change current (up or down) by inductor.
A good compromise between size, efficiency, and transient
response is to set a inductor ripple current (ΔIL) about
20% to 50% of the desired full output load current.
Calculate the approximate inductance by the input voltage,
output voltage, switching frequency (fSW), maximum rated
output current (IOUT(MAX)) and inductor ripple current (ΔIL).
L=
VOUT  ( VIN  VOUT )
VIN  fSW  IL
Once the inductance is chosen, the inductor ripple current
(ΔIL) and peak inductor current can be calculated.
For the typical operating circuit design, the output voltage
is 1.2V, maximum rated output current is 2A, input voltage
is 5V, and inductor ripple current is 0.6A which is 30% of
the maximum rated output current, the calculated
inductance value is :
L=
1.2   5  1.2 
5  1500  103  0.6
= 1μH
The inductor ripple current set at 0.6A and so we select
1uH inductance. The actual inductor ripple current and
required peak current is shown as below :
IL =
1.2   5  1.2 
5  1500  103  1 10-6
= 0.6A
IL(PEAK) = IOUT(MAX)  1 IL = 2 + 0.6 = 2.3A
2
2
Inductor saturation current should be chosen over IC's
current limit.
Output Voltage Setting
The output voltage is set by an external resistive divider
according to the following equation :
R1
)
R2
where VREF equals to 0.6V typical. The resistive divider
allows the FB pin to sense a fraction of the output voltage
as shown in Figure 1.
VOUT  VREF x (1
VOUT
R1
FB
RT5784A/B
R2
GND
Figure 1. Setting the Output Voltage
VOUT   VIN  VOUT 
VIN  fSW  L
IL(PEAK) = IOUT(MAX)  1 IL
2
IL(VALLY) = IOUT(MAX)  1 IL
2
IL =
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RT5784A/B
Low Supply Operation
The RT5784A/B is designed to operate down to an input
supply voltage of 2.5V. One important consideration at
low input supply voltages is that the RDS(ON) of the PChannel and N-Channel power switches increases. The
user should calculate the power dissipation when the
RT5784A/B is used at 100% duty cycle with low input
voltages to ensure that thermal limits are not exceeded.
Under Voltage Protection (UVP)
Hiccup Mode
For the RT5784A/B, it provides Hiccup Mode Under
Voltage Protection (UVP). When the output voltage is
lower than 66% reference voltage after soft-start, the UVP
is triggered. If the UVP condition remains for a period, the
RT5784A/B will retry automatically. When the UVP
condition is removed, the converter will resume operation.
The UVP is disabled during soft-start period.
Post Short
VIN
(2V/Div)
VOUT
(500mV/Div)
SW
(5V/Div)
IOUT
(2A/Div)
VIN = 5V, VOUT = 1.2V, L = 1μH
Time (1ms/Div)
CIN and COUT Selection
The input capacitance, C IN, is needed to filter the
trapezoidal current at the source of the top MOSFET. To
prevent large ripple voltage, a low ESR input capacitor
sized for the maximum RMS current should be used. RMS
current is given by :
IRMS  IOUT(MAX)
VOUT
VIN
VIN
1
VOUT
This formula has a maximum at VIN = 2VOUT, where IRMS =
IOUT / 2. This simple worst case condition is commonly
used for design because even significant deviations do
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not result in much difference. Choose a capacitor rated at
a higher temperature than required.
Several capacitors may also be paralleled to meet size or
height requirements in the design.
The selection of COUT is determined by the effective series
resistance (ESR) that is required to minimize voltage ripple
and load step transients, as well as the amount of bulk
capacitance that is necessary to ensure that the control
loop is stable. Loop stability can be checked by viewing
the load transient response. The output ripple, ΔVOUT, is
determined by :

1 
VOUT  IL ESR 

8fCOUT 

The output ripple is highest at maximum input voltage
since ΔIL increases with input voltage. Multiple capacitors
placed in parallel may be needed to meet the ESR and
RMS current handling requirements. Dry tantalum, special
polymer, aluminum electrolytic and ceramic capacitors are
all available in surface mount packages. Special polymer
capacitors offer very low ESR, but have lower capacitance
density than other types. Tantalum capacitors have the
highest capacitance density, but it is important to only
use types that have been surge tested for use in switching
power supplies. Aluminum electrolytic capacitors have
significantly higher ESR, but can be used in cost-sensitive
applications provided that consideration is given to ripple
current ratings and long term reliability. Ceramic capacitors
have excellent low ESR characteristics, but can have a
high voltage coefficient and audible piezoelectric effects.
The high Q of ceramic capacitors with trace inductance
can also lead to significant ringing.
Using Ceramic Input and Output Capacitors
Higher value, lower cost ceramic capacitors are now
becoming available in smaller case sizes. Their high ripple
current, high voltage rating and low ESR make them ideal
for switching regulator applications. However, care must
be taken when these capacitors are used at the input and
output. When a ceramic capacitor is used at the input
and the power is supplied by a wall adapter through long
wires, a load step at the output can induce ringing at the
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DS5784A/B-02 January 2016
RT5784A/B
Table 1. Capacitors for CIN and COUT
Component
Supplier
Part No.
MuRata
GRM31CR71A106KA01
Capacitance Case
(F)
Size
10F
1206
1.0
Maximum Power Dissipation (W)1
input, VIN. At best, this ringing can couple to the output
and be mistaken as loop instability. At worst, a sudden
inrush of current through the long wires can potentially
cause a voltage spike at VIN large enough to damage the
part.
Four-Layer PCB
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0.0
Thermal Considerations
For continuous operation, do not exceed absolute
maximum junction temperature. The maximum power
dissipation depends on the thermal resistance of the IC
package, PCB layout, rate of surrounding airflow, and
difference between junction and ambient temperature. The
maximum power dissipation can be calculated by the
following formula :
0
25
50
75
100
125
Ambient Temperature (°C)
Figure 2. Derating Curve of Maximum Power Dissipation
PD(MAX) = (TJ(MAX) − TA) / θJA
where TJ(MAX) is the maximum junction temperature, TA is
the ambient temperature, and θJA is the junction to ambient
thermal resistance.
For recommended operating condition specifications, the
maximum junction temperature is 125°C. The junction to
ambient thermal resistance, θJA, is layout dependent. The
junction to ambient thermal resistance, θJA, is layout
dependent. For WDFN-8JL 2x1.5 (FC) package, the
thermal resistance, θJA, is 110°C/W on a standard JEDEC
51-7 four-layer thermal test board. The maximum power
dissipation at TA = 25°C can be calculated by the following
formula :
PD(MAX) = (125°C − 25°C) / (110°C/W) = 0.91W for
WDFN-8JL 2x1.5 (FC) package
The maximum power dissipation depends on the operating
ambient temperature for fixed T J(MAX) and thermal
resistance, θJA. The derating curve in Figure 2 allows the
designer to see the effect of rising ambient temperature
on the maximum power dissipation.
Copyright © 2016 Richtek Technology Corporation. All rights reserved.
DS5784A/B-02 January 2016
is a registered trademark of Richtek Technology Corporation.
www.richtek.com
13
RT5784A/B
Outline Dimension
1
1
2
2
DETAIL A
Pin #1 ID and Tie Bar Mark Options
Note : The configuration of the Pin #1 identifier is optional,
but must be located within the zone indicated.
Symbol
Dimensions In Millimeters
Dimensions In Inches
Min.
Max.
Min.
Max.
A
0.700
0.800
0.028
0.031
A1
0.000
0.050
0.000
0.002
A3
0.150
0.250
0.006
0.010
b
0.200
0.300
0.008
0.012
D
1.900
2.100
0.075
0.083
E
1.400
1.600
0.055
0.063
e
L
0.500
0.300
0.020
0.400
0.012
0.016
W-Type 8JL DFN 2x1.5 (FC) Package
Richtek Technology Corporation
14F, No. 8, Tai Yuen 1st Street, Chupei City
Hsinchu, Taiwan, R.O.C.
Tel: (8863)5526789
Richtek products are sold by description only. Richtek reserves the right to change the circuitry and/or specifications without notice at any time. Customers should
obtain the latest relevant information and data sheets before placing orders and should verify that such information is current and complete. Richtek cannot
assume responsibility for use of any circuitry other than circuitry entirely embodied in a Richtek product. Information furnished by Richtek is believed to be
accurate and reliable. However, no responsibility is assumed by Richtek or its subsidiaries for its use; nor for any infringements of patents or other rights of third
parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Richtek or its subsidiaries.
www.richtek.com
14
DS5784A/B-02 January 2016