EL5156, EL5157, EL5256, EL5257 ® Data Sheet PRELIMINARY July 2, 2004 FN7386.2 <1mV Voltage Offset, 600MHz Amplifiers Features The EL5156, EL5157, EL5256, and EL5257 are 600MHz bandwidth -3dB voltage mode feedback amplifiers with DC accuracy of <0.01%, 1mV offsets and 40kV/V open loop gains. These amplifiers are ideally suited for applications ranging from precision measurement instrumentation to high speed video and monitor applications demanding the very highest linearity at very high frequency. Capable of operating with as little as 6.0mA of current from a single supply ranging from 5V to 12V and dual supplies ranging from ±2.5V to ±5.0V these amplifiers are also well suited for handheld, portable and battery-powered equipment. With their capability to output as much as 140mA, member of this family is comfortable with demanding load conditions. • 600MHz -3dB bandwidth, 240MHz 0.1dB bandwidth Single amplifiers are available in SOT-23 packages and duals in a 10-pin MSOP package for applications where board space is critical. Additionally, singles and duals are available in the industry-standard 8-pin SO package. All parts operate over the industrial temperature range of -40°C to +85°C. Applications • <1mV input offset • Very high open loop gains 92dB • Low supply current = 6mA • 140mA output current • Single supplies from 5V to 12V • Dual supplies from ±2.5V to ±5V • Fast disable on the EL5156 and EL5256 • Low cost • Imaging • Instrumentation • Video • Communications devices Ordering Information PART NUMBER • 700V/µs slew rate PACKAGE TAPE & REEL PKG. DWG. # EL5156IS 8-Pin SO - MDP0027 EL5156IS-T7 8-Pin SO 7” MDP0027 EL5156IS-T13 8-Pin SO 13” MDP0027 EL5157IW-T7 5-Pin SOT-23 7” (3K pcs) MDP0038 EL5157IW-T7A 5-Pin SOT-23 7” (250 pcs) MDP0038 EL5256IY 10-Pin MSOP - MDP0043 EL5256IY-T7 10-Pin MSOP 7” MDP0043 EL5256IY-T13 10-Pin MSOP 13” MDP0043 EL5257IS 8-Pin SO - MDP0027 EL5257IS-T7 8-Pin SO 7” MDP0027 EL5257IS-T13 8-Pin SO 13” MDP0027 EL5257IY 8-Pin MSOP - MDP0043 EL5257IY-T7 8-Pin MSOP 7” MDP0043 EL5257IY-T13 8-Pin MSOP 13” MDP0043 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners. EL5156, EL5157, EL5256, EL5257 Pinouts EL5157 (5-PIN SOT-23) TOP VIEW EL5156 (8-PIN SO) TOP VIEW NC 1 IN- 2 IN+ 3 + VS- 4 8 CE OUT 1 7 VS+ VS- 2 6 OUT IN+ 3 INA+ 1 4 IN- EL5257 (8-PIN SO) TOP VIEW 10 INA+ VS- 3 CEB 4 + - 5 NC EL5256 (10-PIN MSOP) TOP VIEW CEA 2 5 VS+ + - 9 OUTA INA- 2 8 VS+ INA+ 3 7 OUTB 6 INB- INB+ 5 2 OUTA 1 VS- 4 8 VS+ 7 OUTB + 6 INB+ 5 INB+ EL5156, EL5157, EL5256, EL5257 Absolute Maximum Ratings (TA = 25°C) Supply Voltage between VS and GND. . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125°C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Current into IN+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562Ω, RL = 150Ω, TA = 25°C, unless otherwise specified. DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE BW -3dB Bandwidth AV = +1, RL = 500Ω, CL = 4.7pF 600 MHz AV = +2, RL = 150Ω 180 MHz GBWP Gain Bandwidth Product RL = 150Ω 210 MHz BW1 0.1dB Bandwidth AV = +2 70 MHz SR Slew Rate VO = -3.2V to +3.2V, AV = +2, RL = 150Ω 640 V/µs VO = -3.2V to +3.2V, AV = +1, RL = 500Ω 700 V/µs 15 ns 500 tS 0.1% Settling Time AV = +1 dG Differential Gain Error AV = +2, RL = 150Ω 0.005 % dP Differential Phase Error AV = +2, RL = 150Ω 0.04 ° VN Input Referred Voltage Noise 12 nV/√Hz IN Input Referred Current Noise 5.5 pA/√Hz DC PERFORMANCE VOS Offset Voltage TCVOS Input Offset Voltage Temperature Coefficient Measured from TMIN to TMAX AVOL Open Loop Gain VO is from -2.5V to 2.5V -1 10 0.5 1 mV -3 µV/°C 40 kV/V INPUT CHARACTERISTICS CMIR Common Mode Input Range Guaranteed by CMRR test CMRR Common Mode Rejection Ratio VCM = 2.5V to -2.5V 80 108 IB Input Bias Current EL5156 & EL5157 -1 -0.4 +1 µA EL5256 & EL5257 -600 -200 +600 nA -250 100 +250 nA 10 25 MΩ 1 pF IOS Input Offset Current RIN Input Resistance CIN Input Capacitance -2.5 +2.5 V dB OUTPUT CHARACTERISTICS VOUT IOUT Output Voltage Swing Peak Output Current RL = 150Ω to GND ±3.4 ±3.6 V RL = 500Ω to GND ±3.6 ±3.8 V RL = 10Ω to GND ±80 ±140 mA ENABLE (EL5156 and EL5256 ONLY) tEN Enable Time 200 ns tDIS Disable Time 300 ns 3 EL5156, EL5157, EL5256, EL5257 Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562Ω, RL = 150Ω, TA = 25°C, unless otherwise specified. DESCRIPTION CONDITIONS IIHCE CE Pin Input High Current CE = VS+ IILCE CE Pin Input Low Current CE = VS- VIHCE CE Input High Voltage for Power-down VILCE CE Input Low Voltage for Power-up MIN 5 TYP MAX UNIT 0 -1 µA 13 25 µA VS+ -1 V VS+ -3 V SUPPLY ISON Supply Current - Enabled (per amplifier) ISOFF PSRR No load, VIN = 0V, CE = +5V 5.1 6.0 6.9 mA Supply Current - Disabled (per amplifier) No load, VIN = 0V, CE = 5V 5 13 25 µA Power Supply Rejection Ratio 75 90 DC, VS = ±3.0V to ±6.0V dB Typical Performance Curves 4 2 135 RL=150Ω CL=4.7pF 90 1 AV=+2 0 -1 -2 AV=+10 -3 45 AV=+1 AV=+2 -45 AV=+5 -90 AV=+10 -135 -180 AV=+5 -4 RL=150Ω CL=4.7pF 0 PHASE (°) NORMALIZED GAIN (dB) 3 -225 -5 -270 -6 100K 1M 10M 100M -315 100K 1G 1M FREQUENCY (Hz) FIGURE 1. SMALL SIGNAL FREQUENCY RESPONSE - GAIN 5 1 4 3 RL=500Ω 0 -1 RL=150Ω -2 RL=750Ω -3 CL=10pF CL=4.7pF 1 0 -1 CL=1pF -3 -4 -5 -6 100K 1G CL=27pF -2 RL=50Ω -4 AV=+1 RL=500Ω 2 GAIN (dB) NORMALIZED GAIN (dB) 2 VS=±5V AV=+2 RF=RG=562Ω 100M FIGURE 2. SMALL SIGNAL FREQUENCY RESPONSE PHASE FOR VARIOUS GAINS 4 3 10M FREQUENCY (Hz) 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 3. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL 4 -5 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 4. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued) 5 3 16 AV=+2 RL=500Ω RF=RG=500Ω 14 22pF 12 2 8.2pF 0 4.7pF -1 0pF -2 4 10pF 2 0pF -4 -2 10M 100M 33pF 6 0 1M -4 100K 1G 1M FREQUENCY (Hz) 3 1G 5 AV=+5 RL=500Ω 100pF 2 82pF 68pF 1 0 22pF -1 -2 -3 -5 100K 4 3 RL=500Ω CL=4.7pF AV=+1 2 ±2.0V 1 0 ±3.0V -1 ±4.0V -2 ±5.0V -3 -4 -4 1M 10M 100M 100K 1G 1M FIGURE 7. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL 4 4 3 NORMALIZED GAIN (dB) AV=+1 2 1 0 -1 -2 -3 -4 -5 100K AV=+2 AV=+1 RL=500Ω CL=4.7pF 1M AV=+5 10M 2 VS=±5V RF=620Ω RL=150Ω AV=-1 1 0 -1 -2 AV=-2 -3 -4 -5 100M 1G FREQUENCY (Hz) FIGURE 9. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS GAINS 5 500M FIGURE 8. FREQUENCY RESPONSE vs POWER SUPPLY 5 3 100M 10M FREQUENCY (Hz) FREQUENCY (Hz) NORMALIZED GAIN (dB) 100M FIGURE 6. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 10M FREQUENCY (Hz) FIGURE 5. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL 5 180pF 100pF 8 -3 -5 100K AV=+2 RF=RG=562Ω RL=150Ω 10 10pF 1 GAIN (dB) NORMALIZED GAIN (dB) 4 -6 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 10. SMALL SIGNAL INVERTING FREQUENCY RESPONSE FOR VARIOUS GAINS EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued) NORMALIZED GAIN (dB) 5 AV=+1 CL=0.2pF 4 RL=500Ω 2 1 NORMALIZED GAIN (dB) 4 3 RL=300Ω 0 -1 RL=150Ω -2 -3 -4 -5 3 AV=+1 CL=4.7pF 500Ω 2 1 0 -1 200Ω -2 100Ω -3 50Ω -4 -6 100K 1M 10M 100M -5 100K 1G 1M FIGURE 11. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL 2 4 12pF NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 3 8.2pF 4.7pF 1 0 -1 0.2pF -2 0pF -3 -4 3 2 1 AV=+5 CL=4.7pF RL=500Ω RF=102Ω 68pF 47pF 0 -1 22pF 4.7pF 0pF -2 -3 -4 -5 -5 100K 1M 10M 100M 200M 100K 1M FREQUENCY (Hz) 6 5 RF=RG=1kΩ NORMALIZED GAIN NORMALIZED GAIN (dB) 1 VS=±5V AV=+2 RL=150Ω CL=4.7pF 0 -1 350Ω 562Ω 500Ω 250Ω -2 -3 4 1G FREQUENCY (Hz) FIGURE 15. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RF AND RG 6 500Ω 0 200Ω -1 -3 100M 1kΩ 1 -5 10M 2kΩ 2 -2 1M RF=RG=3kΩ AV=+2 CL=4.7pF RL=500Ω 3 -4 -6 100K 100M 200M FIGURE 14. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CIN 4 2 10M FREQUENCY (Hz) FIGURE 13. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CIN 3 1G FIGURE 12. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL 5 AV=+2 RL=500Ω CL=4.7pF RF=500Ω 100M FREQUENCY (Hz) FREQUENCY (Hz) 4 10M -4 100K 1M 10M 100M FREQUENCY (Hz) FIGURE 16. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RF/RG 1G EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued) 4 3 5 AV=+2 RL=200Ω CL=4.7pF 2 1 -20dBm 0 10dBm -1 15dBm -2 17dBm -3 20dBm -4 -5 100K 1M CHANNEL #1 4 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 5 3 CHANNEL #2 2 1 0 -1 -2 AV=+1 RL=500Ω CL=4.7pF -3 -4 100M 10M -5 100K 600M 1M FREQUENCY (Hz) 700 AV=+1,RL=500Ω, CL=5pF 600 500 BW (MHz) CROSS TALK (10dB) AV=+5 RL=500Ω CL=4.7pF -30 -40 -50 -60 -70 AV=+1, RL=150Ω 400 300 200 -80 AV=+2,RL=150Ω 100 -90 -100 100K 1M 10M 100M 0 4.5 1G 5.5 6.5 7.5 8.5 VS (V) FREQUENCY (Hz) FIGURE 19. EL5256 CROSS TALK vs FREQUENCY CHANNEL A TO B & B TO A NORMALIZED GAIN (dB) 3 2 1 500Ω 1000Ω 0 -1 -2 -3 100Ω -4 50Ω -5 1M 10.5 11.5 1K AV=+5 CL=4.7pF -6 100K 9.5 FIGURE 20. BANDWIDTH vs SUPPLY VOLTAGE VOLTAGE NOISE (nV/√Hz), CURRENT NOISE (pA/√Hz) 4 1G FIGURE 18. CHANNEL TO CHANNEL FREQUENCY RESPONSE 0 -20 100M FREQUENCY (Hz) FIGURE 17. LARGE SIGNAL FREQUENCY RESPONSE FOR VARIOUS INPUT AMPLITUDES -10 10M 10M 100M 1G FREQUENCY (Hz) FIGURE 21. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL 7 100 VN 10 IN 1 10 100 1K 10K 100K 1M 10M FREQUENCY (Hz) FIGURE 22. VOLTAGE AND CURRENT NOISE vs FREQUENCY EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued) -20 1000 -30 IMPEDANCE (Ω) CMRR (dB) -40 -50 -60 -70 -80 -90 AV=+2 RL=0Ω RG=RF=400Ω 100 10 1 0.01 -100 -110 0.001 100 1K 10K 100K 1M 10M 100M 1K 10K FREQUENCY (Hz) FIGURE 23. CMRR -30 100M 10M 6.1 VS=±5V AV=+2 RL=150Ω 6 -40 5.9 -50 5.8 -60 -70 -80 -90 5.5 -100 5.4 1M 10M 100M IS- 5.7 5.6 -110 100K 1M FIGURE 24. OUTPUT IMPEDANCE IS (mA) DISABLED ISOLATION (dB) -10 -20 100K FREQUENCY (Hz) IS+ 5.3 4.5 5 5.5 6 6.5 7 7.5 8 8.5 9 9.5 10 10.51111.5 12 1G FREQUENCY (Hz) VS (V) FIGURE 25. INPUT TO OUTPUT ISOLATION vs FREQUENCY DISABLE FIGURE 26. SUPPLY CURRENT vs SUPPLY VOLTAGE 0.8 AV=+2 RL=500Ω SUPPLY=±5.0V ±12.3mA PEAKING (dB) ENABLE 192ns 0.7 DISABLE 322ns 0.6 AV=+1 RL=500Ω CL=5pF 0.5 0.4 0.3 0.2 0.1 TIME (400ns/DIV) FIGURE 27. ENABLE/DISABLE RESPONSE 8 0 4.5 5.5 6.5 7.5 8.5 VS (V) 9.5 10.5 11.5 FIGURE 28. PEAKING vs SUPPLY VOLTAGE EL5156, EL5157, EL5256, EL5257 AV=+2 RL=500Ω SUPPLY=±5.0V ±12.3mA OUTPUT=200mVP-P VOUT (40mV/DIV) VOUT (40mV/DIV) Typical Performance Curves (Continued) 0 RISE 20%-80% ∆T=2.025ns 0 FALL 80%-20% ∆T=1.91ns AV=+2 RL=500Ω SUPPLY=±5.0V ±12.3mA OUTPUT=200mVP-P TIME (4ns/DIV) TIME (4ns/DIV) FIGURE 30. SMALL SIGNAL FALL TIME AV=+2 RL=500Ω SUPPLY=±5.0V ±12.3mA OUTPUT=2.0VP-P VOUT (400mV/DIV) VOUT (400mV/DIV) FIGURE 29. SMALL SIGNAL RISE TIME 0 RISE 20%-80% ∆T=1.657ns AV=+2 RL=500Ω SUPPLY=±5.0V ±12.3mA OUTPUT=2.0VP-P 0 FALL 80%-20% ∆T=1.7ns TIME (2ns/DIV) TIME (2ns/DIV) FIGURE 32. LARGE SIGNAL FALL TIME FIGURE 31. LARGE SIGNAL RISE TIME 1.2 1.6 POWER DISSIPATION (W) POWER DISSIPATION (W) 1.8 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.4 1.2 1.136W SO8 θJA=110°C/W 1 0.8 0.6 543mW 0.4 SOT23-5 θJA=230°C/W 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 33. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 9 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1 781mW 0.8 SO8 θJA=160°C/W 0.6 0.4 488mW SOT23-5 θJA=256°C/W 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 34. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued) 1 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD POWER DISSIPATION (W) POWER DISSIPATION (W) 0.9 870mW 0.8 0.7 MSOP8/10 0.6 θJA=115°C/W 0.6 0.5 0.4 0.3 0.2 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 0.5 486mW MSOP8/10 0.4 θJA=206°C/W 0.3 0.2 0.1 0.1 0 0 0 25 50 75 85 100 125 AMBIENT TEMPERATURE (°C) FIGURE 35. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 10 0 25 50 75 85 100 125 AMBIENT TEMPERATURE (°C) FIGURE 36. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE EL5156, EL5157, EL5256, EL5257 Product Description The EL5156, EL5157, EL5256, and EL5257 are wide bandwidth, single or dual supply, low power and low offset voltage feedback operational amplifiers. Both amplifiers are internally compensated for closed loop gain of +1 or greater. Connected in voltage follower mode and driving a 500Ω load, the -3dB bandwidth is about 610MHz. Driving a 150Ω load and a gain of 2, the bandwidth is about 180MHz while maintaining a 600V/µs slew rate. The EL5156 and EL5256 are available with a power down pin to reduce power to 17µA typically while the amplifier is disabled. Input, Output and Supply Voltage Range The EL5156 and EL5157 families have been designed to operate with supply voltage from 5V to 12V. That means for single supply application, the supply voltage is from 5V to 12V. For split supplies application, the supply voltage is from ±2.5V to ±5V. The amplifiers have an input common mode voltage range from 1.5V above the negative supply (VS- pin) to 1.5V below the positive supply (VS+ pin). If the input signal is outside the above specified range, it will cause the output signal distorted. The outputs of the EL5156 and EL5157 families can swing from -4V to 4V for VS = ±5V. As the load resistance becomes lower, the output swing is lower. If the load resistor is 500Ω, the output swing is about -4V at a 4V supply. If the load resistor is 150Ω, the output swing is from -3.5V to 3.5V. Choice of Feedback Resistor and Gain Bandwidth Product For applications that require a gain of +1, no feedback resistor is required. Just short the output pin to the inverting input pin. For gains greater than +1, the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As this pole becomes smaller, the amplifier's phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF can't be very big for optimum performance. If a large value of RF must be used, a small capacitor in the few Pico farad range in parallel with RF can help to reduce the ringing and peaking at the expense of reducing the bandwidth. For gain of +1, RF = 0 is optimum. For the gains other than +1, optimum response is obtained with RF between 500Ω to 750Ω. The EL5156 and EL5157 families have a gain bandwidth product of 210MHz. For gains > = 5, its bandwidth can be predicted by the following equation: (Gain)X(BW) = 210MHz. Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150Ω, because of the change in output current with DC level. The dG and dP for these families are about 0.006% 11 and 0.04%, while driving 150Ω at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance. Driving Capacitive Loads and Cables The EL5156 and EL5157 families can drive 27pF loads in parallel with 500Ω with less than 5dB of peaking at gain of +1. If less peaking is desired in applications, a small series resistor (usually between 5Ω to 50Ω) can be placed in series with the output to eliminate most peaking. However, this will reduce the gain slightly. If the gain setting is greater than 1, the gain resistor RG can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can help to reduce peaking. Disable/Power-Down The EL5156 and EL5256 can be disabled and their output placed in a high impedance state. The turn off time is about 330ns and the turn on time is about 130ns. When disabled, the amplifier's supply current is reduced to 17µA typically, thereby effectively eliminating the power consumption. The amplifier's power down can be controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or applying a signal that is less than 0.8V above VS- will enable the amplifier. The amplifier will be disabled when the signal at ENABLE pin is above VS+ -1.5V. Output Drive Capability The EL5156 and EL5157 families do not have internal short circuit protection circuitry. They have a typical short circuit current of 95mA and 70mA. If the output is shorted indefinitely, the power dissipation could easily overheat the die or the current could eventually compromise metal integrity. Maximum reliability is maintained if the output current never exceeds ±40mA. This limit is set by the design of the internal metal interconnect. Note that in transient applications, the part is robust. Power Dissipation With the high output drive capability of the EL5156 and EL5157 families, it is possible to exceed the 125°C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if the load conditions or package types need to be modified for the amplifier to remain in the safe operating area. EL5156, EL5157, EL5256, EL5257 The maximum power dissipation allowed in a package is determined according to: Power Supply Bypassing and Printed Circuit Board Layout T JMAX – T AMAX PD MAX = -------------------------------------------Θ JA As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as sort as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7µF tantalum capacitor in parallel with a 0.1µF ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature θJA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing: n V OUTi ∑ ( VS – VOUTi ) × ---------------R Li PD MAX = V S × I SMAX + i=1 For sinking: n ∑ ( VOUTi – VS ) × ILOADi PD MAX = V S × I SMAX + i=1 Where: For good AC performance, parasitic capacitance should be kept to minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces. VS = Supply voltage ISMAX = Maximum quiescent supply current VOUT = Maximum output voltage of the application RLOAD = Load resistance tied to ground ILOAD = Load current N = number of amplifiers (Max = 2) By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat. All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 12