EL2227 ® Data Sheet September 14 ,2010 Dual, Very Low Noise Amplifier Features The EL2227 is a dual, low-noise amplifier, ideally suited to line receiving applications in ADSL and HDSLII designs. With low noise specification of just 1.9nV/√Hz and 1.2pA/√Hz, the EL2227 is perfect for the detection of very low amplitude signals. • Voltage noise of only 1.9nV/√Hz The EL2227 features a -3dB bandwidth of 115MHz and is gain-of-2 stable. The EL2227 also affords minimal power dissipation with a supply current of just 4.8mA per amplifier. The amplifier can be powered from supplies ranging from ±2.5V to ±12V. • Just 4.8mA per amplifier • Current noise of only 1.2pA/√Hz • Bandwidth (-3dB) of 115MHz @AV = +2 • Gain-of-2 stable • 8 Ld MSOP and 8 Ld SOIC package • ±2.5V to ±12V operation • Pb-free available (RoHS compliant) The EL2227 is available in a space-saving 8 Ld MSOP package as well as the industry-standard 8 Ld SOIC. It can operate over the -40°C to +85°C temperature range. Applications Pinout • HDSLII receivers 1 VINA- 2 • ADSL receivers • Ultrasound input amplifiers EL2227 (8 LD SOIC, 8 LD MSOP) TOP VIEW VOUTA FN7058.4 • Wideband instrumentation 8 VS+ 7 VOUTB 6 VINB- 5 VINB+ • Communications equipment • AGC and PLL active filters + VINA+ 3 + VS- 4 • Wideband sensors Ordering Information . PART NUMBER PART MARKING TEMP RANGE (°C) PACKAGE PKG. DWG.# EL2227CYZ* BASAA (Note) -40 to +85 8 Ld MSOP M8.118A (3.0mm) (Pb-free) EL2227CS* -40 to +85 8 Ld SOIC (150 mil) 2227CS EL2227CSZ* 2227CSZ (Note) M8.15E -40 to +85 8 Ld SOIC M8.15E (150 mil) (Pb-free) *Add “-T7” or “-T13” suffix for tape and reel. Please refer to TB347 for details on reel specifications. NOTE: These Intersil Pb-free plastic packaged products employ special Pb-free material sets, molding compounds/die attach materials, and 100% matte tin plate plus anneal (e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations). Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2004, 2005, 2007, 2010. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL2227 Absolute Maximum Ratings Thermal Information Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . .28V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . VS- - 0.3V, VS +0.3V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 40mA Maximum Die Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C ESD Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2kV Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pb-Free Reflow Profile. . . . . . . . . . . . . . . . . . . . . . . . .see link below http://www.intersil.com/pbfree/Pb-FreeReflow.asp CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and result in failures not covered by warranty. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications VS+ = +12V, VS- = -12V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C, Unless Otherwise Specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT -0.2 3 mV INPUT CHARACTERISTICS VOS Input Offset Voltage TCVOS Average Offset Voltage Drift IB Input Bias Current RIN VCM = 0V -0.6 µV/°C -3.4 µA Input Impedance 7.3 MΩ CIN Input Capacitance 1.6 pF CMIR Common-Mode Input Range CMRR Common-Mode Rejection Ratio For VIN from -11.8V to 10.4V 60 94 dB AVOL Open-Loop Gain -5V ≤ VOUT ≤ 5V 70 87 dB eN Voltage Noise f = 100kHz 1.9 nV/√Hz iN Current Noise f = 100kHz 1.2 pA/√Hz RL = 500Ω -10.4 -10 V RL = 250Ω -9.8 -9 V VCM = 0V -9 -11.8 +10.4 V OUTPUT CHARACTERISTICS VOL Output Swing Low VOH Output Swing High RL = 500Ω RL = 250Ω 9.5 10 V ISC Short Circuit Current RL = 10Ω 140 180 mA 65 95 dB 10 10.4 V POWER SUPPLY PERFORMANCE PSRR Power Supply Rejection Ratio VS is moved from ±2.25V to ±12V IS Supply Current (Per Amplifier) No Load VS Operating Range 4.8 ±2.5 6.5 mA ±12 V DYNAMIC PERFORMANCE SR Slew Rate (Note 2) ±2.5V square wave, measured 25% to 75% 50 V/µs tS Settling to 0.1% (AV = +2) (AV = +2), VO = ±1V 65 ns BW -3dB Bandwidth RF = 358Ω 115 MHz HD2 2nd Harmonic Distortion f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 93 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 83 dBc f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 94 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 76 dBc HD3 3rd Harmonic Distortion 2 40 FN7058.4 September 14 ,2010 EL2227 Electrical Specifications VS+ = +5V, VS- = -5V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C, Unless Otherwise Specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT 0.2 3 mV INPUT CHARACTERISTICS VOS Input Offset Voltage TCVOS Average Offset Voltage Drift IB Input Bias Current RIN VCM = 0V -0.6 µV/°C -3.7 µA Input Impedance 7.3 MΩ CIN Input Capacitance 1.6 pF CMIR Common-Mode Input Range CMRR Common-Mode Rejection Ratio For VIN from -4.8V to 3.4V 60 97 dB AVOL Open-Loop Gain -5V ≤ VOUT ≤ 5V 70 84 dB eN Voltage Noise f = 100kHz 1.9 nV/√Hz iN Current Noise f = 100kHz 1.2 pA/√Hz RL = 500Ω -3.8 -3.5 V RL = 250Ω -3.7 -3.5 V VCM = 0V -9 -4.8 3.4 V OUTPUT CHARACTERISTICS VOL VOH ISC Output Swing Low Output Swing High Short Circuit Current RL = 500Ω 3.5 3.7 V RL = 250Ω 3.5 3.6 V RL = 10Ω 60 100 mA 65 95 dB POWER SUPPLY PERFORMANCE PSRR Power Supply Rejection Ratio VS is moved from ±2.25V to ±12V IS Supply Current (Per Amplifier) No Load VS Operating Range 4.5 ±2.5 5.5 mA ±12 V DYNAMIC PERFORMANCE SR Slew Rate ±2.5V square wave, measured 25% to 75% tS Settling to 0.1% (AV = +2) BW HD2 HD3 45 V/µs (AV = +2), VO = ±1V 77 ns -3dB Bandwidth RF = 358Ω 90 MHz 2nd Harmonic Distortion f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 98 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 90 dBc f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 94 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 79 dBc 3rd Harmonic Distortion 3 35 FN7058.4 September 14 ,2010 EL2227 4 4 3 3 2 1 RF = 1kΩ RF = 620Ω 0 -1 RF = 100Ω -2 RF = 350Ω -3 -4 -5 -6 1M VS = ±12V AV = +2 RL = 500Ω 10M NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) Typical Performance Curves RF = 100Ω RF = 350Ω 2 1 0 -1 RF = 420Ω -2 RF = 620Ω -3 -4 -5 VS = ±12V AV = -1 RL = 500Ω -6 1M 100M 200M 10M FIGURE 2. INVERTING FREQUENCY RESPONSE FOR VARIOUS RF 4 4 3 3 2 AV = 2 0 AV = 10 AV = 5 -2 -3 -4 -5 -6 1M VS = ±12V RF = 350Ω RL = 500Ω 10M NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) FIGURE 1. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS RF -1 2 0 -2 -3 -4 -5 AV = -10 AV = -5 VS = ±12V RF = 420Ω RL = 500Ω 10M FIGURE 4. INVERTING FREQUENCY RESPONSE (GAIN) 135 135 90 90 0 0 AV = 2 PHASE (°) PHASE (°) 45 AV = 5 45 -45 -90 AV = 10 -135 -270 -315 1M 100M 200M FREQUENCY (Hz) FIGURE 3. NON-INVERTING FREQUENCY RESPONSE (GAIN) -225 AV = -1 -1 -6 1M 100M 200M AV = -2 1 FREQUENCY (Hz) -180 100M 200M FREQUENCY (Hz) FREQUENCY (Hz) 1 RF = 1kΩ -45 -90 -135 AV = -1 AV = -2 AV = -10 AV = -5 -180 VS = ±12 RF = 350Ω RL = 500Ω -225 -270 10M 100M200M FREQUENCY (Hz) FIGURE 5. NON-INVERTING FREQUENCY RESPONSE (PHASE) 4 -315 1M VS = ±12V RF = 420Ω RL = 500Ω 10M 100M 200M FREQUENCY (Hz) FIGURE 6. INVERTING FREQUENCY RESPONSE (PHASE) FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) 3 2 1 VS = ±12V RF = 350Ω VIN = 20mVP-P AV = +2 RL = 500Ω VIN = 100mVP-P 0 -1 VIN = 500mVP-P -2 VIN = 1VP-P -3 -4 VIN = 2VP-P -5 -6 100k 1M 10M 4 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 3 2 0 -1 -2 -3 -4 -5 VIN = 2.8VP-P VIN = 280mVP-P VS ±12V RF = 420Ω RL = 500Ω AV = -1 -6 1M 100M 10M FREQUENCY (Hz) FIGURE 8. INVERTING FREQUENCY RESPONSE FOR VARIOUS INPUT SIGNAL LEVELS 4 CL = 30pF 4 3 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 5 CL = 12pF 2 1 0 CL = 2pF -1 VS = ±12V -2 V = 620Ω RSF=±1 -3 2V RL = 500Ω -4 R = +2 AF=62 V -5 1M 10M CL = 30pF 3 2 CL = 12pF 1 0 -1 CL = 2pF -2 -3 -4 -5 VS ± 12V R F = 420Ω RL = 500Ω AV = -1 -6 1M 100M 200M 10M FREQUENCY (Hz) 3 RL = 100Ω 2 0 -4 -5 -6 1M RL = 50Ω VS = ±12V RF = 620Ω CL = 15pF AV = +2 10M 100M 200M FREQUENCY (Hz) FIGURE 11. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS RL 5 4 RL = 500Ω 1 -1 FIGURE 10. INVERTING FREQUENCY RESPONSE FOR VARIOUS CL NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 100M 200M FREQUENCY (Hz) FIGURE 9. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS CL -3 100M 200M FREQUENCY (Hz) FIGURE 7. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS INPUT SIGNAL LEVELS -2 VIN = 20mVP-P VIN = 1.4VP-P 1 VO = +10V 3 VO = -10V 2 VO = +5V 1 0 -1 VO = 0V -2 -3 -4 -5 VS = ±12V RF = 620Ω RL = 500Ω AV = +2 -6 100k VO = -5V 1M 10M 100M FREQUENCY (Hz) FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS OUTPUT DC LEVELS FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) AV = +2 120 RF = 620Ω RL = 500Ω 100 4.0 AV = +2 80 A V= -2 60 AV = +5 40 AV = -5 AV = +10 20 0 AV = +2 3.5 AV = -1 PEAKING (dB) 3dB BANDWIDTH (MHz) 140 3.0 AV = -1 2.5 2.0 1.5 AV = +10 AV = -10 1.0 AV = +5 0.5 AV = -10 2 4 8 6 10 12 AV = +2 RF = 620Ω RL = 500Ω 0 2 SUPPLY VOLTAGE (±V) 4 AV = -2 AV = -5 6 10 8 12 SUPPLY VOLTAGE (±V) FIGURE 13. 3dB BANDWIDTH vs SUPPLY VOLTAGE FIGURE 14. PEAKING vs SUPPLY VOLTAGE RF = 620Ω AV = 2 RL = 500Ω 0.5V/DIV RF = 620Ω AV = 2 RL = 500Ω 0.5V/DIV 100ns/DIV 100ns/DIV FIGURE 15. LARGE SIGNAL STEP RESPONSE (VS = ±12V) FIGURE 16. LARGE SIGNAL STEP RESPONSE (VS = ±2.5V) RF = 620Ω AV = 2 RL = 500Ω 20mV/DIV RF = 620Ω AV = 2 RL = 500Ω 20mV/DIV 100ns/DIV FIGURE 17. SMALL SIGNAL STEP RESPONSE (VS = ±12V) 6 100ns/DIV FIGURE 18. SMALL SIGNAL STEP RESPONSE (VS = ±2.5V) FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) 10 0.10 8 dG (%) OR dP (°) 6 GROUP DELAY (ns) 0.08 AV = 5V 4 2 AV = 2V 0 -2 -4 -6 -8 -10 1M VS = ±12V RF = 620Ω RL = 500Ω PIN = -20dBm into 50Ω 0.06 0.04 0 -0.02 -1.0 100M 10M dG 0.5 1.0 FIGURE 20. DIFFERENTIAL GAIN/PHASE vs DC INPUT VOLTAGE AT 3.58MHz 100 OUTPUT IMPEDANCE (Ω) 12 1.2/DI 6 1.2/DI 0 6 10 1 0.1 0.01 10k 12 10M FIGURE 22. CLOSED LOOP OUTPUT IMPEDANCE vs FREQUENCY 0 90 20 PSRR (dB) 110 70 50 30 40 VS- 60 VS+ 80 VS = ±12 100 1k 10k 100k 1M FREQUENCY (Hz) FIGURE 23. CMRR 7 100M FREQUENCY (Hz) FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE 10 10 1M 100k SUPPLY VOLTAGE (±V) -CMRR (dB) 0 -0.5 DC INPUT VOLTAGE (V) FIGURE 19. GROUP DELAY vs FREQUENCY SUPPLY CURRENT (mA) dP 0.02 FREQUENCY (Hz) 0 AV = 2 RF = 620Ω RL = 150Ω fO = 3.58MHz 10M 100M 100 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) FIGURE 24. PSRR FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) -40 2nd -60 -70 3rd H -80 -70 0 8 4 12 16 3rd H -90 -100 20 2nd -80 -90 -100 AV = 2 RF = 358Ω RL = 500Ω -60 DISTORTION (dBc) -50 DISTORTION (dBc) -50 AV = 2 RF = 620Ω RL = 500Ω 0 -60 -60 -70 -70 RL = 50 -90 -100 RL = 500 -110 -120 1 10 2 2.5 RL = 50 -80 -90 RL = 500 -100 -110 100 1000 -120 1 10 100 1000 FREQUENCY (kHz) FREQUENCY (kHz) FIGURE 27. TOTAL HARMONIC DISTORTION vs FREQUENCY @ 2VP-P VS = ±12V FIGURE 28. TOTAL HARMONIC DISTORTION vs FREQUENCY @ 2VP-P VS = ±2.5V 10 0 9 8 7 IN 6 5 4 3 EN 2 1 10 A→B -20 GAIN (dB) VOLTAGE NOISE (nV/√Hz), CURRENT NOISE (pA/√Hz) 1.5 1 FIGURE 26. 1MHz 2nd AND 3rd HARMONIC DISTORTION vs OUTPUT SWING FOR VS = ±2.5V THD (dBc) THD (dBc) FIGURE 25. 1MHz 2nd AND 3rd HARMONIC DISTORTION vs OUTPUT SWING FOR VS = ±12V -80 0.5 OUTPUT SWING (VP-P) OUTPUT SWING (VP-P) 100 -40 B→A -60 -80 1k 10k 100k FREQUENCY (Hz) FIGURE 29. VOLTAGE AND CURRENT NOISE vs FREQUENCY 8 -100 100k 1M 10M 100M FREQUENCY (Hz) FIGURE 30. CHANNEL-TO-CHANNEL ISOLATION vs FREQUENCY FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) 10.0 140 130 9.5 IS (mA) -3dB BANDWIDTH (MHz) 150 120 110 9.0 100 90 80 -40 -20 0 20 40 60 8.5 -50 80 100 120 140 50 0 100 150 DIE TEMPERATURE (°C) DIE TEMPERATURE (°C) FIGURE 31. -3dB BANDWIDTH vs TEMPERATURE FIGURE 32. SUPPLY CURRENT vs TEMPERATURE -2 2 IBIAS (µA) VOS (mV) -3 0 -2 -4 -5 -4 -50 0 50 100 -6 -50 150 55 150 160 140 53 SETTLING TIME (ns) SLEW RATE (V/µs) 100 FIGURE 34. INPUT BIAS CURRENT vs TEMPERATURE FIGURE 33. VOS vs TEMPERATURE 51 49 47 120 0 50 100 150 DIE TEMPERATURE (°C) FIGURE 35. SLEW RATE vs TEMPERATURE 9 VS = ±2.5V VO = 2VP-P VS = ±12V VO = 5VP-P 100 80 60 40 20 45 -50 50 0 DIE TEMPERATURE (°C) DIE TEMPERATURE (°C) 0 0.01 VS = ±12V VO = 2VP-P 0.1 1.0 ACCURACY (%) FIGURE 36. SETTLING TIME vs ACCURACY FN7058.4 September 14 ,2010 EL2227 Typical Performance Curves (Continued) POWER DISSIPATION (W) 0.9 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 781m 0.8 θ 0.7 JA 607m 0.6 0.5 MS θJ A= 0.4 0.3 0.2 +2 OP 06 °C = +1 SO 8 60 °C /W 8 /W 0.1 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 37. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE Pin Descriptions EL2227CY EL2227CS 8 Ld MSOP 8 Ld SOIC 1 1 PIN NAME PIN FUNCTION VOUTA Output EQUIVALENT CIRCUIT VS+ VOUT Circuit 1 2 2 VINA- Input VS+ VIN+ VIN- VS- Circuit 2 3 3 VINA+ Input 4 4 VS- Supply 5 5 VINB+ Input 6 6 VINB- Input Reference Circuit 2 7 7 VOUTB Output Reference Circuit 1 8 8 VS+ Supply 10 Reference Circuit 2 FN7058.4 September 14 ,2010 EL2227 Applications Information +12V Product Description 1k The EL2227 is a dual voltage feedback operational amplifier designed especially for DMT ADSL and other applications requiring very low voltage and current noise. It also features low distortion while drawing moderately low supply current and is built on Elantec's proprietary high-speed complementary bipolar process. The EL2227 use a classical voltage-feedback topology, which allows them to be used in a variety of applications where current-feedback amplifiers are not appropriate because of restrictions placed upon the feedback element used with the amplifier. The conventional topology of the EL2227 allows, for example, a capacitor to be placed in the feedback path, making it an excellent choice for applications such as active filters, sample-and-holds, or integrators. ADSL CPE Applications The low noise EL2227 amplifier is specifically designed for the dual differential receiver amplifier function with ADSL transceiver hybrids, as well as other low-noise amplifier applications. A typical ADSL CPE line interface circuit is shown in Figure 38. The EL2227 is used in receiving DMT down stream signal. With careful transceiver hybrid design and the EL2227 1.9nV/√Hz voltage noise and 1.2pA/√Hz current noise performance, -140dBm/Hz system background noise performance can be easily achieved. DRIVER INPUT + - ROUT RF RG ZLINE RF ROUT + LINE RF RECEIVE OUT + + RECEIVE AMPLIFIERS + RECEIVE OUT - LINE + RF R RIN R RIN FIGURE 38. TYPICAL LINE INTERFACE CONNECTION 1µF 10k 10k 1k + - 1µF 4.7µF 1k 75k FIGURE 39. IMPLEMENTATION OF ENABLE/DISABLE FUNCTION Power Dissipation With the wide power supply range and large output drive capability of the EL2227, it is possible to exceed the +150°C maximum junction temperatures under certain load and power supply conditions. It is therefore important to calculate the maximum junction temperature (TJMAX) for all applications to determine if power supply voltages, load conditions, or package type need to be modified for the EL2227 to remain in the safe operating area. These parameters are related in Equation 1: (EQ. 1) T JMAX = T MAX + ( θ JA × PD MAXTOTAL ) where: PDMAXTOTAL is the sum of the maximum power dissipation of each amplifier in the package (PDMAX) PDMAX for each amplifier can be calculated using Equation 2: V OUTMAX PD MAX = 2 × V S × I SMAX + ( V S – V OUTMAX ) × ---------------------------RL (EQ. 2) where: TMAX = Maximum Ambient Temperature θJA = Thermal Resistance of the Package PDMAX = Maximum Power Dissipation of 1 Amplifier VS = Supply Voltage Disable Function IMAX = Maximum Supply Current of 1 Amplifier The EL2227 is in the standard dual amplifier package without the enable/disable function. A simple way to implement the enable/disable function is depicted in Figure 39. When disabled, both the positive and negative supply voltages are disconnected (see Figure 39). VOUTMAX = Maximum Output Voltage Swing of the Application 11 RL = Load Resistance To serve as a guide for the user, we can calculate maximum allowable supply voltages for the example of the video cable-driver below since we know that TJMAX = +150°C, TMAX = +75°C, ISMAX = 9.5mA, and the package θJAs are shown in Table 1. If we assume (for this example) that we are driving a back-terminated video cable, then the maximum average value (over duty-cycle) of VOUTMAX is 1.4V, and RL = 150Ω, giving the results seen in Table 1. FN7058.4 September 14 ,2010 EL2227 Printed-Circuit Layout TABLE 1. θJA MAX PDISS @ TMAX PART PACKAGE EL2227CS SO8 160°C/W 0.406W @ +85°C EL2227CY MSOP8 206°C/W 0.315W @ +85°C MAX VS Single-Supply Operation The EL2227s have been designed to have a wide input and output voltage range. This design also makes the EL2227 an excellent choice for single-supply operation. Using a single positive supply, the lower input voltage range is within 200mV of ground (RL = 500Ω), and the lower output voltage range is within 875mV of ground. Upper input voltage range reaches 3.6V, and output voltage range reaches 3.8V with a 5V supply and RL = 500Ω. This results in a 2.625V output swing on a single 5V supply. This wide output voltage range also allows single-supply operation with a supply voltage as high as 28V. The EL2227s are well behaved, and easy to apply in most applications. However, a few simple techniques will help assure rapid, high quality results. As with any high-frequency device, good PCB layout is necessary for optimum performance. Ground-plane construction is highly recommended, as is good power supply bypassing. A 0.1µF ceramic capacitor is recommended for bypassing both supplies. Lead lengths should be as short as possible, and bypass capacitors should be as close to the device pins as possible. For good AC performance, parasitic capacitances should be kept to a minimum at both inputs and at the output. Resistor values should be kept under 5kΩ because of the RC time constants associated with the parasitic capacitance. Metal-film and carbon resistors are both acceptable, use of wire-wound resistors is not recommended because of their parasitic inductance. Similarly, capacitors should be low-inductance for best performance. Gain-Bandwidth Product and the -3dB Bandwidth The EL2227s have a gain-bandwidth product of 137MHz while using only 5mA of supply current per amplifier. For gains greater than 2, their closed-loop -3dB bandwidth is approximately equal to the gain-bandwidth product divided by the noise gain of the circuit. For gains less than 2, higher order poles in the amplifiers' transfer function contribute to even higher closed loop bandwidths. For example, the EL2227 have a -3dB bandwidth of 115MHz at a gain of +2, dropping to 28MHz at a gain of +5. It is important to note that the EL2227 have been designed so that this “extra” bandwidth in low-gain applications does not come at the expense of stability. As seen in the typical performance curves, the EL2227 in a gain of +2 only exhibit 0.5dB of peaking with a 1000Ω load. Output Drive Capability The EL2227s have been designed to drive low impedance loads. They can easily drive 6VP-P into a 500Ω load. This high output drive capability makes the EL2227 an ideal choice for RF, IF and video applications. All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 12 FN7058.4 September 14 ,2010 EL2227 Package Outline Drawing M8.15E 8 LEAD NARROW BODY SMALL OUTLINE PLASTIC PACKAGE Rev 0, 08/09 4 4.90 ± 0.10 A DETAIL "A" 0.22 ± 0.03 B 6.0 ± 0.20 3.90 ± 0.10 4 PIN NO.1 ID MARK 5 (0.35) x 45° 4° ± 4° 0.43 ± 0.076 1.27 0.25 M C A B SIDE VIEW “B” TOP VIEW 1.75 MAX 1.45 ± 0.1 0.25 GAUGE PLANE C SEATING PLANE 0.10 C 0.175 ± 0.075 SIDE VIEW “A 0.63 ±0.23 DETAIL "A" (0.60) (1.27) NOTES: (1.50) (5.40) 1. Dimensions are in millimeters. Dimensions in ( ) for Reference Only. 2. Dimensioning and tolerancing conform to AMSE Y14.5m-1994. 3. Unless otherwise specified, tolerance : Decimal ± 0.05 4. Dimension does not include interlead flash or protrusions. Interlead flash or protrusions shall not exceed 0.25mm per side. 5. The pin #1 identifier may be either a mold or mark feature. 6. Reference to JEDEC MS-012. TYPICAL RECOMMENDED LAND PATTERN 13 FN7058.4 September 14 ,2010 EL2227 Package Outline Drawing M8.118A 8 LEAD MINI SMALL OUTLINE PLASTIC PACKAGE (MSOP) Rev 0, 9/09 3.0±0.1 8 A 0.25 CAB 3.0±0.1 4.9±0.15 DETAIL "X" 1.10 Max PIN# 1 ID B SIDE VIEW 2 1 0.18 ± 0.05 2 0.65 BSC TOP VIEW 0.95 BSC 0.86±0.09 H GAUGE PLANE C 0.25 SEATING PLANE 0.33 +0.07/ -0.08 0.08 C A B 0.10 ± 0.05 3°±3° 0.10 C 0.55 ± 0.15 DETAIL "X" SIDE VIEW 1 5.80 NOTES: 4.40 3.00 1. Dimensions are in millimeters. 2. Dimensioning and tolerancing conform to JEDEC MO-187-AA and AMSE Y14.5m-1994. 3. Plastic or metal protrusions of 0.15mm max per side are not included. 4. Plastic interlead protrusions of 0.25mm max per side are not included. 5. Dimensions “D” and “E1” are measured at Datum Plane “H”. 6. This replaces existing drawing # MDP0043 MSOP 8L. 0.65 0.40 1.40 TYPICAL RECOMMENDED LAND PATTERN 14 FN7058.4 September 14 ,2010