A8510 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver Description Features and Benefits • Integrated 2 MHz capable boost converter with 60 V DMOS switch with OVP protection • Sync function to synchronize boost converter switching frequencies up to 2.3 MHz • LED current up to 40 mA per LED channel into 8 channels • Drives up to 12 series LEDs in 8 parallel strings (Vf = 3.5 V, If = 40 mA), VIN = 8 V, switching frequency of 1 MHz • Single EN/PWM pin interface for PWM dimming and enable functions • APWM pin for fine-tuning color adjustment and/or maximizing contrast ratio • Integrated driver for optional external PMOS input disconnect switch • Typical LED accuracy of 0.7% and 0.8% for LED-to-LED matching • Internal bias supply for single-supply operation from 5 to 40 V • Extensive protection features The A8510 is a multi-output white LED driver for LCD backlighting. It integrates a current-mode boost converter with internal power switch and 8 current sinks. The boost converter can drive up to 96 LEDs with 12 LEDs at 40 mA per string. The LED sinks can also be paralleled together to achieve even higher LED currents, up to 320 mA. The A8510 can operate from a single power supply, from 5 to 40 V. If required, the A8510 can drive an external P-FET to disconnect the input supply from the system in the event of a fault. The A8510 provides protection against output short and overvoltage, open or shorted diode, open or shorted LED pin, and overtemperature. A dual level cycle-by-cycle current limit function provides soft start and protects the internal current switch against high current overloads. The A8510 has a synchronization pin that allows PWM switching frequencies to be synchronized in the range of 580 kHz to 2.3 MHz. The device package is a 26-contact, 4 mm × 4 mm, 0.75 mm nominal overall height QFN, with exposed pad for enhanced thermal dissipation. It is lead (Pb) free, with 100% matte tin leadframe plating. Package: 26-pin QFN (suffix EC) Applications • Industrial LCD displays • Backlighting LCD displays • Infotainment displays Approximate scale 1:1 Typical Application Diagram RSC 0.056 Ω VIN RADJ 590 Ω CIN 4.7 μF/ 50 V VGATE VSENSE VIN VDD VC CVDD 0.1 μF 100 kΩ L1 22 μH Q1 D1 2 A / 60 V SW SW A8510 PAD FAULT EN/PWM APWM ISET RISET 8.25 kΩ RFSET 25.5 kΩ FSET/SYNC Figure 1. Typical Application Circuit showing VIN to GND short protection using P-MOSFET sensing A8510-DS, Rev. 2 AGND VOUT ROVP 169 kΩ OVP LED1 LED2 LED3 LED4 LED5 LED6 LED7 LED8 COMP PGND PGND CP 120 pF COUT 4.7 μF 50 V RZ 120 Ω CZ 0.47 μF Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Selection Guide Part Number A8510GECTR-T Packing 7000 pieces per 13-in. reel Absolute Maximum Ratings* Characteristic Symbol Notes LEDx Pin OVP Pin Rating Unit –0.3 to 55 V –0.3 to 60 V VSENSE and VGATE should not exceed VIN by more than 0.4 V. –0.3 to 40 V Continuous –0.6 to 62 V –1.0 V ¯ĀŪ¯L̄¯T̄ ¯ Pin F̄ –0.3 to 40 V ISET, FSET/SYNC, APWM, and COMP Pins –0.3 to 5.5 V –0.3 to 7 V VIN, VSENSE, VGATE Pins SW Pin t < 50 ns All other pins Operating Ambient Temperature TA –40 to 105 ºC Maximum Junction Temperature TJ(max) 150 ºC Tstg –55 to 150 ºC Storage Temperature Range G *Stresses beyond those listed in this table may cause permanent damage to the device. The Absolute Maximum ratings are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the Electrical Characteristics table is not implied. Exposure to Absolute-Maximum-rated conditions for extended periods may affect device reliability. Thermal Characteristics may require derating at maximum conditions Characteristic Package Thermal Resistance Symbol RθJA Test Conditions* On 2-layer, 3 in. × 3 in. PCB Value Unit 48.5 ºC/W *Additional thermal information available on the Allegro website Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 2 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Functional Block Diagram VDD SW SW Internal VCC Regulator UVLO VIN VREF 1.235 V Ref Internal VCC AGND + ∑ FSET/SYNC – Oscillator Diode Open + Sense Driver Circuit COMP – + Current Sense ISS – Internal Soft Start + PGND – VSENSE Thermal Shutdown Input Current Sense Amplifier IADJ Fault + PMOS Driver EN/PWM OVP Sense GOFF – VGATE OVP VREF Open/Short LED Detect Enable PWM 100 kΩ ISS LED1 LED2 LED3 LED4 LED5 LED6 LED7 LED8 LED Driver APWM Internal VCC ISET VREF ISET AGND FAULT PGND PGND AGND Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 3 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 22 OVP 23 SW 24 SW 25 VGATE 26 VSENSE Pin-out Diagram VIN 1 21 PGND FAULT 2 20 PGND NC 3 COMP 4 APWM 5 17 LED2 EN/PWM 6 16 LED3 FSET/SYNC 7 15 LED4 19 VDD LED5 14 LED6 13 18 LED1 LED7 12 LED8 11 AGND 10 9 NC ISET 8 PAD Terminal List Table Number Name 1 VIN Function 2 ¯ĀŪ¯L̄¯T̄ ¯ F̄ 3, 9 NC 4 COMP Output of the error amplifier and compensation node; connect a series RZCZ network from this pin to GND for control loop compensation. 5 APWM Analog trimming option or dimming; applying a digital PWM signal to this pin adjusts the internal ISET current. 6 EN/PWM PWM dimming pin used to control the LED intensity by using pulse width modulation, with the typical PWM dimming frequency is in the range of 200 Hz to 1 kHz; also used to enable the A8510. 7 FSET/SYNC 8 ISET 10 to 18 LED8 to LED1 Input power to the A8510 as well as the positive input used for the current sense resistor. This pin is used to indicate a fault condition, it is an open drain type configuration that will be pulled low when a fault occurs; connect a 100 kΩ resistor between this pin and the required logic level voltage. No connect. Frequency/synchronization pin; connect a resistor RFSET from this pin to GND to set the switching frequency. This pin can also be used to synchronize two or more converters in the system; the maximum synchronization frequency is 2.3 MHz. Connect the RISET resistor between this pin and GND to set the LED 100% current level. Connect the cathode of each LED string to these pins. 19 VDD 20, 21 PGND Output of internal LDO; connect a 0.1 μF decoupling capacitor between this pin and GND. 22 OVP This pin is used to sense an overvoltage condition; connect the ROVP resistor from VOUT to this pin to adjust the Overvoltage Protection (OVP) function. 23, 24 SW The drain of the internal NMOS switch of the boost converter. 25 VGATE Power ground for internal NMOS device. Gate driver pin for external P-MOSFET disconnect switch. 26 VSENSE Connect this pin to the negative sense side of the current sense resistor RSC; the threshold voltage is measured as VIN – VSENSE. – PAD Exposed pad of the package providing enhanced thermal dissipation; this pad must be connected to the ground plane(s) of the PCB with at least 8 thermal vias, directly in the pad. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 4 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 ELECTRICAL CHARACTERISTICS1 Valid at VIN = 16 V, TA = 25°C, indicates specifications guaranteed by design and characterization over the full operating temperature range with TA = TJ = –40°C to 105°C; unless otherwise noted Characteristics Symbol Test Conditions Min. Typ.2 Max. Unit 5 – 40 V Input Voltage Specifications Operating Input Voltage Range3 VIN UVLO Start Threshold VUVLOrise VIN rising − – 4.35 V UVLO Stop Threshold VUVLOfall VIN falling − – 3.90 V UVLO Hysteresis4 VUVLOhys – 450 – mV EN/PWM = VIH ; SW = 2 MHz, no load − 5.5 − mA VIN = 16 V, EN/PWM = SYNC = 0 V − 2 10.0 μA VIL VIN throughout operating input voltage range – – 400 mV Input Logic Level-High VIH VIN throughout operating input voltage range 1.5 – – V EN/PWM Pin Pin Pull-Down Resistor REN EN/PWM = 5 V – 100 – kΩ APWM = VIH – 100 – kΩ fAPWM 20 − 1000 kHz AVOL − 48 − dB Input Currents Input Quiescent Current Input Sleep Supply Current IQ IQSLEEP Input Logic Levels (EN/PWM, APWM) Input Logic Level-Low APWM Pin Pull-Down Resistor RAPWM APWM APWM Frequency Error Amplifier Open Loop Voltage Gain ΔICOMP = ±10 μA − 990 − μA/V Source Current IEA(SRC) VCOMP = 1.5 V − –350 − μA Sink Current IEA(SINK) VCOMP = 1.5 V − 350 − μA COMP Pin Pull-Down Resistor RCOMP − 2000 − Ω Transconductance gm Overvoltage Protection Overvoltage Threshold OVP Sense Current VOVP(th) OVP connected to VOUT 7.7 8.1 8.5 V 188 199 210 μA − 0.1 1 μA − 55 − V ISW = 0.750 A, VIN = 16 V − 300 − mΩ VSW = 16 V, EN/PWM = VIL − 0.1 1 μA 3.0 3.5 4.2 A IOVPH OVP Leakage Current IOVPLKG Secondary Overvoltage Protection VOVP(sec) ROVP = 40.2 kΩ, VIN = 16 V, EN/PWM = VIL Boost Switch Switch On-Resistance RSW Switch Leakage Current ISWLKG Switch Current Limit ISW(LIM) Secondary Switch Current Limit4 ISW(LIM2) Higher than ISW(LIM)(max) for all conditions, device latches when detected − 7.0 − A Soft Start Boost Current Limit ISWSS(LIM) Initial soft start current for boost switch − 700 − mA Minimum Switch On-Time tSWONTIME − 85 − ns Minimum Switch Off-Time tSWOFFTIME − 47 − ns Continued on the next page… Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 5 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 ELECTRICAL CHARACTERISTICS1 (continued) Valid at VIN = 16 V, TA = 25°C, indicates specifications guaranteed by design and characterization over the full operating temperature range with TA = TJ = –40°C to 105°C; unless otherwise noted Min. Typ.2 Max. Unit RFSET = 10 kΩ 1.8 2 2.2 MHz fSW RFSET = 20 kΩ − 1 − MHz RFSET = 35.6 kΩ − 580 − kHz FSET/SYNC Pin Voltage VFSET RFSET = 10 kΩ − 1.00 − V FSET Frequency Range fFSET 580 − 2500 kHz Characteristics Symbol Test Conditions Oscillator Frequency Oscillator Frequency Synchronization Synchronized PWM Frequency fSWSYNC 580 − 2300 kHz Synchronization Input Minimum Off-Time tPWSYNCOFF 150 − − ns Synchronization Input Minimum On-Time tPWSYNCON 150 − − ns SYNC Input Logic Voltage VSYNC(H) FSET/SYNC pin, high level − − 0.4 V VSYNC(L) FSET/SYNC pin, low level 2.0 − − V LED Current Sinks LEDx Accuracy ErrLED ISET = 120 μA − − 3 % LEDx Matching ΔLEDx ISET = 120 μA − − 3 % − 680 − mV LEDx Regulation Voltage VLED VLED1 through VLED8 all equal, ISET = 120 μA ISET to ILEDx Current Gain AISET ISET = 120 μA 317 327 337 A/A ISET Pin Voltage VISET − 1.003 − V Allowable ISET Current ISET 40 − 120 μA 4.6 − − V VLED Short Detect VLEDSC While LED sinks are in regulation, sensed from LEDx pin to GND Soft Start LEDx Current ILEDSS Current through each enabled LEDx pin during soft start, ISET = 120 μA − 1.06 − mA Maximum PWM Dimming Until Off-Time3 tPWML Measured while EN/PWM = low, during dimming control and internal references are powered-on (exceeding tPWML results in shutdown) − 32750 − fSW cycles Minimum EN/PWM On-Time tPWMH First cycle when powering-up device − 0.75 2 μs EN/PWM High to LED-On Delay tdPWM(on) Time between EN/PWM enable and LEDx current reaching 90% of maximum − 0.5 1 μs EN/PWM Low to LED-Off Delay tdPWM(off) Time between EN/PWM enable going low and LEDx current reaching 10% of maximum − − 500 ns VGS = VIN − −104 − μA − − 3 μs − –6.7 − V VGATE Pin VGATE Pin Sink Current IGSINK VGATE Pin Fault Shutdown tGFAULT VGATE Pin Voltage VGS Gate to source voltage measured when gate is on Continued on the next page… Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 6 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 ELECTRICAL CHARACTERISTICS1 (continued) Valid at VIN = 16 V, TA = 25°C, indicates specifications guaranteed by design and characterization over the full operating temperature range with TA = TJ = –40°C to 105°C; unless otherwise noted Characteristics Min. Typ.2 Max. Unit 18.8 20.3 21.8 μA Measured between VIN and VSENSE, RADJ = 0 Ω − 180 − mV IFAULT = 1 mA (400 Ω) − − 0.5 V VFAULT = 5 V − − 1 μA − 165 − ºC − 20 − ºC Symbol Test Conditions VSENSE Pin VSENSE Pin Sink Current VSENSE Trip Point IADJ VSENSEtrip ¯Ā¯Ū¯L̄ ¯T̄ ¯ Pin F̄ ¯ĀŪ¯L̄¯T̄ ¯ Pin Pull-Down Voltage F̄ ¯ĀŪ¯L̄¯T̄ ¯ Pin Leakage Current F̄ VFAULT IFAULTLKG Thermal Protection (TSD) Thermal Shutdown Threshold4 TSD Thermal Shutdown Hysteresis4 TSDHYS Temperature rising 1For input and output current specifications, negative current is defined as coming out of the node or pin (sourcing); positive current is defined as going into the node or pin (sinking). 2Typical specifications are at T = 25ºC. A 3Minimum V = 5 V is only required at startup. After startup is completed, the IC is able to function down to V = 4 V. IN IN 4Ensured by design and characterization, not production tested. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 7 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Typical Characteristic Performance VIN Input Sleep Mode Current versus Ambient Temperature VIN UVLO Rising Threshold Voltage versus Ambient Temperature VUVLOrise (V) IQSLEEP (μA) 5 4 3 2 1 0 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 4.40 4.35 4.30 4.25 4.20 4.15 4.10 4.05 4.00 -50 -40 -30 -20 -10 0 Temperature (°C) Temperature (°C) VIN UVLO Falling Threshold Voltage versus Ambient Temperature VUVLOfall (V) fSW (MHz) Switching Frequency versus Ambient Temperature 2.20 2.15 2.10 2.05 2.00 1.95 1.90 1.85 1.80 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 3.70 3.69 3.68 3.67 3.66 3.65 3.64 3.63 3.62 3.61 3.60 -50 -40 -30 -20 -10 0 Temperature (°C) OVP Pin Overvoltage Threshold versus Ambient Temperature 8.4 8.3 VOVP(th) (V) IOVPH (μA) 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) OVP Pin Sense Current versus Ambient Temperature 210 208 206 204 202 200 198 196 194 192 190 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 8.2 8.1 8.0 7.9 7.8 7.7 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) 7.6 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 8 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Input Disconnect Switch Gate to Source Voltage 330 329 328 327 326 325 324 323 322 321 320 -50 -40 -30 -20 -10 0 versus Ambient Temperature -6.3 -6.4 VGS (V) AISET ISET to LED Current Gain versus Ambient Temperature -6.5 -6.6 -6.7 -6.8 -6.9 10 20 30 40 50 60 70 80 90 100 110 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) Temperature (°C) LEDx Current versus Ambient Temperature ISET = 120 μA VSENSE Pin Sink Current versus Ambient Temperature LED Current, ILEDx (mA) 20.8 20.7 IADJ (μA) 20.6 20.5 20.4 20.3 20.2 20.1 -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) LED to LED Matching Accuracy versus Ambient Temperature LED Set Point Accuracy versus Ambient Temperature LEDx Accuracy, ErrLED (%) -50 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 10.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0 -50 -40 -30 -20 -10 0 Temperature (°C) Efficiency, η (%) 88 fSW 800 kHz 1 MHz 84 7 9 11 13 15 17 Input Voltage, VIN (V) 90 85 fSW 800 kHz 1 MHz 75 92 80 Efficiency for 12 Series LEDs per Channel ILED = 40 mA, LED Vf ≈ 3.2 V 95 90 86 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) Efficiency for 10 Series LEDs per Channel ILED = 40 mA, LED Vf ≈ 3.2 V 92 10 20 30 40 50 60 70 80 90 100 110 Temperature (°C) 10.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0 Efficiency, η (%) ΔLEDx (%) 20.0 40.0 39.8 39.6 39.4 39.2 39.0 38.8 38.6 38.4 38.2 38.0 -50 -40 -30 -20 -10 0 19 21 70 7 9 11 13 15 17 19 21 Input Voltage, VIN (V) Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 9 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Functional Description The A8510 incorporates a current-mode boost controller with internal DMOS switch, and eight LED current sinks. It can be used to drive eight LED strings of up to 12 white LEDs in series, with current up to 40 mA per string. For optimal efficiency, the output of the boost stage is adaptively adjusted to the minimum voltage required to power all of the LED strings. This is expressed by the following equation: VOUT = max ( VLED1 ,..., VLED8 ) + VREG (1) where VLEDx is the voltage drop across LED strings 1 through 8, and VREG is the regulation voltage of the LED current sinks (typically 0.68 V at the maximum LED current). Enabling the IC The IC turns on when a logic high signal is applied on the EN/PWM pin with a minimum duration of tPWMH for the first clock cycle, and the input voltage present on the VIN pin is greater than the 4.35 V necessary to clear the UVLO (VUVLOrise ) threshold. The power-up sequence is shown in figure 2. Before the LEDs are enabled, the A8510 driver goes through a system check to determine if there are any possible fault conditions that might prevent the system from functioning correctly. Also, if the FSET/SYNC pin is pulled low, the IC will not power-up. More information on the FSET/SYNC pin can be found below, in the Synchronization section of this document. Powering up: LED pin short-to-GND check The VIN pin has a UVLO function that prevents the A8510 from powering-up until the UVLO threshold is reached. After the VIN pin goes above UVLO, and a high signal is present on the EN/ PWM pin, the IC proceeds to power-up. As shown in figure 3, at this point the A8510 enables the disconnect switch and checks if any LED pins are shorted to GND and/or are not used. The LED detect phase starts when the VGATE voltage of the disconnect switch is equal to VIN – 4.5 V. After the voltage threshold on the LEDx pins exceeds 120 mV, a timer of 3000 to 4000 clock cycles is used to determine the status of the pins. Thus, the LED detection duration varies with the switching frequency, as shown in the following table: Switching Frequency (kHz) Detection Time (ms) 2000 1.5 to 2 1000 3 to 4 800 3.75 to 5 600 5 to 6.7 The LED pin detection voltage thresholds are as follows: LED Pin Voltage LED Pin Status Action <70 mV Short-to-GND Power-up is halted 150 mV Not used LED removed from operation >325 mV LED pin in use None VGATE = VIN – 4.5 V VDD VGATE C1 FSET/SYNC C1 LEDx LED detection period C2 C2 ISET C3 ISET EN/PWM C3 C4 C4 EN/PWM t Figure 2. Power-up diagram at fSW = 2 MHz; shows VDD (ch1, 2 V/div.), FSET/SYNC (ch2, 1 V/div.), ISET (ch3, 1 V/div.), and EN/PWM (ch4, 2 V/ div.) pins, t = 200 μs/div. t Figure 3. Power-up diagram; shows the relationship of an LEDx pin with respect to the gate voltage of the disconnect switch (if used) during the LED detect phase, as well as the duration of the LED detect phase for a switching frequency of 800 kHz; shows VGATE (ch1, 5 V/div.), LEDx (ch2, 500 mV/div.), ISET (ch3, 1 V/div.), and EN/PWM (ch4, 5 V/div.) pins, t = 1 ms/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 10 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 All unused pins should be connected with a 4.75 kΩ resistor to GND, as shown in figure 5. The unused pin, with the pull-down resistor, will be taken out of regulation at this point and will not contribute to the boost regulation loop. A8510 A8510 If an LEDx pin is shorted to ground the A8510 will not proceed with soft start until the short is removed from the LEDx pin. This prevents the A8510 from powering-up and putting an uncontrolled amount of current through the LEDs. The various detect scenarios are presented in figures 4A and 4B. LED1 LED1 LED2 LED2 LED3 LED3 LED4 LED4 LED5 LED5 LED6 LED6 LED7 GND LED7 LED8 GND LED8 4.75 kΩ Figure 5. Channel select setup: (left) channel LED8 not used, (right) using all channels. LED1-7 LED detection period C1 C2 LED8 C3 ISET EN/PWM C4 t 4A. Example with LED8 pin not being used; fSW is 2 MHz, the detect voltage is about 150 mV; shows LED1-7 (ch1, 500 mV/div.), LED8 (ch2, 500 mV/div.), ISET (ch3, 1 V/div.), and EN/PWM (ch4, 5 V/div.) pins, t = 500 μs/div. Short removed Pin shorted LED1 C1 LED2 C2 ISET C3 C4 EN/PWM t 4B. Example with one LED shorted to GND. The IC will not proceed with powerup until the shorted LED pin is released, at which point the LED is checked to see if it is being used; shows LED1 (ch1, 500 mV/div.), LED2 (ch2, 500 mV/div.), ISET (ch3, 1 V/div.), and EN/PWM (ch4, 5 V/div.) pins, t = 1 ms/div. . Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 11 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Inrush current caused by enabling the disconnect switch (when used) Soft start function During soft start the LEDx pins are set to sink (ILEDSS) and the boost switch current is reduced to the ISWSS(LIM) level to limit the inrush current generated by charging the output capacitors. When the converter senses that there is enough voltage on the LEDx pins, the converter proceeds to increase the LED current to the preset regulation current and the boost switch current limit is switched to the ISW(LIM) level to allow the A8510 to deliver the necessary output power to the LEDs. This is shown in figure 7. Frequency selection The switching frequency on the boost regulator is set by the resistor connected to the FSET/SYNC pin, and the switching frequency can be can be anywhere from 580 kHz to 2.3 MHz. Figure 6 shows the typical switching frequencies for given resistor values. If during operation a fault occurs that will increase the switching frequency, the FSET/SYNC pin is clamped to a maximum switching frequency of no more than 3.5 MHz. Synchronization The A8510 can also be synchronized using an external clock on the FSET/SYNC pin. Figure 8 shows the correspondence of a SYNC signal and the SW pin, and figure 9 shows the result when a SYNC signal is detected: the LED current does not show any variation while the frequency synchronization occurs. At powerup if the FSET/SYNC pin is held low, the IC will not power-up. Only when the FSET/SYNC pin is tri-stated to allow for the pin to rise, to about 1 V, or when a sync clock is detected, will the A8510 try to power-up. Normal operation ISW(lim) C1 IOUT IIN Operation during ISWSS(lim) C2 VOUT C3 C4 EN/PWM t Figure 7. Startup diagram showing the input current, output voltage, and output current, fSW = 800 kHz; shows IOUT (ch1, 500 mA/div.), IIN (ch2, 1 A/ div.), VOUT (ch3, 20 V/div.), and EN/PWM (ch4, 5 V/div.), t = 1 ms/div. VOUT C1 ILED C2 C3 FSET/SYNC SW node C4 t Figure 8. Diagram showing a synchronized FSET/SYNC pin and switch node; shows VOUT (ch1, 20 V/div.), ILED (ch2, 200 mA/div.), FSET/SYNC (ch3, 2 V/div.), and SW node (ch4, 20 V/div.), t = 2 μs/div. fSW (MHz) VOUT 2.1 1.9 1.7 1.5 1.3 1.1 0.9 0.7 0.5 IOUT C1 FSET/SYNC C2 C3 800 kHz operation 10.0 12.5 15.0 17.5 20.0 22.5 25.0 30.0 32.5 SW node 1.5 MHz operation 35.0 Resistance for RSET (kΩ) C4 t Figure 6. Typical Switching Frequency versus value of RFSET resistor. Figure 9. Transition of the SW waveform when the SYNC pulse is detected. The A8510 switching at 800 kHz, applied SYNC pulse at 1.5 MHz; shows VOUT (ch1, 20 V/div.), IOUT (ch2, 500 mA/div.), FSET/ SYNC (ch3, 2 V/div.), and SW node (ch4, 20 V/div.), t = 2 μs/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 12 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 The basic requirement of the SYNC signal is 150 ns minimum on-time and 150 ns minimum off time, as indicated by the specifications for tPWSYNCON and tPWSYNCOFF . Figure 10 shows the timing for a synchronization clock into the A8510 at 800 kHz. Thus any pulse with a duty cycle of 12% to 88% at 800 kHz can be used to synchronize the IC. LED current setting and LED dimming The maximum LED current can be up to 40 mA per channel, and is set through the ISET pin. To set the ILED current, connect a resistor, RISET, between this pin and GND, according to the following formula: (2) RISET = (1.003 × 327) / ILED The SYNC pulse duty cycle ranges for selected switching frequencies are: where ILED is in mA and RISET is in Ω. This sets the maximum current through the LEDs, referred to as the 100% current. Standard RISET values, at gain equals 327, are as follows: SYNC Pulse Frequency (kHz) Duty Cycle Range (%) 2200 33 to 66 2000 30 to 70 1000 15 to 85 10.5 30 800 12 to 88 13.0 25 600 9 to 91 16.2 20 If during operation a SYNC clock is lost, the IC will revert to the preset switching frequency that is set by the resistor RFSET. During this period the IC will stop switching for a maximum period of about 7 μs to allow the sync detection circuitry to switch over to the externally preset switching frequency. If the clock is held low for more than 7 μs, the A8510 will shut down. In this shutdown mode the IC will stop switching, the input disconnect switch is open, and the LEDs will stop sinking current. To shutdown the IC into low power mode, the IC must be disabled by keeping the EN/PWM pin low for a period of 32750 clock cycles. If the FSET/SYNC pin is released at any time after 7 μs, the A8510 will proceed to soft start. t PWSYNCON LED current per LED, ILED (mA) 8.25 40 PWM dimming The LED current can be reduced from the 100% current level by PWM dimming using the EN/PWM pin. When the EN/PWM pin is pulled high, the A8510 turns on and all enabled LEDs sink 100% current. When EN/PWM is pulled low, the boost converter and LED sinks are turned off. The compensation (COMP) pin is floated, and critical internal circuits are kept active. The typical PWM dimming frequencies fall between 200 Hz and 1 kHz. Figures 12A to 12D provide examples of PWM switching behavior. Another important feature of the A8510 is the PWM signal to LED current delay. This delay is typically less than 500 ns, which allows greater accuracy at low PWM dimming duty cycles, as shown in figure 11. 10 950 ns 8 ErrLED (%) 150 ns Standard Resistor Value Closest to RISET (kΩ) Worst-case 6 Typical 4 2 150 ns T = 1.25 μs t PWSYNCOFF Figure 10. SYNC pulse on and off time requirements, for an 800-kHz clock. 0 0.1 1 10 100 PWM Duty Cycle, D (%) Figure 11. Percentage Error of the LED current versus PWM duty cycle (at 200 Hz PWM frequency), for 500 ns delay. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 13 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 VOUT VOUT ILED C2 C2 C1 C1 C3 C4 ILED C3 COMP COMP C4 EN/PWM EN/PWM t t Figure 12A. Typical PWM diagram showing VOUT, ILED, and COMP pin as well as the PWM signal. PWM dimming frequency is 200 Hz at 50% duty cycle; shows VOUT (ch1, 10 V/div.), ILED (ch2, 50 mA/div.), COMP (ch3, 2 V/div.), EN/PWM (ch4, 5 V/div.), t = 1 ms/div. Figure 12B. Typical PWM diagram showing VOUT, ILED, and COMP pin as well as the PWM signal. PWM dimming frequency is 200 Hz at 1% duty cycle ; shows VOUT (ch1, 10 V/div.), ILED (ch2, 50 mA/div.), COMP (ch3, 2 V/div.), EN/PWM (ch4, 5 V/div.), t = 2 ms/div. EN/PWM EN/PWM C1 C1 ILED ILED C2 C2 t Figure 12C. Delay from rising edge of PWM signal to LED current; shows EN/PWM (ch1, 2 V/div.), and ILED (ch2, 20 mA/div.), t = 200 ns/div. t Figure 12D. Delay from falling edge of PWM signal to LED current turn off; shows EN/PWM (ch1, 2 V/div.), and ILED (ch2, 50 mA/div.), t = 200 ns/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 14 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 APWM pin The APWM pin is used in conjunction with the ISET pin. This is a digital signal pin that internally adjusts the ISET current. The typical input signal frequency is between 20 kHz and 1 MHz. The duty cycle of this signal is inversely proportional to the percentage of current that is delivered to the LEDs (figure 14). As an example, a system that delivers a full LED current of 40 mA per LED would deliver 20 mA of current per LED when an APWM signal is applied with a duty cycle of 50%. When this pin is not used it should be tied to GND. APWM A8510 ISET APWM ISET Current Adjust ISET Current Mirror RISET EN/PWM LED Driver Figure 13. Simplified block diagram of the APWM ISET block. To use this pin for a trim function, the user should set the maximum output current to a value higher than the required current by at least 5%. The LED ISET current is then trimmed down to the 25 20 5V ErrLED (%) 40 ILED (mA) 30 15 1.5 V 200 kHz 1.5 V 50 kHz 10 20 5V 50 kHz 5 10 0 200 kHz 0 20 40 60 80 0 100 PWM Duty Cycle, D (%) Figure 14. LED current versus PWM duty cycle; 200 kHz APWM frequency. 20 40 60 80 100 PWM Duty Cycle, D (%) Figure 15. Percentage Error of the LED current versus APWM signals. EN/PWM EN/PWM C1 0 C1 APWM APWM C2 C2 ILED C3 ILED C3 t Figure 16. Diagram showing the transition of LED current from 40 mA to 20 mA, when a 50% duty cycle signal is applied to the APWM pin; EN/PWM = 1; shows EN/PWM (ch1, 5 V/div.), APWM (ch2, 5 V/div.), and ILED (ch3, 20 mA/div.), t = 1 ms/div. t Figure 17. Diagram showing the transition of LED current from 20 mA to 40 mA, when a 50% duty cycle signal is removed from the APWM pin. EN/PWM = 1; shows EN/PWM (ch1, 5 V/div.), APWM (ch2, 5 V/div.), and ILED (ch3, 20 mA/div.), t = 1 ms/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 15 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 appropriate value. In cases where the user-supplied APWM has significant duty cycle limitations, it might be preferable to set the maximum ISET current to be 25% to 50% higher, thus allowing the APWM signal to have duty cycles that are between 50% and 75%. is controlled by the following formula: VISET – VDAC ISET = RISET – VDAC Although the APWM dimming function has a wide frequency range, if this function is used strictly as an analog dimming function it is recommended to use frequency ranges between 50 and 500 kHz for best accuracy. The frequency range must be considered only if the user is not using this function as a closed loop trim function. There is a few millisecond propagation delay between the APWM signal and ILED current. This effect is shown in figures 16 through 18. When the DAC voltage is equal to VISET , the internal reference, there is no current through RISET . When the DAC voltage starts to decrease, the ISET current starts to increase, thus increasing the LED current. When the DAC voltage is 0 V, the LED current will be at its maximum. Analog dimming The A8510 can also be dimmed by using an external DAC or another voltage source applied either directly to the ground side of the RISET resistor or through an external resistor to the ISET pin (see figure 19). • For a single resistor (upper panel of figure 19), the ISET current Where VISET is the ISET pin voltage and VDAC is the DAC output voltage. • For a dual-resistor configuration (lower panel of figure 19), the ISET current is controlled by the following formula: VISET VDAC – VISET – ISET = (4) RISET R1 The advantage of this circuit is that the DAC voltage can be higher or lower, thus adjusting the LED current to a higher or lower value of the preset LED current set by the RISET resistor: ▫ VDAC = 1.003 V; the output is strictly controlled by RISET ▫ VDAC > 1.003 V; the LED current is reduced ▫ VDAC < 1.003 V; the LED current is increased DAC EN/PWM (3) R ISET VDAC A8510 ISET GND GND C1 APWM C2 DAC IOUT R1 VDAC GND A8510 ISET R ISET GND C3 t Figure 18. Transition of output current level when a 50% duty cycle signal is applied to the APWM pin, in conjunction with a 50% duty cycle PWM dimming being applied to the EN/PWM pin; shows EN/PWM (ch1, 5 V/ div.), APWM (ch2, 5 V/div.), and ILED (ch3, 20 mA/div.), t = 1 ms/div. Figure 19. Simplified diagrams of voltage control of ILED: typical applications using a DAC to control ILED using a single resistor (upper), and dual resistors (lower). Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 16 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 LED short detect All of the LEDx pins are capable of handling the maximum VOUT that the converter can deliver, thus providing protection from the LED pin to VOUT in the event of a connector short. Any LEDx pin that has a voltage exceeding VLEDSC will be removed from operation (see figure 20). This is to prevent the IC from dissipating too much power by having a large voltage present on the LEDx pin. While the IC is being PWM-dimmed, the IC rechecks the disabled LEDx pin every time the PWM signal goes high, to prevent false tripping of an LEDx short event. This also allows some selfcorrection if an intermittent LEDx pin short-to-VOUT is present. Overvoltage protection The A8510 has overvoltage protection (OVP) and open Schottky diode (D1) protection. The OVP protection has a default level of 8 V and can be increased up to 55 V by connecting ROVP between the OVP pin and VOUT . When the current into the OVP pin exceeds 199 μA typical, the OVP comparator goes low and the boost stops switching. The following equation can be used to determine the resistance for setting the OVP level: where: ROVP = ( VOUTovp – VOVP(th) ) / IOVPH (4) VOUTovp is the target overvoltage level, ROVP is the value of the external resistor, in Ω, VOVP(th) is the pin OVP trip point found in the Electrical Characteristics table, and IOVPH is the current into the OVP pin. There are several possibilities for why an OVP condition would be encountered during operation, the two most common being: an open LED string, and a disconnected output. Examples of these are provided in figures 21 and 22. Figure 21 illustrates when the output of the A8510 is disconnected from load during normal operation. The output voltage instantly increases up to OVP voltage level and then the boost stops switching to prevent damage to the IC. If the output is drained off, eventually the boost might start switching for a short duration until the OVP threshold is hit again. VLED C1 EN/PWM C2 C3 ILED t Figure 20. Example of the disabling of an LED string when the LED pin voltage is increased above 4.6 V; shows VLED (ch1, 5 V/div.), EN/PWM (ch2, 5 V/div.), and ILED (ch3, 50 mA/div.), t = 20 μs/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 17 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Figure 22 displays a typical OVP event caused by an open LED string. After the OVP condition is detected, the boost stops switching, and the open LED string is removed from operation. Afterwards VOUT is allowed to fall, and eventually the boost will resume switching and the A8510 will resume normal operation. A8510 also has built-in secondary overvoltage protection to protect the internal switch in the event of an open diode condition. Open Schottky diode (D1) detection is implemented by detecting overvoltage on the SW pins of the device. If voltage on the SW pins exceeds the device safe operating voltage rating, the A8510 disables and remains latched. To clear this fault, the IC must be Output disconnect event detected shut down either by using the PWM signal or by going below the UVLO threshold on the VIN pin. Figure 23 illustrates this. As soon as the switch node voltage (SW) exceeds VOVP(sec), the IC shuts down. Due to small delays in the detection circuit, as well as there being no load present, the switch node voltage will rise above the trip point voltage. Figure 24 illustrates when the A8510 is being enabled during an open diode condition. The IC goes through all of its initial LED detection and then tries to enable the boost, at which point the open diode is detected. LED string open condition detected VOUT VOUT SW node SW node C2 C2 EN/PWM C1 C3 C1 C3 ILED C4 EN/PWM ILED C4 t t Figure 21. OVP protection in an output disconnect from load event; shows VOUT (ch1, 10 V/div.), SW node (ch2, 20 V/div.), EN/PWM (ch3, 5 V/div.), and ILED (ch4, 50 mA/div.), t = 2 ms/div. Figure 22. OVP protection in an open LED string event; shows VOUT (ch1, 10 V/div.), SW node (ch2, 20 V/div.), EN/PWM (ch3, 5 V/div.), and ILED (ch4, 200 mA/div.), t = 1 ms/div. Open diode condition detected EN/PWM SW node C1 SW node C1 C2 IOUT Open diode condition detected C2 VOUT FAULT C3 C3 EN/PWM ILED C4 C4 t Figure 23. OVP protection in an open Schottky diode D1 event, while the IC is in normal operation; shows SW node (ch1, 50 V/div.), IOUT (ch2, 500 ¯ĀŪ¯L̄¯T̄ ¯ (ch3, 5 V/div.), and EN/PWM (ch4, 5 V/div.), t = 2 μs/div. mA/div.), F̄ t Figure 24. OVP protection when the IC is enabled during an open diode condition; shows EN/PWM (ch1, 5 V/div.), SW node (ch2, 50 V/div.), VOUT (ch3, 10 V/div.), and ILED (ch4, 200 mA/div.), t = 500 μs/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 18 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Boost switch overcurrent protection in figures 25 through 27. The boost switch is protected with cycle-by-cycle current limiting set at a minimum of 3.0 A. There is also a secondary current limit that is sensed on the boost switch. When detected this current limit immediately shuts down the A8510. The level of this current limit is set above the cycle-by-cycle current limit to protect the switch from destructive currents when the boost inductor is shorted. Various boost switch overcurrent conditions are shown Input overcurrent protection and disconnect switch The primary function of the input disconnect switch is to protect the system and the device from catastrophic input currents during a fault condition. The external circuit implementing the disconnect is shown in figure 28. If the input disconnect switch is not used, the VSENSE pin must be tied to VIN and the VGATE pin must be left open. IL IL SW node C1 C1 C2 SW node C2 VOUT VOUT EN/PWM C3 EN/PWM C3 C3 C4 t t Figure 25. Normal operation of the switch node (SW); inductor current (IL) and output voltage (VOUT) for 12 series LEDs in each of 8 strings configuration; shows IL (ch1, 500 mA/div.), SW node (ch2, 20 V/div.), VOUT (ch3, 20 V/div.), and EN/PWM (ch4, 5 V/div.), t = 1 μs/div. Figure 26. Cycle-by-cycle current limiting; inductor current (IL), note reduction in output voltage as compared to normal operation with the same configuration (figure 25); shows IL (ch1, 1 A/div.), SW node (ch2, 20 V/div.), VOUT (ch3, 10 V/div.), and EN/PWM (ch4, 5 V/div.), t = 2 μs/div. EN/PWM C1 FAULT C2 SW node C3 IL C4 t Figure 27. Secondary boost switch current limit; when this limit is hit, the ¯ĀŪ¯L̄¯T̄ ¯ A8510 immediately shuts down; shows EN/PWM (ch1, 5 V/div.), F̄ (ch2, 5 V/div.), SW node (ch3, 50 V/div.), and IL (ch4, 2 A/div.), t = 200 ns/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 19 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 When selecting the external PMOS, check for the following parameters: • Drain-source breakdown voltage V(BR)DSS > –40 V • Gate threshold voltage (make sure it is fully conducting at VGS = -4 V, and cut-off at –1 V) If the input current level goes above the preset current limit threshold, the A8510 will shut down in less than 3 μs regardless of user input (figure 29). This is a latched condition. The Fault flag is also set to indicate a fault. This feature is meant to prevent catastrophic failure in the system due to a short of the inductor or output voltage to GND. • RDS(on): Make sure the on-resistance is rated at VGS = -4.5 V or similar, not at -10 V; derate it for higher temperature FAULT C1 VIN RSC RADJ Q1 To L1 C2 VGATE A8510 IIN VSENSE VIN A8510 shuts down VGATE C3 C4 EN/PWM t Figure 28. Typical circuit showing the implementation of the input disconnect feature. Figure 29. Diagram showing input disconnect current limit wave forms ¯ĀŪ¯L̄¯T̄ ¯ (ch1, 5 V/div.), VGATE (ch2, during fault condition; shows F̄ 10 V/div.), IIN (ch3, 2 A/div.), and EN/PWM (ch4, 5 V/div.), t = 5 μs/div. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 20 A8510 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver Setting the current sense resistor The typical threshold for the current sense circuit is 180 mV, when RADJ is 0 Ω. This voltage can be trimmed by the RADJ resistor. The typical trip point should be set at about 3 A, which coincides with the cycle-by-cycle current limit minimum threshGiven: 2.85 A of input current, and the calculated maximum value of the sense resistor, RSC = 0.063 Ω. The RSC chosen is 0.056 Ω, a standard value. Also: (5) The typical trip point voltage is calculated as: VADJ = 2.85 A × 0.056 Ω = 0.160 V RADJ = (0.180 – 0.160 V) / (20.3 μA) = 1.0 kΩ Input UVLO When VIN and VSENSE rise above the UVLO enable hysteresis (VUVLOrise + VUVLOhys ), the A8510 is enabled. A8510 is disabled when VIN falls below the VUVLOfall threshold for more than 50 μs. This lag is to avoid shutting down because of momentary glitches in the input power supply. Shutdown If the EN/PWM pin is pulled low for more than tPWML , the device enters shutdown mode and clears all internal fault registers. As an example, at a 2-MHz clock frequency, the maximum PWM low period, while avoiding shutdown, is 16 ms. In shut down, the IC disables all current sources and waits until the EN/PWM pin goes high to re-enable the IC and proceed with power-up. old. A sample calculation is done below: RADJ = (VSENSETRIP – VADJ ) / IADJ VDD The VDD pin provides regulated bias supply for internal circuits. Connect the capacitor CVDD with a value of 0.1 μF or greater to this pin. Fault protection during operation The A8510 constantly monitors the state of the system to determine if any fault conditions occur during normal operation. The response to a triggered fault condition is summarized in the Fault Mode table, on the next page. The possible fault conditions that the device can detect are: Open LED pin, LED pin shorted to GND, shorted inductor, VOUT short to GND, SW pin shorted to GND, ISET pin shorted to GND, and input disconnect switch source shorted to GND. Note the following: • Some of the protection features might not be active during startup, to prevent false triggering of fault conditions. • Some of these faults will not be protected if the input disconnect switch is not being used. An example of this is VOUT short to ground. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 21 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Fault Mode Table Fault Name Type Active Fault Flag Set Primary switch overcurrent protection (cycle-by-cycle current limit) Auto-restart Always No This fault condition is triggered by the cycle-bycycle current limit, ISW(LIM). Secondary switch current limit Input disconnect current limit Secondary OVP LEDx pin short protection LEDx pin open ISET short protection Latched Latched Latched Auto-restart Auto-restart Auto-restart Always Always Always Startup Normal Operation Always Boost Disconnect switch Sink driver Off for a single cycle On On Yes When the current through the boost switch exceeds secondary current SW limit (ISW(LIM2)) the device immediately shuts down the disconnect switch, LED drivers, and boost. The Fault flag is set. To reenable the device, the EN/PWM pin must be pulled low for 32750 clock cycles. Off Off Off Yes The device is immediately shut off if the voltage across the input sense resistor is above the VSENSEtrip threshold. The Fault flag is set. To reenable the part the EN/PWM pin must be pulled low for 32750 clock cycles. Off Off Off Yes Secondary overvoltage protection is used for open diode detection. When diode D1 opens, the SW pin voltage will increase until VOVP(SEC) is reached. This fault latches the IC. The input disconnect switch is disabled as well as the LED drivers, and the Fault flag is set. To re-enable the part the EN/PWM pin must be pulled low for 32750 clock cycles. Off Off Off No This fault prevents the device from starting-up if any of the LEDx pins are shorted. The device stops soft-start from starting while any of the LED pins are determined to be shorted. Once the short is removed, soft-start is allowed to start. Off On Off No When an LEDx pin is open the device will determine which LEDx pin is open by increasing the output voltage until OVP is reached. Any LED string not in regulation will be turned off. The device will then go back to normal operation by reducing the output voltage to the appropriate voltage level. On On Off for open pins. On for all others. No This fault occurs when the ISET current goes above 150% of the maximum current. The boost will stop switching and the IC will disable the LED sinks until the fault is removed. When the fault is removed the IC will try to regulate to the preset LED current. Off On Off Description Continued on the next page… Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 22 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Fault Mode Table (continued) Fault Name FSET/SYNC short protection Overvoltage protection Type Auto-restart Auto-restart Active Always Always Fault Flag Set Description Boost Disconnect Switch Sink driver Yes Fault occurs when the FSET/SYNC current goes above 150% of maximum current. The boost will stop switching, the disconnect switch will turn off and the IC will disable the LEDx sinks until the fault is removed. When the fault is removed the IC will try to restart with soft-start. Off Off Off No Fault occurs when OVP pin exceeds VOVP(th) threshold. The A8510 will immediately stop switching to try to reduce the output voltage. If the output voltage decreases then the A8510 will restart switching to regulate the output voltage. Stop during OVP event. On On On On Off for shorted pins. On for all others. LED short protection Auto-restart Always No Fault occurs when the LEDx pin voltage exceeds 5.1 V. When the LED short protection is detected the LED string above the threshold will be removed from operation. Overtemperature protection Auto-restart Always No Fault occurs when the die temperature exceeds the overtemperature threshold, typically 165°C. Off Off Off VIN UVLO Auto-restart Always No Fault occurs when VIN drops below VUVLO , typically 3.90 V. This fault resets all latched faults. Off Off Off Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 23 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Applications Information Then the OVP resistor is: Design Example for Boost Configuration This section provides a method for selecting component values when designing an application using the A8510. An example schematic is provided in figure 30. Assumptions: For the purposes of this example, the following are given as the application requirements: where both I OVPH and VOVP(th) are taken from the Electrical Characteristics table. Step 3b At this point a quick check must be done to see if the conversion ratio is acceptable for the selected frequency. Step 1 Connect LEDs to pins LED1 through LED8. Dmaxofboost = 1 – tSWOFFTIME × fSW (9) = 1 – 1.5 × 47 ns × 800 kHz = 94.36% where minimum off time (tSWOFFTIME) is found in the Electrical Characteristics table. The Theoretical Maximum VOUT is then calculated as: Step 2 Determining the LED current setting resistor RISET: (6) = 327.981 / 40 mA = 8.20 kΩ Choose a 8.25 kΩ resistor. VOUTthe(max) = VIN(min) 1 – Dmaxofboost – Vd (10) 10 V – 0.4 = 177 V 1 – 0.9436 where Vd is the diode forward voltage. = Step 3 Determining the OVP resistor. The OVP resistor is connected between the OVP pin and the output voltage of the converter. Step 3a The first step is determining the maximum voltage based on the LED requirements. Then this value and the regulation voltage (VLED) should be added together, as well as another 750 mV to take noise and output ripple into consideration. The regulation voltage, VLED , of the A8510 is 680 mV. = 12 × 3.2 V+ 0.680 V + 2 V = 41.08 V = (41.08 V – 8.1 V) / 199 μA = 165.73 kΩ VOUT(OVP) = 169 kΩ × 199 μA + 8.1 V = 41.7 V Procedure: The procedure consists of selecting the appropriate configuration and then the individual component values, in an ordered sequence. It should be noted that in many calculations the minimum and/or maximum specification values are used to guarantee proper system operation. VOUT(OVP) = #SERIESLEDS × Vf + VLED + 2 (8) Chose a value of resistor that is higher value than the calculated ROVP . In this case a value of 169 kΩ was selected. Below is the actual value of the minimum OVP trip level with the selected resistor: • VBAT: 10 to 14 V • Quantity of LED channels, #CHANNELS : 8 • Quantity of series LEDs per channel, #SERIESLEDS : 12 • LED current per channel, ILED : 40 mA • Vf at 40 mA: 3.2 V • fSW : 800 kHz • TA(max): 65°C • PWM dimming frequency: 200 Hz, 1% Duty cycle RISET = 1.003 × 327 / ILED ROVP = (VOUT(OVP) – VOVP(th) ) / IOVPH (7) The Theoretical Maximum VOUT value must be greater than the value VOUT(OVP) . If this is not the case, the switching frequency of the boost converter must be reduced to meet the maximum duty cycle requirements. Step 4 Selecting the inductor. The inductor must be chosen such that it can handle the necessary input current. In most applications, due to stringent EMI requirements, the system must operate in continuous conduction mode throughout the whole input voltage range. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 24 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Then: Step 4a Determining the duty cycle, calculated as follows: D(max) = 1 – VIN(min) VOUT(OVP) + Vd (11) = 10 V =1– = 76.3% 41.7 V + 0.4 V The voltage drop of the diode can be approximated to be about 0.4 V. Step 4b Determining the maximum and minimum input current to the system. The minimum input current will dictate the inductor value. The maximum current rating will dictate the current rating of the inductor. First, the maximum input current, given: IOUT = #CHANNELS = 8 ILED (12) 0.040 A = 0.320 A then: IIN(max) = VOUT(OVP) IOUT VIN(min) L= (13) H VIN(min) ΔIL fSW 10 V 0.444 A 800 kHz 1.059 A > 0.222 A A good inductor value to use would be 22 μH, Lused . Step 4e This step is used to verify that there is sufficient slope compensation for the inductor chosen. The slope compensation value is determined by the following formula: 4.5 fSW Slope Compensation = = 1.8 A /μs (18) 2 10 6 Next insert the inductor value used in the design: = where η is efficiency. (14) Required Slope (min) = = A good approximation of efficiency, η , can be taken from the efficiency curves located in the diode datasheet. A value of 90% is a good starting approximation. Step 4c Determining the inductor value. To ensure that the inductor operates in continuous conduction mode, the value of the inductor must be set such that the ½ inductor ripple current is not greater than the average minimum input current. A first past assumes Iripple to be 30% of the maximum inductor current: = 1.48 A × 0.3 = 0.444 A (19) 10 V 0.763 = 0.434 A 22 μH 800 kHz ΔILused 1 10 –6 1 (1 – D(max)) (20) fSW 41.7 V 0.320 A = = 1.059 A 14 V 0.9 ΔIL = IIN(max) × 0.3 VIN(min) D(max) Lused fSW Calculate the minimum required slope: Next, calculate minimum input current, as follows: VOUT(OVP) IOUT IIN(min) = VIN(max) H 0.76 = 21.4 μH Step 4d Double-check to make sure the ½ current ripple is less than IIN(min): IIN(min) > 1/2 ΔIL (17) ΔILused = 41.7 V 0.320 A = = 1.483 A 10 V 0.9 (16) D(max) (15) 0.434 A 1 10 –6 = 1.46 A/μs 1 (1 – 0.763) 800 kHz If the minimum required slope is larger than the calculated slope compensation, the inductor value must be increased. Note: that the slope compensation value is in A/μs, and 1×10 –6 is a constant multiplier. Step 4f Determining the inductor current rating. The inductor current rating must be greater than the IIN(max) value plus the ripple current ΔIL, or about 1.7 A, calculated as follows: IL(min) = IIN(max) + 1/2 ΔILused (21) = 1.483 A + 0.217 A = 1.70 A Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 25 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Step 5 Determining the resistor value for a particular switching frequency. Use the RFSET values shown in figure 6. For example, a 25.5 kΩ resistor will result in an 800 kHz switching frequency. Step 6 Choosing the proper switching diode. The switching diode must be chosen for three characteristics when it is used in LED lighting circuitry. The most obvious two are: current rating of the diode and reverse voltage rating. The reverse voltage rating should be such that during operation condition, the voltage rating of the device is larger than the maximum output voltage. In this case it is VOUT(OVP). The peak current through the diode is calculated as: Idp = IIN(max) + 1/2 ΔILused Step 7 Choosing the output capacitors. The output capacitors must be chosen such that they can provide filtering for both the boost converter and for the PWM dimming function. The biggest factors that contribute to the size of the output capacitor are PWM dimming frequency and PWM duty cycle. Another major contributor is leakage current ( ILK ). This current is the combination of the OVP leakage current as well as the reverse current of the switching diode. In this design the PWM dimming frequency is 200 Hz and the minimum duty cycle is 1%. Typically the voltage variation on the output (VCOUT) during PWM dimming must be less than 250 mV, so that no audible hum can be heard. The capacitance can be calculated as follows: 1 – D(min) fPWM(dimming) = 200 μA Vendor Value Part number Murata 4.7 μF 50 V GRM32ER71H475KA88L Murata 2.2 μF 50 V GRM31CR71H225KA88L The rms current through the capacitor is given by: ∆ILused IIN(max) 12 1 – D(max) D(max) + ICOUTrms = IOUT (22) = 1.483 A + 0.217 A = 1.70 A The third major component in deciding the switching diode is the reverse current, IR , characteristic of the diode. This characteristic is especially important when PWM dimming is implemented. During PWM off-time the boost converter is not switching. This results in a slow bleeding off of the output voltage, due to leakage currents. IR can be a large contributor, especially at high temperatures. On the diode that was selected in this design, the current varies between 1 and 100 μA. COUT = ILK Corresponding capacitors include: (23) VCOUT 1 – 0.01 = 3.96 μF 200 Hz 0.250 V A capacitor larger than 3.96 μF should be selected due to degradation of capacitance at high voltages on the capacitor. A ceramic 4.7 μF 50 V capacitor is a good choice to fulfill this requirement. = 0.320 A (24) 0.434 A 1.48 A 12 = 0.583 A 1 – 0.763 0.763 + The output capacitor must have a current rating of at least 583 mA. The capacitors selected in this design have a combined rms current rating of 3 A. Step 8 Selecting input capacitor. The input capacitor must be selected such that it provides a good filtering of the input voltage waveform. A good rule of thumb is to set the input voltage ripple ΔVIN to be 1% of the minimum input voltage. The minimum input capacitor requirements are as follows: CIN = = ∆ILused 8 8 (25) fSW ∆VIN 0.434 A = 0.68 μF 800 kHz 0.1 V The rms current through the capacitor is given by: IINrms = IOUT × (26) ∆ILused IIN(max) (1 – D(max)) 12 0.320 A × 0.434 A 1.48 A = (1 – 0.763) 12 = 0.11 A A good ceramic input capacitor with ratings of 2.2 μF 50V or 4.7 μF 50 V will suffice for this application. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 26 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Corresponding capacitors include: The RSC chosen is 0.056 Ω, a standard value. The trip point voltage must be: Vendor Value Part number Murata 4.7 μF 50 V GRM32ER71H475KA88L Murata 2.2 μF 50 V GRM31CR71H225KA88L VADJ = 3.0 A × 0.056 Ω = 0.168 V RADJ = (VSENSEtrip – VADJ ) / IADJ = (0.180 V – 0.168 V) / 20.3 μA = 591 Ω A value of 590 Ω was chosen for this design. Step 9 Choosing the input disconnect switch components. Set the input disconnect current limit to 3 A by choosing a corresponding sense resistor. The calculated maximum value of the sense resistor is: RSC(max) = VSENSEtrip/ 3.0 A = 0.180 V / 3.0 A= 0.060 Ω VIN RSC 0.056 Ω (27) Q1 RADJ 590 Ω CIN 4.7 μF/ 50 V L1 22 μH VGATE VSENSE VIN VDD VC 100 kΩ CVDD 0.1 μF D1 2 A / 60 V SW SW A8510 PAD FAULT EN/PWM APWM ISET RISET 8.25 kΩ (28) RFSET 25.5 kΩ FSET/SYNC AGND VOUT ROVP 169 kΩ OVP LED1 LED2 LED3 LED4 LED5 LED6 LED7 LED8 COMP PGND PGND COUT 4.7 μF 50 V 12 LEDs each string CP 120 pF RZ 120 Ω CZ 0.47 μF Figure 30. The schematic diagram showing calculated values from the design example above Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 27 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Design Example for SEPIC Configuration This section provides a method for selecting component values when designing an application using the A8510 in SEPIC (Single-Ended Primary-Inductor Converter) circuit. SEPIC topology has the advantage that it can generate a positive output voltage either higher or lower than the input voltage. The resulting design is diagrammed in figure 31. Assumptions: For the purposes of this example, the following are given as the application requirements: • VBAT: 6 to 14 V ( VIN(min): 5 V and VIN(max): 16 V ) • Quantity of LED channels, #CHANNELS : 8 VOUT(OVP) = #SERIESLEDS × Vf + VLED + 2 (V) (30) = 4 × 3.3 (V) + 0.680 (V) + 2 (V) = 15.9 V Then the OVP resistor is: ROVP = (VOUT(OVP) – VOVP(th) ) / IOVPH (31) = (15.9 (V) – 8.1 (V)) / 0.199 (mA) = 39.196 kΩ where both I OVPH and VOVP(th) are taken from the Electrical Characteristics table. In this case a value of 39.2 kΩ was selected. Below is the actual value of the minimum OVP trip level with the selected resistor: • Quantity of series LEDs per channel, #SERIESLEDS : 4 • LED current per channel, ILED : 40 mA VOUT(OVP) = 39.2 (kΩ) × 0.199 (mA) + 8.1 (V) = 15.9 V • LED Vf at 60 mA: ≈ 3.3 V Step 3b At this point a quick check must be done to determine if the conversion ratio is acceptable for the selected frequency. • fSW : 800 kHz • TA(max): 65°C Dmax = 1 – tSWOFFTIME × fSW • PWM dimming frequency: 200 Hz, 1% duty cycle (32) = 1 – 1.5 × 47 (ns) × 800 (kHz) = 94.4% Procedure: The procedure consists of selecting the appropriate configuration and then the individual component values, in an ordered sequence. Step 1 Connecting LEDs to LEDx pins. If only some of the LED channels are needed, the unused LEDx pins should be pulled to ground using a 1.5 kΩ resistor. Step 2 Determining the LED current setting resistor RISET: RISET = (VISET × AISET) / ILED of the A8510 is 720 mV. A constant term, 2 V, is added to give margin to the design due to noise and output voltage ripple. where the minimum off-time (tSWOFFTIME) is found in the Electrical Characteristics table. The Theoretical Maximum VOUT is then calculated as: VOUT(max) = VIN(min) = 5 (V) (29) = (1.003 (V) × 327) / 0.40 (A) = 8.20 kΩ Choose an 8.25 kΩ 1% resistor. Dmax 1 – Dmax – Vd (33) 0.94 – 0.4 (V) = 77.9 V 1 – 0.94 where Vd is the diode forward voltage. Step 3 Determining the OVP resistor. The OVP resistor is connected between the OVP pin and the output voltage of the converter. The Theoretical Maximum VOUT value must be greater than the value VOUT(OVP) . If this is not the case, it may be necessary to reduce the frequency to allow the boost to convert the voltage ratios. Step 3a The first step is determining the maximum voltage based on the LED requirements. The regulation voltage, VLED , Step 4 Selecting the inductor. The inductor must be chosen such that it can handle the necessary input current. In most applica- Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 28 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 tions, due to stringent EMI requirements, the system must operate in continuous conduction mode throughout the whole input voltage range. Step 4a Determining the duty cycle, calculated as follows: D(max) = VOUT(OVP) + Vd VIN(min) + VOUT(OVP) + Vd (34) = 8 (39) 0.765 = 14.1 μH than IIN(min): Step 4b Determining the maximum and minimum input current to the system. The minimum input current will dictate the inductor value. The maximum current rating will dictate the current rating of the inductor. First, the maximum input current, given: ILED VIN(min) D(max) ΔIL fSW 5 (V) = 0.339 (A) 800 (kHz) L= Step 4d Double-check to make sure the ½ current ripple is less 15.9 (V) + 0.4 (V) = = 76.5% 5 (V) + 15.9 (V) + 0.4 (V) IOUT = #CHANNELS then: (35) IIN(min) > 1/2 ΔIL (40) 0.353 A > 0.170 A A good inductor value to use would be 15 μH. Step 4e Next insert the inductor value used in the design to determine the actual inductor ripple current: 40 (mA) = 0.320 A then: IIN(max) = = VOUT(OVP) IOUT VIN(min) (36) H = 15.9 (V) 0.32 (A) = 1.131 A 5 (V) 0.90 (41) 0.765 5 (V) = 0.319 A 15 (μH) 800 (kHz) current rating must be greater than the IIN(max) value plus half of Next, calculate minimum input current, as follows: VOUT(OVP) IOUT IIN(min) = VIN(max) H 15.9 (V) 16 (V) VIN(min) D(max) Lused fSW Step 4f Determining the inductor current rating. The inductor where η is efficiency. = ΔILused = the ripple current ΔIL, calculated as follows: (37) 0.32 (A) = 0.353 A 0.90 = 1.131 × 0.30 = 0.339 A (42) = 1.131 (A) + 0.160 (A) = 1.291 A Step 5 Determining the resistor value for a particular switching Step 4c Determining the inductor value. To ensure that the inductor operates in continuous conduction mode, the value of the inductor must be set such that the ½ inductor ripple current is not greater than the average minimum input current. As a first pass assume Iripple to be 30% of the maximum inductor current: ΔIL = IIN(max) × Iripple L(min) = IIN(max) + 1/2 ΔILused (38) frequency. Use the RFSET values shown in figure 6. For example, a 25.5 kΩ resistor will result in an 800 kHz switching frequency. Step 6 Choosing the proper switching diode. The switching diode must be chosen for three characteristics when it is used in LED lighting circuitry. The most obvious two are: current rating of the diode and reverse voltage rating. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 29 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 The reverse breakdown voltage rating for the output diode in a SEPIC circuit should be: VBD > VOUT(OVP)(max) + VIN(max) (43) > 15.9 (V) + 16 (V) = 31.9 V because the maximum output voltage in this case is VOUT(OVP). The peak current through the diode is calculated as: Idp = IIN(max) + 1/2 ΔILused Step 7 Choosing the output capacitors. The output capacitors must be chosen such that they can provide filtering for both the boost converter and for the PWM dimming function. The biggest factors that contribute to the size of the output capacitor are: PWM dimming frequency and PWM duty cycle. Another major contributor is leakage current, ILK . This current is the combination of the OVP leakage current as well as the reverse current of the switching diode. In this design the PWM dimming frequency is 200 Hz and the minimum duty cycle is 1%. Typically, the voltage variation on the output, VCOUT , during PWM dimming must be less than 250 mV, so that no audible hum can be heard. The capacitance can be calculated as follows: 1 – D(min) fPWM(dimming) V COUT = 200 (μA) The rms current through the capacitor is given by: ICOUTrms = IOUT (44) = 1.131 (A) + 0.160 (A) = 1.291 A The third major component in deciding the switching diode is the reverse current, IR , characteristic of the diode. This characteristic is especially important when PWM dimming is implemented. During PWM off-time the boost converter is not switching. This results in a slow bleeding off of the output voltage, due to leakage currents. IR can be a large contributor, especially at high temperatures. On the diode that was selected in this design, the current varies between 1 and 100 μA. It is often advantageous to pick a diode with a much higher breakdown voltage, just to reduce the reverse current. Therefore for this example, pick a diode rated for a VBD of 60 V, instead of just 40 V. COUT = ILK A capacitor larger than 3.96 μF should be selected due to degradation of capacitance at high voltages on the capacitor. Select a 4.7 μF capacitor for this application. (45) D(max) 1 – D(max) = 0.320 (A) (46) 0.765 = 0.577 A 1 – 0.765 The output capacitor must have a ripple current rating of at least 600 mA. The capacitor selected for this design is a 4.7 μF 50 V capacitor with a 1.5 A current rating. Step 8 Selecting input capacitor. The input capacitor must be selected such that it provides a good filtering of the input voltage waveform. A estimation rule is to set the input voltage ripple, ΔVIN , to be 1% of the minimum input voltage. The minimum input capacitor requirements are as follows: CIN = = ∆ILused 8 8 fSW ∆VIN 0.319 (A) = 1.00 μF 800 (kHz) 0.05 (V) The rms current through the capacitor is given by: ∆ILused CINrms = 12 0.319 (A) = 0.092 A = 12 (47) (48) A good ceramic input capacitor with a rating of 2.2 μF 25 V will suffice for this application. 1 – 0.01 = 3.96 μF 200 (Hz) 0.250 (V) Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 30 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 The rms current requirement of the coupling capacitor is given by: (50) ICSWrms = IIN(max) 1 – D(max) D(max) Step 9 Selecting coupling capacitor CSW. The minimum capacitance of CSW is related to the maximum voltage ripple allowed across it: CSW = IOUT DMAX fSW (49) ∆VSW 0.32 (A) 0.765 = = 0.627 μF 0.1 (V) 800 (kHz) VIN 6 to 14 V CIN 2.2 μF 25 V RSC 0.056 Ω VGATE VSENSE VIN VDD VC CVDD 0.1 μF CSW 3.3 μF / 25 V SW SW A8510 PAD FAULT EN/PWM APWM ISET RISET 8.25 kΩ FSET/SYNC RFSET 25.5 kΩ 1 – 0.765 = 0.627 A 0.765 The voltage rating of the coupling capacitor must be greater than VIN(max), or 16 V in this case. A ceramic capacitor rated for 2.2 μF 25 V will suffice for this application. L1 15 μH Q1 RADJ 590 Ω R1 100 kΩ = 1.131 (A) AGND OVP LED1 LED2 LED3 LED4 LED5 LED6 LED7 LED8 COMP PGND PGND L2 15 μH D1 2 A / 60 V ROVP 39.2 kΩ CP 120 pF VOUT COUT 4.7 μF 50 V RZ 120 Ω CZ 0.47 μF Figure 31. Typical application showing SEPIC configuration, with accurate input current sense, and VSENSE to GND protection. Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 31 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Package EC, 26-Pin QFN with Exposed Thermal Pad 0.20 4.00 ±0.15 1 2 0.40 26 26 0.95 A 1 2 C 1.10 4.00 4.00 ±0.15 1.23 Top View 2.45 4.00 27X D SEATING PLANE 0.08 C 0.20 ±0.05 C PCB Layout Reference View 0.75 ±0.05 0.40 BSC For Reference Only (reference JEDEC MO-220WGGE) Dimensions in millimeters Exact case and lead configuration at supplier discretion within limits shown A Terminal #1 mark area +0.15 0.40 –0.10 B 1.23 1.10 2 1 26 B Exposed thermal pad (reference only, terminal #1 identifier appearance at supplier discretion) C Reference land pattern layout (reference IPC7351 QFN40P400X400X80-29M) All pads a minimum of 0.20 mm from all adjacent pads; adjust as necessary to meet application process requirements and PCB layout tolerances; when mounting on a multilayer PCB, thermal vias at the exposed thermal pad land can improve thermal dissipation (reference EIA/JEDEC Standard JESD51-5) D Coplanarity includes exposed thermal pad and terminals 2.45 Bottom View Allegro MicroSystems, LLC 115 Northeast Cutoff Worcester, Massachusetts 01615-0036 U.S.A. 1.508.853.5000; www.allegromicro.com 32 Wide Input Voltage Range, High Efficiency Fault Tolerant LED Driver A8510 Revision History Revision Revision Date Rev. 2 December 15, 2011 Description of Revision Update to application examples, add VSYNC Copyright ©2010-2013, Allegro MicroSystems, LLC Allegro MicroSystems, LLC reserves the right to make, from time to time, such departures from the detail specifications as may be required to permit improvements in the performance, reliability, or manufacturability of its products. 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