A8835 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver Features and Benefits Description ▪ Eight-level, digitally-programmable current limits from 550 mA to 1.75 A ▪ Voltage sensing feedback before output diode for low leakage ▪ No external pull-down resistors needed ▪ Power with 1 Li+ or 2 Alkaline/NiMH/NiCAD batteries ▪ Low quiescent current draw (1 μA max in shutdown mode) ▪ Zero-voltage switching for lower loss ▪ Adjustable output voltage ▪ Integrated IGBT driver with trigger ▪ Charge complete indication ▪ >75% efficiency ▪ Low-profile (0.75 mm high) 3 mm × 3 mm TDFN 10-contact package The A8835 is a highly integrated IC that charges photoflash capacitors for digital and film cameras. An integrated MOSFET switch drives the transformer in a flyback topology. It also features an integrated IGBT driver that facilitates the flash discharge function and saves board space. Applications: The A8835 can be used with two Alkaline/NiMH/NiCAD or one single-cell Li+ battery connected to the transformer primary. Connect the VIN pin to a 3.0 to 5.5 V supply, which can be either the system rail or the Li+ battery, if used. ▪ Digital camera flash ▪ Film camera flash ▪ Cell phone flash ▪ Emergency strobe light Package: 10-contact TDFN with exposed thermal pad (suffix EJ) The CHARGE pin enables the A8835 and starts the charging of the output capacitor. When the designated output voltage is reached, the A8835 stops the charging until the CHARGE pin ¯ pin is an open-drain indicator of is toggled again. The D̄¯¯Ō¯¯N̄¯Ē when the designated output voltage is reached. The peak current limit can be adjusted to eight different levels between 550 mA and 1.75 A, by clocking the CHARGE pin. This allows the user to operate the flash even at low battery voltages. The A8835 is available in a very low profile (0.75 mm) 10-contact 3 mm × 3 mm TDFN package, making it ideal for space-constrained applications. It is lead (Pb) free, with 100% matte-tin leadframe plating and has an exposed pad for enhanced thermal dissipation. Approximate Scale Typical Applications VBATT 1.5 to 5.5 V N =10.2 + VBIAS 3.0 to 5.5 V R4 T1 CIN 4.7 μF C1 0.1 μF 100 k7 D1 R1 150 k7 1% VOUT COUT 100 μF 330 V R2 VIN CHARGE 150 k7 1% SW A8835 T1 C1 0.1 μF R4 IGBTDRV VIN GND FB R3 1.20 k7 DONE Figure 1. Typical circuit with separate power supply to transformer TRIGGER IGBTDRV GND To IGBT Gate Figure 2. Typical circuit with single power supply VOUT R1 150 k7 150 k7 SW A8835 R3 To IGBT Gate D1 R2 1.20 k7 1% TRIGGER CIN 4.7 μF 100 k7 CHARGE FB DONE A8835-DS, Rev. 1 VBIAS 3.0 to 5.5 V COUT Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Selection Guide Part Number A8835EEJTR-T Package Packing* 10-pin TDFN *Contact Allegro for additional packing options 1500 pieces/ 7-in. reel Absolute Maximum Ratings Characteristic Symbol Notes Rating Units VSW DC voltage. (VSW is self-clamped by an internal active clamp and is allowed to exceed 40 V during flyback spike durations. Maximum repetitive energy during flyback spike: 0.5 μJ at frequency ≤ 400 kHz.) –0.3 to 40 V VIGBTDRV –0.3 to VIN + 0.3 V FB pin VFB –0.3 to VIN V All other pins VX –0.3 to 7 V SW pin IGBTDRV pin Operating Ambient Temperature TA –40 to 85 ºC Maximum Junction Temperature TJ(max) 150 ºC Tstg –55 to 150 ºC Storage Temperature Range E Package Thermal Characteristics Characteristic Package Thermal Resistance Symbol RθJA Test Conditions* On 4-layer PCB, based on JEDEC standard Rating Units 45 ºC/W *Additional information is available on the Allegro website. Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 2 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Functional Block Diagram SW VIN Control Logic DCM Detector (dV/dt = 0) 18 μs HmL Triggered Timer 40 V DMOS Q S SET Q R CMP2 CLR Q ILIM Comparator CHARGE Adjustable Reference ILIM Decoder Enable Q 100 kΩ Q SET CLR S FB R CMP1 1.2 V DONE VIN TRIGGER One-Shot 100 kΩ 20 kΩ IGBTDRV GND Terminal List Table Device Pin-out Diagram Number 1,10 2 NC IGBTDRV VIN GND CHARGE 10 NC 9 FB 1 2 3 4 5 PAD 8 DONE 7 TRIGGER 6 SW Name NC Function No connection. IGBTDRV IGBT driver gate drive output. 3 VIN Input voltage. Connect to 3 to 5.5 V bias supply. Decouple VIN voltage with 0.1 μF ceramic capacitor placed close to this pin. 4 GND Device ground 5 CHARGE 6 SW 7 Charge enable and current limit serial programming pin. Set this pin low to shut down the chip. Drain connection of internal DMOS switch. Connect to transformer primary winding. TRIGGER Strobe signal input 8 ¯N̄¯Ē¯ D̄¯Ō 9 FB – PAD Open collector output, pulls low when output reaches target value and CHARGE is high. Goes high during charging or whenever CHARGE is low. Output voltage feedback Exposed pad for enhanced thermal dissipation. Connect to ground plane. Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 3 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 ELECTRICAL CHARACTERISTICS Valid at VIN = 3.3 V, TA = 25°C except indicates specifications guaranteed from −40°C to 85°C ambient, unless otherwise specified Characteristics Supply Voltage* UVLO Enable Threshold UVLO Hysteresis Supply Current Primary Side Current Limit (ILIM clock input at CHARGE pin) SW On Resistance SW Leakage Current* Switch Off Timeout Switch On Timeout CHARGE Input Current CHARGE Input Voltage* ILIM Clock High Time at CHARGE Pin ILIM Clock Low Time at CHARGE Pin Total ILIM Setup Time Symbol Test Conditions Min. VIN Typ. Max. Units 3 – 5.5 V 2.55 – – – – 1.58 – – – – – – – – 2.65 150 1.5 1 0.01 1.75 1.58 1.4 1.22 1.05 0.86 0.7 0.55 0.27 2.75 – – 10 1 1.93 – – – – – – – – V mV mA μA μA A A A A A A A A Ω – – 1 μA tOFF(Max) tON(Max) ICHARGE VCHARGE = VIN VCHARGE(H) – – – 2 18 18 33 – – – – – μs μs μA V VCHARGE(L) – – 0.8 V 20 0.2 0.2 – – – – 54 – – – – μs μs μs μs – – 1 μA – – 100 mV VUVLO VIN rising VUVLOHYS IIN Charging Charging done Shutdown (VCHARGE = 0 V, VTRIGGER = 0 V) ISWLIM1 ISWLIM2 ISWLIM3 ISWLIM4 ISWLIM5 ISWLIM6 ISWLIM7 ISWLIM8 RDS(On)SW VIN = 3.3 V, ID = 800 mA ISWLKG tILIM1(H) tILIM(H) tILIM(L) tILIM(SU) D̄¯Ō ¯N̄¯Ē¯ Output Leakage Current* IDONELKG D̄¯Ō ¯N̄¯Ē ¯ Output Low Voltage* FB Voltage Threshold* FB Input Current IGBT Driver IGBTDRV On Resistance to VIN IGBTDRV On Resistance to GND TRIGGER Input Current VDONE(L) VFB IFB VSW = 35 V Initial pulse Subsequent pulses 32 μA into D̄¯Ō ¯N̄¯Ē¯ pin 1.187 1.205 1.223 – –120 – VFB = 1.205 V RDS(On)I-V VIN = 3.3 V, VIGBTDRV = 1.5 V, VTRIGGER = VIN RDS(On)I-G VIN = 3.3 V, VIGBTDRV = 1.5 V, VTRIGGER = 0 V ITRIGGER VTRIGGER = VIN VTRIGGER(H) TRIGGER Input Voltage* VTRIGGER(L) Propagation Delay, Rising tDr Rgate=12 Ω, CLOAD = 6500 pF, VIN = 3.3 V Propagation Delay, Falling tDf Rgate=12 Ω, CLOAD = 6500 pF, VIN = 3.3 V Output Rise Time tr Rgate=12 Ω, CLOAD = 6500 pF, VIN = 3.3 V Output Fall Time tf Rgate=12 Ω, CLOAD = 6500 pF, VIN = 3.3 V dV/dt Threshold for ZVS Comparator dV/dt Measured at SW pin *Specification over the range TA = –40°C to 85°C guaranteed by design and characterization. – – – 2 – – – – – – 5 6 33 – – 30 30 70 70 20 – – – – 0.8 – – – – – V nA Ω Ω μA V V ns ns ns ns V/μs Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 4 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Operation Timing Diagram VUVLO VIN CHARGE SW Target VOUT VOUT DONE TRIGGER IGBTDRV A C B D E F Explanation of Events: A. Start charging by pulling CHARGE to high, provided that VIN is above the VUVLO level. B. Charging stops when VOUT reaches the target voltage. D̄¯Ō ¯N̄¯Ē¯ goes low, to signal the completion of the charging process. C. Start a new charging process with a low-to-high transition at the CHARGE pin. D. Pull CHARGE to low, to put the controller in low-power standby mode. E. Charging does not start, because VIN is below VUVLO level when CHARGE goes high. F. After VIN goes above VUVLO, another low-to-high transition at the CHARGE pin is required to start charging. IGBT Drive Timing Definition TRIGGER 50% tDr IGBTDRV 10% 50% tr tDf 90% 90% tf 10% Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 5 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Performance Characteristics IGBT Drive waveforms are measured with R-C load (12 Ω, 6800 pF) IGBT Drive Performance tr Rising Signal VIGBTDRV Symbol C2 C3 t Conditions Parameter VIGBTDRV VTRIGGER time Parameter tDr tr CLOAD Rgate Units/Division 1V 1V 50 ns Value 22.881 ns 63.125 ns 6800 pF 12 Ω C2 VTRIGGER C3 t tf Falling Signal Symbol C2 C3 t Conditions Parameter VIGBTDRV VTRIGGER time Parameter tDf tf CLOAD Rgate Units/Division 1V 1V 50 ns Value 27.427 ns 65.529 ns 6800 pF 12 Ω C2 VIGBTDRV C3 VTRIGGER t Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 6 A8835 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver Functional Description Overview lower current limit at low battery voltages. The A8835 is a photoflash capacitor charger control IC with adjustable input current limiting. It also integrates an IGBT driver for strobe operation of the flash tube, dramatically saving board space in comparison to discrete solutions for strobe flash operation. The control logic is shown in the functional block diagram. Figure 4 shows the ILIM clock timing scheme protocol. The total ILIM setup time, tILIM(SU) , denotes the time needed for the decoder circuit to receive ILIM inputs and set ISWLIM . Apply current limit pulses during tILIM(SU) (54 μs) period. The charging operation of the A8835 is started by a low-to-high signal on the CHARGE pin, provided that VIN is above VUVLO level. It is strongly recommended to keep the CHARGE pin at logic low during power-up. When VIN exceeds the UVLO level, a low-to-high transition on the CHARGE pin is required to start the charging. The primary peak current is set by input programming signals from the CHARGE pin. When a charging cycle is initiated, the transformer primary side current, IPrimary, ramps up linearly at a rate determined by the combined effect of the battery voltage, VBATT , and the primary side inductance, LPrimary. When IPrimary reaches the current limit, ISWLIM , the internal MOSFET is turned off immediately, allowing the energy to be pushed into the photoflash capacitor, COUT, from the secondary winding. The secondary side current drops linearly as COUT charges. The switching cycle starts again, either after the transformer flux is reset, or after a predetermined time period, tOFF(Max) (18 μs), whichever occurs first. The output voltage, VOUT, is sensed by a resistor string, R1, R2 , and R3 (see application circuit diagrams), connected across the transformer secondary winding. This resistor string forms a voltage divider that feeds back to the FB pin. The resistors must be sized to achieve a desired output voltage level based on a typical value of 1.205 V at the FB pin. As soon as VOUT reaches the desired value, the charging process is terminated. Toggling the CHARGE pin can start a refresh operation. Figure 5 shows the timing definition of the primary current limiting circuit. At the end of the setup period, tILIM(SU) , primary current starts to ramp up to the set ISWLIM. The ISWLIM setting remains in effect as long as the CHARGE pin is high. To reset the ILIM counter, pull the CHARGE pin low before clocking in the new setting. t ILIM(H) ≥ 0.2 μs t ILIM(L) ≥ 0.2 μs Clock input at CHARGE pin t ILIM1(H) = first pulse width t ILIM(SU) = ILIM setup time Subsequent rising edges (0 to 7) First rising edge 0 μs Switching starts 54 μs 20 μs Figure 4. ILIM Clock Timing Definition Start ILIM counter Reset ILIM counter CHARGE Four rising edges within t ILIM(SU) ISWLIM4 = 1.22 A I SW Input Current Limiting The peak current limit can be programmed to eight different levels, from 1.75 A down to 550 mA, by clocking the CHARGE pin. An internal digital circuit decodes the input clock signals, which sets the switch current limit. This flexible scheme allows the user to operate the flash circuit according to different battery input voltages. The battery life can be effectively extended by setting a Switching starts 0 μs 20 μs Switching stops 54 μs Figure 5. Current Limit Programming Example (ISWLIM4 selected). Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 7 A8835 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver VOUT Timer Mode After the first start-up or an ILIM decoder reset, each new current limit can be set by sending a burst of pulses to the CHARGE pin. The first rising edge starts the ILIM decoder, and up to 8 rising edges will be counted to set the ISWLIM level. The first pulse width, tILIM1(H), must be at least 20 μs long. Subsequent pulses (up to 7 more) can be as short as 0.2 μs. The last low-to-high edge must arrive within 54 μs from the first edge. The CHARGE pin will stay high afterwards. Fast Charging Mode VBAT IIN Figure 4. Timer mode and Fast Charging mode: t = 200 ms/div; VOUT = 50 V/div; VBAT = 1 V/div.; IIN = 100 mA/div., VBAT = 3.6 V; COUT = 20 μF / 330 V; and ISWlim ≈ 0.7 A. Switch On-Time and Off-Time Control The A8835 implements an adaptive on-time/off-time control. Ontime duration, ton , is equal to ton = ISWlim × LP / VBAT. Off-time duration, toff , depends on the operating conditions during switch off-time. The A8835 applies its two charging modes, Fast Charging mode and Timer mode, according to those conditions. VSW VBAT VOUT ISW Timer Mode and Fast Charging Mode The A8835 achieves fast charging times and high efficiency by operating in discontinuous conduction mode (DCM) through most of the charging process The relationship of Timer mode and Fast Charging mode is shown in figure 4. Figure 5. Expanded view of Timer mode: VOUT ≤ 14 V; t = 2 μs/div; VBAT = 3.6 V; ISWlim = 1.05 A. The IC operates in Timer mode when beginning to charge a completely discharged photoflash capacitor, usually when the output voltage, VOUT, is less than approximately 15 to 20 V. Timer mode is a fixed period, 18 μs, off-time control. One advantage of having Timer mode is that it limits the initial battery current surge and thus acts as a “soft-start.” A time-expanded view of a Timer mode interval is shown in figure 5. As soon as a sufficient voltage has built up at the output capacitor, the IC enters Fast-Charging mode. In this mode, the next switching cycle starts after the secondary side current has stopped flowing, and the switch voltage has dropped to a minimum value. A proprietary circuit is used to allow minimum-voltage switching, even if the SW pin voltage does not drop to 0 V. This enables Fast-Charging mode to start earlier, thereby reducing the overall charging time. Minimum-voltage switching is shown in figure 6. During Fast-Charging mode, when VOUT is high enough (over 50 V), true zero-voltage switching (ZVS) is achieved. This further improves efficiency as well as reduces switching noise. A ZVS interval is shown in figure 7. VSW VBAT VOUT ISW Figure 6. Minimum-voltage switching: VOUT ≥ 15 V; t =1 μs/div; VBAT = 3.6 V; and ISWlim = 1.05 A. VOUT VSW VSW VBAT VBAT ISW VOUT ISW Figure 7. ZVS voltage switching: VOUT = 120 V, t =0.2 μs/div, VBAT = 3.6 V, ISWlim = 1.05 A. Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 8 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Applications Information Transformer Design Turns Ratio. The minimum transformer turns ratio, N, (Second- ary : Primary) should be chosen based on the following formula: N≥ VOUT + VD_Drop 40 − VBATT (1) where: VOUT (V) is the required output voltage level, VD_Drop (V) is the forward voltage drop of the output diode(s), VBATT (V) is the transformer battery supply, and 40 (V) is the rated voltage for the internal MOSFET switch, representing the maximum allowable reflected voltage from the output to the SW pin. For example, if VBATT is 3.5 V and VD_Drop is 1.7 V (which could be the case when two high voltage diodes were in series), and the desired VOUT is 320 V, then the turns ratio should be at least 8.9. In a worst case, when VBATT is highest and VD_Drop and VOUT are at their maximum tolerance limit, N will be higher. Taking VBATT = 5.5 V, VD_Drop = 2 V, and VOUT = 320 V × 102 % = 326.4 V as the worst case condition, N can be determined to be 9.5. In practice, always choose a turns ratio that is higher than the calculated value to give some safety margin. In the worst case example, a minimum turns ratio of N = 10 is recommended. Primary Inductance. As a loose guideline when choosing the primary inductance, LPrimary (μH), use the following formula: LPrimary ≥ 300 × 10−9 × VOUT N × ISWLIM (2) . Ideally, the charging time is not affected by transformer primary inductance. In practice, however, it is recommended that a primary inductance be chosen between 10 μH and 20 μH. When LPrimary is lower than 10 μH, the converter operates at higher frequency, which increases switching loss proportionally. This leads to lower efficiency and longer charging time. When LPrimary is greater than 20 μH, the rating of the transformer must be dramatically increased to handle the required power density, and the series resistances are usually higher. A design that is optimized to achieve a small footprint solution would have an LPrimary of 12 to 14 μH, with minimized leakage inductance and secondary capacitance, and minimized primary and secondary series resistance. See the table Recommended Components for more information. Leakage Inductance and Secondary Capacitance The transformer design should minimize the leakage inductance to ensure the turn-off voltage spike at the SW node does not exceed the 40 V limit. An achievable minimum leakage inductance for this application, however, is usually compromised by an increase in parasitic capacitance. Furthermore, the transformer secondary capacitance should be minimized. Any secondary capacitance is multiplied by N2 when reflected to the primary, leading to high initial current swings when the switch turns on, and to reduced efficiency. Input Capacitor Selection Ceramic capacitors with X5R or X7R dielectrics are recommended for the input capacitor, CIN. During initial timer mode the device operates with 18 μs off-time. A typical input section for a photoflash module with input filter inductor, or a test setup with long connecting wires is shown in figure 12. The resonant period caused by input filter inductor and capacitor should be at least 2 times greater or smaller than the 18 μs timer period, to reduce input ripple current during this period. See figure 13. IVIN IVIN VOUT VOUT LIN + VBAT CIN A8835 Figure 12. Typical input section with input inductance (inductance, LIN, may be an input filter inductor or inductance due to long wires in test setup) CIN = 4.7 μF CIN = 10 μF Figure 13. Effects of changing the values of CIN . Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com 9 A8835 Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver VBAT VOUT IBAT Figure 14. Input current waveforms with Li+ battery connected by 5-in. wire and decoupled by 4.7 μF capacitor. t = 500 ms/div; VBAT = 2 V/div; VOUT = 100 V/div.; IBAT = 1 A/div. VBAT The resonant period is given by: Tres = 2 × × (LIN × CIN ) ½ It is recommended to use at least 4.7 μF / 6.3 V to decouple the battery input, VBAT, at the primary of the transformer. Decouple the VIN pin using a 0.1 μF / 6.3 V bypass capacitor. Output Diode Selection Choose the rectifying diode(s), D1, to have small parasitic capacitance (short reverse recovery time) while satisfying the reverse voltage and forward current requirements. The peak reverse voltage of the diode, VDPeak, occurs when the internal MOSFET switch is closed. It can be calculated as: VDPeak = VOUT + N × VBAT The peak current of the rectifying diode, IDPeak, is calculated as: IDPeak = IPrimaryPeak / N VOUT IBAT Figure 15. Input current waveforms with Li+ battery connected through 10 μH inductor and 4.7 μF capacitor. t = 500 ms/div; VBAT = 2 V/div; VOUT = 100 V/div.; IBAT = 1 A/div. VBAT VOUT IBAT Layout Guidelines Key to a good layout for the photoflash capacitor charger circuit is to keep the parasitics minimized on the power switch loop (transformer primary side) and the rectifier loop (secondary side). Use short, thick traces for connections to the transformer primary ¯ signal trace and other and SW pin. It is important that the D̄¯¯ Ō¯¯N̄¯Ē signal traces be routed away from the transformer and other switching traces, in order to minimize noise pickup. In addition, high voltage isolation rules must be followed carefully to avoid breakdown failure of the circuit board. Avoid locating the ground plane underneath transformer secondary and diode to minimize parasitic capacitance. It is recommended to use a single high voltage resistor to sense output voltage. Two series resistors, R1 and R2, may be used on the high voltage VOUT side. Referring to figure 17, a parasitic capacitor, CP1, across the R1-R2 junction and GND, can affect output voltage accuracy due to slow voltage sensing at the FB pin. A parasitic capacitor, CP2, between the R1-R2 junction and VOUT , can affect output voltage accuracy due to overshoot in the sensed voltage at the FB pin. Very small capacitance (≈1 pF) can cause a significant error. Figure 16. Input current waveforms with Li+ battery connected through 10 μH inductor and 10 μF capacitor. t = 500 ms/div; VBAT = 2 V/div; VOUT = 100 V/div.; IBAT = 500 mA/div. 10 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Minimize parasitic capacitors with careful layout. The center pad between R1 and R2 should be routed away from any GND and other traces. Avoid placing the GND plane directly underneath the center pad. Place R1 and R2 as close as possible in a straight line as shown in figure 18. D1 CP2 R1 VOUT + COUT R2 SW R1 Do not locate areas of the GND plane underneath this zone CP1 R2 FB A8835 R3 R3 FB Figure 17. Equivalent circuit with parasitic capacitors across feedback divider. GND Figure 18. Recommended layout for feedback divider. 11 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Recommended Layout VIN C4 D1 X2 CIN COUT R1 VIN TRIGGER TRIGGER CHARGE CHARGE DONE R4 A8835 SW Xenon+ R5 C3 R2 GND Xenon– IGBTDRV DONE FB NC NC PAD Xenon Trigger Rg1 Q1 R3 12 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Recommended Components Component C1, Input Capacitor CIN, Input Capacitor Rating 0.1 μF, ±10%, 16 V, X5R or X7R ceramic capacitor (0603) 4.7 μF, ±10%, 10 V, X5R or X7R ceramic capacitor (0805) Part Number Source GRM188R71C104KA01D Murata LMK212BJ475KG Taiyo Yuden COUT, Photoflash Capacitor 330 V 100 μF (or 19 to 180 μF) EPH-331ELL101B131S Chemi-Con D1, Output Diode 2 x 250 V, 225 mA, 5 pF Philips Semiconductor, Fairchild Semiconductor BAV23S Instead of two resistors, a single 300 kΩ resistor with 350 V rating can be used 150 kΩ each 1/4 W, ± 1%; R1, R2, FB Resistors 1206, 0805, or 0603 resistors rated for 150 V R3, FB Resistor T1, Transformer Remarks 10 V minimum rating can be used 1.2 kΩ 1/10 W ±1% (0603 or 0402) LP = 14.2 μH, IP = 2 A, N = 10 T-15-154M Tokyo Coil Suitable for ILIM from 0.55 to 1.75 A LP = 7.4 μH, IP = 2 A, N = 10 T-16-103A Tokyo Coil Suitable for ILIM from 1.2 to 1.75 A only LP = 12.8 μH, IP = 1.5 A, N=10 T-16-024A Tokyo Coil Suitable for ILIM from 0.55 to 1.4 A only 13 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Package EJ, 10-Contact TDFN with Exposed Thermal Pad 0.30 3.00 ±0.15 0.85 0.50 10 10 3.00 ±0.15 1.65 3.10 A 1 2 1 11X D SEATING PLANE 0.08 C +0.05 0.25 –0.07 C C 2.38 PCB Layout Reference View 0.75 ±0.05 0.50 1 For Reference Only (reference JEDEC MO-229WEED) Dimensions in millimeters Exact case and lead configuration at supplier discretion within limits shown 2 0.40 ±0.10 1.65 B 10 2.38 A Terminal #1 mark area B Exposed thermal pad (reference only, terminal #1 identifier appearance at supplier discretion) C Reference land pattern layout (reference IPC7351 SON50P300X300X80-11WEED3M); All pads a minimum of 0.20 mm from all adjacent pads; adjust as necessary to meet application process requirements and PCB layout tolerances; when mounting on a multilayer PCB, thermal vias at the exposed thermal pad land can improve thermal dissipation (reference EIA/JEDEC Standard JESD51-5) 14 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com Photoflash Capacitor Charger with Programmable Current Limit and IGBT Driver A8835 Revision History Revision Rev. 1 Revision Date April 19, 2012 Description of Revision Miscellaneous format changes Copyright ©2008-2013, Allegro MicroSystems, LLC Allegro MicroSystems, LLC reserves the right to make, from time to time, such departures from the detail specifications as may be required to permit improvements in the performance, reliability, or manufacturability of its products. Before placing an order, the user is cautioned to verify that the information being relied upon is current. Allegro’s products are not to be used in life support devices or systems, if a failure of an Allegro product can reasonably be expected to cause the failure of that life support device or system, or to affect the safety or effectiveness of that device or system. The information included herein is believed to be accurate and reliable. However, Allegro MicroSystems, LLC assumes no responsibility for its use; nor for any infringement of patents or other rights of third parties which may result from its use. For the latest version of this document, visit our website: www.allegromicro.com 15 Allegro MicroSystems, LLC 115 Northeast Cutoff, Box 15036 Worcester, Massachusetts 01615-0036 (508) 853-5000 www.allegromicro.com