NCP1217 D

NCP1217, NCP1217A
Enhanced PWM Current-Mode
Controller for High-Power
Universal Off-Line Supplies
Housed in an SO−8 or PDIP−7 package, the NCP1217 represents
the enhanced version of the NCP1203−based controllers. Due to its
high drive capability, NCP1217 drives large gate−charge MOSFETs,
which together with internal ramp compensation and built−in
overvoltage protection, ease the design of modern AC/DC adapters.
NCP1217 offers a true alternative to UC384X−based designs.
With an internal structure operating at different fixed frequencies
(65–100–133 kHz), the controller features a high−voltage startup FET,
which ensures a clean and loss less startup sequence. Its current−mode
control topology provides an excellent input audio−susceptibility and
inherent pulse−by−pulse control. Internal ramp compensation easily
prevents subharmonic oscillations from taking place in continuous
conduction mode designs.
When the current setpoint falls below a given value, e.g. the output
power demand diminishes, the IC automatically enters the so−called
skip cycle mode and provides excellent efficiency at light loads.
Because this occurs at a user adjustable low peak current, no acoustic
noise takes place.
The NCP1217 features two efficient protective circuitries: 1) In
presence of an overcurrent condition, the output pulses are disabled
and the device enters a safe burst mode, trying to restart. Once the
default has gone, the device auto−recovers. 2) If an external signal
(e.g. a temperature sensor) pulls Pin 1 above 3.2 V, output pulses are
immediately stopped and the NCP1217 stays latched in this position.
Reset occurs when the VCC collapses to ground, e.g. the user unplugs
the power supply.
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MARKING
DIAGRAMS
8
SOIC−8
D SUFFIX
CASE 751
8
1
XXXXX
ALYW
G
1
XXXXXXXXX
AWL
YYWWG
PDIP−7
P SUFFIX
CASE 626B
8
1
1
XXXXXX
A
L, WL
Y, YY
W, WW
G or G
=
=
=
=
=
=
Specific Device Code
Assembly Location
Wafer Lot
Year
Work Week
Pb−Free Package
Features
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Current−Mode with Adjustable Skip−Cycle Capability
Built−in Internal Ramp Compensation
Auto−Recovery Internal Output Short−Circuit Protection
Internal 1.0 ms Soft−Start (NCP1217A Only)
Limited Duty−Cycle to 50% (NCP1217A Only)
Full Latchoff if Adjustment Pin is Brought High
Extremely Low No−Load Standby Power
Internal Temperature Shutdown
500 mA Peak Current Capability
Fixed Frequency Versions at 65 kHz, 100 kHz and 133 kHz
Direct Optocoupler Connection
Internal Leading Edge Blanking
SPICE Models Available for TRANsient and AC Analysis
These are Pb−Free Devices
DEVICE MARKING INFORMATION
See detailed device marking information in the ordering
information section on page 17 of this data sheet.
PIN CONNECTIONS
Adj 1
8
HV
FB 2
7
NC
CS 3
6
VCC
5
Drv
GND
4
(Top View)
ORDERING INFORMATION
See detailed ordering and shipping information in the ordering
information section on page 17 of this data sheet.
Typical Applications
•
•
•
•
High Power AC/DC Converters for TVs, Set−Top Boxes, etc.
Offline Adapters for Notebooks
Telecom DC−DC Converters
All Power Supplies
© Semiconductor Components Industries, LLC, 2015
April, 2015 − Rev. 9
1
Publication Order Number:
NCP1217/D
NCP1217, NCP1217A
See Application
Section
+
Aux.
+
VOUT
NCP1217
Adj
1
2
EMI
FILTER
CS VCC
3
Gnd Drv
4
UNIVERSAL
INPUT
HV
FB
8
7
6
5
Ramp Adjustment
+
Figure 1. Typical Application Example
PIN FUNCTION DESCRIPTION
Pin No.
Pin Name
Function
Description
1
Adj
Adjust the skipping peak current
This pin lets you adjust the level at which the cycle skipping process takes
place. Shorting this pin to ground permanently disables the skip cycle
feature.
By bringing this pin above 3.1 V, you permanently shut off the device.
2
FB
Sets the peak current setpoint
By connecting an optocoupler to this pin, the peak current setpoint is adjusted accordingly to the output power demand.
3
CS
Current sense input
This pin senses the primary current and routes it to the internal comparator via an L.E.B. By inserting a resistor in series with the pin, you control
the amount of ramp compensation you need.
4
GND
The IC ground
5
Drv
Driving pulses
6
VCC
Supplies the IC
7
NC
8
HV
−
The driver’s output to an external MOSFET.
This pin is connected to an external bulk capacitor of typically 22 F.
−
Ensures a clean and lossless
startup sequence
This unconnected pin ensures adequate creepage distance.
Connected to the high−voltage rail, this pin injects a constant current into
the VCC capacitor during the startup sequence.
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2
NCP1217, NCP1217A
Adj
Latchoff
Comparator
+
-
1
+
−
80 k
FB
HV
8
Set
3.1 V
Latch
1.1 V
UVLO
Reset
Skip Cycle
Comparator
+
-
2
HV Current
Source
NC
7
UVLO High and Low
Internal VCC
24 k
Reset
Current
Sense
250 ns
L.E.B.
3
65−100−133 kHz
Clock
Q Flip−Flop
DCmax = 74%
Set
Q
Reset
VCC
Overload
Management
6
19 k
Ramp
Compensation
20 k
Ground
4
+
−
+
-
57 k
VREF
Drv
25 k
* Available for “A” version only
1ms SS*
1V
5
±500 mA
Figure 2. Internal Circuit Architecture
MAXIMUM RATINGS
Rating
Symbol
Value
Unit
VCC
16
V
−
−0.3 to 10
V
Maximum Voltage on Pin 8 (HV), Pin 6 (VCC) Decoupled to Ground with 10 F
VHV
500
V
Maximum Voltage on Pin 8 (HV), Pin 6 (VCC) Grounded
VHV
450
V
28
V
−
5.0
mA
Thermal Resistance, Junction−to−Case
RJC
57
°C/W
Thermal Resistance, Junction−to−Air, PDIP−7 Version
Thermal Resistance, Junction−to−Air, SO−8 Version
RJA
RJA
100
178
°C/W
Power Supply Voltage
Power Supply Voltage on All Other Pins Except Pin 8 (HV), Pin 6 (VCC) and Pin 5 (Drv)
Minimum Operating Voltage on Pin 8 (HV)
Maximum Current into All Pins Except VCC (6) and HV (8) when 10 V ESD Diodes are Activated
Maximum Junction Temperature
TJMAX
150
°C
Temperature Shutdown
−
155
°C
Hysteresis in Shutdown
−
30
°C
Storage Temperature Range
−
−60 to +150
°C
ESD Capability, HBM Model (All Pins Except VCC and HV)
−
2.0
kV
ESD Capability, Machine Model
−
200
V
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. This device series contains ESD protection rated using the following tests:
Human Body Model (HBM) 2000 V per JEDEC Standard JESD22, Method A114E.
Machine Model (MM) 200 V per JEDEC Standard JESD22, Method A115A.
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3
NCP1217, NCP1217A
ELECTRICAL CHARACTERISTICS (For typical values TJ = 25°C, for min/max values TJ = 0°C to +125°C, Max TJ = 150°C,
VCC = 11 V unless otherwise noted.)
Characteristic
Pin
Symbol
Min
Typ
Max
Unit
Turn−On Threshold Level, VCC Going Up
6
VCCON
11.8
12.8
13.8
V
Minimum Operating Voltage After Turn−On
6
VCCmin
6.9
7.6
8.3
V
VCC Decreasing Level at which the Latchoff Phase Ends
6
VCClatch
−
5.6
−
V
Internal IC Consumption, No Output Load on Pin 5,
FSW = 65 kHz
6
ICC1
−
960
1110
(Note 1)
A
Internal IC Consumption, No Output Load on Pin 5,
FSW = 100 kHz
6
ICC1
−
1020
1180
(Note 1)
A
Internal IC Consumption, No Output Load on Pin 5,
FSW = 133 kHz
6
ICC1
−
1060
1200
(Note 1)
A
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
FSW = 65 kHz
6
ICC2
−
1.7
2.0
(Note 1)
mA
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
FSW = 100 kHz
6
ICC2
−
2.1
2.4
(Note 1)
mA
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
FSW = 133 kHz
6
ICC2
−
2.4
2.9
(Note 1)
mA
Internal IC Consumption, Latchoff Phase, VCC = 6.0 V
6
ICC3
−
230
−
A
High−Voltage Current Source, VCC = 10 V
8
IC1
3.5
(Note 2)
6.0
7.8
mA
High−Voltage Current Source, VCC = 0
8
IC2
−
7.0
−
mA
Output Voltage Rise−Time @ CL = 1.0 nF, 10−90% of a 12 V
Output Signal
5
Tr
−
60
−
ns
Output Voltage Fall−Time @ CL = 1.0 nF, 10−90% of a 12 V
Output Signal
5
Tf
−
20
−
ns
Source Resistance
5
ROH
15
20
35
Sink Resistance
5
ROL
5.0
10
18
SUPPLY SECTION (All frequency versions, unless otherwise noted)
INTERNAL STARTUP CURRENT SOURCE (TJ u 0°C)
DRIVE OUTPUT
CURRENT COMPARATOR (Pin 5 Unloaded)
Input Bias Current @ 1.0 V Input Level on Pin 3
3
IIB
−
0.02
−
A
Maximum Internal Current Setpoint
3
ILimit
0.9
1.0
1.1
V
Default Internal Current Setpoint for Skip Cycle Operation
3
ILskip
−
330
−
mV
Propagation Delay from Current Detection to Gate OFF State
3
TDEL
−
90
150
ns
Leading Edge Blanking Duration
3
TLEB
−
250
−
ns
INTERNAL OSCILLATOR (VCC = 11 V, Pin 5 Loaded by 1.0 k)
Oscillation Frequency, 65 kHz Version
−
fOSC
58.5
65
71.5
kHz
Oscillation Frequency, 100 kHz Version
−
fOSC
90
100
110
kHz
Oscillation Frequency, 133 kHz Version
−
fOSC
120
133
146
kHz
Maximum Duty−Cycle, NCP1217
−
Dmax
69
74
80
%
Maximum Duty−Cycle, NCP1217A
−
Dmax
42
46.5
50
%
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
1. Maximum Value @ TJ = 0°C.
2. Minimum Value @ TJ = 125°C.
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NCP1217, NCP1217A
ELECTRICAL CHARACTERISTICS (continued) (For typical values TJ = 25°C, for min/max values TJ = 0°C to +125°C,
Max TJ = 150°C, VCC = 11 V unless otherwise noted.)
Pin
Symbol
Min
Typ
Max
Unit
Internal Pull−Up Resistor
2
Rup
−
19
−
k
Pin 2 (FB) to Internal Current Setpoint Division Ratio
−
Iratio
−
3.3
−
−
Default Skip Mode Level
1
Vskip
0.93
1.1
1.26
V
Pin 1 Internal Output Impedance
1
Zout
−
27
−
k
Internal Ramp Level @ 25°C (Note 3)
3
Vramp
2.6
2.9
3.2
V
Internal Ramp Resistance to CS Pin
3
Rramp
−
19
−
k
1
Vlatch
2.69
3.10
3.42
V
Characteristic
FEEDBACK SECTION (VCC = 11 V, Pin 5 Loaded by 1.0 k)
SKIP CYCLE GENERATION
INTERNAL RAMP COMPENSATION
ADJUSTMENT LATCHOFF LEVEL
Latching Level
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
3. A 1.0 M resistor is connected to the ground for the measurement.
80
14.0
70
13.5
60
50
VCCOFF, (V)
HV PIN LEAKAGE CURRENT @ 500V (A)
TYPICAL CHARACTERISTICS
40
30
13.0
12.5
12.0
20
11.5
10
0
−50
0
50
11.0
−50
150
100
0
50
100
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 3. High Voltage Pin Leakage Current vs.
Temperature
Figure 4. VCCOFF vs. Temperature
9.0
150
3.0
ICC 1.0 nF LOAD, (mA)
2.8
VCCMIN, (V)
8.5
8.0
7.5
2.6
2.4
133 kHz
2.2
2.0
100 kHz
1.8
1.6
65 kHz
1.4
1.2
7.0
−50
0
50
1.0
−50
150
100
TEMPERATURE (°C)
0
50
100
TEMPERATURE (°C)
Figure 5. VCCMIN vs. Temperature
Figure 6. ICC 1.0 nF Load vs. Temperature
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5
150
NCP1217, NCP1217A
TYPICAL CHARACTERISTICS (continued)
150
5.90
133 kHz
5.80
110
VCClatch, (V)
FOSC, (kHz)
130
100 kHz
90
65 kHz
70
50
−50
0
50
5.70
5.60
5.50
5.40
100
5.30
−50
150
0
Figure 7. Switching Frequency vs.
Temperature
DRIVE SOURCE RESISTANCE, ()
ICC3, (A)
400
350
300
250
0
50
20
15
10
5
0
−50
150
100
25
0
50
100
150
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 9. ICC3 vs. Temperature
Figure 10. Drive Source Resistance vs.
Temperature
1.10
CURRENT SENSE LIMIT, (V)
30
DRIVE SINK RESISTANCE, ()
150
30
450
25
20
15
10
5
0
−50
100
Figure 8. VCClatch vs. Temperature
500
200
−50
50
TEMPERATURE (°C)
TEMPERATURE (°C)
0
50
100
150
1.05
1.00
0.95
0.90
−50
TEMPERATURE (°C)
0
50
100
TEMPERATURE (°C)
Figure 11. Drive Sink Resistance vs.
Temperature
Figure 12. Current Sense Limit vs.
Temperature
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6
150
NCP1217, NCP1217A
TYPICAL CHARACTERISTICS (continued)
3.10
INT COMP RAMP LEVEL (V)
1.15
1.10
1.05
1.00
−50
0
50
100
3.05
3.00
2.95
2.90
2.85
2.80
2.75
2.70
−50
150
0
50
Figure 13. Skip Mode Level vs. Temperature
Figure 14. Int Comp Ramp Max Level vs.
Temperature
8.0
7.0
6.0
5.0
4.0
3.0
−50
100
TEMPERATURE (°C)
TEMPERATURE (°C)
HV SOURCE CURRENT (mA)
DSKIP MODE LEVEL (V)
1.20
0
50
100
TEMPERATURE (°C)
Figure 15. High Voltage Current Source
(@ VCC = 10V) vs. Temperature
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7
150
150
NCP1217, NCP1217A
APPLICATION INFORMATION
Introduction
help reducing magnetics or improve the EMI signature
before reaching the 150 kHz starting point.
Overcurrent Protection (OCP): By continuously
monitoring the VCC auxiliary winding voltage, NCP1217
enters burst mode as soon as the power supply undergoes an
overload: when the VCC voltage goes down until it crosses
the undervoltage lockout level (VCCmin). When the
NCP1217 reaches this level (typically 7.6 V), it stops the
switching pulses until the VCC pin voltage reaches VCClatch
(5.6 V). At VCClatch, the NCP1217 attempts to restart. As
soon as the default disappears, the power supply resumes
operation.
Overvoltage Protection (OVP): If pin1 is brought to a level
higher than the internal 3.2 V reference voltage, the
controller is permanently shut down until the user cycles the
VCC OFF and ON again. This allows the building of
efficient and low−cost over voltage protection circuits.
Wide Duty−Cycle Operation: Wide mains operation
requires a large duty−cycle excursion. The NCP1217 can go
up to 74% typically.
Low Standby−Power: If SMPS naturally exhibit a good
efficiency at nominal load, they begin to be less efficient
when the output power demand diminishes. By skipping
unneeded switching cycles, the NCP1217 drastically
reduces the power wasted during light load conditions. In
no−load conditions, the NPC1217 allows the total standby
power to easily reach next International Energy Agency
(IEA) recommendations.
No Acoustic Noise While Operating: Instead of skipping
cycles at high peak currents, the NCP1217 waits until the
peak current demand falls below a user−adjustable 1/3 of the
maximum limit. As a result, cycle skipping can take place
without having a singing transformer … You can thus select
cheap magnetic components free of noise problems.
External MOSFET Connection: By leaving the external
MOSFET external to the IC, you can select avalanche proof
devices, which in certain cases (e.g. low output powers), let
you work without an active clamping network. Also, by
controlling the MOSFET gate signal flow, you have an
option to slow down the device commutation, therefore
reducing the amount of ElectroMagnetic Interference
(EMI).
SPICE Model: A dedicated model to run transient
cycle−by−cycle simulations is available but also an
averaged version to help you closing the loop. Ready−to−use
templates can be downloaded in OrCAD’s Pspice and
INTUSOFT’s IsSpice from ON Semiconductor web site,
NCP1217 related section.
The NCP1217 implements a standard current mode
architecture where the switch−off event is dictated by the
peak current setpoint. This component represents the ideal
candidate where low part−count is the key parameter,
particularly in low−cost AC/DC adapters, TV power
supplies, etc. Due to its high−performance High−Voltage
technology, the NCP1217 incorporates all the necessary
components normally needed in UC384X based supplies:
timing components, feedback devices, low−pass filter and
startup device but also enhances the original component
by offering: 1) an externally triggerable latchoff
2) ramp compensation and finally, 3) short−circuit
protection. Due to its high−voltage current source,
ON Semiconductor’s NCP1217 does not need an external
startup resistance but supplies the startup current directly
from the high−voltage rail. On the other hand, more and
more applications are requiring low no−load standby power,
e.g. for AC/DC adapters, VCRs, etc. UC384X series have a
lot of difficulty to reduce the switching losses at low power
levels. NCP1217 elegantly solves this problem by skipping
unwanted switching cycles at a user−adjustable power level.
By ensuring that skip cycles take place at low peak current,
the device ensures quiet, noise−free operation:
Current−Mode Operation: As the UC384X series, the
NCP1217 features a well−known current mode control
architecture which provides superior input audio−
susceptibility compared to traditional voltage−mode
controllers. Primary current pulse−by−pulse checking
together with a fast over current comparator offers greater
security in the event of a difficult fault condition, e.g. a
saturating transformer.
Ramp Compensation: By inserting a resistor between the
current−sense (CS) pin and the actual sense resistor, it
becomes possible to inject a given amount of ramp
compensation since the internal saw tooth clock is routed to
the CS pin. Subharmonic oscillations in Continuous
Conduction Mode (CCM) can thus be compensated via a
single resistor.
Adjustable Skip Cycle Level: By offering the ability to
tailor the level at which the skip cycle takes place, the
designer can make sure that the skip operation only occurs
at low peak current. This point guarantees a noise−free
operation with cheap transformers. Skip cycle offers a
proven mean to reduce the standby power in no or light loads
situations.
Wide Switching−Frequency Offer: Three different options
are available: 65 kHz – 100 kHz–133 kHz. Depending on
the application, the designer can pick up the right device to
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8
NCP1217, NCP1217A
Startup Sequence
12.8 V), the current source turns off and no longer wastes
any power. At this time, the VCC capacitor only supplies the
controller and the auxiliary supply is supposed to take over
before VCC collapses below VCCmin. Figure 16 shows the
internal arrangement of this structure.
When the power supply is first powered from the mains
outlet, the internal current source (typically 7.0 mA) is
biased and charges up the VCC capacitor. When the voltage
on this VCC capacitor reaches the VCCON level (typically
8
12.8 V/5.6 V
+
-
HV
6 mA or 0
6
CVCC
Aux
4
Figure 16. The Current Source Brings VCC Above 12.8 V and then Turns Off
level, preventing a bias current to circulate in the
optocoupler LED. As a result, the auxiliary voltage also
decreases because it also operates in Flyback and thus
duplicates the output voltage, providing the leakage
inductance between windings is kept low. To account for this
situation and properly protect the power supply, NCP1217
hosts a dedicated overload detection circuitry. Once
activated, this circuitry imposes to deliver pulses in a burst
manner with a low duty−cycle. The system auto−recovers
when the fault condition disappears.
During the startup phase, the peak current is pushed to the
maximum until the output voltage reaches its target and the
feedback loop takes over. The auxiliary voltage takes place
after a few switching cycles and self−supplies the IC. In
presence of a short circuit on the output, the auxiliary
voltage will go down until it crosses the undervoltage
lockout level of typically 7.6 V. When this happens,
NCP1217 immediately stops the switching pulses and
unbiases all unnecessary logical blocks. The overall
consumption drops, while keeping the gate grounded, and
the VCC slowly falls down. As soon as VCC reaches typically
5.6 V, the startup source turns−on again and a new startup
sequence occurs, bringing VCC toward 12.8 V as an attempt
to restart. If the default has gone, then the power supply
normally restarts. If not, a new protective burst is initiated,
shielding the SMPS from any runaway. Figure 18 portrays
the typical operating signals in short circuit.
Once the power supply has started, the VCC shall be
constrained below 16 V, which is the maximum rating on
Pin 6. Figure 17 portrays a typical startup sequence with a
VCC regulated at 12.5 V.
13.5
12.5
REGULATION
12.8 V
11.5
10.5
9.5
3.00 M
8.00 M
13.0 M
18.0 M
23.0 M
t, TIME (sec)
Figure 17. A Typical Startup Sequence for
the NCP1217
Overload Operation
In applications where the output current is purposely not
controlled (e.g. wall adapters delivering raw DC level), it is
interesting to implement a true short−circuit protection. A
short−circuit actually forces the output voltage to be at a low
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9
NCP1217, NCP1217A
VCCON = 12.8 V
VCCmin = 7.6 V
VCC
VCClatch = 5.6 V
DRIVING PULSES
Figure 18. Typical Waveforms in Short Circuit Conditions
Calculating the VCC Capacitor
The
The VCC capacitor can be calculated knowing the IC
consumption as soon as VCC reaches 12.8 V. Suppose that a
NCP1217P065 is used and drives a MOSFET with a 30 nC
total gate charge (Qg). The total average current is thus
made of ICC1 (750 A) plus the driver current,
Fsw * Qg + 1.95 mA. The total current is therefore 2.7 mA.
The V available to fully startup the circuit (e.g. never reach
the 8.2 V VCCmin during power on) is 13.7−8.2 + 5.5 V
best case or 4.9 V worse case (11.9−7.0) . We have a
capacitor that then needs to supply the NCP1217 with
2.7 mA during a given time until the auxiliary supply takes
over. Suppose that this time was measured at around 15 ms.
CVCC is calculated using the equation C +
C w 8.3 F. Select a 22 F/25 V and this will fit.
theoretical
power
transfer
is
therefore:
1 · Lp · Ip2 · Fsw + 4.1 W. If this IC enters skip cycle
2
mode with a bunch length of 10 ms over a recurrent
period of 100 ms, then the total power transfer is:
4.1 * 0.1 + 410 mW.
To better understand how this skip cycle mode takes place,
a look at the operation mode versus the FB level
immediately gives the necessary insight.
FB
4.2 V, FB Pin Open
3.2 V, Upper
Dynamic Range
NORMAL CURRENT
MODE OPERATION
t · i
or
V
Skipping Cycle Mode
SKIP CYCLE OPERATION
IP(min) = 333 mV/RSENSE
The NCP1217 automatically skips switching cycles when
the output power demand drops below a given level. This is
accomplished by monitoring the FB pin. In normal
operation, pin 2 imposes a peak current accordingly to the
load value. If the load demand decreases, the internal loop
asks for less peak current. When this setpoint reaches a
determined level (Vpin 1), the IC prevents the current from
decreasing further down and starts to blank the output
pulses: the IC enters the so−called skip cycle mode, also
named controlled burst operation. The power transfer now
depends upon the width of the pulse bunches (Figure 20).
Suppose we have the following component values:
1V
Time
Figure 19.
When FB is above the skip cycle threshold (1.0 V by
default), the peak current cannot exceed 1.0 V/Rsense.
When the IC enters the skip cycle mode, the peak current
cannot go below Vpin1/3.3. The user still has the flexibility
to alter this 1.0 V by either shunting pin 1 to ground through
a resistor or raising it through a resistor up to the desired
level. In this later case, care must be taken to keep sufficient
margin between this pin 1 adjustment level and the latchoff
level. Grounding pin 1 permanently invalidates the skip
cycle operation.
Lp, primary inductance = 350 H
Fsw, switching frequency = 65 kHz
Ip skip = 600 mA (or 333 mV/Rsense)
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10
NCP1217, NCP1217A
Power P1
Power P2
Power P3
Figure 20. Output Pulses at Various Power Levels (X = 5.0 ms/div) P1 t P2 t P3
MAX PEAK
CURRENT
300 M
SKIP CYCLE
CURRENT LIMIT
200 M
100 M
0
315.40 U
882.70 U
1.450 M
2.017 M
2.585 M
Figure 21. The Skip Cycle Takes Place at Low Peak Currents which Guarantees Noise−Free Operation
Sufficient margin shall be kept between normal Pin1 level and the latchoff point in order to avoid false triggering.
Ramp Compensation
Continuous Conduction Mode (CCM) with a duty−cycle
greater than 50%. To lower the current loop gain, one usually
injects between 50 and 100% of the inductor down−slope.
Figure 22 depicts how internally the ramp is generated.
Ramp compensation is a known mean to cure
subharmonic oscillations. These oscillations take place at
half the switching frequency and occur only during
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11
NCP1217, NCP1217A
Latching Off the NCP1217
Duty Cycle Typ = 74%
Total latched shutdown can easily be implemented
through a simple PNP bipolar transistor as depicted by
Figure 23. When OFF, Q1 is transparent to the operation.
When forward biased, the transistor pulls the Adj pin toward
VCC and permanently latches−off the IC as soon Vadj goes
above the latching level (typical 3.1 V). Figure 23 shows
how to wire the bipolar transistor to activate the latchoff. A
typical candidate for Q1 could be an MMBT3906 from
ON Semiconductor.
2.9 V
0V
19 k
Rcomp
+
-
L.E.B.
CS
Rsense
VCC
From
Setpoint
Figure 22. Inserting a Resistor in Series with the Current
Sense Information Brings Ramp Compensation
Off
In the NCP1217, the ramp features a swing of 2.9 V with
a duty cycle max at 74%. Over a 65 kHz frequency, for
instance, it corresponds to a 254 mV/s ramp. In our
FLYBACK design, let’s suppose that our primary
inductance Lp is 350 H, delivering 12 V with a Np:Ns ratio
of 1:0.1. The OFF time primary current slope is thus given
by:
(Vout ) Vf) ·
Lp
Np
Ns
Q1
Rlimit
+ 371 mAńs or 37 mVńs when
projected over an Rsense of 0.1 , for instance. If we select
75% of the downslope as the required amount of ramp
compensation, then we shall inject 27 mV/s. Our
internal compensation being of 254 mV/s, the divider
ratio (divratio) between Rcomp and the 19 k is 0.106.
A few lines of algebra to determine Rcomp:
1
8
2
7
3
6
4
5
CVCC
Figure 23. A Simple Bipolar Transistor Totally
Disables the IC
19 k · divratio
+ 2.26 k.
(1−divratio)
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12
NCP1217, NCP1217A
VCC
The startup current source keeps the
device latched until reset occurs.
VCCON = 12.8 V
VCCmin = 7.6 V
VCClatch = 5.6 V
Reset level
Time
Drv
Driver
Pulses
Latched−off
Time
Adj
Default
adj level
Time
Fault brings adj above latching level
Figure 24. When Vadj is Pulled Above 3.1 V, NCP1217 Permanently Latches−Off the Output Pulses
In normal operation, the Adj pin level is kept at a fixed
level, the default one or lower. As soon as some external
signal pulls this Adj pin level above 3.1 V typical, the output
pulses are permanently disabled. Care must be taken to limit
the injected current into pin 1 to less than 2.0 mA, e.g.
through a series resistor of 5.6 k with a 10 V VCC. The
startup switch is activated every time VCC reaches 5.6 V and
maintains a VCC voltage ramping up and down between
5.6 V and 12.8 V. Reset occurs when VCC falls below 5.6 V,
e.g. when the user cycle the SMPS down. Figure 25
illustrates the operation. Adding a zener diode from Q1 base
to ground makes a cheap OVP, protecting the supply from
any lethal open−loop operation. If a thermistor (NTC) is
added in parallel with the Zener−diode, overtemperature
protection is also ensured.
Vaux
OVP
T
1
8
2
7
3
6
4
5
t16 V
CVCC
Laux
Figure 25. A Thermistor and a Zener Diode Offer
Both OVP and Overtemperature Latched−Off
Protection
Nonlatching Shutdown
In some cases, it might be desirable to shut off the part
temporarily and authorize its restart once the default has
disappeared. This option can easily be accomplished
through a single NPN bipolar transistor wired between FB
and ground. By pulling FB below the Adj Pin 1 level, the
output pulses are disabled as long as FB is pulled below
Pin 1. As soon as FB is relaxed, the IC resumes its operation.
Figure 26 depicts the application example.
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13
NCP1217, NCP1217A
ON/OFF
Q1
1
8
2
7
3
6
4
5
internal parasitic SCRs are triggered, engendering
irremediable damages to the IC if a low impedance path is
offered between VCC and GND. If the current sense pin is
often the seat of such spurious signals, the high−voltage pin
can also be the source of problems in certain circumstances.
During the turn−off sequence, e.g. when the user unplugs the
power supply, the controller is still fed by its VCC capacitor
and keeps activating the MOSFET ON and OFF with a peak
current limited by Rsense. Unfortunately, if the quality
coefficient Q of the resonating network formed by Lp and
Cbulk is low (e.g. the MOSFET Rdson + Rsense are small),
conditions are met to make the circuit resonate and thus
negatively bias the controller. Since we are talking about ms
pulses, the amount of injected charge (Q = I * t) immediately
latches the controller that brutally discharges its VCC
capacitor. If this VCC capacitor is of sufficient value, its
stored energy damages the controller. Figure 27 depicts a
typical negative shot occurring on the HV pin where the
brutal VCC discharge testifies for latchup.
Figure 26. Another Way of Shutting Down the IC
Without a Definitive Latchoff State
Protecting the Controller Against Negative Spikes
As with any controller built upon a CMOS technology, it
is the designer’s duty to avoid the presence of negative
spikes on sensitive pins. Negative signals have the bad habit
to forward bias the controller substrate and induce erratic
behaviors. Sometimes, the injection can be so strong that
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14
NCP1217, NCP1217A
Vcc 5 V/DIV
Vlatch 1 V/DIV
Time 10 ms/DIV
Figure 27. A Negative Spike Takes Place on the Bulk Capacitor at the Switch−Off Sequence
Another option (Figure 29) consists in wiring a diode
from VCC to the bulk capacitor to force VCC to reach
VCCON sooner and thus stops the switching activity before
the bulk capacitor gets deeply discharged. For security
reasons, two diodes can be connected in series.
Simple and inexpensive cures exist to prevent from
internal parasitic SCR activation. One of them consists in
inserting a resistor in series with the high−voltage pin to
keep the negative current to the lowest when the bulk
becomes negative (Figure 28). Please note that the negative
spike is clamped to (−2*Vf) thanks to the diode bridge. Also,
the power dissipation of this resistor is extremely small since
it only heats up during the startup sequence.
3
Rbulk
u4.7 k
+
Cbulk
1
8
2
7
3
6
4
5
+
2
1
+
CVCC
Figure 28. A simple resistor in series avoids any
latch−up in the controller . . .
Cbulk
1
8
2
7
3
6
4
5
3
D3
1N4007
1
+
CVCC
Figure 29. . . . or one diode forces VCC to reach
VCCON sooner.
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15
NCP1217, NCP1217A
Soft−Start (NCP1217A only)
also activated during the Over Current Burst (OCP)
sequence. Every restart attempt is followed by a soft−start
activation. Generally speaking, the soft−start will be
activated when VCC ramps up either from zero (fresh
power−on sequence) or 5.6 V, the latchoff voltage occurring
during OCP. Figure 30 portrays the soft−start behavior. The
time scales are purposely shifted to offer a better zoom
portion.
The NCP1217A features an internal 1.0 ms soft−start
activated during the power on sequence (PON). As soon as
VCC reaches VCCOFF, the peak current is gradually
increased from nearly zero up to the maximum clamping
level (e.g. 1.0 V). This situation lasts during 1.0 ms and
further to that time period, the peak current limit is blocked
to 1.0 V until the supply enters regulation. The soft−start is
Figure 30. Soft−start is activated during a startup sequence or an OCP condition
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16
NCP1217, NCP1217A
ORDERING INFORMATION
Version
Marking
Package
Shipping†
NCP1217D65R2G
65 kHz
17D06
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217D100R2G
100 kHz
17D10
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217D133R2G
133 kHz
17D13
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217P65G
65 kHz
P1217P065
PDIP−7
(Pb−Free)
50 Units / Rail
NCP1217P100G
100 kHz
P1217P100
PDIP−7
(Pb−Free)
50 Units / Rail
NCP1217P133G
133 kHz
N1217P133
PDIP−7
(Pb−Free)
50 Units / Rail
NCP1217AD65R2G
65 kHz
17A06
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217AD100R2G
100 kHz
17A10
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217AD133R2G
133 kHz
17A13
SO−8
(Pb−Free)
2500 / Tape & Reel
NCP1217AP65G
65 kHz
1217AP06
PDIP−7
(Pb−Free)
50 Units / Rail
NCP1217AP100G
100 kHz
P1217AP10
PDIP−7
(Pb−Free)
50 Units / Rail
NCP1217AP133G
133 kHz
1217AP13
PDIP−7
(Pb−Free)
50 Units / Rail
Device
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specification Brochure, BRD8011/D.
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17
NCP1217, NCP1217A
PACKAGE DIMENSIONS
SOIC−8 NB
CASE 751−07
ISSUE AK
−X−
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.
6. 751−01 THRU 751−06 ARE OBSOLETE. NEW
STANDARD IS 751−07.
A
8
5
S
B
0.25 (0.010)
M
Y
M
1
4
−Y−
K
G
C
N
DIM
A
B
C
D
G
H
J
K
M
N
S
X 45 _
SEATING
PLANE
−Z−
0.10 (0.004)
H
D
0.25 (0.010)
M
Z Y
S
X
M
J
S
SOLDERING FOOTPRINT*
1.52
0.060
7.0
0.275
4.0
0.155
0.6
0.024
1.270
0.050
SCALE 6:1
mm Ǔ
ǒinches
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
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18
MILLIMETERS
MIN
MAX
4.80
5.00
3.80
4.00
1.35
1.75
0.33
0.51
1.27 BSC
0.10
0.25
0.19
0.25
0.40
1.27
0_
8_
0.25
0.50
5.80
6.20
INCHES
MIN
MAX
0.189
0.197
0.150
0.157
0.053
0.069
0.013
0.020
0.050 BSC
0.004
0.010
0.007
0.010
0.016
0.050
0 _
8 _
0.010
0.020
0.228
0.244
NCP1217, NCP1217A
PACKAGE DIMENSIONS
PDIP−7 (PDIP−8 LESS PIN 7)
P SUFFIX
CASE 626B
ISSUE C
D
A
E
H
8
5
E1
1
4
NOTE 8
b2
c
B
END VIEW
TOP VIEW
WITH LEADS CONSTRAINED
NOTE 5
A2
A
e/2
NOTE 3
L
SEATING
PLANE
A1
C
D1
M
e
8X
SIDE VIEW
b
0.010
eB
END VIEW
M
C A
M
B
M
NOTES:
1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994.
2. CONTROLLING DIMENSION: INCHES.
3. DIMENSIONS A, A1 AND L ARE MEASURED WITH THE PACKAGE SEATED IN JEDEC SEATING PLANE GAUGE GS−3.
4. DIMENSIONS D, D1 AND E1 DO NOT INCLUDE MOLD FLASH
OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS ARE
NOT TO EXCEED 0.10 INCH.
5. DIMENSION E IS MEASURED AT A POINT 0.015 BELOW DATUM
PLANE H WITH THE LEADS CONSTRAINED PERPENDICULAR
TO DATUM C.
6. DIMENSION E3 IS MEASURED AT THE LEAD TIPS WITH THE
LEADS UNCONSTRAINED.
7. DATUM PLANE H IS COINCIDENT WITH THE BOTTOM OF THE
LEADS, WHERE THE LEADS EXIT THE BODY.
8. PACKAGE CONTOUR IS OPTIONAL (ROUNDED OR SQUARE
CORNERS).
DIM
A
A1
A2
b
b2
C
D
D1
E
E1
e
eB
L
M
INCHES
MIN
MAX
−−−−
0.210
0.015
−−−−
0.115 0.195
0.014 0.022
0.060 TYP
0.008 0.014
0.355 0.400
0.005
−−−−
0.300 0.325
0.240 0.280
0.100 BSC
−−−−
0.430
0.115 0.150
−−−−
10 °
MILLIMETERS
MIN
MAX
−−−
5.33
0.38
−−−
2.92
4.95
0.35
0.56
1.52 TYP
0.20
0.36
9.02
10.16
0.13
−−−
7.62
8.26
6.10
7.11
2.54 BSC
−−−
10.92
2.92
3.81
−−−
10 °
NOTE 6
ON Semiconductor and the
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC) or its subsidiaries in the United States and/or other countries.
SCILLC owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of SCILLC’s product/patent coverage may be accessed
at www.onsemi.com/site/pdf/Patent−Marking.pdf. SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation
or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets
and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each
customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended,
or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which
the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or
unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and
expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim
alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable
copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
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Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
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Phone: 81−3−5817−1050
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19
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
For additional information, please contact your local
Sales Representative
NCP1217/D