EL2227 ® Data Sheet May 1, 2007 Dual Very Low Noise Amplifier Features The EL2227 is a dual, low-noise amplifier, ideally suited to line receiving applications in ADSL and HDSLII designs. With low noise specification of just 1.9nV/√Hz and 1.2pA/√Hz, the EL2227 is perfect for the detection of very low amplitude signals. • Voltage noise of only 1.9nV/√Hz The EL2227 features a -3dB bandwidth of 115MHz and is gain-of-2 stable. The EL2227 also affords minimal power dissipation with a supply current of just 4.8mA per amplifier. The amplifier can be powered from supplies ranging from ±2.5V to ±12V. • Just 4.8mA per amplifier FN7058.3 • Current noise of only 1.2pA/√Hz • Bandwidth (-3dB) of 115MHz @AV = +2 • Gain-of-2 stable • 8 Ld MSOP package • ±2.5V to ±12V operation • Pb-free plus anneal available (RoHS compliant) The EL2227 is available in a space-saving 8 Ld MSOP package as well as the industry-standard 8 Ld SOIC. It can operate over the -40°C to +85°C temperature range. Applications Pinout • HDSLII receivers • ADSL receivers • Ultrasound input amplifiers EL2227 (8 LD SOIC, 8 LD MSOP) TOP VIEW • Wideband instrumentation • Communications equipment VOUTA 1 VINA- 2 VINA+ 3 - 8 VS+ 7 VOUTB 6 VINB- 5 VINB+ • AGC and PLL active filters • Wideband sensors + + VS- 4 . Ordering Information PART MARKING PART NUMBER EL2227CY L TEMP RANGE (°C) TAPE AND REEL -40 to +85 - PACKAGE 8 Ld MSOP (3.0mm) PKG. DWG.# MDP0043 EL2227CY-T13 L -40 to +85 13” 8 Ld MSOP (3.0mm) MDP0043 EL2227CY-T7 L -40 to +85 7” 8 Ld MSOP (3.0mm) MDP0043 EL2227CYZ (Note) BASAA -40 to +85 - 8 Ld MSOP (3.0mm) (Pb-free) MDP0043 EL2227CYZ-T13 (Note) BASAA -40 to +85 13” 8 Ld MSOP (3.0mm) (Pb-free) MDP0043 EL2227CYZ-T7 (Note) BASAA -40 to +85 7” 8 Ld MSOP (3.0mm) (Pb-free) MDP0043 EL2227CS 2227CS -40 to +85 - 8 Ld SOIC (150 mil) MDP0027 EL2227CS-T13 2227CS -40 to +85 13” 8 Ld SOIC (150 mil) MDP0027 EL2227CS-T7 2227CS -40 to +85 7” 8 Ld SOIC (150 mil) MDP0027 EL2227CSZ (Note) 2227CSZ -40 to +85 - 8 Ld SOIC (150 mil) (Pb-free) MDP0027 EL2227CSZ-T13 (Note) 2227CSZ -40 to +85 13” 8 Ld SOIC (150 mil) (Pb-free) MDP0027 EL2227CSZ-T7 (Note) 2227CSZ -40 to +85 7” 8 Ld SOIC (150 mil) (Pb-free) MDP0027 NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2004, 2005, 2007. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL2227 Absolute Maximum Ratings Thermal Information Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . .28V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . VS- - 0.3V, VS +0.3V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 40mA Maximum Die Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C ESD Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2kV Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pb-free reflow profile . . . . . . . . . . . . . . . . . . . . . . . . . .see link below http://www.intersil.com/pbfree/Pb-FreeReflow.asp CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications VS+ = +12V, VS- = -12V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C Unless Otherwise Specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT -0.2 3 mV INPUT CHARACTERISTICS VOS Input Offset Voltage TCVOS Average Offset Voltage Drift IB Input Bias Current RIN VCM = 0V -0.6 µV/°C -3.4 µA Input Impedance 7.3 MΩ CIN Input Capacitance 1.6 pF CMIR Common-Mode Input Range CMRR Common-Mode Rejection Ratio for VIN from -11.8V to 10.4V 60 94 dB AVOL Open-Loop Gain -5V ≤ VOUT ≤ 5V 70 87 dB eN Voltage Noise f = 100kHz 1.9 nV/√Hz iN Current Noise f = 100kHz 1.2 pA/√Hz RL = 500Ω -10.4 -10 V RL = 250Ω -9.8 -9 V VCM = 0V -9 -11.8 +10.4 V OUTPUT CHARACTERISTICS VOL Output Swing Low VOH Output Swing High RL = 500Ω RL = 250Ω 9.5 10 V ISC Short Circuit Current RL = 10Ω 140 180 mA 65 95 dB 10 10.4 V POWER SUPPLY PERFORMANCE PSRR Power Supply Rejection Ratio VS is moved from ±2.25V to ±12V IS Supply Current (Per Amplifier) No Load VS Operating Range 4.8 ±2.5 6.5 mA ±12 V DYNAMIC PERFORMANCE SR Slew Rate (Note 2) ±2.5V square wave, measured 25% to 75% 50 V/µS tS Settling to 0.1% (AV = +2) (AV = +2), VO = ±1V 65 ns BW -3dB Bandwidth RF = 358Ω 115 MHz HD2 2nd Harmonic Distortion f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 93 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 83 dBc f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 94 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 76 dBc HD3 3rd Harmonic Distortion 2 40 FN7058.3 May 1, 2007 EL2227 Electrical Specifications VS+ = +12V, VS- = -12V, RL = 500Ω and CL = 3pF to 0V, RF = RG = 620Ω, and TA = +25°C Unless Otherwise Specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT 0.2 3 mV INPUT CHARACTERISTICS VOS Input Offset Voltage TCVOS Average Offset Voltage Drift IB Input Bias Current RIN VCM = 0V -0.6 µV/°C -3.7 µA Input Impedance 7.3 MΩ CIN Input Capacitance 1.6 pF CMIR Common-Mode Input Range CMRR Common-Mode Rejection Ratio for VIN from -4.8V to 3.4V 60 97 dB AVOL Open-Loop Gain -5V ≤ VOUT ≤ 5V 70 84 dB eN Voltage Noise f = 100kHz 1.9 nV/√Hz iN Current Noise f = 100kHz 1.2 pA/√Hz RL = 500Ω -3.8 -3.5 V RL = 250Ω -3.7 -3.5 V VCM = 0V -9 -4.8 3.4 V OUTPUT CHARACTERISTICS VOL VOH ISC Output Swing Low Output Swing High Short Circuit Current RL = 500Ω 3.5 3.7 V RL = 250Ω 3.5 3.6 V RL = 10Ω 60 100 mA 65 95 dB POWER SUPPLY PERFORMANCE PSRR Power Supply Rejection Ratio VS is moved from ±2.25V to ±12V IS Supply Current (Per Amplifier) No Load VS Operating Range 4.5 ±2.5 5.5 mA ±12 V DYNAMIC PERFORMANCE SR Slew Rate ±2.5V square wave, measured 25%-75% tS Settling to 0.1% (AV = +2) BW HD2 HD3 45 V/µS (AV = +2), VO = ±1V 77 ns -3dB Bandwidth RF = 358Ω 90 MHz 2nd Harmonic Distortion f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 98 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 90 dBc f = 1MHz, VO = 2VP-P, RL = 500Ω, RF = 358Ω 94 dBc f = 1MHz, VO = 2VP-P, RL = 150Ω, RF = 358Ω 79 dBc 3rd Harmonic Distortion 3 35 FN7058.3 May 1, 2007 EL2227 4 4 3 3 2 2 RF = 1kΩ 1 RF = 620Ω 0 -1 RF = 100Ω -2 RF = 350Ω -3 -4 -5 VS = ±12V AV = +2 RL = 500Ω -6 1M NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) Typical Performance Curves 0 -1 RF = 420Ω -2 RF = 620Ω -3 -4 -6 1M 100M 200M RF = 350Ω 1 -5 10M RF = 100Ω RF = 1kΩ VS = ±12V AV = -1 RL = 500Ω 10M FIGURE 2. INVERTING FREQUENCY RESPONSE FOR VARIOUS RF 4 4 3 3 2 AV = 2 0 -1 AV = 10 AV = 5 -2 -3 -4 -5 -6 1M VS = ±12V RF = 350Ω RL = 500Ω NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) FIGURE 1. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS RF 1 2 AV = -10 -2 AV = -5 -3 -4 VS = ±12V RF = 420Ω RL = 500Ω 10M FREQUENCY (Hz) 135 90 90 45 AV = 5 -45 AV = 10 -135 -270 -315 1M -45 AV = -10 -90 AV = -2 AV = -5 -135 -180 -180 -225 AV = -1 0 AV = 2 PHASE (°) PHASE (°) FIGURE 4. INVERTING FREQUENCY RESPONSE (GAIN) 135 -90 100M 200M FREQUENCY (Hz) FIGURE 3. NON-INVERTING FREQUENCY RESPONSE (GAIN) 0 AV = -1 0 -1 -6 1M 100M 200M AV = -2 1 -5 10M 45 100M 200M FREQUENCY (Hz) FREQUENCY (Hz) -225 VS = ±12 RF = 350Ω RL = 500Ω -270 10M 100M 200M FREQUENCY (Hz) FIGURE 5. NON-INVERTING FREQUENCY RESPONSE (PHASE) 4 -315 1M VS = ±12V RF = 420Ω RL = 500Ω 10M 100M 200M FREQUENCY (Hz) FIGURE 6. INVERTING FREQUENCY RESPONSE (PHASE) FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) NORMALIZED GAIN (dB) 3 2 1 4 VS = ±12V RF = 350Ω AV = +2 RL = 500Ω 3 VIN = 100mVPP VIN = 20mVPP 0 -1 VIN = 500mVPP -2 VIN = 1VPP -3 -4 VIN = 2VPP -5 -6 100k NORMALIZED GAIN (dB) 4 2 VIN = 1.4VPP 1 0 -1 VIN = 2.8VPP -2 VIN = 280mVPP -3 -4 -5 1M 10M -6 1M 100M VS ±12V RF = 420Ω RL = 500Ω AV = -1 10M FREQUENCY (Hz) FIGURE 8. INVERTING FREQUENCY RESPONSE FOR VARIOUS INPUT SIGNAL LEVELS 5 4 3 CL = 12pF 2 1 0 CL = 2pF -1 -4 -5 1M CL = 30pF 3 CL = 30pF NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 -3 VVSS=±12 = ±12V VRF = 620Ω R RFL=620 = 500Ω Ω AV = +2 2 CL = 12pF 1 0 -1 CL = 2pF -2 -3 VS ± 12V R F= 420Ω RL = 500Ω AV = -1 -4 -5 10M -6 1M 100M 200M 10M FREQUENCY (Hz) FIGURE 10. INVERTING FREQUENCY RESPONSE FOR VARIOUS CL 4 4 RL = 500Ω 1 0 RL = 50Ω -1 -2 -5 -6 1M VS = ±12V RF = 620Ω CL = 15pF AV = +2 NORMALIZED GAIN (dB) NorMalized GAIN (dB) 2 -4 VO = +10V 3 3 RL = 100Ω 100M 200M FREQUENCY (Hz) FIGURE 11. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS RL 5 VO = -10V 2 VO = +5V 1 0 -1 VO = 0V -2 -3 -4 -5 10M 100M 200M FREQUENCY (Hz) FIGURE 9. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS CL -3 100M 200M FREQUENCY (Hz) FIGURE 7. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS INPUT SIGNAL LEVELS -2 VIN = 20mVPP VO = -5V VS = ±12V RF = 620Ω RL = 500Ω AV = +2 -6 100k 1M 10M 100M FREQUENCY (Hz) FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS OUTPUT DC LEVELS FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) 140 AV = +2 RF = 620Ω RL = 500Ω AV = -1 AV = +2 80 A V= -2 60 40 A = +5 V AV = -5 AV = +10 AV = +2 RF = 620Ω RL = 500Ω AV = -1 2.5 2 AV = +10 AV = -10 1.5 1 20 0 AV = +2 3 100 PEAKING (dB) 3dB BANDWIDTH (MHz) 120 4 3.5 AV = +5 0.5 AV = -10 2 4 6 8 10 12 0 2 SUPPLY VOLTAGE (±V) 4 6 AV = -2 AV = -5 8 10 12 SUPPLY VOLTAGE (±V) FIGURE 13. 3dB BANDWIDTH vs SUPPLY VOLTAGE FIGURE 14. PEAKING vs SUPPLY VOLTAGE RF = 620Ω AV = 2 RL = 500Ω 0.5V/DIV RF = 620Ω AV = 2 RL = 500Ω 0.5V/DIV 100ns/DIV 100ns/DIV FIGURE 15. LARGE SIGNAL STEP RESPONSE (VS = ±12V) FIGURE 16. LARGE SIGNAL STEP RESPONSE (VS = ±2.5V) RF = 620Ω AV = 2 RL = 500Ω 20mV/DIV RF = 620Ω AV = 2 RL = 500Ω 20mV/DIV 100ns/DIV FIGURE 17. SMALL SIGNAL STEP RESPONSE (VS = ±12V) 6 100ns/DIV FIGURE 18. SMALL SIGNAL STEP RESPONSE (VS = ±2.5V) FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) 10 0.1 8 GROUP DELAY (ns) 0.08 AV = 5V 6 2 dG (%) OR dP (°) 4 AV = 2V 0 -2 -4 VS = ±12V RF = 620Ω RL = 500Ω PIN = -20dBm into 50Ω -6 -8 -10 1M 0.04 AV = 2 RF = 620Ω RL = 150Ω fO = 3.58MHz dP 0.02 0 -0.02 -1 100M 10M 0.06 dG -0.5 FREQUENCY (Hz) FIGURE 19. GROUP DELAY vs FREQUENCY OUTPUT IMPEDANCE (Ω) SUPPLY CURRENT (mA) 1 100 1.2/DIV 6 1.2/DIV 0 6 10 1 0.1 0.01 10k 12 1M 100k 10M 100M FREQUENCY (Hz) SUPPLY VOLTAGE (±V) FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE FIGURE 22. CLOSED LOOP OUTPUT IMPEDANCE vs FREQUENCY 110 0 90 20 PSRR (dB) -CMRR (dB) 0.5 FIGURE 20. DIFFERENTIAL GAIN/PHASE vs DC INPUT VOLTAGE AT 3.58MHz 12 0 0 DC INPUT VOLTAGE (V) 70 50 30 40 VS- 60 VS+ 80 VS = ±12 10 10 100 1k 10k 100k 1M 10M 100M 100 1k 10k 100k 1M FREQUENCY (Hz) FREQUENCY (Hz) FIGURE 23. CMRR FIGURE 24. PSRR 7 10M 100M FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) -40 2nd H -60 -70 3rd H -80 -70 2nd H -80 3rd H -90 -90 -100 AV = 2 RF = 358Ω RL = 500Ω -60 DISTORTION (dBc) -50 DISTORTION (dBc) -50 AV = 2 RF = 620Ω RL = 500Ω 0 4 8 12 16 -100 20 0 OUTPUT SWING (VPP) -60 -70 -70 THD (dBc) THD (dBc) -100 RL = 500 10 RL = 50 RL = 500 -100 -110 100 1000 1 10 100 1000 FREQUENCY (kHz) FREQUENCY (kHz) FIGURE 27. TOTAL HARMONIC DISTORTION vs FREQUENCY @ 2VPP VS = ±12V FIGURE 28. TOTAL HARMONIC DISTORTION vs FREQUENCY @ 2VPP VS = ±2.5V 10 0 9 8 7 -20 A→B IN GAIN (dB) VOLTAGE NOISE (nV/√Hz), CURRENT NOISE (pA/√Hz) 2.5 -90 -120 1 2 -80 RL = 50 -90 -120 1.5 FIGURE 26. 1MHz 2nd and 3rd HARMONIC DISTORTION vs OUTPUT SWING FOR VS = ±2.5V -60 -110 1 OUTPUT SWING (VPP) FIGURE 25. 1MHz 2nd and 3rd HARMONIC DISTORTION vs OUTPUT SWING FOR VS = ±12V -80 0.5 6 5 4 3 EN B→A -60 -80 2 1 10 -40 100 1k 10k 100k FREQUENCY (Hz) FIGURE 29. VOLTAGE AND CURRENT NOISE vs FREQUENCY 8 -100 100k 1M 10M 100M FREQUENCY (Hz) FIGURE 30. CHANNEL TO CHANNEL ISOLATION vs FREQUENCY FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) 150 10 130 9.5 120 IS (mA) -3dB BANDWIDTH (MHz) 140 110 9 100 90 80 -40 -20 0 20 40 60 80 8.5 -50 100 120 140 DIE TEMPERATURE (°C) 0 50 100 150 DIE TEMPERATURE (°C) FIGURE 31. -3dB BANDWIDTH vs TEMPERATURE FIGURE 32. SUPPLY CURRENT vs TEMPERATURE -2 2 -3 VOS (mV) IBIAS (µA) 0 -4 -2 -5 -4 -50 0 50 100 -6 -50 150 55 150 160 140 SETTLING TIME (ns) 53 SLEW RATE (V/µs) 100 50 FIGURE 34. INPUT BIAS CURRENT vs TEMPERATURE FIGURE 33. VOS vs TEMPERATURE 51 49 47 120 0 50 100 150 DIE TEMPERATURE (°C) FIGURE 35. SLEW RATE vs TEMPERATURE 9 VS = ±2.5V VO = 2VPP VS = ±12V VO = 5VPP 100 80 60 40 20 45 -50 0 DIE TEMPERATURE (°C) DIE TEMPERATURE (°C) 0 0.01 VS = ±12V VO = 2VPP 0.1 1 ACCURACY (%) FIGURE 36. SETTLING TIME vs ACCURACY FN7058.3 May 1, 2007 EL2227 Typical Performance Curves (Continued) 0.9 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 781mW POWER DISSIPATION (W) 0.8 0.7 θ JA = 607mW 0.6 0.5 θJ 0.4 A= 0.3 MS OP 8 +2 06 °C /W SO 8 +1 60 °C /W 0.2 0.1 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 37. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE Pin Descriptions EL2227CY 8-PIN MSOP EL2227CS 8-PIN SO PIN NAME PIN FUNCTION 1 1 VOUTA Output EQUIVALENT CIRCUIT VS+ VOUT Circuit 1 2 2 VINA- Input VS+ VIN+ VIN- VS- Circuit 2 3 3 VINA+ Input 4 4 VS- Supply 5 5 VINB+ Input 6 6 VINB- Input Reference Circuit 2 7 7 VOUTB Output Reference Circuit 1 8 8 VS+ Supply 10 Reference Circuit 2 FN7058.3 May 1, 2007 EL2227 Applications Information +12V Product Description 1k The EL2227 is a dual voltage feedback operational amplifier designed especially for DMT ADSL and other applications requiring very low voltage and current noise. It also features low distortion while drawing moderately low supply current and is built on Elantec's proprietary high-speed complementary bipolar process. The EL2227 use a classical voltage-feedback topology which allows them to be used in a variety of applications where current-feedback amplifiers are not appropriate because of restrictions placed upon the feedback element used with the amplifier. The conventional topology of the EL2227 allows, for example, a capacitor to be placed in the feedback path, making it an excellent choice for applications such as active filters, sample-and-holds, or integrators. ADSL CPE Applications The low noise EL2227 amplifier is specifically designed for the dual differential receiver amplifier function with ADSL transceiver hybrids as well as other low-noise amplifier applications. A typical ADSL CPE line interface circuit is shown in Figure 38. The EL2227 is used in receiving DMT down stream signal. With careful transceiver hybrid design and the EL2227 1.9nV/√Hz voltage noise and 1.2pA/√Hz current noise performance, -140dBm/Hz system background noise performance can be easily achieved. DRIVER INPUT + - ROUT LINE + RF RG ZLINE RF ROUT + LINE RF RECEIVE OUT + RECEIVE AMPLIFIERS RECEIVE OUT - + + RF 1µF 10k 10k 1k + - 1µF 4.7µF 1k 75k FIGURE 39. Power Dissipation With the wide power supply range and large output drive capability of the EL2227, it is possible to exceed the +150°C maximum junction temperatures under certain load and power-supply conditions. It is therefore important to calculate the maximum junction temperature (TJMAX) for all applications to determine if power supply voltages, load conditions, or package type need to be modified for the EL2227 to remain in the safe operating area. These parameters are related as follows: T JMAX = T MAX + ( θ JA × PD MAXTOTAL ) (EQ. 1) where: PDMAXTOTAL is the sum of the maximum power dissipation of each amplifier in the package (PDMAX) PDMAX for each amplifier can be calculated as follows: V OUTMAX PD MAX = 2 × V S × I SMAX + ( V S – V OUTMAX ) × ---------------------------RL (EQ. 2) R RIN where: TMAX = Maximum Ambient Temperature R RIN FIGURE 38. TYPICAL LINE INTERFACE CONNECTION θJA = Thermal Resistance of the Package PDMAX = Maximum Power Dissipation of 1 Amplifier VS = Supply Voltage Disable Function The EL2227 is in the standard dual amplifier package without the enable/disable function. A simple way to implement the enable/disable function is depicted below. When disabled, both the positive and negative supply voltages are disconnected (see Figure 39) IMAX = Maximum Supply Current of 1 Amplifier VOUTMAX = Maximum Output Voltage Swing of the Application RL = Load Resistance To serve as a guide for the user, we can calculate maximum allowable supply voltages for the example of the video cable-driver below since we know that TJMAX = +150°C, TMAX = +75°C, ISMAX = 9.5mA, and the package θJAs are shown in Table 1. If we assume (for this example) that we are driving a back-terminated video cable, then the 11 FN7058.3 May 1, 2007 EL2227 maximum average value (over duty-cycle) of VOUTMAX is 1.4V, and RL = 150Ω, giving the results seen in Table 1. TABLE 1. θJA MAX PDISS @ TMAX PART PACKAGE EL2227CS SO8 160°C/W 0.406W @ +85°C EL2227CY MSOP8 206°C/W 0.315W @ +85°C MAX VS Single-Supply Operation The EL2227 have been designed to have a wide input and output voltage range. This design also makes the EL2227 an excellent choice for single-supply operation. Using a single positive supply, the lower input voltage range is within 200mV of ground (RL = 500Ω), and the lower output voltage range is within 875mV of ground. Upper input voltage range reaches 3.6V, and output voltage range reaches 3.8V with a 5V supply and RL = 500Ω. This results in a 2.625V output swing on a single 5V supply. This wide output voltage range also allows single-supply operation with a supply voltage as high as 28V. Printed-Circuit Layout The EL2227 are well behaved, and easy to apply in most applications. However, a few simple techniques will help assure rapid, high quality results. As with any high-frequency device, good PCB layout is necessary for optimum performance. Ground-plane construction is highly recommended, as is good power supply bypassing. A 0.1µF ceramic capacitor is recommended for bypassing both supplies. Lead lengths should be as short as possible, and bypass capacitors should be as close to the device pins as possible. For good AC performance, parasitic capacitances should be kept to a minimum at both inputs and at the output. Resistor values should be kept under 5kW because of the RC time constants associated with the parasitic capacitance. Metal-film and carbon resistors are both acceptable, use of wire-wound resistors is not recommended because of their parasitic inductance. Similarly, capacitors should be low-inductance for best performance. Gain-Bandwidth Product and the -3dB Bandwidth The EL2227 have a gain-bandwidth product of 137MHz while using only 5mA of supply current per amplifier. For gains greater than 2, their closed-loop -3dB bandwidth is approximately equal to the gain-bandwidth product divided by the noise gain of the circuit. For gains less than 2, higherorder poles in the amplifiers' transfer function contribute to even higher closed loop bandwidths. For example, the EL2227 have a -3dB bandwidth of 115MHz at a gain of +2, dropping to 28MHz at a gain of +5. It is important to note that the EL2227 have been designed so that this “extra” bandwidth in low-gain applications does not come at the expense of stability. As seen in the typical performance curves, the EL2227 in a gain of +2 only exhibit 0.5dB of peaking with a 1000Ω load. Output Drive Capability The EL2227 have been designed to drive low impedance loads. They can easily drive 6VP-P into a 500Ω load. This high output drive capability makes the EL2227 an ideal choice for RF, IF and video applications. 12 FN7058.3 May 1, 2007 EL2227 Small Outline Package Family (SO) A D h X 45° (N/2)+1 N A PIN #1 I.D. MARK E1 E c SEE DETAIL “X” 1 (N/2) B L1 0.010 M C A B e H C A2 GAUGE PLANE SEATING PLANE A1 0.004 C 0.010 M C A B L b 0.010 4° ±4° DETAIL X MDP0027 SMALL OUTLINE PACKAGE FAMILY (SO) INCHES SYMBOL SO-14 SO16 (0.300”) (SOL-16) SO20 (SOL-20) SO24 (SOL-24) SO28 (SOL-28) TOLERANCE NOTES A 0.068 0.068 0.068 0.104 0.104 0.104 0.104 MAX - A1 0.006 0.006 0.006 0.007 0.007 0.007 0.007 ±0.003 - A2 0.057 0.057 0.057 0.092 0.092 0.092 0.092 ±0.002 - b 0.017 0.017 0.017 0.017 0.017 0.017 0.017 ±0.003 - c 0.009 0.009 0.009 0.011 0.011 0.011 0.011 ±0.001 - D 0.193 0.341 0.390 0.406 0.504 0.606 0.704 ±0.004 1, 3 E 0.236 0.236 0.236 0.406 0.406 0.406 0.406 ±0.008 - E1 0.154 0.154 0.154 0.295 0.295 0.295 0.295 ±0.004 2, 3 e 0.050 0.050 0.050 0.050 0.050 0.050 0.050 Basic - L 0.025 0.025 0.025 0.030 0.030 0.030 0.030 ±0.009 - L1 0.041 0.041 0.041 0.056 0.056 0.056 0.056 Basic - h 0.013 0.013 0.013 0.020 0.020 0.020 0.020 Reference - 16 20 24 28 Reference - N SO-8 SO16 (0.150”) 8 14 16 Rev. M 2/07 NOTES: 1. Plastic or metal protrusions of 0.006” maximum per side are not included. 2. Plastic interlead protrusions of 0.010” maximum per side are not included. 3. Dimensions “D” and “E1” are measured at Datum Plane “H”. 4. Dimensioning and tolerancing per ASME Y14.5M-1994 13 FN7058.3 May 1, 2007 EL2227 Mini SO Package Family (MSOP) 0.25 M C A B D MINI SO PACKAGE FAMILY (N/2)+1 N E MDP0043 A E1 MILLIMETERS PIN #1 I.D. 1 B (N/2) e H C SEATING PLANE 0.10 C N LEADS SYMBOL MSOP8 MSOP10 TOLERANCE NOTES A 1.10 1.10 Max. - A1 0.10 0.10 ±0.05 - A2 0.86 0.86 ±0.09 - b 0.33 0.23 +0.07/-0.08 - c 0.18 0.18 ±0.05 - D 3.00 3.00 ±0.10 1, 3 E 4.90 4.90 ±0.15 - E1 3.00 3.00 ±0.10 2, 3 e 0.65 0.50 Basic - L 0.55 0.55 ±0.15 - L1 0.95 0.95 Basic - N 8 10 Reference - 0.08 M C A B b Rev. D 2/07 NOTES: 1. Plastic or metal protrusions of 0.15mm maximum per side are not included. L1 2. Plastic interlead protrusions of 0.25mm maximum per side are not included. A 3. Dimensions “D” and “E1” are measured at Datum Plane “H”. 4. Dimensioning and tolerancing per ASME Y14.5M-1994. c SEE DETAIL "X" A2 GAUGE PLANE L A1 0.25 3° ±3° DETAIL X All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 14 FN7058.3 May 1, 2007