LTM4630-1 Dual 18A or Single 36A µModule Regulator with 0.8% DC and 3% Transient Accuracy FEATURES DESCRIPTION ±0.8% Maximum Total DC Output Error Over Line, Load and Temperature (LTM4630-1A) nn ±3% Transient Output Error with Minimum Output Capacitance nn Dual 18A or Single 36A Output nn 4.5V to 15V Input, 0.6V to 1.8V Output Voltage Range nn Differential Remote Sense Amplifier nn Current Mode Control/Fast Transient Response nn Current Sharing Up to 144A nn 16mm × 16mm × 5.01mm BGA Package The LTM®4630-1A/LTM4630-1B are dual 18A or single 36A output step-down µModule® (micromodule) regulators with ±0.8% (LTM4630-1A) and ±1.5% (LTM4630-1B) total DC output error, respectively, with ±3% transient output error. Included in the package are the switching controller, power FETs, inductors, and all supporting components. External compensation allows for fast transient response to minimize output capacitance when powering FPGAs, ASICs, and processors. With synchronized multiphase parallel current sharing, four LTM4630-1 devices can deliver up to 144A. The LTM4630-1 is offered in a 16mm × 16mm × 5.01 BGA package. nn APPLICATIONS nn nn L, LT, LTC, LTM, Linear Technology, the Linear logo, µModule, Burst Mode and PolyPhase are registered trademarks and LTpowerCAD is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents, including 5481178, 5705919, 5929620, 6100678, 6144194, 6177787, 6304066 and 6580258. Other patents pending. FPGA, ASIC, µProcessor Core Voltage Regulation Information, Communication Systems TYPICAL APPLICATION 36A, 1.2V Output DC/DC µModule Regulator 1.2V Output Efficiency, fSW = 500kHz 95 INTVCC 4.7µF 10k 22µF 25V ×4 CLKOUT INTVCC EXTVCC PGOOD2 PGOOD1 VOUT1 VIN 121k TEMP VOUT2 RUN1 DIFFP RUN2 TRACK2 LTM4630-1 f SET 0.1µF 121k 2200pF 33pF DIFFOUT 80 75 65 VFB1 VFB2 COMP2 VIN = 12V 85 70 VOUTS1 VOUTS2 PHASMD COMP1 3.75k 220µF 4V ×5 DIFFN TRACK1 VOUT 1.2V 36A EFFICIENCY (%) VIN 4.5V TO 15V VIN = 5V 90 PGOOD 0 60.4k 4 8 12 16 20 24 28 OUTPUT CURRENT (A) 32 36 46301 TA01b SGND GND MODE_PLLIN 46301 TA01a 25% Load Step Transient Response, ±3% Output Regulation Window. 12VIN, 1.2VOUT, 36A with 5x 220μF Ceramic Cap VOUT 20mV/DIV AC-COUPLED 65mV LOAD STEP 4A/DIV 9A STEP *SEE DEMO CIRCUIT DC2081A-B 50µs/DIV 46301 TA01c For more information www.linear.com/LTM4630-1 46301fa 1 LTM4630-1 ABSOLUTE MAXIMUM RATINGS PIN CONFIGURATION (Note 1) TOP VIEW VIN...............................................................–0.3V to 16V VSW1, VSW2.....................................................–1V to 16V PGOOD1, PGOOD2, RUN1, RUN2, INTVCC , EXTVCC........................................... –0.3V to 6V MODE_PLLIN, fSET, TRACK1, TRACK2, DIFFOUT, PHASMD................................ –0.3V to INTVCC VOUT1, VOUT2, VOUTS1, VOUTS2 (Note 6)......... –0.3V to 6V DIFFP, DIFFN.......................................... –0.3V to INTVCC INTVCC Peak Output Current.................................100mA Internal Operating Temperature Range (Note 2).............................................. –40°C to 125°C Storage Temperature Range................... –55°C to 125°C Peak Package Body Temperature........................... 245°C TEMP EXTVCC M L VIN K J CLKOUT SW1 PHASMD MODE_PLLIN TRACK1 VFB1 VOUTS1 INTVCC SW2 PGOOD1 PGOOD2 RUN2 DIFFOUT DIFFP DIFFN H G RUN1 SGND F GND COMP1 COMP2 E SGND VFB2 TRACK2 D GND fSET SGND VOUTS2 C B VOUT1 VOUT2 GND A 1 2 3 4 5 6 7 8 9 10 11 12 BGA PACKAGE 144-LEAD (16mm × 16mm × 5.01mm) TJMAX = 125°C, θJA = 7°C/W, θJCbottom = 1.5°C/W, θJCtop = 3.7°C/W, θJB + θJBA ≅ 7°C/W θ VALUES DEFINED PER JESD 51-12 WEIGHT = 3.5g ORDER INFORMATION PART MARKING* PART NUMBER PAD OR BALL FINISH DEVICE FINISH CODE PACKAGE TYPE MSL RATING TOTAL DC ACCURACY TEMPERATURE RANGE (Note 2) LTM4630EY-1A#PBF SAC305 (RoHS) LTM4630Y-1 e4 BGA 3 ±0.8% –40°C to 125°C LTM4630IY-1A#PBF SAC305 (RoHS) LTM4630Y-1 e4 BGA 3 ±0.8% –40°C to 125°C LTM4630EY-1B#PBF SAC305 (RoHS) LTM4630Y-1 e4 BGA 3 ±1.5% –40°C to 125°C LTM4630IY-1B#PBF SAC305 (RoHS) LTM4630Y-1 e4 BGA 3 ±1.5% –40°C to 125°C Consult Marketing for parts specified with wider operating temperature ranges. *Device temperature grade is indicated by a label on the shipping container. Pad or ball finish code is per IPC/JEDEC J-STD-609. • Recommended LGA and BGA PCB Assembly and Manufacturing Procedures: www.linear.com/umodule/pcbassembly • Terminal Finish Part Marking: www.linear.com/leadfree • LGA and BGA Package and Tray Drawings: www.linear.com/packaging 2 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the specified internal operating temperature range. Specified as each individual output channel. TA = 25°C (Note 2), VIN = 12V and VRUN1, VRUN2 at 5V unless otherwise noted. Per the typical application in Figure 25. SYMBOL PARAMETER CONDITIONS VIN Input DC Voltage l 4.5 15 V VOUT Output Voltage l 0.6 1.8 V VOUT1(DC), VOUT2(DC) Output Voltage, Total Variation with Line and Load l l 1.488 1.477 1.5 1.5 1.512 1.523 V V 1.1 1.25 1.40 V CIN = 22µF × 3, COUT = 100µF × 1 Ceramic, 470µF POSCAP, RFB = 40.2kΩ VIN = 12V, VOUT = 1.5V, IOUT = 0A to 18A A-Grade (0.8%) B-Grade (1.5%) MIN TYP MAX UNITS Input Specifications VRUN1, VRUN2 RUN Pin On/Off Threshold RUN Rising VRUN1HYS , VRUN2HYS RUN Pin On Hysteresis 150 mV IINRUSH(VIN) Input Inrush Current at Start-Up IOUT = 0A, CIN = 22µF ×3, CSS = 0.01µF, COUT = 100µF ×3, VOUT1 = 1.5V, VOUT2 = 1.5V, VIN = 12V 1 A IQ(VIN) Input Supply Bias Current VIN = 12V, VOUT = 1.5V, Burst Mode® Operation VIN = 12V, VOUT = 1.5V, Pulse-Skipping Mode VIN = 12V, VOUT= 1.5V, Switching Continuous Shutdown, RUN = 0, VIN = 12V 3 15 65 50 mA mA mA µA IS(VIN) Input Supply Current VIN = 5V, VOUT = 1.5V, IOUT = 18A VIN = 12V, VOUT = 1.5V, IOUT = 18A 6 2.6 A A IOUT1(DC), IOUT2(DC) Output Continuous Current Range VIN = 12V, VOUT = 1.5V (Note 7) ΔVOUT1(LINE) /VOUT1 ΔVOUT2(LINE) /VOUT2 Line Regulation Accuracy VOUT = 1.5V, VIN from 4.5V to 15V IOUT = 0A for Each Output, ΔVOUT1/VOUT1 ΔVOUT2 /VOUT2 Load Regulation Accuracy For Each Output, VOUT = 1.5V, 0A to 18A VIN = 12V (Note 7) A-Grade B-Grade Output Specifications 0 18 A l 0.01 0.03 %/V l l 0.1 0.2 0.3 0.5 % % VOUT1(AC), VOUT2(AC) Output Ripple Voltage For Each Output, IOUT = 0A, COUT = 100µF ×3/ X7R/Ceramic, 470µF POSCAP, VIN = 12V, VOUT = 1.5V, Frequency = 450kHz fS (Each Channel) Output Ripple Voltage Frequency VIN = 12V, VOUT = 1.5V, fSET = 1.25V (Note 4) fSYNC (Each Channel) SYNC Capture Range ∆VOUTSTART (Each Channel) Turn-On Overshoot COUT = 100µF/X5R/Ceramic, 470µF POSCAP, VOUT = 1.5V, IOUT = 0A VIN = 12V 10 mV tSTART (Each Channel) Turn-On Time COUT = 100µF/X5R/Ceramic, 470µF POSCAP, No Load, TRACK/SS with 0.01µF to GND, VIN = 12V 5 ms ∆VOUT(LS) (Each Channel) Peak Deviation for Dynamic Load Load: 0% to 25% to 0% of Full Load COUT = 5 × 220µF Ceramic VIN = 12V, VOUT = 1.5V 83 mV tSETTLE (Each Channel) Settling Time for Dynamic Load Step Load: 0% to 25% to 0% of Full Load, VIN = 12V, VOUT = 1.5V, COUT = 5 × 220µF Ceramic 40 µs IOUT(PK) (Each Channel) Output Current Limit VIN = 12V, VOUT = 1.5V 30 A 15 mVP-P 500 400 kHz 780 kHz 46301fa For more information www.linear.com/LTM4630-1 3 LTM4630-1 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the specified internal operating temperature range. Specified as each individual output channel. TA = 25°C (Note 2), VIN = 12V and VRUN1, VRUN2 at 5V unless otherwise noted. Per the typical application in Figure 25. SYMBOL PARAMETER CONDITIONS Voltage at VFB Pins IOUT = 0A, VOUT = 1.5V A-Grade B-Grade MIN TYP MAX UNITS 0.595 0.592 0.600 0.600 0.605 0.606 V V –5 –20 nA 0.64 0.66 0.68 V 1 1.25 1.5 µA Control Section VFB1, VFB2 IFB l l (Note 6) VOVL Feedback Overvoltage Lockout TRACK1 (I), TRACK2 (I) Track Pin Soft-Start Pull-Up Current UVLO Undervoltage Lockout (Falling) l TRACK1 (I),TRACK2 (I) Start at 0V UVLO Hysteresis tON(MIN) Minimum On-Time RFBHI1, RFBHI2 Resistor Between VOUTS1, VOUTS2 and VFB1, VFB2 Pins for Each Output (Note 6) VPGOOD1, VPGOOD2 Low PGOOD Voltage Low IPGOOD = 2mA IPGOOD PGOOD Leakage Current VPGOOD = 5V VPGOOD PGOOD Trip Level VFB with Respect to Set Output Voltage VFB Ramping Negative VFB Ramping Positive 3.3 V 0.6 V 90 60.05 ns 60.4 60.75 0.1 0.3 V ±5 µA –10 10 kΩ % % INTVCC Linear Regulator VINTVCC Internal VCC Voltage 6V < VIN < 15V VINTVCC Load Regulation INTVCC Load Regulation ICC = 0mA to 50mA VEXTVCC EXTVCC Switchover Voltage EXTVCC Ramping Positive VEXTVCC(DROP) EXTVCC Dropout ICC = 20mA, VEXTVCC = 5V VEXTVCC(HYST) EXTVCC Hysteresis 4.8 4.5 5 5.2 V 0.5 2 % 4.7 50 V 100 220 mV mV Oscillator and Phase-Locked Loop Frequency Nominal Nominal Frequency fSET = 1.2V 450 500 550 kHz Frequency Low Lowest Frequency fSET = 0V (Note 5) 210 250 290 kHz Frequency High Highest Frequency fSET > 2.4V, Up to INTVCC 700 780 860 kHz fSET Frequency Set Current 10 11 RMODE_PLLIN MODE_PLLIN Input Resistance CLKOUT Phase (Relative to VOUT1) CLK High CLK Low Clock High Output Voltage Clock Low Output Voltage 4 9 PHASMD = GND PHASMD = Float PHASMD = INTVCC 2 µA 250 kΩ 60 90 120 Deg Deg Deg 0.2 V V 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the specified internal operating temperature range. Specified as each individual output channel. TA = 25°C (Note 2), VIN = 12V and VRUN1, VRUN2 at 5V unless otherwise noted. Per the typical application in Figure 25. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS Differential Amplifier AV Differential Amplifier Gain RIN Input Resistance Measured at DIFFP Input VOS Input Offset Voltage VDIFFP = VDIFFOUT = 1.5V, IDIFFOUT = 100µA PSRR Differential Amplifier Power Supply Rejection Ratio 5V < VIN < 15V ICL Maximum Output Current VOUT(MAX) Maximum Output Voltage GBW Gain Bandwidth Product VTEMP Diode Connected PNP TC Temperature Coefficient 1 80 kΩ 3 IDIFFOUT = 300µA l mV 90 dB 3 mA 3 MHz INTVCC – 1.4 I = 100µA Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTM4630-1 is tested under pulsed load conditions such that TJ ≈ TA. The LTM4630E-1 is guaranteed to meet specifications from 0°C to 125°C internal temperature. Specifications over the –40°C to 125°C internal operating temperature range are assured by design, characterization and correlation with statistical process controls. The LTM4630I-1 is guaranteed over the full –40°C to 125°C internal operating temperature range. Note that the maximum ambient temperature consistent with these specifications is determined by specific operating conditions in conjunction with board layout, the rated package thermal impedance and other environmental factors. V/V V 0.6 V –2.2 mV/C Note 3: Two outputs are tested separately and the same testing condition is applied to each output. Note 4: The switching frequency is programmable from 400kHz to 750kHz. Note 5: LTM4630-1 device is designed to operate from 400kHz to 750kHz Note 6: These parameters are tested at wafer sort. Note 7: See output current derating curves for different VIN, VOUT and TA. 46301fa For more information www.linear.com/LTM4630-1 5 LTM4630-1 TYPICAL PERFORMANCE CHARACTERISTICS 95 EFFICIENCY (%) EFFICIENCY (%) 95 90 85 VOUT = 1V VOUT = 1.2V VOUT = 1.5V VOUT = 1.8V 80 75 2 0 4 6 8 10 12 14 LOAD CURRENT (A) 16 Efficiency vs Output Current, VIN = 12V, fS = 450kHz 90 90 85 85 80 75 VOUT = 1V VOUT = 1.2V VOUT = 1.5V VOUT = 1.8V 70 65 18 95 EFFICIENCY (%) 100 Efficiency vs Output Current, VIN = 5V, fS = 450kHz 0 2 4 6 8 10 12 14 LOAD CURRENT (A) 16 Burst Mode and Pulse-Skip Mode Efficiency VIN=12V, VOUT = 1.2V, fS = 450kHz CCM Burst Mode OPERATION PULSE-SKIP MODE 90 75 VOUT = 1V VOUT = 1.2V VOUT = 1.5V VOUT = 1.8V 70 65 0 5 10 15 20 25 30 LOAD CURRENT (A) 35 40 46301 G03 Dual Phase Single Output 25% (9A) Transient Response at 0.9V Output Dual Phase Single Output 25% (9A) Transient Response at 1V Output PK-PK: 55mV PK-PK: 48mV 80 EFFICIENCY (%) 80 46301 G02 46301 G01 100 18 Dual Phase Single Output Efficiency vs Output Current, VIN = 12V, fS = 450kHz VOUT 20mV/DIV AC-COUPLED VOUT 20mV/DIV AC-COUPLED LOAD STEP 4A/DIV LOAD STEP 4A/DIV 70 60 50 40 30 0.01 0.1 1 10 LOAD CURRENT (A) 100 46301 G06 50µs/DIV 12VIN, 1VOUT, 450kHz 9A LOAD STEP, 10A/µs LOAD SLEW RATE COUT = 12 • 100µF 6.3V CERAMIC, CTH = 2200pF, RTH = 4.24k, CFF = 33pF 46301 G05 50µs/DIV 12VIN, 0.9VOUT, 450kHz 9A LOAD STEP, 10A/µs LOAD SLEW RATE COUT = 12 • 100µF 6.3V CERAMIC, CTH = 2200pF, RTH = 4.24k, CFF = 33pF 46301 G04 Dual Phase Single Output 25% (9A) Transient Response at 1.2V Output VOUT 20mV/DIV AC-COUPLED PK-PK: 66mV LOAD STEP 4A/DIV VOUT 20mV/DIV AC-COUPLED PK-PK: 83mV LOAD STEP 4A/DIV 46301 G07 50µs/DIV 12VIN, 1.2VOUT, 450kHz 9A LOAD STEP, 10A/µs LOAD SLEW RATE COUT = 10 • 100µF 6.3V CERAMIC, CTH = 2200pF, RTH = 3.75k, CFF = 33pF 6 Dual Phase Single Output 25% (9A) Transient Response at 1.5V Output Dual Phase Single Output 25% (9A) Transient Response at 1.8V Output VOUT 20mV/DIV AC-COUPLED PK-PK: 93mV LOAD STEP 4A/DIV 46301 G08 50µs/DIV 12VIN, 1.5VOUT, 450kHz 9A LOAD STEP, 10A/µs LOAD SLEW RATE COUT = 8 • 100µF 6.3V CERAMIC, CTH = 2200pF, RTH = 4.02k, CFF = 33pF 46301 G09 50µs/DIV 12VIN, 1.8VOUT, 450kHz 9A LOAD STEP, 10A/µs LOAD SLEW RATE COUT = 7 • 100µF 6.3V CERAMIC, CTH = 2200pF, RTH = 4.02k, CFF = 33pF 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 TYPICAL PERFORMANCE CHARACTERISTICS Single Phase Start-Up with No load VSW 10V/DIV Single Phase Start-Up with 18A VSW 10V/DIV VOUT 0.5V/DIV VOUT 0.5V/DIV LIN 1A/DIV LIN 0.2A/DIV 4630 G10 20ms/DIV 12VIN, 1.2VOUT, 450kHz COUT = 1 • 470µF 4V POSCAP + 1 • 100µF 6.3V CERAMIC, CSS = 0.1µF 46301 G11 20ms/DIV 12VIN, 1.2VOUT, 450kHz COUT = 1 • 470µF 4V POSCAP + 1 • 100µF 6.3V CERAMIC, CSS = 0.1µF Single Phase Short-Circuit Protection with No load Single Phase Short-Circuit Protection with 18A VSW 10V/DIV VSW 10V/DIV VOUT 0.5V/DIV LIN 1A/DIV VOUT 0.5V/DIV LIN 1A/DIV 4630 G12 50µs/DIV 12VIN, 1.2VOUT, 450kHz COUT = 1 • 470µF 4V POSCAP + 1 • 100µF 6.3V CERAMIC 46301 G13 50µs/DIV 12VIN, 1.2VOUT, 450kHz COUT = 1 • 470µF 4V POSCAP + 1 • 100µF 6.3V CERAMIC 46301fa For more information www.linear.com/LTM4630-1 7 LTM4630-1 PIN FUNCTIONS (Recommended to Use Test Points to Monitor Signal Pin Connections.) PACKAGE ROW AND COLUMN LABELING MAY VARY AMONG µModule PRODUCTS. REVIEW EACH PACKAGE LAYOUT CAREFULLY. VOUT1 (A1-A5, B1-B5, C1-C4): Power Output Pins. Apply output load between these pins and GND pins. Recommend placing output decoupling capacitance directly between these pins and GND pins. Review Table 4. GND (A6-A7, B6-B7, D1-D4, D9-D12, E1-E4, E10-E12, F1-F3, F10-F12, G1, G3, G10, G12, H1-H7, H9-H12, J1, J5, J8, J12, K1, K5-K8, K12, L1, L12, M1 , M12): Power Ground Pins for Both Input and Output Returns. VOUT2 (A8-A12, B8-B12, C9-C12): Power Output Pins. Apply output load between these pins and GND pins. Recommend placing output decoupling capacitance directly between these pins and GND pins. Review Table 4. VOUTS1, VOUTS2 (C5, C8): This pin is connected to the top of the internal top feedback resistor for each output. The pin can be directly connected to its specific output, or connected to DIFFOUT when the remote sense amplifier is used. In paralleling modules, one of the VOUTS pins is connected to the DIFFOUT pin in remote sensing or directly to VOUT with no remote sensing. It is very important to connect these pins to either the DIFFOUT or VOUT since this is the feedback path, and cannot be left open. See the Applications Information section. fSET (C6): Frequency Set Pin. A 10µA current is sourced from this pin. A resistor from this pin to ground sets a voltage that in turn programs the operating frequency. Alternatively, this pin can be driven with a DC voltage that can set the operating frequency. See the Applications Information section. SGND (C7, D6, G6-G7, F6-F7): Signal Ground Pin. Return ground path for all analog and low power circuitry. Tie a single connection to the output capacitor GND in the application. See layout guidelines in Figure 14. 8 VFB1, VFB2 (D5, D7): The Negative Input of the Error Amplifier for Each Channel. Internally, this pin is connected to VOUTS1 or VOUTS2 with a 60.4kΩ precision resistor. Different output voltages can be programmed with an additional resistor between VFB and GND pins. In PolyPhase® operation, tying the VFB pins together allows for parallel operation. See the Applications Information section for details. Do not drive this pin. TRACK1, TRACK2 (E5, D8): Output Voltage Tracking Pin and Soft-Start Inputs. Each channel has a 1.3µA pull-up current source. When one channel is configured to be master of the two channels, then a capacitor from this pin to ground will set a soft-start ramp rate. The remaining channel can be set up as the slave, and have the master’s output applied through a voltage divider to the slave output’s track pin. This voltage divider is equal to the slave output’s feedback divider for coincidental tracking. See the Applications Information section. COMP1, COMP2 (E6, E7): Current control threshold and error amplifier compensation point for each channel. The current comparator threshold increases with this control voltage. COMP pin internal has 10pF filter cap to SGND. An external RC filter circuit is required for control loop compensation. See Applications Information section. Tie the COMP pins together for parallel operation. Do not drive this pin. DIFFP (E8): Positive input of the remote sense amplifier. This pin is connected to the remote sense point of the output voltage. See the Applications Information section. DIFFN (E9): Negative input of the remote sense amplifier. This pin is connected to the remote sense point of the output GND. See the Applications Information section. MODE_PLLIN (F4): Force Continuous Mode, Burst Mode Operation, or Pulse-Skipping Mode Selection Pin and External Synchronization Input to Phase Detector Pin. Connect this pin to SGND to force both channels into force continuous mode of operation. Connect to INTVCC to enable pulse-skipping mode of operation. Leaving the pin floating will enable Burst Mode operation. A clock on the pin will force both channels into continuous mode of operation and synchronized to the external clock applied to this pin. 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 PIN FUNCTIONS (Recommended to Use Test Points to Monitor Signal Pin Connections.) RUN1, RUN2 (F5, F9): Run Control Pin. A voltage above 1.25V will turn on each channel in the module. A voltage below 1.25V on the RUN pin will turn off the related channel. Each RUN pin has a 1µA pull-up current, once the RUN pin reaches 1.2V an additional 4.5µA pull-up current is added to this pin. DIFFOUT (F8): Internal Remote Sense Amplifier Output. Connect this pin to VOUTS1 or VOUTS2 depending on which output is using remote sense. In parallel operation connect one of the VOUTS pin to DIFFOUT for remote sensing. SW1, SW2 (G2, G11): Switching node of each channel that is used for testing purposes. Also an R-C snubber network can be applied to reduce or eliminate switch node ringing, or otherwise leave floating. See the Applications Information section. PHASMD (G4): Connect this pin to SGND, INTVCC, or floating this pin to select the phase of CLKOUT to 60 degrees, 120 degrees, and 90 degrees respectively. CLKOUT (G5): Clock output with phase control using the PHASMD pin to enable multiphase operation between devices. See the Applications Information section. INTVCC (H8): Internal 5V Regulator Output. The control circuits and internal gate drivers are powered from this voltage. Decouple this pin to PGND with a 4.7µF low ESR tantalum or ceramic. INTVCC is activated when either RUN1 or RUN2 is activated. TEMP (J6): Onboard General Purpose Temperature Diode for Monitoring the VBE Junction Voltage Change with Temperature. See the Applications Information section. EXTVCC (J7): External power input that is enabled through a switch to INTVCC whenever EXTVCC is greater than 4.7V. Do not exceed 6V on this input, and connect this pin to VIN when operating VIN on 5V. An efficiency increase will occur that is a function of the (VIN – INTVCC) multiplied by power MOSFET driver current. Typical current requirement is 30mA. VIN must be applied before EXTVCC , and EXTVCC must be removed before VIN. VIN (M2-M11, L2-L11, J2-J4, J9-J11, K2-K4, K9-K11): Power Input Pins. Apply input voltage between these pins and GND pins. Recommend placing input decoupling capacitance directly between VIN pins and GND pins. PGOOD1, PGOOD2 (G9, G8): Output Voltage Power Good Indicator. Open drain logic output that is pulled to ground when the output voltage is not within ±10% of the regulation point. 46301fa For more information www.linear.com/LTM4630-1 9 LTM4630-1 SIMPLIFIED BLOCK DIAGRAM PGOOD1 TRACK1 SS CAP VIN = 100µA VIN RT OR TEMP MONITORS RT VIN 4.5V TO 15V VIN CIN1 22µF 25V 0.1µF GND TEMP MTOP1 SW1 CLKOUT 0.33µH RUN1 MODE_PLLIN VOUT1 1.5V 18A VOUT1 0.22µF MBOT1 PHASEMD CIN2 22µF 25V + GND COUT1 VOUTS1 COMP1 RTH1 CTH1 60.4k VFB1 10pF SGND RFB1 40.2k POWER CONTROL PGOOD2 TRACK2 SS CAP VIN INTVCC CIN3 22µF 25V 0.1µF 4.7µF GND EXTVCC MTOP2 SW2 0.33µH RUN2 CIN4 22µF 25V VOUT2 0.22µF MBOT2 GND + VOUT2 1.2V 18A COUT2 VOUTS2 60.4k COMP2 + – VFB2 RFB2 60.4k 10pF RTH2 CTH2 fSET RFSET SGND INTERNAL FILTER DIFFOUT DIFFN DIFFP 46301 BD Figure 1. Simplified LTM4630-1 Block Diagram DECOUPLING REQUIREMENTS TA = 25°C. Use Figure 1 configuration. SYMBOL PARAMETER CONDITIONS CIN1, CIN2 CIN3, CIN4 External Input Capacitor Requirement (VIN1 = 4.5V to 15V, VOUT1 = 1.5V) (VIN2 = 4.5V to 15V, VOUT2 = 1.2V) IOUT1 = 18A IOUT2 = 18A 44 44 µF µF COUT1 COUT2 External Output Capacitor Requirement (VIN1 = 4.5V to 15V, VOUT1 = 1.5V) (VIN2 = 4.5V to 15V, VOUT2 = 1.2V) IOUT1 = 18A IOUT2 = 18A 400 400 µF µF 10 MIN TYP MAX UNITS 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 OPERATION Power Module Description The LTM4630-1 is a dual-output standalone nonisolated switching mode DC/DC power supply with ±0.8% total DC output error over line, load and temperature variation. It can provide two 18A outputs or single 36A output with few external input and output capacitors and setup components. This module provides precisely regulated output voltages programmable via external resistors from 0.6VDC to 1.8VDC over 4.5V to 15V input voltages. The typical application schematic is shown in Figure 25. The LTM4630-1 has dual integrated constant-frequency current mode regulators and built-in power MOSFET devices with fast switching speed. The typical switching frequency is 500kHz. For switching-noise sensitive applications, it can be externally synchronized from 400kHz to 780kHz. A resistor can be used to program a free run frequency on the FSET pin. See the Applications Information section. With current mode control, multi LTM4630-1s can be easily paralleled to provide up to 144A current with guaranteed perfect current sharing. Also, with current mode control, the LTM4630-1 module is able to achieve sufficient stability margins and a very fast ±3% output transient response with a minimum number of output capacitors, even with all ceramic output capacitors. This makes LTM4630-1 the best candidate when powering FPGAs, ASICs and processors in terms of DC accuracy, AC transient response, high output current and accuracy current sharing. See Applications Information section. Current mode control provides cycle-by-cycle fast current limit and foldback current limit in an overcurrent condition. Internal overvoltage and undervoltage comparators pull the open-drain PGOOD outputs low if the output feedback voltage exits a ±10% window around the regulation point. As the output voltage exceeds 10% above regulation, the bottom MOSFET will turn on to clamp the output voltage. The top MOSFET will be turned off. This overvoltage protect is feedback voltage referred. Pulling the RUN pins below 1.1V forces the regulators into a shutdown state, by turning off both MOSFETs. The TRACK pins are used for programming the output voltage ramp and voltage tracking during start-up or used for soft-starting the regulator. See the Applications Information section. The LTM4630-1 has a built-in 10pF high frequency filter cap from COMP to SGND for each output. An external RC filtering circuit is required to achieve fast Type II control loop compensation. Table 4 provides a guide line for input, output capacitances and RC comp values for several operating conditions. The Linear Technology µModule Power Design Tool (LTpowerCAD™) will be provided for transient and stability analysis. The VFB pin is used to program the output voltage with a single external resistor to ground. A differential remote sense amplifier is available for sensing the output voltage accurately on one of the outputs at the load point, or in parallel operation sensing the output voltage at the load point. High efficiency at light loads can be accomplished with selectable Burst Mode operation or pulse-skipping operation using the MODE_PLLIN pin. These light load features will accommodate battery operation. Efficiency graphs are provided for light load operation in the Typical Performance Characteristics section. See the Applications Information section for details. A general purpose temperature diode is included inside the module to monitor the temperature of the module. See the Applications Information section for details. The switch pins are available for functional operation monitoring and a resistor-capacitor snubber circuit can be careful placed on the switch pin to ground to dampen any high frequency ringing on the transition edges. See the Applications Information section for details. 46301fa For more information www.linear.com/LTM4630-1 11 LTM4630-1 APPLICATIONS INFORMATION OUTPUT TOTAL DC ACCURACY AND AC TRANSIENT PERFORMANCE In modern ASIC and FPGA power supply designs, a tight total voltage regulation window, ±3% for example, is required of the supply powering the core and periphery. To meet this requirement, the supply’s DC voltage variance plus any AC voltage variation which may occur during any load step transient must fall within this allowed window. The DC voltage variance is determined by the accuracies of the supply’s reference voltage, resistor divider, load regulation and line regulation over the operating temperature range. The AC voltage variance is determined by the supply’s output voltage overshoot and undershoots in response to a load transient condition for a given output capacitor network. Figure 2 shows a typical load step transient response waveform together with DC voltage accuracy variance. For a given allowable voltage regulation window, a tighter DC voltage accuracy allows more margin for the AC variation due to a load transient response. This increased margin for AC variation allows for a reduction in the total output capacitance required to meet the regulation window requirement. This allows for a reduced total solution cost and footprint area. LOAD STEP For example, in an FPGA core voltage application, for a 12V input, 0.9V output at 72A design, a total overall ±3% total voltage regulation window is required in responding to a 25% load step transient. Figure 3 illustrates the benefit of overall output capacitor reduction versus improved total DC accuracy by using 100µF ceramic output capacitors. 5000 REQUIRED OUTPUT CAPACITANCE (µF) The typical LTM4630-1 application circuit is shown in Figure 25. External component selection is primarily determined by the maximum load current and output voltage. Refer to Table 4 for specific external capacitor requirements to achieve ±3% transient response for a 25% or a 50% load step application. 4700 4500 4000 3500 3200 3000 2500 2600 2200 2000 1500 1000 500 0 0.8 1.2 1.5 TOTAL DC ACCURACY (%) 2.0 46301 F03 Figure 3.Overall Output Capacitor vs Total DC Accuracy VIN to VOUT Step-Down Ratios There are restrictions in the maximum VIN and VOUT stepdown ratio that can be achieved for a given input voltage. Each output of the LTM4630-1 is capable of 98% duty cycle, but the VIN to VOUT minimum dropout is still shown as a function of its load current and will limit output current capability related to high duty cycle on the top side switch. Minimum on-time tON(MIN) is another consideration in operating at a specified duty cycle while operating at a certain frequency due to the fact that tON(MIN) < D/fSW, where D is duty cycle and fSW is the switching frequency. tON(MIN) is specified in the electrical parameters as 90ns. Output Voltage Programming AC OVERSHOOT ALLOWABLE REGULATION WINDOW DC ACCURACY AC UNDERSHOOT 46301 F02 Figure 2. Typical Load Step Transient Response with DC Voltage Accuracy Variance 12 The PWM controller has an internal 0.6V reference voltage. As shown in the Block Diagram, a 60.4kΩ internal feedback resistor connects between the VOUTS1 to VFB1 and VOUTS2 to VFB2. It is very important that these pins be connected to their respective outputs for proper feedback regulation. Overvoltage can occur if these VOUTS1 and VOUTS2 pins are left floating when used as individual regulators, or at least one of them is used in paralleled regulators. The output 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION voltage will default to 0.6V with no feedback resistor on either VFB1 or VFB2. Adding a resistor RFB from VFB pin to GND programs the output voltage: VOUT 2.5k COMP1 LTM4630-1 VOUT1 COMP2 VOUT2 6800pF 60.4k 60.4k + RFB = 0.6V • RFB VOUTS1 VOUTS2 VFB1 TRACK1 Table 1. VFB Resistor Table vs Various Output Voltages 0.6V 1.0V 1.2V 1.5V 1.8V RFB Open 90.9k 60.4k 40.2k 30.2k For parallel operation of multiple channels the same feedback setting resistor can be used for the parallel design. This is done by connecting the VOUTS1 to the output as shown in Figure 4, thus tying one of the internal 60.4k resistors to the output. All of the VFB pins tie together with one programming resistor as shown in Figure 4. VFB2 In parallel operation, the VFB pins have an IFB current of 20nA maximum each channel. To reduce output voltage error due to this current, an additional VOUTS pin can be tied to VOUT, and an additional RFB resistor can be used to lower the total Thevenin equivalent resistance seen by this current. For example in Figure 4, the total Thevenin equivalent resistance of the VFB pin is (60.4k//RFB), which is 30.2k where RFB is equal to 60.4k for a 1.2V output. Four phases connected in parallel equates to a worse case feedback current of 4 • IFB = 80nA maximum. The voltage error is 80nA • 30.2k = 2.4mV. If VOUTS2 is connected, as shown in Figure 4, to VOUT, and another 60.4k resistor is connected from VFB2 to ground, then the voltage error is reduced to 1.2mV. If the voltage error is acceptable then no additional connections are necessary. The onboard 60.4k resistor is 0.5% accurate and the VFB resistor can be chosen by the user to be as accurate as needed. All COMP pins are tied together for current sharing between the phases. The TRACK/SS pins can be tied together and a single soft-start capacitor can be used to soft-start the regulator. The soft-start equation will need to have the soft-start current parameter increased by the number of paralleled channels. See Output Voltage Tracking section. COMP1 LTM4630-1 VOUT1 COMP2 VOUT2 60.4k VOUTS1 VOUTS2 VFB1 TRACK1 0.1µF TRACK2 OPTIONAL CONNECTION 60.4k TRACK2 VOUT 4 PARALLELED OUTPUTS FOR 1.2V AT 70A OPTIONAL RFB 60.4k USE TO LOWER TOTAL EQUIVALENT RESISTANCE TO LOWER IFB VOLTAGE ERROR 60.4k VFB2 4630 F04 RFB 60.4k Figure 4. 4-Phase Parallel Configurations Input Capacitors The LTM4630-1 module should be connected to a low acimpedance DC source. For the regulator input four 22µF input ceramic capacitors are used for RMS ripple current. A 47µF to 100µF surface mount aluminum electrolytic bulk capacitor can be used for more input bulk capacitance. This bulk input capacitor is only needed if the input source impedance is compromised by long inductive leads, traces or not enough source capacitance. If low impedance power planes are used, then this bulk capacitor is not needed. For a buck converter, the switching duty-cycle can be estimated as: D= VOUT VIN 46301fa For more information www.linear.com/LTM4630-1 13 LTM4630-1 APPLICATIONS INFORMATION Without considering the inductor current ripple, for each output, the RMS current of the input capacitor can be estimated as: ICIN(RMS) = IOUT(MAX) • D • (1− D) η% In the above equation, η% is the estimated efficiency of the power module. The bulk capacitor can be a switcherrated electrolytic aluminum capacitor, Polymer capacitor. Output Capacitors The LTM4630-1 is designed for low output voltage ripple noise and good transient response. The bulk output capacitors defined as COUT are chosen with low enough effective series resistance (ESR) to meet the output voltage ripple and transient requirements. COUT can be a low ESR tantalum capacitor, the low ESR polymer capacitor or ceramic capacitor. The typical output capacitance range for each output is from 200µF to 470µF per output channel. Additional output filtering may be required by the system designer, if further reduction of output ripples or dynamic transient spikes is required. Table 4 shows a matrix of different output voltages and output capacitors to minimize the voltage droop and overshoot to achieve ±3% transient accuracy during a 25% load step. In multi LTM4630-1 paralleling applications, Table 4 RC compensation value is still valid in terms of having one set of RC filters on each of the paralleling modules while connecting all the COMP, FB and VOUT pins together. See Figure 28 and Multiphase Operation section. The table optimizes total equivalent ESR and total bulk capacitance to optimize the transient performance. Stability criteria are considered in the Table 4 matrix, and the Linear Technology µModule Power Design Tool will be provided for stability analysis. Multiphase operation will reduce effective output ripple as a function of the number of phases. Application Note 77 discusses this noise reduction versus output ripple current cancellation, but the output capacitance should be considered carefully as a function of stability and transient response. The Linear Technology µModule Power Design Tool can calculate the output ripple reduction as the number of implemented phases increases by N times. A small value 14 10Ω to 50Ω resistor can be place in series from VOUT to the VOUTS pin to allow for a bode plot analyzer to inject a signal into the control loop and validate the regulator stability. The same resistor could be place in series from VOUT to DIFFP and a bode plot analyzer could inject a signal into the control loop and validate the regulator stability. Burst Mode Operation The LTM4630-1 is capable of Burst Mode operation on each regulator in which the power MOSFETs operate intermittently based on load demand, thus saving quiescent current. For applications where maximizing the efficiency at very light loads is a high priority, Burst Mode operation should be applied. Burst Mode operation is enabled with the MODE_PLLIN pin floating. During this operation, the peak current of the inductor is set to approximately one third of the maximum peak current value in normal operation even though the voltage at the COMP pin indicates a lower value. The voltage at the COMP pin drops when the inductor’s average current is greater than the load requirement. As the COMP voltage drops below 0.5V, the BURST comparator trips, causing the internal sleep line to go high and turn off both power MOSFETs. In sleep mode, the internal circuitry is partially turned off, reducing the quiescent current to about 450µA for each output. The load current is now being supplied from the output capacitors. When the output voltage drops, causing COMP to rise above 0.5V, the internal sleep line goes low, and the LTM4630-1 resumes normal operation. The next oscillator cycle will turn on the top power MOSFET and the switching cycle repeats. Either regulator can be configured for Burst Mode operation. Pulse-Skipping Mode Operation In applications where low output ripple and high efficiency at intermediate currents are desired, pulse-skipping mode should be used. Pulse-skipping operation allows the LTM4630-1 to skip cycles at low output loads, thus increasing efficiency by reducing switching loss. Tying the MODE_PLLIN pin to INTVCC enables pulse-skipping operation. At light loads the internal current comparator 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION Multiphase Operation may remain tripped for several cycles and force the top MOSFET to stay off for several cycles, thus skipping cycles. The inductor current does not reverse in this mode. This mode will maintain higher effective frequencies thus lower output ripple and lower noise than Burst Mode operation. Either regulator can be configured for pulse-skipping mode. For output loads that demand more than 18A of current, two outputs in LTM4630-1 or even multiple LTM4630-1s can be paralleled to run out of phase to provide more output current without increasing input and output voltage ripples. The MODE_PLLIN pin allows the LTM4630-1 to synchronize to an external clock (between 400kHz and 780kHz) and the internal phase-locked-loop allows the LTM4630-1 to lock onto incoming clock phase as well. The CLKOUT signal can be connected to the MODE_PLLIN pin of the following stage to line up both the frequency and the phase of the entire system. Tying the PHASMD pin to INTVCC, SGND, or (floating) generates a phase difference (between MODE_PLLIN and CLKOUT) of 120 degrees, 60 degrees, or 90 degrees respectively. A total of 12 phases can be cascaded to run simultaneously with respect to each other by programming the PHASMD pin of each LTM4630-1 channel to different levels. Figure 5 shows a 2-phase design, 4-phase design and a 6-phase design example for clock phasing with the PHASMD table. Forced Continuous Operation In applications where fixed frequency operation is more critical than low current efficiency, and where the lowest output ripple is desired, forced continuous operation should be used. Forced continuous operation can be enabled by tying the MODE_PLLIN pin to GND. In this mode, inductor current is allowed to reverse during low output loads, the COMP voltage is in control of the current comparator threshold throughout, and the top MOSFET always turns on with each oscillator pulse. During start-up, forced continuous mode is disabled and inductor current is prevented from reversing until the LTM4630-1’s output voltage is in regulation. Either regulator can be configured for force continuous mode. 2-PHASE DESIGN PHASMD FLOAT CLKOUT 0 PHASE MODE_PLLIN VOUT1 VOUT2 SGND FLOAT INTVCC CONTROLLER1 0 0 0 CONTROLLER2 180 180 240 CLKOUT 60 90 120 180 PHASE PHASMD 4-PHASE DESIGN 90 DEGREE CLKOUT 0 PHASE FLOAT CLKOUT MODE_PLLIN VOUT1 VOUT2 180 PHASE 90 PHASE FLOAT PHASMD MODE_PLLIN VOUT1 VOUT2 270 PHASE PHASMD 6-PHASE DESIGN 60 DEGREE 60 DEGREE CLKOUT 0 PHASE SGND CLKOUT MODE_PLLIN VOUT1 PHASMD VOUT2 180 PHASE 60 PHASE SGND CLKOUT MODE_PLLIN VOUT1 VOUT2 240 PHASE PHASMD 120 PHASE FLOAT MODE_PLLIN VOUT1 VOUT2 300 PHASE PHASMD 46301 F05 Figure 5. Examples of 2-Phase, 4-Phase, and 6-Phase Operation with PHASMD Table 46301fa For more information www.linear.com/LTM4630-1 15 LTM4630-1 APPLICATIONS INFORMATION A multiphase power supply significantly reduces the amount of ripple current in both the input and output capacitors. The RMS input ripple current is reduced by, and the effective ripple frequency is multiplied by, the number of phases used (assuming that the input voltage is greater than the number of phases used times the output voltage). The output ripple amplitude is also reduced by the number of phases used when all of the outputs are tied together to achieve a single high output current design. In multi LTM4630-1s parallel applications, CTH and RTH values in Table 4 are still valid to achieve a ±3% transient response in a 25% load step. Connect one set of RC (RTH and CTH) network to the COMP pin of each paralleling module like a dual phase single output setup. Then connect the COMP pins, FB pins, TRACK/SS pin and VOUT pins from different modules together. See Figure 28 for an example of parallel operation. LTpowerCAD Power Design Tool can also be used to optimize loop compensation and transient performance if only one set of RC (RTH and CTH) network is to be added to the common COMP pins. The LTM4630-1 device is an inherently current mode controlled device, so parallel modules will have very good current sharing. This will balance the thermals on the design. Input RMS Ripple Current Cancellation Application Note 77 provides a detailed explanation of multiphase operation. The input RMS ripple current cancellation mathematical derivations are presented, and a graph is displayed representing the RMS ripple current reduction as a function of the number of interleaved phases. Figure 6 shows this graph. 0.60 1-PHASE 2-PHASE 3-PHASE 4-PHASE 6-PHASE 0.55 0.50 RMS INPUT RIPPLE CURRENT DC LOAD CURRENT 0.45 0.40 0.35 0.30 0.25 0.20 0.15 0.10 0.05 0 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 0.55 0.6 0.65 0.7 0.75 0.8 0.85 0.9 DUTY FACTOR (VOUT/VIN) 46301 F06 Figure 6. Input RMS Current Ratios to DC Load Current as a Function of Duty Cycle 16 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION Frequency Selection and Phase-Lock Loop (MODE_PLLIN and fSET Pins) The LTM4630-1 device is operated over a range of frequencies to improve power conversion efficiency. It is recommended to operate the module at 500kHz over the output range for the best efficiency and inductor current ripple. The LTM4630-1 switching frequency can be set with an external resistor from the fSET pin to SGND. An accurate 10µA current source into the resistor will set a voltage that programs the frequency or a DC voltage can be applied. Figure 7 shows a graph of frequency setting verses programming voltage. An external clock can be applied to the MODE_PLLIN pin from 0V to INTVCC over a frequency range of 400kHz to 780kHz. The clock input high threshold is 1.6V and the clock input low threshold is 1V. The LTM4630-1 has the PLL loop filter components on board. The frequency setting resistor should always be present to set the initial switching frequency before locking to an external clock. Both regulators will operate in continuous mode while being externally clock. The output of the PLL phase detector has a pair of complementary current sources that charge and discharge the internal filter network. When the external clock is applied then the fSET frequency resistor is disconnected with an internal switch, and the current sources control the frequency adjustment to lock to the incoming external clock. When no external clock is applied, then the internal switch is on, thus connecting the external fSET frequency set resistor for free run operation. Minimum On-Time Minimum on-time tON is the smallest time duration that the LTM4630-1 is capable of turning on the top MOSFET on either channel. It is determined by internal timing delays, and the gate charge required turning on the top MOSFET. Low duty cycle applications may approach this minimum on-time limit and care should be taken to ensure that: VOUT > tON(MIN) VIN •FREQ If the duty cycle falls below what can be accommodated by the minimum on-time, the controller will begin to skip cycles. The output voltage will continue to be regulated, but the output ripple and current will increase. The on-time can be increased by lowering the switching frequency. A good rule of thumb is to keep on-time longer than 110ns. Output Voltage Tracking 900 800 FREQUENCY (kHz) 700 600 500 400 300 200 100 0 0 0.5 1 1.5 fSET PIN VOLTAGE (V) 2 2.5 46301 F07 Figure 7. Operating Frequency vs fSET Pin Voltage Output voltage tracking can be programmed externally using the TRACK pins. The output can be tracked up and down with another regulator. The master regulator’s output is divided down with an external resistor divider that is the same as the slave regulator’s feedback divider to implement coincident tracking. The LTM4630-1 uses an accurate 60.4k resistor internally for the top feedback resistor for each channel. Figure 8 shows an example of coincident tracking. Equations: 60.4k •V SLAVE = 1+ TRACK RTA VTRACK is the track ramp applied to the slave’s track pin. VTRACK has a control range of 0V to 0.6V, or the internal reference voltage. When the master’s output is divided 46301fa For more information www.linear.com/LTM4630-1 17 LTM4630-1 APPLICATIONS INFORMATION down with the same resistor values used to set the slave’s output, then the slave will coincident track with the master until it reaches its final value. The master will continue to its final value from the slave’s regulation point. Voltage tracking is disabled when VTRACK is more than 0.6V. RTA in Figure 8 will be equal to the RFB for coincident tracking. Figure 9 shows the coincident tracking waveforms. The TRACK pin of the master can be controlled by a capacitor placed on the master regulator TRACK pin to ground. A 1.3µA current source will charge the TRACK pin up to the reference voltage and then proceed up to INTVCC. After the 0.6V ramp, the TRACK pin will no longer be in control, and the internal voltage reference will control output regulation from the feedback divider. Foldback current limit is disabled during this sequence of turn-on during tracking or soft-starting. The TRACK pins are pulled low when the RUN pin is below 1.2V. The total soft-start time can be calculated as: C tSOFT-START = SS • 0.6 1.3µA Regardless of the mode selected by the MODE_PLLIN pin, the regulator channels will always start in pulse-skipping mode up to TRACK = 0.5V. Between TRACK = 0.5V and 0.54V, it will operate in forced continuous mode and revert to the selected mode once TRACK > 0.54V. In order to track with another channel once in steady state operation, the LTM4630-1 is forced into continuous mode operation as soon as VFB is below 0.54V regardless of the setting on the MODE_PLLIN pin. Ratiometric tracking can be achieved by a few simple calculations and the slew rate value applied to the master’s TRACK pin. As mentioned above, the TRACK pin has a control range from 0 to 0.6V. The master’s TRACK pin 18 slew rate is directly equal to the master’s output slew rate in Volts/Time. The equation: MR • 60.4k = RTB SR where MR is the master’s output slew rate and SR is the slave’s output slew rate in Volts/Time. When coincident tracking is desired, then MR and SR are equal, thus RTB is equal the 60.4k. RTA is derived from equation: RTA = 0.6V V V VFB + FB − TRACK 60.4k RFB RTB where VFB is the feedback voltage reference of the regulator, and VTRACK is 0.6V. Since RTB is equal to the 60.4k top feedback resistor of the slave regulator in equal slew rate or coincident tracking, then RTA is equal to RFB with VFB = VTRACK. Therefore RTB = 60.4k, and RTA = 60.4k in Figure 8. In ratiometric tracking, a different slew rate maybe desired for the slave regulator. RTB can be solved for when SR is slower than MR. Make sure that the slave supply slew rate is chosen to be fast enough so that the slave output voltage will reach it final value before the master output. For example, MR = 1.5V/1ms, and SR = 1.2V/1ms. Then RTB = 76.8k. Solve for RTA to equal to 49.9k. Each of the TRACK pins will have the 1.3µA current source on when a resistive divider is used to implement tracking on that specific channel. This will impose an offset on the TRACK pin input. Smaller values resistors with the same ratios as the resistor values calculated from the above equation can be used. For example, where the 60.4k is used then a 6.04k can be used to reduce the TRACK pin offset to a negligible value. 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION INTVCC C10 4.7µF R2 10k PGOOD MODE_PLLIN CLKOUT INTVCC EXTVCC PGOOD1 4V TO 15V INTERMEDIATE BUS C4 22µF 25V C3 22µF 25V C2 22µF 25V C1 22µF 25V VOUT1 VIN R6 100k TEMP VOUTS1 SW1 RUN1 RUN2 CSS 0.1µF RTA 60.4k VFB2 LTM4630-1 TRACK2 RTB 60.4k RFB 60.4k COMP1 f SET COMP2 40.2k 2200pF 1.5V PHASMD VOUTS2 VOUT2 R4 121k PGOOD2 GND DIFFP DIFFN DIFFOUT 40.2k 40.2k 2200pF SLAVE SW2 PGOOD SGND 1.5V 18A VFB1 TRACK1 MASTER C8 470µF 6.3V C6 100µF 6.3V C5 100µF 6.3V C7 470µF 6.3V 12V 18A INTVCC R9 10k RAMP TIME tSOFTSTART = (CSS /1.3µA) • 0.6 46301 F08 Figure 8. Example of Output Tracking Application Circuit OUTPUT VOLTAGE MASTER OUTPUT SLAVE OUTPUT TIME 4630 F09 Figure 9. Output Coincident Tracking Waveform 46301fa For more information www.linear.com/LTM4630-1 19 LTM4630-1 APPLICATIONS INFORMATION Power Good The PGOOD pins are open drain pins that can be used to monitor valid output voltage regulation. This pin monitors a 10% window around the regulation point. A resistor can be pulled up to a particular supply voltage no greater than 6V maximum for monitoring. Stability Compensation The LTM4630-1 has a built-in 10pF high frequency filter capacitor from COMP to SGND on each output channel. An external RC filtering circuit is required to add from COMP to SGND to achieve fast Type II control loop compensation. Table 4 is provided for most application requirements. The Linear Technology µModule Power Design Tool (LTpowerCAD) will be provided for other control loop optimization. Run Enable The RUN pins have an enable threshold of 1.4V maximum, typically 1.25V with 150mV of hysteresis. They control the turn on each of the channels and INTVCC. These pins can be pulled up to VIN for 5V operation, or a 5V Zener diode can be placed on the pins and a 10k to 100k resistor can be placed up to higher than 5V input for enabling the channels. There is 1µA pull-up current for each RUN pin. The LTM4630-1 will turn on with RUN floating. Please note RUN has a 6V Abs Max voltage rating. The RUN pins can also be used for output voltage sequencing. In parallel operation the RUN pins can be tie together and controlled from a single control. See the Typical Application circuits in Figure 25. INTVCC and EXTVCC The LTM4630-1 module has an internal 5V low dropout regulator that is derived from the input voltage. This regulator is used to power the control circuitry and the power MOSFET drivers. This regulator can source up to 70mA, and typically uses ~30mA for powering the device at the maximum frequency. This internal 5V supply is enabled by either RUN1 or RUN2. 20 EXTVCC allows an external 5V supply to power the LTM4630-1 and reduce power dissipation from the internal low dropout 5V regulator. The power loss savings can be calculated by: (VIN – 5V) • 30mA = PLOSS EXTVCC has a threshold of 4.7V for activation, and a maximum rating of 6V. When using a 5V input, connect this 5V input to EXTVCC also to maintain a 5V gate drive level. EXTVCC must sequence on after VIN, and EXTVCC must sequence off before VIN. Differential Remote Sense Amplifier An accurate differential remote sense amplifier is provided to sense low output voltages accurately at the remote load points. This is especially true for high current loads. The amplifier can be used on one of the two channels, or on a single parallel output. It is very important that the DIFFP and DIFFN are connected properly at the output, and DIFFOUT is connected to either VOUTS1 or VOUTS2. In parallel operation, the DIFFP and DIFFN are connected properly at the output, and DIFFOUT is connected to one of the VOUTS pins. Review the parallel schematics in Figure 26 and review Figure 4. SW Pins The SW pins are generally for testing purposes by monitoring these pins. These pins can also be used to dampen out switch node ringing caused by LC parasitic in the switched current paths. Usually a series R-C combination is used called a snubber circuit. The resistor will dampen the resonance and the capacitor is chosen to only affect the high frequency ringing across the resistor. If the stray inductance or capacitance can be measured or approximated then a somewhat analytical technique can be used to select the snubber values. The inductance is usually easier to predict. It combines the power path board inductance in combination with the MOSFET interconnect bond wire inductance. 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION First the SW pin can be monitored with a wide bandwidth scope with a high frequency scope probe. The ring frequency can be measured for its value. The impedance Z can be calculated: Z(L) = 2πfL, where f is the resonant frequency of the ring, and L is the total parasitic inductance in the switch path. If a resistor is selected that is equal to Z, then the ringing should be dampened. The snubber capacitor value is chosen so that its impedance is equal to the resistor at the ring frequency. Calculated by: Z(C) = 1/(2πfC). These values are a good place to start with. Modification to these components should be made to attenuate the ringing with the least amount of power loss. Temperature Monitoring A diode connected PNP transistor is used for the TEMP monitor function by monitoring its voltage over temperature. The temperature dependence of this diode voltage can be understood in the equation: where VT is the thermal voltage (kT/q), and n, the ideality factor, is 1 for the diode connected PNP transistor being used in the LTM4630. IS is expressed by the typical empirical equation: –V IS =I0 exp G0 VT If we take the IS equation and substitute into the VD equation, then we get: V –V dVD = – G0 D dT T This dVD/dT term is the temperature coefficient equal to about –2mV/K or –2mV/°C. The equation is simplified for the first order derivation. Solving for T, T = –(VG0 – VD)/(dVD/dT) provides the temperature. 1st Example: Figure 10 for 27°C, or 300K the diode voltage is 0.598V, thus, 300K = –(1200mV – 598mV)/ –2.0 mV/K) 2nd Example: Figure 10 for 75°C, or 350K the diode voltage is 0.50V, thus, 350K = –(1200mV – 500mV)/ –2.0mV/K) Converting the Kelvin scale to Celsius is simply taking the Kelvin temp and subtracting 273 from it. A typical forward voltage is given in the electrical characteristics section of the data sheet, and Figure 10 is the plot of this forward voltage. Measure this forward voltage at 27°C to establish a reference point. Then using the above 0.8 where I0 is a process and geometry dependent current, (I0 is typically around 20k orders of magnitude larger than IS at room temperature) and VG0 is the band gap voltage of 1.2V extrapolated to absolute zero or –273°C. kT kT I VD = VG0 – ln 0 , VT = q ID q If we take this equation and differentiate it with respect to temperature T, then: ID = 100µA 0.7 DIODE VOLTAGE (V) I VD = nVT ln D IS The expression shows that the diode voltage decreases (linearly if I0 were constant) with increasing temperature and constant diode current. Figure 10 shows a plot of VD vs Temperature over the operating temperature range of the LTM4630-1. 0.6 0.5 0.4 0.3 –50 –25 50 25 0 75 TEMPERATURE (°C) 100 125 46301 F10 Figure 10. Diode Voltage VD vs Temperature T(K) for Different Bias Currents 46301fa For more information www.linear.com/LTM4630-1 21 LTM4630-1 APPLICATIONS INFORMATION expression while measuring the forward voltage over temperature will provide a general temperature monitor. Connect a resistor between TEMP and VIN to set the current to 100µA. See Figure 26 for an example. Thermal Considerations and Output Current Derating The thermal resistances reported in the Pin Configuration section of the data sheet are consistent with those parameters defined by JESD51-9 and are intended for use with finite element analysis (FEA) software modeling tools that leverage the outcome of thermal modeling, simulation, and correlation to hardware evaluation performed on a µModule package mounted to a hardware test board—also defined by JESD51-9 (“Test Boards for Area Array Surface Mount Package Thermal Measurements”). The motivation for providing these thermal coefficients is found in JESD 51-12 (“Guidelines for Reporting and Using Electronic Package Thermal Information”). Many designers may opt to use laboratory equipment and a test vehicle such as the demo board to anticipate the µModule regulator’s thermal performance in their application at various electrical and environmental operating conditions to compliment any FEA activities. Without FEA software, the thermal resistances reported in the Pin Configuration section are in-and-of themselves not relevant to providing guidance of thermal performance; instead, the derating curves provided in the data sheet can be used in a manner that yields insight and guidance pertaining to one’s application-usage, and can be adapted to correlate thermal performance to one’s own application. The Pin Configuration section typically gives four thermal coefficients explicitly defined in JESD 51-12; these coefficients are quoted or paraphrased below: 1.θJA, the thermal resistance from junction to ambient, is the natural convection junction-to-ambient air thermal resistance measured in a one cubic foot sealed enclosure. This environment is sometimes referred to as “still air” although natural convection causes the air to move. This value is determined with the part mounted to a JESD 51-9 defined test board, which does not reflect an actual application or viable operating condition. 22 2.θJCbottom, the thermal resistance from junction to the bottom of the product case, is the junction-to-board thermal resistance with all of the component power dissipation flowing through the bottom of the package. In the typical µModule, the bulk of the heat flows out the bottom of the package, but there is always heat flow out into the ambient environment. As a result, this thermal resistance value may be useful for comparing packages but the test conditions don’t generally match the user’s application. 3.θJCTOP, the thermal resistance from junction to top of the product case, is determined with nearly all of the component power dissipation flowing through the top of the package. As the electrical connections of the typical µModule are on the bottom of the package, it is rare for an application to operate such that most of the heat flows from the junction to the top of the part. As in the case of θJCBOTTOM, this value may be useful for comparing packages but the test conditions don’t generally match the user’s application. 4.θJB, the thermal resistance from junction to the printed circuit board, is the junction-to-board thermal resistance where almost all of the heat flows through the bottom of the µModule and into the board, and is really the sum of the θJCbottom and the thermal resistance of the bottom of the part through the solder joints and through a portion of the board. The board temperature is measured a specified distance from the package, using a two sided, two layer board. This board is described in JESD 51-9. A graphical representation of the aforementioned thermal resistances is given in Figure 11; blue resistances are contained within the µModule regulator, whereas green resistances are external to the µModule. As a practical matter, it should be clear to the reader that no individual or sub-group of the four thermal resistance parameters defined by JESD 51-12 or provided in the Pin Configuration section replicates or conveys normal operating conditions of a µModule. For example, in normal board-mounted applications, never does 100% of the device’s total power loss (heat) thermally conduct exclusively through the top or exclusively through bottom of the 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION JUNCTION-TO-AMBIENT RESISTANCE (JESD 51-9 DEFINED BOARD) CASE (TOP)-TO-AMBIENT RESISTANCE JUNCTION-TO-CASE (TOP) RESISTANCE JUNCTION-TO-BOARD RESISTANCE JUNCTION JUNCTION-TO-CASE CASE (BOTTOM)-TO-BOARD (BOTTOM) RESISTANCE RESISTANCE AMBIENT BOARD-TO-AMBIENT RESISTANCE 46301a F11 µMODULE DEVICE Figure 11. Graphical Representation of JESD51-12 Thermal Coefficients µModule—as the standard defines for θJCtop and θJCbottom, respectively. In practice, power loss is thermally dissipated in both directions away from the package—granted, in the absence of a heat sink and airflow, a majority of the heat flow is into the board. Within a SIP (system-in-package) module, be aware there are multiple power devices and components dissipating power, with a consequence that the thermal resistances relative to different junctions of components or die are not exactly linear with respect to total package power loss. To reconcile this complication without sacrificing modeling simplicity—but also, not ignoring practical realities—an approach has been taken using FEA software modeling along with laboratory testing in a controlled-environment chamber to reasonably define and correlate the thermal resistance values supplied in this data sheet: (1) Initially, FEA software is used to accurately build the mechanical geometry of the µModule and the specified PCB with all of the correct material coefficients along with accurate power loss source definitions; (2) this model simulates a software-defined JEDEC environment consistent with JSED51-9 to predict power loss heat flow and temperature readings at different interfaces that enable the calculation of the JEDEC-defined thermal resistance values; (3) the model and FEA software is used to evaluate the µModule with heat sink and airflow; (4) having solved for and analyzed these thermal resistance values and simulated various operating conditions in the software model, a thorough laboratory evaluation replicates the simulated conditions with thermocouples within a controlled-environment chamber while operating the device at the same power loss as that which was simulated. An outcome of this process and due-diligence yields a set of derating curves provided in other sections of this data sheet. After these laboratory test have been performed and correlated to the µModule model, then the θJB and θBA are summed together to correlate quite well with the µModule model with no airflow or heat sinking in a properly define chamber. This θJB + θBA value is shown in the Pin Configuration section and should accurately equal the θJA value because approximately 100% of power loss flows from the junction through the board into ambient with no airflow or top mounted heat sink. Each system has its own thermal characteristics, therefore thermal analysis must be performed by the user in a particular system. The LTM4630-1 module has been designed to effectively remove heat from both the top and bottom of the package. The bottom substrate material has very low thermal resistance to the printed circuit board. An external heat sink can be applied to the top of the device for excellent heat sinking with airflow. 46301fa For more information www.linear.com/LTM4630-1 23 LTM4630-1 APPLICATIONS INFORMATION Figures 12 and 13 show temperature plots of the LTM46301 with no heat sink and 200LFM airflow. These plots equate to a paralleled 12V to 1.0V at 36A design operating at 84.5% efficiency, and 12V to 1.2V at 36A design operating at 86% efficiency. Safety Considerations The LTM4630-1 modules do not provide isolation from VIN to VOUT. There is no internal fuse. If required, a slow blow fuse with a rating twice the maximum input current needs to be provided to protect each unit from catastrophic failure. The device does support over current protection. A temperature diode is provided for monitoring internal temperature, and can be used to detect the need for thermal shutdown that can be done by controlling the RUN pin. Power Derating The 1.0V and 1.5V power loss curves in Figures 15 and 16 can be used in coordination with the load current derating curves in Figures 17 to 24 for calculating an approximate ΘJA thermal resistance for the LTM4630-1 with various heat sinking and airflow conditions. The power loss curves are taken at room temperature, and are increased with a 1.35 to 1.4 multiplicative factor at 125°C. These factors come from the fact that the power loss of the regulator increases about 45% from 25°C to 150°C, thus a 50% spread over Figure 12. Thermal Image 12V to 1.0V, 36A with 200LFM Airflow without Heat Sink 24 125°C delta equates to ~0.35%/°C loss increase. A 125°C maximum junction minus 25°C room temperature equates to a 100°C increase. This 100°C increase multiplied by 0.35%/°C equals a 35% power loss increase at the 125°C junction, thus the 1.35 multiplier. The derating curves are plotted with CH1 and CH2 in parallel single output operation starting at 36A of load with low ambient temperature. The output voltages are 1.0V and 1.5V. These are chosen to include the lower and higher output voltage ranges for correlating the thermal resistance. Thermal models are derived from several temperature measurements in a controlled temperature chamber along with thermal modeling analysis. The junction temperatures are monitored while ambient temperature is increased with and without airflow. The power loss increase with ambient temperature change is factored into the derating curves. The junctions are maintained at ~120°C maximum while lowering output current or power while increasing ambient temperature. The decreased output current will decrease the internal module loss as ambient temperature is increased. The monitored junction temperature of 120°C minus the ambient operating temperature specifies how much module temperature rise can be allowed. As an example in Figure 17, the load current is derated to ~25A at ~86°C with Figure 13. Thermal Image 12V to 1.2V, 36A with 200LFM Airflow without Heat Sink 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION no air or heat sink and the power loss for the 12V to 1.0V at 25A output is a ~5.5W loss. The 5.5W loss is calculated with the ~4.1W room temperature loss from the 12V to 1.0V power loss curve at 25A, and the 1.35 multiplying factor at 125°C ambient. If the 86°C ambient temperature is subtracted from the 120°C junction temperature, then the difference of 34°C divided 5.5W equals a 6.2°C/W ΘJA thermal resistance. Table 2 specifies a 7°C/W value which is pretty close. The airflow graphs are more accurate due to the fact that the ambient temperature environment is controlled better with airflow. As an example in Figure 21, the load current is derated to ~30A at ~72°C with 200LFM of airflow and the power loss for the 12V to 1.5V at 30A output is a ~7.9W loss. The 7.9W loss is calculated with the ~5.9W room temperature loss from the 12V to 1.5V power loss curve at 22A, and the 1.35 multiplying factor at 125°C ambient. If the 72°C ambient temperature is subtracted from the 120°C junction temperature, then the difference of 48°C divided 7.9W equals a 6.0°C/W θJA thermal resistance. Table 2 specifies a 6.0°C/W value which is pretty close. Tables 2 and 3 provide equivalent thermal resistances for 1.0V and 1.5V outputs with and without airflow and heat sinking. The derived thermal resistances in Tables 2 and 3 for the various conditions can be multiplied by the calculated power loss as a function of ambient temperature to derive temperature rise above ambient, thus maximum junction temperature. Room temperature power loss can be derived from the efficiency curves and adjusted with the above ambient temperature multiplicative factors. The printed circuit board is a 1.6mm thick four layer board with two ounce copper for the two outer layers and one ounce copper for the two inner layers. The PCB dimensions are 101mm × 114mm. The BGA heat sinks are listed in Table 3. Layout Checklist/Example The high integration of LTM4630-1 makes the PCB board layout very simple and easy. However, to optimize its electrical and thermal performance, some layout considerations are still necessary. • Use large PCB copper areas for high current paths, including VIN, GND, VOUT1 and VOUT2. It helps to minimize the PCB conduction loss and thermal stress. • Place high frequency ceramic input and output capacitors next to the VIN, PGND and VOUT pins to minimize high frequency noise. • Place a dedicated power ground layer underneath the unit. • To minimize the via conduction loss and reduce module thermal stress, use multiple vias for interconnection between top layer and other power layers. • Do not put via directly on the pad, unless they are capped or plated over. • Use a separated SGND ground copper area for components connected to signal pins. Connect the SGND to GND underneath the unit. • For parallel modules, tie the VOUT, VFB, and COMP pins together. Use an internal layer to closely connect these pins together. The TRACK pin can be tied a common capacitor for regulator soft-start. • Bring out test points on the signal pins for monitoring. Figure 14 gives a good example of the recommended layout. 46301fa For more information www.linear.com/LTM4630-1 25 LTM4630-1 APPLICATIONS INFORMATION CIN1 CIN2 VIN M GND L GND K J H G SGND F COUT1 COUT2 E D C B A 1 2 3 4 5 6 7 8 9 10 11 12 GND VOUT1 VOUT2 CNTRL 4630 F14 Figure 14. Recommended PCB Layout Table 2. 1.0V Output DERATING CURVE Figures 17, 18 Figures 17, 18 Figures 17, 18 Figures 19, 20 Figures 19, 20 Figures 19, 20 VIN (V) 5, 12 5, 12 5, 12 5, 12 5, 12 5, 12 POWER LOSS CURVE Figure 15 Figure 15 Figure 15 Figure 15 Figure 15 Figure 15 AIRFLOW (LFM) 0 200 400 0 200 400 HEAT SINK None None None BGA Heat Sink BGA Heat Sink BGA Heat Sink θJA (°C/W) 7 6 5.5 6.5 5 4 VIN (V) 5, 12 5, 12 5, 12 5, 12 5, 12 5, 12 POWER LOSS CURVE Figure 16 Figure 16 Figure 16 Figure 16 Figure 16 Figure 16 AIRFLOW (LFM) 0 200 400 0 200 400 HEAT SINK None None None BGA Heat Sink BGA Heat Sink BGA Heat Sink θJA (°C/W) 7 6 5.5 6.5 4 3.5 Table 3. 1.5V Output DERATING CURVE Figures 21, 22 Figures 21, 22 Figures 21, 22 Figures 23, 24 Figures 23, 24 Figures 23, 24 HEAT SINK MANUFACTURER PART NUMBER WEBSITE Aavid Thermalloy 375424B00034G www.aavid.com 26 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 APPLICATIONS INFORMATION Table 4. Output Voltage Response vs Component Matrix (Refer to Figure 26) Load Step Typical Measured Values 2-Phase Single Output Solution CIN (CERAMIC) COUT (CERAMIC) VENDORS VALUE COUT (BULK) VENDORS VALUE PART NUMBER MURATA 22uF, 16V, X5R, 1210 GRM32ER61C226KE20L MURATA 100uF, 6.3V, GRM32ER60J107ME20L X5R, 1210 MURATA 22uF, 16V, X5R, 1206 GRM31CR61C226KE15K MURATA 220uF, 4V, X5R, 1206 TDK 22uF, 16V, X5R, 1210 C3225X5R1C226M250AA Taiyo Yuden 100uF, 6.3V, JMK325BJ107MM-T X5R, 1210 Taiyo Yuden 220uF, 4V, X5R, 1210 PART NUMBER VENDORS VALUE SANYO PART NUMBER 680uF, 2R5TPF680M6L 2.5V, 6mΩ GRM31CR60G227M AMK325ABJ227MM-T 25% Load Step (0A to 9A) Ceramic Output Capacitor Only Solutions CTRL FEEDPEAKLOOP LOAD PEAK SETTLING CTRL LOOP PHASE COMP PIN COMP PIN FORWARD STEP COUT RESISTOR CAPACITOR CAPACITOR DEVIATION TIME BANDWIDTH MARGIN LOAD SLEW (CTH) (CFF) (VPK-PK) (tSETTLE) (BW) (CERAMIC) (RTH) (PM) STEP RATE PEAK-PEAK DEVIATION PERCENTAGE CIN* CIN VIN VOUT (BULK) (CERAMIC) ±3% (<54mV) 12V 0.9V 150µF 22µF • 2 None 100µF • 12 4.22kΩ 2200pF 33pF 48mV 30µs 82kHz 50 Deg 9A 10A/µs 120.8 450kHz ±3% (<60mV) 12V 150µF 22µF • 2 None 100µF • 12 4.22kΩ 2200pF 33pF 56mV 30µs 81kHz 50 Deg 9A 10A/µs 90.9 450kHz ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 None 100µF • 10 3.74kΩ 2200pF 33pF 66mV 30µs 81kHz 51 Deg 9A 10A/µs 60.4 450kHz ±3% (<90mV) 12V 1.5V 150µF 22µF • 2 None 100µF • 8 4.01kΩ 2200pF 33pF 83mV 40µs 83kHz 50 Deg 9A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 None 100µF • 7 4.12kΩ 2200pF 33pF 94mV 50µs 81kHz 53 Deg 9A 10A/µs 30.2 450kHz ±3% (<54mV) 12V 0.9V 150µF 22µF • 2 None 220µF • 6 5.76kΩ 3300pF 33pF 45mV 50µs 80kHz 63 Deg 9A 10A/µs 120.8 450kHz ±3% (<60mV) 12V 150µF 22µF • 2 None 220µF • 6 5.76kΩ 3300pF 33pF 52mV 50µs 80kHz 61 Deg 9A 10A/µs 90.9 450kHz ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 None 220µF • 5 4.64kΩ 2200pF 33pF 65mV 50µs 81kHz 61 Deg 9A 10A/µs 60.4 450kHz ±3% (<90mV) 12V 1.5V 150µF 22µF • 2 None 220µF • 4 4.22kΩ 2200pF 33pF 84mV 50µs 81kHz 53 Deg 9A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 None 220µF • 4 4.53kΩ 2200pF 33pF 95mV 50µs 81kHz 54 Deg 9A 10A/µs 30.2 450kHz 1V 1V COUT (BULK) RFB (kΩ) FREQ (kHz) 25% Load Step (0A to 9A) Bulk + Ceramic Output Capacitor Solutions PEAK-PEAK DEVIATION PERCENTAGE CIN* CIN VIN VOUT (BULK) (CERAMIC) ±3% (<54mV) 12V 0.9V 1V 150µF 22µF • 2 COUT (BULK) 680µF • 2 CTRL FEEDPEAKLOAD LOOP PEAK SETTLING CTRL LOOP PHASE STEP COMP PIN COMP PIN FORWARD COUT RESISTOR CAPACITOR CAPACITOR DEVIATION TIME BANDWIDTH MARGIN LOAD SLEW (CTH) (CFF) (VPK-PK) (tSETTLE) (BW) (CERAMIC) (RTH) (PM) STEP RATE 100µF • 7 3.65kΩ 1500pF None 53mV 30µs RFB (kΩ) FREQ (kHz) 60kHz 60 Deg 9A 10A/µs 120.8 450kHz ±3% (<60mV) 12V 150µF 22µF • 2 680µF • 2 100µF • 7 3.65kΩ 1500pF None 60mV 30µs 60kHz 59 Deg 9A 10A/µs 90.9 450kHz ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 680µF • 2 100µF • 4 4.33kΩ 1500pF None 68mV 30µs 63kHz 68 Deg 9A 10A/µs 60.4 450kHz ±3% (<90mV) 12V 1.5V 150µF 22µF • 2 680µF • 2 100µF • 2 6.98kΩ 1500pF None 83mV 30µs 81kHz 62 Deg 9A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 680µF • 2 100µF • 1 8.45kΩ 1500pF None 96mV 30µs 80kHz 64 Deg 9A 10A/µs 30.2 450kHz 46301fa For more information www.linear.com/LTM4630-1 27 LTM4630-1 APPLICATIONS INFORMATION CIN (CERAMIC) COUT (CERAMIC) VENDORS VALUE COUT (BULK) VENDORS VALUE PART NUMBER MURATA 22uF, 16V, X5R, 1210 GRM32ER61C226KE20L MURATA 100uF, 6.3V, GRM32ER60J107ME20L X5R, 1210 MURATA 22uF, 16V, X5R, 1206 GRM31CR61C226KE15K MURATA 220uF, 4V, X5R, 1206 TDK 22uF, 16V, X5R, 1210 C3225X5R1C226M250AA Taiyo Yuden 100uF, 6.3V, JMK325BJ107MM-T X5R, 1210 Taiyo Yuden 220uF, 4V, X5R, 1210 PART NUMBER VENDORS VALUE SANYO PART NUMBER 680uF, 2R5TPF680M6L 2.5V, 6mΩ GRM31CR60G227M AMK325ABJ227MM-T 50% Load Step (0A to 18A), Ceramic Output Capacitor Only Solutions PEAK-PEAK DEVIATION PERCENTAGE CIN* CIN VIN VOUT (BULK) (CERAMIC) COUT (BULK) CTRL FEEDLOOP COMP PIN COMP PIN FORWARD PEAK-PEAK SETTLING CTRL LOOP PHASE TIME BANDWIDTH MARGIN LOAD COUT RESISTOR CAPACITOR CAPACITOR DEVIATION (CTH) (CFF) (VPK-PK) (tSETTLE) (BW) (CERAMIC) (RTH) (PM) STEP LOAD STEP SLEW RFB RATE (kΩ) FREQ (kHz) ±3% (<54mV) 12V 0.9V 150µF 22µF • 2 None 100µF • 24 6.98kΩ 3300pF 100pF 52mV 80µs 70kHz 65 Deg 18A 10A/µs 120.8 450kHz ±3% (<60mV) 12V 150µF 22µF • 2 None 100µF • 23 8.06kΩ 3300pF 100pF 58mV 80µs 80kHz 63 Deg 18A 10A/µs 90.9 450kHz ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 None 100µF • 20 6.19kΩ 3300pF 100pF 67mV 80µs 82kHz 63 Deg 18A 10A/µs 60.4 450kHz ±3% (<90mV) 1V 12V 1.5V 150µF 22µF • 2 None 100µF • 16 4.32kΩ 3300pF 100pF 88mV 80µs 70kHz 68 Deg 18A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 None 100µF • 14 4.12kΩ 3300pF 100pF 101mV 80µs 70kHz 72 Deg 18A 10A/µs 30.2 450kHz ±3% (<54mV) 22µF • 2 None 220µF • 9 7.68kΩ 3300pF 100pF 52mV 80µs 70kHz 68 Deg 18A 10A/µs 120.8 450kHz 12V 0.9V 150µF ±3% (<60mV) 12V 150µF 22µF • 2 None 220µF • 9 6.81kΩ 3300pF 100pF 58mV 80µs 70kHz 67 Deg 18A 10A/µs 90.9 450kHz ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 None 220µF • 7 5.11kΩ 3300pF 100pF 71mV 80µs 80kHz 64 Deg 18A 10A/µs 60.4 450kHz ±3% (<90mV) 12V 1.5V 150µF 22µF • 2 None 220µF • 7 5.11kΩ 3300pF 100pF 85mV 80µs 81kHz 65 Deg 18A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 None 220µF • 6 4.99kΩ 3300pF 100pF 101mV 80µs 81kHz 67 Deg 18A 10A/µs 30.2 450kHz 1V 50% Load Step (0A to 18A), Bulk + Ceramic Output Capacitor Solutions PEAK-PEAK DEVIATION PERCENTAGE CIN* CIN VIN VOUT (BULK) (CERAMIC) COUT (BULK) CTRL FEEDLOOP COMP PIN COMP PIN FORWARD PEAK-PEAK SETTLING CTRL LOOP PHASE TIME BANDWIDTH MARGIN LOAD COUT RESISTOR CAPACITOR CAPACITOR DEVIATION (CTH) (CFF) (VPK-PK) (tSETTLE) (BW) (CERAMIC) (RTH) (PM) STEP LOAD STEP SLEW RFB RATE (kΩ) FREQ (kHz) ±3% (<54mV) 12V 0.9V 150µF 22µF • 2 680µF • 2 100µF • 14 5.76kΩ 2200pF 47pF 53mV 40µs 61kHz 84 Deg 18A 10A/µs 120.8 450kHz ±3% (<60mV) 12V 22µF • 2 680µF • 2 100µF • 12 6.04kΩ 2200pF 47pF 60mV 40µs 70kHz 86 Deg 18A 10A/µs 90.9 450kHz 1V 150µF ±3% (<72mV) 12V 1.2V 150µF 22µF • 2 680µF • 2 100µF • 6 4.99kΩ 2200pF 47pF 68mV 40µs 80kHz 88 Deg 18A 10A/µs 60.4 450kHz ±3% (<90mV) 12V 1.5V 150µF 22µF • 2 680µF • 2 100µF • 4 6.98kΩ 1500pF 47pF 90mV 30µs 81kHz 95 Deg 18A 10A/µs 40.2 450kHz ±3% (<108mV) 12V 1.8V 150µF 22µF • 2 680µF • 2 100µF • 2 4.94kΩ 1000pF 47pF 101mV 25µs 80kHz 96 Deg 18A 10A/µs 30.2 450kHz 28 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 40 7 7 35 6 6 30 5 4 VIN = 5V 3 5 VIN = 12V 4 VIN = 5V 3 25 20 15 2 2 10 1 1 5 0 0 5 10 15 20 25 30 LOAD CURRENT (A) 35 0 40 0 5 10 15 20 25 30 LOAD CURRENT (A) 35 0 40 46301 F15 46301 F16 Figure 15. 1.0V Power Loss Curve Figure 16. 1.5V Power Loss Curve 0LFM 200LFM 400LFM 30 Figure 17. 12V to 1V Derating Curve, No Heat Sink 40 35 35 35 30 30 30 20 15 10 25 20 15 10 0LFM 200LFM 400LFM 5 30 40 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 5 0 40 30 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 46301 F18 Figure 18. 5V to 1V Derating Curve, No Heat Sink Figure 19. 12V to 1V Derating Curve, BGA Heat Sink 40 35 35 30 30 25 20 15 10 0 0LFM 200LFM 400LFM 30 40 20 15 0LFM 200LFM 400LFM 5 0 30 40 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 46301 F19 40 5 25 10 0LFM 200LFM 400LFM LOAD CURRENT (A) 0 LOAD CURRENT (A) 40 25 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 40 46301 F17 40 LOAD CURRENT (A) LOAD CURRENT (A) VIN = 12V LOAD CURRENT (A) 8 POWER LOSS (W) 8 LOAD CURRENT (A) POWER LOSS (W) APPLICATIONS INFORMATION 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) Figure 20. 5V to 1V Derating Curve, BGA Heat Sink 25 20 15 10 0LFM 200LFM 400LFM 5 0 30 40 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 46301 F21 Figure 21. 12V to 1.5V Derating Curve, No Heat Sink 46301 F20 46301 F22 Figure 22. 5V to 1.5V Derating Curve, No Heat Sink 46301fa For more information www.linear.com/LTM4630-1 29 LTM4630-1 APPLICATIONS INFORMATION 40 LOAD CURRENT (A) 35 30 25 20 15 10 0LFM 200LFM 400LFM 5 0 30 40 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 46301 F23 Figure 23. 12V to 1.5V Derating Curve, Heat Sink 40 LOAD CURRENT (A) 35 30 25 20 15 10 0LFM 200LFM 400LFM 5 0 30 40 50 60 70 80 90 100 110 120 AMBIENT TEMPERATURE (°C) 46301 F24 Figure 24. 5V to 1.5V Derating Curve, Heat Sink 30 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 TYPICAL APPLICATIONS INTVCC C10 4.7µF R2 10k PGOOD1 VIN 4.5V TO 15V MODE_PLLIN CLKOUT INTVCC 4.5V TO 15V INTERMEDIATE BUS + CIN (OPT) C4 22µF 25V C3 22µF 25V C2 22µF 25V C1 22µF 25V R7 100k C5 0.1µF TEMP VOUTS1 RUN1 SW1 RUN2 VFB1 C9 0.1µF CFF1* 33pF VFB2 LTM4630-1 TRACK2 TRACK2 RFB2 60.4k COMP1 4.01k 3.47k VOUTS2 2200pF VOUT2 SW2 fSET R4 121k RFB1 40.2k PHASMD SGND CBOT* CFF2* 33pF COMP2 2200pF VOUT1 COUT1 1.5V AT 18A 100µF 6.3V ×5 VOUT1 VIN TRACK1 TRACK1 EXTVCC PGOOD1 GND DIFFP DIFFN PGOOD2 DIFFOUT VOUT2 1.2V AT 18A INTVCC R3 10k PGOOD2 COUT1 100µF 6.3V ×5 *SEE TABLE 4 46301 F25 Figure 25. Typical 4.5VIN to 15VIN, 1.5V and 1.2V at 18A Outputs 46301fa For more information www.linear.com/LTM4630-1 31 32 R1 10k C3 22µF 25V TRACK C11 22µF 25V C9 0.1µF C2 22µF 25V For more information www.linear.com/LTM4630-1 R4 121k 9A STEP LOAD STEP 4A/DIV VIN 100µA SGND PHASMD fSET COMP2 COMP1 TRACK2 GND DIFFN DIFFOUT PGOOD R5 90.9k 33pF PGOOD 46301 F26 COUT1 100µF 6.3V ×12 FREQUENCY (Hz) 12VIN, 1.0VOUT, 36A Bode Plot per Above Circuit DIFFP PGOOD2 SW2 VOUT2 VOUTS2 VFB2 VFB1 SW1 RUN1 RUN2 TRACK1 VOUT1 VOUTS1 LTM4630-1 R2 10k EXTVCC PGOOD1 C10 4.7µF INTVCC TEMP CLKOUT INTVCC INTVCC VIN MODE_PLLIN RT = Figure 26. LTM4630-1 2-Phase, 1V at 36A Design with ±3% Transient Response 55mV VOUT 20mV/DIV AC-COUPLED 50µs/DIV RT 2200pF 4.22k RUN C1 22µF 25V 4.5V TO 15V INTERMEDIATE BUS 25% Load Step Transient Response ±3% Output Regulation Window. 12VIN, 1.OVOUT, 36A per Above Circuit VIN 4.5V TO 15V A/D VIN GAIN (dB) µC VOUT 1V 36A LTM4630-1 TYPICAL APPLICATIONS PHASE (Deg) 46301fa VIN 4.5V TO 15V C5 0.1µF C3 22µF 25V R9 60.4k VOUT1 1.2V C4 22µF 25V R7 90.9k For more information www.linear.com/LTM4630-1 2200pF 4.22k C1 22µF 25V R4 121k 2200pF 4.22k R6 100k SGND PHASMD fSET COMP2 COMP1 DIFFP DIFFN VFB2 TRACK1 GND VFB1 RUN2 DIFFOUT PGOOD2 SW2 VOUT2 VOUTS2 SW1 RUN1 LTM4630-1 VOUTS1 TEMP TRACK2 VOUT1 VIN R8 90.9k 33pF R5 60.4k PGOOD1 INTVCC R3 10k PGOOD2 Figure 27. LTM4630-1 1.2V and 1V Output with Tracking Function C2 22µF 25V 4.5V TO 15V INTERMEDIATE BUS R2 10k MODE_PLLIN CLKOUT INTVCC EXTVCC PGOOD1 C10 4.7µF INTVCC COUT1 100µF 6.3V ×6 33pF 4630 F27 VOUT2 1V AT 18A VOUT1 1.2V COUT1 18A 100µF 6.3V ×5 LTM4630-1 TYPICAL APPLICATIONS 46301fa 33 LTM4630-1 TYPICAL APPLICATIONS INTVCC C10 4.7µF CLK1 C3 22µF 25V C2 22µF 25V C1 22µF 25V PGOOD MODE_PLLIN CLKOUT INTVCC 4.5V TO 15V INTERMEDIATE BUS VIN 4.5V TO 15V R6 100k RUN TRACK R2 5k EXTVCC PGOOD1 VOUT1 VIN TEMP VOUTS1 RUN1 SW1 VFB1 RUN2 TRACK1 VFB2 LTM4630-1 TRACK2 33pF VFB COUT1 100µF 6.3V ×12 R5 60.4k COMP1 COMP COMP2 4.22k VOUTS2 2200pF VOUT2 SW2 fSET R4 121k PGOOD2 PHASMD SGND GND DIFFP DIFFN PGOOD DIFFOUT VOUT 1.2V 70A C16 4.7µF CLK1 MODE_PLLIN CLKOUT INTVCC 4.5V TO 15V INTERMEDIATE BUS C12 22µF 25V C15 22µF 25V C5 22µF 25V R9 100k EXTVCC PGOOD1 VOUT1 VIN RUN TRACK TEMP VOUTS1 RUN1 SW1 RUN2 VFB1 TRACK1 VFB2 LTM4630-1 TRACK2 C19 COMP 0.22µF 4.22k 2200pF R10 121k PGOOD COMP1 VOUTS2 COMP2 fSET VOUT2 46301 F28 SW2 PGOOD2 PHASMD SGND VFB COUT1 100µF 6.3V ×12 GND DIFFP DIFFN PGOOD DIFFOUT INTVCC Figure 28. LTM4630-1 4-Phase, 1.2V at 70A 34 46301fa For more information www.linear.com/LTM4630-1 LTM4630-1 PACKAGE DESCRIPTION LTM4630-1 Component BGA Pinout PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION A1 VOUT1 B1 VOUT1 C1 VOUT1 D1 GND E1 GND F1 GND A2 VOUT1 B2 VOUT1 C2 VOUT1 D2 GND E2 GND F2 GND A3 VOUT1 B3 VOUT1 C3 VOUT1 D3 GND E3 GND F3 GND A4 VOUT1 B4 VOUT1 C4 VOUT1 D4 GND E4 GND F4 MODE_PLLIN A5 VOUT1 B5 VOUT1 C5 VOUT1S D5 VFB1 E5 TRACK1 F5 RUN1 A6 GND B6 GND C6 fSET D6 SGND E6 COMP1 F6 SGND A7 GND B7 GND C7 SGND D7 VFB2 E7 COMP2 F7 SGND A8 VOUT2 B8 VOUT2 C8 VOUT2S D8 TRACK2 E8 DIFFP F8 DIFFOUT A9 VOUT2 B9 VOUT2 C9 VOUT2 D9 GND E9 DIFFN F9 RUN2 A10 VOUT2 B10 VOUT2 C10 VOUT2 D10 GND E10 GND F10 GND A11 VOUT2 B11 VOUT2 C11 VOUT2 D11 GND E11 GND F11 GND A12 VOUT2 B12 VOUT2 C12 VOUT2 D12 GND E12 GND F12 GND PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION PIN ID FUNCTION G1 GND H1 GND J1 GND K1 GND L1 GND M1 GND G2 SW1 H2 GND J2 VIN K2 VIN L2 VIN M2 VIN G3 GND H3 GND J3 VIN K3 VIN L3 VIN M3 VIN G4 PHASEMD H4 GND J4 VIN K4 VIN L4 VIN M4 VIN G5 CLKOUT H5 GND J5 GND K5 GND L5 VIN M5 VIN G6 SGND H6 GND J6 TEMP K6 GND L6 VIN M6 VIN G7 SGND H7 GND J7 EXTVCC K7 GND L7 VIN M7 VIN G8 PGOOD2 H8 INTVCC J8 GND K8 GND L8 VIN M8 VIN G9 PGOOD1 H9 GND J9 VIN K9 VIN L9 VIN M9 VIN G10 GND H10 GND J10 VIN K10 VIN L10 VIN M10 VIN G11 SW2 H11 GND J11 VIN K11 VIN L11 VIN M11 VIN G12 GND H12 GND J12 GND K12 GND L12 GND M12 GND 46301fa For more information www.linear.com/LTM4630-1 35 aaa Z 0.630 ±0.025 Ø 144x E PACKAGE TOP VIEW 3.1750 3.1750 SUGGESTED PCB LAYOUT TOP VIEW 1.9050 4 0.6350 0.0000 0.6350 PIN “A1” CORNER 1.9050 For more information www.linear.com/LTM4630-1 6.9850 5.7150 4.4450 3.1750 1.9050 0.6350 0.0000 0.6350 1.9050 3.1750 4.4450 5.7150 6.9850 Y X D DETAIL B H2 MOLD CAP ccc Z SYMBOL A A1 A2 b b1 D E e F G H1 H2 aaa bbb ccc ddd eee H1 SUBSTRATE A1 NOM 5.01 0.60 4.41 0.75 0.63 16.00 16.00 1.27 13.97 13.97 0.41 4.00 MAX 5.21 0.70 4.51 0.90 0.66 Z NOTES DETAIL B PACKAGE SIDE VIEW 0.46 4.05 0.15 0.10 0.20 0.30 0.15 TOTAL NUMBER OF BALLS: 144 0.36 3.95 MIN 4.81 0.50 4.31 0.60 0.60 b1 DIMENSIONS ddd M Z X Y eee M Z DETAIL A Øb (144 PLACES) aaa Z A2 A (Reference LTC DWG # 05-08-1969 Rev Ø) // bbb Z 36 Z BGA Package 144-Lead (16mm × 16mm × 5.01mm) e L b K J G G F E e PACKAGE BOTTOM VIEW H D C B DETAIL A A 12 11 10 9 8 7 6 5 4 3 2 1 DETAILS OF PIN #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE ZONE INDICATED. THE PIN #1 IDENTIFIER MAY BE EITHER A MOLD OR MARKED FEATURE BALL DESIGNATION PER JESD MS-028 AND JEP95 7 TRAY PIN 1 BEVEL ! PACKAGE IN TRAY LOADING ORIENTATION LTMXXXXXX µModule BGA 144 0114 REV Ø PACKAGE ROW AND COLUMN LABELING MAY VARY AMONG µModule PRODUCTS. REVIEW EACH PACKAGE LAYOUT CAREFULLY 6. SOLDER BALL COMPOSITION IS 96.5% Sn/3.0% Ag/0.5% Cu 5. PRIMARY DATUM -Z- IS SEATING PLANE 4 3 PIN 1 7 SEE NOTES 3 SEE NOTES 2. ALL DIMENSIONS ARE IN MILLIMETERS. DRAWING NOT TO SCALE NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M-1994 COMPONENT PIN “A1” F b M LTM4630-1 PACKAGE DESCRIPTION Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. 46301fa 6.9850 5.7150 4.4450 4.4450 5.7150 6.9850 LTM4630-1 REVISION HISTORY REV DATE DESCRIPTION A 08/15 Figure 3: Changed 2500 to 2600 for 1.2% Total DC Accuracy PAGE NUMBER 12 46301fa Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of itsinformation circuits as described herein will not infringe on existing patent rights. For more www.linear.com/LTM4630-1 37 LTM4630-1 PACKAGE PHOTO 46301 TA02 DESIGN RESOURCES SUBJECT DESCRIPTION µModule Design and Manufacturing Resources Design: • Selector Guides • Demo Boards and Gerber Files • Free Simulation Tools µModule Regulator Products Search 1. Sort table of products by parameters and download the result as a spread sheet. Manufacturing: • Quick Start Guide • PCB Design, Assembly and Manufacturing Guidelines • Package and Board Level Reliability 2. Search using the Quick Power Search parametric table. TechClip Videos Quick videos detailing how to bench test electrical and thermal performance of µModule products. Digital Power System Management Linear Technology’s family of digital power supply management ICs are highly integrated solutions that offer essential functions, including power supply monitoring, supervision, margining and sequencing, and feature EEPROM for storing user configurations and fault logging. RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LTM4630 Similar to LTM4630-1B But Without Guaranteed Transient Accuracy On-board Compensation Circuitry; ±1.5% Total Output DC Accuracy LTM4644 Quad Output uModule Regulator Quad 4A, Configurable Up to 16A LTM4676 µModule Regulator with Digital Telemetry PMBus Interface, On-Board EEPROM, Dual 13A, Single 26A LTM4606 Ultralow Noise Low Ripple, Low EMI for Powering High-Speed I/O, 6A LTM4641 µModule Regulator with Advanced Input and Load Protection 10A, 4.5V ≤ VIN ≤ 38V, Latchoff Overvoltage Protection, Overvoltage Crowbar, UVLO, etc. 38 Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 For more information www.linear.com/LTM4630-1 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LTM4630-1 46301fa LT 0815 REV A • PRINTED IN USA LINEAR TECHNOLOGY CORPORATION 2015