LTC3870-1 PolyPhase Step-Down Slave Controller for Digital Power System Management Description Features LTC3887-1 Phase Extender nn Operates with Power Blocks, DrMOS or External Gate Drivers and MOSFETs nn Cascade with Multiple Chips for Very Large Current Applications nn Accurate PolyPhase Current Sharing nn EXTV CC Capable of 5V to 14V Input nn Wide V Range: 4.5V to 60V IN nn Wide Output Voltage Range : 0.5V to 14V nn Wide SYNC Frequency Range: 100kHz to 1MHz nn Pin Programmable CCM/DCM Operation nn Pin Programmable Phase-Shift Control nn Available in a 24-Pin (4mm × 4mm) QFN Package nn Applications The LTC®3870-1 is a PolyPhase® step-down slave controller specially designed for multiphase operation with LTC's digital power system management DC/DC controllers. It provides a small and cost effective solution for supplying very large currents by cascading it with a LTC3887-1 controller. A peak current mode architecture provides the LTC3870-1 with excellent current sharing from phase to phase and from chip to chip. Coherently working with the LTC3887-1, the LTC3870-1 does not require additional I2C addresses, and it supports all programmable features as well as fault protection. The constant switching frequency can be synchronized to an external clock from the LTC3887-1 over a range of 100kHz to 1MHz. L, LT, LTC, LTM, PolyPhase, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents including 5481178, 5705919, 5929620, 6144194, 6177787, 6580258, 5408150 High Power Distributed Power Systems Telecom Systems nn Industrial Applications nn nn Typical Application VIN 7V TO 14V 22µF 4.7µF Load Transient Response of a 2-Phase Master (3887-1)/Slave (3870-1) Converter VIN INTVCC VCC0 ILOAD 20A/DIV 10A TO 20A TO 10A VCC1 LTC3870-1 VOUT0 3.3V, 30A 1.0µH 0.56µH DrMOS 530µF PWM0 PWM1 DrMOS 2.15k 1.74k 0.2µF LTC3887-1 RUN0 RUN1 3.3V VSENSE0+ GPIO0 GPIO1 1.8V VSENSE1+ ITH0 ITH1 SYNC * REFER TO LTC3887-1 DATA SHEET FOR MASTER SETUP 0.2µF ISENSE0+ ISENSE1+ ISENSE0- ISENSE1- RUN0 RUN1 FAULT0 FAULT1 ITH0 ITH1 SYNC VOUT1 1.8V, 40A 530µF EXTVCC FREQ PHASMD ILIM MODE0 MODE1 GND IL LTC3887–1 (CH0) 10A/DIV IL LTC3870–1 (CH0) 10A/DIV VOUT 200mV/DIV AC–COUPLED 100µs/DIV 38701 TA01b VIN = 12V VOUT = 1.8V 82.5k 38701 TA01a 38701f For more information www.linear.com/LTC3870-1 1 LTC3870-1 Absolute Maximum Ratings Pin Configuration (Note 1) PWM0 FAULT1 FAULT0 FREQ MODE0 ITH0 TOP VIEW VIN.............................................................. –0.3V to 65V VCC0, VCC1..................................................... –0.3V to 6V ISENSE0+, ISENSE0−, ISENSE1+, ISENSE1−........ –0.3V to 15V INTVCC, RUN0/RUN1................................... –0.3V to 6V EXTVCC ..................................................... –0.3V to 14V MODE0/MODE1, FREQ, PHASMD, ILIM......................... –0.3V to INTVCC FAULT0/FAULT1, ITH0/ITH1, SYNC............... –0.3V to 3.6V INTVCC, EXTVCC Peak Current (Note 7)................100mA Operating Junction Temperature Range............................. –40°C to 125°C Storage Temperature Range................... –65°C to 150°C 24 23 22 21 20 19 ISENSE0+ 1 18 VCC0 ISENSE0– 2 17 VIN RUN0 3 16 GND 25 GND RUN1 4 15 EXTVCC 13 VCC1 PWM1 PHASMD 9 10 11 12 SYNC 8 ILIM 7 ITH1 14 INTVCC ISENSE1+ 6 MODE1 ISENSE1– 5 UF PACKAGE 24-LEAD (4mm × 4mm) PLASTIC QFN TJMAX = 125°C, θJA = 46.9°C/W, θJC_BOT = 4.5°C/W EXPOSED PAD (PIN 25) IS GND, MUST BE SOLDERED TO PCB Order Information LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTC3870EUF-1#PBF LTC3870EUF-1#TRPBF 38701 24-Lead (4mm × 4mm) Plastic QFN –40°C to 125°C LTC3870IUF-1#PBF LTC3870IUF-1#TRPBF 38701 24-Lead (4mm × 4mm) Plastic QFN –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix. Electrical Characteristics The l denotes the specifications which apply over the specified operating junction temperature range, otherwise specifications are at TA = 25°C. (Note 2) VIN = 15V, VRUN0,VRUN1 = 3.3V, fSYNC = 350kHz (externally driven) unless otherwise specified. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS VIN Input Voltage Range (Note 3) 4.5 60 V VOUT Output Voltage Range (Note 4) 0.5 14 V IQ Input Voltage Supply Current Normal Operation VRUN0, VRUN1 = 0V VRUN0, VRUN1 = 3.3V 1.1 2.6 mA mA VUVLO Undervoltage Lockout Threshold when VIN > 4.2V VINTVCC Falling VINTVCC Rising 3.7 4.0 V V IISENSE0+, IISENSE1+ Current Sense + Pin Current VISENSE0,1+ = 3.3V l ±0.1 ±1 µA IISENSE0–, IISENSE1– Current Sense – Pin Current VISENSE0,1– = 3.3V l ±0.1 ±1 µA CONTROL LOOP 2 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Electrical Characteristics The l denotes the specifications which apply over the specified operating junction temperature range, otherwise specifications are at TA = 25°C. (Note 2) VIN = 15V, VRUN0,VRUN1 = 3.3V, fSYNC = 350kHz (externally driven) unless otherwise specified. SYMBOL PARAMETER CONDITIONS VIILIMIT Maximum Current Sense Threshold (High Range) VITH = 2.22V, ILIM = INTVCC MIN TYP MAX l 70 75 80 mV 50 55 mV 0.2 5 V V µA Maximum Current Sense Threshold (Low Range) VITH = 2.22V, ILIM = GND l 45 PWM Output High Voltage PWM Output Low Voltage PWM Output Current in Hi-Z State ILOAD = 500µA ILOAD = –500µA l l VCC – 0.2 Minimum On-Time (Note 5) UNITS PWM Outputs PWM tON(MIN) –5 90 ns INTVCC Regulator VINTVCC_VIN Internal VCC Voltage No Load 6.0V < VIN < 60V, VEXTVCC = 0V VLDO INT INTVCC Load Regulation ICC = 0mA to 50mA, VEXTVCC = 0V VINTVCC_EXT Internal VCC Voltage No Load VEXTVCC = 8.5V (Note 6) VLDO EXT EXTVCC Load Regulation ICC = 0mA to 20mA, VEXTVCC = 8.5V VEXTVCC EXTVCC Switchover Voltage VEXTVCC Ramping Positive (Note 6) VHYS_EXTVCC EXTVCC Hysteresis 4.85 4.85 4.65 5.1 5.35 V 0.8 ±2 % 5.1 5.35 V 0.5 ±2 % 4.8 4.95 V 200 mV Oscillator and Phase-Locked Loop fSYNC Oscillator SYNC Range VTH,SYNC SYNC Input Threshold VTH,SYNC Falling (Note 7) VTH,SYNC Rising 0.4 2.0 V V fNOM Nominal Frequency VFREQ = 1.0V 500 kHz IFREQ FREQ Setting Current qSYNC-q0 SYNC to Ch0 Phase Relationship Based on the Falling Edge of SYNC and Rising Edge of PWM0 PHASMD =0 PHASMD = 1/3 INTVCC PHASMD = 2/3 INTVCC PHASMD = INTVCC 180 60 120 90 Deg Deg Deg Deg qSYNC-q1 SYNC to Ch1 Phase Relationship Based on the Falling Edge of SYNC and Rising Edge of PWM1 PHASMD = 0 PHASMD = 1/3 INTVCC PHASMD = 2/3 INTVCC PHASMD = INTVCC 0 300 240 270 Deg Deg Deg Deg l 100 9 1000 10 11 kHz µA Digital Inputs RUN0/RUN1, MODE0/MODE1, FAULT0/FAULT1 VIH Input High Threshold Voltage l VIL Input Low Threshold Voltage l Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTC3870-1 is tested under pulsed load conditions such that TJ ≈ TA. The LTC3870E-1 is guaranteed to meet specifications from 0°C to 85°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization and correlation with statistical process controls. The LTC3870I-1 is guaranteed over the full –40°C to 125°C operating junction temperature range. Note that the maximum ambient temperature consistent with these specifications is determined by specific operating conditions in conjunction with board layout, the related package thermal 2.0 1.4 V V impedance and other environmental factors. The junction temperature TJ is calculated from the ambient temperature TA and power dissipation PD according to the following formula: TJ = TA + (PD • 46.9°C/W) Note 3: When VIN >15V, EXTVCC is recommended to reduce IC Temperature. Note 4: Output voltage is set and controlled by the master controller in multiphase operations. Note 5: The minimum on-time condition corresponds to an inductor peak-to-peak ripple current ≥40% of IMAX (see Minimum On-Time Considerations in the Applications Information section). Note 6: EXTVCC is enabled only if VIN is higher than 6.5V. Note 7: Guaranteed by design. 38701f For more information www.linear.com/LTC3870-1 3 LTC3870-1 Typical Performance Characteristics Efficiency vs Load Current Efficiency vs Load Current 100 85 CCM DCM 90 80 70 EFFICIENCY (%) EFFICIENCY (%) 100 CCM DCM 55 40 VIN = 12V VOUT = 1.8V L = 0.56µH DCR = 1.61mΩ fSW = 350kHz 25 10 0.1 1 10 LOAD CURRENT (A) 70 60 50 40 20 10 0.1 100 3874 G01 EFFICIENCY (%) 2.9 92.5 2.8 92.0 2.7 91.0 VOUT = 1.8V L = 0.56µH DCR = 1.61mΩ 5 6 7 8 9 10 11 11 12 13 14 15 16 INPUT VOLTAGE (V) 2.6 ILOAD 50A/DIV 0A TO 20A TO 0A POWER LOSS (W) 93.0 91.5 100 Load Step (Discontinuous Conduction Mode) 4-Phase Operation LTC3887-1 and LTC3870-1 3.0 EFFICIENCY POWER LOSS 1 10 LOAD CURRENT (A) 38701 G02 Full Load (ILOAD = 20A/Phase) Efficiency and Power Loss vs Input Voltage 93.5 VIN = 12V VOUT = 3.3V fSW = 350kHz L = 1µH DCR = 2.4mΩ 30 INDUCTOR CURRENT LTC3887–1 (CH0) 10A/DIV INDUCTOR CURRENT LTC3870–1 (CH0) 10A/DIV VOUT 50mV/DIV AC–COUPLED VIN = 12V VOUT = 1.0V 2.5 38701 G04 50µs/DIV 38701 G03 Load Step (Forced Continuous Mode) 4-Phase Operation LTC3887-1 and LTC3870-1 ILOAD 50A/DIV 0A TO 20A TO 0A INDUCTOR CURRENT LTC3887–1 (CH0) 10A/DIV INDUCTOR CURRENT LTC3870–1 (CH0) 10A/DIV VOUT 50mV/DIV AC–COUPLED IL LTC3870–1 (CH1) DISCONTINUOUS MODE 5A/DIV VIN = 12V VOUT = 1.0V 4 Inductor Current at Light Load IL LTC3870–1 (CH1) FORCED CONTINUOUS MODE 5A/DIV 50µs/DIV 38701 G05 1µs/DIV 38701 G06 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Typical Performance Characteristics Start-Up into a Pre-Biased Load 2-Phase Operation LTC3887-1 and LTC3870-1 Current Sense Threshold vs ITH Voltage 80 RUN ALL RUN PINS TIED TOGETHER 2V/DIV RANGE HIGH RANGE LOW VOUT LTC3870–1 IN DCM 500mV/DIV VIN = 12V VOUT = 1.8V VISENSE (mV) 60 38701 G07 2ms/DIV 40 20 0 –20 –40 0 0.5 1 1.5 VITH (V) 2 2.5 38701 G08 6.0 DC Output Current Matching in a 4-Phase Operation LTC3887-1 and LTC3870-1 INTVCC Line Regulation 30 25 CHANNEL CURRENT (A) INTVCC VOLTAGE (V) 5.0 4.0 3.0 2.0 1.0 0 20 15 10 5 0 10 20 30 40 INPUT VOLTAGE (V) 50 0 60 0 LTC3887–1 CH0 LTC3887–1 CH1 LTC3870–1 CH0 LTC3870–1 CH1 10 20 30 40 50 60 70 80 90 100 TOTAL OUTPUT CURRENT (A) 38701 G09 38701 G10 Dynamic Current Sharing During a Load Transient in a 4-Phase System LTC3887-1 and LTC3870-1 3.5 Quiescent Current vs Input Voltage without EXTVCC 3.0 SUPPLY CURRENT (mA) LTC3887–1 CH0 10A/DIV LTC3887–1 CH1 10A/DIV LTC3870–1 CH0 10A/DIV LTC3870–1 CH1 10A/DIV 50µs/DIV VIN = 12V VOUT = 1.0V ILOAD = 0A TO 32A TO 0A 38701 G11 2.5 2.0 1.5 1.0 0.5 0 0 10 20 30 40 INPUT VOLTAGE (V) 50 60 38701 G12 38701f For more information www.linear.com/LTC3870-1 5 LTC3870-1 Pin Functions ISENSE0+/ISENSE1+ (Pin 1/Pin 6): Current Sense Comparator positive inputs, normally connected to the positive node of the DCR sensing networks or current sensing resistors. ISENSE0−/ISENSE1− (Pin 2/Pin 5): Current Sense Comparator negative inputs, normally connected to the negative node of the DCR sensing network or current sensing resistors. RUN0/RUN1 (Pin 3/Pin 4): Enable Run Input Pins. A logic high on these pins enables the corresponding channel. In multiphase operation, these pins are connected to LTC3887-1's RUN pins. MODE0/MODE1 (Pin 24/Pin 7): DCM/CCM Mode Control Pins. Channel0/Channel1 operate in forced continuous mode if MODE0/MODE1 pin is logic high. There is a 500kΩ pull-down resistor on MODE0/MODE1 internally. The default operation mode in each channel is discontinuous mode operation unless these pins are actively driven high. ITH0/ITH1 (Pin 23/Pin 8): Current Control Threshold. Each associated channel’s current comparator tripping threshold increases with its ITH voltage. In multiphase operation, these pins are connected to the master controller's ITH pins for current sharing. ILIM (Pin 9): Programs Current Comparators' Sense Voltage Range. This pin can be tied to GND or INTVCC to select the maximum current sense threshold for each current comparator. GND sets both channels' current low range with maximum 50mV sensing voltage. INTVCC sets both channels' current high range with maximum 75mV sensing voltage. For equal current sharing, the setup on the ILIM pin has to be same as the setup on the bit 7 of MFR_PWM_MODE_3887-1 register in the master controller. See Table 2 in the Operation Section for details. SYNC (Pin 10): External Clock Synchronization Input. If an external clock is present at this pin, the switching frequency will be synchronized to the falling edge of the external clock. In multiphase operation, this pin is connected to LTC3887-1 SYNC pin for frequency synchronization. Do not float the SYNC Pin. 6 PHASMD (Pin 11): Phase Set Pin. This pin can be tied to GND, INTVCC or a resistor divider from INTVCC to GND. This pin determines the relative phases between the external clock on the SYNC pin and the internal controllers. See Table 1 in the Operation Section for details. PWM0/PWM1 (Pin 19/Pin 12): (Top) Gate Signal Outputs. This signal goes to the PWM or top gate input of the external driver, integrated driver MOSFET or Power Block. This is a three-state compatible output. To support three-state mode, an external resistive divider is typically used from VCC0/VCC1 to ground. VCC0/VCC1 (Pin 18/Pin 13): PWM Pin Driver Supplies. Decouple these pins to GND with a capacitor (0.1µF) or tie these pins to the INTVCC pin. PWM0/PWM1 signal swing is from ground to VCC0/VCC1. INTVCC (Pin 14): Internal Regulator 5V Output. The internal control circuits are powered from this voltage. Bypass this pin to GND with a minimum of 4.7µF low ESR tantalum or ceramic capacitor. INTVCC is enabled as soon as VIN is powered. The INTVCC pin is not short circuit proof. If overloaded, this will disrupt internal operation that can damage the part. EXTVCC (Pin 15): External power input to an internal LDO connected to INTVCC. This LDO supplies INTVCC power bypassing the internal LDO powered from VIN whenever EXTVCC is higher than 4.8V. See EXTVCC connection in the Applications Information Section. Do not exceed 14V on this pin. Bypass this pin to GND with a minimum of 4.7µF low ESR tantalum or ceramic capacitor. If the EXTVCC pin is not used, leave it open or tie it to ground. EXTVCC can be present before VIN. However, EXTVCC is enabled only if VIN is higher than 6.5V. GND (Pin 16/Exposed Pad Pin 25): Signal ground. All small-signal and compensation components should connect to this ground. The exposed pad must be soldered 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Pin Functions to the PCB ground for electrical connection and rated thermal performance. resistor on FAULT0/FAULT1 internally. These pins have to be driven high externally for normal operation. VIN (Pin 17): Main Input Supply. Bypass this pin to GND with a capacitor (0.1µF to 1µF). FREQ (Pin 22): Frequency Set Pin. There is a precision 10µA current flowing out of this pin. A resistor to ground sets a voltage which in turn programs the frequency. This pin sets the default switching frequency when there is no external clock on the SYNC pin. Setting the frequency close to the external clock helps the internal PLL sync to the SYNC pin clock quickly and smoothly. See the Application Section for the detailed information. FAULT0 /FAULT1 (Pin 21/Pin 20): Fault Input Pins. Connect these pins to the master chip GPIO pins to respond to fault signals from the master controller. If this pin is low, the PWM pin is in three-state. There is a 500kΩ pull-down Block Diagram 10µA 10 11 SYNC PHASMD SYNC DET 4.8V PHASE PROGRAM FREQ 15 EXTVCC VIN + – 27 (CH0 Shown) PFD OSC VCO S R – + ICMP 3K – + Q 5.0V 5.0V LDO EN LDO EN IREV INTVCC ON VCC0 REV UVLO 9 ILIM ILIM RANGE SELECT HI: 1:1 LO: 1:1.5 FAULT INTVCC PWM0 SWITCH LOGIC ISENSE0– + – CIN 18 L 19 DrMOS RC ISENSE0+ + – VIN 14 RUN SLOPE COMPENSATION CC VOUT0 + COUT0 1 2 INTVCC + – 500k ITH0 23 + FCNT UVLO 1 71.1k 17 1.7V REF 500k MODE0 24 RUN0 3 FAULT0 21 GND 16 38701 BD 38701f For more information www.linear.com/LTC3870-1 7 LTC3870-1 Operation Main Control Loop Start-Up and Shutdown (RUN0, RUN1) The LTC3870-1 is a constant frequency, current mode step-down slave controller for parallel operation with the LTC3887-1. During normal operation, each top MOSFET is turned on when the clock for that channel sets the RS latch, and turned off when the main current comparator, ICMP, resets the RS latch. The peak inductor current at which ICMP resets the RS latch is controlled by the voltage on the ITH pin, which is tied directly to the corresponding ITH pin of the master controllers (LTC3887-1). When the load current increases, LTC3887-1 master controllers drive and increase the ITH voltage, which in turn causes the peak current in the corresponding slave channels to increase, until the average inductor current matches the new load current. After the top MOSFET has been turned off, the bottom MOSFET is turned on until the beginning of the next cycle in Continuous Conduction Mode (CCM) or until the inductor current starts to reverse, as indicated by the reverse current comparator IREV, in Discontinuous Conduction Mode (DCM). LTC3870-1 slave controllers DO NOT regulate the output voltage but regulate the current in each channel for current sharing with master controllers. Output voltage regulation is achieved through the voltage feedback loops in the master controller. The two channels of the LTC3870-1 can independently start up and shut down using the RUN0 and RUN1 pins. Pulling either of these pins below 1.4V shuts down the control circuits for that channel. During shutdown, the PWM pin is in three-state mode. Pulling either of these pins above 2V enables the corresponding channel and internal circuits. During startup, the RUN0/RUN1 pins are actively pulled down until the INTVCC voltage passes the undervoltage lockout threshold of 4V. For multiphase parallel operation, the RUN0/RUN1 pins have to be connected and driven by the RUN pins of the master controller. Do not exceed the Absolute Maximum Rating of 6V on these pins. INTVCC/EXTVCC Power Power for most internal circuitry is derived from the INTVCC pin. Normally an internal 5.0V linear regulator supplies INTVCC power from VIN. In high VIN applications, if a high efficiency external voltage source is available for the EXTVCC pin, another internal 5.0V linear regulator is enabled and supplies INTVCC power from EXTVCC. To enable the linear regulator driven by the EXTVCC pin, VIN needs to be higher than 6.5V and EXTVCC pin voltage has to be higher than 4.8V. Do not exceed 14V on the EXTVCC pin. 8 The start-up of each channel’s output voltage VOUT is controlled and programmed by the master controller. After the RUN pins are released, the master controller drives the output based on the programmed delay time and rise time, and the slave controller LTC3870-1 just follows the master to supply equivalent current to the output during start-up. Light Load Current Operation (Discontinuous Conduction Mode, Continuous Conduction Mode) The LTC3870-1 can be set to operate either in Discontinuous Conduction Mode (DCM) or forced Continuous Conduction Mode (CCM). To select forced Continuous Mode of operation, tie the MODE pin to a DC voltage above 2V (e.g., INTVCC). To select Discontinuous Conduction Mode of operation, tie the MODE pin to a DC voltage below 1.4V (e.g., SGND). In forced continuous operation, the inductor current is allowed to reverse at light loads or under large transient conditions. The peak inductor current is determined by the voltage on the ITH pin. In this mode, the efficiency at light loads is lower than in discontinuous mode operation. However, continuous mode has the advantages of lower output ripple and less interference with audio circuitry. When the MODE pin is connected to 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Operation GND, the LTC3870-1 operates in discontinuous mode at light loads. At very light loads, the current comparator ICMP may remain tripped for several cycles and force the external top MOSFET to stay off for the same number of cycles (i.e., skipping pulses). This mode provides higher light load efficiency than forced continuous mode and the inductor current is not allowed to reverse. There are 500kΩ pull-down resistors internally connected to the MODE0/MODE1 pins. If MODE0/MODE1 pins are floating, both channels default to Discontinuous Conduction Mode. Multichip Operation (PHASMD and SYNC Pins) The PHASMD pin determines the relative phases between the internal channels as well as the external clock signal on the SYNC pin, as shown in Table 1. The phases tabulated are relative to zero degree phase being defined as the falling edge of the clock on SYNC. Table 1. PHASMD Channel 0 Phase Channel 1 Phase GND 180° 0° 1/3 INTVCC 60° 300° 2/3 INTVCC or Float 120° 240° INTVCC 90° 270° The SYNC pin is used to synchronize switching frequency between master and slave controllers. Input capacitance ESR requirements and efficiency losses are substantially reduced because the peak current drawn from the input capacitor is effectively divided by the number of phases used and power loss is proportional to the RMS current squared. A two-phase, single output voltage implementation can reduce input path power loss by 75% and radically reduce the required RMS current rating of the input capacitor(s). Single Output Multiphase Operation The LTC3870-1 is designed for multiphase converters with the LTC3887-1 by making these connections: • Tie all the ITH pins of paralleled channels together for current sharing between masters and slaves. Note that ILIM setup on slaves has to match MFR_PWM_MODE current range setup in masters. • Tie all SYNC pins together between master and slaves for same switching frequency synchronization; one and only one of the LTC3887-1 controllers has to be programmed as master to generate clock signal on the SYNC pin. • Tie all the RUN pins of paralleled channels together between master and slaves for startup and shutdown sequences. • Tie the GPIO pin of the master controller to the FAULT pin of slave controller and program the master GPIO as fault sharing for fault protection. Examples of single output multiphase converters are shown in Figure 1. Inductor Current Sensing Like the LTC3887-1, the LTC3870-1 can use either inductor DCR or RSENSE to sense the inductor current. Inductor DCR current sensing provides a lossless method of sensing the instantaneous current. Therefore, it can provide higher efficiency for applications with high output currents. However, the DCR of a copper inductor typically has 10% tolerance. For precise current sensing, a precision sensing resistor RSENSE can be used to sense the inductor current. It is important to match the current sensing circuit between master controllers and slave controllers to guarantee balanced load sharing and overcurrent protection. 38701f For more information www.linear.com/LTC3870-1 9 LTC3870-1 Operation 2 + 2 OPERATION CH0 CH1 1 + 3 OPERATION CH0 0° CH1 120° 180° CH0 240° LTC3870-1 LTC3887-1 CH1 0° 180° LTC3887-1 PHASMD = 2/3 INTVCC OR FLOAT CH0 CH1 180° 0° LTC3870-1 PHASMD = GND 4 PHASE OPERATION CH0 CH1 90° 270° LTC3870-1 6 PHASE OPERATION CH0 CH1 0° CH0 180° LTC3887-1 PHASMD = INTVCC CH1 0° 180° LTC3887-1 CH0 CH1 60° 300° CH0 CH1 120° 240° LTC3870-1 LTC3870-1 PHASMD = 1/3 INTVCC PHASMD = 2/3 INTVCC 38701 F01 Figure 1. Examples of Single/Dual Output Multiphase Converters Frequency Selection and Phase-Locked Loop (FREQ and SYNC Pins) The selection of switching frequency is a trade-off between efficiency and component size. Low frequency operation increases efficiency by reducing MOSFET switching losses, but requires larger inductance and/or capacitance to maintain low output ripple voltage. The switching frequency of the LTC3870-1 controllers can be synchronized to the falling edge of the external clock on the SYNC pin or selected using the FREQ pin. A phase-locked loop (PLL) is integrated in the LTC3870-1 to synchronize the internal oscillator to an external clock source that is connected to the SYNC pin; this source is normally provided by the master controllers. The PLL loop filter network is 10 integrated inside the LTC3870-1. The phase-locked loop is capable of locking to any frequency within the range of 100kHz to 1MHz. If the SYNC pin is not being driven by an external clock source, the FREQ pin can be used to program the LTC3870-1’s operating frequency from 100kHz to 1MHz. There is a precision 10µA current flowing out of the FREQ pin, so the user can program the controller’s switching frequency with a single resistor to SGND. A curve is provided later in the application section showing the relationship between the voltage on the FREQ pin and switching frequency. The frequency setting resistor should always be present to set the controller’s initial switching frequency before locking to the external clock. 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Applications Information The Typical Application on the first page of this data sheet is a basic LTC3870-1 application circuit featuring the LTC3887-1 as a slave controller. In paralleled operation, the current sensing scheme as well as the power stage parameters in LTC3870-1 must be the same as the master controller to achieve balanced current sharing between masters and slaves. Finally, input and output capacitors are selected based on RMS current rating, ripple, and transient specs. Current Limit Programming To match the master controller current limit, each channel of the LTC3870-1 can be programmed separately with two current ranges. The ILIM pin of LTC3870-1 is a 4-level logic input which sets the current limit of LTC3870-1. When ILIM is grounded, both channel0 and channel1 are set to be low current range. When ILIM is tied to INTVCC, both channel0 and channel1 are set to be high current range. Here, low current range means the current sense threshold linearly increases from 0mV to 50mV as ITH voltage is increased from 0.5V to 2.22V without slope compensation. High current range means the current sense threshold increases to 75mV as ITH voltage is increased to 2.22V without slope compensation. Set ILIM to one-third INTVCC for channel0 high current range and channel1 low current range. Set ILIM to two-thirds INTVCC or float for channel0 low current range and channel1 high current range. The summary of ILIM pin setups is shown in Table 2. For balanced load current sharing, use the same current range setting as in the master controller. Note that the LTC3870-1 does not have active clamping circuit on the ITH pin for peak current limit and over current protection. Over current protection relies on the master controller to drive and clamp the ITH pin voltage not to exceed the programmed voltage through the PMBus command. Table 2. Current Limit Programming INTVCC Regulators and EXTVCC The LTC3870-1 includes a PMOS LDO that supplies power to INTVCC from the VIN supply. INTVCC powers most of the LTC3870-1’s internal circuitry. The linear regulator regulates the voltage at the INTVCC pin to 5.0V when VIN is greater than 6V. EXTVCC connects to INTVCC through another PMOS LDO and can supply the needed power when its voltage is higher than 4.8V and VIN is higher than 6.5V. Each of these LDOs can supply a peak current of 100mA and must be bypassed to ground with a minimum of 4.7µF ceramic capacitor or low ESR electrolytic capacitor. No matter what type of bulk capacitor is used, an additional 0.1µF ceramic capacitor placed directly adjacent to the INTVCC and PGND pins is highly recommended. Good bypassing is needed to prevent interaction between the channels. The INTVCC pin is not short-circuit proof. If overloaded, this will disrupt internal operation that can damage the part. When the voltage applied to EXTVCC rises above 4.8V and VIN above 6.5V, the INTVCC linear regulator is turned off and the EXTVCC linear regulator is turned on. Using the EXTVCC allows the control power to be derived from other high efficiency sources such as +5V or +12V rails in the system. Do not apply more than 14V to the EXTVCC pin. For applications where the main input power is 5V, tie the VIN and INTVCC pins together and tie the combined pins to the 5V input with a 1Ω or 2.2Ω resistor as shown in Figure 2 to minimize the voltage drop. This will override the INTVCC linear regulator and will prevent INTVCC from dropping too low due to the dropout voltage. Make sure the INTVCC voltage is at or exceeds the RDS(ON) test voltage for the external power MOSFETs which is typically 4.5V for logic-level devices. LTC3870-1 ILIM Channel 0 Current limit Channel 1 Current limit GND Range Low Range Low 1/3 INTVCC Range High Range Low 2/3 INTVCC or Float Range Low Range High INTVCC Range High Range High VIN INTVCC GND RVIN 1Ω 5V CINTVCC 4.7µF + CIN 38701 F04 Figure 2. Setup for a 5V Input 38701f For more information www.linear.com/LTC3870-1 11 LTC3870-1 Applications Information Undervoltage Lockout 1400 The LTC3870-1 has a precision UVLO comparator constantly monitoring the INTVCC voltage. It locks out the switching action and pulls down the RUN pins when INTVCC is below 3.7V. To prevent oscillation when there is a disturbance on the INTVCC, the UVLO comparator has 300mV of precision hysteresis. In multiphase operation, when LTC3870-1 is in undervoltage lockout, the RUN0 and RUN1 pins are pulled down to disable the master’s switching action. SWITCHING FREQUENCY (kHz) 1200 1000 800 600 400 200 0 0 Phase-Locked Loop and Frequency Synchronization The LTC3870-1 has a phase-locked loop (PLL) comprised of an internal voltage-controlled oscillator (VCO) and a phase detector. This allows the internal clock to be locked to the falling edge of an external clock signal applied to the SYNC pin. The turn-on of channel 0/channel 1’s top MOSFET is synchronized or out-of-phase with the falling edge of the external clock. The phase detector is an edge sensitive digital type that provides zero degree phase shift between the external and internal oscillators. This type of phase detector does not exhibit false lock to harmonics of the external clock. The output of the phase detector is a pair of complementary current sources that charge or discharge the internal filter network. There is a precision 10µA of current flowing out of the FREQ pin. This allows the user to use a single resistor to GND to set the switching frequency when no external clock is applied to the SYNC pin. The voltage on the FREQ pin is equal to the resistance multiplied by 10µA current (e.g. the voltage is 1V with a 100k resistor from the FREQ pin to SGND). The internal switch between FREQ pin and the integrated PLL filter network is ON, allowing the filter network to be pre-charged to the same voltage potential as the FREQ pin. The relationship between the voltage on the FREQ pin and the operating frequency is shown in Figure 3 and specified in the Electrical Characteristics table. If an external clock is detected on the SYNC pin, the internal switch mentioned above will turn off and isolate the influence of FREQ pin. Note that the LTC3870-1 can only be synchronized to an external clock whose frequency is 12 0.5 1 1.5 FREQ PIN VOLTAGE (V) 2 2.5 38701 F02 Figure 3. Relationship Between Oscillator Frequency and Voltage at the FREQ Pin 2.4V 5V RSET 10µA FREQ EXTERNAL OSCILLATOR SYNC DIGITAL SYNC PHASE/ FREQUENCY DETECTOR VCO 38701 F03 Figure 4. Phase-Locked Loop Block Diagram within the range of the LTC3870-1’s internal VCO. This is guaranteed to be between 100kHz and 1MHz. A simplified block diagram is shown in Figure 4. If the external clock frequency is greater than the internal oscillator’s frequency, fOSC, then current is sourced continuously from the phase detector output, pulling up the filter network. When the external clock frequency is less than fOSC, current is sunk continuously, pulling down the filter network. If the external and internal frequencies are the same but exhibit a phase difference, the current sources turn on for an amount of time corresponding to 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Applications Information the phase difference. The voltage on the filter network is adjusted until the phase and frequency of the internal and external oscillators are identical. At the stable operating point, the phase detector output is high impedance and the filter capacitor holds the voltage. Typically, the external clock (on the SYNC pin) input high threshold is 2V, while the input low threshold is 0.4V. Fault Protection and Responses LTC3887-1 master controllers monitor system voltage, current, and temperature and provide many protection features during fault conditions. LTC3870-1 slave controllers do not provide as many fault monitors as master controllers and have to respond to fault signals from the master controller. FAULT0 and FAULT1 pins are designed to share fault signals between masters and slaves. In a typical parallel application, connect the FAULT pins on LTC3870-1 to the master GPIO pins of the corresponding paralleled channels and program the master GPIO as fault sharing, so that the slave controller can respond to all fault protections from the master. When the FAULT pin is pulled below 1.4V, the PWM pin in the corresponding channel is in three-state. When the FAULT pin voltage is above 2V, the corresponding channel returns to normal operation. During fault conditions, all internal circuits in LTC3870-1 are still running so the slave controllers can immediately go back to normal operation when the FAULT pin is released. LTC3870-1 has internal thermal shutdown protection which forces the PWM pin three-state when the junction temperature is higher than 160°C. In thermal shutdown, FAULT0 and FAULT1 pins are also pulled low. There is a 500kΩ pull-down resistor on each FAULT pin which sets the default voltage on FAULT pins low if FAULT pins are left floating. Transient Response and Loop Stability In a typical parallel operation, LTC3870-1 cooperates with master controllers to supply more current. To achieve balanced current sharing between master and slave, it is recommended that each slave channel copy the design from the master channel. Select same inductors, same MOSFET driver, same current sensing circuit and same output capacitors between the master channel and slave channels. Control loop and compensation design on the ITH pin should start with the single phase operation of the master controller. If the master and slave channels are exactly the same, then the transient response and loop stability of the multiphase design is almost the same as the single phase operation of the master by tying the ITH pins together between the master and slaves. For example, design the compensation for a single phase 1.8V/20A output using LTC3887-1 with a 0.56µH inductor and 530µF output capacitors. To extend the output to 1.8V/40A, simply parallel one channel of LTC3870-1 with the same inductor and output capacitors (total output capacitors are 1060µF) and tie the ITH pin of LTC3870-1 to the master ITH. The loop stability and transient responses of the two phase converter are very similar to the single phase design without any extra compensator on the ITH pin of LTC3870-1 slave controller. Furthermore, LTpowerCAD is provided on the LTC website as a free download for transient and stability analysis. To minimize the high frequency noise on the ITH trace between master and slave ITH pins, a small filter capacitor in the range of tens of pF can be placed closely at each ITH pin of the slave controller. This small capacitor normally does not significantly affect the closed loop bandwidth but increases the gain margin at high frequency. Mode Selection and Pre-Biased Startup There may be situations that require the power supply to start up with a pre-bias on the output capacitors. In this case, it is desirable to start up without discharging the output capacitors. The LTC3870-1 can be configured to DCM mode for pre-biased start-up. If a PGOOD signal is available on the master controller, the PGOOD pin can be connected to MODE pins of LTC3870-1 to ensure DCM operation at startup and CCM operation at steady state. 38701f For more information www.linear.com/LTC3870-1 13 LTC3870-1 Applications Information Minimum On-Time Considerations PC Board Layout Checklist Minimum on-time tON(MIN) is the smallest time duration that the LTC3870-1 is capable of turning on the top MOSFET. It is determined by internal timing delays and the gate charge required to turn on the top MOSFET. Low duty cycle applications may approach this minimum on-time limit and care should be taken to ensure that: When laying out the printed circuit board, the following checklist should be used to ensure proper operation of the IC. Figure 5 illustrates the current waveforms present in the various branches of the 2-phase synchronous regulators operating in the continuous mode. Check the following in the PC layout: tON(MIN) < TSW VOUT/VIN 1.Are the signal and power grounds kept separate? The combined IC signal ground pin and the ground return of CINTVCC must return to the combined COUT (–) terminals. The ITH traces should be as short as possible. The CIN capacitor should have short leads and PC trace lengths. The output capacitor (–) terminals should be connected as close as possible to the (–) terminals of the input capacitor by placing the capacitors next to each other. where TSW is the switching period. If the duty cycle falls below what can be accommodated by the minimum on-time, the controller will begin to skip cycles. The output voltage will continue to be regulated, but the ripple voltage and current will increase. The minimum on-time for the LTC3870-1 is approximately 90ns, with reasonably good PCB layout, minimum 30% inductor current ripple and at least 10mV ripple on the current sense signal. The minimum on-time can be affected by PCB switching noise in the current loop. As the peak sense voltage decreases, the minimum on-time gradually increases to 130ns. This is of particular concern in forced continuous applications with low ripple current at light loads. If the duty cycle drops below the minimum on-time limit in this situation, a significant amount of cycle skipping can occur with correspondingly larger current and voltage ripple. PWM Pins The PWM output pins are three-state compatible outputs, designed to drive MOSFET drivers, DrMOSs, etc. which do not represent a heavy capacitive load. An external resistor divider may be used to set the voltage to mid-rail while in the high impedance state. The VCC pin is the corresponding PWM pin driver supply. Decouple this pin to GND with a capacitor (0.1µF) or tie this pin to the INTVCC pin. MOSFET Driver Selection Gate driver ICs, DrMOSs and power blocks with an interface compatible with the LTC3870-1’s three-state PWM outputs can be used. 14 2.Are the ISENSE+ and ISENSE– leads routed together with minimum PC trace spacing? The filter capacitor between ISENSE+ and ISENSE– should be as close as possible to the IC. Ensure accurate current sensing with Kelvin connections at the sense resistor or inductor, whichever is used for current sensing. 3.Is the INTVCC bypassing capacitor connected close to the IC, between the INTVCC and the ground pins? An additional 1µF ceramic capacitor placed immediately next to the INTVCC and PGND pins can help improve noise performance substantially. 4.Keep the switching nodes (SW1, SW0), away from sensitive small-signal nodes, especially from the opposite channel’s current sensing feedback pins. All of these nodes have very large and fast moving signals and therefore should be kept on the “output side” of the LTC3870-1 and occupy minimum PC trace area. If DCR sensing is used, place the right resistor (Block Diagram, “RC”) close to the switching node. 5.Use a modified “star ground” technique: a low impedance, large copper area central grounding point on the same side of the PC board as the input and output capacitors with tie-ins for the bottom of the INTVCC bypassing capacitor, the bottom of the voltage feedback resistive divider and the GND pin of the IC. 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Applications Information PC Board Layout Debugging Start with one controller at a time. It is helpful to use a DC-50MHz current probe to monitor the current in the inductor while testing the circuit. Monitor the output switching node (SW pin) to synchronize the oscilloscope to the internal oscillator and probe the actual output voltage as well. Check for proper performance over the operating voltage and current range expected in the application. The frequency of operation should be maintained over the input voltage range down to dropout and until the output load drops below the low current operation threshold— typically 10% of the maximum designed current level in Burst Mode operation. The duty cycle percentage should be maintained from cycle to cycle in a well-designed, low noise PCB implementation. Variation in the duty cycle at a sub-harmonic rate can suggest noise pickup at the current or voltage sensing inputs or inadequate loop compensation. Overcompensation of the loop can be used to tame a poor PC layout if regulator bandwidth optimization is not required. Only after each controller is checked for its individual performance should both controllers be turned on at the same time. A particularly difficult region of operation is when one controller channel is nearing its current comparator trip point when the other channel is turning on its top MOSFET. This occurs around 50% duty cycle on either channel due to the phasing of the internal clocks and may cause minor duty cycle jitter. Reduce VIN from its nominal level to verify operation of the regulator in dropout. Check the operation of the undervoltage lockout circuit by further lowering VIN while monitoring the outputs to verify operation. Investigate whether any problems exist only at higher output currents or only at higher input voltages. If problems coincide with high input voltages and low output currents, look for capacitive coupling between the BOOST, SW, TG, and possibly BG connections and the sensitive voltage and current pins. The capacitor placed across the current sensing pins needs to be placed immediately adjacent to the pins of the IC. This capacitor helps to minimize the effects of differential noise injection due to high frequency capacitive coupling. If problems are encountered with high current output loading at lower input voltages, look for inductive coupling between CIN, Schottky and the top MOSFET components to the sensitive current and voltage sensing traces. In addition, investigate common ground path voltage pickup between these components and the SGND pin of the IC. Design Example As a design example using master chip LTC3887-1 and slave chip LTC3870-1 for a 4-phase high current regulator, assume VIN = 12V (nominal), VIN = 14V (maximum), VOUT = 1.0V, IMAX = 120A, and f = 425kHz (see Typical Applications). The master chip LTC3887-1 design can be found in the LTC3887-1 data sheet Design Example section. LTC3887-1's SYNC pin is connected to LTC3870-1's SYNC pin and LTC3870-1's PHASMD is connected to LTC3870-1’s GND. Slave chip LTC3870-1 should use the same inductor, DrMOS, CIN, and COUT as the master chip. DCR sensing is also used for the slave chip. LTC3870-1's ILIM pin is forced to 0V to match the master chip's 50mV current limit. Both chips' VIN, VOUT, RUN, ITH pins are connected together. LTC3887-1's GPIO pins are connected to LTC3870-1's FAULT pins so the slave controller will be disabled during fault conditions. 38701f For more information www.linear.com/LTC3870-1 15 LTC3870-1 Applications Information SW1 L1 VOUT1 COUT1 D1 RL1 VIN RIN CIN SW0 BOLD LINES INDICATE HIGH SWITCHING CURRENT. KEEP LINES TO A MINIMUM LENGTH. L0 D0 VOUT0 COUT0 RL0 38701 F05 Figure 5. Branch Current Waveforms 16 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Typical Applications High Efficiency 350kHz 2-Phase 3.3V and 2-Phase 1.8V Step-Down Converters 2Ω VIN 7V TO 14V 0.1µF VOUT1 VOUT0 10nF VIN 22µF x 2 25V LTC3887-1 5k 5k 5k 5k 4.7µF 5k 5k 5k 4700pF 5k 5k 180pF 10k TSNS1 10Ω VDR 5V SHARE_CLK 1µF 1µF 0Ω PHASE VIN BOOT 2k 2k 1µF L1 1.0µH FDMF6820A GH GL PWM VSWH VDRV THWN# DISB# PGND VCIN SMOD# CGND 2k VOUT0 3.3V/30A COUT1 100µF x 2 6.3V + COUT2 330µF 6.3V SCL ALERT ISENSE1– ISENSE1+ SDA VDD33 PWM1 VDD25 100nF 100nF VOUT0_CFG GPIO0 GPIO1 VOUT1_CFG ASEL1 ASEL0 RUN0 RUN1 FREQ_CFG SYNC ITH0 ITH1 1500pF 13.7k 0.22µF 100nF PWM0 TSNS0 10nF 2.55k 4.7µF VIN INTVCC VSENSE1 VCC0 VSENSE0+ VCC1 VSENSE0– ISENSE0– WP ISENSE0+ 15.8k 10k 17.4k 16.2k 17.4k 16.2k 3.57k PHAS_CFG VIN 22µF x 2 25V 10k 10Ω VDR 5V 1µF 30.1k 1µF VIN BOOT 0Ω PHASE 1.58k FDMF6820A GH GL PWM VSWH VDRV THWN# DISB# PGND VCIN SMOD# CGND 2k 1.58k 1µF L2 0.56µH VOUT1 1.8V/40A COUT3 100µF x 2 6.3V + COUT4 330µF 6.3V 1µF GND 75pF 0.22µF VIN 7V TO 14V 100nF 2Ω VIN 0.1µF 180pF 75pF RUN0 RUN1 SYNC ITH0 ITH1 VCC0 VCC1 ISENSE0– ISENSE0+ FAULT0 FAULT1 ISENSE1– ISENSE1+ EXTVCC PWM1 10k 10Ω VDR 5V PWM0 LTC3870-1 FREQ PHASMD ILIM MODE0 MODE1 GND 22µF x 2 25V 4.7µF VIN INTVCC 1µF 1µF 0Ω PHASE VIN BOOT 2k 2k 1µF L3 1.0µH FDMF6820A GH GL PWM VSWH VDRV THWN# DISB# PGND VCIN SMOD# CGND 2k COUT5 100µF x 2 6.3V + COUT6 330µF 6.3V 100nF 100nF 82.5k VIN 22µF x 2 25V 10k VDR 5V 10Ω 1µF 1µF VIN BOOT PHASE FDMF6820A GH GL PWM VSWH VDRV THWN# DISB# PGND VCIN SMOD# CGND 2k COUT1,3,5,7: Murata GRM32ER60J107ME20L (100µF, 6.3V, X5R, 1210) COUT2,4,6,8: SANYO 6TPE330MFL (330µF, 6.3V) L1, L3: VISHAY IHLP-4040DZ-11 (1.0µH, DCR = 2.4mΩ) L2, L4: VISHAY IHLP-4040DZ-11 (0.56µH, DCR = 1.61mΩ) 0Ω 1.58k 1.58k 1µF L4 0.56µH COUT7 100µF x 2 6.3V + COUT8 330µF 6.3V 38701 TA02 38701f For more information www.linear.com/LTC3870-1 17 LTC3870-1 Typical Applications High Efficiency 425kHz 4-Phase 1.0V Step-Down Converter VIN 7V TO 14V 2Ω 0.1µF VOUT 4.7µF INTVCC VCC0 VCC1 ISENSE0– ISENSE0+ VIN VSENSE1 VSENSE0+ ISENSE0– WP 10nF 100nF 100nF VIN 22µF x 2 25V PWM0 TSNS0 10nF 5k 5k 5k 5k 4.7µF 5k 5k 5k 4700pF 2.55k 10k VDR 5V LTC3887-1 1µF TSNS1 1µF VIN BOOT 0Ω PHASE 1.78k GL SW TMON EN/FAULT# PGND VCC ZCD# AGND 10k 1.78k L1 0.16µH FDMF5820DC PWM PVCC 1µF VOUT 1.0V/120A COUT1 100µF x 6 6.3V + 25k COUT2 470µF 2.5V 0.1µF SDA ISENSE1– ISENSE1+ SCL 100nF PWM1 VDD25 ALERT 100nF SHARE_CLK VOUT0_CFG VOUT1_CFG VDD33 ASEL1 ASEL0 GPIO0 GPIO1 FREQ_CFG RUN0 RUN1 SYNC ITH0 ITH1 PHAS_CFG 7.32k 24.9k 17.8k 20k 4.32k 24.9k 1.96k GND VIN 22µF x 2 25V 10k VDR 5V 1µF 30.1k 1µF VIN BOOT 0Ω PHASE 1.78k FDMF5820DC GL SW TMON EN/FAULT# PGND VCC ZCD# AGND 10k 1.78k 1µF L2 0.16µH PWM PVCC COUT3 100µF x 6 6.3V + 25k COUT4 470µF 2.5V 0.1µF 1µF 47pF 100nF VIN 7V TO 14V 100nF 2Ω VIN 0.1µF 47pF RUN0 RUN1 SYNC ITH0 ITH1 VCC0 VCC1 ISENSE0– ISENSE0+ 10k VDR 5V PWM0 LTC3870-1 FAULT0 FAULT1 EXTVCC 22µF x 2 25V 4.7µF VIN INTVCC 1µF 1µF VIN BOOT PHASE 1.78k GL SW TMON EN/FAULT# PGND VCC ZCD# AGND 10k 1.78k 1µF L3 0.16µH FDMF5820DC PWM PVCC COUT5 100µF x 6 6.3V + 25k COUT6 470µF 2.5V 0.1µF ISENSE1– ISENSE1+ 100nF PWM1 FREQ PHASMD ILIM MODE0 MODE1 GND 100nF 100k VIN 22µF x 2 25V 10k VDR 5V 1µF 1µF VIN BOOT 0Ω PHASE 1.78k FDMF5820DC GL SW TMON EN/FAULT# PGND VCC ZCD# AGND 10k 1.78k 1µF L4 0.16µH PWM PVCC COUT1,3,5,7: Murata GRM32ER60J107ME20L (100µF, 6.3V, X5R, 1210) COUT2,4,6,8: SANYO 2R5TPE470M9 (470µF, 2.5V) L1-4: COILCRAFT XAL7070-161 (0.16µH, DCR = 0.75mΩ) 18 0Ω COUT7 100µF x 6 6.3V + 25k 0.1µF COUT8 470µF 2.5V 38701 TA03 38701f For more information www.linear.com/LTC3870-1 LTC3870-1 Package Description Please refer to http://www.linear.com/product/LTC3870-1#packaging for the most recent package drawings. UF Package 24-Lead Plastic QFN (4mm × 4mm) (Reference LTC DWG # 05-08-1697 Rev B) 0.70 ±0.05 4.50 ±0.05 2.45 ±0.05 3.10 ±0.05 (4 SIDES) PACKAGE OUTLINE 0.25 ±0.05 0.50 BSC RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 4.00 ±0.10 (4 SIDES) BOTTOM VIEW—EXPOSED PAD R = 0.115 TYP 0.75 ±0.05 PIN 1 NOTCH R = 0.20 TYP OR 0.35 × 45° CHAMFER 23 24 PIN 1 TOP MARK (NOTE 6) 0.40 ±0.10 1 2 2.45 ±0.10 (4-SIDES) (UF24) QFN 0105 REV B 0.200 REF 0.00 – 0.05 0.25 ±0.05 0.50 BSC NOTE: 1. DRAWING PROPOSED TO BE MADE A JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGD-X)—TO BE APPROVED 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE, IF PRESENT 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 38701f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representaFor more www.linear.com/LTC3870-1 tion that the interconnection of itsinformation circuits as described herein will not infringe on existing patent rights. 19 LTC3870-1 Typical Application 4-Phase 1.5V/80A Step-Down Converter with Sensing Resistors VIN 7V TO 14V 4.7µF 0.0015Ω + VIN INTVCC VCC0 VCC1 DrMOS: FAIRCHILD FDMF6820A LTC3870-1 0.42µH DrMOS PWM0 0.42µH PWM1 DrMOS + 530µF 100Ω 1000pF 100Ω LTC3887-1 RUN0 RUN1 1.5V VSENSE0+ GPIO0 GPIO1 VSENSE1+ ITH0 ITH1 SYNC ISENSE0+ ISENSE1+ ISENSE0- ISENSE1- 0.0015Ω 530µF VOUT 1.5V 80A 100Ω 1000pF 100Ω EXTVCC RUN0 RUN1 FAULT0 FAULT1 ITH0 ITH1 SYNC * REFER TO LTC3887-1 DATA SHEET FOR MASTER SETUP FREQ PHASMD ILIM MODE0 MODE1 GND 84.5k 38701 TA04 Related Parts PART NUMBER DESCRIPTION COMMENTS LTM4676A Dual 13A or Single 26A Step-Down DC/DC µModule Regulator with Digital Power System Management 4.5V ≤ VIN ≤ 17V, 0.5V ≤ VOUT (±0.5%) ≤ 5.5V, I2C/PMBus Interface, 16mm × 16mm × 5mm, BGA Package LTM4675 Dual 9A or Single 18A μModule Regulator with Digital Power System Management 4.5V ≤ VIN ≤1 7V; 0.5V ≤ VOUT (±0.5%) ≤ 5.5V, I2C/PMBus Interface, 11.9mm × 16mm × 5mm, BGA Package LTM4677 Dual 18A or Single 18A μModule Regulator with Digital Power System Management 4.5V ≤ VIN ≤ 16V; 0.5V ≤ VOUT (±0.5%) ≤ 1.8V, I2C/PMBus Interface, 16mm × 16mm × 5.01mm, BGA Package LTC3884 Dual Output Multiphase Step-Down Controller with Sub MilliOhm DCR 4.5V ≤ VIN ≤ 38V, 0.5V ≤ VOUT (±0.5%) ≤ 5.5V, 70ms Start-Up, I2C/PMBus Sensing Current Mode Control and Digital Power System Management Interface, Programmable Analog Loop Compensation, Input Current Sense LTC3887/ Dual Output Multiphase Step-Down DC/DC Controller LTC3887-1 with Digital Power System Management, 70ms Start-Up 4.5V ≤ VIN ≤ 24V, 0.5V ≤ VOUT0,1 (±0.5%) ≤ 5.5V, 70ms Start-Up, I2C/ PMBus Interface, –1 Version Uses DrMOS and Power Blocks LTC3882/ Dual Output Multiphase Step-Down DC/DC Voltage Mode LTC3882-1 Controller with Digital Power System Management 3V ≤ VIN ≤ 38V, 0.5V ≤ VOUT1,2 ≤ 5.25V, ±0.5% VOUT Accuracy I2C/PMBus Interface, Uses DrMOS or Power Blocks LTC3886 4.5V ≤ VIN ≤ 60V, 0.5V ≤ VOUT0,1 (±0.5%) ≤ 13.8V, 70ms Start-Up, I2C/PMBus Interface, Input Current Sense 60V Dual Output Step-Down Controller with Digital Power System Management LTC3883/ Single Phase Step-Down DC/DC Controller LTC3883-1 with Digital Power System Management VIN Up to 24V, 0.5V ≤ VOUT ≤ 5.5V, Input Current Sense Amplifier, I2C/PMBus Interface with EEPROM and 16-Bit ADC, ±0.5% VOUT Accuracy LTC3815 6A Monolithic Synchronous DC/DC Step-Down Converter with Digital Power System Management 2.25V ≤ VIN ≤ 5.5V, 0.4V ≤ VOUT ≤ 0.72VIN, Programmable VOUT Range ±25% with 0.1% Resolution, Up to 3MHz Operation with 13-bit ADC LTC3874 Multiphase Step-Down Synchronous Slave Controller with Sub MilliOhm DCR Sensing 4.5V ≤ VIN ≤ 38V, VOUT Up to 5.5V, Very High Output Current, Accurate Current Sharing, Current Mode Applications LTC3880/ Dual Output Multiphase Step-Down DC/DC Controller LTC3880-1 with Digital Power System Management 20 Linear Technology Corporation 4.5V ≤ VIN ≤ 24V, 0.5V ≤ VOUT0 (±0.5%) ≤ 5.4V, 145ms Start-Up, I2C/PMBus Interface with EEPROM and 16-Bit ADC 1630 McCarthy Blvd., Milpitas, CA 95035-7417 For more information www.linear.com/LTC3870-1 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LTC3870-1 38701f LT 1115 • PRINTED IN USA LINEAR TECHNOLOGY CORPORATION 2015