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SI-8000SD
Application Note
Surface Mount 3A Chopper Type Switching Regulator IC
SI-8000SD Series
Edition April 2010 Rev.2.0
SANKEN ELECTRIC CO., LTD.
SI-8000SD
---
Content
---
1. General Description
1-1 Features
----------
3
1-2 Application
----------
3
1-3 Type
----------
3
2-1 Package Information
----------
4
2-2 Ratings
----------
5
2-3 Circuit Diagram
----------
7
2. Specification
3. Operational Description
3-1 PWM Output Voltage Control
3-2 Overcurrent Protection / Thermal Shutdown
----------
8
--------
9
4. Cautions
4-1 External Components
----------
10
4-2 Pattern Design Notes
----------
15
4-3 Operation Waveform Check
----------
17
4-4 Power Supply Stability
----------
18
4-5 Thermal Design
----------
23
5. Applications
5-1
Soft-start
----------
23
5-2
Output ON / OFF Control
----------
24
5-3
Controllable Output Voltage
----------
25
5-4
Spike Noise Reduction
----------
27
5-5
Reverse Bias Protection
----------
27
6. Thermal Derating Curve
----------
28
7. Typical Characteristics
----------
29
8. Terminology
----------
31
2
SI-8000SD
1. General Description
The SI-8000SD is a chopper type switching regulator IC which is provided with various functions required
for the buck switching regulator and protection functions. By using four external components, a highly
efficient switching regulator can be configured.
●1-1 Features
- Compact size and large output current of 3A
The maximum output current of 3A for the outline of TO263-5 (surface mount)
-
High efficiency of 84% (SI-8050SD VIN=20V/IO=1A)
Heat dissipation is small due to high efficiency to contribute to the downsizing of a heat sink.
-
Four external components
The regulator can be configured by input / output capacitor, diode and coil.
-
Internal adjustment of output voltage and phase compensation having been done in production
Troublesome adjustment of output voltage and phase compensation by external components is no
longer required.
-
Reference oscillation by a built-in timing capacitor
No external capacitor for the oscillation frequency setting is required.
-
Built-in functions for overcurrent and thermal shutdown
A current limiting type overcurrent protection circuit and overheat protection are built in.
(automatic restoration type)
・Soft-start function (output ON/OFF is possible)
It is possible to delay the output voltage rising speed by adding the external capacitor during startup.
In addition, the output can be also ON/OFF-controlled.
●1-2 Applications
For on-board local power supplies, power supplies for OA equipment, stabilization of secondary output
voltage of regulator and power supply for communication equipment
●1-3 Type
- Type: Semiconductor integrated circuits (monolithic IC)
- Structure: Resin molding type (transfer molding)
3
5-0.80±0.10
φ 1.50 Dp : ±0.20
4-[1.70±0.25]
9.20±0.20
4.90±0.20
(15°)
(3°)
(3°)
2.00±0.10
(0.75)
15.30±0.30
9.90±0.20
4.
5.
3.
15.30±0.30
0~6°
2.54
±0.30
(R0.30)
2.40±0.20
(3°)
+0.15
-0.10
+0.10
-0.05
0.10
1.30
Vos
SS
GND
PIN assignments
1.
VIN
2.SWOUTO
(0.50)
(R0.30)
3-(R0.30)
4.50±0.20
(1.75)
(4.60)
(0.40)
4-[1.70±0.25]
4.90±0.20
9.20±0.20
(6.80)
Notes:
1) Dimensions do not include molding burr.
) are shown
2) Figures in parentheses (
only for reference.
3) Figures in parentheses [ ] are dimensions
after lead forming.
4) Backside bumps: 0.8 mm at maximum
5) Unit: mm
5-0.80±0.10
2x(R0.45)
(4.40)
(8.00)
10.00±0.20
SI-8000SD
2. Specification
●2-1 Package Information (surface mount: TO263-5)
Products Weight: Approx.1.48g
4
SI-8000SD
●2-2 Ratings
Lineup
Product Name
VOUT(V)
SI-8033SD
3.3
SI-8050SD
5
Absolute Maximum Ratings
Parameter
Symbol
Rating
Input Voltage
VIN
Allowable Power Dissipation
Pd1
3
W
Pd2
1.5
W
Junction Temperature
Tj
125
°C
Storage Temperature
Tstg
-40 - +125
°C
Vsw
-1
V
43 *1
Unit
V
*2
Allowable Power Dissipation
without Heat sink
SW to GND Reverse Voltage
*1: 35V for SI-8033SD
*2: Glass epoxy single side board 40 × 40
Recommended Conditions
Parameter
Symbol
SI-8033SD
SI-8050SD
Unit
DC Input Voltage
VIN
5.5 - 28
7 - 40
V
Output Current
IO
0-3
Junction Temperature
Tjop
-30 - +125
*3
A
°C
in Operation
*3 It should be used within the temperature range which does not exceed Tjmax.
5
SI-8000SD
Electrical Characteristics
(Ta=25 ゚ C)
SI-8033SD
Parameter
SI-8050SD
Unit
Symbol
Vo
min
typ
max
min
typ
max
3.17
3.30
3.43
4.80
5.00
5.20
V
Set Output Voltage
conditions
VIN=15V/Io=1A
VIN=20V/Io=1A
η
79
84
conditions
VIN=15V/Io=1A
VIN=20V/Io=1A
f
60
60
conditions
VIN=15V/Io=1A
VIN=20V/Io=1A
Input Voltage – Output
⊿Voline
25
40
Voltage
conditions
VIN=8 - 28V
%
Efficiency
kHZ
Operation Frequency
80
100
mV
40
mV
VIN=10 - 30V
(Iout=1A)
Output Current -
Output ⊿Voload
Voltage
10
conditions
30
10
VIN=15V
VIN=20V
(Iout=0.5 - 1.5A)
Overcurrent Protection Start
Is
Current
conditions
VIN=15V
VIN=20V
Output Voltage Temperature
Kt
±0.5
±0.5
3.1
3.1
A
mV/°C
Variation
6
SI-8000SD
●2-3 Circuit Diagram
2-3-1 Internal Equivalent Circuit
VIN
1
SI-8000SD
VIN
SWOUT
L1
2
VOUT
過電流保護
内部電源
Overcurrent
protection
Internal
regulator
発振器
リセット
Oscillator
ラッチ & ドライバ
Reset
Latch & driver
Thermal
shutdown
Compalator
C1
D1
過熱保護
コンパレータ
C2
VOS
4
エラーアンプ
Error amp
基準電圧
Reference
voltage
S.S
GND
5
3
C3
GND
GND
2-3-2 Typical Connection Diagram
1
VIN
VIN
SWOUT
SI-8000SD
C1
S.S
5
GND
3
VOS
L1
2
VOUT C1 :50V/1000μF
C2 :50V/1000μF
4
C3 :0.01μF
D1
C2
(C3 is necessary when soft-start
function is used)
C3
GND
L1 :150μH
GND D1 :SPB-G56S (Sanken)
7
SI-8000SD
3. Operational Description
●3-1 PWM Output Voltage Control
In the SI-8000SD series, the output voltage is controlled by the PWM system and the IC incorporates the
PWM comparator, oscillator, error amplifier, reference voltage, output transistor drive circuit etc. The
triangular wave output (≒60KHz) from the oscillator and the output of the error amplifier are given to the
input of the PWM comparator. The PWM comparator compares the oscillator output with the error
amplifier output to turn on the switching transistor for a time period when the output of the error amplifier
exceeds the oscillator output.
PWM Control Chopper Type Regulator Basic
Configuration
VOUT
Switching
Transistor
スイッチングトランジスタ
VIN
PWMコンパレータ
PWM
Comparator
D1
The error amplifier output and the
C2
oscillator output are compared by the
Drive
Circuit
ドライブ回路
PWM comparator to generate the drive
Error誤差増幅器
Amplifier
Oscillator
発振器
signal of rectangular wave and to drive
the switching transistor.
Reference
基準電圧Voltage
On the assumption that the output voltage commences to rise, the output of the error amplifier will drop,
because the error amplifier is inverting type. As the error amplifier output falls down, the time period
during which it falls below the triangular wave level of the oscillator is increased to shorten the ON time of
the switching transistor and as a result, the output voltage is maintained at a certain level. As described
above, the output voltage is controlled by varying the ON time of the switching transistor, while fixing the
switching frequency.
(the higher Vin is , the shorter the ON time of the switching transistor is.)
PWM Comparator Operation
発振器出力
Oscillator
Output
Error Amplifier
誤差増幅器出力
ON
OFF
Output
Switching Transistor
スイッチングトランジスタ出力
Output
The rectangular wave output of the switching transistor is smoothed by the LC low pass filter of a choke
coil and capacitor, and the stabilized DC voltage is supplied to the load.
8
SI-8000SD
●3-2
Overcurrent Protection / Thermal Shutdown
Output Voltage Characteristics in Overcurrent
出力電圧
Output Voltage
The oscillating
ここで周波数が低下
frequency is lowered
Output
Current
出力電流
The SI-8000SD series incorporates a current limiting type overcurrent protection circuit. The overcurrent
protection circuit detects the peak current of a switching transistor and when the peak current exceeds the
set value, the ON time of the transistor is compulsorily shortened to limit the current by lowering the output
voltage. In addition, when the output voltage is lowered up to the 50% of the rated value, the increase of
current at low output voltage is prevented by dropping the switching frequency to about 30kHz. When the
overcurrent condition is released, the output voltage will be automatically restored.
Output Voltage Characteristics in Thermal
Shutdown
出力電圧
Output
Voltage
Restoration Setting
復帰設定温度
Temperature
Protection
Setting Temperature
保護設定温度
Junction
Temperature
接合温度
The thermal shutdown circuit detects the semiconductor junction temperature of the IC and when the
junction temperature exceeds the set value, the output transistor is stopped and the output is turned OFF.
When the junction temperature drops around 15°C from the set value for overheat protection, the output
transistor is automatically restored.
* Note for thermal shutdown characteristic
This circuit protects the IC against overheat resulting from the instantaneous short circuit, but this function
does not assure the operation including reliability in the state of continuous overheat due to long time short
circuit.
9
SI-8000SD
4. Cautions
●4-1 External Components
4-1-1 Choke coil L1
The choke coil L1 is a key component of chopper type switching regulator. In order to maintain the stable
operation of the regulator, such dangerous state of operation as saturation state and operation at high
temperature due to heat generation must be avoided.
The following points should be taken into consideration for the selection of the choke coil.
a) The choke coil should be fit for the switching regulator.
The coil for a noise filter should not be used because of large loss and generated heat.
b) The inductance value should be appropriate.
The larger the inductance of the choke coil is, the less the ripple current flowing in the choke coil is, and
the output ripple voltage drops. As a result, the overall size of the coil becomes larger.
On the other hand, if the inductance is small, the peak current flowing in the switching transistor and diode
is increased and the ripple voltage becomes higher and this operation state is not favorable for maintaining
the stable operation.
Small
Ripple Voltage/
リップル電圧・電流小
Current
Large
Inductance
インダクタンス大
C2
Small
Inductance
インダクタンス小
Large Ripple Voltage/
リップル電圧・電流大
Current
C2
The larger the inductance is, the smaller the ripple
current/voltage is. But the outer size of the coil
becomes larger.
The smaller the inductance is, the larger the ripple
current/voltage is.
Although the outer size of the coil is smaller, the
operation is likely to be unstable.
The inductance value shown in the specifications should be considered as a reference value for the stable
operation and the appropriate inductance value can be obtained by the equation (1).
ΔIL shows the ripple current value of the choke coil and the inductance value is set as described in the
following.
-
In the case that the output current to be used is nearly equal to the maximum rating (3A) of the
SI-8000SD: Output current × 0.2 - 0.3
-
In the case that the output current to be used is approximately 1A or less: Output current × 0. 3 – 0. 4
L1 
(VIN  VOUT )  VOUT
IL  VIN  f
---(1)
10
SI-8000SD
For example, where VIN = 25V, VOUT = 5V, ΔIL = 0.5A, frequency = 60 KHz,
L1 
(25  5)  5
≒133uH
0.5  25  60  10 3
As shown above, the coil of about 130μH may be selected.
However, it is to be noted that the peak current of the switching transistor is increased depending on the
calculated inductance value.
Therefore, because the peak current detection system is adopted for overcurrent detection in this case, the
overcurrent detection point may become lower.
c) The rated current shall be met.
The rated current of the choke coil must be higher than the maximum load current to be used. When the
load current exceeds the rated current of the coil, the inductance is sharply decreased to the extent that it
causes saturation state at last. Please note that overcurrent may flow since the high frequency impedance
becomes low.
d) Noise shall be low.
In the open magnetic circuit core like drum shape type, since magnetic flux passes outside the coil, the
peripheral circuit may be affected by noise. It is recommended to use the toroidal type, EI type or EE type
coil which has a closed magnetic circuit type core as much as possible.
11
SI-8000SD
4-1-2 Input Capacitor C1
The input capacitor is operated as a bypass capacitor of the input circuit to supply steep current to the
regulator during switching and to compensate the voltage drop of the input side. Therefore, the input
capacitor should be placed as close as to the regulator IC.
In addition, in the case that the smoothing capacitor of the AC rectifier circuit is located in the input circuit,
the input capacitor may be also used as a smoothing capacitor, but similar attention should be paid.
The selection of C1 shall be made in consideration of the following points:
a) The requirement of withstand voltage shall be met.
b) The requirement of the allowable ripple current shall be met.
Current Flow of C1
IIN
Current
Waveform of C1
C1電流波形
VIN
1.VIN
Ripple
Current
リップル電流
0
Iv
Ip
C1
Ton
D
Ton
T
T
The ripple current of the input capacitor is
increased in accordance with the increase of
the load
If the withstanding voltage and allowable ripple current are exceeded or used without derating, it is in
danger of causing not only the decreasing the capacitor lifetime (burst, capacitance decrease, equivalent
impedance increase, etc) but also the abnormal oscillations of regulator. Therefore, the selection with
sufficient margin is needed. The effective value of ripple current flowing across the input capacitor can be
obtained by the following equation (2):
Irms  1.2 
Vo
 Io
Vin
--(2)
For instance, where VIN=20V,Io=3A,Vo=5V
I r m 1s.2 
5
 3  0 .9 A
20
Therefore, it is necessary to select the capacitor with the allowable ripple current of 0.9A or higher.
12
SI-8000SD
4-1-3 Output Capacitor C2
The output capacitor C2 configures an LC low pass filter together with a choke coil L1 and functions as a
rectifying capacitor of switching output.
The current equivalent to the pulse current ΔIL of the choke coil current is charged and discharged in the
output capacitor.
Therefore, it is necessary to meet the requirements of withstand voltage and allowable ripple current with
sufficient margin like the input capacitor.
Current Flow of C2
IL
Vout
L1
ESR
C2電流波形
Io
Ripple
Current
リップル電流
Current Waveform of C2
0
RL
⊿IL
The ripple current of the output capacitor is
equal to the ripple current of the choke coil
and does not vary even if the load current
increases or decreases.
C2
The ripple current effective value of the output capacitor is obtained by the equation (3).
Irms 
IL
2 3
Irms 
0.5
≒ 014
. A
2 3
---(3)
When ΔIL = 0.5A,
Therefore a capacitor having the allowable ripple current of 0.14A or higher is required.
In addition, the output ripple voltage Vrip of the regulator is determined by a product of the pulse current
ΔIL of the choke coil current (= C2 charging/discharging current) and the equivalent series resistance ESR
of the output capacitor C2.
Vrip  IL  C2 ESR
---(4)
It is therefore necessary to select a capacitor with low equivalent series resistance ESR in order to lower the
output ripple voltage. As for general electrolytic capacitors of same product series, the ESR shall be lower,
for the products of higher capacitance with same withstand voltage, or with higher withstand voltage
(almost proportional to larger externals) with same capacitance.
When ΔIL = 0.5A, Vrip = 40mV,
C2esr  40  05
.  80m
As shown above, a capacitor with the ESR of 80mΩ or lower should be selected. In addition, since the ESR
varies with temperature and increases at low temperature, it is required to examine the ESR at the actual
operating temperatures. It is recommended to contact capacitor manufacturers for the ESR value since it is
13
SI-8000SD
peculiar to capacitors.
However, if the ESR of the output capacitor is too low (10 - 30mΩ or lower), the phase margin within the
feedback loop of the regulator will be short to make the operation unstable. Therefore, it is not appropriate
that a tantalum capacitor or a laminated ceramic capacitor is used for the output capacitor as an
independent component. However, connecting a tantalum capacitor or a laminated ceramic capacitor in
parallel with an electrolytic capacitor is effective in reducing the output ripple voltage only when it is used
at low temperature (< 0°C).
In addition, in order to further decrease the ripple voltage, as shown below, it is also effective to add one
stage of the LC filter to form the π type filter.
L1
L2
2.SWOUT
1.VIN
SI-8000SD
3.GND
Secondary-filter
4.VOS
D1
C2
C4
L2:20μH
C4:200μF
However, if the secondary-filter is added , care must be taken because abnormal oscillation may take place
unless the output voltage detecting point (wiring to Vos pin) is on the primary-filter(L1 & C2).
It should be noted that the operating stability is more influenced by the ESR than the capacitance as
described above if the requirements of withstand voltage and allowable ripple current are met.
4-1-4 The flywheel Diode D1
The flywheel diode D1 is to discharge the energy which is stored in the choke coil at switching OFF.
For the flywheel diode, the Schottky barrier diode must be used. If a general rectifying diode or fast
recovery diode is used, the IC may be destroyed by applying reverse voltage due to the recovery and ON
voltage.
In addition, since the output voltage from the SWOUT terminal (pin 2) of the SI-8000SD series is almost
equivalent to the input voltage, the flywheel diode with the reverse withstand voltage of the input voltage or
higher should be used.
14
SI-8000SD
●4-2 Pattern Design Notes
4-2-1 High Current Line
Since high current flows in the bold lines in the connection diagram, the pattern should be as wide and
short as possible.
L1
1,VIN
VIN
2.SWOUT
VOUT
SI-8000SD
4.VOS
C1
5.SS
3.GND
C2
D1
GND
GND
4-2-2 Input / Output Capacitor
The input capacitor C1 and the output capacitor C2 should be placed to the IC as close as possible. If the
rectifying capacitor for AC rectifier circuit is on the input side, it can be used as an input capacitor.
However, if it is not close to the IC, the input capacitor should be connected in addition to the rectifying
capacitor.
Since high current is discharged and charged through the leads of input/output capacitor at high speed, the
leads should be as short as possible.
A similar care should be taken for the patterning of the capacitor.
C1,C2
Improper Pattern Example
C1,C2
Proper Pattern Example
15
SI-8000SD
4-2-3 Sensing Terminal
The output voltage sensing terminal Vos shall be connected near the output capacitor C2 as much as
possible. (Vos terminal flow-in current is approx. 1mA.) If it is connected far from C2, it should be noted
that abnormal oscillation may happen due to the low regulation and increased switching ripple.
Recommended board pattern
Recommended land pattern
11±0.2
9±0.2
6.8±0.1
9±0.1
3.7±0.05
4±0.1
1±0.05
1.7±0.1
16
SI-8000SD
●4-3 Operation Waveform Check
It can be checked by the waveform between the pin 2 and 3 (SWOUT-GND waveform) of the SI-8000SD
whether the switching operation is normal or not.
The examples of waveforms at normal and abnormal operations are shown below:
1. Normal Operation (continuous area)
2. Normal Operation (discontinuous area)
3. When C1 is distant from IC
4. When C2 is distant from IC
The continuous area is an area where the DC component of the triangular wave is superimposed on the
current flowing across the choke coil and the discontinuous area is an area where the current flowing across
the choke coil is intermittent (a period of zero current may happen.) because the current flowing across the
choke coil is low.
Therefore, when the load current is high, the area is a continuous area and when the same current is low,
the area is a discontinuous area.
In the continuous area, the switching waveform is formed in the normal rectangular waveform (waveform
1) and in the discontinuous area, damped oscillation is caused in the switching waveform (waveform 2), but
this is a normal operation without any problem.
In the meantime, when the IC is far from C1 and C2, jitter which disturbs the ON – OFF time of switching
will happen as shown in the waveforms (3, 4). As described above, C1 and C2 should be connected close to
the IC.
17
SI-8000SD
●4-4 Power Supply Stability
4-4-1 Phase Margin
This block diagram shows that the chopper type regulator is a negative feedback amplifier which controls
the output voltage by constantly comparing with the output voltage and the reference voltage which is set in
advance. Therefore, it has a negative feedback loop to control the output by detecting the variation of
output voltage with the error amplifier.
Reference
Voltage
基
準
電
圧
L1
Control
制御部
Block
基
準
電
圧
ESR
Reference
Voltage
-180deg
Negative
Feedback Loop
負帰還ループ
C2
Load
負荷
0deg
The phase within the negative feedback loop is displaced by 180° to negate the variation of the output
voltage, but in the event that the phase is further delayed by 180° in the state that the amplification degree
(gain) is 1 or more, the total phase delay amounts to 360° to deviate from the stable operation zone to cause
abnormal oscillation. This is called Barkhausen oscillation conditions. Therefore, the oscillation conditions
should not be accrued in the actual stabilized power supply.
It is possible to judge whether the Barkhausen oscillation conditions are accrued or not by means of
frequency and gain/phase characteristics of the negative feedback loop. The frequency-gain/phase
characteristics are called Bode diagram.
1-step Differential Amplifier
IN
OUT
20dB
0dB
9k
1k
-0deg
-45deg
-90deg
Bode Diagram Example
Gain
ゲイン
0.1fp
Frequency
周波数
Phase
位相
fp
10fp
18
SI-8000SD
In the Bode diagram, the frequency at which the gain is 1 (0 dB) is called gain intersection and the
frequency at which the phase of feedback loop is -180° is called phase intersection.
Unless the phase reaches -180° at the frequency of gain intersection, the oscillation conditions are not met.
In this respect, the phase at gain intersection - (-180°) is equal to the phase at gain intersection + 180° and
this value is used as a margin to -180° which is called phase margin. The more the phase margin is, the less
likely the abnormal oscillation is to occur against the variation of environmental conditions such as
input/output conditions and temperature. Therefore, sufficient phase margin should be taken into
consideration in order to maintain the stable operation.
Stability Judgment at Bode Diagram
Gain Characteristics
ゲイン特性
Gainゲイン特性
Characteristics
Gain
Intersection
ゲイン交点
0dB
Phase Characteristics
位相特性
0dB
Gain
Intersection
ゲイン交点
Frequency
周波数
Frequency
周波数
Phase 位相特性
Characteristics
Phase位相余裕
Margin
(>0)
-180deg
Phase
Intersection
位相交点
Stable
安定な場合
Phase Intersection
位相交点
-180deg
Unstable
不安定な場合
位相余裕
Phase
Margin
(<0)
4-4-2 Phase Characteristics of Regulator IC
The phase characteristics of the chopper type regulator are synthesized by the phase characteristics inside
the regulator IC and that of the LC filter.
The phase characteristics inside the regulator IC are generally determined by the delay time of the control
block and the phase characteristic of the output error amplifier.
Among these two factors, the phase delay due to the delay time of the control block rarely causes problems
in actual use. Therefore, the phase characteristics of the error amplifier are important.
With respect to the compensation of phase characteristics of the output error amplifier, there are two types
of regulator ICs. One is that compensation is made in the IC in advance, while another type is that external
components such as resistors and capacitors are added to the IC for compensation.
In the former case, it is only a matter of selection of the LC filter described below, but in the latter case,
appropriate phase compensation should be made in accordance with the application of the product.
19
SI-8000SD
4-4-3 Phase Characteristics of LC Filter
The phase margin of the chopper type regulator depends largely on the phase characteristics of the LC filter
for output smoothing. The phase characteristic of the LC filter theoretically shows the characteristics of a
secondary delay factor. Resonance is caused at a specific frequency due to the combination of inductance
L1 of coil and of capacitance C2 of the capacitor and at frequency higher than the resonance point, the
phase is delayed by 180°at a maximum.
The resonance frequency is expressed as shown in the equation (5):
fLC 
1
2 LC
---(5)
The phase characteristics are 0° if they are lower than the resonance frequency fLC.
The phase characteristics are 180° if they are higher than the resonance frequency fLC.
Accordingly, when the LC filter for output smoothing shows the theoretical phase characteristics, the phase
delay reaches -180° in this filter portion and the phase margin will be zero for this regulator.
However, in the actual LC filter, the phase delay of the LC filter is less than 180°because of influence of
the equivalent series resistance (ESR) of capacitor. Consequently, the phase margin can be secured for the
regulator because of this phase compensation effect of the equivalent series resistance (ESR).
LC FilterLCフィルタ位相特性
Phase Characteristics
L1
0deg
ESR
VIN
Phase
Delay
位相遅れ
VOUT
C2
ESRHigh
大
ESR:
ESR:
ESRLow
小
-180deg
ESR00
ESR:
fLC
Frequency
周波数
Generally speaking, when such capacitors as tantalum capacitors or laminated capacitors are used for the
output LC filter, the phase delay of filters will be large.
Therefore, from the viewpoint of securing the phase margin, use of the electrolytic capacitor is preferable.
20
SI-8000SD
4-4-4 Relation of Phase Characteristics of Internal IC and LC Filter
As described above, the phase characteristics of the chopper type regulator is almost determined by the
phase characteristics of the error amplifier and LC filter. In this respect, the relation between these two
characteristics is important.
When the gain lowering commencement frequency of the error amplifier, namely the first pole frequency fp
and the resonant frequency of the LC filter fLC are closer, the phase margin of the regulator is decreased
because of concentrated phase delay. In this respect, the proper distribution of fp and fLC is important.
Normally, the phase delay of error amplifier commences from 0.1 times of the first pole frequency fp.
In order to avoid the concentration of phase delay, the resonant frequency of the LC filter fLC should be
kept to be less than 0.1 times of the first pole frequency fp of the error amplifier.
Phase
位相
Phase Characteristics:
fpとf
LCが近い場合の位相特性
when
fp and fLC are close
Phase
位相
Phase Characteristics:
fpとfLCfp
が離れている場合の位相特性
when
and fLC are distant
fp
fp
Amplification
増幅部
Section
Amplification
増幅部
Section
LC
Filter
LCフィルタ
LC
Filter
LCフィルタ
fLC
-180deg
fLC
-180deg
Synthesized
Characteristics
合成特性
Synthesized
合成特性
Characteristics
位相遅れ大
Long
Phase Delay
位相遅れ小
Short
Phase Delay
-180deg
Frequency
周波数
-180deg
Frequency
周波数
Generally, the frequency fp of the chopper type regulator IC is set from several KHz to higher than ten
KHz.
With respect to the constants of LC filters described in the applications of each regulator IC, if the
inductance of coil or capacitance of the capacitor is set to be less than the recommended values, the
resonant frequency fLC of the LC filter may rise to decrease the phase margin. Care should be taken to this
phenomenon.
21
SI-8000SD
The constants of peripheral components should be properly selected according to the applications of each
regulator IC.
チョッパーReg ゲイン、位相特性例
60
630
50
540
40
450
Gain
ゲイン
30
360
20
270
10
180
0
90
-10
-20
0
Phase
位相
-90
-30
-40
100
位相(゜)
Phase (°)
Gain (dB)
ゲイン(dB)
Typical Characteristics of Gain and Phase
-180
1000
Frequency
周波数
(Hz) (Hz)
-270
10000
22
SI-8000SD
●4 - 5 Thermal Design
In the case of the surface mounting type SI-8000SD, the heat is dissipated toward the copper foil on the
mounting board, therefore the thermal design should be made in consideration of copper foil area, board
material and number of copper foil layers.
The stem part of the backside of the SI-8000SD is connected with pin 3 (GND) by the inner frame and heat
dissipation performance is improved by taking the larger GND pattern which is directly connected with the
stem part.
In order to confirm the junction temperature, the temperature of the stem spot shown below should be
measured to calculate the temperature by the following equation.
Tj=Tc+Pd×3°C /W
* Tc = Actually measured stem temperature
Temperature measurement point
Junction thermal resistance: 3°C /W
Reference data (Copper foil are vs Thermal resistance on single side copper foil board)
23
SI-8000SD
5. Application
●5-1 Soft-start
When a capacitor is connected to the pin 5, the soft-start is applied when input voltage is turned on. The
capacitor C3 is intended to control rising time by controlling Off period of PW control. The delay time Td
and the rising time Ts can be calculated by the following equation. However, there are some fluctuations in
the actual machine because of influence of input power source and rising of load, etc. When not using the
soft -start function, pin 5 should be open.
VIN
SI-8000SD
5.SS
Td 
VOUT
C3
Td
Ts 
Ts
0.7  C3
20  10 6
(Sec)
Vo  0.9  C 3
Vin  20  10 6
--(11)
(Sec)--(12)
For example, when VIN = 20V, Vo = 5v and C3 = 1uF
0.7  1  10 6
 35( ms)
20  10 6
Td  Ts≒47( ms )
Td 
Ts 
5  0.9  1  10 6
≒12(ms)
20  20  10 6
Accordingly, it takes 47ms until output voltage rises after power is turned on.
However, if the capacity of Css is enlarged, the discharge-time of Css becomes slow after VinOFF. It is
recommended to use the C3 at 10uF or less.
* Ts may be shorter than the above calculated value under the load condition in discontinuous mode
(light load).
●5-2 Output ON / OFF Control
The output ON-Off control is possible using the soft-start pin 5. The output is turned OFF when the pin 5
voltage falls to a low level by such as open collector. It is possible to use the soft-start together.
Since the soft-start terminal has been already pulled up, no voltage shall be applied from the external side.
SI-8000SD
SI-8000SD
5.SS
5.SS
C3
ON/OFF
SS+ON/OFF
24
SI-8000SD
●5-3 Controllable Output Voltage
The output voltage can be increased by adding a resistor to the Vos terminal (pin 4)
(not applicable for voltage fall).
5-3-1 Variable Output Voltage by One External Resistor
The output voltage adjustment resistance Rex is
L1
V
OUT'
obtained by the following equation.
2.SWOUT
SI-8000SD
3.GND
Re x 
Rex
D1
4.VOS
Vos: Set output voltage for product
Vout: Variable output voltage
Ivos: Vos terminal in-flow current ≒1mA
C2
Ivos
Vout 'Vos
---(13)
Ivos
GND
* Since no temperature compensation is made for Rex, the temperature characteristic of output voltage is
lowered. Ivos is variable at maximum ±20% depending on each IC product. Therefore, as the variation
range of the output voltage becomes wider, the semi-fixed type resistor is required for the adjustment of
accurate output voltage.
The variation range of the output voltage including the variation of Rex, Ivos and Vos is shown as follows:
-
Maximum output voltage (VOUT’MAX)
VOUT' MAX=VosMAX +RexMAX  IvosMAX ---(14)
VosMAX: The maximum value of set output voltage. The MAX value of the set output voltage
should be put, shown in the electrical characteristics in page 6.
RexMAX: The maximum value of Rex. It is obtained from the allowable tolerance.
IvosMAX : The maximum in-flow current of Vos terminal. 1.2mA
-
The minimum output voltage (Vout’MIN)
Vout' MIN=VosMIN+RexMIN  IvosMIN ---(15)
VosMIN: The minimum value of set output voltage. The MIN value of the set output voltage
should be put, shown in the electrical characteristics in page 6.
RexMIN: The minimum value of Rex. It is obtained from the allowable tolerance of resistance.
IvosMIN : The minimum in-flow current of Vos terminal. 0.8mA
5-3-2 Variable Output Voltage by Two External Resistors
L1
VOUT' The output voltage adjustment resistors Rex1 and 2 are
2.SWOUT
SI-8000SD
3.GND
obtained by the following equation.
D1
Ivos
Rex1
4.VOS
C2
IRex2
Vout 'Vos
S  IVos
Vos
Re x 2 
( S  1)  IVos
Re x1 
Rex2
GND
---(16)
---(17)
S: Stability coefficient
The tolerance of temperature characteristics and output voltage is improved more by bypassing the current
25
SI-8000SD
to Rex2 than the method 5-3-1.
Stability coefficient S means the ratio of Rex 2 to the Vos terminal in-flow current Ivos. The larger S is, the
more the variation of temperature characteristic and output voltage are improved. (Normally, about 5 - 10)
The tolerance of the output voltage including variation of Rex 1, Rex 2, Ivos, Vos is shown below.
-
Maximum output voltage (Vout’MAX)
Vout' MAX=VosMAX +Rex1MAX(
VosMAX
---(18)
+IvosMAX)
Rex2MIN
VosMAX: The maximum value of set output voltage. The MAX value of set output voltage should
be put, shown in the electrical characteristics in page 6.
Rex1MAX: The maximum value of Rex1. It is obtained from the tolerance of the resistor.
Rex2MIN: The minimum value of Rex2. It is obtained from the tolerance of the resistor.
IvosMAX: The maximum in-flow current of Vos terminal. 1.2mA
-
The minimum output voltage (Vout’MIN)
Vout' MIN=VosMIN+Rex1MIN(
VosMIN
---(19)
+IvosMIN)
Rex2MAX
VosMIN: The minimum value of the set output voltage. Please fill in the MIN value of the set
output voltage which is shown in the electrical characteristics in page 6.
Rex1MIN: The minimum value of Rex1. It is obtained from the tolerance of the resistor.
Rex2MAX: The maximum value of Rex2. It is obtained from the tolerance of the resistor.
IvosMIN: The minimum in-flow current of Vos terminal. 0.8mA
5-3-3 Cautions for variation of output voltages
The degradation of regulation and the increase in the output voltage temperature coefficient are assumed
when the output voltage is varied.
If it is varied drastically, the increase of coil capacitance value may be required since the overcurrent
protection current is assumed to be lowered due to the increase in coil current.
Therefore, the use within the set output voltage +5V is recommended as for the upper limit of output
voltage variation.
In addition, the MAX value of the set output voltage is recommended as for the lower limit of output
voltage variation.
26
SI-8000SD
●5-4 Spike Noise Reduction
In order to reduce the spike noise, it is possible to compensate the output waveform of the SI-8000SD and
the recovery time of the diode by a capacitor, but it should be noted that the efficiency is also slightly
reduced.
0~ 20Ω
1.VIN
100~ 3000pF
2.SWOUT
SI-8000SD
0~ 20Ω
3.GND
100~ 4000pF
With noise reduction circuit
Without noise reduction circuit
A resistor of 10Ω and a capacitor of 2200pF
are connected to external resistor
*When the spike noise is observed with an oscilloscope, the lead wire may function as an antenna and the
spike noise may be observed extremely higher than usual if the probe GND lead wire is too long. In the
observation of spike noise, the probe lead wire should be made as short as possible and be connected with
the root of the output capacitor.
●5-5 Reverse Bias Protection
A diode for reverse bias protection is required between input and output when the output voltage is higher
than the input terminal voltage, such as in battery chargers.
SI-8000S,SS
SI-8000SD
27
SI-8000SD
6. Thermal derating Curve
20

V
 100 
PD  VO  I O 
 1  V F  I O 1  O
 x

 V IN



Infinite radiator
VO:Output voltage
VIN:Input voltage
15
IO :Output current
η :Efficiency (%)
VF:Di forward voltage
許容損失
Power dissipation Pd (W)
200×200×2mm (2.3°C/W)
RK46…0.5V(IO=3A)
10
100×100×2mm (5.2°C /W)
75×75×2mm (7.6°C /W)
5
Without radiator
0
-25
0
25
50
75
100
125
Ambient temperature Ta (°C)
Note1:As the efficiency varies subject to the input voltage and output current, it shall be obtained
from the efficiency curve in 4-2 and substituted in percent.
Note2:Thermal design for Di shall be made separately
28
SI-8000SD
7. Typical Characteristics
SI-8033SD
(1) Efficiency
(4) Overcurrent protection characteristics
100
5
90
VIN=28V
15V
70
6V
8V
60
50
40
Output voltage VO (V)
3
0
28V
2
1
1.0 1.5 2.0
2.5
3.0
Output current IO (A)
(2) Startup of output voltage
* Load=C.C
IO=0A
0.5
0
5
5
4
4
3
IO=0A
1A
3A
2
1
0
4
6
8
10
Input voltage VIN (V)
(3) Load regulation
3.40 VIN=15V, IO=1A
2
Frequency fo (kHz)
3.30
3.25
VIN=28V
15V
8V
6V
3.20
3.15
0
0.5
1.0 1.5
2.0 2.5
Thermal
shutdown
6
VIN=15V,
2
TSD OFF
TSD ON
1
50
75 100 125 150 175 200
Ambient temperature Ta (°C)
(6)
3.35
2
3
4
5
Output current IO (A)
3
0
12
Efficiency η (%)
0
1
(5)
Output voltage VO (V)
Output voltage VO (V)
15V
0
30
Output voltage VO (V)
VIN=6V
Temperature
characteristics
90
3.40
80
3.35
70
η
3.30
VO
60
50
40
-50
3.25
fo
-25
3.20
0
25
50
75 100
3.0
29
3.15
Output voltage VO (V)
Efficiency η (%)
4
80
SI-8000SD
Output current IO (A)
100
Ambient temperature
SI-8050SD
(1) Efficiency
Ta (°C)
(4) Overcurrent protection characteristics
10
80
7V
70
VIN=40V
20V
10V
60
50
8
Output voltage VO (V)
Efficiency η (%)
90
6
4
VIN=7V
20V
40V
2
40
30
0
0.5
0
1.0 1.5
2.0 2.5 3.0
Output current IO (A)
(2) Rising of output voltage
IO=0A
0
*Load=C.C
(5)
8
8
Output voltage VO (V)
10
6
IO=0A
4
1A
3A
2
Thermal
shutdown
6
VIN=20V,
6
4
TSD OFF
TSD ON
2
0
0
2
4
6
8
10
Input voltage VIN (V)
0
12
(3) Load regulation
50
Efficiency η (%)
5.10
5.05
Frequency fo (kHz)
VIN=40V
20V
10V
5.00
7V
4.95
4.90
0
0.5
75
100 125 150 175 200
Ambient temperature Ta (°C)
(6) Temperature characteristics VIN=20V, IO=1A
5.15
Output voltage VO (V)
2
3
4
5
Output current IO (A)
1.0 1.5
2.0 2.5
3.0
100
5.15
90
5.10
η
80
5.05
VO
70
5.00
60
4.95
fo
50
-50
4.90
-25
0
25
50
75 100
30
Output voltage VO (V)
Output voltage VO (V)
10
1
SI-8000SD
Output current IO (A)
Ambient temperature
Ta (°C)
8. Terminology
-
Jitter
It is a kind of abnormal switching operations and is a phenomenon that the switching pulse width varies in
spite of the constant condition of input and output. The output ripple voltage peak width is increased when
a jitter occurs.
-
Recommended Conditions
It shows the operation conditions required for maintaining normal circuit functions. It is required to meet
the conditions in actual operations.
-
Absolute Maximum Ratings
It shows the destruction limits. It is required to take care so that even one item does not exceed the pacified
value for a moment during instantaneous or normal operation.
-
Electrical Characteristics
It is the specified characteristic value in the operation under the conditions shown in each item. If the
operating conditions are different, it may be out of the specifications.
-
PWM (Pulse Width Modulation))
It is a kind of pulse modulation systems. The modulation is achieved by changing the pulse width in
accordance with the variation of modulation signal waveform (the output voltage for chopper type
switching regulator).
-
ESR (Equivalent Series Resistance)
It is the equivalent series resistance of a capacitor. It acts in a similar manner to the resistor
series-connected to the capacitor.
31
SI-8000SD
Notice
・The contents of this description are subject to change without prior notice for improvement etc. Please
make sure that any information to be used is the latest one.
・Any example of operation or circuitry described in this application note is only for reference, and we are
not liable to any infringement of industrial property rights, intellectual property rights or any other rights
owned by third parties resulting from such examples.
・In the event that you use any product described here in combination with other products, please review the
feasibility of combination at your responsibility.
・Although we endeavor to improve the quality and reliability of our product, in the case of semi-conductor
components, defects or failures which occur at a certain rate of probability are inevitable.
The user should take into adequate consideration the safety design in the equipment or the system in order to
prevent accidents causing death or injury, fires, social harms etc..
・Products described here are designed to be used in the general-purpose electronic equipment (home
appliances, office equipment, communication terminals, measuring equipment etc.).
If used in the equipment or system requiring super-high reliability (transport machinery and its control
equipment, traffic signal control equipment, disaster/crime prevention system, various safety apparatus etc.),
please consult with our sales office. Please do not use our product for the equipment requiring ultrahigh
reliability (aerospace equipment, atomic control, medical equipment for life support etc.) without our written
consent.
・The products described here are not of radiation proof type.
・The contents of this brochure shall not be transcribed nor copied without our written consent.
32