PDF Data Sheet Rev. 0

11-Bit/16-Bit, 12 GSPS,
RF Digital-to-Analog Converters
AD9161/AD9162
Data Sheet
FEATURES
In baseband mode, wide bandwidth capability combines with
high dynamic range to support DOCSIS 3.1 cable infrastructure
compliance from the minimum of two carriers to full maximum
spectrum of 1.794 GHz. A 2× interpolator filter (FIR85) enables
the AD9161/AD9162 to be configured for lower data rates and
converter clocking to reduce the overall system power and ease
the filtering requirements. In Mix-Mode™ operation, the AD9161/
AD9162 can reconstruct RF carriers in the second and third
Nyquist zones up to 7.5 GHz while still maintaining exceptional
dynamic range. The output current can be programmed from
8 mA to 38.76 mA. The AD9161/AD9162 data interface consists
of up to eight JESD204B serializer/deserializer (SERDES) lanes
that are programmable in terms of lane speed and number of
lanes to enable application flexibility.
DAC update rate up to 12 GSPS (minimum)
Direct RF synthesis at 6 GSPS (minimum)
DC to 2.5 GHz in baseband 1× bypass mode
DC to 6 GHz in 2× nonreturn-to-zero (NRZ) mode
1.5 GHz to 7.5 GHz in Mix-Mode
Bypassable interpolation (1× or bypass mode)
2×, 3×, 4×, 6×, 8×, 12×, 16×, 24×
Excellent dynamic performance
APPLICATIONS
Broadband communications systems
DOCSIS 3.1 cable modem termination system (CMTS)/
video on demand (VOD)/edge quadrature amplitude
modulation (EQAM)
Wireless communications infrastructure
W-CDMA, LTE, LTE-A, point to point
Instrumentation, automatic test equipment (ATE)
Radars and jammers
A serial peripheral interface (SPI) can configure the AD9161/
AD9162 and monitor the status of all registers. The AD9161/
AD9162 are offered in an 165-ball, 8.0 mm × 8.0 mm, 0.5 mm
pitch, CSP_BGA package and in an 169-ball, 11 mm × 11 mm,
0.8 mm pitch, CSP_BGA package, including a leaded ball
option for the AD9162.
GENERAL DESCRIPTION
PRODUCT HIGHLIGHTS
The AD9161/AD91621 are high performance, 11-bit/16-bit
digital-to-analog converters (DACs) that supports data rates to
6 GSPS. The DAC core is based on a quad-switch architecture
coupled with a 2× interpolator filter that enables an effective
DAC update rate of up to 12 GSPS in some modes. The high
dynamic range and bandwidth makes these DACs ideally suited
for the most demanding high speed radio frequency (RF) DAC
applications.
1.
2.
3.
High dynamic range and signal reconstruction bandwidth
supports RF signal synthesis of up to 7.5 GHz.
Up to eight lanes JESD204B SERDES interface flexible in
terms of number of lanes and lane speed.
Bandwidth and dynamic range to meet DOCSIS 3.1
compliance with margin.
FUNCTIONAL BLOCK DIAGRAM
RESET
SDIO
SDO
CS
SCLK
IRQ
ISET VREF
VREF
AD9161/AD9162
SPI
NRZ RZ MIX
SERDIN0±
NCO
INV
SINC
SYSREF±
HB
2×
HB
3×
HB
2×,
4×,
8×
TO JESD
TO DATAPATH
TX_ENABLE
DAC
CORE
OUTPUT±
CLOCK
DISTRIBUTION
CLK±
14379-001
HB
2×
JESD
DATA
LATCH
SERDIN7±
SYNCOUT±
Figure 1.
Protected by U.S. Patents 6,842,132 and 7,796,971.
Rev. 0
1
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Technical Support
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AD9161/AD9162
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
JESD204B Overview .................................................................. 45
Applications ....................................................................................... 1
Physical Layer ............................................................................. 46
General Description ......................................................................... 1
Data Link Layer .......................................................................... 49
Product Highlights ........................................................................... 1
Transport Layer .......................................................................... 57
Functional Block Diagram .............................................................. 1
JESD204B Test Modes ............................................................... 59
Revision History ............................................................................... 2
JESD204B Error Monitoring..................................................... 61
Specifications..................................................................................... 3
Hardware Considerations ......................................................... 63
DC Specifications ......................................................................... 3
Main Digital Datapath ................................................................... 64
DAC Input Clock Overclocking Specifications ........................ 4
Data Format ................................................................................ 64
Power Supply DC Specifications ................................................ 4
Interpolation Filters ................................................................... 64
Serial Port and CMOS Pin Specifications ................................. 7
Digital Modulation ..................................................................... 67
JESD204B Serial Interface Speed Specifications ...................... 8
Inverse Sinc ................................................................................. 69
SYSREF± to DAC Clock Timing Specifications ....................... 8
Downstream Protection ............................................................ 70
Digital Input Data Timing Specifications ................................. 9
Interrupt Request Operation ........................................................ 71
JESD204B Interface Electrical Specifications ........................... 9
Interrupt Service Routine .......................................................... 71
AC Specifications........................................................................ 10
Applications Information .............................................................. 72
Absolute Maximum Ratings .......................................................... 12
Hardware Considerations ......................................................... 72
Thermal Resistance .................................................................... 12
Analog Interface Considerations.................................................. 75
ESD Caution ................................................................................ 12
Analog Modes of Operation ..................................................... 75
Pin Configurations and Function Descriptions ......................... 13
Clock Input.................................................................................. 76
Typical Performance Characteristics ........................................... 17
Shuffle Mode ............................................................................... 77
AD9161 ........................................................................................ 17
DLL............................................................................................... 77
AD9162 ........................................................................................ 27
Voltage Reference ....................................................................... 77
Terminology .................................................................................... 41
Analog Outputs .......................................................................... 78
Theory of Operation ...................................................................... 42
Start-Up Sequence .......................................................................... 80
Serial Port Operation ..................................................................... 43
Register Summary .......................................................................... 82
Data Format ................................................................................ 43
Register Details ............................................................................... 88
Serial Port Pin Descriptions ...................................................... 43
Outline Dimensions ..................................................................... 138
Serial Port Options ..................................................................... 43
Ordering Guide ........................................................................ 139
JESD204B Serial Data Interface .................................................... 45
REVISION HISTORY
5/2016—Revision 0: Initial Version
Rev. 0 | Page 2 of 139
Data Sheet
AD9161/AD9162
SPECIFICATIONS
DC SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, DAC output full-scale current (IOUTFS) = 40 mA, and TA = −40°C to
+85°C, unless otherwise noted.
Table 1.
Parameter
RESOLUTION
AD9161
DAC Update Rate
Minimum
Maximum
Maximum
Adjusted 4
AD9162
DAC Update Rate
Minimum
Maximum
Maximum
Adjusted4
ACCURACY
Integral Nonlinearity (INL)
Differential Nonlinearity (DNL)
ANALOG OUTPUTS
Gain Error (with Internal Reference)
Full-Scale Output Current
Minimum
Maximum
DAC CLOCK INPUT (CLK+, CLK−)
Differential Input Power
Common-Mode Voltage
Input Impedance 5
TEMPERATURE DRIFT
Gain
Reference Voltage
REFERENCE
Internal Reference Voltage
ANALOG SUPPLY VOLTAGES
VDD25_DAC
VDD12A 6
VDD12_CLK6
VNEG_N1P2
DIGITAL SUPPLY VOLTAGES
DLL_VDD_1P2
DVDD
IOVDD 7
SERDES SUPPLY VOLTAGES
VDD_1P2
VTT_1P2
Test Conditions/Comments
Min
11
Typ
Max
Unit
Bit
VDDx 1 = 1.3 V ± 2% 2
VDDx1 = 1.3 V ± 2%2, FIR85 3 2× interpolator enabled
VDDx1 = 1.3 V ± 2%2, minimum 2× interpolation
6
12
3
16
6.4
12.8
3.2
1.5
GSPS
GSPS
GSPS
GSPS
Bit
VDDx1 = 1.3 V ± 2%2
VDDx1 = 1.3 V ± 2%2, FIR853 2× interpolator enabled
VDDx1 = 1.3 V ± 2%2
6
12
6
1.5
6.4
12.8
6.4
GSPS
GSPS
GSPS
GSPS
±2.7
±1.7
LSB
LSB
−1.7
%
RSET = 9.76 kΩ
RSET = 9.76 kΩ
7.37
35.8
8
38.76
8.57
41.3
mA
mA
RLOAD = 90 Ω differential on-chip
AC-coupled
3 GSPS input clock
−20
0
0.6
90
+10
dBm
V
Ω
Can connect to DVDD
Includes VDD12_DCD/DLL
Can connect to VDD_1P2
Rev. 0 | Page 3 of 139
105
75
ppm/°C
ppm/°C
1.19
V
2.375
1.14
1.14
−1.26
2.5
1.2
1.2
−1.2
2.625
1.326
1.326
−1.14
V
V
V
V
1.14
1.14
1.71
1.2
1.2
2.5
1.326
1.326
3.465
V
V
V
1.14
1.14
1.2
1.2
1.326
1.326
V
V
AD9161/AD9162
Parameter
DVDD_1P2
PLL_LDO_VDD12
PLL_CLK_VDD12
SYNC_VDD_3P3
BIAS_VDD_1P2
Data Sheet
Test Conditions/Comments
Can connect to PLL_LDO_VDD12
Can connect to VDD_1P2
Min
1.14
1.14
1.14
3.135
1.14
Typ
1.2
1.2
1.2
3.3
1.2
Max
1.326
1.326
1.326
3.465
1.326
Unit
V
V
V
V
V
VDDx is VDD12_CLK, DVDD, VDD_1P2, DVDD_1P2, and PLL_LDO_VDD12. Any clock speed over 5.1 GSPS requires a maximum junction temperature of 105°C to avoid
damage to the device. See Table 11 for details on maximum junction temperature permitted for certain clock speeds.
See Table 2 for the complete details on the guaranteed speed performance.
3
FIR85 is the finite impulse response filter with 85 dB digital attenuation that implements 2× NRZ mode.
4
The adjusted DAC update rate is calculated as fDAC divided by the minimum required interpolation factor. For the AD9162, the minimum interpolation factor is 1.
Therefore, with fDAC = 6 GSPS, fDAC adjusted = 6 GSPS. For the AD9161, the minimum interpolation is 2×. Therefore, with fDAC = 6 GSPS, fDAC adjusted = 3 GSPS. When
FIR85 is enabled, which puts the device into 2× NRZ mode, fDAC = 2 × (DAC clock input frequency), and the minimum interpolation increases to 2× (interpolation
value). Thus, for the AD9162, with FIR85 enabled and DAC clock = 6 GSPS, fDAC = 12 GSPS, minimum interpolation = 2×, and the adjusted DAC update rate = 6 GSPS.
5
See the Output Stage Configuration section for more details.
6
For the lowest noise performance, use a separate power supply filter network for the VDD12_CLK and the VDD12A pins.
7
IOVDD can range from 1.8 V to 3.3 V, with ±5% tolerance.
1
2
DAC INPUT CLOCK OVERCLOCKING SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted.
Maximum guaranteed speed using the temperatures and voltages conditions as shown in Table 2, where VDDx is VDD12_CLK, DVDD,
VDD_1P2, DVDD_1P2, and PLL_LDO_VDD12. Any DAC clock speed over 5.1 GSPS requires a maximum junction temperature of
105°C to avoid damage to the device. See Table 11 for details on maximum junction temperature permitted for certain clock speeds.
Table 2.
Parameter 1
MAXIMUM DAC UPDATE RATE
VDDx = 1.2 V ± 5%
VDDx = 1.2 V ± 2%
VDDx = 1.3 V ± 2%
1
Test Conditions/Comments
Min
TJMAX = 25°C
TJMAX = 85°C
TJMAX = 105°C
TJMAX = 25°C
TJMAX = 85°C
TJMAX = 105°C
TJMAX = 25°C
TJMAX = 85°C
TJMAX = 105°C
6.0
5.6
5.4
6.1
5.8
5.6
6.4
6.2
6.0
Typ
Max
Unit
GSPS
GSPS
GSPS
GSPS
GSPS
GSPS
GSPS
GSPS
GSPS
TJMAX is the maximum junction temperature.
POWER SUPPLY DC SPECIFICATIONS
IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted. FIR85 is the finite impulse response with 85 dB digital attenuation.
Table 3.
Parameter
8 LANES, 2× INTERPOLATION (80%), 3 GSPS
Analog Supply Currents
VDD25_DAC = 2.5 V
VDD12A = 1.2 V
VDD12_CLK = 1.2 V
VNEG_N1P2 = −1.2 V
Digital Supply Currents
DVDD = 1.2 V
IOVDD 1 = 2.5 V
Test Conditions/Comments
Numerically controlled oscillator (NCO) on,
FIR85 on
Includes VDD12_DCD/DLL
Rev. 0 | Page 4 of 139
Min
Typ
Max
Unit
100
150
279
−119
93.8
3.7
229
−112
mA
µA
mA
mA
621.3
2.5
971
2.7
mA
mA
Data Sheet
Parameter
SERDES Supply Currents
VDD_1P2 = 1.2 V
DVDD_1P2 = 1.2 V
PLL_LDO_VDD12 = 1.2 V
SYNC_VDD_3P3 = 3.3 V
8 LANES, 6× INTERPOLATION (80%), 3 GSPS
Analog Supply Currents
VDD25_DAC = 2.5 V
VDD12A = 1.2 V
VDD12_CLK = 1.2 V
VNEG_N1P2 = −1.2 V
Digital Supply Currents
DVDD = 1.2 V
IOVDD1 = 2.5 V
SERDES Supply Currents
VDD_1P2 = 1.2 V
DVDD_1P2 = 1.2 V
PLL_LDO_VDD12 = 1.2 V
SYNC_VDD_3P3 = 3.3 V
NCO ONLY MODE, 5 GSPS
Analog Supply Currents
VDD25_DAC = 2.5 V
VDD12A = 1.2 V
VDD12_CLK = 1.2 V
VNEG_N1P2 = −1.2 V
Digital Supply Currents
DVDD = 1.2 V
IOVDD1 = 2.5 V
SERDES Supply Currents
VDD_1P2 = 1.2 V
DVDD_1P2 = 1.2 V
PLL_LDO_VDD12 = 1.2 V
SYNC_VDD_3P3 = 3.3 V
8 LANES, 4× INTERPOLATION (80%), 5 GSPS
Analog Supply Currents
VDD25_DAC = 2.5 V
VDD12A = 1.2 V
VDD12_CLK = 1.2 V
AD9161/AD9162
Test Conditions/Comments
Min
Includes VTT_1P2, BIAS_VDD_1P2
Connected to PLL_CLK_VDD12
IOVDD1 = 2.5 V
SERDES Supply Currents
VDD_1P2 = 1.2 V
DVDD_1P2 = 1.2 V
PLL_LDO_VDD12 = 1.2 V
SYNC_VDD_3P3 = 3.3 V
Max
Unit
425.5
62
84.4
9.3
550
86
106
11
mA
mA
mA
mA
NCO on, FIR85 on
93.8
3.7
228.7
−120.7
mA
µA
mA
mA
Includes VDD12_DCD/DLL
598.4
2.5
mA
mA
Includes VTT_1P2, BIAS_VDD_1P2
443.4
72.3
81.8
9.4
mA
mA
mA
mA
Connected to PLL_CLK_VDD12
93.7
10
340.6
−112
100
150
432
mA
µA
mA
mA
Includes VDD12_DCD/DLL
425.5
2.5
753
2.7
mA
mA
Includes VTT_1P2, BIAS_VDD_1P2
1.4
1.0
0.13
0.32
34
14.1
1.5
0.43
mA
mA
mA
mA
102
80
340.5
408
−120.2
108
150
432.4
mA
µA
mA
mA
mA
665.4
706.5
894.6
1090
2.5
1033
2.7
mA
mA
mA
mA
mA
411.2
52.1
85.8
9.3
550
73
105
11
mA
mA
mA
mA
−119
Connected to PLL_CLK_VDD12
NCO on, FIR85 off (unless otherwise noted)
At 6 GSPS
VNEG_N1P2 = −1.2 V
Digital Supply Currents
DVDD = 1.2 V (Includes VDD12_DCD/DLL)
DVDD = 1.2 V
Typ
−127.4
NCO on, FIR85 off
NCO off, FIR85 on
NCO on, FIR85 on
NCO on, FIR85 on, at 6 GSPS
Includes VTT_1P2, BIAS_VDD_1P2
Connected to PLL_CLK_VDD12
Rev. 0 | Page 5 of 139
AD9161/AD9162
Parameter
8 LANES, 3× INTERPOLATION (80%), 4.5 GSPS
Analog Supply Currents
VDD25_DAC = 2.5 V
VDD12A = 1.2 V
VDD12_CLK = 1.2 V
VNEG_N1P2 = −1.2 V
Digital Supply Currents
DVDD = 1.2 V
IOVDD1 = 2.5 V
SERDES Supply Currents
VDD_1P2 = 1.2 V
DVDD_1P2 = 1.2 V
PLL_LDO_VDD12 = 1.2 V
SYNC_VDD_3P3 = 3.3 V
POWER DISSIPATION
3 GSPS
NRZ Mode, 2×, FIR85 Enabled, NCO On
2× NRZ Mode, 6×, FIR85 Enabled, NCO On
2× NRZ Mode, 4×, FIR85 Enabled, NCO On
2× NRZ Mode, 1×, FIR85 Enabled, NCO On
NRZ Mode, 24×, FIR85 Disabled, NCO On
5 GSPS
NCO Mode, FIR85 Disabled, NCO On
NRZ Mode, 4×, FIR85 Disabled, NCO On
2× NRZ Mode, 4x, FIR85 Enabled, NCO Off
2× NRZ Mode, 4×, FIR85 Enabled, NCO On
NRZ Mode, 8×, FIR85 Disabled, NCO On
NRZ Mode, 16×, FIR85 Disabled, NCO On
2× NRZ Mode, 6×, FIR85 Enabled, NCO On
NRZ Mode, 3×, FIR85 Disabled, NCO On (4.5 GSPS)
1
Data Sheet
Test Conditions/Comments
NCO on, FIR85 on
Min
Typ
94
85
314.3
−112.1
Max
175
Unit
mA
µA
mA
mA
Includes VDD12_DCD/DLL
IOVDD = 2.5 V
948.5
2.5
mA
mA
Includes VTT_1P2, BIAS_VDD_1P2
432.3
62.3
84.7
9.2
mA
mA
mA
mA
2.1
2.1
2.1
1.94
W
W
W
W
1.3
W
Connected to PLL_CLK_VDD12
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 3× filter, eight-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
1× bypass mode (AD9162 only), eight-lane
JESD204B
Using 80%, 2× filter, one-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 2× filter, eight-lane JESD204B
Using 80%, 3× filter, eight-lane JESD204B
Using 80%, 3× filter, six-lane JESD204B
IOVDD can range from 1.8 V to 3.3 V, with ±5% tolerance.
Rev. 0 | Page 6 of 139
1.3
2.3
2.35
2.58
2.18
2.09
2.65
2.62
1.83
W
W
W
W
W
W
W
W
Data Sheet
AD9161/AD9162
SERIAL PORT AND CMOS PIN SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted.
Table 4.
Parameter
WRITE OPERATION
Maximum SCLK Clock Rate
SCLK Clock High
SCLK Clock Low
SDIO to SCLK Setup Time
SCLK to SDIO Hold Time
CS to SCLK Setup Time
SCLK to CS Hold Time
READ OPERATION
SCLK Clock Rate
SCLK Clock High
SCLK Clock Low
SDIO to SCLK Setup Time
SCLK to SDIO Hold Time
CS to SCLK Setup Time
SCLK to SDIO (or SDO) Data Valid Time
CS to SDIO (or SDO) Output Valid to High-Z
INPUTS (SDIO, SCLK, CS, RESET, TX_ENABLE)
Voltage Input
High
Low
Current Input
High
Low
OUTPUTS (SDIO, SDO)
Voltage Output
High
Low
Current Output
High
Low
Symbol
fSCLK, 1/tSCLK
tPWH
tPWL
tDS
tDH
tS
tH
Test Comments/Conditions
See Figure 141
SCLK = 20 MHz
SCLK = 20 MHz
Min
100
3.5
4
4
1
9
9
Typ
Max
Unit
MHz
ns
ns
ns
ns
ns
ns
2
0.5
1
0.5
See Figure 140 and Figure 141
fSCLK, 1/tSCLK
tPWH
tPWL
tDS
tDH
tS
tDV
20
Not shown in Figure 140 or
Figure 141
VIH
VIL
1.8 V ≤ IOVDD ≤ 2.5 V
1.8 V ≤ IOVDD ≤ 2.5 V
IIH
IIL
VOH
VOL
17
45
MHz
ns
ns
ns
ns
ns
ns
ns
0.3 × IOVDD
V
V
20
20
10
5
10
0.7 × IOVDD
75
−150
1.8 V ≤ IOVDD ≤ 3.3 V
1.8 V ≤ IOVDD ≤ 3.3 V
IOH
IOL
0.8 × IOVDD
0.2 × IOVDD
4
4
Rev. 0 | Page 7 of 139
µA
µA
V
V
mA
mA
AD9161/AD9162
Data Sheet
JESD204B SERIAL INTERFACE SPEED SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted.
Table 5.
Parameter
SERIAL INTERFACE SPEED
Half Rate
Full Rate
Oversampling
2× Oversampling
Test Conditions/Comments
Guaranteed operating range
Min
Typ
6
3
1.5
0.750
Max
Unit
12.5
6.25
3.125
1.5625
Gbps
Gbps
Gbps
Gbps
SYSREF± TO DAC CLOCK TIMING SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted.
Table 6.
Parameter1
8 mm × 8 mm BGA Package (AD9162BBCZ)
SYSREF± DIFFERENTIAL SWING = 0.4 V
Minimum Setup Time, tSYSS
Minimum Hold Time, tSYSH
SYSREF± DIFFERENTIAL SWING = 0.8 V
Minimum Setup Time, tSYSS
Minimum Hold Time, tSYSH
SYSREF± DIFFERENTIAL SWING = 1.0 V
Minimum Setup Time, tSYSS
Minimum Hold Time, tSYSH
11 mm × 11 mm BGA Package (AD9161BBCZ,
AD9162BBCAZ, AD9162BBCA)
SYSREF± DIFFERENTIAL SWING = 1.0 V
Minimum Setup Time, tSYSS
Minimum Hold Time, tSYSH
AC-coupled
DC-coupled, common-mode voltage = 0 V
DC-coupled, common-mode voltage = 1.25 V
AC-coupled
DC-coupled, common-mode voltage = 0 V
DC-coupled, common-mode voltage = 1.25 V
Min
Typ
Max
Unit
163
160
424
318
ps
ps
162
169
412
350
ps
ps
163
176
376
354
ps
ps
65
45
68
19
5
51
117
77
129
63
37
114
ps
ps
ps
ps
ps
ps
The SYSREF± pulse must be at least four DAC clock edges wide plus the setup and hold times in Table 6. For more information, see the Sync Processing Modes
Overview section.
tSYSS
tSYSH
SYSREF+
CLK+
MIN 4 DAC CLOCK EDGES
Figure 2. SYSREF± to DAC Clock Timing Diagram (Only SYSREF+ and CLK+ Shown)
Rev. 0 | Page 8 of 139
14379-002
1
Test Conditions/Comments
DC-coupled, common-mode voltage = 1.2 V
Data Sheet
AD9161/AD9162
DIGITAL INPUT DATA TIMING SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted.
Table 7.
Parameter
LATENCY 1
Interface
Interpolation
Power-Up Time
DETERMINISTIC LATENCY
Fixed
Variable
SYSREF± to LOCAL MULTIFRAME
CLOCKS (LMFC) DELAY
Test Conditions/Comments
Min
From DAC output off to enabled
Typ
Max
Unit
1
See Table 34
10
PCLK 2 cycle
ns
12
2
PCLK2 cycles
PCLK2 cycles
DAC clock cycles
4
Total latency (or pipeline delay) through the device is calculated as follows:
Total Latency = Interface Latency + Fixed Latency + Variable Latency + Pipeline Delay
See Table 34 for examples of the pipeline delay per block.
2
PCLK is the internal processing clock for the AD9161/AD9162 and equals the lane rate ÷ 40.
1
JESD204B INTERFACE ELECTRICAL SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 = DVDD_1P2 =
PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −40°C to +85°C, unless otherwise noted. VTT is the termination
voltage.
Table 8.
Parameter
JESD204B DATA INPUTS
Input Leakage Current
Logic High
Logic Low
Unit Interval
Common-Mode Voltage
Differential Voltage
VTT Source Impedance
Differential Impedance
Differential Return Loss
Common-Mode Return Loss
SYSREF± INPUT
Differential Impedance
DIFFERENTIAL OUTPUTS (SYNCOUT±) 2
Output Differential Voltage
Output Offset Voltage
1
2
Symbol
Test Conditions/Comments
Min
TA = 25°C
Input level = 1.2 V ± 0.25 V,
VTT = 1.2 V
Input level = 0 V
UI
VRCM
R_VDIFF
ZTT
ZRDIFF
RLRDIF
RLRCM
AC-coupled, VTT = VDD_1P2 1
At dc
At dc
80
Rev. 0 | Page 9 of 139
100
8
6
1333
+1.85
1050
30
120
110
121
420
1.2
Unit
µA
−4
80
−0.05
110
350
1.15
As measured on the input side of the ac coupling capacitor.
IEEE Standard 1596.3 LVDS compatible.
Max
10
165-ball CSP_BGA (AD9162 only)
169-ball CSP_BGA
Driving 100 Ω differential load
VOD
VOS
Typ
µA
ps
V
mV
Ω
Ω
dB
dB
Ω
Ω
450
1.27
mV
V
AD9161/AD9162
Data Sheet
AC SPECIFICATIONS
VDD25_DAC = 2.5 V, VDD12A = VDD12_CLK = 1.2 V, VNEG_N1P2 = −1.2 V, DVDD = 1.2 V, IOVDD = 2.5 V, VDD_1P2 =
DVDD_1P2 = PLL_LDO_VDD12 = 1.2 V, SYNC_VDD_3P3 = 3.3 V, IOUTFS = 40 mA, TA = −25°C.
Table 9. AD9161 Specifications
Parameter
SPURIOUS-FREE DYNAMIC RANGE (SFDR) 1
Single Tone, fDAC = 5000 MSPS
fOUT = 70 MHz
fOUT = 500 MHz
fOUT = 1000 MHz
fOUT = 2000 MHz
fOUT = 4000 MHz
Single Tone, fDAC = 5000 MSPS
fOUT = 70 MHz
fOUT = 500 MHz
fOUT = 1000 MHz
fOUT = 2000 MHz
fOUT = 4000 MHz
Data Over Cable Service Interface Specification (DOCSIS)
fOUT = 70 MHz
fOUT = 70 MHz
fOUT = 70 MHz
fOUT = 950 MHz
fOUT = 950 MHz
fOUT = 950 MHz
ADJACENT CHANNEL POWER
fOUT = 877 MHz
fOUT = 877 MHz
INTERMODULATION DISTORTION
fOUT = 900 MHz
fOUT = 900 MHz
fOUT = 1800 MHz
fOUT = 1800 MHz
NOISE SPECTRAL DENSITY (NSD)
Single Tone, fDAC = 5000 MSPS
fOUT = 550 MHz
fOUT = 960 MHz
fOUT = 1990 MHz
1
2
Test Conditions/Comments
With Marki Microwave BAL-0006SMG 2
Min
FIR85 enabled
−6 dBFS, shuffle enabled
FIR85 enabled
fDAC = 3076 MSPS
Single carrier
Four carriers
Eight carriers
Single carriers
Four carriers
Eight carriers
fDAC = 5000 MSPS
One carrier, first adjacent channel
Two carriers, first adjacent channel
fDAC = 5000 MSPS, two-tone test
0 dBFS
−6 dBFS, shuffle enabled
0 dBFS
−6 dBFS, shuffle enabled
See the Clock Input section for more details on optimizing SFDR and reducing the image of the fundamental with clock input tuning.
The Marki Microwave BAL-0006SMG is used on the AD9162-FMC-EBZ evaluation board.
Rev. 0 | Page 10 of 139
Typ
Max
Unit
−82
−75
−65
−70
−55
dBc
dBc
dBc
dBc
dBc
−75
−75
−70
−75
−50
dBc
dBc
dBc
dBc
dBc
−70
−68
−65
−70
−68
−64
dBc
dBc
dBc
dBc
dBc
dBc
−76
−75
dBc
dBc
−75
−80
−71
−75
dBc
dBc
dBc
dBc
−157
−155
−155
dBm/Hz
dBm/Hz
dBm/Hz
Data Sheet
AD9161/AD9162
Table 10. AD9162 Specifications
Parameter
SPURIOUS-FREE DYNAMIC RANGE (SFDR) 1
Single Tone, fDAC = 5000 MSPS
fOUT = 70 MHz
fOUT = 500 MHz
fOUT = 1000 MHz
fOUT = 2000 MHz
fOUT = 4000 MHz
Single Tone, fDAC = 5000 MSPS
fOUT = 70 MHz
fOUT = 500 MHz
fOUT = 1000 MHz
fOUT = 2000 MHz
fOUT = 4000 MHz
DOCSIS
fOUT = 70 MHz
fOUT = 70 MHz
fOUT = 70 MHz
fOUT = 950 MHz
fOUT = 950 MHz
fOUT = 950 MHz
Wireless Infrastructure
fOUT = 960 MHz
fOUT = 1990 MHz
ADJACENT CHANNEL POWER
fOUT = 877 MHz
fOUT = 877 MHz
fOUT = 1887 MHz
fOUT = 1980 MHz
INTERMODULATION DISTORTION
fOUT = 900 MHz
fOUT = 900 MHz
fOUT = 1800 MHz
fOUT = 1800 MHz
NOISE SPECTRAL DENSITY (NSD)
Single Tone, fDAC = 5000 MSPS
fOUT = 550 MHz
fOUT = 960 MHz
fOUT = 1990 MHz
SINGLE SIDEBAND (SSB) PHASE NOISE AT OFFSET
1 kHz
10 kHz
100 kHz
1 MHz
10 MHz
1
2
Test Conditions/Comments
With Marki Microwave BAL-0006SMG 2
Min
FIR85 enabled
−6 dBFS, shuffle enabled
FIR85 enabled
fDAC = 3076 MSPS
Single carrier
Four carriers
Eight carriers
Single carriers
Four carriers
Eight carriers
fDAC = 5000 MSPS
Two-carrier GSM signal at −9 dBFS;
across 925 MHz to 960 MHz band
Two-carrier GSM signal at −9 dBFS;
across 1930 MHz to 1990 MHz band
fDAC = 5000 MSPS
One carrier, first adjacent channel
Two carriers, first adjacent channel
One carriers, first adjacent channel
Four carriers, first adjacent channel
fDAC = 5000 MSPS, two-tone test
0 dBFS
−6 dBFS, shuffle enabled
0 dBFS
−6 dBFS, shuffle enabled
Typ
Max
Unit
−82
−75
−65
−70
−60
dBc
dBc
dBc
dBc
dBc
−75
−75
−70
−75
−65
dBc
dBc
dBc
dBc
dBc
−70
−70
−67
−70
−68
−64
dBc
dBc
dBc
dBc
dBc
dBc
−85
dBc
−81
dBc
−79
−76
−74
−70
dBc
dBc
dBc
dBc
−80
−80
−68
−78
dBc
dBc
dBc
dBc
−168
−167
−164
dBm/Hz
dBm/Hz
dBm/Hz
−119
−125
−135
−144
−156
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
fOUT = 3800 MHz, fDAC = 4000 MSPS
See the Clock Input section for more details on optimizing SFDR and reducing the image of the fundamental with clock input tuning.
The Marki Microwave BAL-0006SMG is used on the AD9162-FMC-EBZ evaluation board.
Rev. 0 | Page 11 of 139
AD9161/AD9162
Data Sheet
ABSOLUTE MAXIMUM RATINGS
THERMAL RESISTANCE
Table 11.
Parameter
ISET, VREF to VBG_NEG
SERDINx±,
VTT_1P2, SYNCOUT±
OUTPUT± to VNEG_N1P2
SYSREF±
CLK± to Ground
RESET, IRQ, CS, SCLK, SDIO,
SDO to Ground
Junction Temperature1
fDAC = 6 GSPS
fDAC ≤ 5.1 GSPS
Ambient Operating
Temperature Range (TA)
Storage Temperature Range
1
Rating
−0.3 V to VDD25_DAC + 0.3 V
−0.3 V to SYNC_VDD_3P3 + 0.3 V
−0.3 V to VDD25_DAC + 0.3 V
GND − 0.5 V to +2.5 V
−0.3 V to VDD12_CLK + 0.3 V
−0.3 V to IOVDD + 0.3 V
Typical θJA and θJC values are specified for a 4-layer JEDEC 2S2P
high effective thermal conductivity test board for balled
surface-mount packages. θJA is obtained in still air conditions
(JESD51-2). Airflow increases heat dissipation, effectively reducing
θJA. θJC is obtained with the test case temperature monitored at
the bottom of the package.
ΨJT is thermal characteristic parameters obtained with θJA in still
air test conditions but are not applicable to the CSP_BGA package.
Estimate the junction temperature (TJ) using the following
equations:
105°C
110°C
−40°C to +85°C
TJ = TT + (ΨJT × PDISS)
−65°C to +150°C
Some operating modes of the device may cause the device to approach or
exceed the maximum junction temperature during operation at supported
ambient temperatures. Removal of heat from the device may require
additional measures such as active airflow, heat sinks, or other measures.
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
where:
TT is the temperature measured at the top of the package.
PDISS is the total device power dissipation.
Table 12. Thermal Resistance
Package Type
165-Ball CSP_BGA
169-Ball CSP_BGA
ESD CAUTION
Rev. 0 | Page 12 of 139
θJA
15.4
14.6
θJC
0.04
0.02
Unit
°C/W
°C/W
Data Sheet
AD9161/AD9162
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
A
2
3
4
5
6
VNEG_N1P2 VDD25_DAC VNEG_N1P2 VNEG_N1P2 VDD25_DAC VDD25_DAC
7
8
OUTPUT–
OUTPUT+
9
10
11
12
VDD25_DAC VDD25_DAC VNEG_N1P2 VNEG_N1P2
13
14
15
VSS
VSS
ISET
A
VDD12A
VDD12A
VREF
B
B
VSS
VSS
VDD25_DAC VNEG_N1P2 VNEG_N1P2 VDD25_DAC VDD25_DAC VDD25_DAC VDD25_DAC VNEG_N1P2 VNEG_N1P2 VDD25_DAC
C
CLK+
VSS
VDD25_DAC VNEG_N1P2 VNEG_N1P2 VDD25_DAC VDD25_DAC VNEG_N1P2 VNEG_N1P2 VDD25_DAC
D
CLK–
VSS
VSS
VSS
VSS
VSS
D
E
VSS
VSS
VSS
VSS
VSS
VDD12_CLK
E
VDD12_CLK VDD12_CLK VDD12_CLK
F
F
VDD12_CLK VDD12_CLK VDD12_CLK
VSS
VSS
VDD12_DCD/ VDD12_DCD/
DLL
DLL
VBG_NEG
VNEG_N1P2 VDD25_DAC C
VSS
VSS
VSS
VSS
VDD12_
DCD/DLL
VDD12_
DCD/DLL
VSS
VSS
CS
G
G
IRQ
VSS
VSS
H
VSS
TX_ENABLE
VSS
VSS
VSS
VSS
VSS
VSS
VSS
SDO
VSS
H
J
SERDIN7+
VDD_1P2
RESET
VSS
VSS
VSS
VSS
VSS
SCLK
VDD_1P2
SERDIN0+
J
K
SERDIN7–
VDD_1P2
IOVDD
DVDD
DVDD
DVDD
DVDD
DVDD
SDIO
VDD_1P2
SERDIN0–
K
L
VSS
VSS
DVDD_1P2
DVDD_1P2
VSS
VSS
L
M
SERDIN6+
VDD_1P2
VTT_1P2
VTT_1P2
VDD_1P2
SERDIN1+
M
N
SERDIN6–
VDD_1P2
VDD_1P2
SERDIN1–
N
P
VSS
SYNC_
VDD_3P3
R
BIAS_VDD_
1P2
1
SYSREF+
SYSREF–
VSS
VSS
PLL_CLK_
VDD12
PLL_LDO_
VDD12
VSS
SYNCOUT–
SYNCOUT+
VDD_1P2
VDD_1P2
DNC
VDD_1P2
VDD_1P2
PLL_LDO_
BYPASS
VDD_1P2
VDD_1P2
DNC
VDD_1P2
VDD_1P2
SYNC_
VDD_3P3
VSS
P
VSS
SERDIN5+
SERDIN5–
VSS
SERDIN4+
SERDIN4–
VSS
SERDIN3–
SERDIN3+
VSS
SERDIN2–
SERDIN2+
VSS
BIAS_
VDD_1P2
R
2
3
4
5
6
7
8
9
10
11
12
13
14
15
–1.2V ANALOG SUPPLY V
2.5V ANALOG SUPPLY V
1.2V DAC SUPPLY V
GROUND
1.2V DAC CLK SUPPLY V
SERDES INPUT
SERDES 3.3V VCO SUPPLY V
SERDES 1.2V SUPPLY V
DAC RF SIGNALS
SYSREF±/SYNCOUT±
CMOS I/O
IOVDD
REFERENCE
DNC = DO NOT CONNECT.
14379-003
1
Figure 3. 165-Ball CSP_BGA Pin Configuration
Table 13. 165-Ball CSP_BGA Pin Function Descriptions
Pin No.
A1, A3, A4, A11, A12, B4, B5, B10, B11, C5, C6, C9, C10, C14
A2, A5, A6, A9, A10, B3, B6, B7, B8, B9, B12, C4, C7, C8, C11,
C15
A7
A8
A13, A14, B1, B2, C2, D2, D3, D13, D14, D15, E1, E2, E3, E13,
E14, F6, F7, F8, F9, F10, G2, G3, G8, G13, G14, H1, H3, H6,
H7, H8, H9, H10, H13, H15, J6, J7, J8, J9, J10, L1, L2, L14,
L15, N6, N7, N10, P1, P15, R2, R5, R8, R11, R14
A15
Mnemonic
VNEG_N1P2
VDD25_DAC
Description
−1.2 V Analog Supply Voltage.
2.5 V Analog Supply Voltage.
OUTPUT−
OUTPUT+
VSS
DAC Negative Current Output.
DAC Positive Current Output.
Supply Return. Connect these pins to ground.
ISET
B13, B14
B15
VDD12A
VREF
C1, D1
C12
CLK+, CLK−
VBG_NEG
E15, F1, F2, F3, F13, F14, F15
G1
VDD12_CLK
IRQ
Reference Current. Connect this pin to VNEG_N1P2 with
a 9.6 kΩ resistor.
1.2 V Analog Supply Voltage.
1.2 V Reference Input/Output. Connect this pin to VSS
with a 1 µF capacitor.
Positive and Negative DAC Clock Inputs.
−1.2 V Reference. Connect this pin to VNEG_N1P2 with
a 0.1 µF capacitor.
1.2 V Clock Supply Voltage.
Interrupt Request Output (Active Low, Open Drain).
Rev. 0 | Page 13 of 139
AD9161/AD9162
Data Sheet
Pin No.
G6, G7, G9, G10
G15
Mnemonic
VDD12_DCD/DLL
CS
H14
SDO
J13
SCLK
K13
SDIO
J3
RESET
H2
TX_ENABLE
P5, P11
J2, J14, K2, K14, M2, M14, N2, N14, P3, P4, P6, P7, P9, P10,
P12, P13
K3
DNC
VDD_1P2
K6, K7, K8, K9, K10
L3, L13
M3, M13
J1, K1
IOVDD
N4, N5
DVDD
DVDD_1P2
VTT_1P2
SERDIN7+,
SERDIN7−
SERDIN6+,
SERDIN6−
SERDIN5+,
SERDIN5−
SERDIN4+,
SERDIN4SERDIN3−,
SERDIN3+
SERDIN2−,
SERDIN2+
SERDIN1+,
SERDIN1−
SERDIN0+,
SERDIN0−
SYSREF+, SYSREF−
N8
PLL_CLK_VDD12
N9
N11, N12
PLL_LDO_VDD12
SYNCOUT−
, SYNCOUT+
SYNC_VDD_3P3
PLL_LDO_BYPASS
BIAS_VDD_1P2
M1, N1
R3, R4
R6, R7
R9, R10
R12, R13
M15, N15
J15, K15
P2, P14
P8
R1, R15
Rev. 0 | Page 14 of 139
Description
1.2 V Digital Supply Voltage.
Serial Port Chip Select Bar (Active Low) Input. CMOS
levels on this pin are determined with respect to
IOVDD.
Serial Port Data Output. CMOS levels on this pin are
determined with respect to IOVDD.
Serial Port Data Clock. CMOS levels on this pin are
determined with respect to IOVDD.
Serial Port Data Input/Output. CMOS levels on this pin
are determined with respect to IOVDD.
Reset Bar (Active Low) Input. CMOS levels on this pin
are determined with respect to IOVDD.
Transmit Enable Input. This pin can be used instead of
the DAC output bias power down bits in Register 0x040,
Bits [1:0] to enable the DAC output. CMOS levels are
determined with respect to IOVDD.
Do Not Connect. Do not connect to these pins.
1.2 V SERDES Digital Supply.
Supply Voltage for CMOS Input/Output and SPI.
Operational for 1.8 V to 3.3 V plus tolerance (see Table 1
for details).
1.2 V Digital Supply Voltage.
1.2 V SERDES Digital Supply Voltage.
1.2 V SERDES VTT Digital Supply Voltage.
SERDES Lane 7 Positive and Negative Inputs.
SERDES Lane 6 Positive and Negative Inputs.
SERDES Lane 5 Positive and Negative Inputs.
SERDES Lane 4 Positive and Negative Inputs.
SERDES Lane 3 Negative and Positive Inputs.
SERDES Lane 2 Negative and Positive Inputs.
SERDES Lane 1 Positive and Negative Inputs.
SERDES Lane 0 Positive and Negative Inputs.
System Reference Positive and Negative Inputs. These
pins are self biased for ac coupling. They can be
ac-coupled or dc-coupled.
1.2 V SERDES Phase-Locked Loop (PLL) Clock Supply
Voltage.
1.2 V SERDES PLL Supply.
Negative and Positive LVDS Sync (Active Low) Output
Signals.
3.3 V SERDES Sync Supply Voltage.
1.2 V SERDES PLL Supply Voltage Bypass.
1.2 V SERDES Supply Voltage.
Data Sheet
AD9161/AD9162
1
2
3
4
5
6
7
8
9
10
11
12
13
A
VSS
VNEG_N1P2
VDD25_DAC
VNEG_N1P2
VDD25_DAC
OUTPUT–
OUTPUT+
VDD25_DAC
VNEG_N1P2
VDD25_DAC
VSS
ISET
VREF
A
B
CLK+
VSS
VSS
VDD25_DAC
VNEG_N1P2
VDD25_DAC
VDD25_DAC
VNEG_N1P2
VDD25_DAC
VDD12A
VDD12A
VDD25_DAC
VNEG_N1P2
B
C
CLK–
VSS
VSS
VSS
VDD25_DAC
VNEG_N1P2
VNEG_N1P2
VDD25_DAC
VBG_NEG
VSS
VSS
VSS
VSS
C
D
VSS
VDD12_CLK
VDD12_CLK
VDD12_CLK
VDD12_CLK
VSS
VSS
VDD12_CLK
VDD12_CLK
VDD12_CLK
VDD12_CLK
VDD12_CLK
VDD12_CLK
D
E
VDD12_CLK
VSS
VSS
VSS
DVDD
DVDD
VSS
DVDD
DVDD
VSS
VSS
VSS
VSS
E
F
SYSREF+
SYSREF–
VSS
VSS
VSS
VSS
VSS
VSS
VSS
VSS
VSS
CS
VSS
F
G
VSS
VSS
TX_ENABLE
IRQ
DVDD
DVDD
DVDD
DVDD
DVDD
SDIO
SDO
VSS
VSS
G
H
SERDIN7+
SERDIN7–
VDD_1P2
RESET
IOVDD
DVDD_1P2
VSS
DVDD_1P2
IOVDD
SCLK
VDD_1P2
SERDIN0–
SERDIN0+
H
J
VSS
VSS
VDD_1P2
DNC
DNC
VSS
VSS
VSS
SYNCOUT–
SYNCOUT+
VDD_1P2
VSS
VSS
J
K
SERDIN6+
SERDIN6–
VTT_1P2
SYNC_
VDD_3P3
DNC
VSS
PLL_CLK_
VDD12
PLL_LDO_
VDD12
DNC
SYNC_
VDD_3P3
VTT_1P2
SERDIN1–
SERDIN1+
K
L
VSS
VSS
VDD_1P2
VDD_1P2
VDD_1P2
VSS
DNC
VSS
VDD_1P2
VDD_1P2
VDD_1P2
VSS
VSS
L
M
VSS
VSS
SERDIN5+
VSS
SERDIN4+
VSS
PLL_LDO_
BYPASS
VSS
SERDIN3+
VSS
SERDIN2+
VSS
VSS
M
N
BIAS_VDD_1P2
VSS
SERDIN5–
VSS
SERDIN4–
VSS
VSS
VSS
SERDIN3–
VSS
SERDIN2–
VSS
BIAS_
VDD_1P2
N
1
2
3
4
5
6
7
8
9
10
11
12
13
1.2V DAC CLK SUPPLY V
SERDES INPUT
SERDES 3.3V VCO SUPPLY V
SERDES 1.2V SUPPLY V
DAC RF SIGNALS
SYSREF±/SYNCOUT±
CMOS I/O
IOVDD
DNC = DO NOT CONNECT.
REFERENCE
14379-004
–1.2V ANALOG SUPPLY V
2.5V ANALOG SUPPLY V
1.2V DAC SUPPLY V
GROUND
Figure 4. 169-Ball CSP_BGA Pin Configuration
Table 14. 169-Ball CSP_BGA Pin Function Descriptions
Pin No.
A1, A11, B2, B3, C2, C3, C4, C10, C11, C12, C13, D1, D6, D7, E2, E3,
E4, E7, E10, E11, E12, E13, F3, F4, F5, F6, F7, F8, F9, F10, F11, F13,
G1, G2, G12, G13, H7, J1, J2, J6, J7, J8, J12, J13, K6, L1, L2, L6, L8,
L12, L13, M1, M2, M4, M6, M8, M10, M12, M13, N2, N4, N6, N7, N8,
N10, N12
A2, A4, A9, B5, B8, B13, C6, C7
A3, A5, A8, A10, B4, B6, B7, B9, B12, C5, C8
A6
A7
A12
Mnemonic
VSS
Description
Supply Return. Connect these pins to ground.
VNEG_N1P2
VDD25_DAC
OUTPUT−
OUTPUT+
ISET
A13
VREF
B1, C1
B10, B11
C9
CLK+, CLK−
VDD12A
VBG_NEG
D2, D3, D4, D5, D8, D9, D10, D11, D12, D13, E1
E5, E6, E8, E9, G5, G6, G7, G8, G9
F1, F2
VDD12_CLK
DVDD
SYSREF+, SYSREF−
−1.2 V Analog Supply Voltage.
2.5 V Analog Supply Voltage.
DAC Negative Current Output.
DAC Positive Current Output.
Reference Current. Connect this pin to
VNEG_N1P2 with a 9.6 kΩ resistor.
1.2 V Reference Input/Output. Connect this pin
to VSS with a 1 µF capacitor.
Positive and Negative DAC Clock Inputs.
1.2 V Analog Supply Voltage.
−1.2 V Reference. Connect this pin to
VNEG_N1P2 with a 0.1 µF capacitor.
1.2 V Clock Supply Voltage.
1.2 V Digital Supply Voltage.
System Reference Positive and Negative Inputs.
These pins are self biased for ac coupling. They
can be ac-coupled or dc-coupled.
Rev. 0 | Page 15 of 139
AD9161/AD9162
Data Sheet
Pin No.
F12
Mnemonic
CS
G3
TX_ENABLE
G4
IRQ
G10
SDIO
G11
SDO
H10
SCLK
H3, H11, J3, J11, L3, L4, L5, L9, L10, L11
H4
VDD_1P2
RESET
H5, H9
IOVDD
H6, H8
H1, H2
DVDD_1P2
SERDIN7+,
SERDIN7−
SERDIN6+,
SERDIN6−
SERDIN5+,
SERDIN5−
SERDIN4+,
SERDIN4−
SERDIN3+,
SERDIN3−
SERDIN2+,
SERDIN2−
SERDIN1−,
SERDIN1+
SERDIN0−,
SERDIN0+
DNC
SYNCOUT−
, SYNCOUT+
VTT_1P2
SYNC_VDD_3P3
PLL_CLK_VDD12
PLL_LDO_VDD12
PLL_LDO_BYPASS
BIAS_VDD_1P2
K1, K2
M3, N3
M5, N5
M9, N9
M11, N11
K12, K13
H12, H13
J4, J5, K5, K9, L7
J9, J10
K3, K11
K4, K10
K7
K8
M7
N1, N13
Rev. 0 | Page 16 of 139
Description
Serial Port Chip Select Bar (Active Low) Input.
CMOS levels on this pin are determined with
respect to IOVDD.
Transmit Enable Input. This pin can be used
instead of the DAC output bias power down bits
in Register 0x040, Bits [1:0] to enable the DAC
output. CMOS levels are determined with
respect to IOVDD.
Interrupt Request Output (Active Low, Open
Drain).
Serial Port Data Input/Output. CMOS levels on
this pin are determined with respect to IOVDD.
Serial Port Data Output. CMOS levels on this pin
are determined with respect to IOVDD.
Serial Port Data Clock. CMOS levels on this pin
are determined with respect to IOVDD.
1.2 V SERDES Digital Supply.
Reset Bar (Active Low) Input. CMOS levels on this
pin are determined with respect to IOVDD.
Supply Voltage for CMOS Input/Output and SPI.
Operational for 1.8 V to 3.3 V (see Table 1 for
details).
1.2 V SERDES Digital Supply Voltage.
SERDES Lane 7 Positive and Negative Inputs.
SERDES Lane 6 Positive and Negative Inputs.
SERDES Lane 5 Positive and Negative Inputs.
SERDES Lane 4 Positive and Negative Inputs.
SERDES Lane 3 Positive and Negative Inputs.
SERDES Lane 2 Positive and Negative Inputs.
SERDES Lane 1 Negative and Positive Inputs.
SERDES Lane 0 Negative and Positive Inputs.
Do Not Connect. Do not connect to these pins.
Negative and Positive LVDS Sync (Active Low)
Output Signals.
1.2 V SERDES VTT Digital Supply Voltage.
3.3 V SERDES Sync Supply Voltage.
1.2 V SERDES PLL Clock Supply Voltage.
1.2 V SERDES PLL Supply.
1.2 V SERDES PLL Supply Voltage Bypass.
1.2 V SERDES Supply Voltage.
Data Sheet
AD9161/AD9162
TYPICAL PERFORMANCE CHARACTERISTICS
AD9161
Static Linearity
0.4
0.3
0.3
0.2
0.2
0.1
0.1
DNL (LSB)
0.4
0
–0.1
–0.1
–0.2
–0.2
–0.3
–0.3
500
1000
1500
2000
CODE
–0.4
0
0.3
0.2
0.2
0.1
0.1
DNL (LSB)
0.3
0
–0.1
–0.2
–0.2
–0.3
–0.3
1000
1500
2000
CODE
–0.4
0
0.3
0.2
0.2
0.1
0.1
DNL (LSB)
0.3
0
–0.1
–0.2
–0.2
–0.3
–0.3
–0.4
1500
CODE
1500
2000
0
–0.1
2000
14379-507
INL (LSB)
0.4
1000
1000
Figure 9. DNL, IOUTFS = 30 mA
0.4
500
500
CODE
Figure 6. INL, IOUTFS = 30 mA
0
2000
0
–0.1
14379-506
INL (LSB)
0.4
500
1500
Figure 8. DNL, IOUTFS = 20 mA
0.4
0
1000
CODE
Figure 5. INL, IOUTFS = 20 mA
–0.4
500
14379-509
0
Figure 7. INL, IOUTFS = 40 mA
–0.4
0
500
1000
1500
CODE
Figure 10. DNL, IOUTFS = 40 mA
Rev. 0 | Page 17 of 139
2000
14379-510
–0.4
14379-508
0
14379-505
INL (LSB)
IOUTFS = 40 mA, nominal supplies, TA = 25°C, unless otherwise noted.
AD9161/AD9162
Data Sheet
AC Performance (NRZ Mode)
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–80
–40
–60
1000
2000
3000
4000
5000
FREQUENCY (MHz)
0
3000
4000
5000
Figure 14. Single-Tone Spectrum at fOUT = 2000 MHz
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–40
–60
–80
0
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-312
–80
0
–40
fDAC 2500MHz
fDAC 3000MHz
fDAC 5000MHz
fDAC 6000MHz
–50
2000
3000
4000
5000
FREQUENCY (MHz)
Figure 15. Single-Tone Spectrum at fOUT = 2000 MHz (FIR85 Enabled)
Figure 12. Single-Tone Spectrum at fOUT = 70 MHz (FIR85 Enabled)
–40
1000
14379-315
MAGNITUDE (dBm)
2000
FREQUENCY (MHz)
Figure 11. Single-Tone Spectrum at fOUT = 70 MHz
fDAC 2500MHz
fDAC 3000MHz
fDAC 5000MHz
fDAC 6000MHz
–50
–60
IMD (dBc)
–60
–70
–70
–80
–80
–90
–90
–100
0
500
1000
1500
2000
fOUT (MHz)
2500
3000
14379-313
SFDR (dBc)
1000
14379-314
0
14379-311
–80
–100
0
500
1000
1500
2000
fOUT (MHz)
Figure 16. IMD vs. fOUT over fDAC
Figure 13. SFDR vs. fOUT over fDAC
Rev. 0 | Page 18 of 139
2500
3000
14379-416
MAGNITUDE (dBm)
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
Data Sheet
AD9161/AD9162
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–40
–40
DIGITAL SCALE 0dB
DIGITAL SCALE –6dB
DIGITAL SCALE –12dB
DIGITAL SCALE –18dB
–50
–50
SFDR (dBc)
–60
SFDR (dBc)
IOUTFS 20mA
IOUTFS 30mA
IOUTFS 40mA
–70
–80
–60
–70
–80
–90
–90
0
500
1000
1500
2000
2500
fOUT (MHz)
–100
14379-317
–100
0
2000
2500
–40
IOUTFS 20mA
IOUTFS 30mA
IOUTFS 40mA
–50
–60
–60
IMD (dBc)
IMD (dBc)
1500
Figure 20. SFDR vs. fOUT over DAC IOUTFS
DIGITAL SCALE 0dB
DIGITAL SCALE –6dB
DIGITAL SCALE –12dB
DIGITAL SCALE –18dB
–50
1000
fOUT (MHz)
Figure 17. SFDR vs. fOUT over Digital Full Scale
–40
500
14379-322
SHUFFLE FALSE
SHUFFLE TRUE
–70
–80
–70
–80
–90
–90
0
1000
2000
3000
4000
5000
fOUT (MHz)
–100
14379-418
–100
0
1000
2000
3000
4000
5000
fOUT (MHz)
Figure 18. IMD vs. fOUT over Digital Full Scale
14379-422
SHUFFLE FALSE
SHUFFLE TRUE
Figure 21. IMD vs. fOUT over DAC IOUTFS
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
Figure 19. Single-Tone NSD Measured at 70 MHz vs. fOUT over fDAC
–160
–165
–170
–175
14379-619
fOUT (MHz)
–155
fDAC 2500MHz
fDAC 3000MHz
fDAC 5000MHz
fDAC 6000MHz
0
500
1000
fOUT (MHz)
1500
2000
14379-425
SINGLE-TONE NSD (dBm/Hz)
SINGLE-TONE NSD (dBm/Hz)
–150
Figure 22. Single-Tone NSD Measured at 10% Offset from fOUT vs. fOUT over fDAC
Rev. 0 | Page 19 of 139
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–150
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–155
W-CDMA NSD (dBm/Hz)
–155
–160
–165
–160
–165
500
1000
1500
fOUT (MHz)
2000
2500
3000
Figure 23. W-CDMA NSD Measured at 70 MHz vs. fOUT over fDAC
–175
0
500
1000
1500
2000
2500
fOUT (MHz)
Figure 25. W-CDMA NSD Measured at 10% Offset from fOUT vs. fOUT over fDAC
14379-336
0
14379-532
–175
14379-225
–170
–170
14379-333
W-CDMA NSD (dBm/Hz)
–150
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
Figure 24. Single-Carrier W-CDMA at 877.5 MHz
Figure 26. Two-Carrier W-CDMA at 875 MHz
Rev. 0 | Page 20 of 139
Data Sheet
AD9161/AD9162
AC (Mix-Mode)
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–40
–60
–80
1000
2000
3000
4000
5000
FREQUENCY (MHz)
0
3000
4000
5000
Figure 30. Single-Tone Spectrum at fOUT = 4000 MHz
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–40
–60
–80
0
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-440
–80
Figure 28. Single-Tone Spectrum at fOUT = 2550 MHz (FIR85 Enabled)
0
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-444
MAGNITUDE (dBm)
2000
FREQUENCY (MHz)
Figure 27. Single-Tone Spectrum at fOUT = 2550 MHz
Figure 31. Single-Tone Spectrum at fOUT = 4000 MHz (FIR85 Enabled)
–140
–40
–145
–50
–150
SFDR (dBc)
–60
–155
–160
–70
–80
–165
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–170
–175
2000
3000
4000
5000
6000
7000
8000
fOUT (MHz)
9000
10000
–90
14379-424
SINGLE-TONE NSD (dBm/Hz)
1000
14379-344
0
14379-439
–80
Figure 29. Single-Tone NSD vs. fOUT
–100
2000
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
SHUFFLE FALSE
SHUFFLE TRUE
3000
4000
5000
6000
7000
fOUT (MHz)
Figure 32. SFDR vs. fOUT over Digital Full Scale
Rev. 0 | Page 21 of 139
8000
14379-445
MAGNITUDE (dBm)
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–50
–60
IMD (dBc)
IMD (dBc)
–60
–70
–70
–80
–80
–90
–90
SHUFFLE FALSE
SHUFFLE TRUE
3000
4000
5000
6000
7000
8000
fOUT (MHz)
–100
2000
14379-446
–100
2000
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
3000
–50
–40
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–50
SFDR (dBc)
IMD (dBc)
–90
–90
2000
3000
4000
5000
6000
7000
8000
9000
14379-447
–80
fOUT (MHz)
–100
1000
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
–50
–60
–70
–80
4000
5000
6000
7000
fOUT (MHz)
8000
14379-448
–90
3000
2000
3000
4000
5000
6000
7000
fOUT (MHz)
Figure 37. IMD vs. fOUT over fDAC
Figure 34. SFDR vs. fOUT over fDAC
SFDR (dBc)
8000
–70
–80
–100
2000
7000
–60
–70
–40
6000
Figure 36. IMD vs. fOUT over DAC IOUTFS
–60
–100
1000
5000
fOUT (MHz)
Figure 33. IMD vs. fOUT over Digital Full Scale
–40
4000
14379-449
–50
–40
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
Figure 35. SFDR vs. fOUT over DAC IOUTFS
Rev. 0 | Page 22 of 139
8000
9000
14379-450
–40
Data Sheet
AD9161/AD9162
0
0
–10
–10
–20
–20
–30
–40
–50
–60
–30
–40
–50
–60
–70
–70
–80
–80
1000
1500
2000
2500
3000
FREQUENCY (MHz)
–90
0
–10
–10
–20
–20
MAGNITUDE (dBc)
MAGNITUDE (dBc)
0
–30
–40
–50
–60
–60
–80
3000
FREQUENCY (MHz)
–90
14379-361
–90
2500
0
–10
–20
–20
MAGNITUDE (dBc)
0
–30
–40
–50
–60
2000
2500
3000
–60
–80
1500
2500
–50
–70
FREQUENCY (MHz)
2000
–40
–80
1000
1500
–30
–70
3000
14379-363
MAGNITUDE (dBc)
0
500
1000
Figure 42. Four Carriers at 950 MHz Output
–10
0
500
FREQUENCY (MHz)
Figure 39. Four Carriers at 70 MHz Output
–90
3000
–50
–80
2000
2500
–40
–70
1500
2000
–30
–70
1000
1500
Figure 41. Single Carrier at 950 MHz Output
0
500
1000
FREQUENCY (MHz)
Figure 38. Single Carrier at 70 MHz Output
0
500
14379-365
500
Figure 40. Eight Carriers at 70 MHz Output
–90
0
500
1000
1500
2000
2500
FREQUENCY (MHz)
Figure 43. Eight Carriers at 950 MHz Output
Rev. 0 | Page 23 of 139
3000
14379-366
0
14379-361
–90
14379-364
MAGNITUDE (dBc)
MAGNITUDE (dBc)
DOCSIS Performance (NRZ Mode)
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–50
–60
–70
–80
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
Figure 44. In-Band Second Harmonic vs. fOUT Performance for One DOCSIS
Carrier
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
Figure 47. In-Band Third Harmonic vs. fOUT Performance for One DOCSIS
Carrier
–80
0
200
400
600
800
1000
1200
1400
Figure 45. In-Band Second Harmonic vs. fOUT Performance for Four DOCSIS
Carriers
–50
–60
–70
–80
–90
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
14379-371
IN-BAND THIRD HARMONIC (dBc)
–70
14379-368
IN-BAND SECOND HARMONIC (dBc)
–60
fOUT (MHz)
Figure 48. In-Band Third Harmonic vs. fOUT Performance for Four DOCSIS
Carriers
–40
IN-BAND THIRD HARMONIC (dBc)
–40
–50
–60
–70
–80
0
200
400
600
800
fOUT (MHz)
1000
1200
1400
Figure 46. In-Band Second Harmonic vs. fOUT Performance for Eight DOCSIS
Carriers
–50
–60
–70
–80
–90
14379-369
IN-BAND SECOND HARMONIC (dBc)
–80
–40
–50
–90
–70
–90
–40
–90
–60
0
200
400
600
800
fOUT (MHz)
1000
1200
1400
14379-372
–90
–50
14379-370
IN-BAND THIRD HARMONIC (dBc)
–40
14379-367
IN-BAND SECOND HARMONIC (dBc)
–40
Figure 49. In-Band Third Harmonic vs. fOUT Performance for Eight DOCSIS
Carriers
Rev. 0 | Page 24 of 139
Data Sheet
AD9161/AD9162
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–40
Y-AXIS: FIRST ACP
Y-AXIS: SECOND ACP
Y-AXIS: THIRD ACP
Y-AXIS: FOURTH ACP
Y-AXIS: FIFTH ACP
–50
ACPR (dBc)
–50
–60
–70
–80
–60
–70
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
–90
14379-373
–90
0
200
–70
–80
1200
1400
1200
1400
–60
–70
200
400
600
800
1000
1200
1400
–90
14379-374
0
0
200
800
1000
Figure 54. 32-Carrier ACPR vs. fOUT
0
Y-AXIS: FIRST ACP
Y-AXIS: SECOND ACP
Y-AXIS: THIRD ACP
Y-AXIS: FOURTH ACP
Y-AXIS: FIFTH ACP
–10
–20
MAGNITUDE (dBc)
–50
600
fOUT (MHz)
Figure 51. Four-Carrier ACPR vs. fOUT
–40
400
14379-377
–80
fOUT (MHz)
–60
–70
–30
–40
–50
–60
–70
–80
–80
–90
0
200
400
600
800
1000
fOUT (MHz)
1200
1400
14379-375
ACPR (dBc)
1000
Y-AXIS: FIRST ACP
Y-AXIS: SECOND ACP
Y-AXIS: THIRD ACP
Y-AXIS: FOURTH ACP
Y-AXIS: FIFTH ACP
–50
ACPR (dBc)
ACPR (dBc)
–40
–60
–90
800
Figure 53. 16-Carrier ACPR vs. fOUT
Y-AXIS: FIRST ACP
Y-AXIS: SECOND ACP
Y-AXIS: THIRD ACP
Y-AXIS: FOURTH ACP
Y-AXIS: FIFTH ACP
–50
600
fOUT (MHz)
Figure 50. Single-Carrier Adjacent Channel Power Ratio (ACPR) vs. fOUT
–40
400
14379-376
–80
–90
0
500
1000
1500
2000
2500
FREQUENCY (MHz)
Figure 55. 194-Carrier, Sinc On, FIR85 Enabled
Figure 52. Eight-Carrier ACPR vs. fOUT
Rev. 0 | Page 25 of 139
3000
14379-378
ACPR (dBc)
–40
Y-AXIS: FIRST ACP
Y-AXIS: SECOND ACP
Y-AXIS: THIRD ACP
Y-AXIS: FOURTH ACP
Y-AXIS: FIFTH ACP
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–50
–60
–70
–80
–90
–100
0
200
400
600
800
1000
1200
fGAP (fOUT = fGAP) (MHz)
1400
14379-478
ACLR IN GAP CHANNEL (dBc)
–40
Figure 56. ACLR in Gap Channel vs. fGAP
Rev. 0 | Page 26 of 139
Data Sheet
AD9161/AD9162
AD9162
Static Linearity
IOUTFS = 40 mA, nominal supplies, TA = 25°C, unless otherwise noted.
15
4
2
10
5
–2
DNL (LSB)
INL (LSB)
0
0
–4
–6
–8
–5
0
10000
20000
30000
40000
50000
60000
CODE
–12
14379-005
–10
0
10000
20000
30000
40000
50000
60000
CODE
Figure 57. INL, IOUTFS = 20 mA
14379-008
–10
Figure 60. DNL, IOUTFS = 20 mA
15
4
2
10
5
–2
DNL (LSB)
INL (LSB)
0
0
–4
–6
–8
–5
0
10000
20000
30000
40000
50000
60000
CODE
–12
14379-006
–10
0
10000
20000
30000
40000
50000
60000
CODE
Figure 58. INL, IOUTFS = 30 mA
14379-009
–10
Figure 61. DNL, IOUTFS = 30 mA
4
15
2
10
DNL (LSB)
5
0
–2
–4
–6
–8
–5
–10
0
10000
20000
30000
40000
50000
CODE
60000
Figure 59. INL, IOUTFS = 40 mA
–12
0
10000
20000
30000
40000
50000
CODE
Figure 62. DNL, IOUTFS = 40 mA
Rev. 0 | Page 27 of 139
60000
14379-010
–10
14379-007
INL (LSB)
0
AD9161/AD9162
Data Sheet
AC Performance (NRZ Mode)
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–40
–60
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-011
0
0
0
0
–20
–20
MAGNITUDE (dBm)
4000
5000
–40
–60
–40
–60
–80
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-012
0
2000
3000
4000
5000
FREQUENCY (MHz)
–40
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–50
1000
Figure 67. Single-Tone Spectrum at fOUT = 2000 MHz (FIR85 Enabled)
Figure 64. Single-Tone Spectrum at fOUT = 70 MHz (FIR85 Enabled)
–40
0
14379-015
MAGNITUDE (dBm)
3000
Figure 66. Single-Tone Spectrum at fOUT = 2000 MHz
–80
–50
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–60
IMD (dBc)
–60
–70
–70
–80
–80
–90
–90
0
500
1000
1500
2000
fOUT (MHz)
2500
3000
14379-013
SFDR (dBc)
2000
FREQUENCY (MHz)
Figure 63. Single-Tone Spectrum at fOUT = 70 MHz
–100
1000
14379-014
–80
–80
Figure 65. SFDR vs. fOUT over fDAC
–100
0
500
1000
1500
2000
fOUT (MHz)
Figure 68. IMD vs. fOUT over fDAC
Rev. 0 | Page 28 of 139
2500
3000
14379-016
MAGNITUDE (dBm)
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
Data Sheet
AD9161/AD9162
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–40
SHUFFLE FALSE
SHUFFLE TRUE
–50
–70
–70
–80
–80
–90
–90
–100
0
500
1000
1500
2000
2500
fOUT (MHz)
–100
0
SHUFFLE FALSE
SHUFFLE TRUE
SFDR (dBc)
–70
–80
–90
–90
500
1000
1500
2000
2500
fOUT (MHz)
–100
0
–50
1500
2000
2500
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
–60
IMD (dBc)
–70
–70
–80
–80
–90
–90
500
1000
1500
fOUT (MHz)
2000
2500
14379-019
IN-BAND THIRD HARMONIC (dBc)
–40
–60
–100
0
1000
Figure 73. SFDR vs. fOUT over DAC IOUTFS
SHUFFLE FALSE
SHUFFLE TRUE
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
500
fOUT (MHz)
Figure 70. SFDR for In-Band Second Harmonic vs. fOUT over Digital Scale
–50
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
–70
–80
–40
2500
–60
–60
–100
0
2000
–50
14379-018
IN-BAND SECOND HARMONICA (dBc)
–50
1500
Figure 72. IMD vs. fOUT over Digital Scale
–40
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
1000
fOUT (MHz)
Figure 69. SFDR vs. fOUT over Digital Scale
–40
500
14379-020
IMD (dBc)
–60
14379-017
SFDR (dBc)
–60
SHUFFLE FALSE
SHUFFLE TRUE
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
14379-021
–50
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
Figure 71. SFDR for In-Band Third Harmonic vs. fOUT over Digital Scale
Rev. 0 | Page 29 of 139
–100
0
500
1000
1500
2000
fOUT (MHz)
Figure 74. IMD vs. fOUT over DAC IOUTFS
2500
14379-022
–40
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–155
–70
–80
1000
1500
2000
2500
fOUT (MHz)
–175
400
W-CDMA NSD (dBm/Hz)
–155
600
800
1000
1200
1400
1600
1800
2000
fOUT (MHz)
Figure 76. Single-Tone NSD Measured at 70 MHz vs. fOUT over fDAC
1600
1800
2000
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–160
–165
–175
400
600
800
1000
1200
1400
1600
fOUT (MHz)
–150
fDAC
fDAC
fDAC
fDAC
W-CDMA NSD (dBm/Hz)
–155
–165
1800
2000
fDAC
fDAC
fDAC
fDAC
–160
–165
–170
–170
–175
600
800
1000
1200
1400
fOUT (MHz)
1600
1800
2000
14379-224
SINGLE-TONE NSD (dBm/Hz)
1400
Figure 79. W-CDMA NSD Measured at 10% Offset from fOUT vs. fOUT over fDAC
–160
–175
400
1200
–170
–170
14379-024
SINGLE-TONE NSD (dBm/Hz)
–150
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–165
–155
1000
Figure 78. W-CDMA NSD Measured at 70 MHz vs. fOUT over fDAC
–160
–150
800
fOUT (MHz)
Figure 75. SFDR vs. fOUT over Temperature
–175
400
600
14379-025
500
14379-023
–100
0
–155
–165
–170
–90
–150
–160
14379-225
SFDR (dBc)
–60
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
Figure 77. Single-Tone NSD Measured at 10% Offset from fOUT vs. fOUT over fDAC
Rev. 0 | Page 30 of 139
fOUT (MHz)
Figure 80. IMD vs. fOUT over Temperature
14379-680
–50
–150
TEMPERATURE = –40°C
TEMPERATURE = +25°C
TEMPERATURE = +85°C
W-CDMA NSD (dBm/Hz)
–40
Data Sheet
AD9161/AD9162
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–150
–150
–155
W-CDMA NSD (dBm/Hz)
–160
–165
–170
–160
–165
600
800
1000
1200
1400
1600
1800
2000
fOUT (MHz)
–175
400
Figure 81. Single-Tone NSD Measured at 70 MHz vs. fOUT over Temperature
1000
1200
1400
1600
1800
2000
Figure 84. W-CDMA NSD Measured at 70 MHz vs. fOUT over Temperature
–150
TEMPERATURE = –40°C
TEMPERATURE = +25°C
TEMPERATURE = +90°C
TEMPERATURE = –40°C
TEMPERATURE = +25°C
TEMPERATURE = +90°C
–155
W-CDMA NSD (dBm/Hz)
–155
–160
–165
–170
–160
–165
–170
600
800
1000
1200
1400
1600
1800
2000
fOUT (MHz)
–175
400
14379-227
SINGLE-TONE NSD (dBm/Hz)
800
fOUT (MHz)
–150
–175
400
600
14379-028
–170
800
1000
1200
1400
1600
1800
2000
fOUT (MHz)
Figure 85. W-CDMA NSD Measured at 10% Offset from fOUT vs. fOUT over
Temperature
14379-029
14379-032
Figure 82. Single-Tone NSD Measured at 10% Offset from fOUT vs. fOUT over
Temperature
600
14379-331
–175
400
TEMPERATURE = –40°C
TEMPERATURE = +25°C
TEMPERATURE = +90°C
–155
14379-027
SINGLE-TONE NSD (dBm/Hz)
TEMPERATURE = –40°C
TEMPERATURE = +25°C
TEMPERATURE = +90°C
Figure 86. Two-Carrier W-CDMA at 875 MHz
Figure 83. Single-Carrier W-CDMA at 877.5 MHz
Rev. 0 | Page 31 of 139
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–60
–65
–70
–70
ACLR (dBc)
–65
–75
–80
–85
–85
1000
1200
1400
1600
1800
2000
2200
fOUT (MHz)
Figure 87. Single-Carrier, W-CDMA ACLR vs. fOUT (First ACLR, Second ACLR)
–65
–90
800
–60
–65
1600
1800
2000
2200
THIRD ACLR
FOURTH ACLR
FIFTH ACLR
ACLR (dBc)
–70
–75
–80
–80
–85
–85
1000
1200
1400
1600
1800
2000
2200
fOUT (MHz)
Figure 88. Single-Carrier, W-CDMA ACLR vs. fOUT (Third ACLR, Fourth ACLR,
Fifth ACLR)
–60
1000
1200
1400
1600
1800
SSB PHASE NOISE (dBc/Hz)
–120
–140
70MHz
900MHz
1800MHz
3900MHz
CLOCK SOURCE
–100
–120
–140
10
100
1k
10k
100k
1M
10M
100M
OFFSET OVER fOUT (Hz)
–180
Figure 89. SSB Phase Noise vs. Offset over fOUT, fDAC = 4000 MSPS
(Two Different DAC Clock Sources Used for Best Composite Curve)
10
100
1k
10k
100k
1M
10M
100M
OFFSET OVER fOUT (Hz)
Figure 92. SSB Phase Noise vs. Offset over fOUT, fDAC = 6000 MSPS
Rev. 0 | Page 32 of 139
14379-036
–160
14379-035
–160
2200
Figure 91. Two-Carrier, W-CDMA ACLR vs. fOUT (Third ACLR, Fourth ACLR,
Fifth ACLR)
–80
–100
2000
fOUT (MHz)
–60
70MHz
900MHz
1800MHz
3900MHz
CLOCK SOURCE
–80
–90
800
14379-031
ACLR (dBc)
1400
Figure 90. Two-Carrier, W-CDMA ACLR vs. fOUT (First ACLR, Second ACLR)
THIRD ACLR
FOURTH ACLR
FIFTH ACLR
–75
–180
1200
fOUT (MHz)
–70
–90
800
1000
14379-034
–60
SSB HASE NOISE (dBc/Hz)
–75
–80
–90
800
FIRST ACLR
SECOND ACLR
14379-033
FIRST ACLR
SECOND ACLR
14379-030
ACLR (dBc)
–60
Data Sheet
AD9161/AD9162
AC (Mix-Mode)
0
0
–20
–20
MAGNITUDE (dBm)
–40
–60
–40
–60
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-038
0
0
0
0
–20
–20
MAGNITUDE (dBm)
4000
5000
–40
–60
–40
–60
–80
1000
2000
3000
4000
5000
FREQUENCY (MHz)
14379-039
0
Figure 94. Single-Tone Spectrum at fOUT = 2350 MHz (FIR85 Enabled)
0
3000
4000
5000
Figure 97. Single-Tone Spectrum at fOUT = 4000 MHz (FIR85 Enabled)
–155
–155
W-CDMA NSD (dBm/Hz)
–150
–165
2000
FREQUENCY (MHz)
–150
–160
1000
14379-042
MAGNITUDE (dBm)
3000
Figure 96. Single-Tone Spectrum at fOUT = 4000 MHz
–80
–160
–165
–170
–170
3000
4000
5000
6000
fOUT (MHz)
7000
14379-040
SINGLE-TONE NSD (dBm/Hz)
2000
FREQUENCY (MHz)
Figure 93. Single-Tone Spectrum at fOUT = 2350 MHz
–175
1000
14379-041
–80
–80
Figure 95. Single-Tone NSD vs. fOUT
–175
3000
4000
5000
6000
fOUT (MHz)
Figure 98. W-CDMA NSD vs. fOUT
Rev. 0 | Page 33 of 139
7000
14379-599
MAGNITUDE (dBm)
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
–40
–50
–50
–60
–60
SFDR (dBc)
–70
–80
3000
4000
SHUFFLE FALSE
SHUFFLE TRUE
5000
6000
7000
8000
fOUT (MHz)
–100
2000
–50
–40
–50
IMD (dBc)
–70
–80
–90
–90
3000
4000
5000
7000
6000
8000
fOUT (MHz)
–100
2000
–40
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
–50
3000
4000
5000
6000
7000
8000
9000
fDAC = 2500MHz
fDAC = 3000MHz
fDAC = 5000MHz
fDAC = 6000MHz
IMD (dBc)
–60
–70
–70
–80
–80
–90
–90
2000
3000
4000
5000
6000
7000
fOUT (MHz)
8000
9000
14379-046
SFDR (dBc)
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
Figure 103. IMD vs. fOUT over DAC IOUTFS
–60
–100
1000
8000
fOUT (MHz)
Figure 100. IMD vs. fOUT over Digital Scale
–50
7000
–70
–80
–40
6000
–60
14379-045
IMD (dBc)
–60
–100
2000
5000
Figure 102. SFDR vs. fOUT over DAC IOUTFS
SHUFFLE FALSE
SHUFFLE TRUE
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
4000
fOUT (MHz)
Figure 99. SFDR vs. fOUT over Digital Scale
–40
3000
14379-047
–90
DIGITAL SCALE = 0dB
DIGITAL SCALE = –6dB
DIGITAL SCALE = –12dB
DIGITAL SCALE = –18dB
14379-048
–100
2000
–70
–80
14379-044
–90
IOUTFS = 20mA
IOUTFS = 30mA
IOUTFS = 40mA
14379-049
SFDR (dBc)
–40
–100
1000
Figure 101. SFDR vs. fOUT over fDAC
2000
3000
4000
5000
6000
7000
fOUT (MHz)
Figure 104. IMD vs. fOUT over fDAC
Rev. 0 | Page 34 of 139
8000
Data Sheet
AD9161/AD9162
14379-053
14379-051
IOUTFS = 40 mA, fDAC = 5.0 GSPS, nominal supplies, TA = 25°C, unless otherwise noted.
Figure 105. Single-Carrier W-CDMA at 1887.5 MHz
–60
FIRST ACLR
SECOND ACLR
–65
–70
–70
–75
–80
–85
–85
2800
3000
3200
3400
3600
3800
fOUT (MHz)
Figure 106. Single-Carrier, W-CDMA ACLR vs. fOUT (First ACLR, Second ACLR)
–90
2600
3000
3200
3400
3600
3800
Figure 109. Four-Carrier, W-CDMA ACLR vs. fOUT (First ACLR, Second ACLR)
–60
THIRD ACLR
FOURTH ACLR
FIFTH ACL
THIRD ACLR
FOURTH ACLR
FIFTH ACL
–65
–65
–70
ACLR (dBc)
–70
–75
–75
–80
–80
3000
3200
fOUT (MHz)
3400
3600
3800
14379-055
2800
Figure 107. Single-Carrier, W-CDMA ACLR vs. fOUT (Third ACLR, Fourth ACLR,
Fifth ACLR)
–90
2600
2800
3000
3200
fOUT (MHz)
3400
3600
3800
14379-057
–85
–85
–90
2600
2800
fOUT (MHz)
–60
ACLR (dBc)
–75
–80
–90
2600
FIRST ACLR
SECOND ACLR
14379-056
ACLR (dBc)
–65
14379-054
ACLR (dBc)
–60
Figure 108. Four-Carrier W-CDMA at 1980 MHz
Figure 110. Four-Carrier, W-CDMA ACLR vs. fOUT (Third ACLR, Fourth ACLR,
Fifth ACLR)
Rev. 0 | Page 35 of 139
AD9161/AD9162
Data Sheet
0
–10
–10
–20
–20
–30
–40
–50
–60
–30
–40
–50
–60
–70
–70
–80
–80
–90
500
1000
1500
2000
2500
3000
FREQUENCY (MHz)
–90
–10
–20
–20
–30
–30
MAGNITUDE (dBc)
–10
–40
–50
–60
–80
–90
2500
2500
3000
–60
–80
2000
2000
–50
–70
1500
1500
–40
–70
3000
FREQUENCY (MHz)
–90
14379-059
MAGNITUDE (dBc)
0
1000
1000
Figure 114. Single Carrier at 70 MHz Output (Shuffle On)
0
500
500
FREQUENCY (MHz)
Figure 111. Single Carrier at 70 MHz Output
0
0
0
500
1000
1500
2000
2500
3000
FREQUENCY (MHz)
14379-362
0
14379-361
MAGNITUDE (dBc)
0
14379-058
MAGNITUDE (dBc)
DOCSIS Performance (NRZ Mode)
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
Figure 115. Four Carriers at 70 MHz Output (Shuffle On)
Figure 112. Four Carriers at 70 MHz Output
0
0
–10
–10
–20
MAGNITUDE (dBc)
–40
–50
–60
–30
–40
–50
–60
–70
–70
–80
0
500
1000
1500
2000
2500
FREQUENCY (MHz)
3000
Figure 113. Eight Carriers at 70 MHz Output
–90
0
500
1000
1500
2000
2500
3000
FREQUENCY (MHz)
Figure 116. Eight Carriers at 70 MHz Output (Shuffle On)
Rev. 0 | Page 36 of 139
14379-363
–80
–90
14379-060
MAGNITUDE (dBc)
–20
–30
Data Sheet
AD9161/AD9162
0
–10
–10
–20
–20
–30
–40
–50
–60
–30
–40
–50
–60
–70
–70
–80
–80
500
1000
1500
2000
2500
3000
FREQUENCY (MHz)
–90
–10
–20
–20
MAGNITUDE (dBc)
0
–30
–40
–50
–60
2500
3000
FREQUENCY (MHz)
–90
0
–10
–20
–20
MAGNITUDE (dBc)
–10
–30
–40
–50
–60
2500
FREQUENCY (MHz)
3000
3000
–60
–80
2000
2500
–50
–80
1500
2000
–40
–70
1000
1500
–30
–70
14379-062
MAGNITUDE (dBc)
0
500
1000
Figure 121. Eight Carriers at 950 MHz Output
0
0
500
FREQUENCY (MHz)
Figure 118. Single Carrier at 950 MHz Output (Shuffle On)
–90
3000
–60
–80
2000
2500
–50
–80
1500
2000
–40
–70
1000
1500
–30
–70
14379-364
MAGNITUDE (dBc)
0
500
1000
Figure 120. Four Carriers at 950 MHz Output (Shuffle On)
–10
0
500
FREQUENCY (MHz)
Figure 117. Single Carrier at 950 MHz Output
–90
0
14379-063
0
Figure 119. Four Carriers at 950 MHz Output
–90
0
500
1000
1500
2000
2500
3000
FREQUENCY (MHz)
Figure 122. Eight Carriers at 950 MHz Output (Shuffle On)
Rev. 0 | Page 37 of 139
14379-366
–90
14379-365
MAGNITUDE (dBc)
0
14379-061
MAGNITUDE (dBc)
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–40
–60
–70
–80
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
Figure 123. In-Band Second Harmonic vs. fOUT Performance for One DOCSIS
Carrier
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
Figure 126. In-Band Third Harmonic vs. fOUT Performance for One DOCSIS
Carrier
–80
0
200
400
600
800
1000
1200
1400
Figure 124. In-Band Second Harmonic vs. fOUT Performance for Four DOCSIS
Carriers
–50
–60
–70
–80
–90
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
14379-068
IN-BAND THIRD HARMONIC (dBc)
–70
14379-065
IN-BAND SECOND HARMONIC (dBc)
–60
fOUT (MHz)
Figure 127. In-Band Third Harmonic vs. fOUT Performance for Four DOCSIS
Carriers
–40
IN-BAND THIRD HARMONIC (dBc)
–40
–50
–60
–70
–80
0
200
400
600
800
fOUT (MHz)
1000
1200
1400
Figure 125. In-Band Second Harmonic vs. fOUT Performance for Eight DOCSIS
Carriers
–50
–60
–70
–80
–90
14379-066
IN-BAND SECOND HARMONIC (dBc)
–80
–40
–50
–90
–70
–90
–40
–90
–60
0
200
400
600
800
fOUT (MHz)
1000
1200
1400
14379-069
–90
–50
14379-067
IN-BAND THIRD HARMONIC (dBc)
–50
14379-064
IN-BAND SECOND HARMONIC (dBc)
–40
Figure 128. In-Band Third Harmonic vs. fOUT Performance for Eight DOCSIS
Carriers
Rev. 0 | Page 38 of 139
Data Sheet
AD9161/AD9162
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–40
–60
–70
–60
–70
400
600
800
1000
1200
1400
fOUT (MHz)
–90
0
200
–70
–80
0
200
400
600
800
1000
1200
1400
fOUT (MHz)
1400
1200
1400
–60
–70
–90
0
–40
400
600
800
1000
Figure 133. 32-Carrier ACPR vs. fOUT
0
Y-AXIS: FIRST ACPR
Y-AXIS: SECOND ACPR
Y-AXIS: THIRD ACPR
Y-AXIS: FOURTH ACPR
Y-AXIS: FIFTH ACPR
–10
–20
MAGNITUDE (dBc)
–50
200
fOUT (MHz)
Figure 130. Four-Carrier ACPR vs. fOUT
–60
–70
–30
–40
–50
–60
–70
–80
–90
0
200
400
600
800
1000
1200
fOUT (MHz)
1400
–90
0
500
1000
1500
2000
2500
FREQUENCY (MHz)
Figure 131. Eight-Carrier ACPR vs. fOUT
Figure 134. 194-Carrier, Sinc Enabled, FIR85 Enabled
Rev. 0 | Page 39 of 139
3000
14379-075
–80
14379-072
ACPR (dBc)
1200
–80
14379-071
–90
1000
Y-AXIS: FIRST ACPR
Y-AXIS: SECOND ACPR
Y-AXIS: THIRD ACPR
Y-AXIS: FOURTH ACPR
Y-AXIS: FIFTH ACPR
–50
ACPR (dBc)
ACPR (dBc)
–40
–60
800
Figure 132. 16-Carrier ACPR vs. fOUT
Y-AXIS: FIRST ACPR
Y-AXIS: SECOND ACPR
Y-AXIS: THIRD ACPR
Y-AXIS: FOURTH ACPR
Y-AXIS: FIFTH ACPR
–50
600
fOUT (MHz)
Figure 129. Single-Carrier Adjacent Channel Power Ratio (ACPR) vs. fOUT
–40
400
14379-073
200
14379-070
0
14379-074
–80
–80
–90
Y-AXIS: FIRST ACPR
Y-AXIS: SECOND ACPR
Y-AXIS: THIRD ACPR
Y-AXIS: FOURTH ACPR
Y-AXIS: FIFTH ACPR
–50
ACPR (dBc)
–50
ACPR (dBc)
–40
Y-AXIS: FIRST ACPR
Y-AXIS: SECOND ACPR
Y-AXIS: THIRD ACPR
Y-AXIS: FOURTH ACPR
Y-AXIS: FIFTH ACPR
AD9161/AD9162
Data Sheet
IOUTFS = 40 mA, fDAC = 3.076 GSPS, nominal supplies, FIR85 enabled, TA = 25°C, unless otherwise noted.
–40
–25
–35
–50
ACLR IN GAP CHANNEL (dBc)
–55
–65
–75
–85
–95
–105
–60
–70
–80
–90
–125
CENTER 77MHz
RES BW 10kHz
VBW 1.kHz
SPAN 60.0MHz
SWEEP 6.041s (1001pts)
–100
Figure 135. Gap Channel ACLR at 77 MHz
0
200
400
600
800
1000
1200
fGAP (fOUT = fGAP) (MHz)
Figure 136. ACLR in Gap Channel vs. fGAP
Rev. 0 | Page 40 of 139
1400
14379-077
–115
14379-076
MAGNITUDE (dBm)
–45
Data Sheet
AD9161/AD9162
TERMINOLOGY
Integral Nonlinearity (INL)
INL is the maximum deviation of the actual analog output from
the ideal output, determined by a straight line drawn from zero
scale to full scale.
Differential Nonlinearity (DNL)
DNL is the measure of the variation in analog value, normalized
to full scale, associated with a 1 LSB change in digital input code.
Offset Error
Offset error is the deviation of the output current from the ideal
of 0 mA. For OUTPUT+, 0 mA output is expected when all
inputs are set to 0. For OUTPUT−, 0 mA output is expected
when all inputs are set to 1.
Gain Error
Gain error is the difference between the actual and ideal output
span. The actual span is determined by the difference between
the output when the input is at its minimum code and the
output when the input is at its maximum code.
Temperature Drift
Temperature drift is specified as the maximum change from the
ambient (25°C) value to the value at either TMIN or TMAX. For offset
and gain drift, the drift is reported in ppm of full-scale range
(FSR) per degree Celsius. For reference drift, the drift is reported
in ppm per degree Celsius.
Settling Time
Settling time is the time required for the output to reach and
remain within a specified error band around its final value,
measured from the start of the output transition.
Spurious-Free Dynamic Range (SFDR)
SFDR is the difference, in decibels, between the peak amplitude
of the output signal and the peak spurious signal within the dc
to Nyquist frequency of the DAC. Typically, energy in this band
is rejected by the interpolation filters. This specification,
therefore, defines how well the interpolation filters work and
the effect of other parasitic coupling paths on the DAC output.
Signal-to-Noise Ratio (SNR)
SNR is the ratio of the rms value of the measured output signal
to the rms sum of all other spectral components below the Nyquist
frequency, excluding the first six harmonics and dc. The value
for SNR is expressed in decibels.
Interpolation Filter
If the digital inputs to the DAC are sampled at a multiple rate of
the interpolation rate (fDATA), a digital filter can be constructed
that has a sharp transition band near fDATA/2. Images that
typically appear around the output data rate (fDAC) can be greatly
suppressed.
Adjacent Channel Leakage Ratio (ACLR)
ACLR is the ratio in decibels relative to the carrier (dBc)
between the measured power within a channel relative to its
adjacent channel.
Adjusted DAC Update Rate
The adjusted DAC update rate is the DAC update rate divided
by the smallest interpolating factor. For clarity on DACs with
multiple interpolating factors, the adjusted DAC update rate for
each interpolating factor may be given.
Physical Lane
Physical Lane x refers to SERDINx±.
Logical Lane
Logical Lane x refers to physical lanes after optionally being
remapped by the crossbar block (Register 0x308 to Register 0x30B).
Link Lane
Link Lane x refers to logical lanes considered in the link.
Rev. 0 | Page 41 of 139
AD9161/AD9162
Data Sheet
THEORY OF OPERATION
The AD9161/AD9162 are 11-bit and 16-bit single RF DACs with a
SERDES interface. Figure 1 shows a detailed functional block
diagram of the AD9161/AD9162. Eight high speed serial lanes
carry data at a maximum speed of 12.5 Gbps, and either a 5 GSPS
real input or a 2.5 GSPS complex input data rate to the DAC.
Compared to either LVDS or CMOS interfaces, the SERDES
interface simplifies pin count, board layout, and input clock
requirements to the device.
The clock for the input data is derived from the DAC clock, or
device clock (required by the JESD204B specification). This
device clock is sourced with a high fidelity direct external DAC
sampling clock. The performance of the DAC can be optimized by
using on-chip adjustments to the clock input accessible through the
SPI port. The device can be configured to operate in one-lane, twolane, three-lane, four-lane, six-lane, or eight-lane modes,
depending on the required input data rate.
The digital datapath of the AD9161/AD9162 offers a bypass
(1×) mode (AD9162 only) and several interpolation modes (2×,
3×, 4×, 6×, 8×, 12×, 16×, and 24×) through either an initial halfband (2×) or third-band (3×) filter with programmable 80% or
90% bandwidth, and three subsequent half-band filters (all
90%) with a maximum DAC sample rate of 6 GSPS. An inverse
sinc filter is provided to compensate for sinc related roll-off. An
additional half-band filter, FIR85, takes advantage of the quadswitch architecture to interpolate on the falling edge of the
clock, and effectively double the DAC update rate in 2× NRZ
mode. A 48-bit programmable modulus NCO is provided to
enable digital frequency shifts of signals with near infinite
precision. The NCO can be operated alone in NCO only mode
(AD9162 only) or with digital data from the SERDES interface
and digital datapath. The 100 MHz speed of the SPI write
interface enables rapid updating of the frequency tuning word
of the NCO.
to 38.76 mA, typically. The differential current outputs are
complementary. The DAC uses the patented quad-switch architecture, which enables DAC decoder options to extend the output
frequency range into the second and third Nyquist zones with
Mix-Mode, return to zero (RZ) mode, and 2× NRZ mode (with
FIR85 enabled). Operating as a real mode DAC in 1× bypass
(AD9162 only) and NRZ mode, the output signal can range from
0 Hz to 2.5 GHz. Mix-Mode can be used to access 1.5 GHz to
around 7.5 GHz. In the interpolation modes, the output can
range from 0 Hz to 6 GHz in 2× NRZ mode using the NCO to
shift a signal of up to 1.8 GHz instantaneous bandwidth to the
desired fOUT.
The AD9161/AD9162 are capable of multichip synchronization
that can both synchronize multiple DACs and establish a
constant and deterministic latency (latency locking) path for the
DACs. The latency for each of the DACs remains constant to
within several DAC clock cycles from link establishment to link
establishment. An external alignment (SYSREF±) signal makes
the AD9161/AD9162 Subclass 1 compliant. Several modes of
SYSREF± signal handling are available for use in the system.
An SPI configures the various functional blocks and monitors
their statuses. The various functional blocks and the data
interface must be set up in a specific sequence for proper operation
(see the Start-Up Sequence section). Simple SPI initialization
routines set up the JESD204B link and are included in the
evaluation board package. This data sheet describes the various
blocks of the AD9161/AD9162 in greater detail. Descriptions of
the JESD204B interface, control parameters, and various registers
to set up and monitor the device are provided. The recommended
start-up routine reliably sets up the data link.
The AD9161/AD9162 DAC core provides a fully differential
current output with a nominal full-scale current of 38.76 mA.
The full-scale output current, IOUTFS, is user adjustable from 8 mA
Rev. 0 | Page 42 of 139
Data Sheet
AD9161/AD9162
SERIAL PORT OPERATION
The serial port is a flexible, synchronous serial communications
port that allows easy interfacing with many industry-standard
microcontrollers and microprocessors. The serial input/output
(I/O) is compatible with most synchronous transfer formats,
including both the Motorola SPI and Intel® SSR protocols. The
interface allows read/write access to all registers that configure
the AD9161/AD9162. MSB first or LSB first transfer formats are
supported. The serial port interface can be configured as a
4-wire interface or a 3-wire interface in which the input and
output share a single-pin I/O (SDIO).
CS F12
The serial clock pin synchronizes data to and from the device
and runs the internal state machines. The maximum frequency
of SCLK is 100 MHz. All data input is registered on the rising
edge of SCLK. All data is driven out on the falling edge of SCLK.
SPI
PORT
14379-078
SCLK H10
Figure 137. Serial Port Interface Pins (11 mm × 11 mm CSP_BGA)
There are two phases to a communication cycle with the AD9161/
AD9162. Phase 1 is the instruction cycle (the writing of an
instruction byte into the device), coincident with the first 16
SCLK rising edges. The instruction word provides the serial
port controller with information regarding the data transfer
cycle, Phase 2 of the communication cycle. The Phase 1
instruction word defines whether the upcoming data transfer is a
read or write, along with the starting register address for the
following data transfer.
A logic high on the CS pin followed by a logic low resets the
serial port timing to the initial state of the instruction cycle.
From this state, the next 16 rising SCLK edges represent the
instruction bits of the current I/O operation.
The remaining SCLK edges are for Phase 2 of the communication
cycle. Phase 2 is the actual data transfer between the device and
the system controller. Phase 2 of the communication cycle is a
transfer of one or more data bytes. Eight × N SCLK cycles are
needed to transfer N bytes during the transfer cycle. Registers
change immediately upon writing to the last bit of each transfer
byte, except for the frequency tuning word (FTW) and numerically
controlled oscillator (NCO) phase offsets, which change only when
the frequency tuning word FTW_LOAD_REQ bit is set.
DATA FORMAT
The instruction byte contains the information shown in Table 15.
Table 15. Serial Port Instruction Word
I15 (MSB)
R/W
SERIAL PORT PIN DESCRIPTIONS
Serial Clock (SCLK)
SDO G11
SDIO G10
A14 to A0, Bit I14 to Bit I0 of the instruction word, determine
the register that is accessed during the data transfer portion of
the communication cycle. For multibyte transfers, A[14:0] is the
starting address. The remaining register addresses are generated
by the device based on the address increment bit. If the address
increment bits are set high (Register 0x000, Bit 5 and Bit 2),
multibyte SPI writes start on A[14:0] and increment by 1 every
eight bits sent/received. If the address increment bits are set to
0, the address decrements by 1 every eight bits.
I[14:0]
A[14:0]
R/W, Bit 15 of the instruction word, determines whether a read
or a write data transfer occurs after the instruction word write.
Logic 1 indicates a read operation, and Logic 0 indicates a write
operation.
Chip Select (CS)
An active low input starts and gates a communication cycle.
CS allows more than one device to be used on the same serial
communications lines. The SDIO pin goes to a high impedance
state when this input is high. During the communication cycle,
the chip select must stay low.
Serial Data I/O (SDIO)
This pin is a bidirectional data line. In 4-wire mode, this pin
acts as the data input and SDO acts as the data output.
SERIAL PORT OPTIONS
The serial port can support both MSB first and LSB first data
formats. This functionality is controlled by the LSB first bit
(Register 0x000, Bit 6 and Bit 1). The default is MSB first (LSB
bit = 0).
When the LSB first bits = 0 (MSB first), the instruction and data
bits must be written from MSB to LSB. R/W is followed by
A[14:0] as the instruction word, and D[7:0] is the data-word.
When the LSB first bits = 1 (LSB first), the opposite is true.
A[0:14] is followed by R/W, which is subsequently followed by
D[0:7].
The serial port supports a 3-wire or 4-wire interface. When the
SDO active bits = 1 (Register 0x000, Bit 4 and Bit 3), a 4-wire
interface with a separate input pin (SDIO) and output pin (SDO) is
used. When the SDO active bits = 0, the SDO pin is unused and
the SDIO pin is used for both the input and the output.
Multibyte data transfers can be performed as well by holding
the CS pin low for multiple data transfer cycles (eight SCLKs)
after the first data transfer word following the instruction cycle.
The first eight SCLKs following the instruction cycle read from
or write to the register provided in the instruction cycle. For
each additional eight SCLK cycles, the address is either incremented or decremented and the read/write occurs on the new
register. The direction of the address can be set using ADDRINC or
ADDRINC_M (Register 0x000, Bit 5 and Bit 2). When ADDRINC
Rev. 0 | Page 43 of 139
AD9161/AD9162
Data Sheet
To prevent confusion and to ensure consistency between devices,
the chip tests the first nibble following the address phase, ignoring
the second nibble. This test is completed independently from the
LSB first bits and ensures that there are extra clock cycles following
the soft reset bits (Register 0x000, Bit 0 and Bit 7). This test of
the first nibble only applies when writing to Register 0x000.
SCLK
SDIO
A0
A1 A2
A12 A13 A14 R/W D0 0 D10 D20
D4N D5N D6N D7N
Figure 139. Serial Register Interface Timing, LSB First, Register 0x000, Bit 5
and Bit 2 = 1
CS
SCLK
DATA TRANSFER CYCLE
tDV
CS
SDIO
R/W A14 A13
A3
A2 A1
A0 D7N D6N D5N
D30 D20 D10 D00
14379-079
SCLK
SDIO
DATA TRANSFER CYCLE
DATA BIT n
DATA BIT n – 1
Figure 140. Timing Diagram for Serial Port Register Read
Figure 138. Serial Register Interface Timing, MSB First, Register 0x000, Bit 5
and Bit 2 = 0
tS
tH
CS
tPWH
tPWL
tDS
SDIO
tDH
INSTRUCTION BIT 15
INSTRUCTION BIT 14
INSTRUCTION BIT 0
Figure 141. Timing Diagram for Serial Port Register Write
Rev. 0 | Page 44 of 139
14379-082
SCLK
14379-081
INSTRUCTION CYCLE
INSTRUCTION CYCLE
CS
14379-080
or ADDRINC_M is 1, the multicycle addresses are incremented.
When ADDRINC or ADDRINC_M is 0, the addresses are decremented. A new write cycle can always be initiated by bringing
CS high and then low again.
Data Sheet
AD9161/AD9162
JESD204B SERIAL DATA INTERFACE
The various combinations of JESD204B parameters that are
supported depend solely on the number of lanes. Thus, a
unique set of parameters can be determined by selecting the
lane count to be used. In addition, the interpolation rate and
number of lanes can be used to define the rest of the configuration needed to set up the AD9161/AD9162. The interpolation
rate and the number of lanes are selected in Register 0x110.
JESD204B OVERVIEW
The AD9161/AD9162 have eight JESD204B data ports that
receive data. The eight JESD204B ports can be configured as
part of a single JESD204B link that uses a single system reference
(SYSREF±) and device clock (CLK±).
The JESD204B serial interface hardware consists of three layers:
the physical layer, the data link layer, and the transport layer.
These sections of the hardware are described in subsequent
sections, including information for configuring every aspect of
the interface. Figure 142 shows the communication layers
implemented in the AD9161/AD9162 serial data interface to
recover the clock and deserialize, descramble, and deframe the
data before it is sent to the digital signal processing section of
the device.
The AD9161/AD9162 have a single DAC output; however, for
the purposes of the complex signal processing on chip, the converter count is defined as M = 2 whenever interpolation is used.
For a particular application, the number of converters to use
(M) and the DataRate variable are known. The LaneRate
variable and number of lanes (L) can be traded off as follows:
DataRate = (DACRate)/(InterpolationFactor)
LaneRate = (20 × DataRate × M)/L
The physical layer establishes a reliable channel between the
transmitter (Tx) and the receiver (Rx), the data link layer is
responsible for unpacking the data into octets and descrambling
the data. The transport layer receives the descrambled
JESD204B frames and converts them to DAC samples.
where LaneRate must be between 750 Mbps and 12.5 Gbps.
Achieving and recovering synchronization of the lanes is very
important. To simplify the interface to the transmitter, the
AD9161/AD9162 designate a master synchronization signal for
each JESD204B link. The SYNCOUT± pin is used as the master
signal for all lanes. If any lane in a link loses synchronization, a
resynchronization request is sent to the transmitter via the
synchronization signal of the link. The transmitter stops sending
data and instead sends synchronization characters to all lanes in
that link until resynchronization is achieved.
A number of JESD204B parameters (L, F, K, M, N, NP, S, HD)
define how the data is packed and tell the device how to turn
the serial data into samples. These parameters are defined in
detail in the Transport Layer section. The AD9161/AD9162 also
have a descrambling option (see the Descrambler section for
more information).
SYNCOUT±
PHYSICAL
LAYER
SERDIN7±
DATA LINK
LAYER
TRANSPORT
LAYER
QBD/
DESCRAMBLER
FRAME TO
SAMPLES
I DATA[15:0]
DESERIALIZER
TO DAC
DSP BLOCK
Q DATA[15:0]
DESERIALIZER
14379-083
SERDIN0±
SYSREF±
Figure 142. Functional Block Diagram of Serial Link Receiver
Table 16. Single-Link JESD204B Operating Modes
Parameter
L (Lane Count)
M (Converter Count)
F (Octets per Frame per Lane)
S (Samples per Converter per Frame)
1
1
2
4
1
2
2
2
2
1
Rev. 0 | Page 45 of 139
3
3
2
4
3
4
4
2
1
1
Number of Lanes (L)
6
8
6
8
2
1 (real), 2 (complex)
2
1
3
4 (real), 2 (complex)
AD9161/AD9162
Data Sheet
Table 17. Data Structure per Lane for JESD204B Operating Modes 1
JESD204B Parameters
L = 8, M = 1, F = 1, S = 4
L = 8, M = 2, F = 1, S = 2
L = 6, M = 2, F = 2, S = 3
L = 4, M = 2, F = 1, S = 1
L = 3, M = 2, F = 4, S = 3
L = 2, M = 2, F = 2, S = 1
L = 1, M = 2, F = 4, S = 1
1
Lane No.
Lane 0
Lane 1
Lane 2
Lane 3
Lane 4
Lane 5
Lane 6
Lane 7
Lane 0
Lane 1
Lane 2
Lane 3
Lane 4
Lane 5
Lane 6
Lane 7
Lane 0
Lane 1
Lane 2
Lane 3
Lane 4
Lane 5
Lane 0
Lane 1
Lane 2
Lane 3
Lane 0
Lane 1
Lane 2
Lane 0
Lane 1
Lane 0
Frame 0
M0S0[15:8]
M0S0[7:0]
M0S1[15:8]
M0S1[7:0]
M0S2[15:8]
M0S2[7:0]
M0S3[15:8]
M0S3[7:0]
M0S0[15:8]
M0S0[7:0]
M0S1[15:8]
M0S1[7:0]
M1S0[15:8]
M1S0[7:0]
M1S1[15:8]
M1S1[7:0]
M0S0[15:8]
M0S1[15:8]
M0S2[15:8]
M1S0[15:8]
M1S1[15:8]
M1S2[15:8]
M0S0[15:8]
M0S0[7:0]
M1S0[15:8]
M1S0[7:0]
M0S0[15:8]
M0S2[15:8]
M1S1[15:8]
M0S0[15:8]
M1S0[15:8]
M0S0[15:8]
Frame 1
Frame 2
Frame 3
M0S1[15:8]
M1S0[15:8]
M1S2[15:8]
M0S1[7:0]
M1S0[7:0]
M1S2[7:0]
M1S0[15:8]
M1S0[7:0]
M0S0[7:0]
M0S1[7:0]
M0S2[7:0]
M1S0[7:0]
M1S1[7:0]
M1S2[7:0]
M0S0[7:0]
M0S2[7:0]
M1S1[7:0]
M0S0[7:0]
M1S0[7:0]
M0S0[7:0]
Mx is the converter number and Sy is the sample number. For example, M0S0 means Converter 0, Sample 0. Blank cells are not applicable.
PHYSICAL LAYER
The physical layer of the JESD204B interface, hereafter referred
to as the deserializer, has eight identical channels. Each channel
consists of the terminators, an equalizer, a clock and data recovery
(CDR) circuit, and the 1:40 demux function (see Figure 143).
DESERIALIZER
TERMINATION
EQUALIZER
CDR
SPI
CONTROL
FROM SERDES PLL
Figure 143. Deserializer Block Diagram
1:40
14379-084
SERDINx±
JESD204B data is input to the AD9161/AD9162 via the
SERDINx± 1.2 V differential input pins as per the JESD204B
specification.
Interface Power-Up and Input Termination
Before using the JESD204B interface, it must be powered up by
setting Register 0x200, Bit 0 = 0. In addition, each physical lane
(PHY) that is not being used (SERDINx±) must be powered
down. To do so, set the corresponding Bit x for Physical Lane x in
Register 0x201 to 0 if the physical lane is being used, and to 1 if it is
not being used.
The AD9161/AD9162 autocalibrate the input termination to
50 Ω. Before running the termination calibration, Register 0x2A7
and Register 0x2AE must be written as described in Table 18 to
guarantee proper calibration. The termination calibration begins
when Register 0x2A7, Bit 0 and Register 0x2AE, Bit 0 transition
from low to high. Register 0x2A7 controls autocalibration for
Rev. 0 | Page 46 of 139
Data Sheet
AD9161/AD9162
Clock Relationships
PHY 0, PHY 1, PHY 6, and PHY 7. Register 0x2AE controls
autocalibration for PHY 2, PHY 3, PHY 4, and PHY 5.
The PHY termination autocalibration routine is as shown in
Table 18.
The following clocks rates are used throughout the rest of the
JESD204B section. The relationship between any of the clocks
can be derived from the following equations:
DataRate = (DACRate)/(InterpolationFactor)
Table 18. PHY Termination Autocalibration Routine
Address
0x2A7
Value
0x01
0x2AE
0x01
LaneRate = (20 × DataRate × M)/L
Description
Autotune PHY 0, PHY 1, PHY 6, and
PHY 7 terminations
Autotune PHY 2, PHY 3, PHY 4, and
PHY 5 terminations
ByteRate = LaneRate/10
This relationship comes from 8-bit/10-bit encoding, where each
byte is represented by 10 bits.
The input termination voltage of the DAC is sourced externally
via the VTT_1P2 pins (M3 and M 13 on the 8 mm × 8 mm
BGA package, or K3 and K13 on the 11 mm × 11 mm BGA
package). Set VTT, the termination voltage, by connecting it to
VDD_1P2. It is recommended that the JESD204B inputs be accoupled to the JESD204B transmit device using 100 nF capacitors.
PCLK Rate = ByteRate/4
The processing clock is used for a quad-byte decoder.
FrameRate = ByteRate/F
where F is defined as octets per frame per lane.
PCLK Factor = FrameRate/PCLK Rate = 4/F
The calibration code of the termination can be read from
Bits[3:0] in Register 0x2AC (PHY 0, PHY 1, PHY 6, PHY 7)
and Register 0x2B3 (PHY 2, PHY 3, PHY 4, PHY 5). If needed,
the termination values can be adjusted or set using several
registers. The TERM_BLKx_CTRLREG1 registers (Register 0x2A8
and Register 0x2AF), can override the autocalibrated value. When
set to 0xXXX0XXXX, the termination block autocalibrates,
which is the normal, default setting. When set to 0xXXX1XXXX,
the autocalibration value is overwritten with the value in Bits[3:1]
of Register 0x2A8 and Register 0x2AF. Individual offsets from the
autocalibration value for each lane can be programmed in Bits[3:0]
of Register 0x2BB to Register 0x2C2. The value is a signed magnitude, with Bit 3 as the sign bit. The total range of the termination
resistor value is about 94 Ω to 120 Ω, with approximately 3.5%
increments across the range (for example, smaller steps at the
bottom of the range than at the top).
where:
M is the JESD204B parameter for converters per link.
L is the JESD204B parameter for lanes per link.
F is the JESD204B parameter for octets per frame per lane.
Receiver Eye Mask
The reference clock to the SERDES PLL is always running at a
frequency, fREF, that is equal to 1/40 of the lane rate (PCLK Rate).
This clock is divided by a DivFactor value (set by SERDES_PLL_
DIV_FACTOR) to deliver a clock to the phase frequency detector
(PFD) block that is between 35 MHz and 80 MHz. Table 19
includes the respective SERDES_PLL_DIV_FACTOR register
settings for each of the desired PLL_REF_CLK_RATE options
available.
The AD9161/AD9162 comply with the JESD204B specification
regarding the receiver eye mask and is capable of capturing data
that complies with this mask. Figure 144 shows the receiver eye
mask normalized to the data rate interval with a 600 mV VTT
swing. See the JESD204B specification for more information
regarding the eye mask and permitted receiver eye opening.
LV-OIF-11G-SR RECEIVER EYE MASK
The independent SERDES PLL uses integer N techniques to
achieve clock synthesis. The entire SERDES PLL is integrated
on chip, including the VCO and the loop filter. The SERDES
PLL VCO operates over the range of 6 GHz to 12.5 GHz.
In the SERDES PLL, a VCO divider block divides the VCO
clock by 2 to generate a 3 GHz to 6.25 GHz quadrature clock for
the deserializer cores. This clock is the input to the clock and
data recovery block that is described in the Clock and Data
Recovery section.
Table 19. SERDES PLL Divider Settings
525
AMPLITUDE (mV)
SERDES PLL
Functional Overview of the SERDES PLL
Lane Rate
(Gbps)
0.750 to 1.5625
1.5 to 3.125
3 to 6.25
6 to 12.5
55
0
–55
0
0.35
0.5
0.65
TIME (UI)
1.00
14379-085
–525
Figure 144. Receiver Eye Mask for 600 mV VTT Swing
Rev. 0 | Page 47 of 139
PLL_REF_CLK_RATE,
Register 0x084, Bits[5:4]
0b01 = 2×
0b00 = 1×
0b00 = 1×
0b00 = 1×
SERDES_PLL_DIV_FAC
TOR Register 0x289,
Bits[1:0]
0b10 = ÷1
0b10 = ÷1
0b01 = ÷2
0b00 = ÷4
AD9161/AD9162
Data Sheet
Register 0x280 controls the synthesizer enable and recalibration.
To enable the SERDES PLL, first set the PLL divider register (see
Table 19). Then enable the SERDES PLL by writing Register 0x280,
Bit 0 = 1. If a recalibration is needed, write Register 0x280, Bit 2 =
0b1 and then reset the bit to 0b0. The rising edge of the bit causes a
recalibration to begin.
Confirm that the SERDES PLL is working by reading
Register 0x281. If Register 0x281, Bit 0 = 1, the SERDES PLL
has locked. If Register 0x281, Bit 3 = 1, the SERDES PLL was
successfully calibrated. If Register 0x281, Bit 4 or Bit 5 is high, the
PLL reaches the lower or upper end of its calibration band and
must be recalibrated by writing 0 and then 1 to Register 0x280,
Bit 2.
After configuring the CDR circuit, reset it and then release the
reset by writing 1 and then 0 to Register 0x206, Bit 0.
Power-Down Unused PHYs
Note that any unused and enabled lanes consume extra power
unnecessarily. Each lane that is not being used (SERDINx±)
must be powered off by writing a 1 to the corresponding bit of
PHY_PD (Register 0x201).
Equalization
Clock and Data Recovery
The deserializer is equipped with a CDR circuit. Instead of
recovering the clock from the JESD204B serial lanes, the CDR
recovers the clocks from the SERDES PLL. The 3 GHz to
6.25 GHz output from the SERDES PLL, shown in Figure 145, is
the input to the CDR.
A CDR sampling mode must be selected to generate the lane
rate clock inside the device. If the desired lane rate is greater
than 6.25 GHz, half rate CDR operation must be used. If the
desired lane rate is less than 6.25 GHz, disable half rate operation.
If the lane rate is less than 3 GHz, disable full rate and enable 2×
oversampling to recover the appropriate lane rate clock. Table 20
gives a breakdown of CDR sampling settings that must be set
depending on the LaneRate value.
Table 20. CDR Operating Modes
To compensate for signal integrity distortions for each PHY
channel due to PCB trace length and impedance, the
AD9161/AD9162 employ an easy to use, low power equalizer
on each JESD204B channel. The AD9161/AD9162 equalizers
can compensate for insertion losses far greater than required by
the JESD204B specification. The equalizers have two modes of
operation that are determined by the EQ_POWER_MODE
register setting in Register 0x268, Bits[7:6]. In low power mode
(Register 0x268, Bits[7:6] = 2b’01) and operating at the maximum
lane rate of 12.5 GBPS, the equalizer can compensate for up to
11.5 dB of insertion loss. In normal mode (Register 0x268,
Bits[7:6] = 2b’00), the equalizer can compensate for up to 17.2 dB
of insertion loss. This performance is shown in Figure 146 as an
overlay to the JESD204B specification for insertion loss. Figure 146
shows the equalization performance at 12.5 Gbps, near the maximum baud rate for the AD9161/AD9162.
SPI_DIVISION_RATE,
Register 0x230,
Bits[2:1]
10b (divide by 4)
01b (divide by 2)
00b (no divide)
00b (no divide)
SPI_ENHALFRATE
Register 0x230, Bit 5
0 (full rate)
0 (full rate)
0 (full rate)
1 (half rate)
MODE
HALF RATE
FULL RATE, NO DIV
FULL RATE, DIV 2
FULL RATE, DIV 4
INTERPOLATION
JESD LANES
REG 0x110
DAC CLOCK
(5GHz)
÷4
PCLK
GENERATOR
CDR OVERSAMP
REG 0x289
PLL REF CLOCK
VALID RANGE
35MHz TO 80MHz
÷4, ÷2,
OR ÷1
DIVIDE (N)
20
40
80
160
ENABLE HALF RATE
DIVISION RATE
REG 0x230
SAMPLE CLOCK
I, Q TO CDR
VALID RANGE
3GHz TO 6.25GHz
CP
LF
PLL_REF_CLK_RATE
1×, 2×, 4×
REG 0x084
÷2
CDR
÷N
÷8
÷6 TO ÷127,
DEFAULT: 10
Figure 145. SERDES PLL Synthesizer Block Diagram Including VCO Divider Block
Rev. 0 | Page 48 of 139
JESD LANE CLOCK
(SAME RATE AS PCLK)
14379-086
LaneRate
(Gbps)
0.750 to 1.5625
1.5 to 3.125
3 to 6.25
6 to 12.5
The CDR circuit synchronizes the phase used to sample the data on
each serial lane independently. This independent phase adjustment
per serial interface ensures accurate data sampling and eases the
implementation of multiple serial interfaces on a PCB.
Data Sheet
AD9161/AD9162
JESD204B SPEC ALLOWED
CHANNEL LOSS
EXAMPLE OF
JESD204B
COMPLIANT
CHANNEL
4
INSERTION LOSS (dB)
10
EXAMPLE OF
AD9161/AD9162
COMPATIBLE
CHANNEL (LOW
POWER MODE)
AD9161/AD9162 ALLOWED
CHANNEL LOSS
(LOW POWER MODE)
12
AD9161/AD9162 ALLOWED
CHANNEL LOSS
(NORMAL MODE)
14
16
EXAMPLE OF
AD9161/AD9162
COMPATIBLE
CHANNEL
(NORMAL MODE)
18
20
22
6.25
14379-087
24
3.125
9.375
FREQUENCY (GHz)
Figure 146. Insertion Loss Allowed
0
–5
–15
–20
–25
STRIPLINE = 6"
STRIPLINE = 10"
STRIPLINE = 15"
STRIPLINE = 20"
STRIPLINE = 25"
STRIPLINE = 30"
–35
–40
0
1
2
3
4
5
6
7
8
9
FREQUENCY (GHz)
Figure 147. Insertion Loss of 50 Ω Striplines on FR4
10
14379-088
ATTENUATION (dB)
–10
–30
–15
–20
–25
6" MICROSTRIP
10" MICROSTRIP
15" MICROSTRIP
20" MICROSTRIP
25" MICROSTRIP
30" MICROSTRIP
–30
–35
–40
0
1
2
3
4
5
6
7
8
9
FREQUENCY (GHz)
10
Figure 148. Insertion Loss of 50 Ω Microstrips on FR4
The data link layer of the AD9161/AD9162 JESD204B interface
accepts the deserialized data from the PHYs and deframes, and
descrambles them so that data octets are presented to the transport
layer to be put into DAC samples. The architecture of the data
link layer is shown in Figure 149. The data link layer consists of
a synchronization FIFO for each lane, a crossbar switch, a
deframer, and a descrambler.
6
8
–10
DATA LINK LAYER
0
2
–5
14379-089
Low power mode is recommended if the insertion loss of the
JESD204B PCB channels is less than that of the most lossy
supported channel for low power mode (shown in Figure 146).
If the insertion loss is greater than that, but still less than that of
the most lossy supported channel for normal mode (shown in
Figure 146), use normal mode. At 12.5 Gbps operation, the
equalizer in normal mode consumes about 4 mW more power
per lane used than in low power equalizer mode. Note that either
mode can be used in conjunction with transmitter preemphasis
to ensure functionality and/or optimize for power.
0
ATTENUATION (dB)
Figure 147 and Figure 148 are provided as points of reference
for hardware designers and show the insertion loss for various
lengths of well laid out stripline and microstrip transmission
lines, respectively. See the Hardware Considerations section for
specific layout recommendations for the JESD204B channel.
The AD9161/AD9162 can operate as a single-link high speed
JESD204B serial data interface. All eight lanes of the JESD204B
interface handle link layer communications such as code group
synchronization (CGS), frame alignment, and frame synchronization.
The AD9161/AD9162 decode 8-bit/10-bit control characters,
allowing marking of the start and end of the frame and
alignment between serial lanes. Each AD9161/AD9162 serial
interface link can issue a synchronization request by setting
its SYNCOUT± signal low. The synchronization protocol follows
Section 4.9 of the JESD204B standard. When a stream of four
consecutive /K/ symbols is received, the AD9161/AD9162
deactivates the synchronization request by setting
the SYNCOUT± signal high at the next internal LMFC rising
edge. Then, AD9161/AD9162 wait for the transmitter to issue
an initial lane alignment sequence (ILAS). During the ILAS, all
lanes are aligned using the /A/ to /R/ character transition as
described in the JESD204B Serial Link Establishment section.
Elastic buffers hold early arriving lane data until the alignment
character of the latest lane arrives. At this point, the buffers for
all lanes are released and all lanes are aligned (see Figure 150).
Rev. 0 | Page 49 of 139
AD9161/AD9162
Data Sheet
DATA LINK LAYER
SYNCOUTx±
LANE 7 DATA CLOCK
SYSREF±
CROSSBAR
SWITCH
SERDIN7±
FIFO
LANE 0 OCTETS
LANE 7 OCTETS
SYSTEM CLOCK
PHASE DETECT
14379-090
LANE 7 DESERIALIZED
AND DESCRAMBLED DATA
SERDIN0±
FIFO
DESCRAMBLE
LANE 0 DATA CLOCK
QUAD-BYTE
DEFRAMER
QBD
10-BIT/8-BIT DECODE
LANE 0 DESERIALIZED
AND DESCRAMBLED DATA
PCLK
SPI CONTROL
Figure 149. Data Link Layer Block Diagram
L RECEIVE LANES
(EARLIEST ARRIVAL) K K K R D D
D D A R Q C
L RECEIVE LANES
(LATEST ARRIVAL) K K K K K K K R D D
C
D D A R Q C
D D A R D D
C
D D A R D D
0 CHARACTER ELASTIC BUFFER DELAY OF LATEST ARRIVAL
4 CHARACTER ELASTIC BUFFER DELAY OF EARLIEST ARRIVAL
L ALIGNED
RECEIVE LANES K K K K K K K R D D
D D A R Q C
D D A R D D
14379-091
K = K28.5 CODE GROUP SYNCHRONIZATION COMMA CHARACTER
A = K28.3 LANE ALIGNMENT SYMBOL
F = K28.7 FRAME ALIGNMENT SYMBOL
R = K28.0 START OF MULTIFRAME
Q = K28.4 START OF LINK CONFIGURATION DATA
C = JESD204x LINK CONFIGURATION PARAMETERS
D = Dx.y DATA SYMBOL
C
Figure 150. Lane Alignment During ILAS
JESD204B Serial Link Establishment
A brief summary of the high speed serial link establishment
process for Subclass 1 is provided. See Section 5.3.3 of the
JESD204B specifications document for complete details.
Step 1: Code Group Synchronization
Each receiver must locate /K/ (K28.5) characters in its input
data stream. After four consecutive /K/ characters are detected
on all link lanes, the receiver block deasserts the SYNCOUT±
signal to the transmitter block at the receiver LMFC edge.
The transmitter captures the change in the SYNCOUT± signal
and at a future transmitter LMFC rising edge starts the ILAS.
Step 2: Initial Lane Alignment Sequence
The main purposes of this phase are to align all the lanes of the
link and to verify the parameters of the link.
Before the link is established, write each of the link parameters
to the receiver device to designate how data is sent to the
receiver block.
The ILAS consists of four or more multiframes. The last character
of each multiframe is a multiframe alignment character, /A/.
The first, third, and fourth multiframes are populated with
predetermined data values. Note that Section 8.2 of the JESD204B
specifications document describes the data ramp that is expected
during ILAS. The AD9161/AD9162 do not require this ramp.
The deframer uses the final /A/ of each lane to align the ends of
the multiframes within the receiver. The second multiframe
contains an /R/ (K.28.0), /Q/ (K.28.4), and then data
corresponding to the link parameters. Additional multiframes
can be added to the ILAS if needed by the receiver. By default,
the AD9161/AD9162 use four multiframes in the ILAS (this can
be changed in Register 0x478). If using Subclass 1, exactly four
multiframes must be used.
After the last /A/ character of the last ILAS, multiframe data
begins streaming. The receiver adjusts the position of the /A/
character such that it aligns with the internal LMFC of the
receiver at this point.
Rev. 0 | Page 50 of 139
Data Sheet
AD9161/AD9162
Step 3: Data Streaming
Table 21. Crossbar Registers
In this phase, data is streamed from the transmitter block to the
receiver block.
Address
0x308
0x308
0x309
0x309
0x30A
0x30A
0x30B
0x30B
Optionally, data can be scrambled. Scrambling does not start
until the very first octet following the ILAS.
The receiver block processes and monitors the data it receives
for errors, including the following:
•
•
•
•
•
Bad running disparity (8-bit/10-bit error)
Not in table (8-bit/10-bit error)
Unexpected control character
Bad ILAS
Interlane skew error (through character replacement)
If any of these errors exist, they are reported back to the
transmitter in one of the following ways (see the JESD204B
Error Monitoring section for details):
•
•
•
SYNCOUT± signal assertion: resynchronization
(SYNCOUT± signal pulled low) is requested at each error
for the last two errors. For the first three errors, an optional
resynchronization request can be asserted when the error
counter reaches a set error threshold.
For the first three errors, each multiframe with an error in
it causes a small pulse on SYNCOUT±.
Errors can optionally trigger an interrupt request (IRQ)
event, which can be sent to the transmitter.
For more information about the various test modes for
verifying the link integrity, see the JESD204B Test Modes
section.
Lane FIFO
The FIFOs in front of the crossbar switch and deframer synchronize the samples sent on the high speed serial data interface
with the deframer clock by adjusting the phase of the incoming
data. The FIFO absorbs timing variations between the data
source and the deframer; this allows up to two PCLK cycles of
drift from the transmitter. The FIFO_STATUS_REG_0 register
and FIFO_STATUS_REG_1 register (Register 0x30C and
Register 0x30D, respectively) can be monitored to identify
whether the FIFOs are full or empty.
Lane FIFO IRQ
An aggregate lane FIFO error bit is also available as an IRQ
event. Use Register 0x020, Bit 2 to enable the FIFO error bit,
and then use Register 0x024, Bit 2 to read back its status and
reset the IRQ signal. See the Interrupt Request Operation
section for more information.
Crossbar Switch
Bits
[2:0]
[5:3]
[2:0]
[5:3]
[2:0]
[5:3]
[2:0]
[5:3]
Logical Lane
SRC_LANE0
SRC_LANE1
SRC_LANE2
SRC_LANE3
SRC_LANE4
SRC_LANE5
SRC_LANE6
SRC_LANE7
Write each SRC_LANEy with the number (x) of the desired
physical lane (SERDINx±) from which to obtain data. By
default, all logical lanes use the corresponding physical lane as
their data source. For example, by default, SRC_LANE0 = 0;
therefore, Logical Lane 0 obtains data from Physical Lane 0
(SERDIN0±). To use SERDIN4± as the source for Logical Lane 0
instead, the user must write SRC_LANE0 = 4.
Lane Inversion
Register 0x334 allows inversion of desired logical lanes, which
can be used to ease routing of the SERDINx± signals. For each
Logical Lane x, set Bit x of Register 0x334 to 1 to invert it.
Deframer
The AD9161/AD9162 consist of one quad-byte deframer
(QBD). The deframer accepts the 8-bit/10-bit encoded data
from the deserializer (via the crossbar switch), decodes it, and
descrambles it into JESD204B frames before passing it to the
transport layer to be converted to DAC samples. The deframer
processes four symbols (or octets) per processing clock (PCLK)
cycle.
The deframer uses the JESD204B parameters that the user has
programmed into the register map to identify how the data is
packed, and unpacks it. The JESD204B parameters are
described in detail in the Transport Layer section; many of the
parameters are also needed in the transport layer to convert
JESD204B frames into samples.
Descrambler
The AD9161/AD9162 provide an optional descrambler block
using a self synchronous descrambler with the following
polynomial: 1 + x14 + x15.
Enabling data scrambling reduces spectral peaks that are
produced when the same data octets repeat from frame to
frame. It also makes the spectrum data independent so that
possible frequency selective effects on the electrical interface do
not cause data dependent errors. Descrambling of the data is
enabled by setting the SCR bit (Register 0x453, Bit 7) to 1.
Register 0x308 to Register 0x30B allow arbitrary mapping of
physical lanes (SERDINx±) to logical lanes used by the SERDES
deframers.
Rev. 0 | Page 51 of 139
AD9161/AD9162
Data Sheet
Syncing LMFC Signals
SYSREF+
50Ω
50Ω
SYSREF–
SYSREF± Signal
The SYSREF± signal is a differential source synchronous input that
synchronizes the LMFC signals in both the transmitter and receiver
in a JESD204B Subclass 1 system to achieve deterministic latency.
The SYSREF± signal is a rising edge sensitive signal that is
sampled by the device clock rising edge. It is best practice that the
device clock and SYSREF± signals be generated by the same
source, such as the HMC7044 clock generator, so that the phase
alignment between the signals is fixed. When designing for
optimum deterministic latency operation, consider the timing
distribution skew of the SYSREF± signal in a multipoint link
system (multichip).
The AD9161/AD9162 support a periodic SYSREF± signal. The
periodicity can be continuous, strobed, or gapped periodic. The
SYSREF± signal can always be dc-coupled (with a commonmode voltage of 0 V to 1.25 V). When dc-coupled, a small amount
of common-mode current (<500 µA) is drawn from the SYSREF±
pins. See Figure 151 and Figure 152 for the SYSREF± internal
circuit.
To avoid this common-mode current draw, use a 50% duty cycle
periodic SYSREF± signal with ac coupling capacitors. If ac-coupled,
the ac coupling capacitors combine with the resistors shown in
Figure 151 or Figure 152 to make a high-pass filter with an RC
time constant of τ = RC. Select C such that τ > 4/SYSREF±
frequency. In addition, the edge rate must be sufficiently fast to
meet the SYSREF± vs. DAC clock keep out window (KOW)
requirements.
It is possible to use ac-coupled mode without meeting the
frequency to time constant constraints (τ = RC and τ > 4/SYSREF±
frequency) by using SYSREF± hysteresis (Register 0x088 and
Register 0x089). However, using hystereis increases the DAC
clock KOW (Table 6 does not apply) by an amount depending
on the SYSREF± frequency, level of hysteresis, capacitor choice,
and edge rate.
100Ω
19kΩ
3kΩ
Figure 152. SYSREF± Input Circuit for the 11 mm × 11 mm 169-Ball BGA
Sync Processing Modes Overview
The AD9161/AD9162 support several LMFC sync processing
modes. These modes are one-shot, continuous, and monitor
modes. All sync processing modes perform a phase check to
confirm that the LMFC is phase aligned to an alignment edge. In
Subclass 1, the SYSREF± rising edge acts as the alignment edge; in
Subclass 0, an internal processing clock acts as the alignment edge.
The SYSREF± signal is sampled by a divide by 4 version of the
DAC clock. After SYSREF± is sampled, the phase of the (DAC
clock) ÷4 used to sample SYSREF± is stored in Register 0x037,
Bits[7:0] and Register 0x038, Bits[3:0] as a thermometer code. This
offset can be used by the SERDES data transmitter (for example,
FPGA) to align multiple DACs by accounting for this clock offset
when transmitting data. The sync modes are described below. See
the Sync Procedure section for details on the procedure for
syncing the LMFC signals.
One-Shot Sync Mode (SYNCMODE = Register 0x03A,
Bits[1:0] = 0b10)
In one-shot sync mode, a phase check occurs on only the first
alignment edge that is received after the sync machine is armed.
After the phase is aligned on the first edge, the AD9161/AD9162
transition to monitor mode. Though an LMFC synchronization
occurs only once, the SYSREF± signal can still be continuous.
In this case, the phase is monitored and reported, but no clock
phase adjustment occurs.
Continuous Sync Mode (SYNCMODE = Register 0x03A,
Bits[1:0] = 0b01)
Continuous mode must be used in Subclass 1 only with a periodic
SYSREF± signal. In continuous mode, a phase check/alignment
occurs on every alignment edge.
Monitor Sync Mode (SYNCMODE = Register 0x03A,
Bits[1:0]) = 0b00)
200Ω
14379-092
SYSREF–
19kΩ
Continuous mode differs from one-shot mode in two ways.
First, no SPI cycle is required to arm the device; the alignment
edge seen after continuous mode is enabled results in a phase
check. Second, a phase check occurs on every alignment edge in
continuous mode.
200Ω
SYSREF+
3kΩ
14379-147
The first step in guaranteeing synchronization across links and
devices begins with syncing the LMFC signals. In Subclass 0,
the LMFC signal is synchronized to an internal processing
clock. In Subclass 1, LMFC signals are synchronized to an
external SYSREF± signal.
Figure 151. SYSREF± Input Circuit for the 8 mm × 8 mm 165-Ball BGA
In monitor mode, the user can monitor the phase error in real time.
Use this sync mode with a periodic SYSREF± signal. The phase is
monitored and reported, but no clock phase adjustment occurs.
Rev. 0 | Page 52 of 139
Data Sheet
AD9161/AD9162
When an alignment request (SYSREF± edge) occurs, snapshots
of the last phase error are placed into readable registers for
reference (Register 0x037 and Register 0x038, Bits[3:0]), and the
IRQ_SYSREF_JITTER interrupt is set, if appropriate.
Sync Procedure
The procedure for enabling the sync is as follows:
1.
2.
3.
4.
5.
6.
7.
8.
9.
Set up the DAC; the SERDES PLL locks it, and enables the
CDR (see the Start-Up Sequence section).
Set Register 0x039 (SYSREF± jitter window). A minimum
of 4 DAC clock cycles is recommended. See Table 23 for
settings.
Optionally, read back the SYSREF± count to check whether
the SYSREF± pulses are being received.
a. Set Register 0x036 = 0. Writing anything to
SYSREF_COUNT resets the count.
b. Set Register 0x034 = 0. Writing anything to
SYNC_LMFC_STAT0 saves the data for readback and
registers the count.
c. Read SYSREF_COUNT from the value from
Register 0x036.
Perform a one-shot sync.
a. Set Register 0x03A = 0x00. Clear one-shot mode if
already enabled.
b. Set Register 0x03A = 0x02. Enable one-shot sync
mode. The state machine enters monitor mode after a
sync occurs.
Optionally, read back the sync SYNC_LMFC_STATx
registers to verify that sync completed correctly.
a. Set Register 0x034 = 0. Register 0x034 must be written
to read the value.
b. Read Register 0x035 and Register 0x034 to find the
value of SYNC_LMFC_STATx. It is recommended to
set SYNC_LMFC_STATx to 0 but it can be set to 4, or
a LMFC period in DAC clocks – 4, due to jitter.
Optionally, read back the sync SYSREF_PHASEx register
to identify which phase of the divide by 4 was used to
sample SYSREF±. Read Register 0x038 and Register 0x037
as thermometer code. The MSBs of Register 0x037,
Bits[7:4], normally show the thermometer code value.
Turn the link on (Register 0x300, Bit 0 = 1).
Read back Register 0x302 (dynamic link latency).
Repeat the reestablishment of the link several times (Step 1
to Step 7) and note the dynamic link latency values. Based
on the values, program the LMFC delay (Register 0x304)
and the LMFC variable (Register 0x306), and then restart
the link.
Table 22. Sync Processing Modes
Sync Processing
Mode
No synchronization
One shot
Continuous
Table 23. SYSREF± Jitter Window Tolerance
SYSREF± Jitter Window
Tolerance (DAC Clock Cycles)
±½
±4
±8
±12
±16
+20
+24
+28
1
SYSREF_JITTER_WINDOW
(Register 0x039, Bits[5:0])1
0x00
0x04
0x08
0x0C
0x10
0x14
0x18
0x1C
The two least significant digits are ignored because the SYSREF± signal is
sampled with a divide by 4 version of the DAC clock. As a result, the jitter
window is set by this divide by 4 clock rather than the DAC clock. It is
recommended that at least a four-DAC clock SYSREF± jitter window be
chosen.
Deterministic Latency
JESD204B systems contain various clock domains distributed
throughout its system. Data traversing from one clock domain
to a different clock domain can lead to ambiguous delays in the
JESD204B link. These ambiguities lead to nonrepeatable latencies
across the link from power cycle to power cycle with each new
link establishment. Section 6 of the JESD204B specification
addresses the issue of deterministic latency with mechanisms
defined as Subclass 1 and Subclass 2.
The AD9161/AD9162 support JESD204B Subclass 0 and
Subclass 1 operation, but not Subclass 2. Write the subclass to
Register 0x458, Bits[7:5].
Subclass 0
This mode gives deterministic latency to within 32 DAC clock
cycles. It does not require any signal on the SYSREF± pins,
which can be left disconnected.
Subclass 0 still requires that all lanes arrive within the same LMFC
cycle and the dual DACs must be synchronized to each other.
Subclass 1
This mode gives deterministic latency and allows the link to be
synced to within four DAC clock periods. It requires an external
SYSREF± signal that is accurately phase aligned to the DAC clock.
Deterministic Latency Requirements
Several key factors are required for achieving deterministic
latency in a JESD204B Subclass 1 system.
•
•
•
SYNC_MODE (Register 0x03A, Bits[1:0])
0b00
0b10
0b01
Rev. 0 | Page 53 of 139
SYSREF± signal distribution skew within the system must
be less than the desired uncertainty.
SYSREF± setup and hold time requirements must be met
for each device in the system.
The total latency variation across all lanes, links, and
devices must be ≤10 PCLK periods, which includes both
variable delays and the variation in fixed delays from lane
to lane, link to link, and device to device in the system.
AD9161/AD9162
Data Sheet
LINK DELAY = DELAYFIXED + DELAYVARIABLE
LOGIC DEVICE
(JESD204B Tx)
CHANNEL
JESD204B Rx
DSP
DAC
POWER CYCLE
VARIANCE
LMFC
ILAS
DATA
ALIGNED DATA
AT Rx OUTPUT
ILAS
DATA
FIXED DELAY
VARIABLE
DELAY
14379-095
DATA AT
Tx INPUT
Figure 153. JESD204B Link Delay = Fixed Delay + Variable Delay
Link Delay
The link delay of a JESD204B system is the sum of the fixed and
variable delays from the transmitter, channel, and receiver as
shown in Figure 153.
For proper functioning, all lanes on a link must be read during
the same LMFC period. Section 6.1 of the JESD204B specification states that the LMFC period must be larger than the maximum
link delay. For the AD9161/AD9162, this is not necessarily the
case; instead, the AD9161/AD9162 use a local LMFC for each
link (LMFCRx) that can be delayed from the SYSREF± aligned
LMFC. Because the LMFC is periodic, this delay can account
for any amount of fixed delay. As a result, the LMFC period
must only be larger than the variation in the link delays, and the
AD9161/AD9162 can achieve proper performance with a smaller
total latency. Figure 154 and Figure 155 show a case where the link
delay is greater than an LMFC period. Note that it can be
accommodated by delaying LMFCRx.
POWER CYCLE
VARIANCE
DATA
14379-093
ILAS
EARLY ARRIVING
LMFC REFERENCE
LATE ARRIVING
LMFC REFERENCE
Figure 154. Link Delay > LMFC Period Example
POWER CYCLE
VARIANCE
LMFC
ALIGNED DATA
The RBD described in the JESD204B specification takes values
from 1 frame clock cycle to K frame clock cycles, and the RBD
of the AD9161/AD9162 takes values from 0 PCLK cycle to
10 PCLK cycles. As a result, up to 10 PCLK cycles of total delay
variation can be absorbed. LMFCVar and LMFCDel are both in
PCLK cycles. The PCLK factor, or number of frame clock cycles
per PCLK cycle, is equal to 4/F. For more information on this
relationship, see the Clock Relationships section.
Two examples follow that show how to determine LMFCVar
and LMFCDel. After they are calculated, write LMFCDel into
Register 0x304 for all devices in the system, and write LMFCVar
to Register 0x306 for all devices in the system.
Link Delay Setup Example, With Known Delays
LMFC
ALIGNED DATA
Setting LMFCDel appropriately ensures that all the corresponding
data samples arrive in the same LMFC period. Then LMFCVar
is written into the receive buffer delay (RBD) to absorb all link
delay variation. This write ensures that all data samples have
arrived before reading. By setting these to fixed values across
runs and devices, deterministic latency is achieved.
ILAS
DATA
LMFC_DELAY
LMFC REFERENCE FOR ALL POWER CYCLES
FRAME CLOCK
Figure 155. LMFC_DELAY_x to Compensate for Link Delay > LMFC
14379-094
LMFCRX
All the known system delays can be used to calculate LMFCVar
and LMFCDel.
The example shown in Figure 156 is demonstrated in the
following steps. Note that this example is in Subclass 1 to
achieve deterministic latency, which has a PCLK factor (4/F) of
2 frame clock cycles per PCLK cycle, and uses K = 32
(frames/multiframe). Because PCBFixed << PCLK Period,
PCBFixed is negligible in this example and not included in the
calculations.
1.
2.
The method to select the LMFCDel (Register 0x304) and
LMFCVar (Register 0x306) variables is described in the Link
Delay Setup Example, With Known Delays section.
Rev. 0 | Page 54 of 139
Find the receiver delays using Table 8.
RxFixed = 17 PCLK cycles
RxVar = 2 PCLK cycles
Find the transmitter delays. The equivalent table in the
example JESD204B core (implemented on a GTH or GTX
gigabit transceiver on a Virtex-6 FPGA) states that the
delay is 56 ± 2 byte clock cycles.
Data Sheet
4.
5.
6.
7.
Because the PCLK Rate = ByteRate/4 as described in the
Clock Relationships section, the transmitter delays in
PCLK cycles are calculated as follows:
TxFixed = 54/4 = 13.5 PCLK cycles
TxVar = 4/4 = 1 PCLK cycle
Calculate MinDelayLane as follows:
MinDelayLane = floor(RxFixed + TxFixed + PCBFixed)
= floor(17 + 13.5 + 0)
= floor(30.5)
MinDelayLane = 30
Calculate MaxDelayLane as follows:
MaxDelayLane = ceiling(RxFixed + RxVar + TxFixed +
TxVar + PCBFixed))
= ceiling(17 + 2 + 13.5 + 1 + 0)
= ceiling(33.5)
MaxDelayLane = 34
Calculate LMFCVar as follows:
LMFCVar = (MaxDelay + 1) − (MinDelay − 1)
= (34 + 1) − (30 − 1) = 35 − 29
LMFCVar = 6 PCLK cycles
Calculate LMFCDel as follows:
LMFCDel = ((MinDelay − 1) % K
= ((30 − 1)) % 32 = (29) % 32
= 29 % 32
LMFCDel = 29 PCLK cycles
Write LMFCDel to Register 0x304 for all devices in the
system. Write LMFCVar to Register 0x306 for all devices in
the system.
Link Delay Setup Example, Without Known Delay
If the system delays are not known, the AD9161/AD9162 can
read back the link latency between LMFCRX for each link and
the SYSREF± aligned LMFC. This information is then used to
calculate LMFCVar and LMFCDel.
Figure 158 shows how DYN_LINK_LATENCY_0 (Register 0x302)
provides a readback showing the delay (in PCLK cycles)
between LMFCRX and the transition from ILAS to the first data
sample. By repeatedly power cycling and taking this measurement,
the minimum and maximum delays across power cycles can be
determined and used to calculate LMFCVar and LMFCDel.
In Figure 158, for Link A, Link B, and Link C, the system
containing the AD9161/AD9162 (including the transmitter) is
power cycled and configured 20 times. The AD9161/AD9162
are configured as described in the Sync Procedure section.
Because the purpose of this exercise is to determine LMFCDel
and LMFCVar, the LMFCDel value is programmed to 0 and the
DYN_LINK_LATENCY_0 value is read from Register 0x302.
The variation in the link latency over the 20 runs is shown in
Figure 158 in gray, described as follows:



Link A gives readbacks of 6, 7, 0, and 1. Note that the set of
recorded delay values rolls over the edge of a multiframe at
the boundary of K/ PCLK Factor = 8. Add the number of
PCLK cycles per multiframe (PCLKsPerMF) = 8 to the
readback values of 0 and 1 because they rolled over the
edge of the multiframe. Delay values range from 6 to 9.
Link B gives delay values from 5 to 7.
Link C gives delay values from 4 to 7.
LMFC
PCLK
FRAME CLOCK
DATA AT Tx FRAMER
ALIGNED LANE DATA
AT Rx DEFRAMER OUTPUT
ILAS
DATA
ILAS
Tx VAR
DELAY
Rx VAR
DELAY
DATA
PCB FIXED
DELAY
LMFCRX
LMFC DELAY = 26 FRAME CLOCK CYCLES
TOTAL FIXED LATENCY = 30 PCLK CYCLES
Figure 156. LMFC Delay Calculation Example
Rev. 0 | Page 55 of 139
TOTAL VARIABLE
LATENCY = 4
PCLK CYCLES
14379-096
3.
AD9161/AD9162
AD9161/AD9162
Data Sheet
4.
The example shown in Figure 158 is demonstrated in the
following steps. Note that this example is in Subclass 1 to
achieve deterministic latency, which has a PCLK Factor
(FrameRate ÷ PCLK Rate) of 2 and uses K = 16; therefore
PCLKsPerMF = 8. This example is a hypothetical example used
to illustrate the procedure, because K is always 32 on the
AD9161/AD9162.
3.
SYSREF±
LMFCRX
ILAS
ALIGNED DATA
DATA
DYN_LINK_LATENCY
Figure 157. DYN_LINK_LATENCY_x Illustration
LMFC
PCLK
FRAME CLOCK
DYN_LINK_LATENCY_CNT
0
1
2
ALIGNED DATA (LINK A)
ALIGNED DATA (LINK B)
ALIGNED DATA (LINK C)
3
4
5
6
7
0
1
2
3
ILAS
4
5
6
7
DATA
DATA
ILAS
ILAS
DATA
LMFCRX
DETERMINISTICALLY
DELAYED DATA
ILAS
LMFC_DELAY = 6
(FRAME CLOCK CYCLES)
DATA
LMFC_VAR = 7
(PCLK CYCLES)
Figure 158. Multilink Synchronization Settings, Derived Method Example
Rev. 0 | Page 56 of 139
14379-098
2.
Calculate the minimum of all delay measurements across
all power cycles, links, and devices as follows:
MinDelay = min(all Delay values) = 4
Calculate the maximum of all delay measurements across
all power cycles, links, and devices as follows:
MaxDelay = max(all Delay values) = 9
Calculate the total delay variation (with guard band) across
all power cycles, links, and devices as follows:
LMFCVar = (MaxDelay + 1) − (MinDelay − 1)
= (9 + 1) − (4 − 1) = 10 − 3 = 7 PCLK cycles
14379-097
1.
5.
Calculate the minimum delay in PCLK cycles (with guard
band) across all power cycles, links, and devices as follows:
LMFCDel
= ((MinDelay − 1) × PCLK Factor) % K
= ((4 − 1)) % 16 = (3) % 16
= 3 % 16 = 3 PCLK cycles
Write LMFCDel to Register 0x304 for all devices in the
system. Write LMFCVar to Register 0x306 for all devices in
the system.
Data Sheet
AD9161/AD9162
TRANSPORT LAYER
TRANSPORT LAYER
(QBD)
LANE 0 OCTETS
DAC A_I0[15:0]
DELAY
BUFFER 0
F2S_0
DAC A_Q0[15:0]
LANE 3 OCTETS
PCLK_0
SPI CONTROL
LANE 4 OCTETS
DAC B_I0[15:0]
PCLK_0
TO
PCLK_1
FIFO
DELAY
BUFFER 1
F2S_1
DAC B_Q0[15:0]
LANE 7 OCTETS
14379-099
PCLK_1
SPI CONTROL
Figure 159. Transport Layer Block Diagram
The transport layer receives the descrambled JESD204B frames
and converts them to DAC samples based on the programmed
JESD204B parameters shown in Table 24. The device parameters
are defined in Table 25.
Table 24. JESD204B Transport Layer Parameters
Parameter
F
K
L
M
S
Description
Number of octets per frame per lane: 1, 2, or 4
Number of frames per multiframe: K = 32
Number of lanes per converter device (per link), as
follows: 4, or 8
Number of converters per device (per link), as follows:
1 or 2 (2 is used for complex data interface)
Number of samples per converter, per frame: 1 or 2
Table 25. JESD204B Device Parameters
Parameter
CF
CS
HD
N
Nʹ (or NP)
Description
Number of control words per device clock per link.
Not supported, must be 0.
Number of control bits per conversion sample. Not
supported, must be 0.
High density user data format. Used when samples
must be split across lanes.
Set to 1 when F = 1, otherwise 0.
Converter resolution = 16.
Total number of bits per sample = 16.
Certain combinations of these parameters are supported by the
AD9161/AD9162. See Table 28 for a list of supported interpolation
rates and the number of lanes that is supported for each rate.
Table 28 lists the JESD204B parameters for each of the interpolation and number of lanes configuration, and gives an example
lane rate for a 5 GHz DAC clock. Table 27 lists JESD204B
parameters that have fixed values. A value of yes in Table 26
means the interpolation rate is supported for the number of lanes.
A blank cell means it is not supported.
Table 26. Interpolation Rates and Number of Lanes
Interpolation
1×
2×
3×
4×
6×
8×
12×
16×
24×
1
8
Yes1
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
6
4
3
2
1
Yes1
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes1
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
These modes restrict the maximum DAC clock rate to 5 GHz.
Table 27. JESD204B Parameters with Fixed Values
Parameter
K
N
NP
CF
HD
CS
Rev. 0 | Page 57 of 139
Value
32
16
16
0
1
0
AD9161/AD9162
Data Sheet
Table 28. JESD204B Parameters for Interpolation Rate and Number of Lanes
Interpolation
Rate
1
2
2
3
3
4
4
4
4
6
6
6
6
8
8
8
8
8
12
12
12
12
12
16
16
16
16
16
16
24
24
24
24
24
24
1
No. of
Lanes
8
6
8
6
8
3
4
6
8
3
4
6
8
2
3
4
6
8
2
3
4
6
8
1
2
3
4
6
8
1
2
3
4
6
8
M
1
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
F
1
2
1
2
1
4
1
2
1
4
1
2
1
2
4
1
2
1
2
4
1
2
1
4
2
4
1
2
1
4
2
4
1
2
1
S
4
3
2
3
2
3
1
3
2
3
1
3
2
1
3
1
3
2
1
3
1
3
2
1
1
3
1
3
2
1
1
3
1
3
2
PCLK Period
(DAC Clocks)
16
12
16
18
24
12
16
24
32
18
24
36
48
16
24
32
48
64
24
36
48
72
96
16
32
48
64
96
128
24
48
72
96
144
192
LMFC Period
(DAC Clocks)
128
192
128
288
192
384
128
384
256
576
192
576
384
256
768
256
768
512
384
1152
384
1152
768
512
512
1536
512
1536
1024
768
768
2304
768
2304
1536
Maximum lane rate is 12.5 GHz. These modes must be run with the DAC rate below 3.75 GHz.
Rev. 0 | Page 58 of 139
Lane Rate at 5 GHz DAC Clock
(GHz)
12.5
16.661
12.5
11.11
8.33
16.661
12.5
8.33
6.25
11.11
8.33
5.55
4.16
12.5
8.33
6.25
4.16
3.12
8.33
5.55
4.16
2.77
2.08
12.5
6.25
4.16
3.12
2.08
1.56
8.33
4.16
2.77
2.08
1.38
1.04
Data Sheet
AD9161/AD9162
Configuration Parameters
The AD9161/AD9162 modes refer to the link configuration
parameters for L, K, M, N, NP, S, and F. Table 29 provides the
description and addresses for these settings.
Table 29. Configuration Parameters
JESD204B
Setting
L−1
F−1
Description
Number of lanes − 1.
M−1
Number of ((octets per frame) per
lane) − 1.
Number of frames per multiframe −
1.
Number of converters − 1.
N−1
Converter bit resolution − 1.
NP − 1
Bit packing per sample − 1.
S−1
Number of ((samples per
converter) per frame) − 1.
High density format. Set to 1 if F =
1. Leave at 0 if F ≠ 1.
Device ID. Match the Device ID
sent by the transmitter.
Bank ID. Match the Bank ID sent by
the transmitter.
Lane ID for Lane 0. Match the Lane
ID sent by the transmitter on
Logical Lane 0.
JESD204x version. Match the
version sent by the transmitter
(0x0 = JESD204A, 0x1 = JESD204B).
K−1
HD
DID
BID
LID0
JESDV
The error counts for failing lanes are reported for one
JESD204B lane at a time. The process for performing PRBS
testing on the AD9161/AD9162 is as follows:
1.
2.
Address
Register 0x453,
Bits[4:0]
Register 0x454,
Bits[7:0]
Register 0x455,
Bits[4:0]
Register 0x456,
Bits[7:0]
Register 0x457,
Bits[4:0]
Register 0x458,
Bits[4:0]
Register 0x459,
Bits[4:0]
Register 0x45A,
Bit 7
Register 0x450,
Bits[7:0]
Register 0x451,
Bits[7:0]
Register 0x452,
Bits[4:0]
3.
4.
5.
6.
7.
8.
9.
Register 0x459,
Bits[7:5]
Data Flow Through the JESD204B Receiver
The link configuration parameters determine how the serial bits
on the JESD204B receiver interface are deframed and passed on
to the DACs as data samples.
Deskewing and Enabling Logical Lanes
After proper configuration, the logical lanes are automatically
deskewed. All logical lanes are enabled or not based on the lane
number setting in Register 0x110, Bits[7:4]. The physical lanes
are all powered up by default.
To disable power to physical lanes that are not being used, set Bit x
in Register 0x201 to 1 to disable Physical Lane x, and keep it at 0
to enable it.
JESD204B TEST MODES
PHY PRBS Testing
The JESD204B receiver on the AD9161/AD9162 includes a
PRBS pattern checker on the back end of its physical layer. This
functionality enables bit error rate (BER) testing of each
physical lane of the JESD204B link. The PHY PRBS pattern
checker does not require that the JESD204B link be established. It
can synchronize with a PRBS7, PRBS15, or PRBS31 data pattern.
PRBS pattern verification can be done on multiple lanes at once.
Start sending a PRBS7, PRBS15, or PRBS31 pattern from
the JESD204B transmitter.
Select and write the appropriate PRBS pattern to
Register 0x316, Bits[3:2], as shown in Table 30.
Enable the PHY test for all lanes being tested by writing to
PHY_TEST_EN (Register 0x315). Each bit of Register 0x315
enables the PRBS test for the corresponding lane. For example,
writing a 1 to Bit 0 enables the PRBS test for Physical Lane 0.
Toggle PHY_TEST_RESET (Register 0x316, Bit 0) from 0
to 1 then back to 0.
Set PHY_PRBS_TEST_THRESHOLD_xBITS (Bits[23:0],
Register 0x319 to Register 0x317) as desired.
Write a 0 and then a 1 to PHY_TEST_START (Register 0x316,
Bit 1). The rising edge of PHY_TEST_START starts the test.
a. (Optional) In some cases, it may be necessary to
repeat Step 4 at this point. Toggle PHY_TEST_RESET
(Register 0x316, Bit 0) from 0 to 1, then back to 0.
Wait 500 ms.
Stop the test by writing PHY_TEST_START
(Register 0x316, Bit 1) = 0.
Read the PRBS test results.
a. Each bit of PHY_PRBS_PASS (Register 0x31D)
corresponds to one SERDES lane (0 = fail, 1 = pass).
b. The number of PRBS errors seen on each failing lane
can be read by writing the lane number to check (0 to 7)
in PHY_SRC_ERR_CNT (Register 0x316, Bits[6:4])
and reading the PHY_PRBS_ERR_COUNT (Register
0x31C to Register 0x31A). The maximum error count
is 224 − 1. If all bits of Register 0x31C to Register 0x31A are
high, the maximum error count on the selected lane is
exceeded.
Table 30. PHY PRBS Pattern Selection
PHY_PRBS_PAT_SEL Setting
(Register 0x316, Bits[3:2])
0b00 (default)
0b01
0b10
PRBS Pattern
PRBS7
PRBS15
PRBS31
Transport Layer Testing
The JESD204B receiver in the AD9161/AD9162 supports the
short transport layer (STPL) test as described in the JESD204B
standard. This test can be used to verify the data mapping
between the JESD204B transmitter and receiver. To perform
this test, this function must be implemented in the logic device
and enabled there. Before running the test on the receiver side,
the link must be established and running without errors.
The STPL test ensures that each sample from each converter is
mapped appropriately according to the number of converters
(M) and the number of samples per converter (S). As specified
in the JESD204B standard, the converter manufacturer specifies
Rev. 0 | Page 59 of 139
AD9161/AD9162
Data Sheet
what test samples are transmitted. Each sample must have a
unique value. For example, if M = 2 and S = 2, four unique
samples are transmitted repeatedly until the test is stopped. The
expected sample must be programmed into the device and the
expected sample is compared to the received sample one sample
at a time until all are tested. The process for performing this test
on the AD9161/AD9162 is described as follows:
1.
2.
3.
4.
5.
6.
Synchronize the JESD204B link.
Enable the STPL test at the JESD204B Tx.
Depending on JESD204B case, there may be up to two
DACs, and each frame may contain up to four DAC
samples. Configure the SHORT_TPL_REF_SP_MSB bits
(Register 0x32E) and SHORT_TPL_REF_SP_LSB bits
(Register 0x32D) to match one of the samples for one
converter within one frame.
Set SHORT_TPL_SP_SEL (Register 0x32C, Bits[7:4]) to
select the sample within one frame for the selected
converter according to Table 31.
Set SHORT_TPL_TEST_EN (Register 0x32C, Bit 0) to 1.
Set SHORT_TPL_TEST_RESET (Register 0x32C, Bit 1) to
1, then back to 0.
7.
8.
9.
Wait for the desired time. The desired time is calculated as
1/(sample rate × BER). For example, given a bit error rate
of BER = 1 × 10−10 and a sample rate = 1 GSPS, the desired
time = 10 sec. Then, set SHORT_TPL_TEST_EN to 0.
Read the test result at SHORT_TPL_FAIL (Register 0x32F,
Bit 0).
Choose another sample for the same or another converter
to continue with the test, until all samples for both
converters from one frame are verified. (Note that the
converter count is M = 2 for all interpolator modes on the
AD9161/AD9162 to enable complex signal processing.)
Consult Table 31 for a guide to the test sample alignment. Note
that the sample order for 1×, eight-lane mode has Sample 1 and
Sample 2 swapped. Also, the STPL test for the three-lane and
six-lane options is not functional and always fails.
Table 31. Short TPL Test Samples Assignment1
JESD204x Mode
1× Eight-Lane (L = 8, M = 1, F = 1, S = 4)
Required Samples from JESD204x Tx
Send four samples: M0S0, M0S1, M0S2,
M0S3, and repeat
2× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
3× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
4× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
6× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
8× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
12× Eight-Lane e (L = 8, M = 2, F = 1, S = 2)
16× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
24× Eight-Lane (L = 8, M = 2, F = 1, S = 2)
2× Six-Lane (L = 6, M = 2, F = 2, S = 3)
3× Six-Lane (L = 6, M = 2, F = 2, S = 3)
4× Six-Lane (L = 6, M = 2, F = 2, S = 3)
6× Six-Lane (L = 6, M = 2, F = 2, S = 3)
8× Six-Lane (L = 6, M = 2, F = 2, S = 3)
12× Six-Lane (L = 6, M = 2, F = 2, S = 3)
16× Six-Lane (L = 6, M = 2, F = 2, S = 3)
24× Six-Lane (L = 6, M = 2, F = 2, S = 3)
4× Six-Lane (L = 3, M = 2, F = 4, S = 3)
6× Three-Lane (L = 3, M = 2, F = 4, S = 3)
8× Three-Lane (L = 3, M = 2, F = 4, S = 3)
12× Three-Lane (L = 3, M = 2, F = 4, S = 3)
16× Three-Lane (L = 3, M = 2, F = 4, S = 3)
24× Three-Lane (L = 3, M = 2, F = 4, S = 3)
Send four samples: M0S0, M0S1, M1S0,
M1S1, and repeat
Send six samples: M0S0, M0S1, M0S2,
M1S0, M1S1, M1S2, and repeat
Rev. 0 | Page 60 of 139
Samples Assignment
SP0: M0S0, SP4: M0S0, SP8: M0S0, SP12: M0S0
SP1: M0S2, SP5: M0S2, SP9: M0S2, SP13: M0S2
SP2: M0S1, SP6: M0S1, SP10: M0S1, SP14: M0S1
SP3: M0S3, SP7: M0S3, SP11: M0S3, SP15: M0S3
SP0: M0S0, SP4: M0S0, SP8: M0S0, SP12: M0S0
SP1: M1S0, SP5: M1S0, SP9: M1S0, SP13: M1S0
SP2: M0S1, SP6: M0S1, SP10: M0S1, SP14: M0S1
SP3: M1S1, SP7: M1S1, SP11: M1S1, SP15: M1S1
Test hardware is not functional; STPL always fails
Data Sheet
JESD204x Mode
4× Four-Lane (L = 4, M = 2, F = 1, S = 1)
6× Four-Lane (L = 4, M = 2, F = 1, S = 1)
8× Four-Lane (L = 4, M = 2, F = 1, S = 1)
12× Four-Lane (L = 4, M = 2, F = 1, S = 1)
16× Four-Lane (L = 4, M = 2, F = 1, S = 1)
24× Four-Lane (L = 4, M = 2, F = 1, S = 1)
8× Two-Lane (L = 2, M = 2, F = 2, S = 1)
12× Two-Lane (L = 2, M = 2, F = 2, S = 1)
16× Two-Lane (L = 2, M = 2, F = 2, S = 1)
24× Two-Lane (L = 2, M = 2, F = 2, S = 1)
16× One-Lane (L = 1, M = 2, F = 4, S = 1)
24× One-Lane (L = 1, M = 2, F = 4, S = 1)
1
AD9161/AD9162
Required Samples from JESD204x Tx
Send two samples: M0S0, M1S0, repeat
Samples Assignment
SP0: M0S0, SP4: M0S0, SP8: M0S0, SP12: M0S0
SP1: M1S0, SP5: M1S0, SP9: M1S0, SP13: M1S0
SP2: M0S0, SP6: M0S0, SP10: M0S0, SP14: M0S0
SP3: M1S0, SP7: M1S0, SP11: M1S0, SP15: M1S0
Mx is the converter number and Sy is the sample number. For example, M0S0 means Converter 0, Sample 0. SPx is the sample pattern word number. For example, SP0
means Sample Pattern Word 0.
Repeated CGS and ILAS Test
As per Section 5.3.3.8.2 of the JESD204B specification, the
AD9161/AD9162 can check that a constant stream of /K28.5/
characters is being received, or that CGS followed by a constant
stream of ILAS is being received.
To run a repeated CGS test, send a constant stream of /K28.5/
characters to the AD9161/AD9162 SERDES inputs. Next, set up
the device and enable the links. Ensure that the /K28.5/ characters
are being received by verifying that SYNCOUT± is deasserted
and that CGS has passed for all enabled link lanes by reading
Register 0x470.
To run the CGS followed by a repeated ILAS sequence test,
follow the procedure to set up the links, but before performing
the last write (enabling the links), enable the ILAS test mode by
writing a 1 to Register 0x477, Bit 7. Then, enable the links. When
the device recognizes four CGS characters on each lane, it
deasserts the SYNCOUT±. At this point, the transmitter starts
sending a repeated ILAS sequence.
Read Register 0x473 to verify that initial lane synchronization has
passed for all enabled link lanes.
values of the bad disparity error (BDE) count register is 1.
Reporting of disparity errors that occur at the same character
position of an NIT error is disabled. No such disabling is performed for the disparity errors in the characters after an NIT
error. Therefore, it is expected behavior that an NIT error may
result in a BDE error.
A resync is triggered when four NIT errors are injected with
Register 0x476, Bit 4 = 1. When this bit is set, the error counter
does not distinguish between a concurrent invalid symbol with
the wrong running disparity but is in the 8-bit/10-bit decoding
table, and a NIT error. Thus, a resync can be triggered when
four NIT errors are injected because they are not distinguished
from disparity errors.
Checking Error Counts
The error count can be checked for disparity errors, NIT errors,
and unexpected control character errors. The error counts are
on a per lane and per error type basis. Each error type and lane
has a register dedicated to it. To check the error count, the
following steps must be performed:
1.
JESD204B ERROR MONITORING
Disparity, Not in Table, and Unexpected Control (K)
Character Errors
As per Section 7.6 of the JESD204B specification, the AD9161/
AD9162 can detect disparity errors, not in table (NIT) errors,
and unexpected control character errors, and can optionally
issue a sync request and reinitialize the link when errors occur.
Note that the disparity error counter counts all characters with
invalid disparity, regardless of whether they are in the 8-bit/10-bit
decoding table. This is a minor deviation from the JESD204B
specification, which only counts disparity errors when they are
in the 8-bit/10-bit decoding table.
2.
3.
Several other interpretations of the JESD204B specification are
noted in this section. When three NIT errors are injected to one
lane and QUAL_RDERR (Register 0x476, Bit 4) = 1, the readback
Rev. 0 | Page 61 of 139
Choose and enable which errors to monitor by selecting
them in Register 0x480, Bits[5:3] to Register 0x487,
Bits[5:3]. Unexpected K (UEK) character, BDE, and NIT
error monitoring can be selected for each lane by writing a
1 to the appropriate bit, as described in the register map.
These bits are enabled by default.
The corresponding error counter reset bits are in
Register 0x480, Bits[2:0] to Register 0x487, Bits[2:0].
Write a 0 to the corresponding bit to reset that error
counter.
Registers 0x488, Bits[2:0] to Register 0x48F, Bits[2:0] have
the terminal count hold indicator for each error counter. If
this flag is enabled, when the terminal error count of 0xFF
is reached, the counter ceases counting and holds that
value until reset. Otherwise, it wraps to 0x00 and continues
counting. Select the desired behavior and program the
corresponding register bits per lane.
AD9161/AD9162
Data Sheet
Table 32. Setting SYNCOUT± Error Pulse Duration
Check for Error Count Over Threshold
To check for the error count over threshold, follow these steps:
1.
2.
Define the error counter threshold. The error counter
threshold can be set to a user defined value in Register
0x47C, or left to the default value of 0xFF. When the error
threshold is reached, an IRQ is generated or SYNCOUT± is
asserted or both, depending on the mask register settings.
This one error threshold is used for all three types of errors
(UEK, NIT, and BDE).
Set the SYNC_ASSERT_MASK bits. The SYNCOUT±
assertion behavior is set in Register 0x47D, Bits[2:0]. By
default, when any error counter of any lane is equal to the
threshold, it asserts SYNCOUT± (Register 0x47D, Bits[2:0] =
0b111).
Read the error count reached indicator. Each error counter
has a terminal count reached indicator, per lane. This indicator is set to 1 when the terminal count of an error counter
for a particular lane has been reached. These status bits are
located in Register 0x490, Bits[2:0] to Register 0x497, Bits[2:0].
These registers also indicate whether a particular lane is
active by setting Bit 3 = 0b1.
Error Counter and IRQ Control
For error counter and IRQ control, follow these steps:
1.
2.
Enable the interrupts. Enable the JESD204B interrupts. The
interrupts for the UEK, NIT, and BDE error counters are in
Register 0x4B8, Bits[7:5]. There are other interrupts to
monitor when bringing up the link, such as lane deskewing,
initial lane sync, good check sum, frame sync, code group sync
(Register 0x4B8, Bits[4:0], and configuration mismatch
(Register 0x4B9, Bit 0). These bits are off by default but can
be enabled by writing 0b1 to the corresponding bit.
Read the JESD204B interrupt status. The interrupt status
bits are in Register 0x4BA, Bits[7:0] and Register 0x4BB,
Bit 0, with the status bit position corresponding to the
enable bit position.
It is recommended to enable all interrupts that are planned
to be used prior to bringing up the JESD204B link. When
the link is up, the interrupts can be reset and then used to
monitor the link status.
F
1
2
4
1
PCLK Factor
(Frames/PCLK)
4
2
1
SYNC_ERR_DUR (Register 0x312,
Bits[7:4]) Setting1
0 (default)
1
2
These register settings assert the SYNCOUT± signal for two frame clock cycle
pulse widths.
Unexpected Control Character, NIT, Disparity IRQs
For UEK character, NIT, and disparity errors, error count over
the threshold events are available as IRQ events. Enable these
events by writing to Register 0x4B8, Bits[7:5]. The IRQ event
status can be read at Register 0x4BA, Bits[7:5] after the IRQs are
enabled.
See the Error Counter and IRQ Control section for information
on resetting the IRQ. See the Interrupt Request Operation
section for more information on IRQs.
Errors Requiring Reinitializing
A link reinitialization automatically occurs when four invalid
disparity characters are received as per Section 7.1 of the
JESD204B specification. When a link reinitialization occurs, the
resync request is five frames and nine octets long.
The user can optionally reinitialize the link when the error
count for disparity errors, NIT errors, or UEK character errors
reaches a programmable error threshold. The process to enable
the reinitialization feature for certain error types is as follows:
1.
2.
3.
4.
Monitoring Errors via SYNCOUT±
When one or more disparity, NIT, or unexpected control
character errors occur, the error is reported on the SYNCOUT±
pin as per Section 7.6 of the JESD204B specification. The
JESD204B specification states that the SYNCOUT± signal is
asserted for exactly two frame periods when an error occurs. For
the AD9161/AD9162, the width of theSYNCOUT± pulse can be
programmed to ½, 1, or 2 PCLK cycles. The settings to achieve a
SYNCOUT± pulse of two frame clock cycles are given in Table 32.
Rev. 0 | Page 62 of 139
Choose and enable which errors to monitor by selecting
them in Register 0x480, Bits[5:3] to Register 0x487,
Bits[5:3]. UEK, BDE, and NIT error monitoring can be
selected for each lane by writing a 1 to the appropriate bit,
as described in Table 47. These are enabled by default.
Enable the sync assertion mask for each type of error by
writing to SYNC_ASSERT_MASK (Register 0x47D,
Bits[2:0]) according to Table 33.
Program the desired error counter threshold into
ERRORTHRES (Register 0x47C).
For each error type enabled in the SYNC_ASSERT_MASK
register, if the error counter on any lane reaches the
programmed threshold, SYNCOUT± falls, issuing a sync
request. Note that all error counts are reset when a link
reinitialization occurs. The IRQ does not reset and must be
reset manually.
Data Sheet
AD9161/AD9162
Table 33. Sync Assertion Mask (SYNC_ASSERT_MASK)
CGS, Frame Sync, Checksum, and ILAS IRQs
Addr.
0x47D
Fail signals for CGS, frame sync, checksum, and ILAS are available
as IRQ events. Enable them by writing to Register 0x4B8,
Bits[3:0]. The IRQ event status can be read at Register 0x4BA,
Bits[3:0] after the IRQs are enabled. Write a 1 to Register 0x4BA,
Bit 0 to reset the CGS IRQ. Write a 1 to Register 0x4BA, Bit 1 to
reset the frame sync IRQ. Write a 1 to Register 0x4BA, Bit 2 to
reset the checksum IRQ. Write a 1 to Register 0x4BA, Bit 3 to
reset the ILAS IRQ.
Bit No.
2
Bit Name
BDE
1
NIT
0
UEK
Description
Set to 1 to assert SYNCOUT± if
the disparity error count
reaches the threshold
Set to 1 to assert SYNCOUT± if
the NIT error count reaches
the threshold
Set to 1 to assert SYNCOUT± if
the UEK character error
count reaches the threshold
See the Interrupt Request Operation section for more information.
Configuration Mismatch IRQ
CGS, Frame Sync, Checksum, and ILAS Monitoring
Register 0x470 to Register 0x473 can be monitored to verify
that each stage of the JESD204B link establishment has
occurred.
Bit x of CODE_GRP_SYNC (Register 0x470) is high if Link
Lane x received at least four K28.5 characters and passed code
group synchronization.
Bit x of FRAME_SYNC (Register 0x471) is high if Link Lane x
completed initial frame synchronization.
Bit x of GOOD_CHECKSUM (Register 0x472) is high if the
checksum sent over the lane matches the sum of the JESD204B
parameters sent over the lane during ILAS for Link Lane x. The
parameters can be added either by summing the individual fields
in registers or summing the packed register. If Register 0x300,
Bit 6 = 0 (default), the calculated checksums are the lower eight
bits of the sum of the following fields: DID, BID, LID, SCR, L − 1,
F − 1, K − 1, M − 1, N − 1, SUBCLASSV, NP − 1, JESDV, S − 1,
and HD. If Register 0x300, Bit 6 = 1, the calculated checksums
are the lower eight bits of the sum of Register 0x400 to
Register 0x40C and LID.
The AD9161/AD9162 have a configuration mismatch flag that
is available as an IRQ event. Use Register 0x4B9, Bit 0 to enable
the mismatch flag (it is enabled by default), and then use
Register 0x4BB, Bit 0 to read back its status and reset the IRQ
signal. See the Interrupt Request Operation section for more
information.
The configuration mismatch event flag is high when the link
configuration settings (in Register 0x450 to Register 0x45D) do
not match the JESD204B transmitted settings (Register 0x400 to
Register 0x40D).
This function is different from the good checksum flags in
Register 0x472. The good checksum flags ensure that the transmitted checksum matches a calculated checksum based on the
transmitted settings. The configuration mismatch event ensures
that the transmitted settings match the configured settings.
HARDWARE CONSIDERATIONS
See the Applications Information section for information on
hardware considerations.
Bit x of INIT_LANE_SYNC (Register 0x473) is high if Link
Lane x passed the initial lane alignment sequence.
Rev. 0 | Page 63 of 139
AD9161/AD9162
Data Sheet
MAIN DIGITAL DATAPATH
HB
2×
HB
2×
NCO
HB
2×,
4×,
8×
HB
3×
INV
SINC
14379-104
JESD
Figure 160. Block Diagram of the Main Digital Datapath
The block diagram in Figure 160 shows the functionality of the
main digital datapath. The digital processing includes an input
interpolation block with choice of bypass (1×), 2×, or 3×
interpolation, three additional 2× half-band interpolation
filters, a final 2× NRZ mode interpolator filter, FIR85, that can
be bypassed, and a quadrature modulator that consists of a
48-bit NCO and an inverse sinc block.
All of the interpolation filters accept in-phase (I) and quadrature
(Q) data streams as a complex data stream. Similarly, the
quadrature modulator and inverse sinc function also accept
input data as a complex data stream. Thus, any use of the digital
datapath functions requires the input data to be a complex data
stream.
In bypass mode (1× interpolation), the input data stream is
expected to be real data.
Table 34. Pipeline Delay (Latency) for Various DAC Blocks
Mode
NCO only
1× (Bypass)
1× (Bypass)
2×
2×
2×
2×
2×
2×
3×
3×
4×
6×
8×
12×
16×
24×
1
2
FIR85
On
No
No
No
No
No
Yes
No
Yes
Yes
No
No
No
No
No
No
No
No
Filter
Bandwidth
N/A2
N/A2
N/A2
80%
90%
80%
80%
80%
80%
80%
90%
80%
80%
80%
80%
80%
80%
Inverse
Sinc
No
No
Yes
No
No
No
Yes
Yes
Yes
No
No
No
No
No
No
No
No
NCO
Yes
No
No
No
No
No
No
No
Yes
No
No
No
No
No
No
No
No
Pipeline
Delay1
(fDAC
Clocks)
48
113
137
155
176
202
185
239
279
168
202
308
332
602
674
1188
1272
The pipeline delay given is a representative number, and may vary by a cycle
or two based on the internal handoff timing conditions at startup.
N/A means not applicable.
The pipeline delay changes based on the digital datapath
functions that are selected. See Table 34 for examples of the
pipeline delay per block. These delays are in addition to the
JESD204B latency.
DATA FORMAT
The input data format for all modes on the AD9161/AD9162 is
16-bit, twos complement. The digital datapath and the DAC
decoder operate in twos complement format. The DAC is a
current steering DAC and cannot represent 0—it must either
source or sink current. As a result, when the 0 of twos complement is represented in the DAC, it is a +1, and all the positive
values thereafter are shifted by +1. This mapping error introduces a
½ LSB shift in the DAC output. The leakage can become apparent
when using the NCO to shift a signal that is above or below
0 Hz when synthesized. The NCO frequency is seen as a small
spur at the NCO FTW.
To avoid the NCO frequency leakage, operate the DAC with a
slight digital backoff of one or several codes, and then add 1 to
all values in the data stream. These actions remove the NCO
frequency leakage but cause a half LSB DC offset. This small dc
offset is benign to the DAC and does not affect most applications
because the DAC output is ac-coupled through dc blocking
capacitors.
INTERPOLATION FILTERS
The main digital path contains five half-band interpolation
filters, plus a final half-band interpolation filter that is used in
2× NRZ mode. The filters are cascaded as shown in Figure 160.
The first pair of filters is a 2× (HB2) or 3× (HB3) filter. Each of
these filters has two options for bandwidth, 80% or 90%. The
80% filters are lower power than the 90%. The filters default to
the lower power 80% bandwidth. To select the filter bandwidth
as 90%, program the FILT_BW bit in the DATAPATH_CFG
register to 1 (Register 0x111, Bit 4 = 0b1).
Following the first pair of filters is a series of 2× half-band
filters, each of which halves the usable bandwidth of the
previous one. HB4 has 45%, HB5 has 22.5%, and HB6 has
11.25% of the fDATA bandwidth.
The final half-band filter, FIR85, is used in the 2× NRZ mode. It
is clocked at the 2 × fDAC rate and has a usable bandwidth of 45%
of the fDAC rate. The FIR85 filter is a complex filter, and
therefore the bandwidth is centered at 0 Hz. The FIR85 filter is
used in conjunction with the complex interpolation modes to
Rev. 0 | Page 64 of 139
Data Sheet
AD9161/AD9162
1×
2×
3×
4×
6×
8×
12×
16×
24×
FIR85
Table 35 shows how to select each available interpolation mode,
their usable bandwidths, and their maximum data rates. Calculate
the available signal bandwidth as the interpolator filter bandwidth,
BW, multiplied by fDAC/InterpolationFactor, as follows:
–1500
BWSIGNAL = BWFILT × (fDAC/InterpolationFactor)
–500
500
1500
2500
FREQUENCY (MHz)
14379-105
The FIR85 filter can be used with the 1× bypass mode, but in
that mode, the signal is limited to the lower half of the Nyquist
zone, that is, up to fDAC/4. If the NCO is used with FIR85 in 1×
bypass mode, images of the NCO upconversion appears because
the data interface in 1× bypass is real; therefore, an image reject
upconversion cannot be accomplished by the NCO. To synthesize a signal and then upconvert it with the NCO, use the complex
data interface and choose an appropriate interpolator prior to
FIR85.
of each of the filters is shown in Figure 161. The maximum pass
band amplitude of all filters is the same; they are different in the
illustration to improve understanding.
FILTER RESPONSE
push the DAC update rate higher and move images further
from the desired signal.
Figure 161. All Band Responses of Interpolation Filters
Filter Performance
The interpolation filters interpolate between existing data in
such a way that they minimize changes in the incoming data
while suppressing the creation of interpolation images. This
datapath is shown for each filter in Figure 161.
The usable bandwidth (as shown in Table 35) is defined as the
frequency band over which the filters have a pass-band ripple of
less than ±0.001 dB and an image rejection of greater than
85 dB. A conceptual drawing that shows the relative bandwidth
Filter Performance Beyond Specified Bandwidth
Some of the interpolation filters are specified to 0.4 × fDATA (with
a pass band). The filters can be used slightly beyond this ratio at
the expense of increased pass-band ripple and decreased
interpolation image rejection.
Table 35. Interpolation Modes and Usable Bandwidth
Interpolation Mode
1× (Bypass)
2×
3×
4×
6×
8×
12×
16×
24×
2× NRZ (Register 0x111, Bit 0 = 1)
INTERP_MODE, Register 0x110, Bits[3:0]
0x00
0x01
0x02
0x03
0x04
0x05
0x06
0x07
0x08
Any combination 3
Available Signal Bandwidth
(BW) 1
fDAC/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
BW × fDATA/2
0.45 × fDAC 4
Maximum fDATA (MHz)
fDAC 2
fDAC/22
fDAC/3
fDAC/4
fDAC/6
fDAC/8
fDAC/12
fDAC/16
fDAC/24
fDAC (real) or fDAC/2(complex)2
The data rate (fDATA) for all interpolator modes is a complex data rate, meaning each of I data and Q data run at that rate. The data rate for the 1× bypass mode is a real
data rate. Available signal bandwidth is the data rate multiplied by the bandwidth of the initial 2× or 3× interpolator filters, which can be set to BW = 80% or BW =
90%. This bandwidth is centered at 0 Hz.
2
The maximum speed for 1× and 2× interpolation is limited by the JESD204B interface, and is 5000 MHz (real) in 1× or 2500 MHz (complex) in 2× interpolation mode.
3
The 2× NRZ filter, FIR85, can be used with any of the interpolator combinations. When used in 1× bypass mode, the desired signal must be placed in the lower half of the
first Nyquist zone, as in 0 to DAC clock ÷ 4 MHz.
4
The bandwidth of the FIR85 filter is centered at 0 Hz.
1
Rev. 0 | Page 65 of 139
Data Sheet
20
0
90
–0.2
60
–0.3
50
–0.4
40
–0.5
30
–20
42
45
44
43
–80
–120
–140
–0.6
41
–60
–100
IMAGE REJECTION
PASS-BAND RIPPLE
20
40
–40
BANDWIDTH (% fDATA )
0
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
Figure 164. First 2× Half-Band 90% Filter Response
20
0
–20
MAGNITUDE (dB)
Most of the filters are specified to 0.45 × fDATA (with pass band).
Figure 163 to Figure 170 show the filter response for each of the
interpolator filters on the AD9161/AD9162.
0.2
NORMALIZED FREQUENCY (Rad/Sample)
Figure 162. Interpolation Filter Performance Beyond Specified Bandwidth for
the 80% Filters
Figure 162 shows the performance of the interpolation filters
beyond 0.4 × fDATA. The ripple increases much slower than the
image rejection decreases. This means that if the application can
tolerate degraded image rejection from the interpolation filters,
more bandwidth can be used.
0.1
14379-159
70
MAGNITUDE (dB)
–0.1
MAXIMUM PASS-BAND RIPPLE (dB)
0
80
14379-106
–40
–60
–80
–100
–120
20
–140
–160
0
–20
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
MAGNITUDE (dB)
NORMALIZED FREQUENCY (Rad/Sample)
14379-160
0
Figure 165. 3× Third-Band 80% Filter Response
–40
20
–60
0
–80
–20
–140
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
NORMALIZED FREQUENCY (Rad/Sample)
1.0
14379-158
–120
MAGNITUDE (dB)
–100
–40
–60
–80
–100
Figure 163. First 2× Half-Band 80% Filter Response
–120
–140
–160
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
NORMALIZED FREQUENCY (Rad/Sample)
Figure 166. 3× Third-Band 90% Filter Response
Rev. 0 | Page 66 of 139
1.0
14379-161
MINIMUM INTERPOLATION IMAGE REJECTION (dB)
AD9161/AD9162
Data Sheet
AD9161/AD9162
20
20
0
0
–20
–20
MAGNITUDE (dB)
–60
–80
–100
–60
–80
–100
–120
–120
–140
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
NORMALIZED FREQUENCY (Rad/Sample)
–140
14379-162
–160
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
NORMALIZED FREQUENCY (Rad/Sample)
Figure 167. Second 2× Half-Band 45% Filter Response
1.0
Figure 170. FIR85 2× Half-Band 45% Filter Response
20
DIGITAL MODULATION
0
The AD9161/AD9162 have digital modulation features to
modulate the baseband quadrature signal to the desired DAC
output frequency.
–20
–40
–120
The AD9161/AD9162 are equipped with several NCO modes.
The default NCO is a 48-bit, integer NCO. The A/B ratio of the
dual modulus NCO allows the output frequency to be synthesized with very fine precision. NCO mode is selected as shown
in Table 36.
–140
Table 36. Modulation Mode Selection
–60
–80
–100
–160
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
NORMALIZED FREQUENCY (Rad/Sample)
14379-163
MAGNITUDE (dB)
–40
14379-165
MAGNITUDE (dB)
–40
Figure 168. Third 2× Half-Band 22.5% Filter Response
20
MAGNITUDE (dB)
0
Modulation Mode
None
48-Bit Integer NCO
48-Bit Dual Modulus NCO
Modulation Type
Register 0x111, Register 0x111,
Bit 6
Bit 2
0b0
0b0
0b1
0b0
0b1
0b1
–20
48-Bit Dual Modulus NCO
–40
This modulation mode uses an NCO, a phase shifter, and a
complex modulator to modulate the signal by a programmable
carrier signal as shown in Figure 171. This configuration allows
output signals to be placed anywhere in the output spectrum
with very fine frequency resolution.
–60
–80
–100
–140
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
NORMALIZED FREQUENCY (Rad/Sample)
Figure 169. Fourth 2× Half-Band 11.25% Filter Response
1.0
14379-164
–120
The NCO produces a quadrature carrier to translate the input
signal to a new center frequency. A quadrature carrier is a pair of
sinusoidal waveforms of the same frequency, offset 90° from
each other. The frequency of the quadrature carrier is set via a
FTW. The quadrature carrier is mixed with the I and Q data and
then summed into the I and Q datapaths, as shown in Figure 171.
Rev. 0 | Page 67 of 139
AD9161/AD9162
Data Sheet
Integer NCO Mode
The main 48-bit NCO can be used as an integer NCO by using
the following formula to create the frequency tuning word
(FTW):
−fDAC/2 ≤ fCARRIER < +fDAC/2
INTERPOLATION
COS(ωn + θ)
ω
π
NCO
θ
SIN(ωn + θ)
FTW[47:0]
NCO_PHASE_OFFSET
[15:0]
48
OUT_I
OUT_Q
–
where FTW is a 48-bit, twos complement number.
+
–1
When in 2× NRZ mode (FIR85 enabled with Register 0x111,
Bit 0 = 1), the frequency tuning word is calculated as
SEL_SIDEBAND
0
1
0 ≤ fCARRIER < fDAC
Q DATA
FTW = (fCARRIER/fDAC) × 248
where FTW is a 48-bit binary number.
Figure 171. NCO Modulator Block Diagram
This method of calculation causes fCARRIER values in the second
Nyquist zone to appear to move to fDAC − fCARRIER when flipping
the FIR85 enable bit and not changing the FTW to account for
the change in number format.
The intended effect is that a sweep of the NCO from 0 Hz to
fDAC − fDAC/248 appears seamless when the FIR85 enable bit is set
to Register 0x111, Bit 0 = 0b1 prior to fCARRIER/fDAC = 0.5. As can
be seen from examination, the FTWs from 0 to less than fDAC/2
mean the same in either case, but they mean different fCARRIER
values from fDAC/2 to fDAC − fDAC/248. This effect must be considered
when constructing FTW values and using the 2× NRZ mode.
The frequency tuning word is set as shown in Table 37.
Table 37. NCO FTW Registers
Address
0x114
0x115
0x116
0x117
0x118
0x119
Value
FTW[7:0]
FTW[15:8]
FTW[23:16]
FTW[31:24]
FTW[39:32]
FTW[47:40]
INTERPOLATION
14379-108
FTW = (fCARRIER/fDAC) × 2
I DATA
Description
8 LSBs of FTW
Next 8 bits of FTW
Next 8 bits of FTW
Next 8 bits of FTW
Next 8 bits of FTW
8 MSBs of FTW
Modulus NCO Mode
The main 48-bit NCO can also be used in a dual modulus mode
to create fractional frequencies beyond the 48-bit accuracy. The
modulus mode is enabled by programming the MODULUS_EN
bit in the DATAPATH_CFG register to 1 (Register 0x111, Bit 2 =
0b1).
The frequency ratio for the programmable modulus direct
digital synthesis (DDS) is very similar to that of the typical
accumulator-based DDS. The only difference is that N is not
required to be a power of two for the programmable modulus,
but can be an arbitrary integer. In practice, hardware constraints
place limits on the range of values for N. As a result, the
modulus extends the use of the NCO to applications that
require exact rational frequency synthesis. The underlying
function of the programmable modulus technique is to alter the
accumulator modulus.
Implementation of the programmable modulus function within
the AD9161/AD9162 is such that the fraction, M/N, is expressible per Equation 1. Note that the form of the equation implies a
compound frequency tuning word with X representing the
integer part and A/B representing the fractional part.
Unlike other registers, the FTW registers are not updated immediately upon writing. Instead, the FTW registers update on the
rising edge of FTW_LOAD_REQ (Register 0x113, Bit 0). After
an update request, FTW_LOAD_ACK (Register 0x113, Bit 1) must
be high to acknowledge that the FTW has updated.
The SEL_SIDEBAND bit (Register 0x111, Bit 1 = 0b1) is a convenience bit that can be set to use the lower sideband modulation
result, which is equivalent to flipping the sign of the FTW.
A
f CARRIER M X + B
=
=
2 48
f DAC
N
where:
X is programmed in Register 0x114 to Register 0x119.
A is programmed in Register 0x12A to Register 0x12F.
B is programmed in Register 0x124 to Register 0x129.
Rev. 0 | Page 68 of 139
(1)
Data Sheet
AD9161/AD9162
Consider the case in which fDAC = 2500 MHz and the desired
value of fCARRIER is 250 MHz. This scenario synthesizes an output
frequency that is not a power of two submultiple of the sample
rate, namely fCARRIER = (1/10) fDAC, which is not possible with a
typical accumulator-based DDS. The frequency ratio, fCARRIER/fDAC,
leads directly to M and N, which are determined by reducing
the fraction (250,000,000/2,500,000,000) to its lowest terms, that is,
M/N = 250,000,000/2,500,000,000 = 1/10
The speed of the SPI port write function is guaranteed, and is a
minimum of 100 MHz (see Table 4). Thus, the NCO FTW can
be updated in as little as 240 ns with a one register write in
automatic update mode.
The manner in which the NCO transitions to the new frequency is
determined by the frequency change mode selection.
The NCO supports several modes of changing frequency: phase
continuous or phase noncontinuous. The modes are given in
Table 38.
Therefore, M = 1 and N = 10.
Table 38. NCO Frequency Change Mode
After calculation, X = 28147497671065, A = 3, and B = 5.
Programming these values into the registers for X, A, and B (X
is programmed in Register 0x114 to Register 0x119, B is
programmed in Register 0x124 to Register 0x129, and A is
programmed in Register 0x12A to Register 0x12F)) causes the
NCO to produce an output frequency of exactly 250 MHz given
a 2500 MHz sampling clock. For more details, refer to the AN953 Application Note on the Analog Devices, Inc., website.
Register 0x800,
Bits[7:6]
0b00
0b01
Resetting the NCO can be useful when determining the start time
and phase of the NCO. The NCO can be reset by several different methods, including a SPI write, using the TX_ENABLE pin,
or by the SYSREF± signal. Due to internal timing variations
from device to device, these methods achieve an accuracy of
±6 DAC clock cycles.
Program Register 0x800, Bits[7:6] to 0b01 to set the NCO in
phase discontinuous switching mode via a write to the SPI port.
Then, any time the frequency tuning word is updated, the NCO
phase accumulator resets and the NCO begins counting at the
new FTW.
Changing the Main NCO Frequency
In the main 48-bit NCO, the mode of updating the frequency
tuning word can be changed from requiring a write to the
FTW_LOAD_REQ bit (Register 0x113, Bit 0) to an automatic
update mode. In the automatic update mode, the FTW is
updated as soon as the chosen FTW word is written.
To set the automatic FTW update mode, write the appropriate
word to the FTW_REQ_MODE bits (Register 0x113, Bits[6:4]),
choosing the particular FTW word that causes the automatic
update. For example, if relatively coarse frequency steps are
needed, it may be sufficient to write a single word to the MSB
byte of the FTW, and therefore the FTW_REQ_MODE bits can
be programmed to 110 (Register 0x113, Bits[6:4] = 0b110).
Then, each time the most significant byte, FTW5, is written, the
NCO FTW is automatically updated.
In phase continuous switching, the frequency tuning word of
the NCO is updated and the phase accumulator continues to
accumulate to the new frequency. In phase noncontinuous
mode, the FTW of the NCO is updated and the phase accumulator
is reset, making an instantaneous jump to the new frequency.
INVERSE SINC
The AD9161/AD9162 provide a digital inverse sinc filter to
compensate the DAC roll-off over frequency. The filter is
enabled by setting the INVSINC_ENABLE bit (Register 0x111,
Bit 7) and is disabled by default.
The inverse sinc (sinc−1) filter is a seven-tap FIR filter. Figure 172
shows the frequency response of sin(x)/x roll-off, the inverse
sinc filter, and the composite response. The composite response
has less than ±0.05 dB pass-band ripple up to a frequency of
0.4 × fDACCLK. When 2× NRZ mode is enabled, the inverse sinc
filter operates to 0.4 × f2×DACCLK. To provide the necessary
peaking at the upper end of the pass band, the inverse sinc filter
shown has an intrinsic insertion loss of about 3.8 dB.
1
SIN(x)/x ROLL-OFF
SINC–1 FILTER RESPONSE
COMPOSITE RESPONSE
0
MAGNITUDE (dB)
NCO Reset
Description
Phase continuous switch
Phase noncontinuous switch (reset NCO
accumulator)
The FTW_REQ_MODE bits can be configured to use any of the
FTW words as the automatic update trigger word. This configuration provides convenience when choosing the order in which to
program the FTW registers.
Rev. 0 | Page 69 of 139
–1
–2
–3
–4
–5
0
0.05
0.10
0.15
0.20
0.25
0.30
0.35
0.40
0.45
0.50
FREQUENCY (× fDAC )
Figure 172. Responses of Sin(x)/x Roll-Off, the Sinc−1 Filter, and the
Composite of the Two
14379-109
Programmable Modulus Example
AD9161/AD9162
Data Sheet
DOWNSTREAM PROTECTION
The AD9161/AD9162 have several features designed to protect
the power amplifier (PA) of the system, as well as other downstream blocks. They consist of a control signal from the LMFC
sync logic and a transmit enable function. The protection mechanism in each case is the blanking of data that is passed to the
DAC decoder. The differences lie in the location in the datapath
and slight variations of functionality.
The JESD204B serial link has several flags and quality measures
to indicate the serial link is up and running error free. If any of
these measures flags an issue, a signal from the LMFC sync logic is
sent to a mux that stops data from flowing to the DAC decoder
and replaces it with 0s.
There are several transmit enable features, including a TX_
ENABLE register that can be used to squelch data at several
points in the datapath or configure the TX_ENABLE pin to do
likewise.
controlled function, namely to zero the input to the digital
datapath or to zero the output from the digital datapath. In
addition, the TX_ENABLE pin can also be configured to ramp
down (or up) the full-scale current of the DAC. The ramp down
reduces the output power of the DAC by about 20 dB from full
scale to the minimum output current.
The TX_ENABLE pin can also be programmed to reset the
NCO phase accumulator. See Table 39 for a description of the
settings available for the TX_ENABLE function.
Table 39. TX_ENABLE Settings
Register
0x03F
Bit 7
Setting
0
1
Bit 6
0
1
Transmit Enable
The transmit enable feature can be configured either as a SPI
controlled function or a pin controlled function. It can be used
for several different purposes. The SPI controlled function has
less accurate timing due to its reliance on a microcontroller to
program it; therefore, it is typically used as a preventative measure
at power-up or when configuring the device.
The SPI controlled TX_ENABLE function can be used to zero
the input to the digital datapath or to zero the output from the
digital datapath, as shown in Figure 173. If the input to the
digital datapath is zeroed, any filtering that is selected filters the
0 signal, causing a gradual ramp-down of energy in the digital
datapath. If the digital datapath is bypassed, as in 1÷ mode, the
data at the input to the DAC immediately drops to zero.
The TX_ENABLE pin can be used for more accurate timing
when enabling or disabling the DAC output. The effect of the
TX_ENABLE pin can be configured by the same TX_ENABLE
register (Register 0x03F) as is used for the SPI controlled functions, and it can be made to have the same effects as the SPI
Bits[5:4]
Bit 3
N/A1
0
1
0
1
Bit 2
Bit 1
0
1
Bit 0
0
1
1
2
Description
SPI control: zero data to the DAC
SPI control: allow data to pass to the
DAC
SPI control: zero data at input to the
datapath
SPI control: allow data to enter the
datapath
Reserved
Use SPI writes to reset the NCO2
Use TX_ENABLE to reset the NCO
Use SPI control to zero data to the DAC
Use TX_ENABLE pin to zero data to the
DAC
Use SPI control to zero data at the input
to the datapath
Use TX_ENABLE pin to zero data at
input to the datapath
Use SPI registers to control the full-scale
current
Use TX_ENABLE pin to control the fullscale current
N/A means not applicable.
Use SPI writes to reset the NCO if resetting the NCO is desired. Register 0x800,
Bits[7:6] determine whether the NCO is reset. See Table 38 for more details.
DATA
TO DAC
0
0
MAIN
DIGITAL
PATH
0
FROM LMFC
SYNC LOGIC
FROM REG
0x03F[7]
FROM REG
0x03F[6]
FROM REG
0x03F[2]
FROM REG
0x03F[1]
Figure 173. Downstream Protection Block Diagram
Rev. 0 | Page 70 of 139
14379-110
TX_ENABLE
TX_ENABLE
Data Sheet
AD9161/AD9162
INTERRUPT REQUEST OPERATION
The AD9161/AD9162 provide an interrupt request output
signal (IRQ) on Ball G1 (8 mm × 8 mm package) or Ball G4
(11 mm × 11 mm package) that can be used to notify an external
host processor of significant device events. On assertion of the
interrupt, query the device to determine the precise event that
occurred. The IRQ pin is an open-drain, active low output. Pull
the IRQ pin high, external to the device. This pin can be tied to
the interrupt pins of other devices with open-drain outputs to
wire; OR these pins together.
Figure 174 shows a simplified block diagram of how the IRQ
blocks works. If IRQ_EN is low, the INTERRUPT_SOURCE
signal is set to 0. If IRQ_EN is high, any rising edge of EVENT
causes the INTERRUPT_SOURCE signal to be set high. If any
INTERRUPT_SOURCE signal is high, the IRQ pin is pulled
low. INTERRUPT_SOURCE can be reset to 0 by either an
IRQ_RESET signal or a DEVICE_RESET signal.
Depending on the STATUS_MODE signal, the EVENT_STATUS
bit reads back an event signal or INTERRUPT_SOURCE signal.
The AD9161/AD9162 have several IRQ register blocks that can
monitor up to 75 events (depending on device configuration).
Certain details vary by IRQ register block as described in Table 40.
Table 41 shows the source registers of the IRQ_EN, IRQ_RESET,
and STATUS_MODE signals in Figure 174, as well as the address
where EVENT_STATUS is read back.
Table 40. IRQ Register Block Details
Register Block
0x020, 0x024
Event
Reported
Per chip
0x4B8 to 0x4BB; 0x470
to 0x473
Per link and
lane
EVENT_STATUS
INTERRUPT_SOURCE if
IRQ is enabled; if not, it
is the event signal
INTERRUPT_SOURCE if
IRQ is enabled; if not, 0
INTERRUPT SERVICE ROUTINE
Interrupt request management starts by selecting the set of event
flags that require host intervention or monitoring. Enable the
events that require host action so that the host is notified when
they occur. For events requiring host intervention upon IRQ
activation, run the following routine to clear an interrupt request:
1.
2.
3.
4.
Read the status of the event flag bits that are being monitored.
Disable the interrupt by writing 0 to IRQ_EN.
Read the event source.
Perform any actions that may be required to clear the cause
of the event. In many cases, no specific actions may be
required.
Verify that the event source is functioning as expected.
Clear the interrupt by writing 1 to IRQ_RESET.
Enable the interrupt by writing 1 to IRQ_EN.
5.
6.
7.
0
1
EVENT_STATUS
STATUS_MODE
IRQ
IRQ_EN
EVENT
INTERRUPT_SOURCE
0
1
IRQ_EN
OTHER
INTERRUPT
SOURCES
IRQ_RESET
14379-111
DEVICE_RESET
Figure 174. Simplified Schematic of IRQ Circuitry
Table 41. IRQ Register Block Address of IRQ Signal Details
Register Block
0x020, 0x024
0x4B8 to 0x4BB
0x470 to 0x473
1
IRQ_EN
0x020; R/W per chip
0x4B8, 0x4B9; W per error type
0x470 to 0x473; W per error type
Address of IRQ Signals
IRQ_RESET
STATUS_MODE 1
0x024; W per chip
STATUS_MODE = IRQ_EN
0x4BA, 0x4BB; W per error type N/A, STATUS_MODE = 1
0x470 to 0x473; W per link
N/A, STATUS_MODE = 1
N/A means not applicable.
Rev. 0 | Page 71 of 139
EVENT_STATUS
0x024; R per chip
0x4BA, 0x4BB; R per chip
0x470 to 0x473; R per link
AD9161/AD9162
Data Sheet
APPLICATIONS INFORMATION
HARDWARE CONSIDERATIONS
Power Sequencing
Power Supply Recommendations
The AD9161/AD9162 require power sequencing to avoid
damage to the DAC. A board design with the AD9161/AD9162
must include a power sequencer chip, such as the ADM1184, to
ensure that the domains power up in the correct order. The
ADM1184 monitors the level of power domains upon power-up.
It sends an enable signal to the next grouping of power domains.
When all power domains are powered up, a power-good signal
is sent to the system controller to indicate all power supplies are
powered up.
All the AD9161/AD9162 supply domains must remain as noise
free as possible for the best operation. Power supply noise has a
frequency component that affects performance, and is specified in
volts rms terms.
An LC filter on the output of the power supply is recommended
to attenuate the noise, and must be placed as close to the AD9161/
AD9162 as possible. The VDD12_CLK supply is the most noise
sensitive supply on the device, followed by the VDD25_DAC
and VNEG_N1P2 supplies, which are the DAC output rails. It is
highly recommended that the VDD12_CLK be supplied by
itself with an ultralow noise regulator such as the ADM7154 or
ADP1761 or better to achieve the best phase noise performance
possible. Noisier regulators impose phase noise onto the DAC
output.
The VDD12A supply can be connected to the digital DVDD
supply with a separate filter network. All of the SERDES 1.2 V
supplies can be connected to one regulator with separate filter
networks. The IOVDD supply can be connected to the VDD25_
DAC supply with a separate filter network, or can be powered
from a system controller (for example, a microcontroller), 1.8 V
to 3.3 V supply. The power supply sequencing requirement
must be met; therefore, a switch or other solution must be used
when connected to the IOVDD supply with VDD25_DAC.
Take note of the maximum power consumption numbers given
in Table 3 to ensure the power supply design can tolerate temperature and IC process variation extremes. The amount of current
drawn is dependent on the chosen use cases, and specifications
are provided for several use cases to illustrate examples and
contributions from individual blocks, and to assist in calculating
the maximum required current per supply.
Another consideration for the power supply design is peak
current handling capability. The AD9161/AD9162 draw more
current in the main digital supply when synthesizing a signal
with significant amplitude variations, such as a modulated
signal, as compared to when in idle mode or synthesizing a
dc signal. Therefore, the power supply must be able to supply
current quickly to accommodate burst signals such as GSM,
TDMA, or other signals that have an on/off time domain response.
Because the amount of current variation depends on the signals
used, it is best to perform lab testing first to establish ranges. A
typical difference can be several hundred milliamperes.
The IOVDD, VDD12A, VDD12_CLK, and DVDD domains
must be powered up first. Then, the VNEG_N1P2, VDD_1P2,
PLL_CLK_VDD12, DVDD_1P2, and SYNC_VDD_3P3 can be
powered up. The VDD25_DAC domain must be powered up
last. There is no requirement for a power-down sequence.
Power and Ground Planes
Solid ground planes are recommended to avoid ground loops
and to provide a solid, uninterrupted ground reference for the
high speed transmission lines that require controlled impedances.
It is recommended that power planes be stacked between
ground layers for high frequency filtering. Doing so adds extra
filtering and isolation between power supply domains in
addition to the decoupling capacitors.
Do not use segmented power planes as a reference for controlled
impedances unless the entire length of the controlled impedance
trace traverses across only a single segmented plane. These and
additional guidelines for the topology of high speed transmission
lines are described in the JESD204B Serial Interface Inputs
(SERDIN0± to SERDIN7±) section.
For some applications, where highest performance and higher
output frequencies are required, the choice of PCB materials
significantly impacts results. For example, materials such as
polyimide or materials from the Rogers Corporation can be
used, for example, to improve tolerance to high temperatures
and improve performance. Rogers 4350 material is used for the
top three layers in some of the evaluation board designs:
between the top signal layer and the ground layer below it,
between the ground layer and an internal signal layer, and
between that signal layer and another ground layer.
JESD204B Serial Interface Inputs (SERDIN0± to
SERDIN7±)
When considering the layout of the JESD204B serial interface
transmission lines, there are many factors to consider to
maintain optimal link performance. Among these factors are
insertion loss, return loss, signal skew, and the topology of the
differential traces.
Rev. 0 | Page 72 of 139
Data Sheet
AD9161/AD9162
The JESD204B specification limits the amount of insertion loss
allowed in the transmission channel (see Figure 146). The AD9161/
AD9162 equalization circuitry allows significantly more loss in the
channel than is required by the JESD204B specification. It is still
important that the designer of the PCB minimize the amount of
insertion loss by adhering to the following guidelines:



Keep the differential traces short by placing the
AD9161/AD9162 as near the transmitting logic device as
possible and routing the trace as directly as possible between
the devices.
Route the differential pairs on a single plane using a solid
ground plane as a reference. It is recommended to route the
SERDES lanes on the same layer as the AD9161/AD9162 to
avoid vias being used in the SERDES lanes.
Use a PCB material with a low dielectric constant (<4) to
minimize loss, if possible.
When choosing between the stripline and microstrip techniques,
keep in mind the following considerations: stripline has less loss
(see Figure 147 and Figure 148) and emits less EMI, but
requires the use of vias that can add complexity to the task of
controlling the impedance; whereas microstrip is easier to
implement (if the component placement and density allow
routing on the top layer) and eases the task of controlling the
impedance.
If using the top layer of the PCB is problematic or the advantages
of stripline are desirable, follow these recommendations:




Minimize the number of vias.
If possible, use blind vias to eliminate via stub effects and
use microvias to minimize via inductance.
If using standard vias, use the maximum via length to
minimize the stub size. For example, on an 8-layer board,
use Layer 7 for the stripline pair (see Figure 175).
For each via pair, place a pair of ground vias adjacent to them
to minimize the impedance discontinuity (see Figure 175).
LAYER 1
ADD GROUND VIAS
y
STANDARD VIA
LAYER 5
y
DIFF+
LAYER 6
GND
LAYER 7
LAYER 8
y
DIFF–
LAYER 3
LAYER 4
GND
MINIMIZE STUB EFFECT
14379-100
LAYER 2
Figure 175. Minimizing Stub Effect and Adding Ground Vias for Differential
Stripline Traces
AD9162. Minimizing the use of vias, or eliminating them all
together, reduces one of the primary sources for impedance
mismatches on a transmission line (see the Insertion Loss section).
Maintain a solid reference beneath (for microstrip) or above
and below (for stripline) the differential traces to ensure continuity
in the impedance of the transmission line. If the stripline technique is used, follow the guidelines listed in the Insertion Loss
section to minimize impedance mismatches and stub effects.
Another primary source for impedance mismatch is at either
end of the transmission line, where care must be taken to match
the impedance of the termination to that of the transmission
line. The AD9161/AD9162 handle this internally with a calibrated termination scheme for the receiving end of the line. See
the Interface Power-Up and Input Termination section for details
on this circuit and the calibration routine.
Signal Skew
There are many sources for signal skew, but the two sources to
consider when laying out a PCB are interconnect skew within a
single JESD204B link and skew between multiple JESD204B
links. In each case, keeping the channel lengths matched to
within 12.5 mm is adequate for operating the JESD204B link at
speeds of up to 12.5 Gbps. This amount of channel length
match is equivalent to about 85% UI on the AD9161/AD9162
evaluation board. Managing the interconnect skew within a
single link is fairly straightforward. Managing multiple links
across multiple devices is more complex. However, follow the
12.5 mm guideline for length matching. The AD9161/AD9162
can handle more skew than the 85% UI due to the 6 PCLK
buffer in the JESD204B receiver, but matching the channel
lengths as close as possible is still recommended.
Topology
Structure the differential SERDINx± pairs to achieve 50 Ω to
ground for each half of the pair. Stripline vs. microstrip tradeoffs are described in the Insertion Loss section. In either case, it
is important to keep these transmission lines separated from
potential noise sources such as high speed digital signals and
noisy supplies. If using stripline differential traces, route them
using a coplanar method, with both traces on the same layer.
Although this method does not offer more noise immunity than
the broadside routing method (traces routed on adjacent
layers), it is easier to route and manufacture so that the
impedance continuity is maintained. An illustration of
broadside vs. coplanar is shown in Figure 176.
Tx DIFF A
Tx DIFF B
Return Loss
The JESD204B specification limits the amount of return loss
allowed in a converter device and a logic device, but does not
specify return loss for the channel. However, every effort must
be made to maintain a continuous impedance on the transmission line between the transmitting logic device and the AD9161/
Tx ACTIVE
BROADSIDE DIFFERENTIAL Tx LINES
Tx
DIFF A
Tx
DIFF B
Tx
ACTIVE
COPLANAR DIFFERENTIAL Tx LINES
14379-101
Insertion Loss
Figure 176. Broadside vs. Coplanar Differential Stripline Routing Techniques
When considering the trace width vs. copper weight and
thickness, the speed of the interface must be considered. At
Rev. 0 | Page 73 of 139
AD9161/AD9162
Data Sheet
To minimize the impedance mismatch at the pads, select the
package size of the capacitor so that the pad size on the PCB
matches the trace width as closely as possible.
multigigabit speeds, the skin effect of the conducting material
confines the current flow to the surface. Maximize the surface
area of the conductor by making the trace width made wider to
reduce the losses. Additionally, loosely couple differential traces
to accommodate the wider trace widths. This coupling helps
reduce the crosstalk and minimize the impedance mismatch
when the traces must separate to accommodate components,
vias, connectors, or other routing obstacles. Tightly coupled vs.
loosely coupled differential traces are shown in Figure 177.
TIGHTLY COUPLED
DIFFERENTIAL Tx LINES
Tx
DIFF A
Tx
DIFF B
Separate the SYNCOUT± signal from other noisy signals,
because noise on the SYNCOUT± might be interpreted as a
request for /K/ characters.
LOOSELY COUPLED
DIFFERENTIAL Tx LINES
It is important to keep similar trace lengths for the CLK± and
SYSREF± signals from the clock source to each of the devices
on either end of the JESD204B links (see Figure 178). If using a
clock chip that can tightly control the phase of CLK± and
SYSREF±, the trace length matching requirements are greatly
reduced.
Figure 177. Tightly Coupled vs. Loosely Coupled Differential Traces
AC Coupling Capacitors
The AD9161/AD9162 require that the JESD204B input signals
be ac-coupled to the source. These capacitors must be 100 nF
and placed as close as possible to the transmitting logic device.
LANE 0
LANE 1
Tx
DEVICE
Rx
DEVICE
LANE N – 1
LANE N
SYSREF±
DEVICE CLOCK
SYSREF±
CLOCK SOURCE
(AD9516-1, ADCLK925)
SYSREF± TRACE LENGTH
DEVICE CLOCK TRACE LENGTH
DEVICE CLOCK
SYSREF± TRACE LENGTH
DEVICE CLOCK TRACE LENGTH
Figure 178. SYSREF± Signal and Device Clock Trace Length
Rev. 0 | Page 74 of 139
14379-103
Tx
DIFF B
The SYNCOUT± and SYSREF± signals on the AD9161/AD9162
are low speed LVDS differential signals. Use controlled impedance
traces routed with 100 Ω differential impedance and 50 Ω to
ground when routing these signals. As with the SERDIN0± to
SERDIN7± data pairs, it is important to keep these signals separated from potential noise sources such as high speed digital
signals and noisy supplies.
14379-102
Tx
DIFF A
SYNCOUT±, SYSREF±, and CLK± Signals
Data Sheet
AD9161/AD9162
ANALOG INTERFACE CONSIDERATIONS
The AD9161/AD9162 use the quad-switch architecture shown in
Figure 179. Only one pair of switches is enabled during a halfclock cycle, thus requiring each pair to be clocked on alternative
clock edges. A key benefit of the quad-switch architecture is that it
masks the code dependent glitches that occur in the conventional
two-switch DAC architecture.
CLK±
CLK
IOUTP
VG1
DATA INPUT
VG1
INPUT
DATA
D1
D2
VG2 VG3
D3
D4
D5
D6
D7
D8
D3
D10
–D8
D2
FOUR-SWITCH
DAC OUTPUT
(fS MIX-MODE)
VG4
D9
DACCLK_x
IOUTN
VG2
LATCHES V 3
G
When Mix-Mode is used, the output is effectively chopped at
the DAC sample rate. This chopping has the effect of reducing
the power of the fundamental signal while increasing the power
of the images centered around the DAC sample rate, thus
improving the dynamic range of these images.
D4
–D7
D1
D5
–D9
–D6
–D10
t
–D5 D6
–D1
VG4
–D2
D10
–D4
D9
D7
–D3
14379-114
ANALOG MODES OF OPERATION
D8
14379-112
Figure 181. Mix-Mode Waveform
VSSA
Figure 179. Quad-Switch Architecture
In two-switch architecture, when a switch transition occurs and
D1 and D2 are in different states, a glitch occurs. However, if D1
and D2 happen to be at the same state, the switch transitions and
no glitches occur. This code dependent glitching causes an
increased amount of distortion in the DAC. In quad-switch
architecture (no matter what the codes are), there are always
two switches that are transitioning at each half-clock cycle, thus
eliminating the code-dependent glitches but, in the process,
creating a constant glitch at 2 × fDAC. For this reason, a significant
clock spur at 2 × fDAC is evident in the DAC output spectrum.
INPUT
DATA
D1
D2
D3
D4
D5
D6
D7
D8
D9
This ability to change modes provides the user the flexibility to
place a carrier anywhere in the first three Nyquist zones, depending
on the operating mode selected. Switching between baseband
and Mix-Mode reshapes the sinc roll-off inherent at the DAC
output. In baseband mode, the sinc null appears at fDACCLK because
the same sample latched on the rising clock edge is also latched
again on the falling clock edge, thus resulting in the same ubiquitous sinc response of a traditional DAC. In Mix-Mode, the
complement sample of the rising edge is latched on the falling
edge, therefore pushing the sinc null to 2 × fDACCLK. Figure 182
shows the ideal frequency response of the three modes with the
sinc roll-off included.
FIRST
NYQUIST ZONE
D10
SECOND
NYQUIST ZONE
0
THIRD
NYQUIST ZONE
MIX-MODE
DACCLK_x
–5
RZ MODE
D3
D4
D5
t
D6
D6
D2
D3
D4
D7
D7
D8
D8
D9
D9
AMPLITUDE (dBFS)
FOUR-SWITCH
DAC OUTPUT
(NORMAL MODE) D1
D2
D10
D10
D5
t
14379-113
TWO-SWITCH
DAC OUTPUT
D1
–10
–15
NORMAL
MODE
–20
–25
–30
As a consequence of the quad-switch architecture enabling
updates on each half-clock cycle, it is possible to operate that
DAC core at 2× the DAC clock rate if new data samples are latched
into the DAC core on both the rising and falling edge of the
DAC clock. This notion serves as the basis when operating the
AD9161/AD9162 in either Mix-Mode or return to zero (RZ)
mode. In each case, the DAC core is presented with new data
samples on each clock edge: in RZ mode, the rising edge clocks
data and the falling edge clocks zero, while in Mix-Mode; the
falling edge sample is simply the complement of the rising edge
sample value.
–35
0FS
0.25FS
0.50FS
0.75FS
1.00FS
1.25FS
1.50FS
FREQUENCY (Hz)
14379-115
Figure 180. Two-Switch and Quad-Switch DAC Waveforms
Figure 182. Sinc Roll-Off for NRZ, RZ, and Mix-Mode Operation
The quad-switch can be configured via SPI (Register 0x152,
Bits[1:0]) to operate in either NRZ mode (0b00), RZ mode
(0b10), or Mix-Mode (0b01). The AD9161/AD9162 have an
additional frequency response characteristic due to the FIR85
filter. This filter samples data on both the rising and falling
edges of the DAC clock, in essence doubling the input clock
frequency. As a result, the NRZ (normal) mode roll-off in
Figure 182 is extended to 2 × fDAC in Figure 182, and follows the
Rev. 0 | Page 75 of 139
AD9161/AD9162
Data Sheet
Mix-Mode roll-off due to the zero-order hold at 2 × DAC clock
(see Figure 183).
0
NRZ MODE
2× NRZ MODE
MIX-MODE
RZ MODE
–3
–6
–9
–15
The clock input has a register that adjusts the phase of the CLK+
and CLK− inputs. This register is located at Address 0x07F. The
register has a signed magnitude (1 is negative) value that adds
capacitance at 20 fF per step to either the CLK+ or the CLK−
input, according to Table 42. The CLK_PHASE_TUNE register
can be used to adjust the clock input phase for better DAC
image rejection.
–18
–21
–24
–27
–30
0
1020 2040 3060 4080 5100 6120 7140 8160 9180 10200
FREQUENCY (MHz)
Figure 183. Sinc Roll-Off with 2× NRZ Mode Added, fDAC = 5.1 GSPS
CLOCK INPUT
The AD9161/AD9162 contain a low jitter, differential clock
receiver that is capable of interfacing directly to a differential
or single-ended clock source. Because the input is self biased with a
nominal impedance of 90 Ω, it is recommended that the clock
source be ac-coupled to the CLK± input pins. The nominal
differential input is 1 V p-p, but the clock receiver can operate
with a span that ranges from 250 mV p-p to 2.0 V p-p. Better
phase noise performance is achieved with a higher clock input
level.
DUTY CYCLE
RESTORER
CLK+
CROSS
CONTROL
TO DAC
AND DLL
CLK–
5kΩ
5kΩ
1.25V
40kΩ
14379-116
16µA
Table 42. CLK± Phase Adjust Values
Register 0x07F,
Bits[5:0]
000000
000001
000010
…
011111
100000
100001
100010
…
111111
Capacitance at
CLK+
0
1 × 20 fF
2 × 20 fF
…
31 × 20 fF
0
0
0
…
0
Capacitance at
CLK−
0
0
0
…
0
0
1 × 20 fF
2 × 20 fF
…
31 × 20 fF
The improvement in performance from making these
adjustments depends on the accuracy of the balance of the clock
input balun and varies from unit to unit. Thus, if a high level of
image rejection is required, it is likely that a per unit calibration
is necessary. Performing this calibration can yield significant
improvements, as much as 20 dB additional rejection of the
image due to imbalance. Figure 185 shows the results of tuning
clock phase, duty cycle (left at default in this case), and cross
control. The improvement to performance, particularly at
higher frequencies, can be as much as 20 dB.
–20
Figure 184. Clock Input
The quality of the clock source, as well as its interface to the
AD9161/AD9162 clock input, directly impacts ac performance.
Select the phase noise and spur characteristics of the clock source
to meet the target application requirements. Phase noise and
spurs at a given frequency offset on the clock source are directly
translated to the output signal. It can be shown that the phase noise
characteristics of a reconstructed output sine wave are related to
the clock source by 20 × log10 (fOUT/fCLK) when the DAC clock
path contribution is negligible.
Figure 187 shows a clock source based on the ADF4355 low phase
noise/jitter PLL. The ADF4355 can provide output frequencies
from 54 MHz up to 6.8 GHz.
The clock control registers exist at Address 0x082 through
Address 0x084. CLK_DUTY (Register 0x082) can be used to
–30
–40
PHASE 0,
CROSS 6
–50
–60
–70
PHASE 28,
CROSS 10
–80
–90
0
1000
2000
3000
fOUT (MHz)
4000
5000
6000
14379-221
–36
14379-193
–33
DAC OUTPUT IMAGE POWER (fS – fOUT) (dBc)
POWER (dBc)
–12
enable duty cycle correction (Bit 7), enable duty cycle offset
control (Bit 6), and set the duty cycle offset (Bits[4:0]). The duty
cycle offset word is a signed magnitude word, with Bit 4 being
the sign bit (1 is negative) and Bits[3:0] the magnitude. The duty
cycle adjusts across a range of approximately ±3%. Recommended
settings for this register are listed in the Start-Up Sequence
section.
Figure 185. Performance Improvement from Tuning the Clock Input
Rev. 0 | Page 76 of 139
Data Sheet
AD9161/AD9162
SHUFFLE MODE
The spurious performance of the AD9161/AD9162 can be
improved with a feature called shuffle mode. Shuffle mode uses
proprietary technology to spread the energy of spurious signals
across the DAC output as random noise. Shuffle mode is
enabled by programming Register 0x151, Bit 2 = 0b1. Because
shuffle is implemented with the MSBs, it is more effective when
the DAC is operated with a small amount of digital backoff.
The amount of noise rise caused by shuffle mode is directly
related to the power in the affected spurious signals. Because
the AD9161/AD9162 have good spurious performance without
shuffle active, the penalty of shuffle mode to the noise spectral
density is typically about 1 dB to 3 dB. Shuffle mode reduces
spurious performance related to clock and foldback spurs, but
does not affect real harmonics of the DAC output. Examples of
the effects of shuffle mode are given in the Typical Performance
Characteristics section (see Figure 17, Figure 18, Figure 32,
Figure 33, Figure 99, Figure 100, Figure 114, Figure 115, and
Figure 116).
DLL
The CLK± input goes to a high frequency DLL to ensure robust
locking of the DAC sample clock to the input clock. The DLL is
configured and enabled as part of the recommended start-up
sequence. The DLL control registers are located at Register 0x090
through Register 0x09B. The DLL settings are determined during
product characterization and are given in the recommended
start-up sequence (see the Start-Up Sequence section). It is not
normally necessary to change these values, nor is the product
characterization data valid on any settings other than the recommended ones.
VOLTAGE REFERENCE
The AD9161/AD9162 output current is set by a combination of
digital control bits and the ISET reference current, as shown in
Figure 186.
The reference current is obtained by forcing the band gap
voltage across an external 9.6 kΩ resistor from ISET (Ball A15
on the 8 mm × 8 mm package and Ball A12 on the 11 mm ×
11 mm package) to VNEG_N1P2. The 1.2 V nominal band gap
voltage (VREF) generates a 125 µA reference current, ISET, in
the 9.6 kΩ resistor, RSET. The maximum full-scale current
setting is related to the external resistor by the following
equation:
IOUTFS = 1.2 V/RSET × 320 (mA)
Note the following constraints when configuring the voltage
reference circuit:
•
•
•
•
•
The IOUTFS value can be adjusted digitally over an 8 mA to
40 mA range by the ANA_FULL_SCALE_CURRENT[9:0] bits
(Register 0x042, Bits[7:0] and Register 0x041, Bits[1:0]). The
following equation relates IOUTFS to the ANA_FULL_SCALE_
CURRENT[9:0] bits, which can be set from 0 to 1023.
IOUTFS = 32 mA × (ANA_FULL_SCALE_CURRENT[9:0]/1023) +
8 mA
Note that the default value of 0x3FF generates 40 mA full scale,
and this value is used for most of the characterization presented
in this data sheet, unless noted otherwise.
AD9161/AD9162
VBG
1.2V
VREF
ISET
1µF
VSS
DAC
+
CURRENT
SCALING
IOUTFS
ISET
VNEG_N1P2
14379-119
9.6kΩ
ANA_FULL_SCALE_CURRENT [9:0]
–
Both the 9.6 kΩ resistor and 1 µF bypass capacitor are
required for proper operation.
Adjusting the DAC output full-scale current, IOUTFS, from
its default setting of 40 mA must be performed digitally.
The AD9161/AD9162 are not multiplying DACs.
Modulation of the reference current, ISET, with an ac
signal is not supported.
The band gap voltage appearing at the VREF pin must be
buffered for use with an external circuitry because it has a
high output impedance.
An external reference can be used to overdrive the internal
reference by connecting it to the VREF pin.
Figure 186. Voltage Reference Circuit
Rev. 0 | Page 77 of 139
AD9161/AD9162
Data Sheet
VOUT
AD9161/
AD9162
ADF4355
7.4nH
100pF
CLK+
PLL
OUTPUT
STAGE
VCO
100pF
CLK–
FREF
14379-174
7.4nH
VOUT 2GHz TO 6GHz
0dBm
Figure 187. Possible Signal Chain for CLK± Input
The AD9161/AD9162 provide complementary current outputs,
OUTPUT+ and OUTPUT−, that sink current from an external
load that is referenced to the 2.5 V VDD25_DAC supply. Figure
188 shows an equivalent output circuit for the DAC. Compared
to most current output DACs of this type, the outputs of the
AD9161/AD9162 consist of a constant current (IFIXED), and a peak
differential ac current, ICS (ICS = ICSP + ICSN). These two currents
combine to form the IINTx currents shown in Figure 188. The
internal currents, IINTP and IINTN, are sent to the output pin and
to an input termination resistance equivalent to 100 Ω pulled to
the VDD25_DAC supply (RINT). This termination serves to divide
the output current based on the external termination resistors
that are pulled to VDD25_DAC.
VDD25_DAC
IOUTFS = 8mA – 40mA
100Ω
ICSP
IINTP
IFIXED
IFIXED
IINTN
40
35
30
25
20
15
10
5
0
0
16384
32768
DAC CODE
OUTPUT+
OUTPUT–
100Ω
VDD25_DAC
49152
65536
Figure 189. Gain Curve for ANA_FULL_SCALE_CURRENT[9:0] = 1023, DAC
Offset = 3.8 mA
Peak DAC Output Power Capability
14379-120
ICSN
45
14379-121
Equivalent DAC Output and Transfer Function
external load, and thus must be ac-coupled through appropriately
sized capacitors for the chosen operating frequencies. Figure 189
shows the OUTPUT+ vs. DAC code transfer function when
IOUTFS is set to 40 mA.
OUTPUT CURRENT (mA)
ANALOG OUTPUTS
Figure 188. Equivalent DAC Output Circuit
The example shown in Figure 188 can be modeled as a pair of
dc current sources that source a current of IOUT to each output.
This differential ac current source is used to model the signal
(that is, a digital code) dependent nature of the DAC output.
The polarity and signal dependency of this ac current source are
related to the digital code (F) by the following equation:
F (code) = (DACCODE – 32,768)/32,768
(2)
where:
−1 ≤ F (code) < +1.
DACCODE = 0 to 65,535 (decimal).
To calculate the rms power delivered to the load, consider the
following:
The current that is measured at the OUTPUT+ and OUTPUT−
outputs is as follows:
OUTPUT+ = (IFIXED (mA) + (F × IOUTFS)/FMAX(mA)) ×
(RINT/(RINT + RLOAD)
The maximum peak power capability of a differential current
output DAC is dependent on its peak differential ac current,
IPEAK, and the equivalent load resistance it sees. In the case of a
1:1 balun with 100 Ω differential source termination, the equivalent load that is seen by the DAC ac current source is 50 Ω. If
the AD9161/AD9162 are programmed for an IOUTFS = 40 mA, its
ideal peak ac current is 20 mA and its maximum power, delivered to the equivalent load, is 10 × (RINT/(RINT + RLOAD) = 8 mW
(that is, P = I2R). Because the source and load resistance seen by
the 1:1 balun are equal, this power is shared equally. Therefore,
the output load receives 4 mW, or 6 dBm maximum power.
(3)
OUTPUT− = (IFIXED (mA) + ((FMAX − F) ×
IOUTFS)/FMAX(mA)) ×(RINT/(RINT + RLOAD)
The IFIXED value is about 3.8 mA. It is important to note that the
AD9161/AD9162 output cannot support dc coupling to the
•
•
•
•
Peak to rms of the digital waveform
Any digital backoff from digital full scale
DAC sinc response and nonideal losses in the external
network
DAC analog roll-off due to switch parasitic capacitance and
load impedance
For example, a sine wave with no digital backoff ideally measures
6 dBm. If a typical balun loss of 1.2 dB is included, expect to
Rev. 0 | Page 78 of 139
Data Sheet
AD9161/AD9162
Output Stage Configuration
The AD9161/AD9162 are intended to serve high dynamic range
applications that require wide signal reconstruction bandwidth
(such as a DOCSIS cable modem termination system (CMTS))
and/or high IF/RF signal generation. Optimum ac performance
can be realized only when the DAC output is configured for
differential (that is, balanced) operation with its output commonmode voltage biased to a stable, low noise 2.5 V nominal analog
supply (VDD25_DAC).
The output network used to interface to the DAC provides a near
0 Ω dc bias path to VDD25_DAC. Any imbalance in the output
impedance over frequency between the OUTPUT+ and
OUTPUT− pins degrades the distortion performance (mostly
even order) and noise performance. Component selection and
layout are critical in realizing the performance potential of the
AD9161/AD9162.
To assist in matching the AD9161/AD9162 output, an equivalent model of the output was developed, and is shown in
Figure 192. This equivalent model includes all effects from the
ideal 40 mA current source in the die to the ball of the CSP_
BGA package, including parasitic capacitance, trace inductance
and resistance, contact resistance of solder bumps, via
inductance, and other effects.
470pH
OUTPUT–
248fF
1.14pF
470pH
OUTPUT+
3.59Ω
Figure 192. Equivalent Circuit Model of the DAC Output
A Smith chart is provided in Figure 193 showing the simulated
S11 of the DAC output, using the model in Figure 192. The plot
was taken using the circuit in Figure 192, with an ideal balun.
For the measured response of the DAC output, see Figure 191.
1.0
2.0
0.5
Most applications that require balanced to unbalanced conversion
from 10 MHz to 3 GHz can take advantage of several available
transformers that offer impedance ratios of both 2:1 and 1:1.
m1
0.2
5.0
S (1, 1)
m6
Figure 190 shows the AD9161/AD9162 interfacing to the MiniCircuits TCM1-63AX+ and the TC1-1-43X+ transformers.
m2
0
0
m5
m3
m4
MINI-CIRCUITS
TCM1-63AX+
TC1-1-43X+
OUTPUT+
179Ω
40mA
3.59Ω
14379-124
measure 4.8 dBm of actual power in the region where the sinc
response of the DAC has negligible influence and analog roll-off
has not begun. Increasing the output power is best accomplished
by increasing IOUTFS. An example of DAC output characteristics
for several balun and board types is shown in Figure 191.
–5.0
–0.2
L
50Ω
C
L
50Ω
C
14379-122
VDD25_DAC
–0.5
–1.0
FREQUENCY (10MHz TO 6GHz)
5
m1
FREQUENCY = 10MHz
S (1, 1) = 0.770/149.556
IMPEDANCE = Z0 × (0.140 + j0.267)
m4
FREQUENCY = 2GHz
S (1, 1) = 0.583/–148.777
IMPEDANCE = Z0 × (0.282 – j0.259)
0
m2
FREQUENCY = 100MHz
S (1, 1) = 0.227/163.083
IMPEDANCE = Z0 × (0.638 + j0.089)
m5
FREQUENCY = 4GHz
S (1, 1) = 0.794/–170.517
IMPEDANCE = Z0 × (0.116 – j0.082)
m3
FREQUENCY = 1GHz
S (1, 1) = 0.367/–144.722
IMPEDANCE = Z0 × (0.499 – j0.245)
m6
FREQUENCY = 6GHz
S (1, 1) = 0.779/168.448
IMPEDANCE = Z0 × (0.125 + j0.100)
–5
–10
Figure 193. Simulated Smith Chart Showing the DAC Output Impedance
–15
BAL-0006
TC1-1-43X+
TCM1-63AX+
–20
0
1
2
3
4
5
fOUT (GHz)
6
14379-123
OUTPUT POWER (dBm)
Figure 190. Recommended Transformer for Wideband Applications with
Upper Bandwidths of up to 5 GHz
–2.0
14379-125
OUTPUT–
Figure 191. Measured DAC Output Response; fDAC = 6 GSPS
Rev. 0 | Page 79 of 139
AD9161/AD9162
Data Sheet
START-UP SEQUENCE
A number of steps is required to program the AD9161/AD9162
to the proper operating state after the device is powered up. This
sequence is divided into several steps, and is listed in Table 43,
Table 44, and Table 45, along with an explanation of the purpose of
each step. Private registers are reserved but must be written for
proper operation. Blank cells in Table 43 to Table 45 mean that
the value depends on the result as described in the description
column.
The AD9161/AD9162 are calibrated at the factory as part of the
automatic test program. The configure DAC start-up sequence
loads the factory calibration coefficients, as well as configures
some parameters that optimize the performance of the DAC
and the DAC clock DLL (see Table 43). Run this sequence
whenever the DAC is powered down or reset.
The configure JESD204B sequence configures the SERDES
block and then brings up the links (see Table 44). First, run the
configure DAC start-up sequence, then run the configure
JESD204B sequence.
Follow the configure NCO sequence if using the NCO (see
Table 45). Note that the NCO can be used in NCO only mode
or in conjunction with synthesized data from the SERDES data
interface. Only one mode can be used at a time and this mode is
selected in the second step in Table 45. The configure DAC
start-up sequence is run first, then the configure NCO sequence.
Table 43. Configure DAC Start-Up Sequence After Power-Up
R/W
W
W
W
W
W
W
R
Value
0x18
0x52
0xD2
0x02
0x00
0x01
N/A 1
R
Register
0x000
0x0D2
0x0D2
0x606
0x607
0x604
0x003, 0x004, 0x005,
0x006
0x604, Bit 1
W
W
W
W
W
W
W
R
0x058
0x090
0x080
0x040
0x020
0x09E
0x091
0x092, Bit 0
0x03
0x1E
0x00
0x00
0x0F
0x85
0xE9
0b1
W
W
0x0E8
0x152, Bits[1:0]
0x20
1
0b1
Description
Configure the device for 4-wire serial port operation (optional: leave at the default of 3-wire SPI)
Reset internal calibration registers (private)
Clear the reset bit for the internal calibration registers (private)
Configure the nonvolatile random access memory (NVRAM) (private)
Configure the NVRAM (private)
Load the NVRAM. Loads factory calibration factors from the NVRAM. (private)
(Optional) read CHIP_TYPE, PROD_ID[15:0], PROD_GRADE, and DEV_REVISION from Register 0x003,
Register 0x004, Register 0x005, and Register 0x006
(Optional) read the boot loader pass bit in Register 0x604, Bit 1 = 0b1 to indicate a successful boot
load
Enable the band gap reference (private)
Power up the DAC clock DLL
Enable the clock receiver
Enable the DAC bias circuits
Optional. Enable the interrupts
Configure DAC analog parameters (private)
Enable the DAC clock DLL
Check DLL_STATUS; set Register 0x092, Bit 0 = 1 to indicate the DAC clock DLL is locked to the DAC
clock input
Enable calibration factors (private)
Configure the DAC decode mode (0b00 = NRZ, 0b01 = Mix-Mode, or 0b10 = RZ)
N/A means not applicable.
Table 44. Configure JESD204B Start-Up Sequence
R/W
W
W
W
W
W
W
W
W
W
W
W
W
Register
0x300
0x4B8
0x4B9
0x480
0x481
0x482
0x483
0x484
0x485
0x486
0x487
0x110
Value
0x00
0xFF
0x01
0x38
0x38
0x38
0x38
0x38
0x38
0x38
0x38
Description
Ensure the SERDES links are disabled before configuring them.
Enable JESD204B interrupts.
Enable JESD204B interrupts.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Enable SERDES error counters.
Configure number of lanes (Bits[7:4]) and interpolation rate (Bits[3:0]).
Rev. 0 | Page 80 of 139
Data Sheet
AD9161/AD9162
R/W
W
Register
0x111
W
W
W
W
W
W
W
W
R
0x230
0x289,
Bits[1:0]
0x084,
Bits[5:4]
0x200
0x475
0x453, Bit 7
0x458,
Bits[7:5]
0x459,
Bits[7:5]
0x45D
0x475
0x201,
Bits[7:0]
0x2A7
0x2AE
0x29E
0x206
0x206
0x280
0x281, Bit 0
0x01
0x01
0x1F
0x00
0x01
0x03
0b1
W
R
R
R
R
W
W
W
0x300
0x470
0x471
0x472
0x473
0x024
0x4BA
0x4BB
0x01
0xFF
0xFF
0xFF
0xFF
0x1F
0xFF
0x01
W
W
W
W
W
W
W
W
W
Value
Description
Configure the datapath options for Bit 7 (INVSINC_EN), Bit 6 (NCO_EN), Bit 4 (FILT_BW), Bit 2
(MODULUS_EN), Bit 1 (SEL_SIDEBAND), and Bit 0 (FIR85_FILT_EN). See the Register Summary section for
details on the options. Set the reserved bits (Bit 5 and Bit 3) to 0b0.
Configure the CDR block according to Table 20 for both half rate enable and the divider.
Set up the SERDES PLL divider based on the conditions shown in Table 19.
Set up the PLL reference clock rate based on the conditions shown in Table 19.
0x00
0x09
0b1
Enable JESD204B block (disable master SERDES power-down).
Soft reset the JESD204B quad-byte deframer.
(Optional) Enable scrambling on SERDES lanes.
Set the subclass type: 0b000 = Subclass 0, 0b001 = Subclass 1.
0b1
Set the JESD204x version to JESD204B.
0x01
Program the calculated checksum value for Lane 0 from values in Register 0x450 to Register 0x45C.
Bring the JESD204B quad-byte deframer out of reset.
Set any bits to 1 to power down the appropriate physical lane.
(Optional) Calibrate SERDES PHY Termination Block 1 (PHY 0, PHY 1, PHY 6, PHY 7).
(Optional) Calibrate SERDES PHY Termination Block 2 (PHY 2, PHY 3, PHY 4, PHY 5).
Override defaults in the SERDES PLL settings (private).
Reset the CDR.
Enable the CDR.
Enable the SERDES PLL.
Read back Register 0x281 until Bit 0 = 1 to indicate the SERDES PLL is locked. Prior to enabling the links, be
sure that the JESD204B transmitter is enabled and ready to begin bringing up the link.
Enable SERDES links (begin bringing up the link).
Read the CGS status for all lanes.
Read the frame sync status for all lanes.
Read the good checksum status for all lanes.
Read the initial lane sync status for all lanes.
Clear the interrupts.
Clear the SERDES interrupts.
Clear the SERDES interrupt.
Table 45. Configure NCO Sequence
R/W
W
W
Register
0x110
0x111, Bit 6
W
W
W
W
W
W
W
W
W
W
W
0x150, Bit 1
0x14E
0x14F
0x113
0x119
0x118
0x117
0x116
0x115
0x114
0x113
Value
0x80
0b1
0x00
0x01
Description
(Optional) Perform this write if NCO only mode is desired (AD9162 only).
Configure NCO_EN (Bit 6) = 0b1. Configure other datapath options for Bit 7 (INVSINC_EN), Bit 4 (FILT_BW),
Bit 2 (MODULUS_EN), Bit 1 (SEL_SIDEBAND), and Bit 0 (FIR85_FILT_EN). See the Register Summary section
for details on the options. Set the reserved bits (Bit 5 and Bit 3) to 0b0.
Configure the DC_TEST_EN bit: 0b0 = NCO operation with data interface; 0b1 = NCO only mode (AD9162 only).
Write the amplitude value for tone amplitude in NCO only mode, Bits [15:8] (AD9162 only).
Write the amplitude value for tone amplitude in NCO only mode, Bits [7:0] (AD9162 only).
Ensure the frequency tuning word write request is low.
Write FTW, Bits[47:40].
Write FTW, Bits[39:32].
Write FTW, Bits[31:24].
Write FTW, Bits[23:16].
Write FTW, Bits[15:8].
Write FTW, Bits[7:0].
Load the FTW to the NCO.
Rev. 0 | Page 81 of 139
AD9161/AD9162
Data Sheet
REGISTER SUMMARY
Table 46. Register Summary
Reg.
Name
Bits
Bit 7
Bit 6
Bit 5
Bit 4
0x000
SPI_INTFCONFA
[7:0]
SOFTRESET_
M
LSBFIRST_M
ADDRINC_M
SDOACTIVE_ SDOACTIVE
M
Bit 3
0x001
SPI_INTFCONFB
[7:0]
SINGLEINS
CSSTALL
0x002
SPI_DEVCONF
[7:0]
0x003
SPI_CHIPTYPE
[7:0]
CHIP_TYPE
0x00 R
0x004
SPI_PRODIDL
[7:0]
PROD_ID[7:0]
0x00 R
0x005
SPI_PRODIDH
[7:0]
0x006
SPI_CHIPGRADE
[7:0]
0x020
IRQ_ENABLE
[7:0]
RESERVED
EN_SYSREF_
JITTER
0x024
IRQ_STATUS
[7:0]
RESERVED
IRQ_SYSREF_ IRQ_DATA_
JITTER
READY
0x031
SYNC_LMFC_
DELAY_FRAME
[7:0]
RESERVED
0x032
SYNC_LMFC_
DELAY0
[7:0]
0x033
SYNC_LMFC_
DELAY1
[7:0]
0x034
SYNC_LMFC_
STAT0
[7:0]
0x035
SYNC_LMFC_
STAT1
[7:0]
0x036
SYSREF_COUNT
[7:0]
SYSREF_COUNT
0x00 R/W
0x037
SYSREF_PHASE0
[7:0]
SYSREF_PHASE[7:0]
0x00 R/W
RESERVED
DEVSTATUS
Bit 2
Bit 1
Bit 0
Reset RW
ADDRINC
LSBFIRST
SOFTRESET
0x00 R/W
SOFTRESET1
SOFTRESET0
RESERVED
0x00 R/W
CUSTOPMODE
SYSOPMODE
PROD_ID[15:8]
0x00 R
PROD_GRADE
DEV_REVISION
EN_DATA_
READY
0x00 R
EN_LANE_FIFO EN_PRBSQ
EN_PRBSI
0x00 R/W
IRQ_LANE_
FIFO
IRQ_PRBSI
0x00 R/W
IRQ_PRBSQ
SYNC_LMFC_DELAY_SET_FRM
0x00 R/W
SYNC_LMFC_DELAY_SET[7:0]
0x00 R/W
RESERVED
SYNC_LMFC_DELAY_SET[11:8]
SYNC_LMFC_DELAY_STAT[7:0]
RESERVED
SYSREF_PHASE1
[7:0]
0x039
SYSREF_JITTER_
WINDOW
[7:0]
RESERVED
SYSREF_PHASE[11:8]
0x03A
SYNC_CTRL
[7:0]
0x03F
TX_ENABLE
[7:0]
0x040
ANA_DAC_BIAS_
PD
[7:0]
RESERVED
0x041
ANA_FSC0
[7:0]
RESERVED
0x042
ANA_FSC1
[7:0]
0x07F
CLK_PHASE_TUNE [7:0]
0x080
CLK_PD
[7:0]
0x082
CLK_DUTY
[7:0]
CLK_DUTY_
EN
0x083
CLK_CRS_CTRL
[7:0]
CLK_CRS_EN
0x084
PLL_REF_CLK_PD [7:0]
0x088
SYSREF_CTRL0
[7:0]
0x089
SYSREF_CTRL1
[7:0]
0x090
DLL_PD
[7:0]
0x091
DLL_CTRL
[7:0]
0x092
DLL_STATUS
[7:0]
0x093
DLL_GB
[7:0]
0x094
DLL_COARSE
[7:0]
0x095
DLL_FINE
[7:0]
0x096
DLL_PHASE
[7:0]
RESERVED
0x097
DLL_BW
[7:0]
RESERVED
RESERVED
SPI_
DATAPATH_
PRE
0x00 R/W
SYNC_MODE
RESERVED
TXEN_NCO_ TXEN_
DATAPATH_
RESET
POST
TXEN_DAC_FSC
0xC0 R/W
ANA_DAC_
BIAS_PD1
ANA_DAC_BIAS_
PD0
0x03 R/W
ANA_FULL_SCALE_CURRENT[1:0] 0x03 R/W
RESERVED
0xFF R/W
CLK_PHASE_TUNE
0x00 R/W
RESERVED
DACCLK_PD
CLK_DUTY_
BOOST_EN
CLK_DUTY_PRG
RESERVED
RESERVED
0x80 R/W
RESERVED
RESERVED
HYS_ON
PLL_REF_CLK_PD
SYSREF_RISE
HYS_CNTRL[9:8]
HYS_CNTRL[7:0]
DLL_FINE_
DC_EN
DLL_TRACK_ DLL_SEARCH_ DLL_SLOPE
ERR
ERR
DLL_FINE_
XC_EN
DLL_COARSE_
DC_EN
DLL_COARSE_ DLL_CLK_PD
XC_EN
DLL_MODE
DLL_FAIL
RESERVED
DLL_LOST
DLL_LOCKED
0x00 R/W
0x00 R/W
DLL_COARSE
0x00 R/W
0x80 R/W
DLL_PHS
DLL_FILT_BW
0x1F R/W
0xF0 R/W
DLL_FINE
Rev. 0 | Page 82 of 139
0x00 R/W
DLL_ENABLE
DLL_GUARD
RESERVED
0x00 R/W
0x00 R/W
DLL_SEARCH
RESERVED
0x01 R/W
0x80 R/W
CLK_CRS_ADJ
PLL_REF_CLK_RATE
RESERVED
0x00 R/W
TXEN_
DATAPATH_
PRE
ANA_FULL_SCALE_CURRENT[9:2]
CLK_DUTY_
OFFSET_EN
0x00 R/W
0x00 R/W
SYSREF_JITTER_WINDOW
RESERVED
SPI_
DATAPATH_
POST
0x00 R/W
0x00 R/W
SYNC_LMFC_DELAY_STAT[11:8]
0x038
0x00 R/W
0x08 R/W
DLL_WEIGHT
0x00 R/W
Data Sheet
AD9161/AD9162
Reg.
Name
Bits
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
Bit 0
0x098
DLL_READ
[7:0]
0x099
DLL_COARSE_RB
[7:0]
0x09A
DLL_FINE_RB
[7:0]
0x09B
DLL_PHASE_RB
[7:0]
0x09D
DIG_CLK_INVERT
[7:0]
0x0A0
DLL_CLK_DEBUG
[7:0]
0x110
INTERP_MODE
[7:0]
0x111
DATAPATH_CFG
[7:0]
INVSINC_EN
0x113
FTW_UPDATE
[7:0]
RESERVED
0x114
FTW0
[7:0]
FTW[7:0]
0x00 R/W
0x115
FTW1
[7:0]
FTW[15:8]
0x00 R/W
0x116
FTW2
[7:0]
FTW[23:16]
0x00 R/W
0x117
FTW3
[7:0]
FTW[31:24]
0x00 R/W
0x118
FTW4
[7:0]
FTW[39:32]
0x00 R/W
0x119
FTW5
[7:0]
FTW[47:40]
0x00 R/W
0x11C
PHASE_OFFSET0
[7:0]
NCO_PHASE_OFFSET[7:0]
0x00 R/W
0x11D
PHASE_OFFSET1
[7:0]
NCO_PHASE_OFFSET[15:8]
0x00 R/W
0x124
ACC_MODULUS0
[7:0]
ACC_MODULUS[7:0]
0x00 R/W
0x125
ACC_MODULUS1
[7:0]
ACC_MODULUS[15:8]
0x00 R/W
0x126
ACC_MODULUS2
[7:0]
ACC_MODULUS[23:16]
0x00 R/W
0x127
ACC_MODULUS3
[7:0]
ACC_MODULUS[31:24]
0x00 R/W
0x128
ACC_MODULUS4
[7:0]
ACC_MODULUS[39:32]
0x00 R/W
0x129
ACC_MODULUS5
[7:0]
ACC_MODULUS[47:40]
0x00 R/W
0x12A
ACC_DELTA0
[7:0]
ACC_DELTA[7:0]
0x00 R/W
0x12B
ACC_DELTA1
[7:0]
ACC_DELTA[15:8]
0x00 R/W
0x12C
ACC_DELTA2
[7:0]
ACC_DELTA[23:16]
0x00 R/W
0x12D
ACC_DELTA3
[7:0]
ACC_DELTA[31:24]
0x00 R/W
0x12E
ACC_DELTA4
[7:0]
ACC_DELTA[39:32]
0x00 R/W
0x12F
ACC_DELTA5
[7:0]
ACC_DELTA[47:40]
0x14B
PRBS
[7:0]
0x14C
PRBS_ERROR_I
[7:0]
PRBS_COUNT_I
0x14D
PRBS_ERROR_Q
[7:0]
PRBS_COUNT_Q
0x14E
TEST_DC_DATA1
[7:0]
DC_TEST_DATA[15:8]
0x14F
TEST_DC_DATA0
[7:0]
0x150
DIG_TEST
[7:0]
0x151
DECODE_CTRL
[7:0]
0x152
DECODE_MODE
[7:0]
0x1DF
SPI_STRENGTH
[7:0]
0x200
MASTER_PD
[7:0]
0x201
PHY_PD
[7:0]
0x203
GENERIC_PD
[7:0]
0x206
CDR_RESET
[7:0]
0x230
CDR_OPERATING_ [7:0]
MODE_REG_0
0x250
EQ_CONFIG_PHY_ [7:0]
0_1
SPI_EQ_CONFIG1
SPI_EQ_CONFIG0
0x88 R/W
0x251
EQ_CONFIG_PHY_ [7:0]
2_3
SPI_EQ_CONFIG3
SPI_EQ_CONFIG2
0x88 R/W
0x252
EQ_CONFIG_PHY_ [7:0]
4_5
SPI_EQ_CONFIG5
SPI_EQ_CONFIG4
0x88 R/W
RESERVED
DLL_READ
RESERVED
DLL_COARSE_RB
0x00 R
DLL_PHS_RB
DLL_TEST_EN
INV_DIG_CLK
0x00 R
DIG_CLK_DC_
EN
RESERVED
DIG_CLK_XC_EN
DLL_TEST_DIV
JESD_LANES
NCO_EN
INTERP_MODE
RESERVED
FILT_BW
FTW_REQ_MODE
PRBS_GOOD_ PRBS_GOOD_I RESERVED
Q
0x00 R/W
0x81 R/W
MODULUS_EN
SEL_SIDEBAND FIR85_FILT_EN
0x00 R/W
RESERVED
FTW_LOAD_
SYSREF
FTW_LOAD_
ACK
0x00 R/W
PRBS_INV_Q PRBS_INV_I
FTW_LOAD_REQ
0x00 R/W
PRBS_MODE
PRBS_RESET
PRBS_EN
0x00 R
0x00 R/W
0x00 R/W
DC_TEST_EN
RESERVED
SHUFFLE
RESERVED
RESERVED
RESERVED
RESERVED
0x01 R/W
0x00 R/W
SPIDRV
0x0F R/W
SPI_PD_MASTER
SPI_PD_PHY
RESERVED
Rev. 0 | Page 83 of 139
0x01 R/W
0x00 R/W
SPI_SYNC1_PD RESERVED
RESERVED
0x00 R/W
DECODE_MODE
RESERVED
RESERVED
0x10 R/W
0x00 R
DC_TEST_DATA[7:0]
SPI_
ENHALFRATE
0x03 R/W
RESERVED
RESERVED
RESERVED
0x00 R/W
0x00 R
DLL_FINE_RB
RESERVED
RESERVED
Reset RW
SPI_DIVISION_RATE
0x00 R/W
SPI_CDR_RESET
0x01 R/W
RESERVED
0x28 R/W
AD9161/AD9162
Bits
Data Sheet
Reg.
Name
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
0x253
EQ_CONFIG_PHY_ [7:0]
6_7
0x268
EQ_BIAS_REG
[7:0]
0x280
SYNTH_ENABLE_
CNTRL
[7:0]
0x281
PLL_STATUS
[7:0]
0x289
REF_CLK_
DIVIDER_LDO
[7:0]
0x2A7
TERM_BLK1_
CTRLREG0
[7:0]
0x2A8
TERM_BLK1_
CTRLREG1
[7:0]
0x2AC
TERM_BLK1_RD_
REG0
[7:0]
0x2AE
TERM_BLK2_
CTRLREG0
[7:0]
0x2AF
TERM_BLK2_
CTRLREG1
[7:0]
0x2B3
TERM_BLK2_RD_
REG0
[7:0]
0x2BB
TERM_OFFSET_0
[7:0]
RESERVED
TERM_OFFSET_0
0x00 R/W
0x2BC
TERM_OFFSET_1
[7:0]
RESERVED
TERM_OFFSET_1
0x00 R/W
0x2BD
TERM_OFFSET_2
[7:0]
RESERVED
TERM_OFFSET_2
0x00 R/W
0x2BE
TERM_OFFSET_3
[7:0]
RESERVED
TERM_OFFSET_3
0x00 R/W
0x2BF
TERM_OFFSET_4
[7:0]
RESERVED
TERM_OFFSET_4
0x00 R/W
0x2C0
TERM_OFFSET_5
[7:0]
RESERVED
TERM_OFFSET_5
0x00 R/W
0x2C1
TERM_OFFSET_6
[7:0]
RESERVED
TERM_OFFSET_6
0x00 R/W
0x2C2
TERM_OFFSET_7
[7:0]
0x300
GENERAL_JRX_
CTRL_0
[7:0]
0x302
DYN_LINK_
LATENCY_0
[7:0]
RESERVED
DYN_LINK_LATENCY_0
0x304
LMFC_DELAY_0
[7:0]
RESERVED
LMFC_DELAY_0
0x00 R/W
0x306
LMFC_VAR_0
[7:0]
RESERVED
LMFC_VAR_0
0x1F R/W
0x308
XBAR_LN_0_1
[7:0]
RESERVED
SRC_LANE1
SRC_LANE0
0x08 R/W
0x309
XBAR_LN_2_3
[7:0]
RESERVED
SRC_LANE3
SRC_LANE2
0x1A R/W
0x30A
XBAR_LN_4_5
[7:0]
RESERVED
SRC_LANE5
SRC_LANE4
0x2C R/W
0x30B
XBAR_LN_6_7
[7:0]
RESERVED
SRC_LANE7
SRC_LANE6
0x3E R/W
0x30C
FIFO_STATUS_
REG_0
[7:0]
LANE_FIFO_FULL
0x00 R
0x30D
FIFO_STATUS_
REG_1
[7:0]
LANE_FIFO_EMPTY
0x00 R
0x311
SYNC_GEN_0
[7:0]
0x312
SYNC_GEN_1
[7:0]
0x313
SYNC_GEN_3
[7:0]
LMFC_PERIOD
0x00 R
0x315
PHY_PRBS_TEST_ [7:0]
EN
PHY_TEST_EN
0x00 R/W
0x316
PHY_PRBS_TEST_ [7:0]
CTRL
0x317
PHY_PRBS_TEST_ [7:0]
THRESHOLD_
LOBITS
PHY_PRBS_THRESHOLD_LOBITS
0x00 R/W
0x318
PHY_PRBS_TEST_ [7:0]
THRESHOLD_
MIDBITS
PHY_PRBS_THRESHOLD_MIDBITS
0x00 R/W
SPI_EQ_CONFIG7
Bit 0
SPI_EQ_CONFIG6
EQ_POWER_MODE
0x88 R/W
RESERVED
RESERVED
RESERVED
SPI_CP_
OVER_
RANGE_
HIGH_RB
0x62 R/W
SPI_RECAL_
SYNTH
SPI_CP_
OVER_
RANGE_
LOW_RB
SPI_CP_
CAL_VALID_
RB
RESERVED
RESERVED
RESERVED
SPI_ENABLE_
SYNTH
RESERVED
SPI_I_TUNE_R_
CAL_TERMBLK1
SPI_I_SERIALIZER_RTRIM_TERMBLK1
RESERVED
SPI_I_TUNE_R_
CAL_TERMBLK2
SPI_I_SERIALIZER_RTRIM_TERMBLK2
RESERVED
RESERVED
RESERVED
PHY_SRC_ERR_CNT
EOMF_MASK_0 RESERVED
Rev. 0 | Page 84 of 139
PHY_TEST_
START
0x00 R/W
0x00 R
EOF_MASK_0
0x00 R/W
0x00 R/W
SYNC_SYNCREQ_DUR
PHY_PRBS_PAT_SEL
0x00 R/W
0x00 R/W
LINK_EN
SYNC_ERR_DUR
0x00 R
0x00 R
TERM_OFFSET_7
CHECKSUM_
MODE
0x00 R/W
0x00 R/W
SPI_O_RCAL_CODE_TERMBLK2
RESERVED
RESERVED
0x04 R/W
0x00 R/W
SPI_O_RCAL_CODE_TERMBLK1
RESERVED
0x00 R/W
SPI_PLL_LOCK_RB 0x00 R
SERDES_PLL_DIV_FACTOR
RESERVED
Reset RW
PHY_TEST_RESET
0x00 R/W
Data Sheet
AD9161/AD9162
Reg.
Name
Bits
Bit 7
0x319
PHY_PRBS_TEST_ [7:0]
THRESHOLD_
HIBITS
PHY_PRBS_THRESHOLD_HIBITS
0x31A
PHY_PRBS_TEST_ [7:0]
ERRCNT_LOBITS
PHY_PRBS_ERR_CNT_LOBITS
0x00 R
0x31B
PHY_PRBS_TEST_ [7:0]
ERRCNT_MIDBITS
PHY_PRBS_ERR_CNT_MIDBITS
0x00 R
0x31C
PHY_PRBS_TEST_ [7:0]
ERRCNT_HIBITS
PHY_PRBS_ERR_CNT_HIBITS
0x00 R
0x31D
PHY_PRBS_TEST_ [7:0]
STATUS
PHY_PRBS_PASS
0xFF R
0x31E
PHY_DATA_
SNAPSHOT_CTRL
0x31F
PHY_SNAPSHOT_ [7:0]
DATA_BYTE0
PHY_SNAPSHOT_DATA_BYTE0
0x00 R
0x320
PHY_SNAPSHOT_ [7:0]
DATA_BYTE1
PHY_SNAPSHOT_DATA_BYTE1
0x00 R
0x321
PHY_SNAPSHOT_ [7:0]
DATA_BYTE2
PHY_SNAPSHOT_DATA_BYTE2
0x00 R
0x322
PHY_SNAPSHOT_ [7:0]
DATA_BYTE3
PHY_SNAPSHOT_DATA_BYTE3
0x00 R
0x323
PHY_SNAPSHOT_ [7:0]
DATA_BYTE4
PHY_SNAPSHOT_DATA_BYTE4
0x00 R
0x32C
SHORT_TPL_
TEST_0
[7:0]
0x32D
SHORT_TPL_
TEST_1
[7:0]
SHORT_TPL_REF_SP_LSB
0x00 R/W
0x32E
SHORT_TPL_
TEST_2
[7:0]
SHORT_TPL_REF_SP_MSB
0x00 R/W
0x32F
SHORT_TPL_
TEST_3
[7:0]
0x334
JESD_BIT_
INVERSE_CTRL
[7:0]
JESD_BIT_INVERSE
0x400
DID_REG
[7:0]
DID_RD
0x00 R
0x401
BID_REG
[7:0]
BID_RD
0x00 R
0x402
LID0_REG
[7:0]
RESERVED
0x403
SCR_L_REG
[7:0]
SCR_RD
0x404
F_REG
[7:0]
0x405
K_REG
[7:0]
0x406
M_REG
[7:0]
0x407
CS_N_REG
[7:0]
0x408
NP_REG
[7:0]
SUBCLASSV_RD
NP_RD
0x00 R
0x409
S_REG
[7:0]
JESDV_RD
S_RD
0x00 R
0x40A
HD_CF_REG
[7:0]
CF_RD
0x00 R
0x40B
RES1_REG
[7:0]
RES1_RD
0x00 R
0x40C
RES2_REG
[7:0]
RES2_RD
0x00 R
0x40D
CHECKSUM0_REG [7:0]
LL_FCHK0
0x00 R
0x40E
COMPSUM0_REG [7:0]
LL_FCMP0
0x00 R
0x412
LID1_REG
0x415
CHECKSUM1_REG [7:0]
0x416
COMPSUM1_REG [7:0]
0x41A
LID2_REG
0x41D
CHECKSUM2_REG [7:0]
0x41E
COMPSUM2_REG [7:0]
0x422
LID3_REG
0x425
CHECKSUM3_REG [7:0]
LL_FCHK3
0x00 R
0x426
COMPSUM3_REG [7:0]
LL_FCMP3
0x00 R
[7:0]
[7:0]
[7:0]
[7:0]
Bit 6
Bit 5
Bit 4
RESERVED
Bit 3
Bit 2
Bit 1
PHY_GRAB_
MODE
SHORT_TPL_M_SEL
RESERVED
ADJDIR_RD
PHADJ_RD
LL_LID0
L_RD
RESERVED
K_RD
RESERVED
RESERVED
LL_LID1
LL_FCHK1
LL_FCHK2
0x00 R
0x00 R
0x00 R
0x00 R
LL_FCMP2
0x00 R
LL_LID3
Rev. 0 | Page 85 of 139
0x00 R
0x00 R
LL_LID2
RESERVED
0x00 R
0x00 R
LL_FCMP1
RESERVED
0x00 R
0x00 R
N_RD
RESERVED
0x00 R
0x00 R
M_RD
HD_RD
SHORT_TPL_TEST_ 0x00 R/W
EN
0x00 R/W
F_RD
CS_RD
SHORT_TPL_
TEST_RESET
PHY_GRAB_DATA 0x00 R/W
SHORT_TPL_FAIL
RESERVED
Reset RW
0x00 R/W
PHY_GRAB_LANE_SEL
SHORT_TPL_SP_SEL
Bit 0
0x00 R
AD9161/AD9162
Data Sheet
Reg.
Name
Bits
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
0x42A
LID4_REG
[7:0]
0x42D
CHECKSUM4_REG [7:0]
0x42E
COMPSUM4_REG [7:0]
0x432
LID5_REG
0x435
CHECKSUM5_REG [7:0]
LL_FCHK5
0x436
COMPSUM5_REG [7:0]
LL_FCMP5
0x43A
LID6_REG
0x43D
CHECKSUM6_REG [7:0]
0x43E
COMPSUM6_REG [7:0]
0x442
LID7_REG
0x445
CHECKSUM7_REG [7:0]
LL_FCHK7
0x00 R
0x446
COMPSUM7_REG [7:0]
LL_FCMP7
0x00 R
0x450
ILS_DID
[7:0]
0x451
ILS_BID
[7:0]
0x452
ILS_LID0
[7:0]
RESERVED
0x453
ILS_SCR_L
[7:0]
SCR
0x454
ILS_F
[7:0]
0x455
ILS_K
[7:0]
0x456
ILS_M
[7:0]
0x457
ILS_CS_N
[7:0]
0x458
ILS_NP
[7:0]
0x459
ILS_S
[7:0]
0x45A
ILS_HD_CF
[7:0]
0x45B
ILS_RES1
[7:0]
0x45C
ILS_RES2
[7:0]
RES2
0x00 R/W
0x45D
ILS_CHECKSUM
[7:0]
FCHK0
0x00 R/W
0x46C
LANE_DESKEW
[7:0]
ILD7
ILS6
ILD5
ILD4
ILD3
ILD2
ILD1
ILD0
0x00 R
0x46D
BAD_DISPARITY
[7:0]
BDE7
BDE6
BDE5
BDE4
BDE3
BDE2
BDE1
BDE0
0x00 R
0x46E
NOT_IN_TABLE
[7:0]
NIT7
NIT6
NIT5
NIT4
NIT3
NIT2
NIT1
NIT0
0x00 R
0x46F
UNEXPECTED_
KCHAR
[7:0]
UEK7
UEK6
UEK5
UEK4
UEK3
UEK2
UEK1
UEK0
0x00 R
0x470
CODE_GRP_SYNC [7:0]
CGS7
CGS6
CGS5
CGS4
CGS3
CGS2
CGS1
CGS0
0x00 R
0x471
FRAME_SYNC
[7:0]
FS7
FS6
FS5
FS4
FS3
FS2
FS1
FS0
0x00 R
0x472
GOOD_
CHECKSUM
[7:0]
CKS7
CKS6
CKS5
CKS4
CKS3
CKS2
CKS1
CKS0
0x00 R
0x473
INIT_LANE_SYNC
[7:0]
ILS7
ILS6
ILS5
ILS4
ILS3
ILS2
ILS1
ILS0
0x00 R
0x475
CTRLREG0
[7:0]
RX_DIS
CHAR_REPL_
DIS
SOFTRST
FORCESYNCREQ RESERVED
REPL_FRM_ENA
0x01 R/W
0x476
CTRLREG1
[7:0]
CGS_SEL
FCHK_N
0x477
CTRLREG2
[7:0]
ILS_MODE
RESERVED
0x478
KVAL
[7:0]
KSYNC
0x01 R/W
0x47C
ERRORTHRES
[7:0]
ETH
0xFF R/W
0x47D
SYNC_ASSERT_
MASK
[7:0]
0x480
ECNT_CTRL0
[7:0]
RESERVED
ECNT_ENA0
ECNT_RST0
0x3F R/W
0x481
ECNT_CTRL1
[7:0]
RESERVED
ECNT_ENA1
ECNT_RST1
0x3F R/W
0x482
ECNT_CTRL2
[7:0]
RESERVED
ECNT_ENA2
ECNT_RST2
0x3F R/W
0x483
ECNT_CTRL3
[7:0]
RESERVED
ECNT_ENA3
ECNT_RST3
0x3F R/W
0x484
ECNT_CTRL4
[7:0]
RESERVED
ECNT_ENA4
ECNT_RST4
0x3F R/W
0x485
ECNT_CTRL5
[7:0]
RESERVED
ECNT_ENA5
ECNT_RST5
0x3F R/W
0x486
ECNT_CTRL6
[7:0]
RESERVED
ECNT_ENA6
ECNT_RST6
0x3F R/W
0x487
ECNT_CTRL7
[7:0]
RESERVED
ECNT_ENA7
ECNT_RST7
0x3F R/W
RESERVED
Bit 1
Bit 0
LL_LID4
0x00 R
LL_FCHK4
0x00 R
LL_FCMP4
[7:0]
0x00 R
RESERVED
[7:0]
LL_LID5
0x00 R
0x00 R
0x00 R
RESERVED
LL_LID6
0x00 R
LL_FCHK6
0x00 R
LL_FCMP6
[7:0]
0x00 R
RESERVED
LL_LID7
0x00 R
DID
0x00 R/W
BID
ADJDIR
0x00 R/W
PHADJ
RESERVED
LID0
0x00 R/W
L
0x87 R/W
F
0x00 R
RESERVED
K
0x1F R/W
M
CS
0x01 R
RESERVED
SUBCLASSV
JESDV
HD
RESERVED
N
0x0F R
NP
0x0F R/W
S
0x01 R/W
CF
0x80 R
RES1
RESERVED
RESERVED
QUAL_RDERR DEL_SCR
REPDATATEST QUETESTERR AR_ECNTR
RESERVED
0x00 R/W
NO_ILAS
RESERVED
SYNC_ASSERT_MASK
Rev. 0 | Page 86 of 139
Reset RW
0x14 R/W
0x00 R/W
0x07 R/W
Data Sheet
AD9161/AD9162
Reg.
Name
Bits
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
0x488
ECNT_TCH0
[7:0]
RESERVED
ECNT_TCH0
0x07 R/W
0x489
ECNT_TCH1
[7:0]
RESERVED
ECNT_TCH1
0x07 R/W
0x48A
ECNT_TCH2
[7:0]
RESERVED
ECNT_TCH2
0x07 R/W
0x48B
ECNT_TCH3
[7:0]
RESERVED
ECNT_TCH3
0x07 R/W
0x48C
ECNT_TCH4
[7:0]
RESERVED
ECNT_TCH4
0x07 R/W
0x48D
ECNT_TCH5
[7:0]
RESERVED
ECNT_TCH5
0x07 R/W
0x48E
ECNT_TCH6
[7:0]
RESERVED
ECNT_TCH6
0x07 R/W
0x48F
ECNT_TCH7
[7:0]
RESERVED
ECNT_TCH7
0x07 R/W
0x490
ECNT_STAT0
[7:0]
RESERVED
LANE_ENA0
ECNT_TCR0
0x00 R
0x491
ECNT_STAT1
[7:0]
RESERVED
LANE_ENA1
ECNT_TCR1
0x00 R
0x492
ECNT_STAT2
[7:0]
RESERVED
LANE_ENA2
ECNT_TCR2
0x00 R
0x493
ECNT_STAT3
[7:0]
RESERVED
LANE_ENA3
ECNT_TCR3
0x00 R
0x494
ECNT_STAT4
[7:0]
RESERVED
LANE_ENA4
ECNT_TCR4
0x00 R
0x495
ECNT_STAT5
[7:0]
RESERVED
LANE_ENA5
ECNT_TCR5
0x00 R
0x496
ECNT_STAT6
[7:0]
RESERVED
LANE_ENA6
ECNT_TCR6
0x00 R
0x497
ECNT_STAT7
[7:0]
RESERVED
LANE_ENA7
ECNT_TCR7
0x4B0
LINK_STATUS0
[7:0]
BDE0
NIT0
UEK0
ILD0
ILS0
CKS0
FS0
CGS0
0x00 R
0x4B1
LINK_STATUS1
[7:0]
BDE1
NIT1
UEK1
ILD1
ILS1
CKS1
FS1
CGS1
0x00 R
0x4B2
LINK_STATUS2
[7:0]
BDE2
NIT2
UEK2
ILD2
ILS2
CKS2
FS2
CGS2
0x00 R
0x4B3
LINK_STATUS3
[7:0]
BDE3
NIT3
UEK3
ILD3
ILS3
CKS3
FS3
CGS3
0x00 R
0x4B4
LINK_STATUS4
[7:0]
BDE4
NIT4
UEK4
ILD4
ILS4
CKS4
FS4
CGS4
0x00 R
0x4B5
LINK_STATUS5
[7:0]
BDE5
NIT5
UEK5
ILD5
ILS5
CKS5
FS5
CGS5
0x00 R
0x4B6
LINK_STATUS6
[7:0]
BDE6
NIT6
UEK6
ILD6
ILS6
CKS6
FS6
CGS6
0x00 R
0x4B7
LINK_STATUS7
[7:0]
BDE7
NIT7
UEK7
ILD7
ILS7
CKS7
FS7
CGS7
0x00 R
0x4B8
JESD_IRQ_
ENABLEA
[7:0]
EN_BDE
EN_NIT
EN_UEK
EN_ILD
EN_ILS
EN_CKS
EN_FS
EN_CGS
0x00 R/W
0x4B9
JESD_IRQ_
ENABLEB
[7:0]
EN_ILAS
0x00 R/W
0x4BA
JESD_IRQ_
STATUSA
[7:0]
IRQ_CGS
0x00 R/W
0x4BB
JESD_IRQ_
STATUSB
[7:0]
IRQ_ILAS
0x00 R/W
0x800
HOPF_CTRL
[7:0]
RESERVED
IRQ_BDE
IRQ_NIT
IRQ_UEK
IRQ_ILD
IRQ_ILS
IRQ_CKS
RESERVED
HOPF_MODE
RESERVED
Rev. 0 | Page 87 of 139
IRQ_FS
Bit 0
Reset RW
0x00 R
0x00 R/W
AD9161/AD9162
Data Sheet
REGISTER DETAILS
Table 47. Register Details
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x000 SPI_INTFCONFA
7
SOFTRESET_M
Soft reset (mirror). Set this to
mirror Bit 0.
0x0
R
6
LSBFIRST_M
LSB first (mirror). Set this to
mirror Bit 1.
0x0
R
5
ADDRINC_M
Addr increment (mirror). Set this
to mirror Bit 2.
0x0
R
4
SDOACTIVE_M
SDO active (mirror). Set this to
mirror Bit 3.
0x0
R
3
SDOACTIVE
SDO active. Enables 4-wire SPI
bus mode.
0x0
R/W
2
ADDRINC
0x0
R/W
1
LSBFIRST
LSB first. When set, causes input 0x0
and output data to be oriented
as LSB first. If this bit is clear, data
is oriented as MSB first.
R/W
Settings
Address increment. When set,
causes incrementing streaming
addresses; otherwise,
descending addresses are
generated.
1 Streaming addresses are
incremented.
0 Streaming addresses are
decremented.
1 Shift LSB in first.
0 Shift MSB in first.
0x001 SPI_INTFCONFB
0
SOFTRESET
Soft reset. This bit automatically
clears to 0 after performing a
reset operation. Setting this bit
initiates a reset. This bit is
autoclearing after the soft reset
is complete.
1 Pulse the soft reset line.
0 Reset the soft reset line.
0x0
R/W
7
SINGLEINS
Single instruction.
1 Perform single transfers.
0x0
R/W
6
CSSTALL
0x0
R/W
0x0
R/W
0x0
R/W
0x0
R/W
0 Perform multiple transfers.
CS stalling.
0 Disable CS stalling.
1 Enable CS stalling.
[5:3] RESERVED
Reserved.
2
SOFTRESET1
1
SOFTRESET0
0
RESERVED
Soft Reset 1. This bit
automatically clears to 0 after
performing a reset operation.
1 Pulse the Soft Reset 1 line.
0 Pulse the Soft Reset 1 line.
Soft Reset 0. This bit
automatically clears to 0 after
performing a reset operation.
1 Pulse the Soft Reset 0 line.
0 Pulse the Soft Reset 0 line.
0x002 SPI_DEVCONF
Reserved.
0x0
R
[7:4] DEVSTATUS
Device status.
0x0
R/W
[3:2] CUSTOPMODE
Customer operating mode.
0x0
R/W
Rev. 0 | Page 88 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[1:0] SYSOPMODE
Description
System operating mode.
0 Normal operation.
1 Low power operation.
Reset Access
0x0
R/W
2 Medium power standby.
3 Low power sleep.
0x003 SPI_CHIPTYPE
[7:0] CHIP_TYPE
Chip type.
0x0
R
0x004 SPI_PRODIDL
[7:0] PROD_ID[7:0]
Product ID.
0x0
R
0x005 SPI_PRODIDH
[7:0] PROD_ID[15:8]
Product ID.
0x0
R
0x006 SPI_CHIPGRADE
[7:4] PROD_GRADE
Product grade.
0x0
R
[3:0] DEV_REVISION
Device revision.
0x0
R
[7:5] RESERVED
Reserved.
0x0
R
0x020 IRQ_ENABLE
4
EN_SYSREF_JITTER
Enable SYSREF± jitter interrupt.
0 Disable interrupt.
1 Enable interrupt.
0x0
R/W
3
EN_DATA_READY
Enable JESD204x receiver ready
(JRX_DATA_READY) low
interrupt
0 Disable interrupt.
1 Enable interrupt.
0x0
R/W
2
EN_LANE_FIFO
0x0
R/W
0x0
R/W
0x0
R/W
Enable lane FIFO overflow/
underflow interrupt.
0 Disable interrupt.
1 Enable interrupt.
1
EN_PRBSQ
0
EN_PRBSI
Enable PRBS imaginary error
interrupt.
0 Disable interrupt.
1 Enable interrupt.
Enable PRBS real error interrupt
0 Disable interrupt.
1 Enable interrupt.
0x024 IRQ_STATUS
[7:5] RESERVED
Reserved.
0x0
R
4
IRQ_SYSREF_JITTER
SYSREF± jitter is too big. Writing
1 clears the status.
0x0
R/W
3
IRQ_DATA_READY
JRX_DATA_READY is low. Writing 0x0
1 clears the status.
R/W
0 No warning.
1 Warning detected.
2
IRQ_LANE_FIFO
1
IRQ_PRBSQ
0
IRQ_PRBSI
Lane FIFO overflow/underflow.
Writing 1 clears the status.
0 No warning.
0x0
R/W
0x0
R/W
0x0
R/W
0x0
R
1 Warning detected.
PRBS imaginary error. Writing 1
clears the status.
0 No warning.
1 Warning detected.
PRBS real error. Writing 1 clears
the status.
0 No warning.
1 Warning detected.
0x031 SYNC_LMFC_DELAY_FRAME
0x032 SYNC_LMFC_DELAY0
[7:5] RESERVED
Reserved.
[4:0] SYNC_LMFC_DELAY_SET_FRM
Desired delay from rising edge of 0x0
SYSREF± input to rising edge of
LMFC in frames.
R/W
[7:0] SYNC_LMFC_DELAY_SET[7:0]
Desired delay from rising edge of 0x0
SYSREF± input to rising edge of
LMFC in DAC clock units.
R/W
Rev. 0 | Page 89 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x033 SYNC_LMFC_DELAY1
[7:4] RESERVED
Reserved.
0x0
[3:0] SYNC_LMFC_DELAY_SET[11:8]
Desired delay from rising edge of 0x0
SYSREF± input to rising edge of
LMFC in DAC clock units.
R/W
0x034 SYNC_LMFC_STAT0
[7:0] SYNC_LMFC_DELAY_STAT[7:0]
Measured delay from rising edge 0x0
of SYSREF± input to rising edge
of LMFC in DAC clock units (note:
2 LSBs are always zero). A write
to SYNC_LMFC_STATx or
SYSREF_PHASEx saves the data for
readback.
R/W
0x035 SYNC_LMFC_STAT1
[7:4] RESERVED
Reserved.
R
[3:0] SYNC_LMFC_DELAY_STAT[11:8]
Measured delay from rising edge 0x0
of SYSREF± input to rising edge
of LMFC in DAC clock units (note:
2 LSBs are always zero). A write
to SYNC_LMFC_STATx or
SYSREF_PHASEx saves the data for
readback.
R/W
0x036 SYSREF_COUNT
[7:0] SYSREF_COUNT
Count of SYSREF± signals received. 0x0
A write resets the count. A write
to SYNC_LMFC_STATx or
SYSREF_PHASEx saves the data for
readback.
R/W
0x037 SYSREF_PHASE0
[7:0] SYSREF_PHASE[7:0]
Phase of measured SYSREF±
event. Thermometer encoded. A
write to SYNC_LMFC_STATx or
SYSREF_PHASEx saves the data
for readback.
0x0
R/W
0x038 SYSREF_PHASE1
[7:4] RESERVED
Reserved.
0x0
R
[3:0] SYSREF_PHASE[11:8]
Phase of measured SYSREF±
event. Thermometer encoded. A
write to SYNC_LMFC_STATx or
SYSREF_PHASEx saves the data
for readback.
0x0
R/W
[7:6] RESERVED
Reserved.
0x0
R
[5:0] SYSREF_JITTER_WINDOW
Amount of jitter allowed on the
SYSREF± input. SYSREF± jitter
variations bigger than this
triggers an interrupt. Units are in
DAC clocks. The bottom two bits
are ignored.
0x0
R/W
[7:2] RESERVED
Reserved.
0x0
R
0x039 SYSREF_JITTER_WINDOW
0x03A SYNC_CTRL
Settings
[1:0] SYNC_MODE
0x0
Synchronization mode.
0x0
00 Do not perform synchronization,
monitor SYSREF± to LMFC delay
only.
01 Perform continuous
synchronization of LMFC on every
SYSREF±.
R
R/W
10 Perform a single synchronization
on the next SYSREF±, then
switch to monitor mode.
0x03F TX_ENABLE
7
SPI_DATAPATH_POST
SPI control of the data at the
output of the datapath.
0 Disable or zero the data from the
datapath into the DAC.
1 Use the data from the datapath
to drive the DAC.
Rev. 0 | Page 90 of 139
0x1
R/W
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
6
Settings
SPI_DATAPATH_PRE
[5:4] RESERVED
3
Description
SPI control of the data at the
input of the datapath.
0 Disable or zero the data feeding
into the datapath.
1 Use the data from the JESD204B
lanes to drive into the datapath.
Reserved.
TXEN_NCO_RESET
Reset Access
0x1
R/W
0x0
R
Allows TX_ENABLE to control the 0x0
DDS NCO reset.
0 Use the SPI (HOPF_MODE SPI
bits) to control the DDS NCO
reset.
R/W
1 Use the TX_ENABLE pin to
control the DDS NCO reset.
2
TXEN_DATAPATH_POST
Allows TX_ENABLE to control the 0x0
data at the output of the
datapath.
R/W
0 Use the SPI (Bit SPI_DATAPATH_
POST) for control.
1 Use the TX_ENABLE pin for
control.
1
TXEN_DATAPATH_PRE
0
TXEN_DAC_FSC
Allows TX_ENABLE to control the 0x0
data at the input of the datapath.
0 Use the SPI (Bit SPI_DATAPATH_
PRE) for control.
1 Use the TX_ENABLE pin for
control.
R/W
Allows TX_ENABLE to control the 0x0
DAC full-scale current.
R/W
0 Use the SPI register ANA_FSC0
and ANA_FSC1 for control.
1 Use the TX_ENABLE pin for
control.
0x040 ANA_DAC_BIAS_PD
[7:2] RESERVED
Reserved.
0x0
R
1
ANA_DAC_BIAS_PD1
Powers down the DAC core bias
circuits. A 1 powers down the
DAC core bias circuits.
0x1
R/W
0
ANA_DAC_BIAS_PD0
Powers down the DAC core bias
circuits. A 1 powers down the
DAC core bias circuits.
0x1
R/W
[7:2] RESERVED
Reserved.
0x0
R
[1:0] ANA_FULL_SCALE_CURRENT[1:0]
DAC full-scale current. Analog
full-scale current adjustment.
0x3
R/W
0x042 ANA_FSC1
[7:0] ANA_FULL_SCALE_CURRENT[9:2]
DAC full-scale current. Analog
full-scale current adjustment.
0xFF
R/W
0x07F CLK_PHASE_TUNE
[7:6] RESERVED
Reserved.
0x0
R
[5:0] CLK_PHASE_TUNE
Fine tuning of the clock input
phase balance. Adds small
capacitors to the CLK+/CLK−
inputs, ~ 20 fF per step, signed
magnitude.
0x0
R/W
0x041 ANA_FSC0
Rev. 0 | Page 91 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
Description
Reset Access
Capacitance
0x080 CLK_PD
Bits[5:0]
At CLK+
At CLK−
000000
000001
000010
0
1
2
0
0
0
…
011111
…
31
…
0
100000
100001
100010
0
0
0
0
1
2
111111
0
31
[7:1] RESERVED
Reserved.
0x0
R
0
DAC clock power-down. Powers
down the DAC clock circuitry.
0x1
R/W
DACCLK_PD
0 Power up.
1 Power down.
0x082 CLK_DUTY
0x083 CLK_CRS_CTRL
0x084 PLL_REF_CLK_PD
7
CLK_DUTY_EN
Enable duty cycle control.
0x1
R/W
6
CLK_DUTY_OFFSET_EN
Enable duty cycle offset.
0x0
R/W
5
CLK_DUTY_BOOST_EN
Enable duty cycle range boost.
Extends range to ±5% at cost of
1 dB to 2 dB worse phase noise.
0x0
R/W
[4:0] CLK_DUTY_PRG
Program the duty cycle offset.
5-bit signed magnitude field,
with the MSB as the sign bit and
the four LSBs as the magnitude
from 0 to 15. A larger magnitude
skews duty cycle to a greater
amount. Range is ±3%.
0x0
R/W
7
Enable clock cross control
adjustment.
0x1
R/W
[6:4] RESERVED
Reserved.
0x0
R
[3:0] CLK_CRS_ADJ
Program the clock crossing
point.
0x0
R/W
[7:6] RESERVED
Reserved.
0x0
R
0x0
R/W
0x0
R
CLK_CRS_EN
[5:4] PLL_REF_CLK_RATE
PLL reference clock rate
multiplier.
00 Normal rate (1×) PLL reference
clock.
01 Double rate (2×) PLL reference
clock.
10 Quadruple rate (4×) PLL
reference clock.
11 Disable the PLL reference clock.
[3:1] RESERVED
0
0x088 SYSREF_CTRL0
Reserved.
PLL_REF_CLK_PD
PLL reference clock power-down. 0x0
0 Enable the PLL reference clock.
1 Power down the PLL reference
clock.
R/W
[7:4] RESERVED
Reserved.
0x0
R
3
HYS_ON
SYSREF± hysteresis enable. This
bit enables the programmable
hysteresis control for the
SYSREF± receiver.
0x0
R/W
2
SYSREF_RISE
Use SYSREF± rising edge.
0x0
R/W
Rev. 0 | Page 92 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
[1:0] HYS_CNTRL[9:8]
Controls the amount of
0x0
hysteresis in the SYSREF±
receiver. Each of the 10 bits adds
10 mV of differential hysteresis to
the receiver input.
R/W
0x089 SYSREF_CTRL1
[7:0] HYS_CNTRL[7:0]
Controls the amount of
0x0
hysteresis in the SYSREF±
receiver. Each of the 10 bits adds
10 mV of differential hysteresis to
the receiver input.
R/W
0x090 DLL_PD
[7:5] RESERVED
Reserved.
0x0
R
4
DLL_FINE_DC_EN
Fine delay line duty cycle
correction enable.
0x1
R/W
3
DLL_FINE_XC_EN
Fine delay line cross control
enable.
0x1
R/W
2
DLL_COARSE_DC_EN
Coarse delay line duty cycle
correction enable.
0x1
R/W
1
DLL_COARSE_XC_EN
Coarse delay line cross control
enable.
0x1
R/W
0
DLL_CLK_PD
Power down DLL and digital
clock generator.
0x1
R/W
0x1
R/W
0x1
R/W
0x1
R/W
0x2
R/W
0x0
R/W
0x0
R/W
0 Power up DLL controller.
1 Power down DLL controller.
0x091 DLL_CTRL
7
DLL_TRACK_ERR
Track error behavior.
0 Continue on error.
1 Restart on error.
6
DLL_SEARCH_ERR
5
DLL_SLOPE
Search error behavior.
0 Stop on error.
1 Retry on error.
Desired slope.
0 Negative slope.
1 Positive slope.
[4:3] DLL_SEARCH
Search direction.
00 Search down from initial point
only.
01 Search up from initial point only.
10 Search up and down from initial
point.
[2:1] DLL_MODE
Controller mode.
00 Search then track.
01 Track only.
10 Search only.
0
DLL_ENABLE
Controller enable.
0 Disable DLL controller: use static
SPI settings.
1 Enable DLL controller: use
controller with feedback loop.
0x092 DLL_STATUS
0x093 DLL_GB
0x094 DLL_COARSE
0x095 DLL_FINE
[7:3] RESERVED
Reserved.
0x0
R
2
DLL_FAIL
The DAC clock DLL failed to lock.
0x0
R
1
DLL_LOST
The DAC clock DLL has lost lock.
0x0
R/W
0
DLL_LOCKED
The DAC clock DLL has achieved
lock.
0x0
R
[7:4] RESERVED
Reserved.
0x0
R
[3:0] DLL_GUARD
Search guard band.
0x0
R/W
[7:6] RESERVED
Reserved.
0x0
R
[5:0] DLL_COARSE
Coarse delay line setpoint.
0x0
R/W
[7:0] DLL_FINE
Fine delay line setpoint.
0x80
R/W
Rev. 0 | Page 93 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
0x096 DLL_PHASE
[7:5] RESERVED
Settings
[4:0] DLL_PHS
Description
Reset Access
Reserved.
0x0
R
0x8
R/W
Desired phase.
0 Minimum allowed phase.
16 Maximum allowed phase.
0x097 DLL_BW
[7:5] RESERVED
Reserved.
0x0
R
[4:2] DLL_FILT_BW
Phase measurement filter
bandwidth.
0x0
R/W
[1:0] DLL_WEIGHT
Tracking speed.
0x0
R/W
[7:1] RESERVED
Reserved.
0x0
R
0
Read request: 0 to 1 transition
updates the coarse, fine, and
phase readback values.
0x0
R/W
[7:6] RESERVED
Reserved.
0x0
R
[5:0] DLL_COARSE_RB
Coarse delay line readback.
0x0
R
0x09A DLL_FINE_RB
[7:0] DLL_FINE_RB
Fine delay line readback.
0x0
R
0x09B DLL_PHASE_RB
[7:5] RESERVED
Reserved.
0x0
R
[4:0] DLL_PHS_RB
Phase readback.
0x0
R
[7:3] RESERVED
Reserved.
0x0
R
0x0
R/W
0x098 DLL_READ
0x099 DLL_COARSE_RB
0x09D DIG_CLK_INVERT
DLL_READ
2
INV_DIG_CLK
Invert digital clock from DLL.
0 Normal polarity.
1
DIG_CLK_DC_EN
Digital clock duty cycle
correction enable.
0x1
R/W
0
DIG_CLK_XC_EN
Digital clock cross control
enable.
0x1
R/W
7
DLL_TEST_EN
1 Inverted polarity.
0x0A0 DLL_CLK_DEBUG
0x110 INTERP_MODE
DLL clock output test enable.
0x0
R/W
[6:2] RESERVED
Reserved.
0x0
R
[1:0] DLL_TEST_DIV
DLL clock output divide.
0x0
R/W
[7:4] JESD_LANES
Number of JESD204B lanes. For
0x8
proper operation of the
JESD204B data link, this signal
must only be programmed while
the QBD is held in soft reset
(Register 0x475, Bit 3), and must
not be changed during normal
operation.
R/W
Interpolation mode. For proper
0x1
operation of the JESD204B data
link, this signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0000 1× (bypass) (this mode is not
supported in the AD9161).
0001 2×.
R/W
[3:0] INTERP_MODE
0010 3×.
0011 4×.
0100 6×.
0101 8×.
0110 12×.
0111 16×.
1000 24×.
0x111 DATAPATH_CFG
7
INVSINC_EN
Inverse sinc filter enable.
0 Disable inverse sinc filter.
1 Enable inverse sinc filter.
Rev. 0 | Page 94 of 139
0x0
R/W
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
6
NCO_EN
5
RESERVED
4
FILT_BW
Settings
Description
Modulation enable.
0 Disable NCO.
1 Enable NCO.
Reset Access
0x0
R/W
Reserved.
0x0
R
Datapath filter bandwidth.
0x0
R/W
0 Filter bandwidth is 80%.
1 Filter bandwidth is 90%.
3
RESERVED
Reserved.
0x0
R
2
MODULUS_EN
Modulus DDS enable
0x0
R/W
0x0
R/W
0 Disable modulus DDS.
1 Enable modulus DDS.
1
SEL_SIDEBAND
Selects upper or lower sideband
from modulation result.
0 Use upper sideband.
1 Use lower sideband = spectral
flip.
0x113 FTW_UPDATE
0
FIR85_FILT_EN
FIR85 filter enable.
0x0
R/W
7
RESERVED
Reserved.
0x0
R
0x0
R/W
[6:4] FTW_REQ_MODE
Frequency tuning word
automatic update mode.
000 No automatic requests are
generated when the FTW
registers are written.
001 Automatically generate
FTW_LOAD_REQ after FTW0 is
written.
010 Automatically generate
FTW_LOAD_REQ after FTW1 is
written.
011 Automatically generate
FTW_LOAD_REQ after FTW2 is
written.
100 Automatically generate
FTW_LOAD_REQ after FTW3 is
written.
101 Automatically generate
FTW_LOAD_REQ after FTW4 is
written.
110 Automatically generate
FTW_LOAD_REQ after FTW5 is
written.
3
RESERVED
Reserved.
0x0
R
2
FTW_LOAD_SYSREF
FTW load and reset from rising
edge of SYSREF±.
0x0
R/W
1
FTW_LOAD_ACK
Frequency tuning word update
acknowledge.
0 FTW is not loaded.
1 FTW is loaded.
0x0
R
0
FTW_LOAD_REQ
Frequency tuning word update
request from SPI.
0x0
R/W
0 Clear FTW_LOAD_ACK.
1 0 to 1 transition loads the FTW.
0x114 FTW0
[7:0] FTW[7:0]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
0x115 FTW1
[7:0] FTW[15:8]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
Rev. 0 | Page 95 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
0x116 FTW2
[7:0] FTW[23:16]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
0x117 FTW3
[7:0] FTW[31:24]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
0x118 FTW4
[7:0] FTW[39:32]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
0x119 FTW5
[7:0] FTW[47:40]
NCO frequency tuning word. This 0x0
is X in the equation fOUT = fDAC ×
(M/N) = fDAC × ((X + A/B)/248).
R/W
0x11C PHASE_OFFSET0
[7:0] NCO_PHASE_OFFSET[7:0]
NCO phase offset.
0x0
R/W
0x11D PHASE_OFFSET1
[7:0] NCO_PHASE_OFFSET[15:8]
NCO phase offset.
0x0
R/W
0x124 ACC_MODULUS0
[7:0] ACC_MODULUS[7:0]
DDS Modulus. This is B in the
0x0
equation fOUT = fDAC × (M/N) = fDAC
× ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs.
R/W
0x125 ACC_MODULUS1
[7:0] ACC_MODULUS[15:8]
DDS Modulus. This is B in the
0x0
equation fOUT = fDAC × (M/N) = fDAC
× ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs.
R/W
0x126 ACC_MODULUS2
[7:0] ACC_MODULUS[23:16]
DDS Modulus. This is B in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248).Note this
modulus value is used for all
NCO FTWs.
0x0
R/W
0x127 ACC_MODULUS3
[7:0] ACC_MODULUS[31:24]
DDS Modulus. This is B in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs.
0x0
R/W
0x128 ACC_MODULUS4
[7:0] ACC_MODULUS[39:32]
DDS Modulus. This is B in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs.
0x0
R/W
0x129 ACC_MODULUS5
[7:0] ACC_MODULUS[47:40]
DDS Modulus. This is B in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs.
0x0
R/W
0x12A ACC_DELTA0
[7:0] ACC_DELTA[7:0]
DDS Delta. This is A in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs. Note this delta value
is used for all NCO FTWs.
0x0
R/W
0x12B ACC_DELTA1
[7:0] ACC_DELTA[15:8]
DDS Delta. This is A in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs. Note this delta value
is used for all NCO FTWs.
0x0
R/W
0x12C ACC_DELTA2
[7:0] ACC_DELTA[23:16]
DDS Delta. This is A in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs. Note this delta value
is used for all NCO FTWs.
0x0
R/W
Settings
Rev. 0 | Page 96 of 139
Description
Reset Access
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x12D ACC_DELTA3
[7:0] ACC_DELTA[31:24]
DDS Delta. This is 'A' in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
Delta value will be used for all
NCO FTWs.
0x0
R/W
0x12E ACC_DELTA4
[7:0] ACC_DELTA[39:32]
DDS Delta. This is A in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs. Note this delta value
is used for all NCO FTWs.
0x0
R/W
0x12F ACC_DELTA5
[7:0] ACC_DELTA[47:40]
DDS Delta. This is A in the
equation fOUT = fDAC × (M/N) =
fDAC × ((X + A/B)/248). Note this
modulus value is used for all
NCO FTWs. Note this delta value
is used for all NCO FTWs.
0x0
R/W
0x14B PRBS
7
PRBS_GOOD_Q
0x0
R
6
PRBS_GOOD_I
Good data indicator real channel. 0x0
R
Settings
Good data indicator imaginary
channel.
0 Incorrect sequence detected.
1 Correct PRBS sequence detected.
0 Incorrect sequence detected.
1 Correct PRBS sequence detected.
5
RESERVED
Reserved.
0x0
R
4
PRBS_INV_Q
Data inversion imaginary
channel.
0x1
R/W
0x0
R/W
0x0
R/W
0x0
R/W
0x0
R/W
0 Expect normal data.
1 Expect inverted data.
3
PRBS_INV_I
Data inversion real channel.
0 Expect normal data.
2
PRBS_MODE
1 Expect inverted data.
Polynomial select.
0 7-bit: x7 + x6 + 1.
1 15-bit: x15 + x14 + 1.
1
PRBS_RESET
Reset error counters.
0 Normal operation.
1 Reset counters.
0
PRBS_EN
Enable PRBS checker.
0 Disable.
1 Enable.
0x14C PRBS_ERROR_I
[7:0] PRBS_COUNT_I
Error count value real channel.
0x0
R
0x14D PRBS_ERROR_Q
[7:0] PRBS_COUNT_Q
Error Count Value Imaginary
Channel.
0x0
R
0x14E TEST_DC_DATA1
[7:0] DC_TEST_DATA[15:8]
DC test data. DC test mode is not 0x0
supported on the AD9161.
R/W
0x14F TEST_DC_DATA0
[7:0] DC_TEST_DATA[7:0]
DC test data. DC test mode is not 0x0
supported on the AD9161.
R/W
0x150 DIG_TEST
[7:2] RESERVED
Reserved.
0x0
R
1
DC data test mode enable. DC
test mode is not supported on
the AD9161.
0x0
R/W
DC_TEST_EN
1 DC test mode enable.
0 DC test mode disable.
0
0x151 DECODE_CTRL
RESERVED
Reserved.
0x0
R/W
[7:3] RESERVED
Reserved.
0x0
R/W
Rev. 0 | Page 97 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
2
Settings
SHUFFLE
Description
Reset Access
Shuffle mode. Enables shuffle
mode for better spurious
performance.
0x0
R/W
0 Disable MSB shuffling (use
thermometer encoding).
1 Enable MSB shuffling.
0x152 DECODE_MODE
[1:0] RESERVED
Reserved.
0x0
R/W
[7:2] RESERVED
Reserved.
0x0
R
0x0
R/W
[1:0] DECODE_MODE
Decode mode.
00 Nonreturn-to-zero mode (first
Nyquist).
01 Mix-Mode (second Nyquist).
10 Return to zero.
11 Reserved.
0x1DF SPI_STRENGTH
0x200 MASTER_PD
0x201 PHY_PD
[7:4] RESERVED
Reserved.
0x0
R
[3:0] SPIDRV
Slew and drive strength for
CMOS SPI outputs. Slew =
Bits[1:0], drive = Bits[3:2].
0xF
R/W
[7:1] RESERVED
Reserved.
0x0
R
0
Power down the entire JESD204B 0x1
Rx analog (all eight channels and
bias).
R/W
SPI override to power down the
individual PHYs.
0x0
R/W
SPI_PD_MASTER
[7:0] SPI_PD_PHY
Bit 0 controls the SERDIN0± PHY.
Bit 1 controls the SERDIN1± PHY.
Bit 2 controls the SERDIN2± PHY.
Bit 3 controls the SERDIN3± PHY.
Bit 4 controls the SERDIN4± PHY.
Bit 5 controls the SERDIN5± PHY.
Bit 6 controls the SERDIN6± PHY.
Bit 7 controls the SERDIN7± PHY.
0x203 GENERIC_PD
0x206 CDR_RESET
[7:2] RESERVED
Reserved.
0x0
R
1
SPI_SYNC1_PD
Power down LVDS buffer for the
sync request signal, SYNCOUT.
0x0
R/W
0
RESERVED
Reserved.
0x0
R/W
[7:1] RESERVED
Reserved.
0x0
R
0x1
R/W
0
SPI_CDR_RESET
Resets the digital control logic
for all PHYs.
0 CDR logic is reset.
1 CDR logic is operational.
0x230 CDR_OPERATING_MODE_REG_0
[7:6] RESERVED
Reserved.
0x0
R/W
5
Enables half rate CDR operation,
must be enabled for data rates
above 6 Gbps.
0x1
R/W
0x0
R/W
SPI_ENHALFRATE
0 Disables CDR half rate operation,
data rate ≤ 6 Gbps.
1 Enables CDR half rate operation,
data rate > 6 Gbps.
[4:3] RESERVED
Reserved.
Rev. 0 | Page 98 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[2:1] SPI_DIVISION_RATE
Description
Enables oversampling of the
input data.
00 No division. Data rate > 3 Gbps.
Reset Access
0x0
R/W
0x0
R/W
0x8
R/W
0x8
R/W
0x8
R/W
01 Division by 2. 1.5 Gbps < data
rate ≤ 3 Gbps.
10 Division by 4. 750 Mbps < data
rate ≤ 1.5 Gbps.
0
0x250 EQ_CONFIG_PHY_0_1
RESERVED
Reserved.
[7:4] SPI_EQ_CONFIG1
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
[3:0] SPI_EQ_CONFIG0
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
0x251 EQ_CONFIG_PHY_2_3
[7:4] SPI_EQ_CONFIG3
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
Rev. 0 | Page 99 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
Description
Reset Access
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
[3:0] SPI_EQ_CONFIG2
0x8
R/W
0x8
R/W
0x8
R/W
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost Level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
0x252 EQ_CONFIG_PHY_4_5
[7:4] SPI_EQ_CONFIG5
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
[3:0] SPI_EQ_CONFIG4
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
Rev. 0 | Page 100 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
0x253 EQ_CONFIG_PHY_6_7
[7:4] SPI_EQ_CONFIG7
0x8
R/W
0x8
R/W
0x1
R/W
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
[3:0] SPI_EQ_CONFIG6
0000 Manual mode (SPI configured
values used).
0001 Boost level = 1.
0010 Boost level = 2.
0011 Boost level = 3.
0100 Boost level = 4.
0101 Boost level = 5.
0110 Boost level = 6.
0111 Boost level = 7.
1000 Boost level = 8.
1001 Boost level = 9.
1010 Boost level = 10.
1011 Boost level = 11.
1100 Boost level = 12.
1101 Boost level = 13.
1110 Boost level = 14.
1111 Boost level = 15.
0x268 EQ_BIAS_REG
[7:6] EQ_POWER_MODE
Controls the equalizer power
mode/insertion loss capability.
00 Normal mode.
01 Low power mode.
0x280 SYNTH_ENABLE_CNTRL
[5:0] RESERVED
Reserved.
0x4
R/W
[7:3] RESERVED
Reserved.
0x0
R
2
Set this bit high to rerun all of
0x0
the SERDES PLL calibration
routines. Set this bit low again to
allow additional recalibrations.
Rising edge causes the
calibration.
SPI_RECAL_SYNTH
Rev. 0 | Page 101 of 139
R/W
AD9161/AD9162
Hex.
Addr. Name
0x281 PLL_STATUS
Data Sheet
Bits Bit Name
Description
Reset Access
1
RESERVED
Settings
Reserved.
0x0
R/W
0
SPI_ENABLE_SYNTH
Enable the SERDES PLL. Setting
this bit turns on all currents and
proceeds to calibrate the PLL.
Make sure reference clock and
division ratios are correct before
enabling this bit.
0x0
R/W
[7:6] RESERVED
Reserved.
0x0
R
5
If set, the SERDES PLL CP output
is above valid operating range.
0x0
R
SPI_CP_OVER_RANGE_HIGH_RB
0 Charge pump output is within
operating range.
1 Charge pump output is above
operating range.
4
SPI_CP_OVER_RANGE_LOW_RB
If set, the SERDES PLL CP output
is below valid operating range.
0 Charge pump output is within
operating range.
1 Charge pump output is below
operating range.
0x0
R
3
SPI_CP_CAL_VALID_RB
This bit tells the user if the
0x0
charge pump calibration has
completed and is valid.
0 Charge pump calibration is not
valid.
1 Charge pump calibration is valid.
R
[2:1] RESERVED
Reserved.
0x0
R
0
If set, the SERDES synthesizer
locked.
0x0
R
0x0
R
SPI_PLL_LOCK_RB
0 PLL is not locked.
1 PLL is locked.
0x289 REF_CLK_DIVIDER_LDO
[7:2] RESERVED
Reserved.
[1:0] SERDES_PLL_DIV_FACTOR
SERDES PLL reference clock
0x0
division factor. This field controls
the division of the SERDES PLL
reference clock before it is fed
into the SERDES PLL PFD. It must
be set so that fREF/DivFactor is
between 35 MHz and 80 MHz.
00 Divide by 4 for lane rate between
6 Gbps and 12.5 Gbps.
R/W
01 Divide by 2 for lane rate between
3 Gbps and 6 Gbps.
10 Divide by 1 for lane rate between
1.5 Gbps and 3 Gbps.
0x2A7 TERM_BLK1_CTRLREG0
0x2A8 TERM_BLK1_CTRLREG1
[7:1] RESERVED
Reserved.
0x0
R
0
Rising edge of this bit starts a
termination calibration routine.
0x0
R/W
SPI override for termination
value for PHY 0, PHY 1, PHY 6,
and PHY 7. Value options are as
follows:
XXX0XXXX Automatically calibrate
termination value.
XXX1000X Force 000 as termination value.
0x0
R/W
SPI_I_TUNE_R_CAL_TERMBLK1
[7:0] SPI_I_SERIALIZER_RTRIM_TERMBLK1
XXX1001X Force 001 as termination value.
XXX1010X Force 010 as termination value.
XXX1011X Force 011 as termination value.
XXX1100X Force 100 as termination value.
XXX1101X Force 101 as termination value.
Rev. 0 | Page 102 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
XXX1110X Force 110 as termination value.
XXX1111X Force 111 as termination value.
XXX1000X Force 000 as termination value.
0x2AC TERM_BLK1_RD_REG0
0x2AE TERM_BLK2_CTRLREG0
0x2AF TERM_BLK2_CTRLREG1
[7:4] RESERVED
Reserved.
0x0
R
[3:0] SPI_O_RCAL_CODE_TERMBLK1
Readback of calibration code for
PHY 0, PHY 1, PHY 6, and PHY 7.
0x0
R
[7:1] RESERVED
Reserved.
0x0
R
0
SPI_I_TUNE_R_CAL_TERMBLK2
Rising edge of this bit starts a
termination calibration routine.
0x0
R/W
[7:0] SPI_I_SERIALIZER_RTRIM_TERMBLK2
SPI override for termination
value for PHY 2, PHY 3, PHY 4,
and PHY 5. Value options are as
follows:
0x0
R/W
XXX0XXXX Automatically calibrate
termination value.
XXX1000X Force 000 as termination value.
XXX1001X Force 001 as termination value.
XXX1010X Force 010 as termination value.
XXX1011X Force 011 as termination value.
XXX1100X Force 100 as termination value.
XXX1101X Force 101 as termination value.
XXX1110X Force 110 as termination value.
XXX1111X Force 111 as termination value.
XXX1000X Force 000 as termination value.
0x2B3 TERM_BLK2_RD_REG0
0x2BB TERM_OFFSET_0
0x2BC TERM_OFFSET_1
0x2BD TERM_OFFSET_2
0x2BE TERM_OFFSET_3
[7:4] RESERVED
Reserved.
0x0
R
[3:0] SPI_O_RCAL_CODE_TERMBLK2
Readback of calibration code for
PHY 2, PHY 3, PHY 4, and PHY 5.
0x0
R
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_0
Add or subtract from the
termination calibration value of
Physical Lane 0. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_1
Add or subtract from the
termination calibration value of
Physical Lane 1. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_2
Add or subtract from the
termination calibration value of
Physical Lane 2. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_3
Add or subtract from the
termination calibration value of
Physical Lane 3. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
Rev. 0 | Page 103 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x2BF TERM_OFFSET_4
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_4
Add or subtract from the
termination calibration value of
Physical Lane 4. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_5
Add or subtract from the
termination calibration value of
Physical Lane 5. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_6
Add or subtract from the
termination calibration value of
Physical Lane 6. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
[7:4] RESERVED
Reserved.
0x0
R
[3:0] TERM_OFFSET_7
Add or subtract from the
termination calibration value of
Physical Lane 7. 4-bit signed
magnitude value that adds to or
subtracts from the termination
value. Bit 3 is the sign bit, and
Bits[2:0] are the magnitude bits.
0x0
R/W
7
RESERVED
Reserved.
0x0
R
6
CHECKSUM_MODE
0x0
R/W
0x0
R
0x2C0 TERM_OFFSET_5
0x2C1 TERM_OFFSET_6
0x2C2 TERM_OFFSET_7
0x300 GENERAL_JRX_CTRL_0
Settings
JESD204B link parameter
checksum calculation method.
0 Checksum is sum of fields.
1 Checksum is sum of octets.
0x302 DYN_LINK_LATENCY_0
0x304 LMFC_DELAY_0
0x306 LMFC_VAR_0
0x308 XBAR_LN_0_1
[5:1] RESERVED
Reserved.
0
This bit brings up the JESD204B 0x0
receiver when all link parameters
are programmed and all clocks
are ready.
R/W
[7:5] RESERVED
Reserved.
0x0
R
[4:0] DYN_LINK_LATENCY_0
Measurement of the JESD204B
link delay (in PCLK units). Link 0
dynamic link latency. Latency
between current deframer LMFC
and the global LMFC.
0x0
R
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LMFC_DELAY_0
Fixed part of the JESD204B link
delay (in PCLK units). Delay in
frame clock cycles for global
LMFC for Link 0.
0x0
R/W
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LMFC_VAR_0
Variable part of the JESD204B
link delay (in PCLK units).
Location in Rx LMFC where
JESD204B words are read out
from buffer. This setting must
not be more than 10 PCLKs.
0x1F
R/W
[7:6] RESERVED
Reserved.
0x0
R
LINK_EN
Rev. 0 | Page 104 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[5:3] SRC_LANE1
Description
Reset Access
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 1.
0x1
R/W
0x0
R/W
0x0
R
0x3
R/W
0x2
R/W
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
[2:0] SRC_LANE0
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 0.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
0x309 XBAR_LN_2_3
[7:6] RESERVED
Reserved.
[5:3] SRC_LANE3
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 3.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
[2:0] SRC_LANE2
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 2.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
Rev. 0 | Page 105 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
0x30A XBAR_LN_4_5
[7:6] RESERVED
Settings
[5:3] SRC_LANE5
Description
Reset Access
Reserved.
0x0
R
0x5
R/W
0x4
R/W
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 5.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
[2:0] SRC_LANE4
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 4.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
0x30B XBAR_LN_6_7
[7:6] RESERVED
Reserved.
0x0
R
[5:3] SRC_LANE7
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 7.
0x7
R/W
0x6
R/W
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
[2:0] SRC_LANE6
Select data from SERDIN0±,
SERDIN1±, …, or SERDIN7± for
Logic Lane 6.
000 Data is from SERDIN0±.
001 Data is from SERDIN1±.
010 Data is from SERDIN2±.
011 Data is from SERDIN3±.
100 Data is from SERDIN4±.
101 Data is from SERDIN5±.
110 Data is from SERDIN6±.
111 Data is from SERDIN7±.
0x30C FIFO_STATUS_REG_0
[7:0] LANE_FIFO_FULL
Bit 0 corresponds to FIFO full flag 0x0
for data from SERDIN0±.
Bit 1 corresponds to FIFO full flag
for data from SERDIN1±.
Bit 2 corresponds to FIFO full flag
for data from SERDIN2±.
Bit 3 corresponds to FIFO full flag
for data from SERDIN3±.
Bit 4 corresponds to FIFO full flag
for data from SERDIN4±.
Rev. 0 | Page 106 of 139
R
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
Bit 5 corresponds to FIFO full flag
for data from SERDIN5±.
Bit 6 corresponds to FIFO full flag
for data from SERDIN6±.
Bit 7 corresponds to FIFO full flag
for data from SERDIN7±.
0x30D FIFO_STATUS_REG_1
[7:0] LANE_FIFO_EMPTY
Bit 0 corresponds to FIFO empty
flag for data from SERDIN0±.
0x0
R
0x0
R
Bit 1 corresponds to FIFO empty
flag for data from SERDIN1±.
Bit 2 corresponds to FIFO empty
flag for data from SERDIN2±.
Bit 3 corresponds to FIFO empty
flag for data from SERDIN3±.
Bit 4 corresponds to FIFO empty
flag for data from SERDIN4±.
Bit 5 corresponds to FIFO empty
flag for data from SERDIN5±.
Bit 6 corresponds to FIFO empty
flag for data from SERDIN6±.
Bit 7 corresponds to FIFO empty
flag for data from SERDIN7±.
0x311 SYNC_GEN_0
[7:3] RESERVED
Reserved.
2
Mask EOMF from QBD_0.
0x0
Assert SYNCOUT based on loss of
multiframe sync.
EOMF_MASK_0
R/W
0 Don not assert SYNCOUT on loss
of multiframe.
1 Assert SYNCOUT on loss of
multiframe.
1
RESERVED
Reserved.
0x0
R/W
0
EOF_MASK_0
Mask EOF from QBD_0.
0x0
Assert SYNCOUT based on loss of
frame sync.
R/W
0 Do not assert SYNCOUT on loss
of frame.
1 Assert SYNCOUT on loss of
frame.
0x312 SYNC_GEN_1
[7:4] SYNC_ERR_DUR
Duration of SYNCOUT signal low
for purpose of sync error report.
0 means half PCLK cycle. Add an
additional PCLK = 4 octets for
each increment of the value.
0x0
R/W
[3:0] SYNC_SYNCREQ_DUR
Duration of SYNCOUT signal low 0x0
for purpose of sync request. 0
means 5 frame + 9 octets. Add an
additional PCLK = 4 octets for
each increment of the value.
R/W
0x313 SYNC_GEN_3
[7:0] LMFC_PERIOD
LMFC period in PCLK cycle. This
is to report the global LMFC
period based on PCLK.
0x0
R
0x315 PHY_PRBS_TEST_EN
[7:0] PHY_TEST_EN
0x0
R/W
0x316 PHY_PRBS_TEST_CTRL
7
0x0
R
Enable PHY BER by ungating the
clocks.
1 PHY test enable.
0 PHY test disable.
RESERVED
Reserved.
Rev. 0 | Page 107 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
Description
[6:4] PHY_SRC_ERR_CNT
Reset Access
0x0
R/W
0x0
R/W
Start and stop the PHY PRBS test. 0x0
0 Test not started.
R/W
000 Report Lane 0 error count.
001 Report Lane 1 error count.
010 Report Lane 2 error count.
011 Report Lane 3 error count.
100 Report Lane 4 error count.
101 Report Lane 5 error count.
110 Report Lane 6 error count.
111 Report Lane 7 error count.
[3:2] PHY_PRBS_PAT_SEL
Select PRBS pattern for PHY BER
test.
00 PRBS7.
01 PRBS15.
10 PRBS31.
11 Not used.
1
PHY_TEST_START
1 Test started.
0
PHY_TEST_RESET
Reset PHY PRBS test state
machine and error counters.
0x0
R/W
Bits[7:0] of the 24-bit threshold
value set the error flag for PHY
PRBS test.
0x0
R/W
0x318 PHY_PRBS_TEST_THRESHOLD_MIDBITS [7:0] PHY_PRBS_THRESHOLD_MIDBITS
Bits[15:8] of the 24-bit threshold
value set the error flag for PHY
PRBS test.
0x0
R/W
0x319 PHY_PRBS_TEST_THRESHOLD_HIBITS
[7:0] PHY_PRBS_THRESHOLD_HIBITS
Bits[23:16] of the 24-bit
threshold value set the error flag
for PHY PRBS test.
0x0
R/W
0x31A PHY_PRBS_TEST_ERRCNT_LOBITS
[7:0] PHY_PRBS_ERR_CNT_LOBITS
Bits[7:0] of the 24-bit reported
PHY BER test error count from
selected lane.
0x0
R
0x31B PHY_PRBS_TEST_ERRCNT_MIDBITS
[7:0] PHY_PRBS_ERR_CNT_MIDBITS
Bits[15:8] of the 24-bit reported
PHY BER test error count from
selected lane.
0x0
R
0x31C PHY_PRBS_TEST_ERRCNT_HIBITS
[7:0] PHY_PRBS_ERR_CNT_HIBITS
Bits[23:16] of the 24-bit reported
PHY BER test error count from
selected lane.
0x0
R
0x31D PHY_PRBS_TEST_STATUS
[7:0] PHY_PRBS_PASS
Each bit is for the corresponding
lane. Report PHY BER test
pass/fail for each lane.
0xFF
R
0x31E PHY_DATA_SNAPSHOT_CTRL
[7:5] RESERVED
Reserved.
0x0
R
[4:2] PHY_GRAB_LANE_SEL
Select which lane to grab data.
0x0
R/W
0x0
R/W
0 Not reset.
1 Reset.
0x317 PHY_PRBS_TEST_THRESHOLD_LOBITS
[7:0] PHY_PRBS_THRESHOLD_LOBITS
000 Grab data from Lane 0.
001 Grab data from Lane 1.
010 Grab data from Lane 2.
011 Grab data from Lane 3.
100 Grab data from Lane 4.
101 Grab data from Lane 5.
110 Grab data from Lane 6.
111 Grab data from Lane 7.
1
PHY_GRAB_MODE
Rev. 0 | Page 108 of 139
Use error trigger to grab data.
0 Grab data when
PHY_GRAB_DATA is set.
1 Grab data upon bit error.
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
0
Settings
PHY_GRAB_DATA
Description
Reset Access
Transition from 0 to 1 causes
logic to store current receive
data from one lane.
0x0
R/W
0x31F PHY_SNAPSHOT_DATA_BYTE0
[7:0] PHY_SNAPSHOT_DATA_BYTE0
Current data received represents 0x0
PHY_SNAPSHOT_DATA[7:0].
R
0x320 PHY_SNAPSHOT_DATA_BYTE1
[7:0] PHY_SNAPSHOT_DATA_BYTE1
Current data received represents 0x0
PHY_SNAPSHOT_DATA[15:8].
R
0x321 PHY_SNAPSHOT_DATA_BYTE2
[7:0] PHY_SNAPSHOT_DATA_BYTE2
Current data received represents 0x0
PHY_SNAPSHOT_DATA[23:16].
R
0x322 PHY_SNAPSHOT_DATA_BYTE3
[7:0] PHY_SNAPSHOT_DATA_BYTE3
Current data received represents 0x0
PHY_SNAPSHOT_DATA[31:24].
R
0x323 PHY_SNAPSHOT_DATA_BYTE4
[7:0] PHY_SNAPSHOT_DATA_BYTE4
Current data received represents 0x0
PHY_SNAPSHOT_DATA[39:32].
R
0x32C SHORT_TPL_TEST_0
[7:4] SHORT_TPL_SP_SEL
Short transport layer sample
0x0
selection. Select which sample to
check from a specific DAC.
0000 Sample 0.
R/W
0001 Sample 1.
0010 Sample 2.
0011 Sample 3.
0100 Sample 4.
0101 Sample 5.
0110 Sample 6.
0111 Sample 7.
1000 Sample 8.
1001 Sample 9.
1010 Sample 10.
1011 Sample 11.
1100 Sample 12.
1101 Sample 13.
1110 Sample 14.
1111 Sample 15.
[3:2] SHORT_TPL_M_SEL
Short transport layer test DAC
selection. Select which DAC to
check.
00 DAC 0.
0x0
R/W
0x0
R/W
Short transport layer test enable. 0x0
Enable short transport layer test.
R/W
01 DAC 1.
10 DAC 2.
11 DAC 3.
1
SHORT_TPL_TEST_RESET
0
SHORT_TPL_TEST_EN
Short transport layer test reset.
Resets the result of short
transport layer test.
0 Not reset.
1 Reset.
0 Disable.
1 Enable.
0x32D SHORT_TPL_TEST_1
[7:0] SHORT_TPL_REF_SP_LSB
Rev. 0 | Page 109 of 139
Short transport layer reference
sample LSB. This is the lower
eight bits of expected DAC
sample. It is used to compare
with the received DAC sample at
the output of JESD204B Rx.
0x0
R/W
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
0x32E SHORT_TPL_TEST_2
[7:0] SHORT_TPL_REF_SP_MSB
Short transport layer test
0x0
reference sample MSB. This is the
upper eight bits of expected
DAC sample. It is used to
compare with the received
sample at JESD204B Rx output.
R/W
0x32F SHORT_TPL_TEST_3
[7:1] RESERVED
Reserved.
0x0
R
0
Short transport layer test fail.
This bit shows if the selected
DAC sample matches the
reference sample. If they match,
the test passes; otherwise, the
test fails.
0x0
R
Settings
SHORT_TPL_FAIL
Description
Reset Access
0 Test pass.
1 Test fail.
0x334 JESD_BIT_INVERSE_CTRL
[7:0] JESD_BIT_INVERSE
Each bit of this byte inverses the 0x0
JESD204B deserialized data from
one specific JESD204B Rx PHY.
The bit order matches the logical
lane order. For example, Bit 0
controls Lane 0, Bit 1 controls
Lane 1.
R/W
0x400 DID_REG
[7:0] DID_RD
Received ILAS configuration on
0x0
Lane 0. DID is the device ID
number. Link information
received on Lane 0 as specified in
Section 8.3 of JESD204B.
R
0x401 BID_REG
[7:0] BID_RD
Received ILAS configuration on
Lane 0. BID is the bank ID,
extension to DID. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0x0
R
0x402 LID0_REG
7
RESERVED
Reserved.
0x0
R
6
ADJDIR_RD
Received ILAS configuration on
0x0
Lane 0. ADJDIR is the direction to
adjust the DAC LMFC. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
R
5
PHADJ_RD
Received ILAS configuration on
Lane 0. PHADJ is the phase
adjustment request to DAC. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0x0
R
Received ILAS LID configuration
on Lane 0. LID0 is the lane
identification for Lane 0. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0x0
R
Received ILAS configuration on
Lane 0. SCR is the Tx scrambling
status. Link information received
on Lane 0 as specified in
Section 8.3 of JESD204B.
0 Scrambling is disabled.
0x0
R
[4:0] LL_LID0
0x403 SCR_L_REG
7
SCR_RD
1 Scrambling is enabled.
Rev. 0 | Page 110 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[6:5] RESERVED
[4:0] L_RD
Description
Reset Access
Reserved.
0x0
R
0x0
R
0x0
R
0x0
R
Received ILAS configuration on
0x0
Lane 0. K is the number of frames
per multiframe. Settings of 16 or
32 are valid. On this device, all
modes use K = 32 (value in
register is K − 1). Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
01111 16 frames per multiframe.
R
Received ILAS configuration on
Lane 0. L is the number of lanes
per converter device. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
00000 1 lane per converter device.
00001 2 lanes per converter device.
00011 4 lanes per converter device.
00111 8 lanes per converter device.
0x404 F_REG
[7:0] F_RD
0x405 K_REG
[7:5] RESERVED
Received ILAS configuration on
Lane 0. F is the number of octets
per frame. Settings of 1, 2, and 4
are valid (value in register is F −
1). Link information received on
Lane 0 as specified in Section 8.3
of JESD204B.
0 1 octet per frame.
1 2 octets per frame.
11 4 octets per frame.
Reserved.
[4:0] K_RD
11111 32 frames per multiframe.
0x406 M_REG
[7:0] M_RD
Received ILAS configuration on
Lane 0. M is the number of
converters per device. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B. M is 1 for real
interface and 2 for complex
interface (value in register is M −
1).
0x0
R
0x407 CS_N_REG
[7:6] CS_RD
Received ILAS configuration on
Lane 0. CS is the number of
control bits per sample. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B. CS is always 0 on this
device.
0x0
R
5
Reserved.
0x0
R
Received ILAS configuration on
0x0
Lane 0. N is the converter resolution. Value in register is N − 1 (for
example, 16 bits = 0b01111).
R
RESERVED
[4:0] N_RD
0x408 NP_REG
[7:5] SUBCLASSV_RD
Received ILAS configuration on
Lane 0. SUBCLASSV is the device
subclass version. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
000 Subclass 0.
001 Subclass 1.
Rev. 0 | Page 111 of 139
0x0
R
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
[4:0] NP_RD
0x409 S_REG
[7:5] JESDV_RD
Description
Reset Access
Received ILAS configuration on
0x0
Lane 0. NP is the total number of
bits per sample. Link information
received on Lane 0 as specified in
Section 8.3 of JESD204B. Value in
register is NP − 1, for example,
16 bits per sample = 0b01111.
R
Received ILAS configuration on
0x0
Lane 0. JESDV is the JESD204x
version. Link information
received on Lane 0 as specified in
Section 8.3 of JESD204B.
000 JESD204A.
R
001 JESD204B.
[4:0] S_RD
0x40A HD_CF_REG
7
Received ILAS configuration on
Lane 0. S is the number of
samples per converter per frame
cycle. Link information received
on Lane 0 as specified in Section
8.3 of JESD204B. Value in register
is S − 1.
HD_RD
Received ILAS configuration on
Lane 0. HD is the high density
format. Refer to Section 5.1.3 of
JESD204B standard. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0 Low density mode.
1 High density mode.
0x0
R
0x0
R
[6:5] RESERVED
Reserved.
0x0
R
[4:0] CF_RD
Received ILAS configuration on
0x0
Lane 0. CF is the number of
control words per frame clock
period per link. Link information
received on Lane 0 as specified in
Section 8.3 of JESD204B. CF is
always 0 on this device.
R
0x40B RES1_REG
[7:0] RES1_RD
Received ILAS configuration on
Lane 0. Reserved Field 1. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0x0
R
0x40C RES2_REG
[7:0] RES2_RD
Received ILAS configuration on
Lane 0. Reserved Field 2. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B.
0x0
R
0x40D CHECKSUM0_REG
[7:0] LL_FCHK0
Received checksum during ILAS
on Lane 0. Checksum for Lane 0.
Link information received on
Lane 0 as specified in Section 8.3
of JESD204B.
0x0
R
0x40E COMPSUM0_REG
[7:0] LL_FCMP0
Computed checksum on Lane 0. 0x0
Computed checksum for Lane 0.
The JESD204B Rx computes the
checksum of the link information
received on Lane 0 as specified in
Section 8.3 of JESD204B. The
computation method is set by
the CHECKSUM_MODE bit
(Register 0x300, Bit 6) and must
match the likewise calculated
checksum in Register 0x40D.
R
Rev. 0 | Page 112 of 139
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x412 LID1_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID1
Received ILAS LID configuration 0x0
on Lane 1. Lane identification for
Lane 1. Link information received
on Lane 0 as specified in
Section 8.3 of JESD204B.
R
0x415 CHECKSUM1_REG
[7:0] LL_FCHK1
Received checksum during ILAS
on lane 1. Checksum for Lane 1.
Link information received on
Lane 0 as specified in Section 8.3
of JESD204B.
0x0
R
0x416 COMPSUM1_REG
[7:0] LL_FCMP1
Computed checksum on Lane 1.
Computed checksum for Lane 1
(see description for Register
0x40E).
0x0
R
0x41A LID2_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID2
Received ILAS LID configuration 0x0
on Lane 2. Lane identification for
Lane 2.
R
0x41D CHECKSUM2_REG
[7:0] LL_FCHK2
Received checksum during ILAS
on Lane 2. Checksum for Lane 2.
0x0
R
0x41E COMPSUM2_REG
[7:0] LL_FCMP2
Computed checksum on Lane 2. 0x0
Computed checksum for Lane 2
(see description for Register 0x40E).
R
0x422 LID3_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID3
Received ILAS LID configuration 0x0
on Lane 3. Lane identification for
Lane 3.
R
0x425 CHECKSUM3_REG
[7:0] LL_FCHK3
Received checksum during ILAS
on Lane 3. Checksum for Lane 3.
0x0
R
0x426 COMPSUM3_REG
[7:0] LL_FCMP3
Computed checksum on Lane 3. 0x0
Computed checksum for Lane 3
(see description for Register 0x40E).
R
0x42A LID4_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID4
Received ILAS LID configuration 0x0
on Lane 4. Lane identification for
Lane 4.
R
0x42D CHECKSUM4_REG
[7:0] LL_FCHK4
Received checksum during ILAS
on Lane 4. Checksum for Lane 4.
0x0
R
0x42E COMPSUM4_REG
[7:0] LL_FCMP4
Computed checksum on Lane 4. 0x0
Computed checksum for Lane 4
(see description for Register 0x40E).
R
0x432 LID5_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID5
Received ILAS LID configuration 0x0
on Lane 5. Lane identification for
Lane 5.
R
0x435 CHECKSUM5_REG
[7:0] LL_FCHK5
Received checksum during ILAS
on lane 5. Checksum for Lane 5.
0x0
R
0x436 COMPSUM5_REG
[7:0] LL_FCMP5
Computed checksum on Lane 5. 0x0
Computed checksum for Lane 5
(see description for Register 0x40E).
R
0x43A LID6_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID6
Received ILAS LID configuration 0x0
on Lane 6. Lane identification for
Lane 6.
R
0x43D CHECKSUM6_REG
[7:0] LL_FCHK6
Received checksum during ILAS
on Lane 6. Checksum for Lane 6.
0x0
R
0x43E COMPSUM6_REG
[7:0] LL_FCMP6
Computed checksum on Lane 6. 0x0
Computed checksum for Lane 6
(see description for Register 0x40E).
R
Settings
Rev. 0 | Page 113 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x442 LID7_REG
[7:5] RESERVED
Reserved.
0x0
R
[4:0] LL_LID7
Received ILAS LID configuration 0x0
on Lane 7. Lane identification for
Lane 7.
R
0x445 CHECKSUM7_REG
[7:0] LL_FCHK7
Received checksum during ILAS
on Lane 7. Checksum for Lane 7.
0x0
R
0x446 COMPSUM7_REG
[7:0] LL_FCMP7
Computed checksum on Lane 5. 0x0
Computed checksum for Lane 7
(see description for Register 0x40E).
R
0x450 ILS_DID
[7:0] DID
Device (= link) identification
0x0
number. DID is the device ID
number. Link information
received on Lane 0 as specified in
Section 8.3 of JESD204B. Must be
set to the value read in Register
0x400. This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
R/W
0x451 ILS_BID
[7:0] BID
Bank ID, extension to DID. This
0x0
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
R/W
0x452 ILS_LID0
7
RESERVED
Reserved.
R
6
ADJDIR
Direction to adjust DAC LMFC
0x0
(Subclass 2 only). ADJDIR is the
direction to adjust DAC LMFC.
Link information received on
Lane 0 as specified in Section 8.3
of JESD204B. This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
R/W
5
PHADJ
Phase adjustment to DAC
0x0
(Subclass 2 only). PHADJ is the
phase adjustment request to the
DAC. Link information received
on Lane 0 as specified in Section
8.3 of JESD204B. This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
R/W
Lane identification number
0x0
(within link). LID0 is the lane
identification for Lane 0. Link
information received on Lane 0
as specified in Section 8.3 of
JESD204B. This signal must only
be programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
R/W
Settings
[4:0] LID0
Rev. 0 | Page 114 of 139
0x0
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
0x453 ILS_SCR_L
7
Settings
Description
Reset Access
0x1
Scramble enable. SCR is the Rx
descrambling enable. This signal
must only be programmed while
the QBD is held in soft reset
(Register 0x475, Bit 3), and must
not be changed during normal
operation.
SCR
R/W
0 Descrambling is disabled.
1 Descrambling is enabled.
[6:5] RESERVED
Reserved.
0x0
R
[4:0] L
0x7
Number of lanes per converter
(minus 1). L is the number of
lanes per converter device.
Settings of 1, 2, 3, 4, 6, and 8 are
valid. Refer to Table 16 and Table
17.
R
0x454 ILS_F
[7:0] F
Number of octets per frame
(minus 1). This value of F is not
used to soft configure the QBD.
Register CTRLREG1 is used to
soft-configure the QBD.
0x0
R
0x455 ILS_K
[7:5] RESERVED
Reserved.
0x0
[4:0] K
0x1F
Number of frames per
multiframe (minus 1). K is the
number of frames per
multiframe. On this device, all
modes use K = 32 (value in
register is K − 1). This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
R
R/W
01111 16 frames per multiframe.
11111 32 frames per multiframe.
0x456 ILS_M
[7:0] M
Number of converters per device 0x1
(minus 1). M is the number of
converters/device. Settings of 1
and 2 are valid. Refer to Table 16
and Table 17.
R
0x457 ILS_CS_N
[7:6] CS
Number of control bits per
sample. CS is the number of
control bits per sample. Must be
set to 0. Control bits are not
supported.
0x0
R
Reserved.
5
0x458 ILS_NP
0x0
R
[4:0] N
RESERVED
Converter resolution (minus 1). N 0xF
is the converter resolution. Must
be set to 16 (0x0F).
R
[7:5] SUBCLASSV
0x0
Device subclass version.
SUBCLASSV is the device
subclass version. This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
R/W
000 Subclass 0.
001 Subclass 1.
010 Subclass 2 (not supported.)
Rev. 0 | Page 115 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
[4:0] NP
0x459 ILS_S
Description
Reset Access
Total number of bits per sample 0xF
(minus 1) NP is the total number
of bits per sample. Must be set to
16 (0x0F). Refer to Table 16 and
Table 17.
[7:5] JESDV
JESD204x version. JESDV is the
JESD204x version. This signal
must only be programmed while
the QBD is held in soft reset
(Register 0x475, Bit 3), and must
not be changed during normal
operation.
000 JESD204A.
0x0
R
R/W
001 JESD204B.
[4:0] S
0x45A ILS_HD_CF
7
Number of samples per
0x1
converter per frame cycle (minus
1). S is the number of samples
per converter per frame cycle.
Settings of 1 and 2 are valid.
Refer to Table 16 and Table 17.
HD
High density format. HD is the
high density mode. Refer to
Section 5.1.3 of JESD204B
standard.
0 Low density mode.
R
0x1
R
1 High density mode.
[6:5] RESERVED
Reserved.
0x0
R
[4:0] CF
Number of control bits per
sample. CF is the number of
control words per frame clock
period per link. Must be set to 0.
Control bits are not supported.
0x0
R
0x45B ILS_RES1
[7:0] RES1
Reserved. Reserved Field 1. This 0x0
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
R/W
0x45C ILS_RES2
[7:0] RES2
Reserved. Reserved Field 2. This 0x0
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
R/W
0x45D ILS_CHECKSUM
[7:0] FCHK0
Link configuration checksum.
0x0
Checksum for Lane 0. The
checksum for the values programmed into Register 0x450 to
Register 0x45C must be
calculated according to Section
8.3 of the JESD204B specification
and written to this register
(SUM(Register 0x450 to Register
0x45C) % 256). This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
R/W
0x46C LANE_DESKEW
7
ILD7
Interlane deskew status for
Lane 7 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
Rev. 0 | Page 116 of 139
0x0
R
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
6
Settings
ILS6
Description
Reset Access
Initial lane synchronization
status for Lane 6 (ignore this
output when NO_ILAS = 1).
0x0
R
0 Synchronization lost.
1 Synchronization achieved.
5
ILD5
Interlane deskew status for
Lane 5 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
0x0
R
4
ILD4
Interlane deskew status for
Lane 4 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
0x0
R
3
ILD3
Interlane deskew status for
Lane 3 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
0x0
R
2
ILD2
0x0
R
1
ILD1
0x0
R
0
ILD0
0x0
R
7
BDE7
Bad disparity error status for Lane 7. 0x0
R
1 Deskew achieved.
Interlane deskew status for
Lane 2 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
Interlane deskew status for
Lane 1 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
Interlane deskew status for Lane 0
(ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
0x46D BAD_DISPARITY
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
6
BDE6
5
BDE5
Bad disparity error status for Lane 6. 0x0
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Bad disparity errors status for
Lane 5.
R
0x0
R
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
BDE4
Bad disparity error status for Lane 4. 0x0
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
R
3
BDE3
Bad disparity error status for Lane 3. 0x0
0 Error count < ETH[7:0] value.
R
2
BDE2
1 Error count ≥ ETH[7:0] value.
Bad disparity error status for Lane 2. 0x0
R
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
1
BDE1
Bad disparity error status for Lane 1. 0x0
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Rev. 0 | Page 117 of 139
R
AD9161/AD9162
Hex.
Addr. Name
0x46E NOT_IN_TABLE
Data Sheet
Bits Bit Name
Settings
Description
Reset Access
0
BDE0
Bad disparity error status for Lane 0. 0x0
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
R
7
NIT7
Not in table error status for Lane 7.
0 Error count < ETH[7:0] value.
0x0
R
6
NIT6
0x0
R
Not in table errors status for Lane 5. 0x0
R
1 Error count ≥ ETH[7:0] value.
Not in table error status for Lane 6.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
5
NIT5
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
NIT4
3
NIT3
2
NIT2
Not in table error status for Lane 4.
0 Error count < ETH[7:0] value.
0x0
R
0x0
R
0x0
R
1 Error count ≥ ETH[7:0] value.
Not in table error status for Lane 3.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Not in table error status for Lane 2.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
1
NIT1
Not in table error status for Lane 1.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
0x0
R
0
NIT0
Not in table error status for Lane 0.
0 Error count < ETH[7:0] value.
0x0
R
7
UEK7
Unexpected K character error
status for Lane 7.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
0x0
R
6
UEK6
Unexpected K character error
status for Lane 6.
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
1 Error count ≥ ETH[7:0] value.
0x46F UNEXPECTED_KCHAR
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
5
UEK5
4
UEK4
3
UEK3
Unexpected K character error
status for Lane 5.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character error
status for Lane 4.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character error
status for Lane 3.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
2
UEK2
Unexpected K character error
status for Lane 2.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
1
UEK1
Unexpected K character error
status for Lane 1.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Rev. 0 | Page 118 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
0
UEK0
7
CGS7
6
CGS6
Settings
Description
Unexpected K character error
status for Lane 0.
0 Error count < ETH[7:0] value.
Reset Access
0x0
R
Code group sync status for
Lane 7.
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
Code group sync status for
Lane 6.
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
1 Error count ≥ ETH[7:0] value.
0x470 CODE_GRP_SYNC
0 Synchronization lost.
1 Synchronization achieved.
5
CGS5
4
CGS4
3
CGS3
Code group sync status for
Lane 5.
0 Synchronization lost.
1 Synchronization achieved.
Code group sync status for
Lane 4.
0 Synchronization lost.
1 Synchronization achieved.
Code group sync status for
Lane 3.
0 Synchronization lost.
1 Synchronization achieved.
2
CGS2
Code group sync status for
Lane 2.
0 Synchronization lost.
1 Synchronization achieved.
1
CGS1
Code group sync status for
Lane 1.
0 Synchronization lost.
0
CGS0
Code group sync status for
Lane 0.
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
7
FS7
Frame sync status for Lane 7
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
6
FS6
Frame sync status for Lane 6
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
0x0
R
5
FS5
0x0
R
4
FS4
0x0
R
1 Synchronization achieved.
0x471 FRAME_SYNC
1 Synchronization achieved.
Frame sync status for Lane 5
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Frame sync status for Lane
4(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Rev. 0 | Page 119 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
3
Settings
FS3
Description
Reset Access
Frame sync status for Lane 3
(ignore this output when
NO_ILAS = 1).
0x0
R
0x0
R
0 Synchronization lost.
1 Synchronization achieved.
2
FS2
Frame sync status for Lane 2
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x472 GOOD_CHECKSUM
1
FS1
Frame sync status for Lane 1
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
0
FS0
Frame sync status for Lane 0
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
7
CKS7
Computed checksum status for
Lane 7 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
0x0
R
6
CKS6
0x0
R
5
CKS5
0x0
R
4
CKS4
0x0
R
3
CKS3
0x0
R
0x0
R
0x0
R
1 Checksum is correct.
Computed checksum status for
Lane 6 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
Computed checksum status for
Lane 5 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
Computed checksum status for
Lane 4 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
Computed checksum status for
Lane 3 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
2
CKS2
Computed checksum status for
Lane 2 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
1
CKS1
Computed checksum status for
Lane 1 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
Rev. 0 | Page 120 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
0
Settings
CKS0
Description
Reset Access
Computed checksum status for
Lane 0 (ignore this output when
NO_ILAS = 1).
0x0
R
0x0
R
0 Checksum is incorrect.
1 Checksum is correct.
0x473 INIT_LANE_SYNC
7
ILS7
Initial lane synchronization
status for Lane 7 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
6
ILS6
Initial lane synchronization
status for Lane 6(ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
5
ILS5
Initial lane synchronization
status for Lane 5 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
4
ILS4
Initial lane synchronization
status for Lane 4 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
0x0
R
3
ILS3
0x0
R
2
ILS2
0x0
R
1
ILS1
0x0
R
0
ILS0
0x0
R
1 Synchronization achieved.
Initial lane synchronization
status for Lane 3 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Initial lane synchronization
status for Lane 2 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Initial lane synchronization
status for Lane 1 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Initial lane synchronization
status for Lane 0 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x475 CTRLREG0
7
RX_DIS
Level input: disable deframer
0x0
receiver when this input = 1. This
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
1 Disable character replacement of
/A/ and /F/ control characters at
the end of received frames and
multiframes.
0 Enables the substitution.
Rev. 0 | Page 121 of 139
R/W
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
6
Settings
CHAR_REPL_DIS
Description
Reset Access
When this input = 1, character
0x0
replacement at the end of
frame/multiframe is disabled.
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
R/W
[5:4] RESERVED
Reserved.
0x0
R
3
Soft reset. Active high
synchronous reset. Resets all
hardware to power-on state.
0x0
R/W
SOFTRST
1 Disables the deframer reception.
0 Enable deframer logic.
0x476 CTRLREG1
2
FORCESYNCREQ
Command from application to
0x0
assert a sync request (SYNCOUT).
Active high.
R/W
1
RESERVED
Reserved.
R
0
REPL_FRM_ENA
When this level input is set, it
0x1
enables replacement of frames
received in error. This signal
must only be programmed while
the QBD is held in soft reset
(Register 0x475, Bit 3), and must
not be changed during normal
operation.
R/W
Reserved.
R
[7:5] RESERVED
4
QUAL_RDERR
0x0
0x0
Error reporting behavior for
0x1
concurrent NIT and RD errors.
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0 NIT has no effect on RD error.
R/W
1 NIT error masks concurrent RD
error.
3
DEL_SCR
Alternative descrambler enable. 0x0
(see JESD204B Section 5.2.4) This
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
1 Descrambling begins at Octet 2
of user data.
0 Descrambling begins at Octet 0
of user data. This is the common
usage.
R/W
2
CGS_SEL
Determines the QBD behavior
0x1
after code group sync has been
achieved. This signal must only
be programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0 After code group sync is
achieved, the QBD
asserts SYNCOUT only if there are
sufficient disparity errors as per
the JESD204B standard.
R/W
Rev. 0 | Page 122 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
1 After code group sync is
achieved, if a /K/ is followed by
any character other than an /R/
or another /K/, QBD
asserts SYNCOUT.
1
NO_ILAS
This signal must only be
0x0
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
1 For single-lane operation, ILAS is
omitted. Code group sync is
followed by user data.
0 Code group sync is followed by
ILAS. For multilane operation,
NO_ILAS must always be set to 0.
R/W
0
FCHK_N
Checksum calculation method.
0x0
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Register 3), and must not be
changed during normal
operation.
0 Calculate checksum by summing
individual fields (this more
closely matches the definition of
the checksum field in the
JESD204B standard.
R/W
1 Calculate checksum by summing
the registers containing the
packed fields (this setting is
provided in case the framer of
another vendor performs the
calculation with this method).
0x477 CTRLREG2
7
ILS_MODE
Data link layer test mode. This
0x0
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
0 Normal mode.
R/W
1 Code group sync pattern is
followed by a perpetual ILAS
sequence.
6
RESERVED
Reserved.
5
REPDATATEST
Repetitive data test enable, using 0x0
JTSPAT pattern. To enable the
test, ILS_MODE must = 0. This
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
R/W
4
QUETESTERR
Queue test error mode. This
0x0
signal must only be programmed
while the QBD is held in soft
reset (Register 0x475, Bit 3), and
must not be changed during
normal operation.
0 Simultaneous errors on multiple
lanes are reported as one error.
1 Detected errors from all lanes are
trapped in a counter and
sequentially signaled
on SYNCOUT.
R/W
Rev. 0 | Page 123 of 139
0x0
R
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
3
Settings
AR_ECNTR
Description
Reset Access
Automatic reset of error counter. 0x0
The error counter that causes
assertion of SYNCOUT is automatically reset to 0 when AR_ECNTR =
1. All other counters are
unaffected. This signal must only
be programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
R/W
R
[2:0] RESERVED
Reserved.
0x478 KVAL
[7:0] KSYNC
Number of 4 × K multiframes
0x1
during ILS. F is the number of
octets per frame. Settings of 1, 2,
and 4 are valid. Refer to Table 16
and Table 17. This signal must
only be programmed while the
QBD is held in soft reset (Register
0x475, Bit 3), and must not be
changed during normal
operation.
0x0
R/W
0x47C ERRORTHRES
[7:0] ETH
0xFF
Error threshold value. Bad
disparity, NIT disparity, and
unexpected K character errors
are counted and compared to
the error threshold value. When
the count is equal, either an IRQ
is generated or SYNCOUT± is
asserted per the mask register
settings or both. Function is
performed in all lanes. This signal
must only be programmed while
the QBD is held in soft reset
(Register 0x475, Bit 3), and must
not be changed during normal
operation.
R/W
0x47D SYNC_ASSERT_MASK
[7:3] RESERVED
Reserved.
0x0
R
[2:0] SYNC_ASSERT_MASK
SYNCOUT assertion enable mask
for BD, NIT, and UEK error
conditions. Active
high, SYNCOUT assertion enable
mask for BD, NIT, and UEK error
conditions, respectively. When
an error counter, in any lane, has
reached the error threshold
count, ETH[7:0], and the
corresponding SYNC_ASSERT_
MASK bit is set, SYNCOUT is
asserted. The mask bits are as
follows. Note that the bit
sequence is reversed with
respect to the other error count
controls and the error counters.
0x7
R/W
Bit 2 = bad disparity error (BDE).
Bit 1 = not in table error (NIT).
Bit 0 = unexpected K (UEK)
character error.
0x480 ECNT_CTRL0
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA0
Error counter enable for Lane 0.
Counters of each lane are
addressed as follows:
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
Rev. 0 | Page 124 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[2:0] ECNT_RST0
Description
Reset Access
Error counters enable for Lane 0,
active high. Counters of each
lane are addressed as follows:
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x481 ECNT_CTRL1
0x482 ECNT_CTRL2
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA1
Error counters enable for Lane 1,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x7
R/W
[2:0] ECNT_RST1
Error counters enable for Lane 1,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x7
R/W
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA2
Error counters enable for Lane 2,
active high. Counters of each
lane are addressed as follows:
0x7
R/W
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
[2:0] ECNT_RST2
Error counters enable for Lane 2,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x483 ECNT_CTRL3
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA3
Error counters enable for Lane 3,
active high. Counters of each
lane are addressed as follows:
0x7
R/W
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
[2:0] ECNT_RST3
Error counters enable for Lane 3,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
Rev. 0 | Page 125 of 139
AD9161/AD9162
Data Sheet
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x484 ECNT_CTRL4
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA4
Error counters enable for Lane 4,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x7
R/W
[2:0] ECNT_RST4
Error counters enable for Lane 4,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
0x7
R/W
Settings
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x485 ECNT_CTRL5
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA5
Error counters enable for Lane 5,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
0x7
R/W
0x7
R/W
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
[2:0] ECNT_RST5
Error counters enable for Lane 5,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x486 ECNT_CTRL6
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA6
Error counters enable for Lane 6,
active high. Counters of each
lane are addressed as follows:
0x7
R/W
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
[2:0] ECNT_RST6
Error counters enable for Lane 6,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x487 ECNT_CTRL7
[7:6] RESERVED
Reserved.
0x0
R
[5:3] ECNT_ENA7
Error counters enable for Lane 7,
active high. Counters of each
lane are addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x7
R/W
Rev. 0 | Page 126 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
Settings
[2:0] ECNT_RST7
Description
Reset Access
Reset error counters for Lane 7,
active high. Counters of each
lane are addressed as follows:
0x7
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x488 ECNT_TCH0
[7:3] RESERVED
Reserved.
0x0
R
[2:0] ECNT_TCH0
Terminal count hold enable of
error counters for Lane 0. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user. Otherwise, the designated counter
rolls over. Counters of each lane
are addressed as follows:
0x7
R/W
0x0
R
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x489 ECNT_TCH1
[7:3] RESERVED
Reserved.
[2:0] ECNT_TCH1
Terminal count hold enable of
0x7
error counters for Lane 1. When set,
the designated counter is to hold
the terminal count value of 0xFF
when it is reached until the counter
is reset by the user. Otherwise, the
designated counter rolls over.
Counters of each lane are
addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
R/W
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x48A ECNT_TCH2
[7:3] RESERVED
Reserved.
[2:0] ECNT_TCH2
Terminal count hold enable of
0x7
error counters for Lane 2. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated counter
rolls over. Counters of each lane are
addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
Rev. 0 | Page 127 of 139
0x0
R
R/W
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
Description
Reset Access
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x48B ECNT_TCH3
[7:3] RESERVED
Reserved.
[2:0] ECNT_TCH3
Terminal count hold enable of
0x7
error counters for Lane 3. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated counter
rolls over. Counters of each lane are
addressed as follows:
0x0
R
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x48C ECNT_TCH4
[7:3] RESERVED
Reserved.
[2:0] ECNT_TCH4
Terminal count hold enable of
0x7
error counters for Lane 4. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated counter
rolls over. Counters of each lane are
addressed as follows:
0x0
R
R/W
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x48D ECNT_TCH5
[7:3] RESERVED
Reserved.
[2:0] ECNT_TCH5
Terminal count hold enable of
0x7
error counters for Lane 5. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated counter
rolls over. Counters of each lane are
addressed as follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
Rev. 0 | Page 128 of 139
0x0
R
R/W
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x48E ECNT_TCH6
[7:3] RESERVED
Reserved.
0x0
R
[2:0] ECNT_TCH6
Terminal count hold enable of
error counters for Lane 6. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated
counter rolls over. Counters of
each lane are addressed as
follows:
Bit 2 = unexpected K (UEK)
character error.
0x7
R/W
Settings
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x48F ECNT_TCH7
[7:3] RESERVED
Reserved.
0x0
R
[2:0] ECNT_TCH7
Terminal count hold enable of
error counters for Lane 7. When
set, the designated counter is to
hold the terminal count value of
0xFF when it is reached until the
counter is reset by the user.
Otherwise, the designated
counter rolls over. Counters of
each lane are addressed as
follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x7
R/W
0x0
R
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 0. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows.
Bit 2 = unexpected K (UEK)
character error.
R
This signal must only be
programmed while the QBD is
held in soft reset (Register 0x475,
Bit 3), and must not be changed
during normal operation.
0x490 ECNT_STAT0
[7:4] RESERVED
3
Reserved.
LANE_ENA0
This output indicates if lane0 is
enabled.
0 Lane0 is held in soft reset.
1 Lane0 is enabled.
[2:0] ECNT_TCR0
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x491 ECNT_STAT1
[7:4] RESERVED
Reserved.
0x0
R
3
This output indicates if Lane 1 is
enabled.
0x0
R
LANE_ENA1
0 Lane 1 is held in soft reset.
1 Lane 1 is enabled.
Rev. 0 | Page 129 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
Settings
[2:0] ECNT_TCR1
Description
Reset Access
Terminal count reached indicator 0x0
of error counters for Lane 1. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows.
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
R
Bit 0 = bad disparity error (BDE).
0x492 ECNT_STAT2
[7:4] RESERVED
0x0
R
0x0
R
[2:0] ECNT_TCR2
Terminal count reached indicator 0x0
of error counters for Lane 2. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows.
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
R
[7:4] RESERVED
Reserved.
0x0
R
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 3. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows:
R
3
Reserved.
LANE_ENA2
This output indicates if Lane 2 is
enabled.
0 Lane 2 is held in soft reset.
1 Lane 2 is enabled.
0x493 ECNT_STAT3
3
LANE_ENA3
This output indicates if Lane 3 is
enabled.
0 Lane 3 is held in soft reset.
1 Lane 3 is enabled.
[2:0] ECNT_TCR3
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x494 ECNT_STAT4
[7:4] RESERVED
Reserved.
0x0
R
3
This output indicates if Lane 4 is
enabled.
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 4. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows:
R
LANE_ENA4
0 Lane 4 is held in soft reset.
1 Lane 4 is enabled.
[2:0] ECNT_TCR4
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
Rev. 0 | Page 130 of 139
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
Description
Reset Access
0x495 ECNT_STAT5
[7:4] RESERVED
Reserved.
0x0
R
3
This output indicates if Lane 5 is
enabled.
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 5. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows:
R
Settings
LANE_ENA5
0 Lane 5 is held in soft reset.
1 Lane 5 is enabled.
[2:0] ECNT_TCR5
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x496 ECNT_STAT6
[7:4] RESERVED
Reserved.
0x0
R
3
This output indicates if Lane 6 is
enabled.
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 6. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows:
Bit 2 = unexpected K (UEK)
character error.
Bit 1 = not in table error (NIT).
R
LANE_ENA6
0 Lane 6 is held in soft reset.
1 Lane 6 is enabled.
[2:0] ECNT_TCR6
Bit 0 = bad disparity error (BDE).
0x497 ECNT_STAT7
[7:4] RESERVED
3
Reserved.
LANE_ENA7
0x0
R
0x0
R
Terminal count reached indicator 0x0
of error counters for Lane 7. Set
to 1 when the corresponding
counter terminal count value of
0xFF has been reached. Counters
of each lane are addressed as
follows:
Bit 2 = unexpected K (UEK)
character error.
R
This output indicates if Lane 7 is
enabled.
0 Lane 7 is held in soft reset.
1 Lane 7 is enabled.
[2:0] ECNT_TCR7
Bit 1 = not in table error (NIT).
Bit 0 = bad disparity error (BDE).
0x4B0 LINK_STATUS0
7
BDE0
6
NIT0
5
UEK0
Bad disparity errors status for
Lane 0.
0 Error count < ETH[7:0] value.
0x0
R
0x0
R
0x0
R
1 Error count ≥ ETH[7:0] value.
Not in table errors status for
Lane 0.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character errors
status for Lane 0.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Rev. 0 | Page 131 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
4
Settings
ILD0
Description
Reset Access
Interlane deskew status for
Lane 0 (ignore this output when
NO_ILAS = 1).
0x0
R
0x0
R
0 Deskew failed.
1 Deskew achieved.
3
ILS0
Initial lane synchronization
status for Lane 0 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
2
CKS0
Computed checksum status for
Lane 0 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
0x0
R
1
FS0
Frame sync status for Lane 0
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
0x0
R
0
CGS0
0x0
R
0x0
R
0x0
R
0x0
R
1 Synchronization achieved.
Code group sync status for
Lane 0.
0 Synchronization lost.
1 Synchronization achieved.
0x4B1 LINK_STATUS1
7
BDE1
Bad Disparity errors status for
Lane 1.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
6
NIT1
Not in table errors status for
Lane 1.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
5
UEK1
Unexpected K character errors
status for Lane 1.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
ILD1
Interlane deskew status for
Lane 1 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
0x0
R
3
ILS1
Initial lane synchronization
status for Lane 1 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
0x0
R
2
CKS1
0x0
R
1
FS1
0x0
R
1 Synchronization achieved.
Computed checksum status for
Lane 1 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
Frame sync status for Lane 1
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Rev. 0 | Page 132 of 139
Data Sheet
Hex.
Addr. Name
AD9161/AD9162
Bits Bit Name
0
CGS1
7
BDE2
6
NIT2
Settings
Description
Code group sync status for
Lane 1.
0 Synchronization lost.
Reset Access
0x0
R
Bad Disparity errors status for
Lane 2.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
0x0
R
Not in table errors status for
Lane 2.
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
1 Synchronization achieved.
0x4B2 LINK_STATUS2
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
5
UEK2
4
ILD2
Unexpected K character errors
status for Lane 2.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Interlane deskew status for
Lane 2 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
3
ILS2
Initial lane synchronization
status for Lane 2 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
2
CKS2
Computed checksum status for
Lane 2 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
1
FS2
Frame sync status for Lane 2
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0
CGS2
Code group sync status for
Lane 2.
0 Synchronization lost.
1 Synchronization achieved.
0x4B3 LINK_STATUS3
7
BDE3
6
NIT3
5
UEK3
Bad Disparity errors status for
Lane 3.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Not in table errors status for
Lane 3.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character errors
status for Lane 3.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
ILD3
Interlane deskew status for
Lane 3 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
Rev. 0 | Page 133 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
3
Settings
ILS3
Description
Reset Access
Initial lane synchronization
status for Lane 3 (ignore this
output when NO_ILAS = 1).
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0 Synchronization lost.
1 Synchronization achieved.
2
CKS3
Computed checksum status for
Lane 3 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
1
FS3
0
CGS3
Frame sync status for Lane 3
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Code group sync status for
Lane 3.
0 Synchronization lost.
1 Synchronization achieved.
0x4B4 LINK_STATUS4
7
BDE4
Bad Disparity errors status for
Lane 4.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
6
NIT4
5
UEK4
Not in table errors status for
Lane 4.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character errors
status for Lane 4.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
ILD4
Interlane deskew status for
Lane 4 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
3
ILS4
Initial lane synchronization
status for Lane 4 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
2
CKS4
Computed checksum status for
Lane 4 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
0x0
R
1
FS4
0x0
R
0
CGS4
0x0
R
1 Checksum is correct.
Frame sync status for Lane 4
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Code group sync status for
Lane 4.
0 Synchronization lost.
1 Synchronization achieved.
Rev. 0 | Page 134 of 139
Data Sheet
AD9161/AD9162
Hex.
Addr. Name
Bits Bit Name
0x4B5 LINK_STATUS5
7
BDE5
6
NIT5
5
UEK5
Settings
Description
Bad disparity errors status for
Lane 5.
0 Error count < ETH[7:0] value.
Reset Access
0x0
R
0x0
R
0x0
R
0x0
R
1 Error count ≥ ETH[7:0] value.
Not in table errors status for
Lane 5.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character errors
status for Lane 5.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
ILD5
Interlane deskew status for
Lane 5 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
3
ILS5
Initial lane synchronization
status for Lane 5 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0x0
R
2
CKS5
Computed checksum status for
Lane 5 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
0x0
R
1
FS5
Frame sync status for Lane 5
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
0x0
R
0
CGS5
0x0
R
0x0
R
0x0
R
1 Synchronization achieved.
Code group sync status for
Lane 5.
0 Synchronization lost.
1 Synchronization achieved.
0x4B6 LINK_STATUS6
7
BDE6
6
NIT6
Bad Disparity errors status for
Lane 6.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Not in table errors status for
Lane 6.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
5
UEK6
Unexpected K character errors
status for Lane 6.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
0x0
R
4
ILD6
Interlane deskew status for Lane
6 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
0x0
R
3
ILS6
Initial lane synchronization
status for Lane 6 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
0x0
R
1 Synchronization achieved.
Rev. 0 | Page 135 of 139
AD9161/AD9162
Hex.
Addr. Name
Data Sheet
Bits Bit Name
2
Settings
CKS6
Description
Reset Access
Computed checksum status for
Lane 6 (ignore this output when
NO_ILAS = 1).
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0x0
R
0 Checksum is incorrect.
1 Checksum is correct.
1
FS6
Frame sync status for Lane 6
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
0
CGS6
Code group sync status for
Lane 6.
0 Synchronization lost.
1 Synchronization achieved.
0x4B7 LINK_STATUS7
7
BDE7
6
NIT7
5
UEK7
Bad Disparity errors status for
Lane 7.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Not in table errors status for
Lane 7.
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
Unexpected K character errors
status for Lane 7
0 Error count < ETH[7:0] value.
1 Error count ≥ ETH[7:0] value.
4
ILD7
Interlane deskew status for
Lane 7 (ignore this output when
NO_ILAS = 1).
0 Deskew failed.
1 Deskew achieved.
3
ILS7
Initial lane synchronization
status for Lane 7 (ignore this
output when NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
2
CKS7
Computed checksum status for
Lane 7 (ignore this output when
NO_ILAS = 1).
0 Checksum is incorrect.
1 Checksum is correct.
1
FS7
0
CGS7
Frame sync status for Lane 7
(ignore this output when
NO_ILAS = 1).
0 Synchronization lost.
1 Synchronization achieved.
Code group sync status for
Lane 7.
0 Synchronization lost.
1 Synchronization achieved.
0x4B8 JESD_IRQ_ENABLEA
7
EN_BDE
Bad disparity error counter.
0x0
R/W
6
EN_NIT
Not in table error counter.
0x0
R/W
5
EN_UEK
Unexpected K error counter.
0x0
R/W
4
EN_ILD
Interlane deskew.
0x0
R/W
3
EN_ILS
Initial lane sync.
0x0
R/W
Rev. 0 | Page 136 of 139
Data Sheet
Hex.
Addr. Name
0x4B9 JESD_IRQ_ENABLEB
0x4BA JESD_IRQ_STATUSA
0x4BB JESD_IRQ_STATUSB
0x800 HOPF_CTRL
AD9161/AD9162
Bits Bit Name
Settings
Description
Reset Access
2
EN_CKS
Good checksum. This is an
0x0
interrupt that compares two
checksums: the checksum that
the transmitter sent over the link
during the ILAS, and the
checksum that the receiver
calculated from the ILAS data
that the transmitter sent over the
link. Note that the checksum IRQ
never at any time looks at the
checksum that is programmed
over the SPI into Register 0x45D.
The checksum IRQ only looks at
the data sent by the transmitter,
and never looks at any data
programmed via the SPI.
R/W
1
EN_FS
Frame sync.
0x0
R/W
0
EN_CGS
Code group sync.
0x0
R/W
[7:1] RESERVED
Reserved.
0x0
R
0
EN_ILAS
Configuration mismatch
0x0
(checked for Lane 0 only). The
ILAS IRQ compares the two sets
of ILAS data that the receiver has:
the ILAS data sent over the
JESD204B link by the transmitter,
and the ILAS data programmed
into the receiver via the SPI
(Register 0x450 to Register
0x45D). If the data differs, the
IRQ is triggered. Note that all of
the ILAS data (including the
checksum) is compared.
R/W
7
IRQ_BDE
Bad disparity error counter.
0x0
R/W
6
IRQ_NIT
Not in table error counter.
0x0
R/W
5
IRQ_UEK
Unexpected K error counter.
0x0
R/W
4
IRQ_ILD
Interlane deskew.
0x0
R/W
3
IRQ_ILS
Initial lane sync.
0x0
R/W
2
IRQ_CKS
Good checksum.
0x0
R/W
1
IRQ_FS
Frame sync.
0x0
R/W
0
IRQ_CGS
Code group sync.
0x0
R/W
[7:1] RESERVED
Reserved.
0x0
R
0
Configuration mismatch
(checked for Lane 0 only).
0x0
R/W
Frequency switch mode.
0x0
00 Phase continuous switch.
Changes frequency tuning word,
and the phase accumulator
continues to accumulate to the
new FTW.
01 Phase discontinuous switch.
Changes the frequency tuning
word and resets the phase
accumulator.
10 Reserved.
R/W
IRQ_ILAS
[7:6] HOPF_MODE
[5:0] RESERVED
Reserved.
Rev. 0 | Page 137 of 139
0x0
R
AD9161/AD9162
Data Sheet
OUTLINE DIMENSIONS
8.05
8.00 SQ
7.95
5.85
BSC
A1 BALL
CORNER
15
14
13
12
11
10
9
8
7
6
5
4
3
2
A1 BALL
CORNER
1
A
B
C
D
E
7.00
REF SQ
F
G
H
5.895
BSC
J
0.50
BSC
K
L
M
N
P
R
0.50
REF
TOP VIEW
DETAIL A
0.35
0.30
0.25
DETAIL A
0.24
REF
0.22 NOM
0.15 MIN
0.35
COPLANARITY
0.30
0.08
0.25
BALL DIAMETER
PKG-004576
SEATING
PLANE
10-28-2014-A
0.86 MAX
0.76 MOM
BOTTOM VIEW
Figure 194. 165-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
(BC-165-1)
Dimensions shown in millimeters
A1 BALL
CORNER
11.05
11.00 SQ
10.95
A1 BALL
PAD CORNER
1.285
BSC
13 12 11 10 9 8 7 6 5 4 3 2 1
A
5.935
BSC
B
C
D
E
F
G
H
J
K
L
M
N
9.60
REF SQ
0.80
BSC
TOP VIEW
2.405 BSC
BOTTOM VIEW
0.70
REF
5.890 BSC
DETAIL A
*0.95 MAX
PKG-004675
SEATING
PLANE
DETAIL A
0.45
0.40
0.35
BALL DIAMETER
0.31 NOM
0.21 MIN
COPLANARITY
0.12
*COMPLIANT TO JEDEC STANDARDS MO-275-FFAC-1 WITH THE
EXCEPTION OF PACKAGE HEIGHT AND THICKNESS.
Figure 195. 169-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
(BC-169-2)
Dimensions shown in millimeters
Rev. 0 | Page 138 of 139
07-10-2015-A
0.35
0.30
0.25
Data Sheet
AD9161/AD9162
ORDERING GUIDE
Model 1
AD9161BBCZ
AD9161BBCZRL
AD9162BBCZ
AD9162BBCZRL
AD9162BBCAZ
AD9162BBCAZRL
AD9162BBCA
AD9162BBCARL
AD9161-FMCC-EBZ
AD9162-FMC-EBZ
AD9162-FMCB-EBZ
AD9162-FMCC-EBZ
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
169-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
169-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
165-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
165-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
169 Ball Chip Scale Package Ball Grid Array [CSP_BGA]
169-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
169 Ball Chip Scale Package Ball Grid Array (CSP_BGA)
169-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
Evaluation Board
Evaluation Board For 8 × 8 mm Package with High Accuracy
Balance Balun
Evaluation Board For 8 × 8 mm Package with Balun and Match
Optimized For Wider Output Bandwidth
Evaluation Board for 11 × 11 mm Package with Balun and
Match Optimized for Wider Output Bandwidth
Z = RoHS Compliant Part.
©2016 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D14379-0-5/16(0)
Rev. 0 | Page 139 of 139
Package Option
BC-169-2
BC-169-2
BC-165-1
BC-165-1
BC-169-2
BC-169-2
BC-169-2
BC-169-2