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IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
IN-PLUG® series: IPS15
Low Cost, High Efficiency, Low Power
Enhanced Off-line Switcher
– REVISION 12 INTRODUCTION
DESCRIPTION
The IN-PLUG® IPS15 is an enhanced off-line
switcher version of the IPS10. It includes additional
features such as soft start and over-voltage limiting.
As the IPS10, the IPS15 Integrated Circuit was
especially designed for low-cost, high efficiency, lowpower fly-back off-line switching power supplies up
to approximately 50 to 70W. It contains a shuntregulator, a precision oscillator, a PWM with its
associated comparator and loop compensation
components as well as all the necessary biasing and
protection circuitry (thermal shutdown, under-voltage,
over-voltage and over-current).
It is optimized to operate with an optocoupler to
provide the feedback from the secondary but can also
be used with a bias winding which could sometimes
be more economical.
Typical applications include domestic and
international power supplies featuring AC input
ranging from 90 to 264V and DC from 100 to 350V.
In addition to being a low-cost IC, the IPS15 allows
further cost reduction for the complete power supply
thanks to:
- fewer and cheaper associated components
- a simpler, cheaper and more forgiving fly-back
transformer.
For very low power applications the IPS15 can be
powered from the rectified AC through a simple
resistor.
For higher power applications, the IPS15 is powered
through a novel patented network which replaces the
usual snubber network. AAI will grant one nonexclusive royalty free licence to use this arrangement
for each IPS15 purchased by Customers, either
directly from the company or through approved
sources.
The IN-PLUG® IPS15 can drive a large variety of
power MOSFETs hence providing the maximum
flexibility at the lowest possible cost.
FEATURES
• Lowest cost solution for low-power off-line
flyback applications.
• High performance yet forgiving.
• Simple, less critical, lower cost transformer.
• Wide range PWM for stable operation at any load
and line voltage.
• Suitable for constant-power applications.
• Operates with optocoupler or bias winding for
constant voltage applications: zeners, adjustable
shunt regulator like TL431 or dedicated feedback
controllers like AAI precision IPS22 & IPS25.
• EMI reduction in critical applications thanks to:
ƒ Adjustable operating frequency.
ƒ Separate MOSFET N & P drives
• Power shut-down for stand-by modes.
• Cycle to cycle over-current protection
• Under-voltage and over-voltage protection.
• External component savings: MOV, X-cap, Y-cap
(ESD/lightning permitting)
APPLICATIONS
• Standby power supplies for TV, VCR and IR
remotely-controlled appliances.
• Cordless and feature phones.
• Cellular phone chargers.
• Power tools fast chargers with trickle and on/off.
• Laptops and personal digital assistants.
• Utility meters.
• Replacements for bulky plug-in transformers.
PIN CONFIGURATION:
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
PDRIVE
1
DIP-8 / SOIC-8
8
GND
ISENSE
IPS15
VCC
RBIAS
NDRIVE
4
OPTO
5
OVERV
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IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
FUNCTIONAL BLOCK DIAGRAM
OVERV
OPTO
VCC
PDRIVE
UNDER
VOLTAGE
LOCKOUT
OVER
VOLTAGE
LOCKOUT
THERMAL
SHUTDOWN
PWM
_
REF1
VCC
+
SHUNT
FILTERS
REF2
COMPARATORS
ENB
_
R
Bandgap
reference
REGULATOR
Q
+
REF3
S
CURRENT
LIMITING
SOFT START
GND
ENB
OSCILLATOR
GND
RBIAS
NDRIVE
ISENSE
TYPICAL APPLICATION SCHEMATIC: AC IN 110V, 5W OUTPUT, zener regulation (EMC components not
shown).
D1
TR1
L1
OUT+
4.2 uH
Schottky
5A - 60V
Patented
Snubber Network
TRANSF-1P1S
LP=1.5mH, LS=1.5microH
C4
R2
820k
NMOSFET
1A, 600V
R1
1
2
3
4
4
1
2
R7
PDRV NDRV
ISENSE GND
VCC OPTO
RBIAS OVRV
10Meg
1/4W
8
7
6
5
D4
Zener
9.2V
C5
470uF
16V
C6
220uF
16V
U2
IPS15
D3
BRIDGE
1.5k
U1
470
D2
1/2W 1N4148
BR1
100
R1A
4.3k
R3
1N4148
+
+
3
R6
Q1
+
100pF
1KV
+
110V AC
C1
C3
10uF
250V
22uF
16V
R4
1.2
R5
C2
R8
220pF
100k
330k
PrimaryGND
OPTO-NPN
SecondaryGND
OUT-
Figure 1
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
2 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
PIN DESCRIPTION
Number
Name
Description
1
PDRIVE
Internal P drive terminal to be connected to the gate of the outside power
MOSFET. (The rising edge can be adjusted with an external resistor)
2
ISENSE
3
VCC
4
RBIAS
5
OVERV
6
OPTO
7
GND
8
NDRIVE
MOSFET current sensing. Any voltage over 700 mv @ 25°C on this pin
will stop gate pulses.
IC positive supply. The chip behaves like a 9.5 volts zener diode.
External RBIAS connection to set the operating frequency.
Over-voltage lock-out pin. @ 25°C a voltage over 4V on this pin will pull
the MOSFET gate to GND.
Feedback input
Ground
Internal N drive terminal to be connected to the gate of the outside power
MOSFET. (The falling edge can be adjusted with an external resistor)
IN-PLUG® IPS15 SERIES FUNCTIONAL DESCRIPTION
The IPS15 is a PWM controller for fly-back switching power supply applications. It has been optimized to reduce
the external component count. The principal features are:
- Low start Current.
- Shunt regulator to allow the maximum flexibility to power the chip.
- Protections against overheating, under-voltage and over-voltage.
- Precise oscillator with externally adjustable frequency.
- On-chip filters for the loop compensation and the over-current sensing.
- Soft start and over-voltage shut-down to protect the MOSFET.
- Separate MOSFET P and N drivers to adjust rising and falling edge independently.
The shunt regulator operates like a zener diode, keeping the chip supply voltage around 9.5 volts. At start-up the
chip stays in stand-by mode until the voltage of VCC reaches about 9.5 volts. During this phase, the consumption is
of the order of 120 μA. When the 9.5 volts are reached, the driver starts providing gate pulses. The chip will go back
to the stand-by mode if the supply voltage decreases down to ~8 volts. The overall chip consumption in normal
operation is about 600 μA, not counting the current required to drive the MOSFET gate.
For domestic application, the chip can be supplied from the rectified line voltage through a resistor. In such case, the
resistor has to be sized to drive enough current to the chip.
For international applications, the IC gets the start current from a resistor connected to the rectified line voltage
(~150 μA) then, after the first gate pulse, the patented modified snubber network (*) provides the additional current
to keep the chip running.
The opto pin is pulled to VCC through an internal resistor, allowing a maximal duty cycle of 60 %. During startup, the duty cycle is controlled by the internal soft start unit which smoothly increases the MOSFET current up to its
maximum, corresponding to 700mV developped across the sense resistor.
When the expected output voltage is reached, the optocoupler's led is driven, and the opto pin voltage decreases,
reducing the duty cycle to a controlled value. The current limiting protection operates by turning-off the MOSFET
when the ISENSE pin voltage exceeds ~700 mv. This ensures a cycle to cycle protection of the MOSFET and
provides a mean of operating the power supply in constant-power mode.
The voltage limiting protection operates by turning-off the MOSFET when the OVERV pin voltage exceeds 4V.
(*) US Patent # 6,233,165 - Royalty free licence for IN-PLUG® Customers.
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
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IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
AC 110V- IPS15 operations at medium load (5W)*
IPS15 operations at heavy load (15W)*
Vout
Vout
Isense
Isense
Drain
Drain
AC 250V - IPS15 operations at medium load (5W)*
IPS15 operations at heavy load (15W)*
Vout
Vout
Isense
Isense
Drain
Drain
* Together with a 1A, 600V MOSFET.
OUTPUT POWER CAPABILITY
Part Number
IPS15
Package
DIP-8 / SOIC-8
230V AC or 115V AC w/ Doubler
Up to 70W (1)
85 – 285V AC
Up to 30W (1)
Note (1): Governed by size and package of external MOSFET
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
4 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
ELECTRICAL CHARACTERISTICS
ABSOLUTE MAXIMUM RATING
Characteristics
Value
UNITS
50
mA
All analog inputs (pin 2, 4, 5, 6)
Min= -0.3, Max= +6.3V
V
Peak drive output current (pin1)
Source=100, Sink=170
mA
Shunt regulator max ICC (pin 3) - see fig 4-
Junction to case thermal resistance RθJ-C
PDIL = 42, SOIC = 45
Junction to PCB thermal resistance RθJ-A
PDIL = 125, SOIC =155
Power dissipation for TA <= 70°C
PDIL = 640, SOIC = 500
Operating junction temperature
- 40 to 150
Storage temperature range
- 55 to 150
Lead temperature (3 mm from case for 5 sec.)
PARAMETER
mW
°C
260
TEST CONDITIONS
@ 25°C unless specified
°C / W
PARAMETERS
UNITS
MIN.
TYP.
MAX.
ICC = 1 to 30 mA
9.2
9.7
10.5
V
1 to 30 mA
2
3
5
Ω
-
35
-
mA
-
-
140
μΑ
VCC – 2.2
VCC - 1.5
VCC - 1.4
V
1.1
3.2
4.9
mA
@
80KHz
@ 150KHz
655
700
745
mV
-
-
50
μV/°C
3.85
4
4.15
V
-
20
-
clock cycles
200
-
450
ns
-
150
-
°C
30
80
150
KHz
550
170
80
KΩ
-1.5
-
1.5
%
-
66
0
-
%
%
Supply, bias & circuit protection
Shunt regulator voltage
Shunt regulator dynamic
resistance (see Fig. 4)
Shunt regulator max peak
repetitive current
Min ICC to start oscillator
Under voltage lock-out
Min ICC to ensure continuous
operation
1A, 600V, 5 nC MOSFET
@ 20KHz
Current limiting sensing
voltage
Temperature coefficient of
current limiting
Overvoltage sensing voltage
Soft/start duration
0 to 700mV
Leading edge blanking
Thermal shutdown trip
temperature
Oscillator & PWM
Range of operating
frequencies
RBIAS values for above
frequencies (see figure 2)
Oscillator stability with
supply & temperature
(see figure 3 for average)
Maximum duty cycle
Minimum duty cycle
ICC = 5 mA
Temp = 0 to 70°C
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
5 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
ELECTRICAL CHARACTERISTICS (cont’d)
PARAMETER
TEST CONDITIONS
PARAMETERS
@ 25°C unless specified
UNITS
MIN.
TYP.
MAX.
-
54
95
mV
Error amplifier
Sensitivity in mV / % of PWM
Voltage for max duty cycle
OPTO pin
-
4
-
V
Voltage for min duty cycle
OPTO pin
-
0.5
-
V
Input impedance
OPTO pin
-
60
-
KΩ
P gate driver saturation
10 mA (source)
-
-
1
V
N gate driver saturation
10 mA (sink)
-
-
0.6
V
Gate pull-down resistor
(internal)
280
400
520
KΩ
PDRIVE Rise time (10% to
90%)
240 pF load
-
250
-
ns
NDRIVE Fall time (10% to
90%)
240 pF load
-
100
-
ns
@ 20 KHz
-
-
100
nC
“
@ 80 KHz
-
-
50
nC
“
@ 150 KHz
-
-
15
nC
P & N Outputs to MOSFET gate
Max recommanded total
external MOSFET charge
Note: Electrical parameters, although guaranted, are not all 100% tested in production.
F ig u re 2 : F re q u e n c y vs R b ia s
190
170
Frequency (kHz)
150
130
110
90
70
50
30
10
0
50
100
150
200
250
300
350
400
450
500
550
R b ia s (k O h m )
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
6 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
Figure 3 Frequency drift vs temperature
Frequency variation (%)
2.00
1.00
ICC=5m A
0.00
-1.00
-2.00
-20
-10
0
10
20
30
40
50
60
70
80
90
100
Tem perature (°C)
Figure 4 Shunt regulator Icc current
50
40
Icc (mA)-
30
20
10
0
0
2
4
6
8
10
12
14
Vcc (V)
ORDERING INFORMATION
Part No.
ROHS /
Package
Temperature Range
Pb-Free
IPS15C-D
-G-LF
8-Pin PDIP
0°C to +70°C
Commercial
IPS15I-D
-G-LF
8-Pin PDIP
-40°C to +85°C
Industrial
IPS15C-SO
-G-LF
8-Pin SOIC
0°C to +70°C
Commercial
IPS15I-SO
-G-LF
8-Pin SOIC
-40°C to +85°C
Industrial
For detailed ordering information, see page 14
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
7 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
GOOD DESIGN PRACTICES
IPS15 and loop stability:
The IPS15 is intrinsically very fast and doesn’t participate to the loop stability. It only involves a comparator that
doesn’t bring any gain and exhibits a negligible phase shift.
It has been designed on purpose to allow its utilization in a large range of applications:
(a) Operating at frequencies up to 200 kHz and even above,
(b) Involving very different types of loop stability from "cycle skipping" where the loop is not compensated at all
(figure 1), to good stability achieved through the utilization of a TL431 (figure 5) and finally superior transient
response when using the IPS25 feedback controller (figure 6).
The loop compensation is entirely achieved on the load side and the feedback is performed by an optocoupler which
gain and dynamic response play an important role in the loop stability.
Precaution in selecting the optocoupler:
The optocoupler must be using a Phototransistor and NOT a Photodarlington. Most optocouplers of this type are
offered in a wide range of coupling efficiency, also called transfer ratio. Even the cheapest ones have a guaranteed
transfer ratio of the order of 100% meaning that 1mA of current in the IR LED creates approximately 1mA of
current in the receiving phototransistor. The user should be able to design the loop to be stable even though the
actual transfer ratio differs by more than a factor of 3 (example from 100% to 300% or 50% to 150%).
Unfortunately optocouplers were not designed for low-current applications and this results in very bad speed and
saturation characteristics for the phototransistor which could become incredibly slow and create severe loop stability
problems should it be allowed to saturate hard in the application (the optocoupler could cause the IPS15 to skip
cycles due to the long time required by the opto transistor to go out of saturation).
In the example of figure 5, the output voltage is 10 volts as defined by R15 and R16 and 2.5V at the Pin #1 of the
TL431. The cathode of the TL431 can go to a voltage as low as 2 Volts. The IR LED requires approximately 1 Volt
which means that the voltage drop across R14 could be up to 6 volts resulting in a maximum current of 700uA. This
value is plentiful for the utilization of a broad range of optocouplers and yet small enough to avoid hard saturation.
Loop stability with the TL431:
The TL431 has an enormous DC gain and will not ensure stability unless specific loop-compensation components
such as a RC network are added as indicated below.
The RC network should have a cut-off frequency at 100Hz to roll-off the gain at low frequencies but reach a
plateau around 100Hz and have enough AC gain at twice the line frequency and achieve a good line ripple
rejection.
This is achieved by the loop compensation network C7, R17 of figure 5. The gain rolls off until the impedance of
C7 reaches the value of R7. At much higher frequencies, the gain continue to roll-off due to the natural frequency
response of the TL431.
The goal is to reach a very low gain at the switching frequency.
If the addition of C7 & R17 with values as shown results in gain is too low, the values of R15 & R16 should be
reduced in proportion to lower the impedance at Pin #1 of TL 431. Alternately, if the gain is too high the values of
R17 should be reduced and C7 re-adjusted accordingly to maintain the required cut-off frequency.
Criteria to calculate the network :
1) R17 must be much higher than the input resistance of TL431 constituted by R16//R15=5K Æ 68Kohm OK.
2) F=100Hz=1/(2 x 3.14 x R17 x C7) gives approximately 22,000 pF for C7.
Discontinuous operation:
Check discontinuous mode of operation of the transformer (see application note AN-IPS02 page 2 for details)
to ensure that the Flyback SMPS is indeed operating in discontinuous mode in the entire range of Input Voltages
and Output Current. The response of the SMPS drastically changes in continuous mode, it gets considerably slower
which requires a totally different loop compensation technique. Remember that it is very difficult to ensure loop
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
8 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
stability with a simple schematic when the SMPS is allowed to transition between Discontinuous and Continuous
modes.
MOSFET driver protection:
The MOSFET driver has been sized to be capable of driving power MOSFETs featuring a total gate charge up to
100nC.
The MOSFET should be turned-on relatively slowly and turned-off much faster. As shown below, these 2
parameters can be independently adjusted through the external resistors R10 (pin1) and R10A (pin8).
The minimum value of these resistors should be 50Ω in order to reduce EMI and minimize the noise injection which could
result from Miller-capacitance kick-back during transient conditions.
See application note AN-IPS-02 for EMI reduction techniques.
APPLICATION 2: AC IN 85-260V, 5 – 10W OUTPUT, voltage regulation with TL431.
L1
D3
TX1 EI/EE FERRITE
OUT+
330uH
Schottky
1A - 60V
Patented
Snubber Network
C4
120pF
600V
+
4
C2
1K
1/2W
400V
R10
NMOSFET
1A, 600V
4.3k
SMT
1
2
3
4
430k
SMT
C7
8
7
6
5
U2
+
C3
4.7uF
400V
10uF
16V
R4
OUTPUT
U3
3
R5
2.2
SMT
C6
470uF
16V
Loop Compensation
OPTO Q817C
+
C1
R17
10Meg
1/4W
IPS15
2 x 1N4148
2
R12
1.5k
SMT
PDRV NDRV
ISENSE GND
VCC OPTO
RBIAS OVRV
R15
4.7K
10k
R10A
U4
D3
BRIDGE
R14
Q1
R2A
D2
1
BR1
390k
SMT
R3
4.7uF
3
Noise-Canceling Type
LP=1.5mH
LS=1.5microH
R2
+
INPUT
90V-270V AC
R11
330k
SMT
PrimaryGND
1
REF
2
C1
100k
SMT
K
A
R16
TL431
220pF
SMT
10k
SecondaryGND
OUT-
R11 and R12 to be adjusted for max line overvoltage protection
R4 controls max pick current
when the ISENSE pin voltage exceeds ~700 mv
R15 and R16 to be adjusted according to output voltage
Figure 5
APPLICATION 2: AC IN 85-260V, 0 – 5W OUTPUT, current & voltage regulation with IPS25.
L1
D3
TX1 EI/EE FERRITE
OUT+
330uH
Schottky
1A - 60V
R6
INPUT
C4
90V-270V AC
120pF
600V
4
+
C2
4.7uF
BR1
390k
4.3k
1
2
3
4
R2A
430k
SMT
R12
1.5k
PDRV NDRV
ISENSE GND
VCC OPTO
RBIAS OVRV
8
7
6
5
10Meg
1/4W
+
C1
C3
4.7uF
400V
10uF
16V
+
2 x 1N4148
R4
+
30k
1.5
330k
C1
220pF
100k
OUTPUT
C5
100uF
16V
105°C
R1
10k
U3
C9
R11
8
7
6
5
R9
R7
R5
VCC
ISENSE
VSENSE
N/C
VCOMP ICOMP
OPTO
GND
IPS25
C6
470uF
16V
105°C
IPS15
D2
2
R10A
U1
D1
1
BRIDGE
R10
R3
1K
1/2W
1
2
3
4
Q1
NMOSFET
1A, 600V
400V
3
R2
U2
23.7k
1%
13mm Noise-Canceling Type
LP=1.5mH, LS=1.5microH
+
Patented
Snubber Network
OPTOCOUPLER
PrimaryGND
25.5k
1%
0.068uF
C10
220pF
C8
0.068uF
R8
SecondaryGND
OUT3.3
Figure 6
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
9 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
OUTPUT CORD SERIAL RESISTANCE COMPENSATION WITH THE IPS25 FEEDBACK CONTROLLER
L1
D3
TX1 EI/EE FERRITE
330uH
R6
C4
120pF
600V
4
+
C2
4.7uF
BR1
390k
NMOSFET
1A, 600V
430k
SMT
R12
1.5k
PDRV NDRV
ISENSE GND
VCC OPTO
RBIAS OVRV
8
7
6
5
10Meg
1/4W
C6
470uF
16V
105°C
+
C1
C3
4.7uF
400V
10uF
16V
+
2 x 1N4148
R4
1.5
330k
30k
C1
R11
100k
OUTPUT
C5
100uF
16V
105°C
R1
10k
U3
C9
220pF
8
7
6
5
R9
R7
R5
VCC
ISENSE
VSENSE
N/C
VCOMP ICOMP
OPTO
GND
IPS25
+
IPS15
D2
2
R10A
4.3k
1
2
3
4
R2A
D1
1
BRIDGE
R10
U1
1K
1/2W
1
2
3
4
Q1
R3
400V
3
R2
U2
23.7k
1%
13mm Noise-Canceling Type
LP=1.5mH, LS=1.5microH
+
INPUT
90V-270V AC
To cord (+)
Schottky
1A - 60V
Patented
Snubber Network
OPTOCOUPLER
25.5k
1%
0.068uF
C10
C8
220pF 0.068uF
R8
R13
Figure 7
To cord (-)
3.3
SecondaryGND
PrimaryGND
R14
Positive feed-back for cord
serial resistance compensation
The voltage drop due to the output serial resistance of the cord can be
compensated by adding a voltage positive feedback to the IPS25 input pin
VSENSE, proportional to Vdrop. This can be achieved either by splitting R8
(output current sensing resistor) in two or by inserting 2 serial resistors R13 and
R14 in parallel to R8 and connect the positive feedback to the intermediate node.
R13 and R14 should be calculated, based on the following conditions:
- (R13 + R14) ≥ 20 x R8 (but should remain low impedance in regards to R7),
- Vint ~ Vdrop, where Vint is the intermediate voltage measured on the
common node of R13 and R14, and Vdrop is the voltage drop across the
cord serial resistor.
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
SMPS with output cord
- Revision 12 – April 02, 2007
10 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
ADDITIONAL RECOMMENDATIONS:
For best results in low power off-line SMPSs with the IPS15, the following MOSFET features are recommended:
- Low gate charge (max 50 nC).
- 400 V breakdown voltage for domestic use (USA / Japan).
- 600V breakdown voltage for European use (800V when transformer leakage inductance is very small).
- 1, 2 or 3A depending on the maximum output power.
Examples of suitable MOSFETS:
- IXYS PolarHT™ and Polar HV™ MOSFET series: IXTY1R4N60P, IXTY2N60P, IXTY3N60P
- Fairchild MOSFET series: FQPF1N60, FQPF 2N60, FQPF 3N60.
- Infineon COOLMOSTM series: SPD01N60S5, SPD02N60S5, SPD03N60S5.
- Motorola MOSFET series: MTP1N60, MTP2N60, MTP3N60.
- SGS-Thomson MOSFET series: STD1NB60, STD2NB60, STD3NB60.
- Etc…
Notes:
- Due to the rapid evolution of MOSFET technologies, please check for current models when designing a new
SMPS.
- PolarHT™ and Polar HV™ are trademarks of IXYS corporation
- COOLMOSTM is a trademark of Infineon.
TRANSFORMER CHARACTERISTICS:
(a) Transformer design:
E-core with suitable gap to prevent saturation or distributed-gap toroid. Primary inductance of 1.5 mH is very
typical.
Turn ratio = 9 for 220V input or universal 85V – 265V.
Turn ratio = 7 for 100-120V AC input (Japan and USA)
(b) Transformer phasing:
Check the phase as indicated in figure 1 , 5 and 6. Also refer to application notes AN-IPS-01 and AN-IPS-02.
SNUBBER NETWORK:
With reference to figure 1, R2 provide the start-up current for the chip. C3 is being charged through R2. Once the
chip supply voltage is high enough, the gate drive starts and the chip is then powered by the modified snubber
network patented by our company.
The snubber values may have to be optimized for different specific operating conditions:
- R3 could be reduced to 100 ohms and sometimes eliminated.
- C4 could be increased to 200pF and sometimes more.
Depending on the characteristics of the transformer, essentially leakage inductance and distributed capacitance, the
snubber network shown in figure 1, may not be efficient enough to reduce the voltage spikes when operating at 20W
or above. Please refer to applications notes AN-IPS-01 and AN-IPS-02 design tips or EMI reduction techniques, or
feel free to contact our technical support for assistance.
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
11 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
POWER SHUT-DOWN SOLUTIONS for STAND-BY REQUIREMENTS:
For low-power stand-by requirements, the primary circuitry can be shut-down by pulling the IPS15 VCC pin
“LOW” through a 100Ω resistor.
This can be easily done using a:
• Simple switch
• PNP transistor
• NPN transistor
SHUT-DOWN SOLUTIONS
D1
TR1
L1
OUT+
4.2 uH
Schottky
5A - 60V
Patented
Snubber Network
TRANSF-1P1S
LP=1.5mH, LS=1.5microH
R2
820k
NMOSFET
1A, 600V
R6
R1
1.5k
1
2
3
4
4
1
PDRV NDRV
ISENSE GND
VCC OPTO
RBIAS OVRV
2
10Meg
1/4W
8
7
6
5
D4
Zener
9.2V
C5
470uF
16V
C6
220uF
16V
U2
IPS15
D3
BRIDGE
R7
U1
470
D2
1/2W 1N4148
BR1
100
R1A
4.3k
R3
1N4148
+
+
3
Q1
+
100pF
1KV
+
C4
110V AC
C1
C3
10uF
250V
22uF
16V
R4
1.2
R5
330k
C2
R8
220pF
100k
OPTO-NPN
SecondaryGND
PrimaryGND
OUT-
SHUT-DOWN
SOLUTIONS
1,2 or 3
Figure 6
Solution 1:
simple switch, close = off
100Ω resistor
mandatory
100 Ω
Solution 2:
PNP transistor, low = off
(low = less than 4V)
100Ω resistor
optional
100 Ω
Solution 3:
NPN transistor, high = off
100Ω resistor
optional
100 Ω
high = off
close = off
low = off
When the "LOW" state is released, the VCC is naturally re-established, re-activating the IPS15.
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
12 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
PACKAGE DIMENSIONS
PLASTIC DIP-8
PLASTIC SOIC-8
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
13 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
ORDERING INFORMATION
Part-Number
IPS XXXH
C – YY – G-LF - TR
Tape and Reel
TR : Tape & Reel
TU : Tube
Note1 : Default or not specified
is « tube ».
Note2 : Does not appear on
package marking.
IN-PLUG® Controller Series
Flyback
Feedback
PFC
Push-Pull
LED Driver
ROHS + Pb-Free
Package Type
Controller Type
Flyback: 10 series
Feedback: 20 series
PFC: 100 series
Push-Pull: 200 series
LED Driver: 400 series
“H” with hiccup overload protection
D : DIP8
SO : SOIC8
(For production with a new date code, after January
2006, the package type will not appear anymore on
package marking)
Temperature Range
C : Commercial (0, +70°C)
I : Industrial (-40°C. +85°C)
Note : Default or not specified is <commercial>
Example of Marking
AAI
IPS15HC
YYWW
Non-Green Package
AAI G-LF
IPS15HC
YYWW
Green ROHS + Pb-Free Package
(Note : For production with a new date code, since January 2006, the package type does not appear anymore on package
marking)
This ordering information is for commercial and industrial standard IN-PLUG® controllers ONLY. For custom controllers or for
automotive and military temperature ranges, call AAI’s sales representative.
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
14 / 15
IN-PLUG® IPS15 Datasheet – Rev.12 - Low cost, High Efficiency, Low Power off-line Switcher
The following is a brief overview of certain terms and conditions of sale of product. For a full and complete copy of all
the General Terms and Conditions of Sale, visit our webpage http://www.asicadvantage.com/terms.htm.
LIMITED WARRANTY
The product is warranted that it will conform to the applicable specifications and be free of defects for one year.
Buyer is responsible for selection of, use of and results obtained from use of the product. Buyer indemnifies and
holds ASIC Advantage, Inc. harmless for claims arising out of the application of ASIC Advantage, Inc.’s products to
Buyer’s designs. Applications described herein or in any catalogs, advertisements or other documents are for
illustrative purposes only.
CRITICAL APPLICATIONS
Products are not authorized for use in critical applications including aerospace and life support applications. Use of
products in these applications is fully at the risk of the Buyer. Critical applications include any system or device
whose failure to perform can result in significant injury to the user.
LETHAL VOLTAGES
Lethal voltages could be present in the applications. Please comply with all applicable safety regulations.
INTELLECTUAL PROPERTY RIGHTS AND PROPRIETARY DATA
ASIC Advantage, Inc. retains all intellectual property rights in the products. Sale of products does not confer on Buyer
any license to the intellectual property. ASIC Advantage, Inc. reserves the right to make changes without notice to
the products at any time. Buyer agrees not to use or disclose ASIC Advantage Inc.’s proprietary information without
written consent.
TRADEMARKS AND PATENTS
- IN-PLUG® is a registered trademark of ASIC Advantage, Inc.
- AAI’s modified snubber network is patented under the US Patent # 6,233,165. IN-PLUG® Customers are granted
a royalty-free licence for its utilization, provision the parts are purchased factory direct or from an authorized agent.
PROTECTION FOR CUSTOM IN-PLUG® SOLUTIONS
When AAI accepts to design and manufacture IN-PLUG® products to Buyer’s designs or specifications, buyer has
certain obligations to provide defense in a suit or proceeding claiming infringement of a patent, copyright or trademark
or for misappropriation of use of any trade secrets or for unfair competition.
COMPLIANCE WITH LAWS
Buyer agrees that at all times it will comply with all applicable federal, state, municipal, and local laws, orders and
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required U.S. Government license, authorization, or approval. Buyer shall pay any duties, levies, taxes, brokerage
fees, or customs fees imposed on the products.
TITLE AND DELIVERY
All shipments of goods shall be delivered ExWorks, Sunnyvale, CA, U.S.A. Title in the goods shall not pass to Buyer
until ASIC Advantage, Inc. has received in full all amounts owed by Buyer.
LATEST DATASHEET UPDATES
For the latest datasheet updates, visit our web page: http://www.in-plug.com/datasheets.htm.
WORLDWIDE REPRESENTATIVES
To access AAI’s list of worldwide representatives , visit our web page http://www.in-plug.com/representatives.htm
COPYRIGHTS
Copyrights and all other proprietary rights in the Content rests with ASIC Advantage Inc. (AAI) or its licensors. All
rights in the Content not expressly granted herein are reserved. Except as otherwise provided, the Content published
on this document may be reproduced or distributed in unmodified form for personal non-commercial use only. Any
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retained on all reproductions.
ASIC Advantage INC.
1290-B Reamwood Ave, Sunnyvale California 94089, USA
Tel: (1) 408-541-8686 Fax: (1) 408-541-8675
Websites: http://www.in-plug.com - http://www.asicadvantage.com
© Copyright 2003-2007 - ASIC Advantage, Inc. – All rights reserved
- Revision 12 – April 02, 2007
15 / 15