OPA360 SB0S294C − DECEMBER 2003 − REVISED JULY 2004 3V Video Amplifier with 6dB Gain and Filter in SC70 FEATURES DESCRIPTION D D D D The OPA360 high-speed amplifier is optimized for 3V portable video applications. It has been specifically designed to be compatible with digital-to-analog converters (DACs) embedded in video processors, such as Texas Instruments’ family of Digital Media Processors and others. The input common-mode range includes GND, which allows the Video-DAC to be DC-coupled to the OPA360. EXCELLENT VIDEO PERFORMANCE INTERNAL GAIN: 6dB 2−POLE RECONSTRUCTION FILTER SAG CORRECTION − Reduces Coupling Capacitor Size D INPUT RANGE INCLUDES GROUND The output swings within 25mV of GND and 300mV to V+ with a standard back-terminated video load (150Ω). An internal level shift circuit prevents the output from saturating with 0V input, thus preventing sync-pulse clipping in common video circuits. Therefore, the OPA360 is ideally suited for DC-coupling to the video load. If AC-coupling is preferred, the OPA360 offers a sag-correction feature that significantly reduces the size of the output coupling capacitor. − DC-Coupled Input D INTEGRATED LEVEL SHIFTER − DC-Coupled Output(1) − No Output Capacitors Needed D D D D D RAIL-TO-RAIL OUTPUT LOW QUIESCENT CURRENT: 6mA SHUTDOWN CURRENT: 5mA SINGLE-SUPPLY: 2.7V to 3.3V SC70-6 PACKAGE: 2.0mm x 2.1mm (1) Internal circuitry prevents the output from saturating, even with 0V sync tip level at the input video signal. APPLICATIONS The OPA360 has been optimized for space-sensitive applications by integrating sag-correction, internal gain setting resistors (G = 2), and a 2-pole video-DAC reconstruction filter. In shutdown mode, the quiescent current is reduced to < 5µA, dramatically reducing power consumption and prolonging battery life. The OPA360 is available in the tiny 2mm x 2.1mm SC70-6 package. D DIGITAL CAMERAS D CAMERA PHONES D SET-TOP-BOX VIDEO FILTERS V+ = 2.7V to 3.3V V+ RELATED LOW VOLTAGE VIDEO AMPS FEATURES OPA360 PRODUCT 2.7V to 5.5V, 200MHz GBW, 300V/µs, 6µA Sleep, SOT23 OPA355 2.7V to 5.5V, RRIO, 150V/µs, 5mA IQ, 6µA Sleep, SOT23 2.7V to 3.3V, SC70, 70MHz, 6mA IQ, 5µA Sleep OPA357 OPA358(1) 2.7V to 3.3V, SC70, Filter, SAG, G = 12dB, 5µA Sleep OPA361(1) VIN ENABLE Level Shifter 2−Pole Filter VO 6dB SAG (1) Available Q4 2004. GND Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. Copyright 2003−2004, Texas Instruments Incorporated ! ! www.ti.com "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 PRELIMINARY ORDERING INFORMATION(1) PRODUCT PACKAGE PACKAGE DESIGNATOR SPECIFIED TEMPERATURE RANGE PACKAGE MARKING OPA360 SC70-6 DCK −40°C to +85°C AUW ORDERING NUMBER TRANSPORT MEDIA, QUANTITY OPA360AIDCKT Tape and Reel, 250 OPA360AIDCKR Tape and Reel, 3000 (1) For the most current package and ordering information, see the Package Option Addendum located at the end of this datasheet. This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ABSOLUTE MAXIMUM RATINGS(1) Supply Voltage, V+ to V− . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +3.6V Signal Input Terminals, Voltage(2) . . . . (V−) −0.5V to (V+) + 0.5V Current(2) . . . . . . . . . . . . . . . . . . . ±10mA Output Short-Circuit through 75Ω to GND(3) . . . . . . . Continuous ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. Operating Temperature . . . . . . . . . . . . . . . . . . . . . . −40°C to +85°C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . −65°C to +150°C Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +160°C Lead Temperature (soldering, 10s) . . . . . . . . . . . . . . . . . . . . +300°C (1) Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may degrade device reliability. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those specified is not implied. (2) Input terminals are diode-clamped to the power-supply rails. Input signals that can swing more than 0.5V beyond the supply rails should be current-limited to 10mA or less. (3) Short-circuit to ground, one amplifier per package. PIN CONFIGURATION OPA360 1 GND 2 SAG 3 LPF AUW +In SC70−6(1) (1) Pin 1 of the SC70-6 is determined by orienting the package marking as indicated in the diagram. 2 6 V+ 5 Enable 4 Out "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 ELECTRICAL CHARACTERISTICS: VS = +2.7V to +3.3V Single-Supply Boldface limits apply over the temperature range, TA = −40°C to +85°C. All specifications at TA = +25°C, RF = 150kΩ connected to GND, unless otherwise noted. OPA360 PARAMETER OFFSET LEVEL-SHIFT VOLTAGE Output Level-Shift Voltage(1) VOLS Over Temperature vs. Power Supply PSRR CONDITIONS MIN TYP MAX VS = +3.3V, VIN = GND, G = +2 Specified Temperature Range 30 60 80 VS = +2.7V to +3.3V UNITS mV 60 mV ±80 µV/V ±3 pA INPUT BIAS CURRENT Input Bias Current IB INPUT VOLTAGE RANGE Common-Mode Voltage Range(2) VCM VS = 3.3V, G = +2 GND (V+) − 1.5 V VS = +3.3V, 0 < VIN < 1.5V 5.8 6 6.2 dB VO = 2VPP VO = 2VPP −0.6 −0.1 +0.4 dB −18 −21 dB 0.5 % Differential Phase Error RL = 150Ω RL = 150Ω 1 ° Group Delay Variation 100kHz, 5MHz 13 ns 100% White Signal 70 dB VS = +3.3V, G = 2, VIN = 2V, RL = 150Ω to GND VS = +3.3V, G = 2, VIN = 0V, RL = 150Ω to GND 160 300 mV 3 25 mV VS = +3.3V, G = 2, VIN = 2V, RL = 75Ω to GND VS = +3.3V, G = 2, VIN = 0V, RL = 75Ω to GND 300 mV 10 mV VS = +3.3V ±80 mA VOLTAGE GAIN FREQUENCY RESPONSE Filter Response Normalized Gain: fIN = 4.5MHz fIN = 27MHz Differential Gain Error Signal-to-Noise Ratio SNR OUTPUT Positive Voltage Output Swing from Rail Negative Voltage Output Swing from Rail Positive Voltage Output Swing from Rail Negative Voltage Output Swing from Rail Output Current(3) IO POWER SUPPLY Specified Voltage Range VS 2.7 Minimum Operating Voltage Range Quiescent Current 3.3 V 7.5 mA 9 mA 0.8 V 2.5 to 3.6 IQ VS = +3.3V, Enabled, IO = 0 Specified Temperature Range 6 V ENABLE/SHUTDOWN FUNCTION Disabled (logic-LOW Threshold) Enabled (logic-HIGH Threshold) 1.6 Enable Time V µs 1.5 Disable Time 50 Shutdown Current VS = +3.3, Disabled 2.5 ns 5 µA TEMPERATURE RANGE Specified Range −40 +85 °C Operating Range −40 +85 °C Storage Range −65 +150 °C Thermal Resistance qJA SC70 250 °C/W (1) Output referred. Tested with SAG pin connected to OUT pin. (2) Limited by output swing and internal G = 2. Tested with the SAG pin connected to OUT pin. (3) See typical characteristics Output Voltage Swing vs Output Current. 3 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 TYPICAL CHARACTERISTICS: VS = 3.3V At TA = +25°C and RL = 150Ω, unless otherwise noted. Normalized Gain at 4.5MHz Production Distribution FREQUENCY RESPONSE 5 Normalized: ”0” dB corresponds to 6dB gain. −5 −10 Population Normalized Gain (dB) 0 −15 −20 −25 −30 −35 −0.125 100M 0.05 0.075 0.1 10M −0.05 −0.025 0 0.025 1M Frequency (Hz) −0.225 −0.2 −0.175 −0.15 −0.125 −0.1 −0.075 100k −0.325 10k −0.3 −0.275 −0.25 −40 Normalized Gain at 4.5MHz (dB) GAIN ERROR 2.0 40 1.8 35 1.6 30 Gain Error (%) Group Delay (ns) GROUP DELAY vs FREQUENCY 45 25 20 15 1.0 0.8 0.6 0.4 5 0.2 0 10k 3.3 3.2 3.1 3.0 2.9 2.8 2.7 2.6 2.5 2.4 2.3 2.2 2.1 2.0 100k 1M 10M −50 −25 0 25 50 75 100 Frequency (Hz) Temperature (_ C) OUTPUT VOTLAGE SWING TO THE POSITIVE RAIL vs OUTPUT CURRENT OUTPUT VOLTAGE SWING TO THE NEGATIVE RAIL vs OUTPUT CURRENT 125 0.30 VS = 3.3V VS = 3.3V, VIN = 0V −40_ C +25_C +125_C 0.25 Output Voltage (V) Output Voltage (V) 1.2 10 0 +85_C 0.20 0.15 +25_ C −40_ C 0.10 +125_ C 0.05 +85_C 0 0 0.01 0.02 0.03 0.04 0.05 0.06 0.07 0.08 0.09 0.1 Output Current (A) 4 1.4 0 0.01 0.02 0.03 0.04 0.05 0.06 0.07 0.08 0.09 0.1 Output Current (A) "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 TYPICAL CHARACTERISTICS: VS = 3.3V (continued) At TA = +25°C and RL = 150Ω, unless otherwise noted. QUIESCENT CURRENT vs TEMPERATURE 8.0 6 7.5 VS = 3.3V Quiescent Current (mA) Quiescent Current (mA) QUIESCENT CURRENT vs SUPPLY VOLTAGE 7 5 4 3 2 7.0 6.5 6.0 5.5 1 0 5.0 −50 2.0 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3.0 3.1 3.2 3.3 −25 0 25 Supply Voltage (V) 50 75 100 125 150 Temperature (_C) SHUTDOWN CURRENT vs TEMPERATURE DIFFERENTIAL GAIN 3.0 Shutdown Current (µA) 2.5 DIFFERENTIAL PHASE VS = 3.3V 2.0 1.5 1.0 0.5 0 −50 −25 0 25 50 75 100 125 Temperature (_C) SHUTDOWN TRIGGER LEVELS LARGE−SIGNAL DISABLE/ENABLE RESPONSE Enable Voltage (500mV/div) Quiescent Current (mA) 6 4 OPA360 Shutdown OPA360 Active 2 OPA360 Output Disable 0 1.4 1.45 1.5 1.55 1.6 Time (1µs/div) Enable Pin Voltage (V) 5 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 APPLICATIONS INFORMATION The OPA360 video amplifier has been optimized for portable video applications: D Internal gain setting resistors (G = 2) reduce the number of external components needed in the video circuit. D A 2-pole filter is incorporated for DAC signal reconstruction. D The sag correction function reduces the size of the output coupling capacitors without compromising performance. D OPA360 employs an internal level shift circuit that avoids sync pulse clipping and allows DC-coupled output. D A shutdown feature reduces quiescent current to less than 5µA—crucial for portable applications such as digital still cameras and camera phones. The OPA360 interfaces to digital media processors (DM320/270, DSC25). It has been optimized for the requirements of digital still cameras and cell phone/camera designs. OPERATING VOLTAGE The OPA360 is fully specified from 2.7V to 3.3V over a temperature range of −40°C to +85°C. Parameters that vary significantly with operating voltages or temperature are shown in the Typical Characteristics. Power-supply pins should be bypassed with 100nF ceramic capacitors. INPUT VOLTAGE The input common-mode range of the OPA360 series extends from GND to (V+) − 1.5V. Because of the internal gain, the input voltage range necessary for an output in the valid range will be limited. INPUT OVERVOLTAGE PROTECTION All OPA360 pins are static-protected with internal ESD protection diodes connected to the supplies. These diodes will provide input overdrive protection if the current is externally limited to 10mA ENABLE/SHUTDOWN The OPA360 has a shutdown feature that disables the output and reduces the quiescent current to less than 5µA. This feature is especially useful for portable video applications such as digital still cameras (DSC) and camera phones, where the equipment is infrequently connected to a TV or other video device. The Enable logic input voltage is referenced to the OPA360 GND pin. A logic level HIGH applied to the enable pin enables the op amp. A valid logic HIGH is defined as ≥ 1.6V above GND. A valid logic LOW is defined as ≤ 0.8V above GND. If the Enable pin is not connected, internal pull-up circuitry will enable the amplifier. Enable pin voltage levels are tested for a valid logic HIGH threshold of 1.6V minimum and a valid logic LOW threshold of 0.8V maximum. INTERNAL 2-POLE FILTER The OPA360 filter is a Sallen-Key topology with a 9MHz cutoff frequency. This allows the video signals to pass without any visible distortion, as shown in Figure 3 through Figure 5. The video DACs embedded in TI’s Digital Media Processors over-sample at 27MHz. At this frequency, the attenuation is typically 21dB, which effectively attenuates the sampling aliases. The filter characteristics vary somewhat with signal source impedance. A source impedance greater than 500Ω can degrade filter performance. With current-output video DACs, a resistor to GND is often used to create a voltage output which is then applied to the OPA360 input (see Figure 1). TI’s Digital Media Processors, such as the DM270 or DM320, typically use a 200Ω resistor to GND to convert the current output signal. This 200Ω source impedance does not degrade video performance. 10pF 1.1kΩ ( Television 1.4kΩ ) VO (1) 75Ω 12pF R 845Ω 325Ω NOTE: (1) Optional. 528Ω 75Ω SAG 650Ω OPA360 Figure 1. Filter Structure of OPA360 6 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 A capacitor placed in parallel with the resistor (Figure 1) creates an additional filter pole that provides additional stop-band attenuation. With a 200Ω source impedance, a 67pF ceramic capacitor provides approximately 28dB attenuation at 27MHz without affecting the pass band. VIDEO PERFORMANCE of amplitude and group delay errors across the video baseband. D Chrominance-to-luminence (CCIR17) — tests amplitude, phase and some distortion D 50Hz, 1/2 black−1/2 white screen test signal—tests the worst case signal swing required by the amplifier. Performance on these test signals are shown. Industry standard video test patterns include: D Multiburst—packets of different test frequencies to check for basic frequency response. D Multipulse—pulses modulated at different frequencies to test for comprehensive measurement Figure 2 shows the test circuits for Figure 3 through Figure 13 and Figure 16. (NOTE: 1 and 2 indicate measurement points corresponding to the waveforms labeled 1 and 2 in the figures.) 2 1 2 1 47µF 22µF SAG a. Test circuit for Figures 3−5. b. Test circuit for Figures 6, 8, and 16. 1 1 2 1 2 COUT 220µF 22µF 22µF c. Test circuits for Figures 10 and 11. d. Test circuit for Figures 7, 12, and 13. NOTE: 1 and 2 indicate measurement points corresponding to the waveforms labeled 1 and 2 in the figures. Figure 2. Test Circuits Used for Figures 2−13 7 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 FREQUENCY RESPONSE OF THE OPA360 Frequency response measurements evaluate the ability of a video system to uniformly transfer signal components of different frequencies without affecting their respective amplitudes. Figure 3 shows the multiburst test pattern; Figure 4 shows the multipulse. The top waveforms in these figures show the full test pattern. The middle and bottom waveform are a more detailed view of the critical portion of the full waveform. The middle waveform represents the input signal from the video generator; the bottom waveform is the OPA360 output to the line. Chrominance-to-luminence gain inequality (or relative chrominance level) is a change in the gain ratio of the chrominance and luminence components of a video signal, which are at different frequencies. A common test pattern is the pulse in test pattern CCIR 17, shown in Figure 5. As in Figure 3 and Figure 4 the top waveform shows the full test pattern, the middle and bottom waveform are a more detailed view of the critical portion of the full waveform, with the middle waveform representing the input signal from the video generator and the bottom waveform being the OPA360 output to the line. Figure 3. Multiburst (CCIR 18) Test Pattern (PAL) Figure 5. CCIR 17 Test Pattern (PAL) Gain errors most commonly appear as attenuation or peaking of the chrominance information. This shows up in the picture as incorrect color saturation. Delay distortion will cause color smearing or bleeding, particularly at the edges of objects in the picture. It may also cause poor reproduction of sharp luminence transitions. All waveforms in Figure 3 through Figure 5 were taken using the sag correction feature of OPA360. Figure 3 through Figure 5 show that the OPA360 causes no visible distortion or change in gain throughout the entire video frequency range. INTERNAL LEVEL SHIFT Figure 4. Multipulse Test Pattern (PAL) 8 Many common video DACs embedded in digital media processors like TI’s TMS320DM270 and the new OMAP2420 processors operate on a single supply (no negative supply). Typically, the lowest point of the sync pulse output by these Video DACs corresponds to 0V. With a 0V input, the output of common single-supply op amps saturates at a voltage > 0V. This effect would clip the tip of the sync pulse and therefore degrade the video signal integity. The OPA360 employs an internal level shift circuit to avoid clipping. The input signal is typically shifted by "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 approximately 60mV. This is well within the linear output voltage range of the OPA360 with a standard 150Ω video load. Figure 6 shows the function of the level shifter. Figure 7. Output Swing with 33mF on 3V Supply OUTPUT SWING TO GND (SYNC PULSE) Figure 6. Internal Level Shifter, Shifts Input Signal by Approximately 60mV to Prevent Sync Tip Clipping Figure 8 shows the true output swing capability of the OPA360 by taking the tip of the input sync pulse to a slightly negative voltage. Even when the output sync tip is at 8mV, the output shows no clipping of the sync pulse. The level shift function is particularly useful when the output of the OPA360 is DC-coupled to the video load. However, it is also helpful when sag correction is employed. The offset helps to shift the video signal closer to the positive rail, so that with even a small 33µF coupling capacitor, the output is well outside the saturation limits of the OPA360. Figure 7 shows the output swing of the OPA360, operated on 3.0V supplies, with a 22µF sag correction capacitor and a 33µF output coupling capacitor. The test signal is a 50Hz signal constructed to generate a 1/2 black, 1/2 white screen. This video pattern is one of the most difficult patterns to display because it is the worst case signal regarding signal swing. A worst case signal such as this is highly unlikely in normal operation. Any other signal has a lower swing range. Note in Figure 7 that neither the white nor the black portion of the video signal is clipped. Figure 8. Input Sync Tip at −30mV (Output Shows No Sign of Clipping) 9 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 SAG CORRECTION Sag correction provides excellent video performance with two small output coupling capacitors. It eliminates the traditional, large 220µF output capacitor. The traditional 220µF circuit (Figure 9a) creates a single low frequency pole (−3dB frequency) at 5Hz. If this capacitor is made much smaller, excessive phase shift in the critical 50 to 100Hz range produces field tilt which can interfere with proper recovery of synchronization signals in the television receiver. The OPA360 sag correction circuit (Figure 9b, see also Figure 14) creates an amplitude response peak in the 20Hz region. This small amount of peaking (a few tenths of a dB) provides compensation of the phase response in the critical 50Hz to 100Hz range, greatly reducing field tilt. Note that two significantly smaller and lower cost capacitors are required. 220µF 75Ω Figure 10. Standard Video Circuit with 220mF Capacitor (top trace) vs OPA360 with 22mF and 47mF Capacitors 75Ω A field tilt equivalent to that achieved using the standard 220µF coupling capacitor can be achieved with a 22µF/67µF combination − see Figure 11. These capacitor values are optimized—sag correction capacitors larger than 22µF do not provide significant improvement. Smaller sag correction capacitors will lead to higher tilt. a) Traditional Video Circuit 47µF 22µF 75Ω 75Ω b) OPA360 with Sag Connection Figure 9. Traditional Video Circuit vs OPA360 with Sag Correction To achieve good performance, a 22µF sag correction and 47µF coupling capacitor can be used. Figure 10 and Figure 11 show comparisons for a standard video circuit with a 220µF coupling capacitor and the OPA360 with sag correction. Figure 10 shows that the 22µF/47µF combination leads to only a slightly greater tilt in the 50Hz, 1/2 black − 1/2 white video signal. No degradation in video quality is observed. 10 Figure 11. 220mF Standard Video Circuit (top trace) vs OPA360 with 22mF/67mF "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 SUPPLY VOLTAGE vs COUPLING CAPACITOR The output voltage swing is a function of the coupling capacitor value. The value of the sag correction capacitor has only a minor influence. The smaller the coupling capacitor, the greater the output swing. Therefore, to accommodate the large signal swing with very small coupling capacitors (22µF and 33µF), a higher supply voltage might be needed. As seen in Figure 7, the output swing with a 33µF coupling capacitor is already very close to the saturation limit on a 3V supply. Over time and temperature, a capacitor might change its value slightly, which in turn could force the output into saturation. Using the 50Hz, 1/2 blackĊ1/2 white screen test signal as a worst−case analysis, Figure 12 and Figure 13 demonstrate that a 3V supply could be used with a coupling capacitor as low as 47µF. Figure 12. Output Swing with 47mF on 3V Supply Figure 13. Output Swing with 67mF on 3V Supply V+ = 2.7V to 3.3V V+ OPA360 Video DAC (1) Level Shifter 2−Pole Filter Enable OUT COUT 47µF + ROUT 75Ω CSAG 22µF + 75Ω SAG AC Gain = 2 DC Gain = 2.8 Television or VCR GND NOTE: (1) Optional 200Ω for use with TI’s Digital Media Processors. Figure 14. DC-Coupled Input/AC-Coupled Output 11 "#$ www.ti.com SB0S294C − DECEMBER 2003 − REVISED JULY 2004 DC COUPLED OUTPUT The DC-coupled output configuration also shows the best video performance. As seen in Figure 16, there is no line or field tilt—allowing use of the lowest power supply. In this mode, the OPA360 will safely operate down to 2.5V with no clipping of the signal. The disadvantage with DC-coupled output is that it uses somewhat higher supply current. Due to the internal level shift, the OPA360 can also be DCcoupled to a video load. As shown in Figure 15, this eliminates the need for AC-coupling capacitors at the output. This is especially important in portable video applications where board space is restricted. V+ = 2.7V to 3.3V V+ OPA360 Video DAC (1) Level Shifter 2−Pole Filter Enable OUT ROUT 75Ω 75Ω 6dB SAG GND NOTE: (1) Optional 200Ω for use with TI’s Digital Media Processors. Figure 15. DC-Coupled Input/DC-Coupled Output Figure 16. DC-Coupled Output 12 Television or VCR PACKAGE OPTION ADDENDUM www.ti.com 20-Jul-2004 PACKAGING INFORMATION ORDERABLE DEVICE STATUS(1) PACKAGE TYPE PACKAGE DRAWING PINS PACKAGE QTY OPA360AIDCKR ACTIVE SOP DCK 6 3000 OPA360AIDCKT ACTIVE SOP DCK 6 250 (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. MECHANICAL DATA MPDS114 – FEBRUARY 2002 DCK (R-PDSO-G6) PLASTIC SMALL-OUTLINE PACKAGE 0,30 0,15 0,65 6 0,10 M 4 1,40 1,10 1 0,13 NOM 2,40 1,80 3 Gage Plane 2,15 1,85 0,15 0°–8° 0,46 0,26 Seating Plane 1,10 0,80 0,10 0,00 0,10 4093553-3/D 01/02 NOTES: A. B. C. D. All linear dimensions are in millimeters. This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusion. 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