TI TPA2001D2

TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
Modulation Scheme Optimized to Operate
PWP PACKAGE
(TOP VIEW)
Without a Filter
1 W Into 8-Ω Speakers (THD+N< 0.4%)
< 0.08% THD+N at 0.5 W, 1 kHz, Into 8-Ω
PGND
LOUTN
GAIN0
PVDD
LINN
AGND
COSC
RINN
PVDD
SHUTDOWN
ROUTN
PGND
Load
Extremely Efficient 3rd Generation 5-V
Class-D Technology:
– Low Supply Current (No Filter) . . . 8 mA
– Low Supply Current (Filter) . . . 15 mA
– Low Shutdown Current . . . 1 µA
– Low Noise Floor . . . 56 µVRMS
– Maximum Efficiency Into 8 Ω, 75 – 85%
– 4 Internal Gain Settings . . . 8 – 23.5 dB
– PSRR . . . –77 dB
Integrated Depop Circuitry
Short-Circuit Protection (Short to Battery,
Ground, and Load)
–40°C to 85°C Operating Temperature
Range
1
2
3
4
5
6
7
8
9
10
11
12
24
23
22
21
20
19
18
17
16
15
14
13
PGND
LOUTP
BYPASS
PVDD
LINP
VDD
ROSC
RINP
PVDD
GAIN1
ROUTP
PGND
description
The TPA2001D2 is the third generation 5-V class-D amplifier from Texas Instruments. Improvements to
previous generation devices include: lower supply current, lower noise floor, better efficiency, four different gain
settings, smaller packaging, and fewer external components. The most significant advancement with this device
is its modulation scheme that allows the amplifier to operate without the output filter. Eliminating the output filter
saves the user approximately 30% in system cost and 75% in PCB area.
The TPA2001D2 is a monolithic class-D power IC stereo audio amplifier, using the high switching speed of
power MOSFET transistors. These transistors reproduce the analog signal through high-frequency switching
of the output stage. The TPA2001D2 is configured as a bridge-tied load (BTL) amplifier capable of delivering
greater than 1 W of continuous average power into an 8-Ω load at less than 0.6% THD+N from a 5-V power
supply in the high fidelity range (20 Hz to 20 kHz). With 1 W being delivered to an 8-Ω load at 1 kHz, the typical
THD+N is less than 0.08%.
A BTL configuration eliminates the need for external coupling capacitors on the output. Low supply current of
8 mA makes the device ideal for battery-powered applications. Protection circuitry increases device reliability:
thermal, over-current, and under-voltage shutdown.
Efficient class-D modulation enables the TPA2001D2 to operate at full power into 8-Ω loads at an ambient
temperature of 85°C.
AVAILABLE OPTIONS
PACKAGED DEVICE
TA
TSSOP (PWP)
– 40°C to 85°C
TPA2001D2PWP
NOTE: The PWP package is available taped and reeled. To
order a taped and reeled part, add the suffix R to the
part number (e.g., TPA2001D2PWPR).
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PowerPAD is a trademark of Texas Instruments.
Copyright  2000, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
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1
TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
functional block diagram
VDD
AGND
PVDD
VDD
Gain
Adjust
RINN
+
_
Gate
Drive
ROUTN
_
+
PGND
+
_
PVDD
_
Gain
Adjust
RINP
Gate
Drive
+
ROUTP
PGND
SHUTDOWN
2
GAIN1
GAIN0
Gain
Biases
and
References
Start-up
Protection
Logic
Ramp
Generator
COSC
ROSC
BYPASS
Thermal
OC
Detect
OC
Detect
VDD ok
PVDD
LINP
Gain
Adjust
+
_
Gate
Drive
_
+
PGND
+
_
PVDD
_
LINN
LOUTP
Gain
Adjust
+
Gate
Drive
LOUTN
PGND
2
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
Terminal Function
TERMINAL
NAME
NO.
I/O
DESCRIPTION
AGND
6
–
Analog ground
BYPASS
22
I
Tap to voltage divider for internal midsupply bias generator used for analog reference.
COSC
7
I
A capacitor connected to this terminal sets the oscillation frequency in conjunction with ROSC. For proper
operation, connect a 220 pF capacitor from COSC to ground.
GAIN0
3
I
Bit 0 of gain control (TTL logic level)
GAIN1
15
I
Bit 1 of gain control (TTL logic level)
LINN
5
I
Left channel negative differential audio input
LINP
20
I
Left channel positive differential audio input
LOUTN
2
O
Left channel negative audio output
LOUTP
23
O
Left channel positive audio output
1, 24
–
Power ground for left channel H-bridge
12, 13
–
Power ground for right channel H-bridge
4, 21
–
Power supply for left channel H-bridge
9, 16
–
Power supply for right channel H-bridge
RINN
8
I
Right channel negative differential audio input
RINP
17
I
Right channel positive differential audio input
ROSC
18
I
A resistor connected to this terminal sets the oscillation frequency in conjunction with COSC. For proper
operation, connect a 120 kΩ resistor from ROSC to ground.
ROUTN
11
O
Right channel negative audio output
ROUTP
14
O
Right channel positive output
SHUTDOWN
10
I
Places the amplifier in shutdown mode if a TTL logic low is placed on this terminal; normal operation if a TTL
logic high is placed on this terminal.
VDD
19
–
Analog power supply
PGND
PVDD
absolute maximum ratings over operating free-air temperature (unless otherwise noted)†
Supply voltage, VDD, PVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 6 V
Input voltage, VI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to VDD+0.3 V
Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Rating Table
Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C
Operating junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 150°C
Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C
Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
† Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATING TABLE
PACKAGE
TA ≤ 25°C
POWER RATING
DERATING FACTOR
ABOVE TA = 25°C
TA = 70°C
POWER RATING
TA = 125°C
POWER RATING
PWP
2.7 W
21.8 mW/°C
1.7 W
1.4 W
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
recommended operating conditions
MIN
Supply voltage, VDD, PVDD
4.5
High-level input voltage, VIH
GAIN0, GAIN1, SHUTDOWN
Low-level input voltage, VIL
GAIN0, GAIN1, SHUTDOWN
MAX
5.5
2
UNIT
V
V
0.8
V
Operating free-air temperature, TA
–40
85
°C
PWM Frequency
200
300
kHz
TYP
MAX
UNIT
electrical characteristics, TA = 25°C, VDD = PVDD = 5 V (unless otherwise noted)
PARAMETER
TEST CONDITIONS
| VOO |
Output offset voltage (measured differentially)
PSRR
Power supply rejection ratio
IIH
IIL
High-level input current
IDD
IDD
Supply current
VDD=PVDD = 5.5 V, VI = VDD = PVDD
VDD=PVDD = 5.5 V, VI = 0 V
No filter (with or without speaker load)
Supply current
With filter, L = 22 µH,
IDD(SD)
Supply current, shutdown mode
Low-level input current
MIN
VI = 0 V
VDD=PVDD = 4.5 V to 5.5 V
10
mV
1
µA
10
mA
–77
dB
µA
–1
8
C = 1 µF
15
1
mA
10
µA
operating characteristics, TA = 25°C, VDD = PVDD = 5 V, RL = 8 Ω, Gain = 8 dB (unless otherwise noted)
PARAMETER
TEST CONDITIONS
f = 1 kHz,
RL = 8 Ω
f = 20 Hz to 20 kHz
PO
THD+N
Output power
THD = 0.4%,
Total harmonic distortion plus noise
BOM
kSVR
Maximum output power bandwidth
PO = 0.5 W,
THD = 5%
Supply ripple rejection ratio
f = 1 kHz,
SNR
Signal-to-noise ratio
20 Hz to 20 kHz
Integrated noise floor
20 Hz to 20 kHz, No input
ZI
MIN
C(BYPASS) = 0.4 µF
4
AMPLIFIER GAIN
(dB)
INPUT IMPEDANCE
(kΩ)
TYP
TYP
0
0
8
104
0
1
12
74
1
0
17.5
44
1
1
23.5
24
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87
Table 1. Gain Settings
GAIN1
1
• DALLAS, TEXAS 75265
MAX
UNIT
W
<0.2%
20
Input impedance
GAIN0
TYP
kHz
dB
dBV
56
µV
>20
kΩ
TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
eliminating the output filter with the TPA2001D2
This section will focus on why the user can eliminate the output filter with the TPA2001D2.
effect on audio
The class-D amplifier outputs a pulse-width modulated (PWM) square wave, which is the sum of the switching
waveform and the amplified input audio signal. The human ear acts as a band-pass filter such that only the
frequencies between approximately 20 Hz and 20 kHz are passed. The switching frequency components are
much greater than 20 kHz, so the only signal heard is the amplified input audio signal.
traditional class-D modulation scheme
The traditional class-D modulation scheme, which is used in the TPA005Dxx family, has a differential output
where each output is 180 degrees out of phase and changes from ground to the supply voltage, VDD. Therefore,
the differential pre-filtered output varies between positive and negative VDD, where filtered 50% duty cycle yields
0 volts across the load. The traditional class-D modulation scheme with voltage and current waveforms is shown
in Figure 1. Note that even at an average of 0 volts across the load (50% duty cycle), the current to the load is
high causing high loss thus causing a high supply current.
OUT+
OUT–
+5 V
Differential Voltage
Across Load
OV
–5 V
Current
Figure 1. Traditional Class-D Modulation Scheme’s Output Voltage and Current Waveforms Into an
Inductive Load With no Input
TPA2001D2 modulation scheme
The TPA2001D2 uses a modulation scheme that still has each output switching from 0 to the supply voltage.
However, OUT+ and OUT– are now in phase with each other with no input. The duty cycle of OUT+ is greater
than 50% and OUT– is less than 50% for positive voltages. The duty cycle of OUT+ is less than 50% and OUT–
is greater than 50% for negative voltages. The voltage across the load sits at 0 volts throughout most of the
switching period greatly reducing the switching current, which reduces any I2R losses in the load.
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
OUT+
OUT–
Differential
Voltage
Across
Load
Output = 0 V
+5 V
0V
–5 V
Current
OUT+
OUT–
Differential
Voltage
Output > 0 V
+5 V
0V
Across
Load
–5 V
Current
Figure 2. The TPA2001D2 Output Voltage and Current Waveforms Into an Inductive Load
efficiency: why you must use a filter with the traditional class-D modulation scheme
The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform
results in maximum current flow. This causes more loss in the load, which causes lower efficiency. The ripple
current is large for the traditional modulation scheme because the ripple current is proportional to voltage
multiplied by the time at that voltage. The differential voltage swing is 2 × VDD and the time at each voltage is
half the period for the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from
each half cycle for the next half cycle, while any resistance causes power dissipation. The speaker is both
resistive and reactive, whereas an LC filter is almost purely reactive.
The TPA2001D2 modulation scheme has very little loss in the load without a filter because the pulses are very
short and the change in voltage is VDD instead of 2 × VDD. As the output power increases, the pulses widen
making the ripple current larger. Ripple current could be filtered with an LC filter for increased efficiency, but for
most applications the filter is not needed.
An LC filter with a cut-off frequency less than the class-D switching frequency allows the switching current to
flow through the filter instead of the load. The filter has less resistance than the speaker that results in less power
dissipated, which increases efficiency.
6
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
effects of applying a square wave into a speaker
Audio specialists have said for years not to apply a square wave to speakers. If the amplitude of the waveform
is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave
could cause the voice coil to jump out of the air gap and/or scar the voice coil. A 250-kHz switching frequency,
however, is not significant because the speaker cone movement is proportional to 1/f2 for frequencies beyond
the audio band. Therefore, the amount of cone movement at the switching frequency is very small. However,
damage could occur to the speaker if the voice coil is not designed to handle the additional power. To size the
speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the
theoretical supplied power, PSUP THEORETICAL, from the actual supply power, PSUP, at maximum output power,
POUT. The switching power dissipated in the speaker is the inverse of the measured efficiency, ηMEASURED,
minus the theoretical efficiency, ηTHEORETICAL.
PSPKR = PSUP – PSUP THEORETICAL (at max output power)
(1)
PSPKR = PSUP / POUT – PSUP THEORETICAL / POUT (at max output power)
(2)
PSPKR = 1/ηMEASURED – 1/ηTHEORETICAL (at max output power)
(3)
The maximum efficiency of the TPA2001D2 with an 8-Ω load is 85%. Using equation 3 with the efficiency at
maximum power (78%) there is an additional 106 mW dissipated in the speaker. The added power dissipated
in the speaker is not an issue as long as it is taken into account when choosing the speaker.
when to use an output filter
Design the TPA2001D2 without the filter if the traces from amplifier to speaker are short. The TPA2001D2
passed FCC and CE radiated emissions with no shielding with speaker wires 8 inches long or less. Notebook
PCs and powered speakers where the speaker is in the same enclosure as the amplifier are good applications
for class-D without a filter.
A ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency
sensitive circuit is greater than 1 MHz. This is good for circuits that just have to pass FCC and CE because FCC
and CE only test radiated emissions greater than 30 MHz. If choosing a ferrite bead, choose one with high
impedance at high frequencies, but very low impedance at low frequencies.
Use an output filter if there are low frequency (< 1 MHz) EMI sensitive circuits and/or there are long leads from
amplifier to speaker.
gain setting via GAIN0 and GAIN1 inputs
The gain of the TPA2001D2 is set by two input terminals, GAIN0 and GAIN1.
The gains listed in Table 2 are realized by changing the taps on the input resistors inside the amplifier. This
causes the input impedance, ZI, to be dependent on the gain setting. The actual gain settings are controlled
by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input
impedance may shift by 30% due to shifts in the actual resistance of the input resistors.
For design purposes, the input network (discussed in the next section) should be designed assuming an input
impedance of 20 kΩ, which is the absolute minimum input impedance of the TPA2001D2. At the higher gain
settings, the input impedance could increase as high as 115 kΩ.
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
Table 2. Gain Settings
AMPLIFIER GAIN
(dB)
INPUT IMPEDANCE
(kΩ)
TYP
TYP
8
104
1
12
74
1
0
17.5
44
1
1
23.5
24
GAIN0
GAIN1
0
0
0
input resistance
Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest
value to over 6 times that value. As a result, if a single capacitor is used in the input high pass filter, the –3 dB
or cut-off frequency will also change by over 6 times. If an additional resistor is connected from the input pin
of the amplifier to ground, as shown in the figure below, the variation of the cut-off frequency will be much
reduced.
ZF
Ci
IN
Input
Signal
ZI
R
The –3 dB frequency can be calculated using equation 4:
f –3 dB 1
2 C iR Z I
(4)
If the filter must be more accurate, the value of the capacitor should be increased while value of the resistor to
ground should be decreased. In addition, the order of the filter could be increased.
input capacitor, Ci
In the typical application an input capacitor, Ci, is required to allow the amplifier to bias the input signal to the
proper dc level for optimum operation. In this case, Ci and the input impedance of the amplifier, ZI, form a
high-pass filter with the corner frequency determined in equation 5.
–3 dB
f c(highpass) (5)
1
2 ZI Ci
fc
8
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
The value of Ci is important as it directly affects the bass (low frequency) performance of the circuit. Consider
the example where ZI is 20 kΩ and the specification calls for a flat bass response down to 80 Hz. Equation 5
is reconfigured as equation 6.
Ci 1
2 Z I f c
(6)
In this example, Ci is 0.1 µF so one would likely choose a value in the range of 0.1 µF to 1 µF. If the gain is known
and will be constant, use ZI from Table 1 to calculate Ci. A further consideration for this capacitor is the leakage
path from the input source through the input network (Ci) and the feedback network to the load. This leakage
current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high
gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When
polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most
applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it
is important to confirm the capacitor polarity in the application.
Ci must be 10 times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off
and entering and leaving shutdown. After sizing Ci for a given cut-off frequency, size the bypass capacitor to
10 times that of the input capacitor.
Ci ≤ CBYP / 10
(7)
power supply decoupling, CS
The TPA2001D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling
to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also
prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is
achieved by using two capacitors of different types that target different types of noise on the power supply leads.
For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance
(ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device VDD lead works best. For
filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near
the audio power amplifier is recommended.
midrail bypass capacitor, CBYP
The midrail bypass capacitor, CBYP, is the most critical capacitor and serves several important functions. During
start-up or recovery from shutdown mode, CBYP determines the rate at which the amplifier starts up. The second
function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This
noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and
THD+N.
Bypass capacitor, CBYP, values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended
for the best THD and noise performance.
Increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving
shutdown. To have minimal pop, CBYP should be 10 times larger than Ci.
CBYP ≥ 10 × Ci
(8)
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
differential input
The differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. To
use the TPA2001D2 EVM with a differential source, connect the positive lead of the audio source to the RINP
(LINP) input and the negative lead from the audio source to the RINN (LINN) input. To use the TPA2001D2 with
a single-ended source, ac ground the RINN and LINN inputs through a capacitor and apply the audio single to
the RINP and LINP inputs. In a single-ended input application, the RINN and LINN inputs should be ac grounded
at the audio source instead of at the device inputs for best noise performance.
shutdown modes
The TPA2001D2 employs a shutdown mode of operation designed to reduce supply current, IDD, to the absolute
minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal
should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the
outputs to mute and the amplifier to enter a low-current state, IDD(SD) = 1 µA. SHUTDOWN should never be left
unconnected because amplifier operation would be unpredictable.
using low-ESR capacitors
Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal)
capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this
resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this
resistance the more the real capacitor behaves like an ideal capacitor.
evaluation circuit
LOUT–
GAIN0
GND
U1
TPA2001D2
C1
0.1 µF
PGND
GND
PGND
LOUTN
LOUTP
GAIN0
BYPASS
LPVDD
LPVDD
LIN+
C2
0.1 µF
C17
120 k
0.1 µF
R1
LIN–
C3
C7
0.1 µF
LINP
R3
120 k
C18
0.1 µF
RIN+
VDD
COSC
ROSC
RINN
RINP
RPVDD
ROUTN
GND
GAIN1
ROUTP
PGND
SHUTDOWN
VDD
0.1 µF
VDD
C20
0.1 µF
R2
120k
C8
RPVDD
SHUTDOWN
0.1 µF
10 µF
C19
R4
120 k
GAIN1
AGND
220 pF
RIN–
C6
LOUT+
1 µF
C21
LINN
C4
C5
10 uF
0.1 µF
PGND
ROUT+
GND
S1
GND
GND
ROUT–
NOTE: R1, R3, and R4 are used in the EVM but are not required for normal applications.
10
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
APPLICATION INFORMATION
Table 3. TPA2001D2 Evaluation Bill of Materials
SIZE
QUANTITY
C1–4,
C17–21
REFERENCE
Capacitor, ceramic chip, 0.1 µF, ±10%, X7R, 50 V
DESCRIPTION
0805
9
Kemet
MANUFACTURER
C0805C104K5RAC
PART NUMBER
C5
Capacitor, ceramic, 1.0 µF, +80%/–20%, Y5V, 16 V
0805
1
Murata
GRM40-Y5V105Z16
C6, C8
Capacitor, ceramic, 10 µF, +80%/–20%, Y5V, 16 V
1210
2
Murata
GRM235-Y5V106Z16
C7
Capacitor, ceramic, 220 pF, ±10%, XICON, 50 V
0805
2
Mouser
140–CC501B221K
R2, R1†,
R3†, R4†
Resistor, chip, 120 kΩ, 1/10 W, 5%, XICON
0805
2
Mouser
260–120K
U1
IC, TPA2001D2, audio power amplifier, 2-W,
2-channel, class-D
24 pin
TSSOP
1
TI
TPA2001D2PWP
† These components are used in the EVM, but they are not required for normal applications.
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TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS292A – MARCH 2000 – REVISED APRIL 2000
MECHANICAL DATA
PWP (R-PDSO-G**)
PowerPAD PLASTIC SMALL-OUTLINE
20 PINS SHOWN
0,30
0,19
0,65
20
0,10 M
11
Thermal Pad
(See Note D)
4,50
4,30
0,15 NOM
6,60
6,20
Gage Plane
1
10
0,25
A
0°–8°
0,75
0,50
Seating Plane
0,15
0,05
1,20 MAX
PINS **
0,10
14
16
20
24
28
A MAX
5,10
5,10
6,60
7,90
9,80
A MIN
4,90
4,90
6,40
7,70
9,60
DIM
4073225/F 10/98
NOTES: A.
B.
C.
D.
All linear dimensions are in millimeters.
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusions.
The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.
This pad is electrically and thermally connected to the backside of the die and possibly selected leads.
E. Falls within JEDEC MO-153
PowerPAD is a trademark of Texas Instruments Incorporated.
12
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