TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 1 TMC239/A – DATA SHEET High current microstep stepper motor driver with protection, diagnostics and SPI Interface ® TRINAMIC Motion Control GmbH & Co KG Sternstraße 67 D – 20357 Hamburg GERMANY www.trinamic.com Features The TMC239 / TMC239A (1) is a dual full bridge driver IC for bipolar stepper motor control applications. The TMC239 is realized in a HVCMOS technology and directly drives eight external LowRDS-ON high efficiency MOSFETs. It supports more than 6000mA coil current. The low power dissipation makes the TMC239 an optimum choice for drives, where a high reliability is desired. With additional drivers, motor current and voltage can be increased. The driver transistors can be chosen depending on output current or environment temperature. Internal DACs allow microstepping as well i as smart current control. The device can be controlled by a serial interface (SPI™ ) or by analog / digital input signals. Short circuit, temperature, undervoltage and overvoltage protection are integrated. More than 6000mA using 8 external MOS transistors (e.g. 4A RMS) Control via SPI with easy-to-use 12 bit protocol or external analog / digital signals Short circuit and over temperature protection integrated Overvoltage protection integrated (A-type) Status flags for overcurrent, open load, over temperature, temperature pre-warning, undervoltage Integrated 4 bit DACs allow up to 16 times microstepping via SPI, any resolution via analog control (for up to 64 microsteps via SPI see last manual page) Mixed decay feature for smooth motor operation Slope control user programmable to reduce electromagnetic emissions Chopper frequency programmable via a single capacitor or external clock Current control allows cool motor and driver operation 7V to 34V motor supply voltage (A-type) up to 58V motor supply voltage using a few additional low cost components External drivers can be added for higher motor voltages and higher currents (e.g. 50V, 5A) Only 4 external PMOS transistors required for unipolar operation 3.3V or 5V operation for digital part Low power dissipation via low RDS-ON power stage Standby and shutdown mode available Choice of SO28 or chip size MLF package (1) The term TMC239 in this datasheet always refers to the TMC239A and the TMC239. The major differences in the older TMC239 are explicitly marked with “non-A-type”. The TMC239A brings a number of enhancements and is fully backward compatible to the TMC239. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 2 FEATURES ............................................................................................................................................. 1 PINNING .................................................................................................................................................. 5 PACKAGE CODES ................................................................................................................................... 5 SO28 DIMENSIONS ................................................................................................................................ 6 QFN32 DIMENSIONS .............................................................................................................................. 6 APPLICATION CIRCUIT / BLOCK DIAGRAM ....................................................................................... 7 PIN FUNCTIONS ...................................................................................................................................... 7 SELECTING POWER TRANSISTORS ................................................................................................... 8 LIST OF RECOMMENDED TRANSISTORS .................................................................................................... 8 LAYOUT CONSIDERATIONS ................................................................................................................ 9 USING ADDITIONAL POWER DRIVERS ............................................................................................. 10 CONTROL VIA THE SPI INTERFACE ................................................................................................. 11 SERIAL DATA WORD TRANSMITTED TO TMC239..................................................................................... 11 SERIAL DATA WORD TRANSMITTED FROM TMC239 ................................................................................ 11 TYPICAL MOTOR COIL CURRENT VALUES ................................................................................................ 12 BASE CURRENT CONTROL VIA INA AND INB IN SPI MODE ....................................................................... 12 CONTROLLING THE POWER DOWN MODE VIA THE SPI INTERFACE ........................................................... 12 OPEN LOAD DETECTION ........................................................................................................................ 13 STANDBY AND SHUTDOWN MODE .......................................................................................................... 13 POWER SAVING .................................................................................................................................... 13 PROTECTION FUNCTIONS ................................................................................................................. 14 OVERCURRENT PROTECTION AND DIAGNOSIS ........................................................................................ 14 OVER TEMPERATURE PROTECTION AND DIAGNOSIS ................................................................................ 14 OVERVOLTAGE PROTECTION AND ENN PIN BEHAVIOR ............................................................................ 14 CHOPPER PRINCIPLE ......................................................................................................................... 15 CHOPPER CYCLE / USING THE MIXED DECAY FEATURE ........................................................................... 15 ADAPTING THE SINE WAVE FOR SMOOTH MOTOR OPERATION .................................................................. 16 BLANK TIME ......................................................................................................................................... 16 BLANK TIME SETTINGS .......................................................................................................................... 16 CLASSICAL NON-SPI CONTROL MODE (STAND ALONE MODE) .................................................. 17 PIN FUNCTIONS IN STAND ALONE MODE ................................................................................................. 17 INPUT SIGNALS FOR MICROSTEP CONTROL IN STAND ALONE MODE .......................................................... 17 UNIPOLAR OPERATION ...................................................................................................................... 18 DIFFERENCES OF SHORT CIRCUIT BEHAVIOR IN UNIPOLAR OPERATION MODE ........................................... 18 DIFFERENCES IN CHOPPER CYCLE IN UNIPOLAR OPERATION MODE .......................................................... 18 CALCULATION OF THE EXTERNAL COMPONENTS ....................................................................... 19 SENSE RESISTOR................................................................................................................................. 19 EXAMPLES FOR SENSE RESISTOR SETTINGS .......................................................................................... 19 HIGH SIDE OVERCURRENT DETECTION RESISTOR RSH ............................................................................ 19 MAKING THE CIRCUIT SHORT CIRCUIT PROOF ......................................................................................... 20 OSCILLATOR CAPACITOR ...................................................................................................................... 21 TABLE OF OSCILLATOR FREQUENCIES ................................................................................................... 21 PULL-UP RESISTORS ON UNUSED INPUTS ............................................................................................... 21 POWER SUPPLY SEQUENCING CONSIDERATIONS .................................................................................... 21 SLOPE CONTROL RESISTOR ................................................................................................................. 22 ABSOLUTE MAXIMUM RATINGS ....................................................................................................... 23 Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 3 ELECTRICAL CHARACTERISTICS ..................................................................................................... 23 OPERATIONAL RANGE .......................................................................................................................... 23 DC CHARACTERISTICS ......................................................................................................................... 24 AC CHARACTERISTICS ......................................................................................................................... 26 THERMAL PROTECTION (1) ................................................................................................................... 26 SPI INTERFACE TIMING ...................................................................................................................... 27 PROPAGATION TIMES ........................................................................................................................... 27 USING THE SPI INTERFACE ................................................................................................................... 27 SPI FILTER (ONLY A-TYPE) ................................................................................................................... 27 APPLICATION NOTE: EXTENDING THE MICROSTEP RESOLUTION ............................................. 28 DOCUMENTATION REVISION ............................................................................................................ 29 Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) Life support policy TRINAMIC Motion Control GmbH & Co KG does not authorize or warrant any of its products for use in life support systems, without the specific written consent of TRINAMIC Motion Control GmbH & Co KG. Life support systems are equipment intended to support or sustain life, and whose failure to perform, when properly used in accordance with instructions provided, can be reasonably expected to result in personal injury or death. © TRINAMIC Motion Control GmbH & Co KG 2005 Information given in this data sheet is believed to be accurate and reliable. However no responsibility is assumed for the consequences of its use nor for any infringement of patents or other rights of third parties, which may result from its use. Specifications subject to change without notice. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG 4 TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 5 Pinning 26 25 OSC 4 25 AGND SDO 5 24 SLP SDI 6 23 INA SCK 7 22 INB CSN 8 21 VCC ENN 9 20 GND SPE 10 19 VS BL1 11 18 VT SRB 12 17 BL2 LB2 13 16 HB1 LB1 14 15 HB2 BL2 HB1 HB2 LB1 LB2 SRB 2 HA1 3 HA2 4 12 13 14 15 16 SPE BL1 11 ENN 10 SCK 9 CSN 8 SRA SDI LA2 SDO LA1 5 - TMC 239-LA OSC ANN VT 1 AGND 24 27 23 28 22 29 21 VS 30 20 GND 31 19 GND 32 18 VCC ANN 17 HA1 26 TMC239 / 239A SO28 27 3 7 2 SRA 6 LA2 INB HA2 INA 28 - 1 SLP LA1 Top view Note: Cooling plane on -LA type should be connected to GND or left open. Package codes Type TMC239A TMC239 Package SO28 SO28 Temperature range automotive (1) automotive (1) TMC239A QFN32, 7*7mm automotive (1) Lead free Code/marking Yes TMC239A-SA From date code 05/05 TMC239-SA (wwyy) Yes TMC239A-LA / 239A-LA (1) ICs are not yet tested according to automotive standards, but are usable within the complete temperature range. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 6 SO28 Dimensions REF A B C D E F G H I K E F G C I D A K H MIN. 10 17.7 7.4 MAX. 10.65 18.1 7.6 1.4 2.65 0.25 0.1 0.3 0.36 0.49 0.4 1.1 1.27 All dimensions are in mm. B MIN NOM 0.80 0.90 1.00 A1 0.00 0.02 0.05 0.20 E 7.0 2 1 RADIUS D2 5.00 5.15 5.25 E2 5.00 5.15 5.25 L 0.45 0.55 0.65 b 0.25 0.30 0.35 aaa C 2x N N-1 TOP VIEW ccc C NX 0.08 C SEATING PLANE SIDE VIEW 0.65 -C- A3 7.0 E 0.15 BOTTOM VIEW WITH TYPE C ID aaa C 2x 0.03 D e -B- A L1 D/2 INDEX AREA (D/2 xE/2) E/2 A A3 D MAX A1 REF -A- QFN32 Dimensions D2 D2/2 All dimensions are in mm. Attention: Drawing not to scale. -B- INDEX AREA (D/2 xE/2) L1 2 1 N N-1 6 SEE DETAIL B Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG NXb -A- SEE DETAIL B E2 e E2/2 NXL Datum A or B ddd BTM VIEW 5 bbb e/2 C A B C e Terminal Tip DETAIL B TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 7 Application Circuit / Block Diagram +VM BL1 BL2 220nF VS TMC239A OSC OSC HA1 Current Controlled Gate Drivers PWM-CTRL +VCC Undervoltage 100nF Temperature HA2 P N SDI [PHB] SDO Parallel Control [ERR] CSN N LA1 RS 0 Control & Diagnosis [PHA] SPIInterface SCK P Coil A LA2 SRA [MDBN] RSH VT 1nF VCC 100µF DAC 4 1 INA REFSEL VREF DAC INB 4 1 0 SRB RS PWM-CTRL Current Controlled Gate Drivers LB1 ENN VCC/2 REFSEL SPE ANN AGND GND LB2 N N Coil B HB2 P P HB1 SLP [MDAN] stand alone mode RSLP [...]: function in stand alone mode Pin Functions Pin Function Pin Function VS Motor supply voltage VT Short to GND detection comparator – connect to VS if not used Digital / Power ground VCC 3.0-5.5V supply voltage for analog and logic circuits AGND Analog ground (Reference for SRA, SRB, OSC, SLP, INA, INB) INA Analog current control phase A SCK Clock input of serial interface SDI Data input of serial interface ENN Device enable (low active), and overvoltage shutdown input ANN Enable analog current control via INA and INB (low active) BL1, BL2 Digital blank time select HA1, HA2, Outputs for high side P-channel HB1, HB2 transistors GND OSC INB SDO CSN SPE SLP SRA, SRB LA1, LA2, LB1, LB2 Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG Oscillator capacitor or external clock input for chopper Analog current control input phase B Data output of serial interface (tri-state) Chip select input of serial interface Enable SPI mode (high active). Tie to GND for non-SPI applications Slope control resistor. Tie to GND for fastest slope Bridge A/B current sense resistor input Outputs for low side N-channel transistors TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 8 Selecting Power Transistors Selection of power transistors for the TMC239 depends on required current, voltage and thermal conditions. Driving large transistors directly with the TMC239 is limited by the gate capacity of these transistors. If the total gate charge is too high, slope time increases and leads to a higher switching power dissipation. A total gate charge of maximum 25nC per transistor pair (N gate charge + P gate charge) is recommended (at 25nC, tie pin SLP to GND to get an acceptable slope). The table below shows a choice of transistors which can be driven directly by the TMC239. The maximum application current mainly is a function of cooling and environment temperature. RDSon and gate charge are read at the nominal drive voltage of 6V and 25°C. All of these transistor types are mainly cooled via their drain connections. In order to provide sufficient cooling, the transistors should be directly connected to massive traces on the PCB which are widened near the transistor package, providing a copper area of some square cm. The heat then is dissipated vertically through the PCB to a massive power or ground plane, which shall cover most of the PCB area in order to use the whole PCB for cooling. As an example, the minimum PCB size required to reach the given current for the SI7501, is about 42mm * 42mm, yielding in a heat up of the transistor packages of about 85°C above ambient temperature. With a 100mm * 100mm PCB, this reduced to 70°C above ambient temperature, so that safe operation is possible up to 60°C ambient temperature at maximum current (transistor package at 130°C). List of recommended transistors Manufacturer and type Fairchild Semi FDD 8424 H Siliconix SI 7501 DN TRINAMIC TMC34NP Fairchild Semi FDS 8960 Fairchild Semi FDS 8958 A Siliconix SI 4539 ADY Siliconix SI 4532 ADY Fairchild Semi FDS 8333C IRF 9952 (/ IRF 7509) TRINAMIC TMC32NP-MLP Siliconix SI 5504 TRINAMIC TMC32NP2-SM8 Siliconix SI 4559 EY Package (#Trans) TO252-4 (1N,1P) PPack (1N,1P) PPack (1N,1P) SO8 (1N,1P) SO8 (1N,1P) SO8 (1N,1P) SO8 (1N,1P) SO8 (1N,1P) SO8 (1N,1P) MLP (1N,1P) 1206-8 (1N,1P) SM8 (2N,2P) SO8 (1N,1P) max. application voltage 34V 28.5V 28.5V 34V 28.5V 28.5V 28.5V 28.5V 28.5V 28.5V 28.5V 28.5V 34V or 58V (see A/N) RDSON [Ohm] 0.023 0.045 0.035 0.055 0.035 0.055 0.023 0.050 0.023 0.050 0.040 0.060 0.055 0.080 0.075 0.130 0.075 0.280 0.120 0.250 0.090 0.170 0.120 0.250 0.045 0.120 Total gate charge [nC] 10 10 5.5 8.0 5.5 8.0 7.0 7.0 7.0 7.0 7.5 9.0 4.5 6.5 2.9 3.0 4.5 4.0 2.8 2.5 3.0 3.2 2.8 2.5 11 10 Typical maximum application current 6000mA Remark (1) (2) 4200mA (1) 4200mA 4000mA 4000mA (1) (1) (2) (2) 3500mA 3000mA 5000mA (2 parallel) 2800mA 5000mA (2 parallel) 2500mA (3) (3) 2300mA 4400mA (2 parallel) 2000mA very small! (3) very small! 2000mA only 2 packages! 3000mA 2500mA (at 48V) (4) (1) These P-channel transistors have a very high drain to gate capacity, which may introduce destructive current impulses into the HA/HB outputs by forcing them above the power supply level, depending on the low-side slope. To ensure reliability, connect one MSS1P3 or ZHCS1000 or an SS14 1A schottky diode or similar to both HA and HB outputs against VS to protect them. (2) Compare (1), but for N-channel transistor. Protect LA/LB outputs with one schottky diode to GND. (3) Higher current with two devices in parallel, i.e. using 8 double transistors instead of four. (4) See application note document for simple extension to operate at up to 58V. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 9 Layout Considerations For optimal operation of the circuit a careful board layout is important, because of the combination of high current chopper operation coupled with high accuracy threshold comparators. Please pay special attention to massive grounding. Depending on the required motor current, either a single massive ground plane or a ground plane plus star connection of the power traces may be used. The schematic shows how the high current paths can be routed separately, so that the chopper current does not flow through the system’s GND-plane. Tie the TMC239’s AGND and GND to the GND plane. Additionally, use enough filtering capacitors located near to the board’s power supply input and small ceramic capacitors near to the power supply connections of the TMC239. Use low inductance sense resistors, or add a ceramic capacitor in parallel to each resistor to avoid high voltage spikes. In some applications it may become necessary to introduce additional RC-filtering into the SRA / SRB line, as optional voltage shown in the schematic, to prevent spikes from divider VS triggering the short circuit protection or the chopper comparator. Alternatively, a 470nF 100nF R VT ceramic capacitor can be placed across the +VM 100R sense resistors. If you want to take advantage GND of the thermal protection and diagnosis, ensure, TMC249/ Bridge A Bridge B that the power transistors are very close to the optional filter TMC239A SRA C package, and that there is a good thermal 100R contact between the TMC239 and the external SRB R R 100R transistors. Please be aware, that long or thin 3.3 GND 10nF traces to the sense resistors may add AGND GNDsubstantial resistance and thus reduce output Plane current. The same is valid for the high side shunt resistor. Place the optional shunt resistor voltage divider near the TMC239, in order to avoid voltage drop in the VCC plane to add up to the measured voltage. RSH DIV VM SA Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG SB TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 10 Using additional Power Drivers For higher voltage and higher output current it is possible to add external MOSFET gate drivers. Both, dedicated transistor drivers are suitable, as well as a circuit based on standard HCMOS drivers. It is important to understand the function of dedicated gate drivers for N-channel transistors: Since the chopping also can be stopped in open load conditions, the gate drive circuit for the upper transistors should allow for continuous ON conditions. In the schematic below this is satisfied by attaching a weak additional charge pump oscillator and pumping the VS up to the high voltage supply. Do not enable the TMC239, before the gate driver capacitors are charged to an appropriate voltage. A current sensing comparator in the VM line pulling down the VT pin by some 100mV on overcurrent can be added, if required. Since the TMC239 in this application can not sense switch-off of the transistor gates to ensure break-before-make operation, the break before-make-delays have to be set by capacitive loading of its transistor drive outputs. The capacitors CdHS and CdLS are charged / discharged with the nominal gate current. The opposite output is not enabled, before the switching-off output has been discharged to 0.5V. To calculate the timing, refer to the required logic levels of the attached power driver, resp. the attached PMOS. For CdHS and CdLS 470pF give about 100ns. Both circuits do not show decoupling capacitors and further details. +12V 1K VS VT +VM e.g. 50V C-Pump 20kHz ICM7555 CDHS 470p HA1 22K small signal PMOS, e.g. BSS84 High current, high voltage MOS, e.g. SI4450 1µF 2n2 12V N HS-Driver N 390R 1K TMC249/ TMC239 to other bridges Coil LA1 LSDriver N 390R N CDLS 470p IR2101 SRA RS 100R 4.7nF opt. SLP Set HS and LS current to 10mA 10K +VS 7..15V +VM 20..60V VS 1K VCC 120R High voltage logic level MOS bridge 1/2 74HC244 on high side VT P 1K CDHS ADJ HA1 LM337 HV 55V low current N-MOS 390R OUT /OE GND VM-5.2V IN TMC249/ TMC239 P 100R +5V Coil VCC 1/2 74HC244 on low side LA1 N 1K CDLS N 100R /OE GND SRA RS SLP 15K set to 7 mA highside drive current Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 11 Control via the SPI Interface The SPI data word sets the current and polarity for both coils. By applying consecutive values, describing a sine and a cosine wave, the motor can be driven in microsteps. Every microstep is initiated by its own telegram. Please refer to the description of the analog mode for details on the waveforms required. The SPI interface timing is described in the timing section. Serial data word transmitted to TMC239 (MSB transmitted first) Bit Name Function Remark 11 MDA mixed decay enable phase A “1” = mixed decay 10 CA3 current bridge A.3 MSB 9 CA2 current bridge A.2 8 CA1 current bridge A.1 7 CA0 current bridge A.0 LSB 6 PHA polarity bridge A “0” = current flow from OA1 to OA2 5 MDB mixed decay enable phase B “1” = mixed decay 4 CB3 current bridge B.3 MSB 3 CB2 current bridge B.2 2 CB1 current bridge B.1 1 CB0 current bridge B.0 LSB 0 PHB polarity bridge B “0” = current flow from OB1 to OB2 Serial data word transmitted from TMC239 (MSB transmitted first) Bit Name Function Remark 11 0 always “0” 10 0 always “0” 9 0 always “0” 8 1 always “1” 7 OT overtemperature 6 OTPW temperature prewarning “1” = prewarning temperature exceeded 5 UV driver undervoltage “1” = undervoltage on VS 4 OCHS overcurrent high side 3 PWM cycles with overcurrent within 63 PWM cycles 3 OLB open load bridge B no PWM switch off for 14 oscillator cycles 2 OLA open load bridge A no PWM switch off for 14 oscillator cycles 1 OCB overcurrent bridge B low side 3 PWM cycles with overcurrent within 63 PWM cycles 0 OCA overcurrent bridge A low side 3 PWM cycles with overcurrent within 63 PWM cycles “1” = chip off due to overtemperature Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 12 Typical motor coil current values Current setting Percentage of current Typical trip voltage of the current sense comparator (internal reference or analog input voltage of 2V is used) 0000 0% 0V 0001 6.7% 23 mV 0010 13.3% 45 mV CA3..0 / CB3..0 ... (bridge continuously in slow decay condition) ... 1110 93.3% 317 mV 1111 100% 340 mV The current values correspond to a standard 4 Bit DAC, where 100%=15/16. The contents of all registers is cleared to “0” on power-on reset or disable via the ENN pin, bringing the IC to a low power standby mode. All SPI inputs have Schmitt-Trigger function. Base current control via INA and INB in SPI mode In SPI mode, the IC can use an external reference voltage for each DAC. This allows the adaptation to different motors. This mode is enabled by tying pin ANN to GND. A 2.0V input voltage gives full scale current of 100%. In this case, the typical trip voltage of the current sense comparator is determined by the input voltage and the DAC current setting (see table above) as follows: “percentage SPI current setting A” “percentage SPI current setting B” VTRIP,A = 0.17 VINA VTRIP,B = 0.17 VINB A maximum of 3.0V VIN is possible. Multiply the percentage of base current setting and the DAC table to get the overall coil current. It is advised to operate at a high base current setting, to reduce the effects of noise voltages. This feature allows a high resolution setting of the required motor current using an external DAC or PWM-DAC (see schematic for examples). using PWM signal 8 level via R2R-DAC 2 level control INA µCPort .2 R1 R2 100K 51K 47K 100nF µCPort .1 10nF 100K 51K AGND +VCC µCPWM INB µCPort .0 100K µCPort 51K ANN Controlling the power down mode via the SPI interface Bit Standard function Control word function 11 10 9 8 7 6 5 4 3 2 1 0 MxA CA3 CA2 CA1 CA0 PhA MxB CB3 CB2 CB1 CB0 PhB - 0 0 0 0 - - 0 0 0 0 - Enable standby mode and clear error flags Programming current value “0000” for both coils at a time clears the overcurrent flags and switches the TMC239 into a low current standby mode with coils switched off. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 13 Open load detection Open load is signaled, whenever there are more than 14 oscillator cycles without PWM switch off. Note that open load detection is not possible while coil current is set to “0000”, because the chopper is off in this condition. The open load flag will then always be read as inactive (“0”). During overcurrent and undervoltage or overtemperature conditions, the open load flags also become active! Due to their principle, the open load flags not only signal an open load condition, but also a torque loss of the motor, especially at high motor velocities. To detect only an interruption of the connection to the motor, it is advised to evaluate the flags during stand still or during low velocities only (e.g. for the first or last steps of a movement). Standby and shutdown mode The circuit can be put into a low power standby mode by the user, or, automatically goes to standby on Vcc undervoltage conditions. Before entering standby mode, the TMC239 switches off all power transistors, and holds their gates in a disable condition using high ohmic resistors. In standby mode the oscillator becomes disabled and the oscillator pin is held at a low state. The standby mode is available via the interface in SPI-mode and via the ENN pin in non-SPI mode. The shutdown mode even reduces supply current further. It can only be entered in SPI-mode by pulling the ENN pin high. In shutdown additionally all internal reference voltages become switched off and the SPI circuit is held in reset. Power saving The possibility to control the output current can dramatically save energy, reduce heat generation and increase precision by reducing thermal stress on the motor and attached mechanical components. Just reduce motor current during stand still: Even a slight reduction of the coil currents to 70% of the current of the last step of the movement, halves power consumption! In typical applications a 50% current reduction or even less during stand still is reasonable, bringing power consumption down to one quarter or even less. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 14 Protection Functions Overcurrent protection and diagnosis The TMC239 uses the current sense resistors on the low side to detect an overcurrent: Whenever a voltage above 0.61V is detected, the PWM cycle is terminated at once and all transistors of the bridge are switched off for the rest of the PWM cycle. The error counter is increased by one. If the error counter reaches 3, the bridge remains switched off for 63 PWM cycles and the error flag is read as “active”. The user can clear the error condition in advance by clearing the error flag. The error counter is cleared, whenever there are more than 63 PWM cycles without overcurrent. There is one error counter for each of the low side bridges, and one for the high side. The overcurrent detection is inactive during the blank pulse time for each bridge (resp. the corresponding bridge in non-A-type), to suppress spikes which can occur during switching. The high side comparator detects a short to GND or an overcurrent, whenever the voltage between VS and VT becomes higher than 0.15 V at any time, except for the blank time period which is logically ORed for both bridges. Here all transistors become switched off for the rest of the PWM cycle, because the bridge with the failure is unknown. The overcurrent flags can be cleared by disabling and re-enabling the chip either via the ENN pin or by sending a telegram with both current control words set to “0000”. In high side overcurrent conditions the user can determine which bridge sees the overcurrent, by selectively switching on only one of the bridges with each polarity (therefore the other bridge should remain programmed to “0000”). Over temperature protection and diagnosis The circuit switches off all output power transistors during an over temperature condition. The over temperature flag should be monitored to detect this condition. The circuit resumes operation after cool down below the temperature threshold. However, operation near the over temperature threshold should be avoided, if a high lifetime is desired. Overvoltage protection and ENN pin behavior During disable conditions the circuit switches off all output power transistors and goes into a low current shutdown mode. All register contents is cleared to “0”, and all status flags are cleared. The circuit in this condition can also stand a higher voltage, because the voltage then is not limited by the maximum power MOSFET voltage. The enable pin ENN provides a fixed threshold of ½ VCC (TTL level in non-A-type) to allow a simple overvoltage protection up to 40V using an external voltage divider (see schematic for A-type). +VM R1 for switch off at 26 - 29V: at VCC=5V: R1=100K; R2=10K at VCC=3.3V: R1=160K; R2=10K ENN R2 µC-Port (opt.) low=Enable, high=Disable Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 15 Chopper Principle Chopper cycle / Using the mixed decay feature RSENSE SWO SWC SWO RSENSE On phase: Current flows in target direction I SWC SWO SWC I SWO SWO SWC I SWO SWC The TMC239 uses a quiet fixed frequency chopper. Both coils are chopped with a phase shift of 180 degrees. The mixed decay option is realized as a self stabilizing system (pat. fi.), by shortening the fast decay phase, if the ON phase becomes longer. It is advised to enable the mixed decay for each phase during the second half of each microstepping half-wave, when the current is meant to decrease. This leads to less motor resonance, especially at medium velocities. With low velocities or during standstill mixed decay should be switched off. In applications requiring high resolution, or using low inductivity motors, the mixed decay mode can also be enabled continuously, to reduce the minimum motor current which can be achieved. When mixed decay mode is continuously on or when using high inductivity motors at low supply voltage, it is advised to raise the chopper frequency to minimum 36kHz, because the half chopper frequency could become audible under these conditions. RSENSE Fast decay phase: Current flows back into power supply Slow decay phase: Current re-circulation target current phase A actual current phase A on slow decay on fast decay slow decay oscillator clock resp. external clock mixed decay disabled mixed decay enabled When polarity is changed on one bridge, the PWM cycle on that bridge becomes restarted at once. Fast decay switches off both upper transistors, while enabling the lower transistor opposite to the selected polarity. Slow decay always enables both lower side transistors. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 16 Adapting the sine wave for smooth motor operation After reaching the target current in each chopper cycle, both, the slow decay and the fast decay cycle reduce the current by some amount. Especially the fast decay cycle has a larger impact. Thus, the medium coil current always is a bit lower than the target current. This leads to a flat line in the current shape flowing through the motor. It can be corrected, by applying an offset to the sine shape. In mixed decay operation via SPI, an offset of 1 does the job for most motors. Target current I Target current I Coil current Coil current t Coil current does not have optimum shape t Target current corrected for optimum shape of coil current Blank Time The TMC239 uses a digital blanking pulse for the current chopper comparators. This prevents current spikes, which can occur during switching action due to capacitive loading, from terminating the chopper cycle. The lowest possible blanking time gives the best results for microstepping: A long blank time leads to a long minimum turn-on time, thus giving an increased lower limit for the current. Please remark, that the blank time should cover both, switch-off time of the lower side transistors and turn-on time of the upper side transistors plus some time for the current to settle. Thus the complete switching duration should never exceed 1.5µs. With slow external power stages it will become necessary to add additional RC-filtering for the sense resistor inputs. The TMC239 allows adapting the blank time to the load conditions and to the selected slope in four steps (the effective resulting blank times are about 200ns shorter in the non-A-type): Blank time settings BL2 BL1 Typical blank time GND GND 0.6 µs GND VCC 0.9 µs VCC GND 1.2 µs VCC VCC 1.5 µs Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 17 Classical non-SPI control mode (stand alone mode) The driver can be controlled by analog current control signals and digital phase signals. To enable this mode, tie pin SPE to GND. In this mode, the SPI interface is disabled and the SPI input pins have alternate functions. The internal DACs are forced to “1111”. Pin functions in stand alone mode Pin Stand alone mode name Function in stand alone mode SPE (GND) Tie to GND to enable stand alone mode ANN MDAN Enable mixed decay for bridge A (low = enable) SCK MDBN Enable mixed decay for bridge B (low = enable) SDI PHA Polarity bridge A (low = current flow from output OA1 to OA2) CSN PHB Polarity bridge B (low = current flow from output OB1 to OB2) SDO ERR Error output (high = overcurrent on any bridge, or over temperature). In this mode, the pin is never tri-stated. ENN ENN Standby mode (high active), high causes a low power mode of the device. Setting this pin high also resets all error conditions. INA, INB INA, INB Current control for bridge A, resp. bridge B. Refer to AGND. The sense resistor trip voltage is 0.34V when the input voltage is 2.0V. Maximum input voltage is 3.0V. Input signals for microstep control in stand alone mode Attention: When transferring these waves to SPI operation, please remark, that the mixed decay bits are inverted when compared to stand alone mode. INA INB 90° 180° 270° 360° PHA (SDI) PHB (CSN) MDAN (ANN) MDBN (SCK) Use dotted line to improve performance at medium velocities Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 18 Unipolar Operation The TMC239 can also be used in a unipolar motor application with microstepping. In this configuration, only the four upper power transistors are required. Differences of short circuit behavior in unipolar operation mode Since there is no possibility to disable a short to VS condition, the circuit is not completely short circuit proof. In a low cost application a motor short would be covered, just using the bottom sense resistors (see schematic). Differences in chopper cycle in unipolar operation mode In unipolar mode, one of the upper side transistors is chopped, depending on the phase polarity. Slow decay mode always means, that both transistors are disabled. There is no difference between slow and fast decay mode, and the mixed decay control bits are “don’t care”. The transistors have to stand an off voltage, which is slightly higher than the double of the supply voltage. Voltage decay in the coil can be adapted to the application by adding additional diodes and a zener diode to feed back coil current in flyback conditions to the supply. +VM HA1 HA2 TMC249/ TMC239 P P One coil of the motor LA2 LA1 SRA RS Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 19 Calculation of the external components Sense Resistor Choose an appropriate sense resistor (RS) to set the desired motor current. The maximum motor current is reached, when the coil current setting is programmed to “1111”. This results in a current sense trip voltage of 0.34V when the internal reference or a reference voltage of 2V is used. When operating your motor in fullstep mode, the maximum motor current is as specified by the manufacturer. When operating in sinestep mode, multiply this value by 1.41 for the maximum current (Imax). RS = VTRIP / Imax In a typical application: RS = 0.34V / Imax RS: VTRIP: Imax: Current sense resistor of bridge A, B Programmed trip voltage of the current sense comparators Desired maximum coil current Examples for sense resistor settings RS 0.47 0.33 0.22 0.15 0.10 Imax 723mA 1030mA 1545mA 2267mA 3400mA High side overcurrent detection resistor RSH The TMC239 detects an overcurrent to ground, when the voltage between VS and VT exceeds 150mV. The high side overcurrent detection resistor should be chosen in a way that 100mV voltage drop are not exceeded between VS and VT, when both coils draw the maximum current. In a sinestep application, this is when sine and cosine wave have their highest sum, i.e. at 45 degrees, corresponding to 1.41 times the maximum current setting for one coil. In a fullstep application this is the double coil current. In a microstep application: RSH = 0.1V / (1.41 Imax) In a fullstep application: RSH = 0.1V / (2 RSH: Imax: Imax) High side overcurrent detection resistor Maximum coil current However, if the user desires to use higher resistance values, a voltage divider in the range of 10 to 100 can be used for VT. This might also be desired to limit the peak short to GND current, as described in the following chapter. Attention: A careful PCB layout is required for the sense resistor traces and for the RSH traces. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 20 Making the circuit short circuit proof In practical applications, a short circuit does not describe a static condition, but can be of very different nature. It typically involves inductive, resistive and capacitive components. Worst events are unclamped switching events, because huge voltages can build up in inductive components and result in a high energy spark going into the driver, which can destroy the power transistors. The same is true when disconnecting a motor during operation: Never disconnect the motor during operation! There is no absolute protection against random short circuit conditions, but pre-cautions can be taken to improve robustness of the circuit: In a short condition, the current can become very high before it is interrupted by the short detection, due to the blanking during switching and internal delays. The high-side transistors allow a high current flowing for the selected blank time. The lower the external inductivity, the faster the current climbs. If inductive components are involved in the short, the same current will shoot through the low-side resistor and cause a high negative voltage spike at the sense resistor. Both, the high current and the voltage spikes are a danger for the driver. Thus there are a three things to be done, if short circuits are expected: 1. Protect SRA/SRB inputs using a series resistance 2. Increase RSH to limit maximum transistor current: Use same value as for sense resistors 3. Use as short as possible blank time The second measure effectively limits short circuit current, because the upper driver transistor with its fixed ON gate voltage of 6V forms a constant current source together with its internal resistance and RSH. A positive side effect is, that only one type of low ohmic resistor is required. The drawback is, that power dissipation increases. A high side short detection resistor of 0.33 Ohms limits maximum high side transistor current to typically 4A. The schematic shows the modifications to be done. However, the effectiveness of these measures should be tested in the given application. VS RDIV RSH 100nF VT +VM 100R GND RSH=RSA=RSB RDIV values for Microstep: Fullstep: internal reference 27R 18R INA/INB up to3V 18R 12R CVM SRA 100R SRB 100R RSA RSB GND Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 21 Oscillator Capacitor The PWM oscillator frequency can be set by an external capacitor. The internal oscillator uses a 28k resistor to charge / discharge the external capacitor to a trip voltage of 2/3 Vcc respectively 1/3 Vcc. It can be overdriven using an external CMOS level square wave signal. Do not set the frequency higher than 100kHz and do not leave the OSC terminal open! The two bridges are chopped with a phase shift of 180 degrees at the positive and at the negative edge of the clock signal. 1 fOSC 40 s COSC [nF] fOSC: COSC: PWM oscillator frequency Oscillator capacitor in nF Table of oscillator frequencies fOSC typ. 16.7kHz 20.8kHz 25.0kHz 30.5kHz 36.8kHz 44.6kHz COSC 1.5nF 1.2nF 1.0nF 820pF 680pF 560pF Please remark that an unnecessary high frequency leads to high switching losses in the power transistors and in the motor. For most applications a chopper frequency slightly above audible range is sufficient. When audible noise occurs in an application, especially with mixed decay continuously enabled, the chopper frequency should be two times the audible range. Pull-up resistors on unused inputs The digital inputs all have integrated pull-up resistors, except for the ENN input, which is in fact an analog input. Thus, there are no external pull-up resistors required for unused digital inputs which are meant to be positive. Power supply sequencing considerations Upon power up, the driver initializes and switches off the bridge power transistors. However, in order for the internal startup logic to work properly, the Vcc supply voltage has to be at least 1.0V, respectively, the Vs supply voltage has to be at least 5.0V. When Vs goes up with Vcc at 0V, a medium current temporary cross conduction of the power stage can result at supply voltages between 2.4V and 4.8V. In this voltage range, the upper transistors conduct, while the gates of the lower transistors are floating. While this typically does no harm to the driver, it may hinder the power supply from coming up properly, depending on the power supply start up behavior. There are two possibilities to prevent this from occurring: Add resistors from the LA and LB outputs to GND in the range of 1M keeping the low side Nchannel MOSFETs gates at GND. Alternatively, either use a dual voltage power supply, or use a local regulator, generating the 5V or 3.3V Vcc voltage. Please pay attention to the local regulator start up voltage: Some newer switching regulators do not start, before the input voltage has reached 5V. Therefore it is recommended to use a standard linear regulator like 7805 or LM317 series or a low drop regulator or a switching regulator like the LM2595, starting at relatively low input voltages. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 22 Slope Control Resistor The output-voltage slope of the full bridge is controlled by a constant current gate charge / discharge of the MOSFETs. The charge / discharge current for the MOSFETs can be controlled by an external resistor: A reference current is generated by internally pulling the SLP-Pin to 1.25V via an integrated 4.7K resistor. This current is used to generate the current for switching ON and OFF the power transistors. (In non-A-type the low side slopes are fixed to typ. +/-15mA corresponding to a 5K to 10K slope control resistor!) The gate-driver output current can be set in range of 2mA to 25mA by an external resistor: 123 IOUT [mA] RSLP [k ] RSLP: IOUT: Slope control resistor Controlled output current of the low-side MOSFET driver 4.7 The SLP-pin can directly be connected to AGND for the fastest output-voltage slope (respectively maximum output current). Please remark, that there is a trade off between reduced electromagnetic emissions (slow slope) and high efficiency because of low dynamic losses (fast slope). Typical slope times range between 100ns and 500ns. Slope times below 100ns are not recommended, because they superimpose additional stress on the power transistors while bringing only very slight improvement in power dissipation. For applications where electromagnetic emission is very critical, it might be necessary to add additional LC (or capacitor only) filtering on the motor connections. For these applications emission is lower, if only slow decay operation is used. 25 IHDON 20 15 -IHDOFF / +/-ILD 10 5 0 0 2 5 10 RSLP [KOhm] Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG 20 50 100 TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 23 Absolute Maximum Ratings The maximum ratings may not be exceeded under any circumstances. Symbol Parameter Min Max Unit -0.5 36 V 40 V 6.0 V VS Supply voltage VSM Supply and bridge voltage max. 20000s VCC Logic supply voltage IOP Gate driver peak current (1) 50 mA IOC Gate driver continuous current 5 mA VI Logic input voltage -0.3 VCC+0.3V V VIA Analog input voltage -0.3 VCC+0.3V V IIO Maximum current to / from digital pins +/-10 mA VS-1V VS+0.3V V -0.5 and analog inputs VVT Short-to-ground detector input voltage TJ Junction temperature -40 150 (1) °C TSTG Storage temperature -55 150 °C (1) Internally limited Electrical Characteristics Operational Range Symbol Parameter Min Max Unit TAI Ambient temperature industrial (1) -25 125 °C TAA Ambient temperature automotive -40 125 °C TJ Junction temperature -40 140 °C VS Bridge supply voltage (A-type) 7 34 V VS Bridge supply voltage (non-A-type) 7 30 V VCC Logic supply voltage 3.0 5.5 V fCLK Chopper clock frequency 100 kHz RSLP Slope control resistor 470 K 0 (1) The circuit can be operated up to 140°C, but output power derates. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 24 DC Characteristics DC characteristics contain the spread of values guaranteed within the specified supply voltage and temperature range unless otherwise specified. Typical characteristics represent the average value of all parts. Logic supply voltage: VCC = 3.0 V ... 5.5 V, Junction temperature: TJ = -40°C … 140°C, Bridge supply voltage : VS = 7 V…34 V (unless otherwise specified) Symbol Min Typ Max Unit VLD < 4V 10 15 25 mA ILDOFF5 Gate drive current VLD > 3V low side switch OFF (non-A-type) VCC = 5V -15 -25 -35 mA ILDOFF3 Gate drive current VLD > 3V low side switch OFF (non-A-type) VCC = 3.3V -10 -15 -20 mA 15 25 40 mA -15 -25 -40 mA -15 -25 -40 mA 15 30 40 mA 70 100 130 % -5.1 -6.0 -8.0 V 5.1 6.0 8.0 V 0 -0.5 V 0 0.5 V 16 20 V ILDON Parameter Conditions Gate drive current low side switch ON (non-A-type) Gate drive current low side switch ON (A-type) VS > 8V, RSLP= 0K Gate drive current low side switch OFF (A-type) VS > 8V, RSLP= 0K Gate drive current high side switch ON VS > 8V, RSLP= 0K Gate drive current high side switch OFF VS > 8V, RSLP= 0K ISET Deviation of Current Setting with Respect to Characterization Curve Deviation from standard value, 10k <RSLP<75k VGH1 Gate drive voltage high side ON ILDON ILDOFF IHDON IHDOFF VLD < 4V VLD > 4V VS - VHD < 4V VS - VHD > 4V VS > 8V relative to VS VGL1 Gate drive voltage low side ON VS > 8V VGH0 Gate drive voltage high side OFF relative to VS VGL0 Gate drive voltage low side OFF VGCL Gate driver clamping voltage -IH / IL = 20mA VGCLI Gate driver inverse clamping voltage -IH / IL = -20mA Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG 12 -0.8 V TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) Symbol Parameter Conditions 25 Min Typ Max Unit VCCUV VCC undervoltage 2.5 2.7 2.9 V VCCOK VCC voltage o.k. 2.7 2.9 3.0 V 0.85 1.35 mA 0.45 0.75 mA 37 70 µA ICC VCC supply current fosc = 25 kHz ICCSTB VCC supply current standby ICCSD VCC supply current shutdown VSUV VS undervoltage 5.5 5.9 6.2 V VCCOK VS voltage o.k. 6.1 6.4 6.7 V ENN = 1 ISSM VS supply current with maximum VS = 14V, current setting (static state) RSLP= 0K 6 ISSD VS supply current shutdown or standby 28 VIH High input voltage (SDI, SCK, CSN, BL1, BL2, SPE, ANN) VIL VS = 14V mA 50 µA 2.2 VCC + 0.3 V V Low input voltage (SDI, SCK, CSN, BL1, BL2, SPE, ANN) -0.3 0.7 V VIHYS Input voltage hysteresis (SDI, SCK, CSN, BL1, BL2, SPE, ANN) 100 300 500 mV VOH High output voltage (output SDO) -IOH = 1mA VCC – 0.6 VCC – 0.2 VCC V VOL Low output voltage (output SDO) IOL = 1mA 0 0.1 0.4 V -IISL Low input current (SDI, SCK, CSN, BL1, BL2, SPE, ANN) VI = 0 VCC = 3.3V VCC = 5.0V 2 70 µA µA µA 10 25 VENNH High input voltage threshold (input ENN) VEHYS Input voltage hysteresis (input ENN) VOSCH High input voltage threshold (input OSC) tbd 2/3 VCC tbd V VOSCL Low input voltage threshold (input OSC) tbd 1/3 VCC tbd V VVTD VT threshold voltage (referenced to VS) -130 -155 -180 mV VTRIP SRA / SRB voltage at DAC=”1111” 315 350 385 mV VSRS SRA / SRB overcurrent detection threshold 570 615 660 mV VSROFFS1 SRA / SRB comparator offset voltage (Standard device) -10 0 10 mV VSROFFS2 SRA / SRB comparator offset voltage (Selected device) -6 0 6 mV 175 264 360 RINAB INA / INB input resistance 1/2 VCC 0.1 VENNH internal ref. or 2V at INA / INB Vin 3V Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG k TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 26 AC Characteristics AC characteristics contain the spread of values guaranteed within the specified supply voltage and temperature range unless otherwise specified. Typical characteristics represent the average value of all parts. Logic supply voltage: VCC = 3.3V, Bridge supply voltage: VS = 14.0V, Ambient temperature: TA = 27°C, External MOSFET gate charge = 3.2nC Symbol Parameter fOSC Oscillator frequency using internal oscillator TBL TONMIN Conditions Min Typ Max Unit COSC = 1nF 1% 20 25 31 kHz 1.35 1.5 1.65 µs Effective Blank time BL1, BL2 = VCC Minimum PWM on-time BL1, BL2 = GND 0.7 µs Thermal Protection (1) Symbol TJOT TJOTHYS TJWT TJWTHYS Parameter Conditions Thermal shutdown Min Typ Max Unit 145 155 165 °C TJOT hysteresis Prewarning temperature TJWT hysteresis 15 135 145 15 (1) All temperatures are for A-type. The non-A-types have 5°C lower values in all fields. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG °C 155 °C °C TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 27 SPI Interface Timing tES ENN CSN t1 tCL tCH t1 t1 SCK tDU SDI bit11 tDH bit10 bit0 tD SDO tZC bit11 bit10 bit0 Propagation Times (3.0 V VCC 5.5 V, -40°C unless otherwise specified) Symbol fSCK Tj 150°C; VIH = 2.8V, VIL = 0.5V; tr, tf = 10ns; CL = 50pF, Parameter SCK frequency Conditions Min ENN = 0 DC Typ Max Unit 4 MHz t1 SCK stable before and after CSN change 50 ns tCH Width of SCK high pulse 100 ns tCL Width of SCK low pulse 100 ns tDSU SDI setup time 40 ns tDH SDI hold time 50 ns tD SDO delay time tZC CSN high to SDO high impedance tES ENN to SCK setup time tPD CSN high to LA / HA / LB / HB output polarity change delay CL = 50pF *) **) 40 100 ns 50 ns 30 ns 3 tOSC + 4 µs *) SDO is tristated whenever ENN is inactive (high) or CSN is inactive (high). **) Whenever the PHA / PHB polarity is changed, the chopper is restarted for that phase. However, the chopper does not switch on, when the SRA resp. SRB comparator threshold is exceeded upon the start of a chopper period. Using the SPI interface The SPI interface allows either cascading of multiple devices, giving a longer shift register, or working with a separate chip select signal for each device, paralleling all other lines. Even when there is only one device attached to a CPU, the CPU can communicate with it using a 16 bit transmission. In this case, the upper 4 bits are dummy bits. SPI Filter (only A-type) To prevent spikes from changing the SPI settings, SPI data words are only accepted, if their length is at least 12 bit. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) 28 Application Note: Extending the Microstep Resolution For some applications it might be desired to have a higher microstep resolution, while keeping the advantages of control via the serial interface. The following schematic shows a solution, which adds two LSBs by selectively pulling up the SRA / SRB pin by a small voltage difference. Please remark, that the lower two bits are inverted in the depicted circuit. A full scale sense voltage of 340mV is assumed. The circuit still takes advantage of completely switching off of the coils when the internal DAC bits are set to “0000”. This results in the following comparator trip voltages: Current setting Trip voltage (MSB first) 0000xx 0V 000111 5.8 mV 000110 11.5 mV 000101 17.3 mV 000100 23 mV ... 111101 334.2 mV 111100 340 mV SPI bit DAC bit SPI bit DAC bit 15 /B1 7 A2 14 /B0 6 PHA 13 /A1 5 MDB 12 /A0 4 B5 11 MDA 3 B4 10 A5 2 B3 9 A4 1 B2 SCK SCK SDI SDI TMC236 / TMC239 SDO SRA 110R 4.7nF opt. CSN /CS 47K 47K RS 47K +VCC 100K /OE C2 /MR C1 DS1D Q0 Q1 Q2 Q3 Q4 Q5 Q6 Q7 /DACA.0 /DACA.1 /DACB.0 /DACB.1 Free for second TMC239 Q7' 74HC595 Vcc = 5V C SDO Q D 1/2 74HC74 Note: Use a 74HC4094 instead of the HC595 to get rid of the HC74 and inverter Please see the FAQ document for more application information. Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG 8 A3 0 PHB TMC239 / TMC239A DATA SHEET (V2.11 / 2009-Jul-30) Documentation Revision Version Author Description V2.08 V2.09 V2.11 BD BD BD Added power supply sequencing considerations updated logo, minor additions Adapted style, added info on chopper cycle i SPI is a trademark of Motorola Copyright © 2005, TRINAMIC Motion Control GmbH & Co KG 29