TM MP2307 3A, 23V, 340KHz Synchronous Rectified Step-Down Converter The Future of Analog IC Technology TM DESCRIPTION FEATURES The MP2307 is a monolithic synchronous buck regulator. The device integrates 100mΩ MOSFETS that provide 3A of continuous load current over a wide operating input voltage of 4.75V to 23V. Current mode control provides fast transient response and cycle-by-cycle current limit. • An adjustable soft-start prevents inrush current at turn-on and in shutdown mode, the supply current drops below 1µA. This device, available in an 8-pin SOIC package, provides a very compact system solution with minimal reliance on external components. EVALUATION BOARD REFERENCE Board Number Dimensions EV2307DN-00A 2.0”X x 1.5”Y x 0.5”Z • • • • • • • • • • 3A Continuous Output Current, 4A Peak Output Current Wide 4.75V to 23V Operating Input Range Integrated 100mΩ Power MOSFET Switches Output Adjustable from 0.925V to 20V Up to 95% Efficiency Programmable Soft-Start Stable with Low ESR Ceramic Output Capacitors Fixed 340KHz Frequency Cycle-by-Cycle Over Current Protection Input Under Voltage Lockout Thermally Enhanced 8-Pin SOIC Package APPLICATIONS • • • • • Distributed Power Systems Networking Systems FPGA, DSP, ASIC Power Supplies Green Electronics/Appliances Notebook Computers “MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION C5 10nF INPUT 4.75V to 23V Efficiency vs Load Current 100 95 7 8 90 1 BS SW EN MP2307 SS GND 4 FB COMP 3 OUTPUT 3.3V 3A 5 6 C3 3.9nF EFFICIENCY (%) 2 IN VIN = 5V VIN = 12V 85 80 VIN = 23V 75 70 65 60 55 50 0.1 1.0 LOAD CURRENT (A) 10 MP2307_EC01 MP2307_TAC01 MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 1 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER ABSOLUTE MAXIMUM RATINGS (1) PACKAGE REFERENCE Supply Voltage VIN ....................... –0.3V to +26V Switch Voltage VSW ................. –1V to VIN + 0.3V Boost Voltage VBS ..........VSW – 0.3V to VSW + 6V All Other Pins................................. –0.3V to +6V Junction Temperature...............................150°C Lead Temperature ....................................260°C Storage Temperature .............–65°C to +150°C TOP VIEW BS 1 8 SS IN 2 7 EN SW 3 6 COMP GND 4 5 FB EXPOSED PAD ON BACKSIDE Recommended Operating Conditions Input Voltage VIN ............................ 4.75V to 23V Output Voltage VOUT .................... 0.925V to 20V Ambient Operating Temp .............. –40°C to +85°C MP2307_PD01_SOIC8N Thermal Resistance Part Number* Package Temperature MP2307DN SOIC8N (Exposed Pad) –40° to +85°C * (2) For Tape & Reel, add suffix –Z (eg. MP2307DN–Z) For Lead Free, add suffix –LF (eg. MP2307DN–LF–Z) (3) θJA θJC SOIC8N .................................. 50 ...... 10... °C/W Notes: 1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately 1” square of 1 oz copper. ELECTRICAL CHARACTERISTICS VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition Shutdown Supply Current Supply Current VEN = 0V VEN = 2.0V, VFB = 1.0V Feedback Voltage VFB Feedback Overvoltage Threshold Error Amplifier Voltage Gain (4) 4.75V ≤ VIN ≤ 23V 0.900 (4) High-Side Switch On-Resistance Low-Side Switch On-Resistance (4) High-Side Switch Leakage Current Upper Switch Current Limit Lower Switch Current Limit COMP to Current Sense Transconductance Oscillation Frequency Short Circuit Oscillation Frequency Maximum Duty Cycle Minimum On Time (4) EN Shutdown Threshold Voltage EN Shutdown Threshold Voltage Hysterisis GEA Max Units 0.3 1.3 3.0 1.5 µA mA 0.925 0.950 V V V/V ∆IC = ±10µA 820 µA/V VEN = 0V, VSW = 0V Minimum Duty Cycle From Drain to Source 100 100 0 5.8 0.9 mΩ mΩ µA A A RDS(ON)1 RDS(ON)2 4.0 GCS Fosc1 Fosc2 DMAX TON Typ 1.1 400 AEA Error Amplifier Transconductance MP2307 Rev. 1.7 3/14/2006 Min 10 5.2 300 VFB = 0V VFB = 1.0V VEN Rising 1.1 340 110 90 220 1.5 220 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. A/V 380 2.0 KHz KHz % ns V mV 2 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER ELECTRICAL CHARACTERISTICS (continued) VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition EN Lockout Threshold Voltage EN Lockout Hysterisis Input Under Voltage Lockout Threshold Input Under Voltage Lockout Threshold Hysteresis Soft-Start Current Soft-Start Period Thermal Shutdown (4) VIN Rising VSS = 0V CSS = 0.1µF Min Typ Max Units 2.2 2.5 210 2.7 V mV 3.80 4.05 4.40 V 210 mV 6 15 160 µA ms °C Note: 4) Guaranteed by design, not tested. MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 3 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER TYPICAL PERFORMANCE CHARACTERISTICS C1 = 2 x 10µF, C2 = 2 x 22µF, L= 10µH, CSS= 0.1µF, TA = +25°C, unless otherwise noted. Steady State Test Waveforms Steady State Test Waveforms Startup through Enable Waveforms VIN = 12V, VOUT = 3.3V, IOUT = 0A VIN = 12V, VOUT = 3.3V, IOUT = 3A VIN = 12V, VOUT = 3.3V, No Load VIN 20mV/div. VIN 200mV/div. VOUT 20mV/div. VOUT 20MV/div. VSW 10V/div. VSW V/div. IL 1A/div. VEN 5V/div. VOUT 2V/div. IL 1A/div. IL 2A/div. VSW 10V/div. 2ms/div. MP2307-TPC01 MP2307-TPC02 MP2307-TPC03 Startup Through Enable Waveforms Shutdown Through Enable Waveforms Shutdown Through Enable Waveforms VIN = 12V, VOUT = 3.3V, IOUT = 3A (Resistance Load) VIN = 12V, VOUT = 3.3V, No Load VIN = 12V, VOUT = 3.3V, IOUT = 3A (Resistance Load) VEN 5V/div. VEN 5V/div. VOUT 2V/div. VEN 5V/div. VOUT 2V/div. IL 2A/div. VSW 10V/div. IL 1A/div. VOUT 2V/div. IL 2A/div. VSW 10V/div. VSW 10V/div. 2ms/div. 2ms/div. MP2307-TP04 MP2307-TPC05 MP2307-TPC06 Load Transient Test Waveforms Short Circuit Test Waveforms Short Circuit Recovery Waveforms VIN = 12V, VOUT = 3.3V, IOUT = 1A to 2A step VIN = 12V, VOUT = 3.3V VIN = 12V, VOUT = 3.3V VOUT 200mV/div. VOUT 2V/div. VOUT 2V/div. IL 1A/div. ILOAD 1A/div. IL 2A/div. MP2307 -TPC07 MP2307 Rev. 1.7 3/14/2006 IL 2A/div. MP2307-TPC08 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. MP2307-TPC09 4 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER PIN FUNCTIONS Pin # Name 1 BS 2 IN 3 SW 4 GND 5 FB 6 COMP 7 EN 8 SS MP2307 Rev. 1.7 3/14/2006 Description High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.01µF or greater capacitor from SW to BS to power the high side switch. Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a 4.75V to 23V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. Ground (Connect the exposed pad to Pin 4). Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage divider connected to it from the output voltage. The feedback threshold is 0.925V. See Setting the Output Voltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator; low to turn it off. Attach to IN with a 100kΩ pull up resistor for automatic startup. Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND to set the soft-start period. A 0.1µF capacitor sets the soft-start period to 15ms. To disable the soft-start feature, leave SS unconnected. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 5 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER OPERATION FUNCTIONAL DESCRIPTION The MP2307 regulates input voltages from 4.75V to 23V down to an output voltage as low as 0.925V, and supplies up to 3A of load current. The MP2307 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at the COMP pin is compared to the switch current (measured internally) to control the output voltage. The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high side gate. The boost capacitor is charged from the internal 5V rail when SW is low. When the FB pin voltage exceeds 20% of the nominal regulation value of 0.925V, the over voltage comparator is tripped and the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off. + CURRENT SENSE AMPLIFIER OVP 1.1V -OSCILLATOR + FB 5 110/340KHz 0.3V RAMP 1 BS 3 SW 4 GND 5V --+ + 0.925V IN -- CLK -SS 8 + 2 + ERROR AMPLIFIER S Q R Q CURRENT COMPARATOR COMP 6 -- EN 7 2.5V + EN OK OVP 1.2V IN < 4.10V LOCKOUT COMPARATOR IN + 7V Zener 1.5V -- INTERNAL REGULATORS SHUTDOWN COMPARATOR MP2307_BD01 Figure 1—Functional Block Diagram MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 6 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER APPLICATIONS INFORMATION The inductance value can be calculated by: COMPONENT SELECTION Setting the Output Voltage The output voltage is set using a resistive voltage divider connected from the output voltage to FB. The voltage divider divides the output voltage down to the feedback voltage by the ratio: VFB = VOUT R2 R1 + R2 R1 + R2 R2 ⎞ ⎟⎟ ⎠ Where VOUT is the output voltage, VIN is the input voltage, fS is the switching frequency, and ∆IL is the peak-to-peak inductor ripple current. ILP = ILOAD + R2 can be as high as 100kΩ, but a typical value is 10kΩ. Using the typical value for R2, R1 is determined by: R1 = 10.81 × ( VOUT − 0.925 ) (kΩ) For example, for a 3.3V output voltage, R2 is 10kΩ, and R1 is 26.1kΩ. Table 1 lists recommended resistance values of R1 and R2 for standard output voltages. Table 1—Recommended Resistance Values VOUT R1 R2 1.8V 2.5V 3.3V 5V 12V 9.53kΩ 16.9kΩ 26.1kΩ 44.2kΩ 121kΩ 10kΩ 10kΩ 10kΩ 10kΩ 10kΩ Inductor The inductor is required to supply constant current to the load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will in turn result in lower output ripple voltage. However, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining inductance is to allow the peak-topeak ripple current to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. MP2307 Rev. 1.7 3/14/2006 ⎛ VOUT V × ⎜⎜1 − OUT f S × ∆I L ⎝ VIN Choose an inductor that will not saturate under the maximum inductor peak current, calculated by: Thus the output voltage is: VOUT = 0.925 × L= ⎛ VOUT V × ⎜1 − OUT 2 × f S × L ⎜⎝ VIN ⎞ ⎟⎟ ⎠ Where ILOAD is the load current. The choice of which style inductor to use mainly depends on the price vs. size requirements and any EMI constraints. Optional Schottky Diode During the transition between the high-side switch and low-side switch, the body diode of the low-side power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table 2 lists example Schottky diodes and their Manufacturers. Table 2—Diode Selection Guide Part Number Voltage/Current Rating B130 SK13 30V, 1A 30V, 1A MBRS130 30V, 1A Vendor Diodes, Inc. Diodes, Inc. International Rectifier Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors will also suffice. Choose X5R or X7R dielectrics when using ceramic capacitors. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 7 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER Since the input capacitor (C1) absorbs the input switching current, it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: I C1 = ILOAD × VOUT ⎛⎜ VOUT ⎞⎟ × 1− VIN ⎜⎝ VIN ⎟⎠ When using tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: ∆VOUT = VOUT ⎛ V × ⎜1 − OUT f S × L ⎜⎝ VIN ⎞ ⎟⎟ × R ESR ⎠ The worst-case condition occurs at VIN = 2VOUT, where IC1 = ILOAD/2. For simplification, use an input capacitor with a RMS current rating greater than half of the maximum load current. The characteristics of the output capacitor also affect the stability of the regulation system. The MP2307 can be optimized for a wide range of capacitance and ESR values. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1µF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple for low ESR capacitors can be estimated by: Compensation Components MP2307 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to govern the characteristics of the control system. ∆VIN = ILOAD V × OUT C1 × fS VIN ⎛ V × ⎜⎜1 − OUT VIN ⎝ ⎞ ⎟⎟ ⎠ The DC gain of the voltage feedback loop is given by: A VDC = R LOAD × G CS × A EA × Where C1 is the input capacitance value. Output Capacitor The output capacitor (C2) is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: ∆VOUT = VOUT ⎛ V × ⎜⎜1 − OUT fS × L ⎝ VIN ⎞ ⎞ ⎛ 1 ⎟ ⎟⎟ × ⎜ R ESR + ⎜ 8 × f S × C2 ⎟⎠ ⎠ ⎝ Where C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. When using ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance which is the main cause for the output voltage ripple. For simplification, the output voltage ripple can be estimated by: ∆VOUT = MP2307 Rev. 1.7 3/14/2006 ⎛ V × ⎜⎜1 − OUT VIN × L × C2 ⎝ VOUT 8 × fS 2 VFB VOUT Where VFB is the feedback voltage (0.925V), AVEA is the error amplifier voltage gain, GCS is the current sense transconductance and RLOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of the error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: fP1 = GEA 2π × C3 × A VEA fP2 = 1 2π × C2 × R LOAD Where GEA is transconductance. the error amplifier ⎞ ⎟⎟ ⎠ www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 8 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: f Z1 = 1 2π × C3 × R3 The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: fESR 1 = 2π × C2 × R ESR In this case, a third pole set by compensation capacitor (C6) and compensation resistor (R3) is used compensate the effect of the ESR zero on loop gain. This pole is located at: fP 3 = the the to the 1 2π × C6 × R3 The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good standard is to set the crossover frequency below one-tenth of the switching frequency. To optimize the compensation components, the following procedure can be used. 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero (fZ1) below one-forth of the crossover frequency provides sufficient phase margin. Determine C3 by the following equation: C3 > 4 2π × R3 × f C Where R3 is the compensation resistor. 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the switching frequency, or the following relationship is valid: f 1 < S 2π × C2 × R ESR 2 If this is the case, then add the second compensation capacitor (C6) to set the pole fP3 at the location of the ESR zero. Determine C6 by the equation: C6 = C2 × R ESR R3 External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5V fixed input or the power supply generates a 5V output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as IN4148 or BAT54. 5V 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine R3 by the following equation: R3 = 2π × C2 × fC VOUT 2π × C2 × 0.1 × fS VOUT × < × GEA × GCS VFB GEA × GCS VFB Where fC is the desired crossover frequency which is typically below one tenth of the switching frequency. BS 10nF MP2307 SW MP2307_F02 Figure 2—External Bootstrap Diode This diode is also recommended for high duty cycle operation (when VOUT >65%) and high VIN output voltage (VOUT>12V) applications. MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 9 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER TYPICAL APPLICATION CIRCUIT C5 10nF INPUT 4.75V to 23V 2 7 8 1 IN BS SW EN MP2307 SS GND FB COMP 4 5 6 C6 (optional) OUTPUT 3.3V 3A 3 C3 3.9nF D1 B130 (optional) MP2307_F03 Figure 3—MP2307 with 3.3V Output, 22uF/6.3V Ceramic Output Capacitor MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 10 TM MP2307 – 3A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER PACKAGE INFORMATION SOIC8N (EXPOSED PAD) 0.229(5.820) 0.244(6.200) PIN 1 IDENT. NOTE 4 0.150(3.810) 0.157(4.000) 0.0075(0.191) 0.0098(0.249) SEE DETAIL "A" NOTE 2 0.011(0.280) x 45o 0.020(0.508) 0.013(0.330) 0.020(0.508) 0.050(1.270)BSC 0o-8o NOTE 3 0.189(4.800) 0.197(5.000) 0.053(1.350) 0.068(1.730) 0.016(0.410) 0.050(1.270) .050 0.049(1.250) 0.060(1.524) DETAIL "A" .028 0.200 (5.07 mm) SEATING PLANE 0.001(0.030) 0.004(0.101) 0.140 (3.55mm) 0.060 Land Pattern NOTE: 1) Control dimension is in inches. Dimension in bracket is millimeters. 2) Exposed Pad Option (N-Package) ; 2.31mm -2.79mm x 2.79mm - 3.81mm. Recommend Solder Board Area: 2.80mm x 3.82mm = 10.7mm 2 (16.6 mil2) 3) The length of the package does not include mold flash. Mold flash shall not exceed 0.006in. (0.15mm) per side. With the mold flash included, over-all length of the package is 0.2087in. (5.3mm) max. 4) The width of the package does not include mold flash. Mold flash shall not exceed 0.10in. (0.25mm) per side. With the mold flash included, over-all width of the package is 0.177in. (4.5mm) max. NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP2307 Rev. 1.7 3/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 11